TPA005D02 [TI]
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER; 2 -W立体声D类音频功率放大器
| 型号： | TPA005D02 |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER |
| 文件： | 总25页 (文件大小：381K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
DCA PACKAGE
(TOP VIEW)
NOT RECOMMENDED FOR NEW DESIGNS
Choose TPA2000D2 For Upgrade
1
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
32
31
30
29
28
27
26
25
SHUTDOWN
MUTE
COSC
AGND
AGND
RINN
Extremely Efficient Class-D Stereo
Operation
2
3
AGND
LINN
LINP
LCOMP
AGND
Drives L and R Channels
2-W BTL Output into 4 Ω
5-W Peak Music Power
Fully Specified for 5-V Operation
Low Quiescent Current
Shutdown Control
4
5
RINP
6
RCOMP
FAULT0
FAULT1
7
8
V
LPV
DD
DD
9
RPV
DD
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
LOUTP
LOUTP
PGND
PGND
LOUTN
LOUTN
ROUTP
ROUTP
PGND
PGND
ROUTN
ROUTN
Thermally-Enhanced PowerPAD Surface-
Mount Packaging
Thermal and Under-Voltage Protection
description
LPV
RPV
DD
DD
NC
NC
NC
PV
DD
NC
NC
V2P5
LSBIAS
PGND
CP4
The TPA005D02 is a monolithic power IC stereo
audio amplifier. It operates in extremely efficient
Class-Doperation, usingthehighswitchingspeed
of power DMOS transistors. These transistors
replicate the analog signal through high-frequen-
cy switching of the output stage. This allows the
TPA005D02 to be configured as a bridge-tied load
(BTL) amplifier.
AGND
PV
DD
VCP
CP3
CP2
CP1
NC – No internal connection
When configured as a BTL amplifier, the
TPA005D02 is capable of delivering up to 2 W of
continuous average power into a 4-Ω load at 0.5%
THD+Nfroma5-Vpowersupplyinthehighfidelity
range (20 Hz to 20 kHz).
A BTL configuration eliminates the need for external coupling capacitors on the output. A chip-level shutdown
control limits total supply current to 400 µA. This makes the device ideal for battery-powered applications.
Protection circuitry increases device reliability: thermal and under-voltage shutdown, with two status feedback
terminals for use when any error condition is encountered.
The high switching frequency of the TPA005D02 allows the output filter to consist of three small capacitors and
two small inductors per channel. The high switching frequency also allows for good THD+N performance.
The TPA005D02 is offered in the thermally enhanced 48-pin PowerPAD TSSOP surface-mount package
(designator DCA).
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PowerPAD is a trademark of Texas Instruments Incorporated.
Copyright 2000, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
1
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
LPV
DD
VCP LSBIAS
LPV
DD
LPV
DD
1.5 V
10 kΩ
THERMAL
DETECT
GATE
DRIVE
10 kΩ
SHUTDOWN
MUTE
CONTROL and
STARTUP
LOGIC
+
_
LINP
LINN
LPV
DD
VCP LSBIAS
+
_
LCOMP
PV
DD
GATE
DRIVE
V
DD
V
DD
HPV
CC
BIAS
GENERATOR
V2P5
RPV
DD
VCP LSBIAS
RAMP
COSC
GENERATOR
VCP-UVLO
DETECT
GATE
DRIVE
_
+
RCOMP
PV
DD
+
_
RINP
RINN
RPV
DD
TRIPLER
CHARGE PUMP
VCP LSBIAS
10 kΩ
10 kΩ
1.5 V
GATE
DRIVE
RPV
DD
RPV
DD
AGND
PGND
NOTE A: LPV , RPV , V , and PV
DD DD DD DD
are externally connected. AGND and PGND are externally connected.
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
Terminal Functions
TERMINAL
NAME
AGND
DESCRIPTION
NO.
3, 7, 20,
46, 47
Analog ground for analog sections
COSC
CP1
48
25
Capacitor I/O for ramp generator. Adjust the capacitor size to change the switching frequency.
First diode node for charge pump
CP2
24
First inverter switching node for charge pump
CP3
23
Second diode node for charge pump
CP4
26
Second inverter switching node for charge pump
FAULT0
FAULT1
LCOMP
LINN
42
Logic level fault0 output signal. Lower order bit of the two fault signals with open drain output.
Logic level fault1 output signal. Higher order bit of the two fault signals with open drain output.
Compensation capacitor terminal for left-channel Class-D amplifier
Class-D left-channel negative input
41
6
4
LINP
5
Class-D left-channel positive input
LOUTN
LOUTP
14, 15
10, 11
9, 16
28
Class-D amplifier left-channel negative output of H-bridge
Class-D amplifier left-channel positive output of H-bridge
Class-D amplifier left-channel power supply
LPV
DD
LSBIAS
Level-shifter power supply, to be tied to VCP
2
MUTE
Active-low logic-level mute input signal. When MUTE is held low, the selected amplifier is muted. When MUTE
is held high, the device operates normally. When the Class-D amplifier is muted, the low-side output transistors
are turned on, shorting the load to ground.
NC
17, 18, 19, No internal connection
30, 31
PGND
PGND
PGND
12, 13
27
Power ground for left-channel H–bridge only
Power ground for charge pump only
36, 37
21, 32
43
Power ground for right-channel H-bridge only
PV
DD
V
DD
supply for charge-pump and internal logic circuitry
RCOMP
RINN
Compensation capacitor terminal for right-channel Class-D amplifier
Class-D right-channel negative input
45
RINP
44
Class-D right-channel positive input
RPV
DD
33, 40
34, 35
38, 39
1
Class-D amplifier right-channel power supply
ROUTN
Class-D amplifier right-channel negative output of H-bridge
Class-D amplifier right-channel positive output of H-bridge
ROUTP
SHUTDOWN
Active-low logic-level shutdown input signal. When SHUTDOWN is held low, the device goes into shutdown
mode. When SHUTDOWN is held at logic high, the device operates normally.
V2P5
VCP
29
22
8
2.5-V internal reference bypass
Storage capacitor terminal for charge pump
V
DD
V
bias supply for analog circuitry. This terminal needs to be well filtered to prevent degrading the device
DD
performance.
3
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
Class-D amplifier faults
Table 1. Amplifier Fault Table
†
†
FAULT 0
FAULT 1
DESCRIPTION
1
1
1
0
No fault—The device is operating normally.
Charge pump under-voltage lock-out (VCP-UV) fault—All low-side transistors are turned on, shorting the load to
ground. Once the charge pump voltage is restored, normal operation resumes, but FAULT1 is still active. FAULT1 is
cleared by cycling MUTE, SHUTDOWN, or the power supply.
0
0
Thermal fault—All the low-side transistors are turned on, shorting the load to ground. Once the junction temperature
drops 20°C, normal operation resumes. But the FAULTx terminals are still set and are cleared by cycling MUTE,
SHUTDOWN, or the power supply.
†
These logic levels assume a pull up to PV
DD
from the open-drain outputs.
AVAILABLE OPTIONS
PACKAGED DEVICES
†
T
A
TSSOP
(DCA)
–40°C to 125°C
TPA005D02DCA
†
The DCA package is available in left-ended tape and reel. To order
a taped and reeled part, add the suffix R to the part number (e.g.,
TPA005D02DCAR).
absolute maximum ratings over operating free-air temperature range, T = 25°C (unless otherwise
C
‡
noted)
Supply voltage, V
(PV , LPV , RPV , V ) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5.5 V
DD DD DD DD
DD
Bias voltage (LSBIAS) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12 V to 20 V
Input voltage, V (SHUTDOWN, MUTE, MODE) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 5.8 V
I
Output current, I (FAULT0, FAULT1), open drain terminated . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 mA
O
Charge pump voltage, V
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . PV
+ 20 V
CP
DD
Continuous H-bridge output current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 A
Pulsed H-Bridge output current, each output, I
(see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 A
max
§
Continuous total power dissipation, T = 25°C . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4.5 W
C
Operating virtual junction temperature range, T . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 150°C
J
Operating case temperature range, T
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 125°C
C
Storage temperature range, T
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C
stg
Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C
†
§
Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Thermal shutdown activates when T = 125°C.
J
NOTE 1: Pulse duration = 10 ms, duty cycle
2%
DISSIPATION RATING TABLE
DERATING FACTOR = 70°C
¶
T
≤ 25°C
T
A
T
A
= 85°C
T = 125°C
A
A
PACKAGE
POWER RATING
ABOVE T = 25°C
POWER RATING POWER RATING POWER RATING
A
DCA
5.6 W
44.8 mW/°C
3.6 W 2.9 W 1.1 W
¶
Please see the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report (literature number
SLMA002), for more information on the PowerPAD package. The thermal data was measured on a PCB layout based on the
information in the section entitled Texas Instruments Recommended Board for PowerPAD on page 33 of the before mentioned
document.
4
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
recommended operating conditions
MIN NOM
4.5
MAX
UNIT
Supply voltage, PV , LPV , RPV , V
DD DD
5.5
V
V
V
DD
DD
High-level input voltage, V
4.25
IH
Low-level input voltage, V
0.75
1
IL
Audio inputs, LINN, LINP, RINN, RINP, HPLIN, HPRIN, differential input voltage
PWM frequency
V
RMS
kHZ
100
500
electrical characteristics, V
(resistive load) (unless otherwise noted)
= PV
= LPV
= RPV
= 5 V, R = 4 Ω, T = 25°C, See Figure 1
DD
DD
DD
DD
L
C
PARAMETER
TEST CONDITIONS
= LPV = RPV = 4.9 V to 5.1 V
MIN
TYP
40
MAX
UNIT
dB
PSRR
Power supply rejection ratio
Supply current
V
= PV
DD DD
DD
DD
I
I
I
I
I
No load or output filter
MUTE = 0 V
25
40
15
mA
mA
µA
DD
Supply current, mute mode
Supply current, shutdown mode
High-level input current
Low-level input current
10
DD(MUTE)
SHUTDOWN = 0 V
400
2000
10
DD(SD)
V
= 5.3 V
µA
IH
IL
IH
IL
V
= –0.3 V
–10
µA
Total static drain-to-source
on-state resistance
(low-side plus high-side FETs)
r
r
I
D
= 0.5 A
620
750
mΩ
DS(on)
DS(on)
Matching
95%
99.5%
operating characteristics, V
(unless otherwise noted)
= PV
= LPV
= RPV
= 5 V, R = 4 Ω, T = 25°C, See Figure 1
DD
DD
DD
DD
L
C
PARAMETER
RMS output power, THD = 0.5%, per channel
TEST CONDITIONS
MIN
TYP
2
MAX
UNIT
P
O
W
THD+N Total harmonic distortion plus noise
Efficiency
P
= 1 W, f = 1 kHz
0.2%
80%
24
O
R
= 8 Ω
L
A
Gain
dB
V
Left/right channel gain matching
Noise floor
95%
60
dB
dB
Dynamic range
Crosstalk
70
f = 1 kHz
55
dB
Frequency response bandwidth, post output filter, –3 dB
Maximum output power bandwidth
20
20,000
20
Hz
B
OM
kHz
thermal resistance
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
R
R
Thermal resistance, junction-to-pad
Thermal resistance, junction-to-pad
10
°C/W
θJP
θJA
†
22.3
°C/W
†
Please see the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report (literature number SLMA002), for
more information on the PowerPAD package. The thermal data was measured on a PCB layout based on the information in the section entitled
Texas Instruments Recommended Board for PowerPAD on page 33 of the before mentioned document.
5
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
PARAMETER MEASUREMENT INFORMATION
42
41
FAULT0
FAULT1
28
1
LSBIAS
VCP
SHUTDOWN
PV
15 µH
DD
14,15
2
LOUTN
PV
MUTE
DD
0.22 µF
0.22 µF
1 µF
4 Ω
9,16
LPV
DD
5 V
10,11
29
LOUTP
V2P5
1 µF
15 µH
5
4
LINP
LINN
Balanced
Differential
Input Signal
1 µF
6
LCOMP
RCOMP
1 µF
43
470 pF
470 pF
8
V
DD
48
COSC
470 pF
25
CP1
47 nF
47 nF
1 µF
24
23
44
CP2
CP3
RINP
RINN
Balanced
Differential
Input Signal
45
1 µF
33,40
26
22
CP4
VCP
RPV
DD
5 V
2, 3, 7,20,46,47
AGND (see Note A)
PGND (see Note A)
12,13,27,36,37
2.2 µF
21, 32
5 V
PV
DD
15 µH
34,35
38,39
ROUTN
ROUTP
0.22 µF
0.22 µF
1 µF
4 Ω
15 µH
Figure 1. 5-V, 4-Ω Test Circuit
6
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
TYPICAL CHARACTERISTICS
Table of Graphs
FIGURE
vs Switching frequency
2
3
I
Supply current
DD
vs Free-air temperature
vs Frequency
4, 5
6, 7
8
THD+N
Total harmonic distortion plus noise
vs Output power
vs Frequency
Voltage amplification and phase shift
Crosstalk
Efficiency
vs Frequency
9
vs Output power
10
SUPPLY CURRENT
SUPPLY CURRENT
vs
vs
FREE–AIR TEMPERATURE
SWITCHING FREQUENCY
50
100
Open Load
Open Load
40
30
80
60
With Output Filter
With Output Filter
20
40
Without Output Filter
10
0
20
0
Without Output Filter
400
120
125
–40
0
40
80
500
0
100
200
300
T
A
– Free–Air Temperature – °C
f – Switching Frequency – Hz
Figure 2
Figure 3
7
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
TYPICAL CHARACTERISTICS
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
1
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
1
P = 500 mW
O
R
L
= 8 Ω
R
L
= 4 Ω
0.5
0.5
P
O
= 100 mW
P
= 2W
= 1W
O
0.2
0.1
0.2
0.1
P
O
= 100 mW
P
O
= 1W
P
O
0.05
0.05
0.02
0.01
0.02
0.01
20
50 100 200
500 1k 2k
5k 10k 20k
20
50 100 200
500 1k 2k
5k 10k 20k
f – Frequency – Hz
f – Frequency – Hz
Figure 4
Figure 5
TOTAL HARMONIC DISTORTION PLUS NOISE
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
vs
OUTPUT POWER
OUTPUT POWER
10
5
10
5
R
L
= 8 Ω
R
L
= 4 Ω
2
2
1
1
0.5
0.5
f = 1 kHz
f = 20 Hz
f = 1 kHz
0.2
0.1
0.2
0.1
f = 20 kHz
f = 20 Hz
f = 20 kHz
0.05
0.05
f = 20 kHz
f = 20 Hz
0.02
0.01
0.02
0.01
0.01 0.02 0.05 0.1 0.2
0.5
1
2
5
10
10m 20m 50m 100m 200m 500m 1
2
5
10
P
O
– Output Power – W
P
O
– Output Power – W
Figure 6
Figure 7
8
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
TYPICAL CHARACTERISTICS
GAIN AND PHASE
vs
FREQUENCY
45°
40°
35°
30°
25°
20°
30
28
26
24
22
20
18
16
14
12
P
R
= 2W
= 4Ω
o
L
Voltage Amplification
15°
10°
5°
0°
–5°
–10°
–15°
–20°
–25°
–30°
–35°
–40°
–45°
Phase Shift
10
8
6
4
2
0
10 20 50 100 200 500 1k 2k 5k 10k 20k 50k 100k
f – Frequency – Hz
Figure 8
CROSSTALK
EFFICIENCY
vs
vs
FREQUENCY
OUTPUT POWER
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
90
P
R
= 2W
= 4Ω
O
L
R
= 8Ω
L
80
70
R
= 4Ω
L
Left-to-Right
60
–100
–110
Right-to-Left
–120
–130
–140
–150
50
40
1.6
2.0
10k
20k
0
0.4
0.8
1.2
20
50 100 200
500 1k 2k
5k
P
O
– Output Power – W
f – Frequency – Hz
Figure 9
Figure 10
9
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
THERMAL INFORMATION
The thermally enhanced DCA package is based on the 56-pin TSSOP, but includes a thermal pad (see Figure 11)
to provide an effective thermal contact between the IC and the PWB.
Traditionally, surface mount and power have been mutually exclusive terms. A variety of scaled-down TO-220-type
packages have leads formed as gull wings to make them applicable for surface-mount applications. These packages,
however, have only two shortcomings: they do not address the very low profile requirements (<2 mm) of many of
today’s advanced systems, and they do not offer a terminal-count high enough to accommodate increasing
integration. Ontheotherhand, traditionallow-powersurface-mountpackagesrequirepower-dissipationderatingthat
severely limits the usable range of many high-performance analog circuits.
The PowerPAD package (thermally enhanced TSSOP) combines fine-pitch surface-mount technology with thermal
performance comparable to much larger power packages.
The PowerPAD package is designed to optimize the heat transfer to the PWB. Because of the very small size and
limited mass of a TSSOP package, thermal enhancement is achieved by improving the thermal conduction paths that
remove heat from the component. The thermal pad is formed using a patented lead-frame design and manufacturing
technique to provide a direct connection to the heat-generating IC. When this pad is soldered or otherwise thermally
coupled to an external heat dissipator, high power dissipation in the ultra-thin, fine-pitch, surface-mount package can
be reliably achieved.
DIE
Side View (a)
Thermal
Pad
DIE
End View (b)
Bottom View (c)
Figure 11. Views of Thermally Enhanced DCA Package
selection of components
Figure 12 is a schematic diagram of a typical notebook computer application circuit.
10
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
42
41
FAULT0
FAULT1
28
1
LSBIAS
VCP
SHUTDOWN
PV
15 µH
DD
14,15
2
LOUTN
PV
MUTE
DD
0.22 µF
0.22 µF
1 µF
4 Ω
9,16
LPV
DD
5 V
10,11
29
LOUTP
V2P5
1 µF
15 µH
5
4
LINP
LINN
Balanced
Differential
Input Signal
1 µF
6
LCOMP
RCOMP
1 µF
43
470 pF
470 pF
8
V
DD
48
COSC
470 pF
25
CP1
47 nF
47 nF
1 µF
24
23
44
CP2
CP3
RINP
RINN
Balanced
Differential
Input Signal
45
1 µF
33,40
26
22
CP4
VCP
RPV
DD
5 V
2, 3, 7,20,46,47
AGND (see Note A)
PGND (see Note A)
12,13,27,36,37
2.2 µF
21, 32
5 V
PV
DD
15 µH
34,35
38,39
ROUTN
ROUTP
0.22 µF
0.22 µF
1 µF
4 Ω
15 µH
NOTE A: A 0.1µFceramiccapacitorshouldbeplacedascloseaspossibletotheIC. Forfilteringlower-frequencynoisesignals, alargeraluminum
electrolytic capacitor of 10 µF or greater should be placed near the audio power amplifier.
Figure 12. TPA005D02 Typical Configuration Application Circuit
11
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
input capacitor, C
I
In the typical application an input capacitor, C , is required to allow the amplifier to bias the input signal to the
I
proper dc level for optimum operation. In this case, C and R , the TPA005D002’s input resistance forms a
I
IN
high-pass filter with the corner frequency determined in equation 8.
–3 dB
1
2 R
f
(8)
c(highpass)
C
IN I
R
is nominally 10 kΩ
IN
f
c
The value of C is important to consider as it directly affects the bass (low frequency) performance of the circuit.
I
Consider the example where the specification calls for a flat bass response down to 40 Hz. Equation 8 is
reconfigured as equation 9.
1
C
(9)
I
2 R
f
c
IN
In this example, C is 0.40 µF so one would likely choose a value in the range of 0.47 µF to 1 µF. A low-leakage
I
tantalum or ceramic capacitor is the best choice for the input capacitors. When polarized capacitors are used,
the positive side of the capacitor should face the amplifier input as the dc level there is held at 1.5 V, which is
likely higher than the source dc level. Please note that it is important to confirm the capacitor polarity in the
application.
differential input
The TPA005D02 has differential inputs to minimize distortion at the input to the IC. Since these inputs nominally
sit at 1.5 V, dc-blocking capacitors are required on each of the four input terminals. If the signal source is
single-ended, optimal performance is achieved by treating the signal ground as a signal. In other words,
reference the signal ground at the signal source, and run a trace to the dc-blocking capacitor which should be
located physically close to the TPA005D02. If this is not feasible, it is still necessary to locally ground the unused
input terminal through a dc-blocking capacitor.
power supply decoupling, C
S
The TPA005D02 is a high-performance Class-D CMOS audio amplifier that requires adequate power supply
decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling
also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling
is achieved by using two capacitors of different types that target different types of noise on the power supply
leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-
resistance (ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device’s various V
leads works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF
DD
or greater placed near the audio power amplifier is recommended.
The TPA005D02 has several different power supply terminals. This was done to isolate the noise resulting from
high-current switching from the sensitive analog circuitry inside the IC.
12
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
mute and shutdown modes
The TPA005D02 employs both a mute and a shutdown mode of operation designed to reduce supply current,
, to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN
I
DD
input terminal should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN
low causes the outputs to mute and the amplifier to enter a low-current state, I = 400 µA. Mute mode alone
DD
reduces I
to 10 mA.
DD
Table 2. Shutdown and Mute Mode Functions
†
OUTPUT
MUTE OUT
Low
AMPLIFIER STATE
INPUT OUTPUT
INPUTS
SE/BTL
Low
X
MUTE IN
Low
HP/LINE
SHUTDOWN
Low
X
Low
High
—
L/R Line
X
BTL
Mute
Mute
BTL
SE
—
—
X
X
High
Low
High
X
Low
High
High
Low
Low
Low
Low
L/R HP
L/R Line
Low
Low
High
High
Low
Low
Low
L/R HP
SE
†
Inputs should never be left unconnected.
X = do not care
using low-ESR capacitors
Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal)
capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this
resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this
resistance the more the real capacitor behaves like an ideal capacitor.
output filter components
The output inductors are key elements in the performance of the class D audio amplifier system. It is important
that these inductors have a high enough current rating and a relatively constant inductance over frequency and
temperature. The current rating should be higher than the expected maximum current to avoid magnetically
saturating the inductor. When saturation occurs, the inductor loses its functionality and looks like a short circuit
to the PWM signal, which increases the harmonic distortion considerably.
A shielded inductor may be required if the class D amplifier is placed in an EMI sensitive system; however, the
switching frequency is low for EMI considerations and should not be an issue in most systems. The DC series
resistance of the inductor should be low to minimize losses due to power dissipation in the inductor, which
reduces the efficiency of the circuit.
Capacitors are important in attenuating the switching frequency and high frequency noise, and in supplying
some of the current to the load. It is best to use capacitors with low equivalent-series-resistance (ESR). A low
ESR means that less power is dissipated in the capacitor as it shunts the high-frequency signals. Placing these
capacitors in parallel also parallels their ESR, effectively reducing the overall ESR value. The voltage rating is
also important, and, as a rule of thumb, should be 2 to 3 times the maximum rms voltage expected to allow for
high peak voltages and transient spikes. These output filter capacitors should be stable over temperature since
large currents flow through them.
13
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
efficiency of class D vs linear operation
Amplifier efficiency is defined as the ratio of output power delivered to the load to power drawn from the supply.
In the efficiency equation below, P is power across the load and P
is the supply power.
L
SUP
P
L
Efficiency
P
SUP
A high-efficiency amplifier has a number of advantages over one with lower efficiency. One of these advantages
is a lower power requirement for a given output, which translates into less waste heat that must be removed
from the device, smaller power supply required, and increased battery life.
Audio power amplifier systems have traditionally used linear amplifiers, which are well known for being
inefficient. Class D amplifiers were developed as a means to increase the efficiency of audio power amplifier
systems.
A linear amplifier is designed to act as a variable resistor network between the power supply and the load. The
transistors operate in their linear region and voltage that is dropped across the transistors (in their role as
variable resistors) is lost as heat, particularly in the output transistors.
The output transistors of a class D amplifier switch from full OFF to full ON (saturated) and then back again,
spending very little time in the linear region in between. As a result, very little power is lost to heat because the
transistors are not operated in their linear region. If the transistors have a low ON resistance, little voltage is
dropped across them, further reducing losses. The ideal class D amplifier is 100% efficient, which assumes that
both the ON resistance (R
) and the switching times of the output transistors are zero.
DS(ON)
the ideal class D amplifier
To illustrate how the output transistors of a class D amplifier operate, a half-bridge application is examined first
(Figure 13).
V
DD
M1
I
L
I
OUT
V
A
+
L
V
OUT
R
C
L
M2
C
L
–
Figure 13. Half-Bridge Class D Output Stage
Figures 14 and 15 show the currents and voltages of the half-bridge circuit. When transistor M1 is on and M2
is off, the inductor current is approximately equal to the supply current. When M2 switches on and M1 switches
off, the supply current drops to zero, but the inductor keeps the inductor current from dropping. The additional
inductor current is flowing through M2 from ground. This means that V (the voltage at the drain of M2, as shown
A
in Figure 13) transitions between the supply voltage and slightly below ground. The inductor and capacitor form
a low-pass filter, which makes the output current equal to the average of the inductor current. The low pass filter
averages V , which makes V
equal to the supply voltage multiplied by the duty cycle.
A
OUT
14
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
the ideal class D amplifier (continued)
Control logic is used to adjust the output power, and both transistors are never on at the same time. If the output
voltage is rising, M1 is on for a longer period of time than M2.
Inductor Current
Output Current
Supply Current
0
M1 on M1 off M1 on
M2 off M2 on M2 off
Time
Figure 14. Class D Currents
V
DD
V
A
V
OUT
0
M1 on M1 off M1 on
M2 off M2 on M2 off
Time
Figure 15. Class D Voltages
15
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
the ideal class D amplifier (continued)
Giventheseplots, theefficiencyoftheclassDdevicecanbecalculatedandcomparedtoanideallinearamplifier
device. In the derivation below, a sine wave of peak voltage (V ) is the output from an ideal class D and linear
P
amplifier and the efficiency is calculated.
CLASS D
LINEAR
V
V
P
P
V
V
P
L(rms)
L(rms)
V
2
2
2
2
V
I
V
L(rms)
L(rms)
L(rms)
P
Average I
DD
L
V
R
L
2 R
L
DD
V
2
P
P
P
V
I
Average I
L
L
L
DD
R
L
V
V
DD
R
P
2
V
Average I
P
V
Average I
SUP
DD
DD
SUP
DD
DD
L
V
I
V
P
L
DD
L(rms)
L(rms)
P
Efficiency
SUP
V
P
DD
SUP
V 2
P
2R
P
L
L
Efficiency
Efficiency
Efficiency
Efficiency
V
DD
P
V
SUP
2
P
R
L
V
P
1
4
V
DD
In the ideal efficiency equations, assume that V = V , which is the maximum sine wave magnitude without
P
DD
clipping. Then, the highest efficiency that a linear amplifier can have without clipping is 78.5%. A class D
amplifier, however, can ideally have an efficiency of 100% at all power levels.
The derivation above applies to an H-bridge as well as a half-bridge. An H-bridge requires approximately twice
the supply current but only requires half the supply voltage to achieve the same output power—factors that
cancel in the efficiency calculation. The H-bridge circuit is shown in Figure 16.
V
DD
V
DD
M1
M4
I
L
I
OUT
V
OUT
+
–
V
A
L
L
R
L
C
C
L
L
M3
M2
Figure 16. H-Bridge Class D Output Stage
16
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
losses in a real-world class D amplifier
Losses make class D amplifiers nonideal, and reduce the efficiency below 100%. These losses are due to the
output transistors having a nonzero R , and rise and fall times that are greater than zero.
DS(on)
The loss due to a nonzero R
nonswitching times, when the transistor is ON (saturated). Any R
is called conduction loss, and is the power lost in the output transistors at
DS(on)
above 0 Ω causes conduction loss.
DS(on)
Figure 17 shows an H-bridge output circuit simplified for conduction loss analysis and can be used to determine
new efficiencies with conduction losses included.
V
DD
= 5 V
R
0.31 Ω
5 MΩ
5 MΩ
R
DS(off)
DS(on)
R
L
4 Ω
R
0.31 Ω
R
DS(on)
DS(off)
Figure 17. Output Transistor Simplification for Conduction Loss Calculation
The power supplied, P , is determined to be the power output to the load plus the power lost in the transistors,
SUP
assuming that there are always two transistors on.
P
L
Efficiency
P
SUP
2
I R
L
Efficiency
2
2
I
2R
I R
DS(on)
L
R
L
Efficiency
2R
R
DS(on)
L
Efficiency
Efficiency
95% at all output levels R
87% at all output levels R
0.1, R
4
DS(on)
DS(on)
L
0.31, R
4
L
17
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
losses in a real-world class D amplifier (continued)
Losses due to rise and fall times are called switching losses. A plot of the output, showing switching losses, is
shown in Figure 18.
1
f
SW
t
t
=
+
t
SW
SWon
SWoff
Figure 18. Output Switching Losses
Rise and fall times are greater than zero for several reasons. One is that the output transistors cannot switch
instantaneously because (assuming a MOSFET) the channel from drain to source requires a specific period
of time to form. Another is that transistor gate-source capacitance and parasitic resistance in traces form RC
time constants that also increase rise and fall times.
Switching losses are constant at all output power levels, which means that switching losses can be ignored at
high power levels in most cases. At low power levels, however, switching losses must be taken into account
when calculating efficiency. Switching losses are dominated by conduction losses at the high output powers,
but should be considered at low powers. The switching losses are automatically taken into account if you
consider the quiescent current with the output filter and load.
class D effect on power supply
Efficiency calculations are an important factor for proper power supply design in amplifier systems. Table 2
shows Class D efficiency at a range of output power levels (per channel) with a 1-kHz sine wave input. The
maximum power supply draw from a stereo 1-W per channel audio system with 8-Ω loads and a 5-V supply is
almost 2.7 W. A similar linear amplifier such as the TPA005D02 has a maximum draw of 3.25 W under the same
circumstances.
Table 3. Efficiency vs Output Power in 5-V 8-Ω H-Bridge Systems
Output Power (W)
Efficiency (%)
Peak Voltage (V)
Internal Dissipation (W)
0.25
0.5
63.4
73
2
0.145
0.183
0.222
0.314
0.3
2.83
3.46
4
0.75
1
77.1
79.3
80.6
†
4.47
1.25
†
High peak voltages cause the THD to increase
18
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
class D effect on power supply (continued)
There is a minor power supply savings with a class D amplifier versus a linear amplifier when amplifying sine
waves. The difference is much larger when the amplifier is used strictly for music. This is because music has
much lower RMS output power levels, given the same peak output power (Figure 19); and although linear
devices are relatively efficient at high RMS output levels, they are very inefficient at mid-to-low RMS power
levels. The standard method of comparing the peak power to RMS power for a given signal is crest factor, whose
equation is shown below. The lower RMS power for a set peak power results in a higher crest factor
PPK
Prms
Crest Factor
10 log
P
PK
P
RMS
Time
Figure 19. Audio Signal Showing Peak and RMS Power
Figure20isacomparisonofa5-VclassDamplifiertoasimilarlinearamplifierplayingmusicthathasa13.76-dB
crest factor. From the plot, the power supply draw from a stereo amplifier that is playing music with a 13.76 dB
crest factor is 1.02 W, while a class D amplifier draws 420 mW under the same conditions. This means that just
under 2.5 times the power supply is required for a linear amplifier over a class D amplifier.
POWER SUPPLIED
vs
PEAK OUTPUT VOLTAGE AND PEAK OUTPUT POWER
600
500
400
TPA0202
300
TPA005D02
200
100
0
3.5
Peak Output Voltage (V)
Peak Output Power (W)
1
1.5
2
1
2.5
3
4
4
4.5
3.06
0.25
0.56
1.56
2.25
5.06
Figure 20. Audio Signal Showing Peak and RMS Power (with Music Applied)
19
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
class D effect on battery life
Battery operations for class D amplifiers versus linear amplifiers have similar power supply savings results. The
essential contributing factor to longer battery life is lower RMS supply current. Figure 21 compares the
TPA005D02 supply current to the supply current of the TPA0202, a 2-W linear device, while playing music at
different peak voltage levels.
SUPPLY CURRENTS
vs
PEAK OUTPUT VOLTAGE AND PEAK OUTPUT POWER
400
350
300
250
TPA0202
200
150
100
TPA005D02
50
0
3.5
3.06
Peak Output Voltage (V)
Peak Output Power (W)
1
1.5
0.56
2
1
2.5
1.56
3
2.25
4
4
0.25
Figure 21. Supply Current vs Peak Output Voltage of TPA005D02 vs TPA0202 With Music Input
Thisplotshowsthatalinearamplifierhasapproximatelythreetimesmorecurrentdrawatnormallisteninglevels
than a class D amplifier. Thus, a class D amplifier has approximately three times longer battery life at normal
listening levels. If there is other circuitry in the system drawing supply current, that must also be taken into
account when estimating battery life savings.
20
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
crest factor and thermal considerations
A typical music CD requires 12 dB to 15 dB of dynamic headroom to pass the loudest portions without distortion
as compared with the average power output. From the TPA005D02 data sheet, one can see that when the
TPA005D02 is operating from a 5-V supply into a 4-Ω speaker that 4 W peaks are available. Converting Watts
to dB:
P
W
4
1
P
10Log
10Log
6 dB
(17)
dB
P
ref
Subtracting the crest factor restriction to obtain the average listening level without distortion yields:
( )
12 dB 15 dB crest factor
6.0 dB 18 dB
6.0 dB 15 dB
6.0 dB 12 dB
6.0 dB 9 dB
6.0 dB 6 dB
6.0 dB 3 dB
(
)
)
9 dB 15 dB crest factor
(
6 dB 12 dB crest factor
(
)
)
3 dB 9 dB crest factor
(
0 dB 6 dB crest factor
(
)
3 dB 3 dB crest factor
Converting dB back into watts:
PdB 10
P
10
P
W
ref
(18)
63 mW (18 dB crest factor)
125 mW (15 dB crest factor)
250 mW (12 dB crest factor)
500 mW (9 dB crest factor)
1000 mW (6 dB crest factor)
2000 mW (3 dB crest factor)
This is valuable information to consider when attempting to estimate the heat dissipation requirements for the
amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3 dB crest
factor, against 12 dB and 15 dB applications drastically affects maximum ambient temperature ratings for the
system. Using the power dissipation curves for a 5-V, 4-Ω system, the internal dissipation in the TPA005D02
and maximum ambient temperatures is shown in Table 4.
21
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
APPLICATION INFORMATION
crest factor and thermal considerations (continued)
Table 4. TPA005D02 Power Rating, 5-V, 4-Ω, Stereo
PEAK OUTPUT POWER
(W)
POWER DISSIPATION
(W/Channel)
MAXIMUM AMBIENT
TEMPERATURE
AVERAGE OUTPUT POWER
4
4
4
4
4
4
2 W (3 dB)
0.56
0.30
0.23
0.20
0.14
0.09
125°C
136°C
139°C
141°C
143°C
146°C
1000 mW (6 dB)
500 mW (9 dB)
250 mW (12 dB)
120 mW (15 dB)
63 mW (18 dB)
DISSIPATION RATING TABLE
PACKAGE
T
A
≤ 25°C
DERATING FACTOR
T
A
= 70°C
T = 85°C
A
5.6 W
44.8 mW/°C
3.5 W
2.9 W
DCA
The maximum ambient temperature depends on the heatsinking ability of the PCB system. Using the 0 CFM
2
data from the dissipation rating table, the derating factor for the DCA package with 6.9 in of copper area on
a multilayer PCB is 44.8 mW/°C. Converting this to Θ
:
JA
1
Θ
JA
Derating
(19)
1
0.0448
22.3°C W
To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are
per channel so the dissipated heat needs to be doubled for two channel operation. Given Θ , the maximum
JA
allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be
calculated with the following equation. The maximum recommended junction temperature for the TPA005D02
is 150 °C. The internal dissipation figures are taken from the Efficiency vs Output Power graphs.
T
Max
T Max
Θ
P
(20)
A
J
JA
D
(
)
)
(
)
150 22.3 0.14
2
143°C 15 dB crest factor
(
(
)
150 22.3 0.56
2
125°C 3dB crest factor
NOTE:
Internal dissipation of 0.6 W is estimated for a 2-W system with a 15 dB crest factor per channel.
Table 4 shows that for some applications no airflow is required to keep junction temperatures in the specified
range. The TPA005D02 is designed with thermal protection that turns the device off when the junction
temperature surpasses 150°C to prevent damage to the IC. Table 4 was calculated for maximum listening
volume without distortion. When the output level is reduced the numbers in the table change significantly. Also,
using 8-Ω speakers dramatically increases the thermal performance by increasing amplifier efficiency.
22
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
THERMAL INFORMATION
The thermally enhanced DCA package is based on the 56-pin TSSOP, but includes a thermal pad (see Figure 59)
to provide an effective thermal contact between the IC and the PWB.
Traditionally, surface-mount and power have been mutually exclusive terms. A variety of scaled-down TO-220-type
packages have leads formed as gull wings to make them applicable for surface-mount applications. These packages,
however, have only two shortcomings: they do not address the very low profile requirements (<2 mm) of many of
today’s advanced systems, and they do not offer a terminal-count high enough to accommodate increasing
integration. Ontheotherhand, traditionallow-powersurface-mountpackagesrequirepower-dissipationderatingthat
severely limits the usable range of many high-performance analog circuits.
The PowerPAD package (thermally enhanced TSSOP) combines fine-pitch surface-mount technology with thermal
performance comparable to much larger power packages.
The PowerPAD package is designed to optimize the heat transfer to the PWB. Because of the very small size and
limited mass of a TSSOP package, thermal enhancement is achieved by improving the thermal conduction paths that
remove heat from the component. The thermal pad is formed using a patented lead-frame design and manufacturing
technique to provide a direct connection to the heat-generating IC. When this pad is soldered or otherwise thermally
coupled to an external heat dissipator, high power dissipation in the ultra-thin, fine-pitch, surface-mount package can
be reliably achieved.
Thermal
Pad
DIE
Side View (a)
DIE
End View (b)
Bottom View (c)
Figure 22. Views of Thermally Enhanced DCA Package
23
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TPA005D02
2-W STEREO CLASS-D AUDIO POWER AMPLIFIER
SLOS227C – AUGUST 1998 – REVISED MARCH 2000
MECHANICAL DATA
DCA (R-PDSO-G**)
PowerPAD PLASTIC SMALL-OUTLINE PACKAGE
48 PINS SHOWN
0,27
0,17
M
0,08
0,50
48
25
Thermal Pad
(See Note D)
6,20
6,00
8,30
7,90
0,15 NOM
Gage Plane
1
24
0,25
A
0°–8°
0,75
0,50
Seating Plane
0,10
0,15
0,05
1,20 MAX
PINS **
48
56
64
DIM
12,60
12,40
14,10
13,90
17,10
16,90
A MAX
A MIN
4073259/A 01/98
NOTES: A. All linear dimensions are in millimeters.
B. This drawing is subject to change without notice.
C. Body dimensions do not include mold flash or protrusion not to exceed 0,15.
D. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane.
This pad is electrically and thermally connected to the backside of the die and possibly selected leads.
E. Falls within JEDEC MO-153
PowerPAD is a trademark of Texas Instruments.
24
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
IMPORTANT NOTICE
Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue
any product or service without notice, and advise customers to obtain the latest version of relevant information
to verify, before placing orders, that information being relied on is current and complete. All products are sold
subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those
pertaining to warranty, patent infringement, and limitation of liability.
TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in
accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent
TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily
performed, except those mandated by government requirements.
Customers are responsible for their applications using TI components.
In order to minimize risks associated with the customer’s applications, adequate design and operating
safeguards must be provided by the customer to minimize inherent or procedural hazards.
TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent
that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other
intellectual property right of TI covering or relating to any combination, machine, or process in which such
semiconductor products or services might be or are used. TI’s publication of information regarding any third
party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.
Copyright 2000, Texas Instruments Incorporated
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