TPS62260TDRVRQ1 [TI]
2.25-MHz 600-mA STEP-DOWN CONVERTERS; 2.25 - MHz的600 - mA的降压转换器
| 型号： | TPS62260TDRVRQ1 |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 2.25-MHz 600-mA STEP-DOWN CONVERTERS |
| 文件： | 总32页 (文件大小：1318K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
www.ti.com
SLVSA16C –AUGUST 2009–REVISED JULY 2012
2.25-MHz 600-mA STEP-DOWN CONVERTERS
Check for Samples: TPS62260-Q1, TPS62261-Q1, TPS62262-Q1, TPS62263-Q1
1
FEATURES
2
•
•
•
•
Qualified for Automotive Applications
High-Efficiency Step-Down Converter
Output Current up to 600 mA
•
•
•
•
Soft Start
Voltage Positioning at Light Loads
Available in a Small 2×2×0,8-mm SON Package
Allows <1-mm Solution Height
Wide VIN Range from 2-V to 6-V for Li-Ion
Batteries with Extended Voltage Range
APPLICATIONS
•
•
•
•
•
2.25-MHz Fixed Frequency Operation
Power Save Mode at Light Load Currents
Output Voltage Accuracy in PWM Mode ±1.5%
15-μA (Typ) Quiescent Current
•
•
•
•
PDAs, Pocket PCs
Low Power DSP Supply
Portable Media Players
POL applications
100% Duty Cycle for Lowest Dropout
DESCRIPTION
The TPS6226x devices are high-efficiency synchronous step-down dc-dc converters optimized for battery
powered applications. It provides up to 600-mA output current from a single Li-Ion cell and is ideal to power
mobile phones and other portable applications.
With an wide input voltage range of 2 V to 6 V, the device supports applications powered by Li-Ion batteries with
extended voltage range, two and three cell alkaline batteries, 3.3-V and 5-V input voltage rails.
The TPS6226x operates at 2.25-MHz fixed switching frequency and enters Power Save Mode operation at light
load currents to maintain high efficiency over the entire load current range.
The Power Save Mode is optimized for low output voltage ripple. For low noise applications, the device can be
forced into fixed frequency PWM mode by pulling the MODE pin high. In the shutdown mode, the current
consumption is reduced to less than 1 μA. TPS6226x allows the use of small inductors and capacitors to achieve
a small solution size.
The TPS6226x is available in a very small 2×2mm 6-pin SON package.
100
90
80
70
60
50
40
30
20
L
TPS62260DRV
VIN = 2V to 6V
VIN = 2.3 V
VIN = 2.7 V
Up to 600mA
2.2 mH
V
V
IN
SW
FB
OUT
C
1
22 pF
C
C
R
OUT
IN
1
EN
V
IN = 3 V
10 mF
4.7 mF
VIN = 3.6 V
VIN = 4.5 V
GND
R
2
MODE
VOUT = 1.8 V,
MODE = GND,
L = 2.2 mH,
DCR 110 mR
10
0
0.01
0.1
1
10
100
1000
IO - Output Current - mA
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
2
PowerPAD is a trademark of Texas Instruments.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2009–2012, Texas Instruments Incorporated
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
SLVSA16C –AUGUST 2009–REVISED JULY 2012
www.ti.com
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more
susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.
ORDERING INFORMATION(1)
OUTPUT
TA
PACKAGE(2)
ORDERABLE PART NUMBER
TOP-SIDE MARKING
VOLTAGE
Adjustable
1.8 V
–40°C to 85°C
TPS62260IDRVRQ1
TPS62261TDRVRQ1
TPS62262TDRVRQ1
TPS62263TDRVRQ1
TPS62260TDRVRQ1
OEO
OFE
OFF
OFG
OEO
–40°C to 105°C
1.2 V
SON – DRV
Reel of 3000
2.5 V
–40°C to 105°C
Adjustable
(1) For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI
web site at www.ti.com.
(2) Package drawings, thermal data, and symbolization are available at www.ti.com/packaging.
ABSOLUTE MAXIMUM RATINGS(1)
over operating free-air temperature range (unless otherwise noted)
Input voltage range(2)
Voltage range at EN, MODE
Voltage on SW
–0.3 V to 7 V
–0.3 V to VIN +0.3 V, ≤ 7 V
–0.3 V to 7 V
Internally limited
2000 V
Peak output current
HBM, Human-body model
CDM, Charged-device model
MM, Machine model
ESD rating(3)
1000 V
200 V
TJ
Operating junction temperature
Storage temperature range
–40°C to 125°C
–65°C to 150°C
Tstg
(1) Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings
only and functional operation of the device at these or any other conditions beyond those indicated under recommended operating
conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
(2) All voltage values are with respect to network ground terminal.
(3) The human body model is a 100-pF capacitor discharged through a 1.5-kΩ resistor into each pin. The machine model is a 200-pF
capacitor discharged directly into each pin.
DISSIPATION RATINGS
PACKAGE
RθJA
POWER RATING FOR TA ≤ 25°C
DERATING FACTOR ABOVE TA = 25°C
DRV
76°C/W
1300 mW
13 mW/°C
RECOMMENDED OPERATING CONDITIONS
MIN NOM
MAX UNIT
VIN Supply voltage
2
0.6
6
VIN
85
V
V
Output voltage range for adjustable voltage
TA Operating ambient temperature
TPS62260IDRVRQ1
TPS6226XTDRVRQ1
–40
-40
–40
°C
105
125
TJ
Operating junction temperature
°C
2
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Product Folder Link(s): TPS62260-Q1 TPS62261-Q1 TPS62262-Q1 TPS62263-Q1
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
www.ti.com
SLVSA16C –AUGUST 2009–REVISED JULY 2012
ELECTRICAL CHARACTERISTICS
Over full operating ambient temperature range, typical values are at TA = 25°C. Unless otherwise noted, specifications apply
for condition VIN = EN = 3.6V. External components CIN = 4.7μF 0603, COUT = 10μF 0603, L = 2.2μH, see the parameter
measurement information.
PARAMETER
Input voltage range
Output current(1)
TEST CONDITIONS
MIN
TYP MAX UNIT
Supply
VIN
2.3
6
V
VIN 2.5 V to 6 V
600
IOUT
VIN 2.3 V to 2.5 V
VIN 2 V to 2.3 V
300 mA
150
IOUT = 0 mA, PFM mode enabled (MODE = GND),
device not switching
IOUT = 0 mA, PFM mode(2) enabled (MODE = GND),
device switching, VOUT = 1.8 V
15
μA
IQ
Operating quiescent current
18.5
IOUT = 0 mA, switching with no load (MODE = VIN),
PWM operation, VOUT = 1.8 V, VIN = 3 V
3.8
0.1
mA
TA = 25°C
1
μA
2.5
ISD
Shutdown current
EN = GND
TA = 105°C
Falling
Rising
1.85
1.95
UVLO
Undervoltage lockout threshold
V
Enable, Mode
VIH
VIL
IIN
High level input voltage, EN, MODE
2 V ≤ VIN ≤ 6 V
1
0
VIN
0.4
1
V
V
Low level input voltage, EN, MODE
Input bias current, EN, MODE
2 V ≤ VIN ≤ 6 V
EN, MODE = GND or VIN
0.01
μA
Power Switch
High-side MOSFET on-resistance
240
185
480
380
RDS(on)
VIN = VGS = 3.6 V, TA = 25°C
VIN = VGS = 3.6 V, TA = 25°C
mΩ
A
Low-side MOSFET on-resistance
Forward current limit MOSFET, high
side and low side
ILIMF
0.8
1
1.3
Thermal shutdown
Increasing junction temperature
Decreasing junction temperature
140
20
TSD
°C
Thermal shutdown hysteresis
Oscillator
fSW
Oscillator frequency
2 V ≤ VIN ≤ 6 V
2
2.25
2.5 MHz
Output
VOUT
Adjustable output voltage range
Reference voltage
0.6
VIN
V
Vref
600
mV
MODE = VIN, PWM operation,
Feedback voltage PWM mode
for fixed output voltage versions VFB = VOUT
2.5 V ≤ VIN ≤ 6 V, 0 mA ≤ IOUT ≤ 600 mA
,
–1.5%
0% 1.5%
1%
(3)
VFB
MODE = GND, device in PFM mode,
voltage positioning active(2)
Feedback voltage PFM mode
Load regulation
PWM Mode
-0.5
500
250
%/A
μs
tStart Up
tRamp
Ilkg
Start-up time
Time from active EN to reach 95% of VOUT nominal
Time to ramp from 5% to 95% of VOUT
VOUT ramp-up time
Leakage current into SW pin
μs
(4)
VIN = 3.6 V, VIN = VOUT = VSW, EN = GND
0.1
1
μA
(1) Not production tested
(2) In PFM mode, the internal reference voltage is set to typ. 1.01×Vref. See the parameter measurement information.
(3) For VIN = VO + 0.6 V
(4) In fixed output voltage versions, the internal resistor divider network is disconnected from FB pin.
Copyright © 2009–2012, Texas Instruments Incorporated
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TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
SLVSA16C –AUGUST 2009–REVISED JULY 2012
www.ti.com
PIN ASSIGNMENTS
DRV PACKAGE
(TOP VIEW)
1
2
3
6
SW
MODE
FB
GND
VIN
EN
Exposed
Thermal
Pad
5
4
TERMINAL FUNCTIONS
TERMINAL
I/O
DESCRIPTION
NAME
NO.
This is the switch pin and is connected to the internal MOSFET switches. Connect the external inductor
between this terminal and the output capacitor.
SW
1
OUT
I
This pin is only available at SON package option. MODE pin = high forces the device to operate in fixed
frequency PWM mode. MODE pin = low enables the Power Save Mode with automatic transition from
PFM mode to fixed frequency PWM mode.
MODE
2
Feedback for the internal regulation loop. Connect the external resistor divider to this pin. In case of
fixed output voltage option, connect this pin directly to the output capacitor.
FB
EN
3
4
I
I
This is the enable pin of the device. Pulling this pin to low forces the device into shutdown mode. Pulling
this pin to high enables the device. This pin must be terminated.
VIN
5
6
PWR Power supply
PWR Ground
GND
FUNCTIONAL BLOCK DIAGRAM
VIN
Current-
Limit Comparator
V
IN
Thermal
Shutdown
Undervoltage
Lockout1.8 V
Limit
EN
High Side
PFM Comparator
+1% Voltage positioning
Reference
0.6 V VREF
FB
VREF +1%
Gate Driver
Anti-
Shoot-Through
Only in 2x2SON
MODE
FB
Control
Stage
MODE
Error Amplifier
Softstart
VOUT RAMP
CONTROL
SW1
VREF
Integrator
PWM
Comp.
FB
Zero-Pole
Amp.
Limit
RI 1
GND
Low Side
RI..N
Current-
Limit Comparator
2.25-MHz
Oscillator
Sawtooth
Generator
Int. Resistor
Network
GND
4
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Product Folder Link(s): TPS62260-Q1 TPS62261-Q1 TPS62262-Q1 TPS62263-Q1
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
www.ti.com
SLVSA16C –AUGUST 2009–REVISED JULY 2012
PARAMETER MEASUREMENT INFORMATION
L
2.2 mH
TPS62260DVR
V
OUT
C
V
IN
SW
FB
R
1
C
C
1
22 pF
IN
EN
OUT
4.7 mF
10 mF
GND
R
2
MODE
L: LPS3015 2.2 mH, 110 mW
GRM188R60J475K 4.7 mF Murata 0603 size
C
IN
C
GRM188R60J106M 10 mF Murata 0603 size
OUT
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Product Folder Link(s): TPS62260-Q1 TPS62261-Q1 TPS62262-Q1 TPS62263-Q1
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
SLVSA16C –AUGUST 2009–REVISED JULY 2012
www.ti.com
TYPICAL CHARACTERISTICS
Table 1. Table of Graphs
FIGURE
Output Current VOUT = 1.8 V, Power Save Mode, MODE = GND
Output Current VOUT = 1.8 V, PWM Mode, MODE = VIN
Output Current VOUT = 3.3 V, PWM Mode, MODE = VIN
Output Current VOUT = 3.3 V, Power Save Mode, MODE = GND
Output Current
Figure 1
Figure 2
Figure 3
η
Efficiency
Figure 4
Figure 5
Output Current
Figure 6
at 25°C, VOUT = 1.8 V, Power Save Mode, MODE = GND
at –40°C, VOUT = 1.8 V, Power Save Mode, MODE = GND
at 85°C, VOUT = 1.8 V, Power Save Mode, MODE = GND
at 25°C, VOUT = 1.8 V, PWM Mode, MODE = VIN
at –40°C, VOUT = 1.8 V, PWM Mode, MODE = VIN
Figure 7
Figure 8
Figure 9
Output Voltage Accuracy
Figure 10
Figure 11
Figure 12
Figure 13
Figure 14
Figure 15
Figure 16
Figure 17
Figure 18
Figure 19
Figure 20
Figure 21
Figure 22
Figure 23
Figure 24
Figure 25
Figure 26
Figure 27
Figure 28
Figure 29
Figure 30
Figure 31
Figure 32
Figure 33
at 85°C, V
= 1.8 V, PWM Mode, MODE = VIN
Typical Operation
Mode Transition
Start-up Timing
PWM ModOeU, TV
= 1.8 V
MODE Pin TraOnUsiTtion From PFM to Forced PWM Mode at light load
MODE Pin Transition From Forced PWM to PFM Mode at light load
Forced PWM Mode , VOUT = 1.5 V, 50 mA to 200 mA
Forced PWM Mode , VOUT = 1.5 V, 200 mA to 400 mA
PFM Mode to PWM Mode, VOUT = 1.5 V, 150 μA to 400 mA
PWM Mode to PFM Mode, VOUT = 1.5 V, 400 mA to 150 μA
PFM Mode, VOUT = 1.5 V, 1.5 mA to 50 mA
Load Transient
PFM Mode, V
= 1.5 V, 50 mA to 1.5 mA
PFM Mode toOPUWT M Mode, VOUT = 1.8 V, 50 mA to 250 mA
PFM Mode to PWM Mode, VOUT = 1.5 V, 50 mA to 400 mA
PWM Mode to PFM Mode, V
= 1.5 V, 400 mA to 50 mA
PFM Mode, VOUT = 1.8 V, 50OmUTA
Line Transient
PFM Mode, VOUT = 1.8 V, 250 mA
PFM V
Ripple, V
= 1.8 V, 10 mA, L = 2.2μH, COUT = 10μF
PFM VOUT Ripple, VOUT = 1.8 V, 10 mA, L = 4.7μH, COUT = 10μF
vs InpuOtUVToltage, (T O=UT85°C, T = 25°C, T = -40°C)
vs Input Voltage, (TAA = 85°C, TAA = 25°C, TAA = -40°C)
Typical Operation
Shutdown Current into VIN
Quiescent Current
Static Drain Source On-State
Resistance
vs Input Voltage, (TA = 85°C, TA = 25°C, TA = -40°C)
EFFICIENCY (Power Save Mode)
EFFICIENCY (PWM Mode)
vs
vs
OUTPUT CURRENT
OUTPUT CURRENT
100
90
100
90
V
= 2.3 V
IN
80
80
V
= 2.7 V
= 3 V
IN
70
70
V
IN
V
= 3.6 V
= 4.5 V
60
50
40
60
50
40
IN
V
IN
30
20
30
20
VOUT = 1.8 V
V
= 1.8 V,
MODE = GND
L = 2.2 mH
DCR 110 mR
OUT
MODE = V
,
IN
L = 2.2 mH
10
0
10
0
0.01
0.1
1
10
100
1000
1
10
100
1000
I
- Output Current - mA
I
- Output Current - mA
Figure 1.
O
O
Figure 2.
6
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Product Folder Link(s): TPS62260-Q1 TPS62261-Q1 TPS62262-Q1 TPS62263-Q1
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
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SLVSA16C –AUGUST 2009–REVISED JULY 2012
EFFICIENCY (PWM Mode)
vs
EFFICIENCY (Power Save Mode)
vs
OUTPUT CURRENT
OUTPUT CURRENT
100
90
80
70
60
50
40
30
20
100
90
80
70
60
50
40
30
20
VIN = 4.2 V
VIN = 3.6 V
VIN = 4.2 V
VIN = 3.6 V
VIN = 5 V
VIN = 4.5 V
VIN = 5 V
VIN = 4.5 V
VOUT = 3.3 V
VOUT = 3.3 V
MODE = VIN
MODE = GND
L = 2.2 mH
DCR = 110 mH
COUT = 10 mF 0603
L = 2.2 mH
DCR 110 mW
COUT = 10 mF 0603
10
0
10
0
1
10
100
1000
0.01
0.1
1
10
100
1000
IOUT – Output Current – mA
IOUT – Output Current – mA
Figure 3.
Figure 4.
EFFICIENCY
vs
EFFICIENCY
vs
OUTPUT CURRENT
OUTPUT CURRENT
100
90
100
90
V
= 2.3 V
I
V
= 2.7 V
I
80
80
V
= 4.5 V
I
70
70
V
= 2.3 V
I
V
I
= 2.3 V
V
= 3.6 V
I
60
50
40
60
50
40
V
= 4.5 V
I
V
= 2.7 V
I
V
= 3.6 V
I
30
V
= 1.2 V,
30
V
= 1.2 V
O
O
MODE = V ,
I
MODE = GND
L = 2 mH
MIPSA2520
20
10
0
20
10
0
L = 2 mH,
MIPSA2520
C
= 10 mF 0603
C
= 10 mF 0603
O
O
1
10
100
1000
0.01
0.1
1
10
100
1000
I
− Output Current − mA
I
− Output Current − mA
O
O
Figure 5.
Figure 6.
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Product Folder Link(s): TPS62260-Q1 TPS62261-Q1 TPS62262-Q1 TPS62263-Q1
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
SLVSA16C –AUGUST 2009–REVISED JULY 2012
www.ti.com
OUTPUT VOLTAGE ACCURACY
OUTPUT VOLTAGE ACCURACY (Power Save Mode)
vs
vs
OUTPUT CURRENT
OUTPUT CURRENT
1.88
1.86
1.84
1.82
1.8
1.88
1.86
1.84
1.82
1.8
PFM Mode, Voltage Positioning
T
V
= 25°C
TA = –40°C
1.78
1.78
A
= 1.8 V
VOUT = 1.8 V
OUT
MODE = GND
L = 2.2 mH
MODE = GND
L = 2.2 mH
1.76
1.74
1.76
1.74
C
= 10 mF
CO = 10 mF
O
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
I
– Output Current – mA
I
– Output Current – mA
O
O
Figure 7.
Figure 8.
OUTPUT VOLTAGE ACCURACY (Power Save Mode)
OUTPUT VOLTAGE ACCURACY (PWM Mode)
vs
vs
OUTPUT CURRENT
OUTPUT CURRENT
1.854
1.836
1.818
1.88
T
= 25°C,
A
V
= 1.8 V,
OUT
MODE = V
1.86
1.84
1.82
1.8
,
IN
L = 2.2 mH
1.8
V
V
= 2.3 V
= 2.7 V
= 3 V
IN
IN
V
1.782
TA = 85°C
IN
1.78
V
V
= 3.6 V
= 4.5 V
VOUT = 1.8 V
MODE = GND
L = 2.2 mH
IN
IN
1.764
1.746
1.76
1.74
CO = 10 mF
0.01
0.1
I
1
10
100
1000
0.01
0.1
1
10
100
1000
- Output Current - mA
I
– Output Current – mA
O
O
Figure 9.
Figure 10.
8
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TPS62262-Q1, TPS62263-Q1
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SLVSA16C –AUGUST 2009–REVISED JULY 2012
OUTPUT VOLTAGE ACCURACY (PWM Mode)
OUTPUT VOLTAGE ACCURACY (PWM Mode)
vs
vs
OUTPUT CURRENT
OUTPUT CURRENT
1.854
1.836
1.818
1.8
1.854
1.836
1.818
T
= 85°C,
T
= -40°C,
A
A
V
= 1.8 V,
V
= 1.8 V,
OUT
MODE = V
OUT
MODE = V
,
,
IN
IN
L = 2.2 mH
L = 2.2 mH
1.8
V
= 2 V
IN
V
= 2.7 V
= 3 V
V
V
= 2.3 V
= 2.7 V
= 3 V
IN
V
IN
1.782
1.764
1.746
1.782
1.764
1.746
IN
IN
V
V
V
= 3.6 V
= 4.5 V
IN
IN
IN
V
V
= 3.6 V
= 4.5 V
IN
IN
0.01
0.1
1
10
100
1000
0.01
0.1
1
10
100
1000
I
- Output Current - mA
I
- Output Current - mA
O
O
Figure 11.
Figure 12.
MODE PIN TRANSITION FROM PFM
TYPICAL OPERATION (PWM Mode)
TO FORCED PWM MODE AT LIGHT LOAD
V
V
3.6V
IN
V
V
I
= 3.6 V
IN
1.8V, I
150mA
10mF 0603
OUT
OUT
= 1.8 V
= 10 mA
OUT
MODE
L 2.2mH, C
OUT
V
10 mV/Div
2V/Div
OUT
OUT
SW 2 V/Div
SW
2V/Div
PFM Mode
Forced PWM Mode
ICOIL 200 mA/Div
I
coil
200mA/Div
Time Base - 1 ms/Div
Time Base - 10 ms/Div
Figure 13.
Figure 14.
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MODE PIN TRANSITION FROM PWM
TO PFM MODE AT LIGHT LOAD
START-UP TIMING
MODE
V
= 3.6 V
EN 2 V/Div
IN
V
V
I
= 3.6 V
IN
2 V/Div
R
V
= 10 Ω
Load
= 1.8 V
= 10 mA
OUT
= 1.8 V
OUT
into C
OUT
I
IN
IN
MODE = GND
SW
SW 2 V/Div
2 V/Div
PFM Mode
Forced PWM Mode
VOUT 2 V/Div
I
COIL
200 mA/Div
I
100 mA/Div
IN
Time Base - 100 ms/Div
Time Base - 2.5 ms/Div
Figure 15.
Figure 16.
LOAD TRANSIENT
(Forced PWM Mode)
LOAD TRANSIENT
(Forced PWM Mode)
V
V
I
3.6 V
V
V
I
3.6 V
IN
OUT
IN
OUT
1.5 V
50 mA to 200 mA
1.5 V
200 mA to 400 mA
VOUT 50 mV/Div
V
50 mV/Div
OUT
OUT
OUT
MODE = V
IN
IOUT 200 mA/Div
400 mA
I
200 mA/Div
200 mA
OUT
ICOIL 500 mA/Div
I
500 mA/Div
COIL
Time Base - 20 ms/Div
Time Base - 20 ms/Div
Figure 17.
Figure 18.
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LOAD TRANSIENT
(Forced PFM Mode To PWM Mode)
LOAD TRANSIENT
(Forced PWM Mode To PFM Mode)
SW 2 V/Div
SW 2 V/Div
VIN 3.6 V
VOUT 1.5 V
V
IN 3.6 V
IOUT 150 mA to 400 mA
MODE = GND
VOUT 1.5 V
V
OUT 50mV/Div
IOUT 150 mA to 400 mA
VOUT 50 mV/Div
MODE = GND
400 mA
400 mA
IOUT 500 mA/Div
IOUT 500 mA/Div
150 mA
150 mA
ICOIL500 mA/Div
I
500mA/Div
COILl
Time Base – 500 ms/Div
Time Base – 500 ms/Div
Figure 19.
Figure 20.
LOAD TRANSIENT (PFM Mode)
LOAD TRANSIENT (PFM Mode)
SW 2 V/Div
SW 2 V/Div
VIN 3.6 V
VIN 3.6 V
VOUT 1.5 V
VOUT 1.5 V
IOUT 50 mA to 1.5mA
MODE = GND
IOUT 1.5 mA to 50 mA
MODE = GND
VOUT 50 mV/Div
VOUT 50mV/Div
50 mA
50 mA
IOUT 50 mA/Div
1.5 mA
IOUT 50 mA/Div
1.5 mA
ICOIL 500 mA/Div
ICOIL 500 mA/Div
Time Base – 50 ms/Div
Time Base – 50 ms/Div
Figure 21.
Figure 22.
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LOAD TRANSIENT
LOAD TRANSIENT
(PFM Mode To PWM Mode)
(PFM Mode To PWM Mode)
SW 2 V/Div
SW 2 V/Div
VIN 3.6 V
VOUT 50 mV/Div
VOUT 1.5 V
VOUT 50 mV/Div
VIN 3.6 V
IOUT 50 mA to 400 mA
MODE = GND
VOUT 1.8 V
IOUT 50 mA to 250 mA
MODE = GND
250 mA
PWM Mode
400 mA
PFM Mode
IOUT 500 mA/Div
50 mA
IOUT 200 mA/Div
50 mA
ICOIL 500 mA/Div
ICOIL 500mA/Div
Time Base – 20 ms/Div
Time Base – 20 ms/Div
Figure 23.
Figure 24.
LOAD TRANSIENT
(PWM Mode To PFM Mode)
SW 2 V/Div
LINE TRANSIENT (PFM Mode)
V
IN 3.6V to 4.2V
500 mV/Div
VIN 3.6 V
VOUT 1.5 V
VOUT 50 mV/Div
IOUT 50 mA to 400 mA
MODE = GND
PFM Mode
IOUT 500 mA/Div
PWM Mode
400 mA
VOUT = 1.8 V
50 mV/Div
50 mA
IOUT = 50 mA
MODE = GND
ICOIL 500 mA/Div
Time Base – 20 ms/Div
Figure 25.
Figure 26.
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SLVSA16C –AUGUST 2009–REVISED JULY 2012
LINE TRANSIENT (PWM Mode)
TYPICAL OPERATION (PFM Mode)
VOUT 20 mV/Div
VIN 3.6V to 4.2V
500 mV/Div
SW 2 V/Div
VOUT = 1.8 V
50 mV/Div
IOUT = 250 mA
MODE = VIN
ICOIL 200 mA/Div
Time Base – 10 ms/Div
Time Base – 100ms/Div
Figure 27.
Figure 28.
SHUTDOWN CURRENT INTO VIN
vs
TYPICAL OPERATION (PFM Mode)
VIN 3.6 V; VOUT 1.8 V, IOUT 10 mA,
L = 4.7 mH, COUT = 10 mF 0603,
INPUT VOLTAGE
0.8
EN = GND
VOUT 20 mV/Div
MODE = GND
0.7
0.6
T
= 85oC
A
SW 2 V/Div
0.5
0.4
0.3
0.2
ICOIL 200 mA/Div
T
= 25oC
T
= -40oC
A
A
0.1
0
Time Base – 2 ms/Div
2
2.5
3
3.5
4
4.5
5
5.5
6
V
− Input Voltage − V
IN
Figure 29.
Figure 30.
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2
2
.5
3
3
.
5
44
44..55
55
55..55
2
2.5
3
3.5
4
4.5
5
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
SLVSA16C –AUGUST 2009–REVISED JULY 2012
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QUIESCENT CURRENT
STATIC DRAIN-SOURCE ON-STATE RESISTANCE
vs
vs
INPUT VOLTAGE
INPUT VOLTAGE
0.8
0.7
0.6
0.5
20
MODE = GND
MODE = GND,
EN = VIN
EN = VIN,
High Side Switching
o
= 85°C
Device Not Switching
Device Not Switching
T
T A = 85
18
16
14
12
10
A
T
= 85oC
A
T
= 25o°C
T
A
A
C
T
= 25oC
A
0.4
0.3
0.2
0.1
0
T
T A = -
= –40o°C
C
T
= -40oC
A
A
8
82
6
6
V
− Input Voltage − V
V
– Input Voltage – V
− Input Voltage − V
V
IN
IN
IN
Figure 31.
Figure 32.
STATIC DRAIN-SOURCE ON-STATE RESISTANCE
vs
INPUT VOLTAGE
0.4
Low Side Switching
0.35
0.3
T
= 85oC
A
0.25
T
= 25oC
A
0.2
0.15
0.1
0.05
0
T
= -40oC
A
2
2.5
3
3.5
4
4.5
5
V
− Input Voltage − V
IN
Figure 33.
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SLVSA16C –AUGUST 2009–REVISED JULY 2012
DETAILED DESCRIPTION
OPERATION
The TPS6226x step down converter operates with typically 2.25 MHz fixed frequency pulse width modulation
(PWM) at moderate to heavy load currents. At light load currents the converter can automatically enter Power
Save Mode and operates then in PFM mode.
During PWM operation the converter use a unique fast response voltage mode control scheme with input voltage
feed-forward to achieve good line and load regulation allowing the use of small ceramic input and output
capacitors. At the beginning of each clock cycle initiated by the clock signal, the High Side MOSFET switch is
turned on. The current flows now from the input capacitor via the High Side MOSFET switch through the inductor
to the output capacitor and load. During this phase, the current ramps up until the PWM comparator trips and the
control logic will turn off the switch. The current limit comparator will also turn off the switch in case the current
limit of the High Side MOSFET switch is exceeded. After a dead time preventing shoot through current, the Low
Side MOSFET rectifier is turned on and the inductor current will ramp down. The current flows now from the
inductor to the output capacitor and to the load. It returns back to the inductor through the Low Side MOSFET
rectifier.
The next cycle will be initiated by the clock signal again turning off the Low Side MOSFET rectifier and turning on
the on the High Side MOSFET switch.
POWER SAVE MODE
The Power Save Mode is enabled with MODE Pin set to low level. If the load current decreases, the converter
will enter Power Save Mode operation automatically. During Power Save Mode the converter skips switching and
operates with reduced frequency in PFM mode with a minimum quiescent current to maintain high efficiency. The
converter will position the output voltage typically +1% above the nominal output voltage. This voltage positioning
feature minimizes voltage drops caused by a sudden load step.
The transition from PWM mode to PFM mode occurs once the inductor current in the Low Side MOSFET switch
becomes zero, which indicates discontinuous conduction mode.
During the Power Save Mode the output voltage is monitored with a PFM comparator. As the output voltage falls
below the PFM comparator threshold of VOUT nominal +1%, the device starts a PFM current pulse. The High
Side MOSFET switch will turn on, and the inductor current ramps up. After the On-time expires, the switch is
turned off and the Low Side MOSFET switch is turned on until the inductor current becomes zero.
The converter effectively delivers a current to the output capacitor and the load. If the load is below the delivered
current, the output voltage will rise. If the output voltage is equal or higher than the PFM comparator threshold,
the device stops switching and enters a sleep mode with typical 15μA current consumption.
If the output voltage is still below the PFM comparator threshold, a sequence of further PFM current pulses are
generated until the PFM comparator threshold is reached. The converter starts switching again once the output
voltage drops below the PFM comparator threshold.
With a fast single threshold comparator, the output voltage ripple during PFM mode operation can be kept small.
The PFM Pulse is time controlled, which allows to modify the charge transferred to the output capacitor by the
value of the inductor. The resulting PFM output voltage ripple and PFM frequency depend in first order on the
size of the output capacitor and the inductor value. Increasing output capacitor values and inductor values will
minimize the output ripple. The PFM frequency decreases with smaller inductor values and increases with larger
values.
The PFM mode is left and PWM mode entered in case the output current can not longer be supported in PFM
mode. The Power Save Mode can be disabled through the MODE pin set to high. The converter will then operate
in fixed frequency PWM mode.
Dynamic Voltage Positioning
This feature reduces the voltage under/overshoots at load steps from light to heavy load and vice versa. It is
active in Power Save Mode and regulates the output voltage 1% higher than the nominal value. This provides
more headroom for both the voltage drop at a load step, and the voltage increase at a load throw-off.
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Output voltage
Vout +1%
PFM Comparator
threshold
Voltage Positioning
Light load
PFM Mode
Vout (PWM)
moderate to heavy load
PWM Mode
Figure 34. Power Save Mode Operation with automatic Mode transition
100% Duty Cycle Low Dropout Operation
The device starts to enter 100% duty cycle mode once the input voltage comes close to the nominal output
voltage. In order to maintain the output voltage, the High Side MOSFET switch is turned on 100% for one or
more cycles.
With further decreasing VIN the High Side MOSFET switch is turned on completely. In this case the converter
offers a low input-to-output voltage difference. This is particularly useful in battery-powered applications to
achieve longest operation time by taking full advantage of the whole battery voltage range.
The minimum input voltage to maintain regulation depends on the load current and output voltage, and can be
calculated as:
VINmin = VOmax + IOmax × (RDS(on)max + RL)
With:
IOmax = maximum output current plus inductor ripple current
RDS(on)max = maximum P-channel switch RDSon.
RL = DC resistance of the inductor
VOmax = nominal output voltage plus maximum output voltage tolerance
Undervoltage Lockout
The undervoltage lockout circuit prevents the device from malfunctioning at low input voltages and from
excessive discharge of the battery and disables the output stage of the converter. The undervoltage lockout
threshold is typically 1.85V with falling VIN.
MODE SELECTION
The MODE pin allows mode selection between forced PWM mode and Power Save Mode.
Connecting this pin to GND enables the Power Save Mode with automatic transition between PWM and PFM
mode. Pulling the MODE pin high forces the converter to operate in fixed frequency PWM mode even at light
load currents. This allows simple filtering of the switching frequency for noise sensitive applications. In this mode,
the efficiency is lower compared to the power save mode during light loads.
The condition of the MODE pin can be changed during operation and allows efficient power management by
adjusting the operation mode of the converter to the specific system requirements.
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ENABLE
The device is enabled setting EN pin to high. During the start up time tStart Up the internal circuits are settled and
the soft start circuit is activated. The EN input can be used to control power sequencing in a system with various
DC/DC converters. The EN pin can be connected to the output of another converter, to drive the EN pin high and
getting a sequencing of supply rails. With EN = GND, the device enters shutdown mode in which all internal
circuits are disabled. In fixed output voltage versions, the internal resistor divider network is then disconnected
from FB pin.
SOFT START
The TPS6226x has an internal soft start circuit that controls the ramp up of the output voltage. The output
voltage ramps up from 5% to 95% of its nominal value within typical 250μs. This limits the inrush current in the
converter during ramp up and prevents possible input voltage drops when a battery or high impedance power
source is used. The soft start circuit is enabled within the start up time tStart Up
.
SHORT-CIRCUIT PROTECTION
The High Side and Low Side MOSFET switches are short-circuit protected with maximum switch current = ILIMF
.
The current in the switches is monitored by current limit comparators. Once the current in the High Side
MOSFET switch exceeds the threshold of it's current limit comparator, it turns off and the Low Side MOSFET
switch is activated to ramp down the current in the inductor and High Side MOSFET switch. The High Side
MOSFET switch can only turn on again, once the current in the Low Side MOSFET switch has decreased below
the threshold of its current limit comparator.
THERMAL SHUTDOWN
As soon as the junction temperature, TJ, exceeds 140°C (typical) the device goes into thermal shutdown. In this
mode, the High Side and Low Side MOSFETs are turned-off. The device continues its operation when the
junction temperature falls below the thermal shutdown hysteresis.
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APPLICATION INFORMATION
L1
2.2 mH
VOUT 1.2 V
TPS62262DRV
Up to 600 mA
VIN = 2 V to 6 V
VIN
SW
COUT
CIN
EN
10 mF
4.7 mF
FB
GND
MODE
Figure 35. Fixed 1.2-V Output
TPS62260DRV
L1
2.2 mH
VOUT 1.2 V
VIN
SW
FB
C1
R1
COUT
CIN
EN
22 pF
360 kW
10 mF
4.7 mF
GND
MODE
R2
360 kW
Figure 36. Adjustable 1.2-V Output
TPS62260DRV
L1
VOUT 1.5 V
VIN = 2 V to 6 V
2.2 mH
Up to 600 mA
VIN
SW
FB
R1
540 kΩ
C1
22 pF
CIN
EN
4.7 mF
COUT
10 mF
GND
MODE
R2
360 kΩ
Figure 37. Adjustable 1.5-V Output
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SLVSA16C –AUGUST 2009–REVISED JULY 2012
VOUT 1.8 V
L1
2.2 mH
TPS62261DRV
VIN = 2 V to 6 V
Up to 600 mA
VIN
SW
CIN
EN
4.7 mF
COUT
FB
10 mF
GND
MODE
Figure 38. Fixed 1.8-V Output
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OUTPUT VOLTAGE SETTING
The output voltage can be calculated to:
R
1
ǒ1 ) Ǔ
V
+ V
OUT
REF
R
2
with an internal reference voltage VREF typical 0.6V.
To minimize the current through the feedback divider network, R2 should be 180 kΩ or 360 kΩ. The sum of R1
and R2 should not exceed ~1MΩ, to keep the network robust against noise. An external feed forward capacitor
C1 is required for optimum load transient response. The value of C1 should be in the range between 22pF and
33pF.
Route the FB line away from noise sources, such as the inductor or the SW line.
OUTPUT FILTER DESIGN (INDUCTOR AND OUTPUT CAPACITOR)
The TPS6226x is designed to operate with inductors in the range of 1.5μH to 4.7μH and with output capacitors in
the range of 4.7μF to 22μF. The part is optimized for operation with a 2.2μH inductor and 10μF output capacitor.
Larger or smaller inductor values can be used to optimize the performance of the device for specific operation
conditions. For stable operation, the L and C values of the output filter may not fall below 1μH effective
inductance and 3.5μF effective capacitance.
Inductor Selection
The inductor value has a direct effect on the ripple current. The selected inductor has to be rated for its dc
resistance and saturation current. The inductor ripple current (ΔIL) decreases with higher inductance and
increases with higher VI or VO.
The inductor selection has also impact on the output voltage ripple in PFM mode. Higher inductor values will lead
to lower output voltage ripple and higher PFM frequency, lower inductor values will lead to a higher output
voltage ripple but lower PFM frequency.
Equation 1 calculates the maximum inductor current in PWM mode under static load conditions. The saturation
current of the inductor should be rated higher than the maximum inductor current as calculated with Equation 2.
This is recommended because during heavy load transient the inductor current will rise above the calculated
value.
V
OUT
1 *
V
IN
DI + V
L
OUT
L f
DI
(1)
(2)
L
I max + I max )
out
L
2
With:
f = Switching Frequency (2.25MHz typical)
L = Inductor Value
ΔIL = Peak to Peak inductor ripple current
ILmax = Maximum Inductor current
A more conservative approach is to select the inductor current rating just for the switch current limit ILIMF of the
converter.
Accepting larger values of ripple current allows the use of lower inductance values, but results in higher output
voltage ripple, greater core losses, and lower output current capability.
The total losses of the coil have a strong impact on the efficiency of the DC/DC conversion and consist of both
the losses in the dc resistance (R(DC)) and the following frequency-dependent components:
•
•
•
•
The losses in the core material (magnetic hysteresis loss, especially at high switching frequencies)
Additional losses in the conductor from the skin effect (current displacement at high frequencies)
Magnetic field losses of the neighboring windings (proximity effect)
Radiation losses
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SLVSA16C –AUGUST 2009–REVISED JULY 2012
Table 2. List of Inductors
DIMENSIONS [mm3]
2.5x2.0x1.0max
2.5x2.0x1.2max
2.5x2.0x1.0max
2.5x2.0x1.2max
3x3x1.5max
Inductance μH
INDUCTOR TYPE
SUPPLIER
FDK
2.0
2.0
2.2
2.2
2.2
MIPS2520D2R2
MIPSA2520D2R2
KSLI-252010AG2R2
LQM2HPN2R2MJ0L
LPS3015 2R2
FDK
Htachi Metals
Murata
Coilcraft
Output Capacitor Selection
The advanced fast-response voltage mode control scheme of the TPS6226x allows the use of tiny ceramic
capacitors. Ceramic capacitors with low ESR values have the lowest output voltage ripple and are
recommended. The output capacitor requires either an X7R or X5R dielectric. Y5V and Z5U dielectric capacitors,
aside from their wide variation in capacitance over temperature, become resistive at high frequencies.
At nominal load current, the device operates in PWM mode and the RMS ripple current is calculated as:
V
OUT
1 *
V
IN
1
I
+ V
RMSC
OUT
Ǹ
L f
2 3
OUT
(3)
At nominal load current, the device operates in PWM mode and the overall output voltage ripple is the sum of the
voltage spike caused by the output capacitor ESR plus the voltage ripple caused by charging and discharging the
output capacitor:
V
OUT
1 *
V
IN
1
ǒ
) ESRǓ
DV
+ V
OUT
OUT
L f
8 Cout f
(4)
At light load currents, the converter operates in Power Save Mode and the output voltage ripple is dependent on
the output capacitor and inductor value. Larger output capacitor and inductor values minimize the voltage ripple
in PFM mode and tighten DC output accuracy in PFM mode.
Input Capacitor Selection
An input capacitor is required for best input voltage filtering, and minimizing the interference with other circuits
caused by high input voltage spikes. For most applications, a 4.7μF to 10μF ceramic capacitor is recommended.
Because ceramic capacitor loses up to 80% of its initial capacitance at 5 V, it is recommended that 10μF input
capacitors be used for input voltages > 4.5V. The input capacitor can be increased without any limit for better
input voltage filtering. Take care when using only small ceramic input capacitors. When a ceramic capacitor is
used at the input and the power is being supplied through long wires, such as from a wall adapter, a load step at
the output or VIN step on the input can induce ringing at the VIN pin. This ringing can couple to the output and
be mistaken as loop instability or could even damage the part by exceeding the maximum ratings.
Table 3. List of Capacitors
CAPACITANCE
4.7 μF
TYPE
SIZE
SUPPLIER
Murata
GRM188R60J475K
GRM188R60J106M69D
0603 1.6x0.8x0.8mm3
0603 1.6x0.8x0.8mm3
10 μF
Murata
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LAYOUT CONSIDERATIONS
Figure 39. Suggested Layout for Fixed Output Voltage Options
VOUT
GND
C1
R1
VIN
C
OUT
L
U
Figure 40. Suggested Layout for Adjustable Output Voltage Version
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SLVSA16C –AUGUST 2009–REVISED JULY 2012
As for all switching power supplies, the layout is an important step in the design. Proper function of the device
demands careful attention to PCB layout. Care must be taken in board layout to get the specified performance. If
the layout is not carefully done, the regulator could show poor line and/or load regulation, stability issues as well
as EMI problems. It is critical to provide a low inductance, impedance ground path. Therefore, use wide and
short traces for the main current paths. The input capacitor should be placed as close as possible to the IC pins
as well as the inductor and output capacitor.
Connect the GND Pin of the device to the PowerPAD™ land of the PCB and use this pad as a star point. Use a
common Power GND node and a different node for the Signal GND to minimize the effects of ground noise.
Connect these ground nodes together to the PowerPAD land (star point) underneath the IC. Keep the common
path to the GND PIN, which returns the small signal components and the high current of the output capacitors as
short as possible to avoid ground noise. The FB line should be connected right to the output capacitor and routed
away from noisy components and traces (e.g., SW line).
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Product Folder Link(s): TPS62260-Q1 TPS62261-Q1 TPS62262-Q1 TPS62263-Q1
TPS62260-Q1, TPS62261-Q1
TPS62262-Q1, TPS62263-Q1
SLVSA16C –AUGUST 2009–REVISED JULY 2012
www.ti.com
REVISION HISTORY
Changes from Revision B (February, 2011) to Revision C
Page
•
Added extra row in ordering information table. ..................................................................................................................... 2
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Copyright © 2009–2012, Texas Instruments Incorporated
Product Folder Link(s): TPS62260-Q1 TPS62261-Q1 TPS62262-Q1 TPS62263-Q1
PACKAGE OPTION ADDENDUM
www.ti.com
13-Jul-2012
PACKAGING INFORMATION
Status (1)
Eco Plan (2)
MSL Peak Temp (3)
Samples
Orderable Device
Package Type Package
Drawing
Pins
Package Qty
Lead/
Ball Finish
(Requires Login)
TPS62260IDRVRQ1
TPS62260TDRVRQ1
TPS62261TDRVRQ1
TPS62262TDRVRQ1
TPS62263TDRVRQ1
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
SON
SON
SON
SON
SON
DRV
DRV
DRV
DRV
DRV
6
6
6
6
6
3000
3000
3000
3000
3000
Green (RoHS
& no Sb/Br)
CU NIPDAU Level-2-260C-1 YEAR
Green (RoHS
& no Sb/Br)
CU NIPDAU Level-2-260C-1 YEAR
CU NIPDAU Level-2-260C-1 YEAR
CU NIPDAU Level-2-260C-1 YEAR
CU NIPDAU Level-2-260C-1 YEAR
Green (RoHS
& no Sb/Br)
Green (RoHS
& no Sb/Br)
Green (RoHS
& no Sb/Br)
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
13-Jul-2012
OTHER QUALIFIED VERSIONS OF TPS62260-Q1, TPS62261-Q1, TPS62262-Q1, TPS62263-Q1 :
Catalog: TPS62260, TPS62261, TPS62262, TPS62263
•
NOTE: Qualified Version Definitions:
Catalog - TI's standard catalog product
•
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
13-Jul-2012
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
TPS62260IDRVRQ1
TPS62260TDRVRQ1
TPS62261TDRVRQ1
TPS62262TDRVRQ1
TPS62263TDRVRQ1
SON
SON
SON
SON
SON
DRV
DRV
DRV
DRV
DRV
6
6
6
6
6
3000
3000
3000
3000
3000
179.0
179.0
179.0
179.0
179.0
8.4
8.4
8.4
8.4
8.4
2.2
2.2
2.2
2.2
2.2
2.2
2.2
2.2
2.2
2.2
1.2
1.2
1.2
1.2
1.2
4.0
4.0
4.0
4.0
4.0
8.0
8.0
8.0
8.0
8.0
Q2
Q2
Q2
Q2
Q2
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
13-Jul-2012
*All dimensions are nominal
Device
Package Type Package Drawing Pins
SPQ
Length (mm) Width (mm) Height (mm)
TPS62260IDRVRQ1
TPS62260TDRVRQ1
TPS62261TDRVRQ1
TPS62262TDRVRQ1
TPS62263TDRVRQ1
SON
SON
SON
SON
SON
DRV
DRV
DRV
DRV
DRV
6
6
6
6
6
3000
3000
3000
3000
3000
195.0
195.0
195.0
195.0
195.0
200.0
200.0
200.0
200.0
200.0
45.0
45.0
45.0
45.0
45.0
Pack Materials-Page 2
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