PWR-82520-300W中文资料_数据手册_规格书

PWR-82520

3-PHASE DC MOTOR TORQUE

CONTROLLER

DESCRIPTION

FEATURES

The PWR-82520 is a high-perfor-

mance current-regulating torque loop

controller. It is designed to accurate-

ly regulate the current in the windings

of 3-phase brushless DC and brush

DC motors.

PWR-82520 can be tuned by using

100V Rating for 28V Motors

•

an external Proportional-Integral (PI)

regulator network in conjunction with

the internal error amplifier.

10 Amp Continuous Output Current

Complementary Four-Quadrant

Operation

APPLICATIONS

3% Linearity Accuracy

•

Packaged in a small DIP-style hybrid,

the PWR-82520 are ideal for applica-

tions with limited printed circuit board

area.

The PWR-82520 is a completely self-

contained motor controller that con-

verts the analog input command sig-

nal into motor current and uses the

signals from Hall-effect sensors in the

motor to commutate the current in the

motor windings. The motor current is

internally sensed and processed into

an analog signal. This signal is

summed together with the command

signal to produce an error signal that

controls the pulse width modulation

(PWM) duty cycle of the output, thus

controlling the motor current. The

5% Current Regulating Accuracy

User-Programmable Compensation

10 kHz - 50 kHz PWM Frequency

The PWR-82520 is ideal for applica-

tion requiring current regulation

and/or holding torque at zero input

Operates as Current or Voltage

Controller

Self-Contained 3-Phase Motor

Controller

•

command.

System applications

include flight surface control on air-

craft for horizontal stabilizers and

flaps, missile fin control, fuel and

hydraulic pumps, radar and counter-

measures systems.

Built-in Current Limit

5.0V

10K 10K 10K

39

HA

HALL A

38

HB

COMMUTATION

HALL B

LOGIC

37

HC

HALL C

40

+15V HALL SUPPLY OUTPUT

41

+15V

SUPPLY GND

HALL

33

VBUS+

4,5,6

COMMAND OUT

10K

DRIVE

A

10K

31

30

PHASE

A

+

-

COMMAND IN

-

100

PHASE

A

14,15,16

+

COMMAND

BUFFER

10K

29

17

COMMAND GND

CASE GND

5.0V

10K

DRIVE

B

PWM

LOGIC

CIRCUITRY

PHASE

B

CASE

PHASE

7,8,9

B

36

28

27

ENABLE

+15V SUPPLY

GROUND

VDD

VEE

+

26

19

DRIVE

C

-15V SUPPLY

PWM IN

C

PHASE

1,2,3

C

20

22

PWM OUT

SYNC IN

100

21

32

34

PWM GND

ERROR AMP OUT

IS+

10

ERROR AMP IN

-

100

Rsense

CURRENT

AMP

+

ERROR

AMPLIFIER

VBUS–

11,12,13

CURRENT

MONITOR OUT

90.9

35

-

+

FIGURE 1. PWR-82520 BLOCK DIAGRAM

1994, 1999 Data Device Corporation

©

TABLE 1. ABSOLUTE MAXIMUM RATINGS (TC = +25°C UNLESS OTHERWISE SPECIFIED)

PARAMETER

Bus Voltage

SYMBOL

VBUS+

V_DD

VALUE

100

UNITS

VDC

A

+15V Supply

+17.5

-17.5

10

V_EE

-15V Supply

Continuous Output Current

Peak Output Current

Command input +

Command input -

I

OC

I

15

A

PEAK

Command input+

Command input-

±15

VDC

±15

ENABLE

HA, HB, HC

Logic inputs

Sync Input

7.0

VDC

SYNC

±15.0

TABLE 2. PWR-82520 SPECIFICATIONS

(Unless otherwise specified, VBUS = 28 VDC, V_DD= +15V, V_EE= -15V, T_C= 25°C)

VALUE

PARAMETERS

SYMBOL

TEST CONDITIONS

UNITS

MIN

TYP

MAX

OUTPUT

Output Current Continuous

Output Current Pulsed

Current Limit

I_OC(note 1)

I_OP

I_CL

I_OFFSET

R_ON(note 2, 3)

10

14

15.4

+0.3

0.040

0.055

A

12.0

-0.3

14.0

-

Current Offset

VDF = 0V

+25°C

+85°C

A

Output On-Resistance

Output Conductor Resistance

Load Inductance

Ω

µH

R

L_MIN

+85°C

note 3

C

100

COMMAND IN+/-

Differential Input

V_DIF

-10

+10

VDC

COMMAND OUT

Internal Voltage Clamp

V_CLMP

-11.5

+11.5

CURRENT COMMAND

Transconductance ratio

Non-Linearity

G

0.95

-3.0

1.0

1.05

+3.0

A/V

%

See FIGURE 9

CURRENT MONITOR AMP

Current Monitor Gain

Current Monitor Offset

Output Current

0.97

-0.1

-10

1.0

0

1.03

0.1

10

V/A

VDC

mA

Ω

VDF = 0V

Output Resistance

R_OUT

100

VBUS+ SUPPLY

Nominal Operating Voltage

V_NOM

+18

+28

+70

VDC

VBUS- To PWM GND

Voltage differential

V_GNDDIF

0.250

+15 VDC

Voltage

Current

V_S+

I +

+14.25

-15.75

+15.0

100

+15.75

150

VDC

mA

-15 VDC

Voltage

Current

V_S-

I -

-15.0

80

-14.25

150

VDC

mA

SYNC (Note 2)

Voltage

Pulse Width

Sync range as % of free-run

frequency

±7.5

130

0

V

ns

%

See FIGURE 7

+20

Note:

1) I_OCis average current as measured in motor winding

2) Guaranteed by design, not tested.

3) The maximum output conductor resistance and on-resistance of FETs at +85°C are:

ΦA_U= 0.20Ω, ΦA_L= 0.16Ω, ΦB_U= 0.08Ω, ΦB_L= 0.08Ω, ΦC_U= 0.08Ω, ΦC_L= 0.20Ω

2

TABLE 2. PWR-82520 SPECIFICATIONS (CONTINUED)

(Unless otherwise specified, VBUS = 28 VDC, V_DD= +15V, V_EE= -15V, T_C= 25°C)

VALUE

PARAMETERS

PWM IN

SYMBOL

TEST CONDITIONS

UNITS

MIN

TYP

MAX

+Peak

-Peak

Frequency

Non -linearity

Duty Cycle

V_P+

V_P-

f

9.8

-10.2

10

-2

49

10.0

-10.0

10.2

-9.8

60

+2

51

V

KHz

%

LIN

D CYCLE

50

%

PWM OUT

Free Run Frequency

45

55

50

KHz

mA

HALL POWER SUPPLY

Max Current Draw

I_MDRW

HALL SIGNALS

Logic 1

Logic 0

HA, HB,

HC

3.5

—

0.7

VDC

ENABLE INPUT

Enabled

ENABLE

—

0.7

Disabled

3.5

—

VDC

ISOLATION

CASE to PIN

500 VDC HIPOT

10

MΩ

SWITCHING CHARACTERISTICS

Upper drive

125

200

ns

Turn-on Rise Time

Turn-off Fall Time

Lower drive

Turn-on Rise Time

Turn-off Fall Time

Diode Forward Voltage Drop

tr

tf

Ip = 4 A

ID = 1A

200

1.25

ns

V

tr

tf

VF

PROPAGATION DELAY

Ip = 4A

Td (on)

Td (off)

From 0.7V on ENABLE

to 10% of VOUT

From 3.5V on ENABLE

to 90% of VOUT

40

20

µs

THERMAL

Thermal Resistance

Junction - Case

Case - Air

Junction Temperature

Case Operating Temperature

Case Storage Temperature

6

10

+175

+125

+150

°C/W

°C

θ_J-C

θ_C-A

T_J

T_C

T_CS

-55

-65

WEIGHT

1.7(48)

oz(gr)

over the operating temperature range and the total error due to

all the factors such as offset, initial component accuracies etc. is

maintained well below 5% of the rated output current.

INTRODUCTION

The PWR-82520 is high performance current control (torque

loop) hybrid which use complementary four quadrant switching

topology (See BASIC OPERATION) to provide linearity through

zero current. The high Pulse Width Modulation (PWM) switching

frequency makes it suitable for even low inductance motors. The

PWR-82520 hybrid can accept single-ended or differential mode

command signals. The current gain can be easily programmed

to match the end user system requirements. With the compen-

sation network externally wired, the hybrid can provide optimum

control of a wide range of loads.

The Hall sensor interface for current commutation has built-in

decoder logic that separates illegal codes and ensures that there

is no cross conduction. The hybrid also has a +15V supply out-

put for powering the Hall sensors. The Hall sensor inputs are

internally pulled up to +5V and they can be driven from open-col-

lector outputs.

The PWM frequency can be programmed externally by adding a

capacitor from PWM OUT to PWM GND. In addition, multiple

PWR-82520’s can be synchronized by using one device as a

master and connecting its PWM OUT pin to the PWM IN of all

the other slave devices in a system or by applying a SYNC pulse

to pin 22.

The PWR-82520 uses unique current sense technology and a

non-inductive hybrid sense resistor which yields a highly linear

current output over the wide military temperature range (see

FIGURE 9). The output current non-linearity is better than 3%

3

The ENABLE input signal provides quick start and shutdown of

the output power switches. In addition, built-in power sequence

fault protection turns off the output in case of low power supply

voltages.

VBUS

The hybrid features dual current limiting functions. The input

command amplifier output is limited to 10.8V thus limiting the

current under normal operation. In addition, there is a built in

over current limit which trips at 14 Amps, protecting the hybrid as

well as the load.

PHASE A

UPPER

PHASE B

UPPER

ON

OFF

I

PHASE A

PHASE B

-

+

BASIC OPERATION

PHASE C

PHASE A

LOWER

PHASE B

LOWER

The PW-82520 utilizes a complimentary four-quadrant drive

technique to control current in the load. The complimentary

drive has the following advantages over the standard drive:

OFF

ON

1. Maximum holding torque and position accuracy

2. Linear current control through zero

3. No deadband at zero

Rsense

The complementary drive design uses a 50% PWM duty cycle

for a zero command signal. For a zero input command, a pair of

MOSFETs are turned on in the drive, Phase A upper & Phase B

lower as shown in FIGURE 2A, to supply current into the load for

the first half of the PWM cycle. This is the same mode of oper-

ation for the standard four-quadrant drive as shown in FIGURE

3A/B. During the second half of the PWM cycle, a second pair

of transistors are turned on, Phase A lower & Phase B upper as

shown in FIGURE 2B, for the flyback current and to provide load

current in the opposite direction.

FIGURE 2A. COMPLEMENTARY FOUR-QUANDRANT

DRIVE FIRST HALF OF PWM CYCLE

This is normally the dead time for standard four-quadrant drive

as shown in FIGURE 3B. The result is current flowing in both

directions in the motor for each PWM cycle. The advantage this

has over standard four-quadrant drive is that at 50% duty cycle,

which corresponds to zero average current in the motor, holding

torque is provided. The motor current at 50% duty cycle is sim-

ply the magnetizing current of the motor winding.

VBUS

Using the complimentary four-quadrant technique allows the

motor direction to be defined by the duty cycle. Relative to a

given switch pair i.e., Phase A upper and Phase B lower, a duty

cycle greater than 50% will result in a clockwise rotation where-

as a duty cycle less than 50% will result in a counter clockwise

rotation. Therefore, with the use of average current mode con-

trol, direction can be controlled without the use of a direction bit

and the current can be controlled through zero in a very precise

and linear fashion.

PHASE A

UPPER

PHASE B

UPPER

OFF

ON

I

PHASE A

PHASE B

+

_

PHASE C

PHASE A

LOWER

PHASE B

LOWER

ON

OFF

The PW-82520 contains all the circuitry required to close an

average current mode control loop around a complimentary four-

quadrant drive. The PWR-82520 use of average current mode

control simplifies the control loop by eliminating the need for

slope compensation and eliminating the pole created by the

motor inductance. These two effects are normally associated

with 50% duty cycle limitations when implementing standard

peak current mode control.

Rsense

FIGURE 2B. COMPLEMENTARY FOUR-QUADRANT DRIVE

SECOND HALF OF PWM CYCLE

4

FUNCTIONAL AND PIN DESCRIPTIONS:

V

BUS

COMMAND IN+, COMMAND IN- (Pins 30 & 31)

The command amplifier has a differential input that operates

from a ±10 V analog current command. The differential input

voltage may vary between ±10 VDC, maximum, corresponding

to ±maximum voltage or current for the output. Either input

(COMMAND IN + or COMMAND IN-) may be referenced to the

command ground (Pin 29) and the other input varied from ±10

VDC to obtain full output. The COMMAND OUT signal is inter-

nally limited to approximately ±11.5 VDC; that is, inputs above or

below ±11.5 VDC will be clamped to ±11.5 VDC. The input

impedance of the Command Amplifier is 10K Ohms.

PHASE A

UPPER

PHASE B

UPPER

ON

OFF

I

PHASE A

PHASE B

-

+

PHASE C

The PWR-82520 can be used either as a current or voltage

mode controller. When the PWR-82520 is used as a torque

amplifier (current mode) as shown in FIGURE 13, the transfer

function of the command amplifier is 1.0 A/V. The input com-

mand signal is processed through the command buffer. The out-

put of the buffer (COMMAND OUT) is summed with the current

monitor output into the error amplifier. When external compen-

sation is used on the error amp, as shown in FIGURE 6A, the

response time can be adjusted to meet the application.

PHASE A

LOWER

PHASE B

LOWER

OFF

ON

Rsense

When used in the voltage mode the Voltage Command uses the

same differential input terminals to control the voltage applied to

the motor (see FIGURE 12). The error amp directly varies the

PWM duty cycle of the voltage applied to the motor phase. The

transfer function in the voltage mode is 4.7% /V ±5% variation of

the PWM duty cycle vs. input command. The duty cycle range of

the output voltage is limited to approximately 5-95% in both cur-

rent and voltage modes.

FIGURE 3A. STANDARD FOUR QUANDRANT DRIVE FIRST

HALF OF PWM CYCLE

TRANSCONDUCTANCE RATIO AND OFFSET

VBUS

When the PWR-82520 is used in the Current Mode, the com-

mand inputs (COMMAND IN+ and COMMAND IN-) are designed

such that ±10 VDC on either input, with the other input connect-

ed to Ground, will result in ±10 DC Average Amperes of current

into the load. The DC current transfer ratio accuracy is ±5% of

the rated output current. The initial output DC current offset with

both COMMAND IN+ and COMMAND IN- tied to the Ground will

be less than 100 mA when measured using a load of 0.5 mH and

1.0 Ohms at room ambient with standard current loop compen-

sation (see FIGURE 6A). The winding phase current error shall

be within the cumulative limits of the transconductance ratio

error and the offset error.

PHASE A

UPPER

PHASE B

UPPER

OFF

PHASE A

PHASE B

+

_

I

Flyback

PHASE C

PHASE A

LOWER

PHASE B

LOWER

HALL A,B,C SIGNALS (Pins 37, 38 and 39)

OFF

These are logic signals from the motor Rotor Position Sensors

(HA, HB, HC). They use a phasing convention referred to as 120

degree spacing; that is, the output of HA is in phase with motor

back EMF voltage VAB, HB is in phase VBC, and HC is in phase

with VCA. Logic “1” (or HIGH) is defined by an input greater than

3.5 VDC or an open circuit to the controller; Logic “0” (or LOW)

is defined as any Hall voltage input less than 0.7 VDC. Internal

to the PWR-82520 are 5K pull-up resistors tied to +5 VDC on

each Hall input.

Rsense

The PWR-82520 will operate with Hall phasing of 60° or 120°

electrical spacing. If 60° commutation is used, then the output of

FIGURE 3B. STANDARD 4 QUANDRANT DRIVE SECOND

HALF OF PWM CYCLE

5

HC must be inverted as shown in FIGURES 4 and 5. In FIGURE 4,

the Hall sensor outputs are shown with the corresponding volt-

age they are in phase with.

HALL-EFFECT SENSOR PHASING vs.

MOTOR BACK EMF FOR CW ROTATION (120° Commutations)

300°

60°

180°

300°

360°/0°

0°

120°

240°

60°

V_AB

V_BC

V_CA

BACK EMF

OF MOTOR

ROTATING

CW

Hall Input Signal Conditioning: When the motor is located

more than two feet away from the PWR-82520 controller the Hall

inputs require filtering from noise. It is recommended to use a

1 kΩ resistor in series with the Hall signal and a 2000 pF capac-

itor from the Hall input pin to the Hall supply ground pin as shown

in FIGURE 12 and 13.

CW

COMPENSATION

In Phase

with V_AB

The PI regulator in the PWR-82520 can be tuned to a specific

load for optimum performance. FIGURE 6A shows the standard

current loop configuration and tuning components, and FIGURE

6B shows the frequency response for the PI regulator. By adjust-

ing R1, R2 and C1, the amplifier can be tuned. The value of R1,

C1 will vary, depending on the loop bandwidth requirement.

HA

In Phase

with V_BC

HB

HC

In Phase

with V_CA

In Phase

with V_AC

(60˚)

HC

EXTERNAL PI REGULATOR

FIGURE 4. HALL PHASING

10.0 K

R1

4700 pF

C1

1 MEG

R7

HA

120°

ERROR

AMP INPUT

32

N

S

470 pf

34

ERROR

AMP OUT

-

R2B

R2A

O

10.0 K

+

HC

HB

COMMAND

OUT

33

35

CURRENT

MONITOR OUT

REMOTE POSITION SENSOR (HALL) SPACING FOR

120 DEGREE COMMUTATION

FIGURE 6A. STANDARD PI CURRENT LOOP

60°

200

120°

HA

100

HC

A, dB

S

N

0

60°

-100

HC

HB

180

θ, degree

REMOTE POSITION SENSOR (HALL) SPACING FOR

60 DEGREE COMMUTATION

90

0

1.0KHz

10KHz

FREQUENCY

100Hz

100MHz

10Hz

100KHz

1.0MHz

10MHz

FIGURE 5. HALL SENSOR SPACING

FIGURE 6B. PI REGULATOR FREQUENCY RESPONSE

6

(

)

ENABLE Pin 36

SYNC PERIOD

This is a logic input to the controller that enables or disables the

controller. In the disabled state, no voltage shall be applied to the

motor phases. The disabled state occurs when the Enable input

is greater than 3.5 VDC or is left open; to enable the controller,

this input must be pulled to less than 0.7 VDC. The Enable input

has a 10K pull-up resistor tied to +5 VDC.

+7.5V

-7.5V

VBUS+ (Pins 4, 5 and 6)

130ns

The VBUS+ supply is the power source for the motor phases and

is nominally +28 VDC. The normal operating voltage may actu-

ally vary from +18 to +48 VDC with respect to Vbus-. The power

stage MOSFETS in the hybrid have an absolute maximum

VBUS+ Supply voltage rating of 100V. The recommended oper-

ating voltage must not exceed +70 VDC, and is subject to the

safe operating curve within FIGURE 10. The user must supply

sufficient external capacitance or circuitry to prevent the bus

supply from exceeding +70 VDC at the hybrid power terminals

under any conditions.

FIGURE 7. SYNC INPUT SIGNAL

PWM FREQUENCY

The PWM frequency from the PWM OUT pin will free-run at a

frequency of 50 kHz ±10 kHz. The user can adjust this frequen-

cy down to 10 kHz through the addition of an external capacitor.

The PWM triangle wave generated internally is brought out to

the PWM OUT pin. This output, or an external triangle waveform

generated by the user, may be connected to PWM IN on the

hybrid.

The VBUS should be applied at least 50 ms after ±15 VDC to

allow the internal analog circuitry to stabilize. If this is not possi-

ble, the hybrid must be powered up in the “disabled” mode.

VBUS- (Pins 11, 12, and 13)

WARNING: Never apply power to the hybrid without connect-

ing either PWM OUT or an external triangular wave to PWM IN!

Failure to do so may result in one or more outputs latching on.

This is the high current ground return for VBUS+. This point

must be externally connected to Ground for proper operation of

the current loop. The voltage difference between Vbus- and the

Ground connections must be less than 0.250 VDC including

transients.

PWM OUT (Pin 20)

This is the output of the internally generated PWM triangle wave

form. It is normally connected to PWM In. The frequency of this

output may be lowered by connecting an NPO capacitor (Cext)

between PWM OUT and PWM GND. The typical PWM frequen-

cy is determined by the following formula:

GROUNDS

SUPPLY GND (Pin 27): This is the return line for the ±15 VDC

supplies. The phase current sensing technique of the

PWR-82520 requires that VBUS- and Supply Ground be con-

nected together externally (see VBUS- supply).

16.5E-6

PWM GND (Pin 21): This is used for the return side of the exter-

nal PWM capacitor (Cext) when switching frequencies below

50 KHz are required.

330 pF + C_EXTpF

COMMAND GND (Pin 29): This is used when the command

buffer is used single-ended and the COMMAND IN- or COM-

MAND IN+ are tied to COMMAND GND.

CASE (Pin 17)

This pin is internally connected to the hybrid case. In some appli-

cations the user may want to tie Pin 17 to Ground for EMI con-

siderations.

HALL GND (Pin 41): This is used for the return of the +15V HALL

supply and should be tied to SUPPLY GROUND.

PHASES A, B, C (Pin A 14-16, B 7-9, C 1-3)

±15 VDC (+15V Supply, Pin 28 / -15V Supply, Pin 26)

These inputs are used to power the small signal analog and dig-

ital circuitry of the hybrid. An internal +5 VDC supply is derived

from the +15 VDC source. These inputs should not vary more

than ±5%, maximum. The absolute maximum voltage ratings of

these inputs are ±17.5 VDC. Reversal of the power supplies

will result in destruction of the hybrid.

These are the power drive outputs to the motor and switch

between VBUS+ Input and VBUS- Input or become high imped-

ance - see TABLE 3.

+15 VDC HALL SUPPLY OUTPUT (Pin 40)

SYNC IN (Pin 22)

This output provides power to the Hall Sensors in the motor.

Maximum current drawn from this supply by the user must not

exceed 50 mA.

The Sync pulse, as shown in FIGURE 7, can be used to syn-

chronize the switching frequency up to 20% faster than the free

running frequency of all th slave devices.

7

TABLE 3. COMMUTATION TRUTH TABLE

6

5

INPUTS

OUTPUTS

VBUS+

+28V

4

PHASE A PHASE B PHASE C

ENABLE DIR ** HA

HB

0

HC

0

16

15

14

9

PHASE

A

PHASE

A

B

C

CW

1

0

1

0

1

—

L

H

Z

L

Z

H

Z

L

Z

L

1

0

8

PHASE

7

CW

1

0

L

3

PHASE

C

2

CW

1

Z

H

L

1

13

12

11

CW

0

1

L

VBUS-

GND

CW

0

1

Z

H

Z

L

39

38

37

41

40

HALL A

HALL B

HALL C

+5V

CCW

—

0

1

H

Z

L

0

1

L

1

Z

H

Z

HALL SUPPLY GND

1

0

L

+15V HALL SUPPLY OUT

1

0

Z

H

Z

0

L

—

Z

FIGURE 8. BRUSH MOTOR HOOK UP

OUTPUT CURRENT

1=Logic Voltage >3.5 VDC, 0=Logic voltage < 0.7 VDC

** DIR is based on the convention shown in Figure 4. Actual

motor set up might be different.

Output current derating as a function of the hybrid case temper-

ature is provided in FIGURE 10. The hybrid contains internal

pulse by pulse current limit circuitry to limit the output current dur-

ing fault conditions.(See TABLE 2) Current Limit accuracy is

+10/-15%.

CURRENT MONITOR OUT (Pin 35)

This is a bipolar analog output voltage representative of motor

current. The Current Monitor Output will have the same scaling

as the Current Command input, 1.0 V/A. The output resistance

will be less than 100 Ω.

WARNING: The PWR-82520 does not have short circuit pro-

tection. The PWR-82520 must see a minimum of 100uH

inductive load or enough line-to-line resistance to limit the

output current to <10A at all times. Operation into a short or

a condition that requires excessive output current will damage

the hybrid.

BRUSH MOTOR OPERATION

The PWR-82520 can also be used as a brush motor controller

for current or voltage control in an H-Bridge configuration. The

PWR-82520 would be connected as shown in FIGURE 8. All

other connections are as shown in either FIGURE 12 or 13

depending on current or voltage mode operation. The Hall inputs

are wired per TABLE 4. A positive input command will result in

positive current to the motor out of Phase A.

THERMAL OPERATION

It is recommended the PWR-82520 be mounted to a heat sink.

This heat sink shall have the capacity to dissipate heat generat-

ed by the hybrid at all levels of current output, up to the peak

limit, while maintaining the case temperature limit as per FIG-

URE 10.

10

TABLE 4. HALL INPUTS FOR H-BRIDGE CONTROLLER

INPUT

OUTPUT

5

Accuracy = ± 5% (of

rated output)

Current

COMMAND

IN

ENABLE

HA

HB

HC PH A PH B PH C

0

(Amps)

L

Positive

Negative

—

1

0

H

L

Z

L

H

Z

-5

H

Z

-10

-8

-6

-4

-2

0

2

4

6

8

10

Input Command (Volt), Inductive Load

FIGURE 9. LINEARITY CURVE

8

11

10

9

8

28V,

Cont. Cur.

7

6

42V,

Cont. Cur.

5

4

70V,

3

Cont. Cur.

2

1

0

-60

-40

-20

0

20

40

60

80

100

120

140

Case Temperature (°C)

FIGURE 10. MOTOR CURRENT DRIVE

2. Switching Losses (Ps)

PWR-82520 POWER DISSIPATION (SEE FIGURE 11)

Ps = [ Vcc ( IOA (ts1) + IOB (ts2) ) fo] / 2

Ps = [ 28 V ( 3 A (125 ns) + 7 A (200 ns) ) 50 kHz] / 2

Ps = 1.24 Watts

There are two major contributors to power dissipation in the

motor driver: conduction losses and switching losses.

VBUS = +28 V (Bus Voltage)

IoA = 3 A, IOB = 7 A (see FIGURE 11)

ton = 36 µs, T = 40 µs (period) (see FIGURE 11)

Ron = 0.055 Ω (on-resistance, see TABLE 2)

Rc = 0.133 Ω (conductor resistance, see TABLE 2,)

ts1 = 125 ns, ts2 = 200 ns (see FIGURE 11)

fo = 50 kHz (switching frequency)

TRANSISTOR POWER DISSIPATION ( P_Q

PQ = PT + Ps

)

PQ = 1.30 + 1.24 = 2.54 Watts

OUTPUT CONDUCTOR DISSIPATION

2

PC = (Imotor rms) x (Rc)

2

PC = (4.87) x (0.133)

PC = 3.15 Watts

1. Transistor Conduction Losses (PC)

2

TRANSISTOR POWER DISSIPATION FOR CONTINUOUS

COMMUTATION

PT = (Imotor rms) x (Ron)

(IOB - IOA)²

ton

PQC = PQ (0.33)

I^{motor rms}=

(IOBIOA +

)( )

3

T

PQC = (2.54) X (0.33)

PQC = 0.84 Watts

(7 - 3)²

3

36

40

I^{motor rms}=

(7 * 3 +

)(

)

TOTAL HYBRID POWER DISSIPATION

P_TOTAL= (P_Q+ P_C) x 2

2

PT = (4.87) x (0.055)

P_TOTAL= (2.54 +3.15) x 2

P_TOTAL= 11.38 Watts

PT = 1.30 Watts

t

on

VBUS

I_OB

I

OA

I_O

t_s1

t_s2

FIGURE 11. OUTPUT CHARACTERISTICS

9

6

5

OPTIONAL

VBUS+

+28V

17

19

20

21

26

27

28

29

30

31

32

33

34

35

36

CASE GND

PWM IN

4

16

15

14

9

PHASE

A

B

PWR-82520

PHASE

A

B

C

PWM OUT

Cext

-15V

GND

+15V

PWM GND

PHASE

8

PHASE

7

+

-15V SUPPLY

SUPPLY GND

+15V SUPPLY

COMMAND GND

3

C

2

1

13

12

11

MOTOR BLDC

VBUS-

GND

-

+

COMMAND IN

-

R4

1K

COMMAND

SIGNAL

HALL A

39

38

37

+

HALL A

HALL B

HALL C

+

R3

1K

HALL B

HALL C

ERROR AMP OUT

COMMAND OUT

R1

R2

1K

470 pF

-

R5

10K

+

ERROR AMP INPUT

CURRENT

MONITOR

OUT

C4

2000pF

C3

2000pF

C5

2000pF

10K

CURRENT MONITOR OUT

ENABLE

HALL SUPPLY GND

41

40

HALL SUPPLY GND

ENABLE

+15V HALL SUPPLY OUTPUT

+15V HALL SUPPLY OUT

FIGURE 12. VOLTAGE CONTROL HOOK-UP

6

OPTIONAL

5

VBUS+

+28V

17

19

20

21

26

27

28

29

30

31

32

33

34

35

36

CASE GND

4

16

15

14

9

PWM IN

PHASE

A

B

PWR-82520

PHASE

A

B

C

PWM OUT

Cext

-15V

PWM GND

PHASE

8

7

-15V SUPPLY

SUPPLY GND

+15V SUPPLY

COMMAND GND

+

3

PHASE

C

GND

+15V

2

1

13

12

11

MOTOR BLDC

VBUS-

GND

-

+

COMMAND IN

-

R4

1K

HALL A

HALL B

HALL C

39

38

37

+

HALL A

HALL B

HALL C

COMMAND

SIGNAL

+

R3

1K

ERROR AMP OUT

COMMAND OUT

R2A

R2

1K

C1

4700pF

470 pF

R1

-

+

10K

R2B

ERROR AMP INPUT

10K

C4

2000pF

C3

2000pF

C5

2000pF

CURRENT MONITOR OUT

ENABLE

HALL SUPPLY GND

+15V HALL SUPPLY OUTPUT

41

40

R7 1MEG

10K

HALL SUPPLY GND

+15V HALL SUPPLY OUT

ENABLE

FIGURE 13. TORQUE CONTROL HOOK-UP

10

TABLE 5. PIN ASSIGNMENTS

FUNCTION FUNCTION

1

41

40

39

38

37

36

35

34

33

32

31

30

29

28

27

26

25

24

23

22

21

20

19

18

17

PHASE C

VBUS +

PHASE B

IS+

HALL SUPPLY GND

+15V HALL SUPPLY OUTPUT

HA

2

29.21

3

4

HB

5

HC

6

ENABLE

7

CURRENT MONITOR OUTPUT

ERROR AMP INPUT

COMMAND OUT

ERROR AMP OUT

COMMAND IN +

COMMAND IN -

COMMAND GND

+15V SUPPLY

SUPPLY GND

-15V SUPPLY

N/C

8

9

10

11

12

13

14

15

16

—

VBUS -

PHASE A

N/C

SYNC

PWM GND

PWM OUT

PWM IN

FIGURE 14. MECHANICAL OUTLINE

N/C

CASE GND

Note:

1. N/C pins have internal connections for factory test purposes.

11

ORDERING INFORMATION

PWR-82520-XX0X

Supplemental Process Requirements:

S = Pre-Cap Source Inspection

L = Pull Test

Q = Pull Test and Pre-Cap Inspection

K = One Lot Date Code

W = One Lot Date Code and PreCap Source

Y = One Lot Date Code and 100% Pull Test

Z = One Lot Date Code, PreCap Source and 100% Pull Test

Blank = None of the Above

Process Requirements:

0 = Standard DDC Processing, no Burn-In (See table below.)

1 = MIL-PRF-38534 Compliant

2 = B*

3 = MIL-PRF-38534 Compliant with PIND Testing

4 = MIL-PRF-38534 Compliant with Solder Dip

5 = MIL-PRF-38534 Compliant with PIND Testing and Solder Dip

6 = B* with PIND Testing

7 = B* with Solder Dip

8 = B* with PIND Testing and Solder Dip

9 = Standard DDC Processing with Solder Dip, no Burn-In (See table below.)

Temperature Grade/Data Requirements:

1 = -55°C to +125°C

2 = -40°C to +85°C

3 = 0°C to +70°C

4 = -55°C to +125°C with Variables Test Data

5 = -40°C to +85°C with Variables Test Data

8 = 0°C to +70°C with Variables Test Data

*Standard DDC Processing with burn-in and full temperature test — see table below.

STANDARD DDC PROCESSING

MIL-STD-883

TEST

METHOD(S)

CONDITION(S)

INSPECTION

SEAL

—

2009, 2010, 2017, and 2032

1014

1010

2001

A and C

TEMPERATURE CYCLE

CONSTANT ACCELERATION

BURN-IN

C

A

1015, Table 1

—

The information in this data sheet is believed to be accurate; however, no responsibility is

assumed by Data Device Corporation for its use, and no license or rights are

granted by implication or otherwise in connection therewith.

Specifications are subject to change without notice.

105 Wilbur Place, Bohemia, New York 11716-2482

For Technical Support - 1-800-DDC-5757 ext. 7420

Headquarters - Tel: (631) 567-5600 ext. 7420, Fax: (631) 567-7358

Southeast - Tel: (703) 450-7900, Fax: (703) 450-6610

West Coast - Tel: (714) 895-9777, Fax: (714) 895-4988

Europe - Tel: +44-(0)1635-811140, Fax: +44-(0)1635-32264

Asia/Pacific - Tel: +81-(0)3-3814-7688, Fax: +81-(0)3-3814-7689

World Wide Web - http://www.ddc-web.com

PRINTED IN THE U.S.A.

C-12/99-1M

12

型号	制造商	描述	价格	文档
PWR-82520-300Y	ETC	Industrial Control IC	获取价格
PWR-82520-300Z	ETC	Industrial Control IC	获取价格
PWR-82520-320	ETC	Industrial Control IC	获取价格
PWR-82520-320K	ETC	Industrial Control IC	获取价格
PWR-82520-320L	ETC	Industrial Control IC	获取价格
PWR-82520-320Q	ETC	Industrial Control IC	获取价格
PWR-82520-320S	ETC	Industrial Control IC	获取价格
PWR-82520-320W	ETC	Industrial Control IC	获取价格
PWR-82520-320Y	ETC	Industrial Control IC	获取价格
PWR-82520-320Z	ETC	Industrial Control IC	获取价格

PWR-82520-300W

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