AD5744BSU [ADI]
Complete, Quad, 14/16-Bit, High Accuracy, Serial Input, Bipolar Voltage Output DAC; 完整的四通道14位/ 16位,高精度,串行输入,双极性电压输出DAC型号: | AD5744BSU |
厂家: | ADI |
描述: | Complete, Quad, 14/16-Bit, High Accuracy, Serial Input, Bipolar Voltage Output DAC |
文件: | 总27页 (文件大小:367K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Complete, Quad, 14/16-Bit, High Accuracy,
Serial Input, Bipolar Voltage Output DAC
i
CMOSTM
Preliminary Technical Data
FEATURES
GENERAꢀ DESCRIPTION
Complete quad 14/16-bit D/A converter
Programmable output range: 10 V, 10.25 V, or 10.5 V
1 ꢀSB max INꢀ error, 1 ꢀSB max DNꢀ error
ꢀow noise : 60 nV/√Hz
The AD5744/64 is a quad, 14/16-bit serial input, voltage output
digital-to analog converter that operates from supply voltages of
1ꢀ ꢁ up to 15 ꢁ. Nominal full-scale output range is 1ꢂ ꢁ,
provided are integrated output amplifiers, reference buffers,
internal reference, and proprietary power-up/power-down
control circuitry. It also features a digital I/O port that may be
programmed via the serial interface, and an analog temperature
sensor. The part incorporates digital offset and gain adjust
registers per channel.
Settling time: 10µs max
Integrated reference buffers
Internal reference, 10 ppm/°C
On-chip temp sensor, 5°C accuracy
Output control during power-up/brownout
Programmable short-circuit protection
Simultaneous updating via ꢀDAC
The AD5744/64 is a high performance converter that offers
guaranteed monotonicity, integral nonlinearity (INL) of 1 LSB,
low noise and 1ꢂ µs settling time and includes an on-chip 5 ꢁ
reference with a reference tempco of 1ꢂ ppm/°C max. During
power-up (when the supply voltages are changing), ꢁout is
clamped to ꢂꢁ via a low impedance path.
CꢀR
Asynchronous
to zero code
Digital offset and gain adjust
ꢀogic output control pins
DSP/microcontroller compatible serial interface
Temperature range:−40°C to +85°C
iCMOS™ Process Technology
The AD5744/64 uses a serial interface that operates at clock rates
of up to 3ꢂ MHz and is compatible with DSP and microcontroller
interface standards. Double buffering allows the simultaneous
updating of all DACs. The input coding is programmable to either
twos complement or Offset binary formats. The asynchronous
clear function clears all DAC registers to either bipolar zero or
zero-scale depending on the coding used. The AD5744/64 is ideal
for both closed-loop servo control and open-loop control
applications. The AD5744/64 is available in a 3ꢀ-lead TQFP
package, and offers guaranteed specifications over the −4ꢂ°C to
+85°C industrial temperature range. See functional block
diagram, Figure 1.
APPꢀICATIONS
Industrial automation
Open/Closed-loop servo control
Process control
Data acquisition systems
Automatic Test Equipment
Automotive test and measurement
High accuracy instrumentation
iCMOS™ Process Technology
For analog systems designers within industrial/instrumentation equipment OEMs who need high performance ICs at higher-voltage levels, iCMOS is a
technology platform that enables the development of analog ICs capable of 30V and operating at +/-15V supplies while allowing dramatic reductions in
power consumption and package size, and increased AC and DC performance.
Rev. PrA
15-Nov-04
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.326.8703
www.analog.com
© 2004 Analog Devices, Inc. All rights reserved.
Preliminary Technical Data
TABLE OF CONTENTS
Functional Block Diagram .............................................................. 3
Coarse gain register.................................................................... ꢀꢂ
Fine gain register ........................................................................ ꢀ1
offset register............................................................................... ꢀ1
AD5744/64 Features....................................................................... ꢀꢀ
Analog Output Control ............................................................. ꢀꢀ
Digital Offset and Gain Control............................................... ꢀꢀ
Programmable Short-Circuit protection................................. ꢀꢀ
Digital I/O Port........................................................................... ꢀꢀ
Temperature Sensor ................................................................... ꢀꢀ
Local ground offset adjust......................................................... ꢀꢀ
applications information ............................................................... ꢀ3
typical operating circuit............................................................. ꢀ3
layout guidelines......................................................................... ꢀ4
Isolated interface ........................................................................ ꢀ4
microprocessor interfacing ....................................................... ꢀ4
Evaluation board ........................................................................ ꢀ6
Outline Dimensions....................................................................... ꢀ7
Ordering Guide .......................................................................... ꢀ7
Specifications..................................................................................... 4
AC Performance Characteristics................................................ 6
Timing Characteristics ................................................................ 7
Absolute Maximum Ratings.......................................................... 1ꢂ
ESD Caution................................................................................ 1ꢂ
Pin Configuration and Function Descriptions........................... 11
Terminology .................................................................................... 13
typical performance characteristics ............................................. 15
General Description....................................................................... 16
dac architecture........................................................................... 16
Reference Buffers........................................................................ 16
Serial interface ............................................................................ 16
LDAC
Simultaneous Updating ꢁia
transfer function......................................................................... 18
CLR
.......................................... 17
Asynchronous Clear (
)....................................................... 18
Function Register ....................................................................... 19
DAta register ............................................................................... ꢀꢂ
REVISION HISTORY
Revision PrA 15-Nov-ꢂ4: Preliminary ꢁersion
Rev. PrA 15-Nov-04| Page 2 of 27
Preliminary Technical Data
FUNCTIONAL BLOCK DIAGRAM
REFGND
PGND AV
AV
AV
AV
SS
VREF AB
RSTOUT
RSTIN
REFOUT
DD
SS
DD
VOLTAGE
MONITOR
AND
DV
CC
+5V
REFERENCE
REFERENCE
BUFFERS
DGND
CONTROL
ISCC
14/16
G1
G1
G1
G1
14/16
INPUT
REG A
DAC
REG A
DAC A
DAC B
DAC C
DAC D
SDIN
SCLK
SYNC
SDO
VOUTA
AGNDA
INPUT SHIFT
REGISTER
AND
CONTROL
LOGIC
G2
GAIN REG A
OFFSET REG A
14/16
14/16
14/16
INPUT
REG B
DAC
REG B
VOUTB
AGNDB
G2
G2
G2
GAIN REG B
OFFSET REG B
D0
D1
INPUT
REG C
DAC
REG C
VOUTC
AGNDC
GAIN REG C
OFFSET REG C
BIN/2SCOMP
INPUT
REG D
DAC
REG D
VOUTD
AGNDD
GAIN REG D
CLR
OFFSET REG D
REFERENCE
BUFFERS
TEMP
SENSOR
LDAC
VREF CD
TEMP
Figure 1. Functional Block Diagram
Rev. PrA 15-Nov-04| Page 3 of 27
Preliminary Technical Data
SPECIFICATIONS
AꢁDD = +11.4 ꢁ to +16.5 ꢁ, AꢁSS = −11.4 ꢁ to −16.5 ꢁ, AGND = DGND = REFGND = PGND=ꢂ ꢁ; REFAB = REFCD= 5 ꢁ Ext;
DꢁCC = ꢀ.7 ꢁ to 5.5 ꢁ, RLOAD = 1ꢂ kΩ, CL = ꢀꢂꢂ pF. All specifications TMIN to TMAX, unless otherwise noted.
Table 1.
Parameter
ACCURACY
Resolution
A Grade1
B Grade1
C Grade1
Unit
Test Conditions/Comments
16
14
4
1
1
16
14
2
1
1
16
14
1
1
1
Bits
AD5764
AD5744
Relative Accuracy (INL)
Differential Nonlinearity
Bipolar Zero Error
LSB max
LSB max
mV max
Guaranteed monotonic
At 25°C. Error at other
temperatures
obtained using bipolar zero TC.
Bipolar Zero TC
Zero Code Error
2
1
2
1
2
1
ppm FSR/°C max
mV max
At 25°C. Error at other
temperatures
obtained using zero code TC.
Zero Code TC
Gain Error
2
0.02
2
0.02
2
0.02
ppm FSR/°C max
% FSR max
At 25°C. Error at other
temperatures
obtained using gain TC.
Gain TC
DC Crosstalk2
2
0.5
2
0.5
2
0.5
ppm FSR/°C max
LSB max
REFERENCE INPUT/OUTPUT
Reference Input2
Reference Input Voltage
DC Input Impedance
Input Current
Reference Range
Reference Output
Output Voltage
5
1
10
1/5
5
1
10
1/5
5
1
10
1/5
V nom
1% for specified performance
Typically 100 MΩ
Typically 30 nA
MΩ min
µA max
V min/max
4.999/5.001 4.999/5.001 4.999/5.001 V min/max
At 25°C
Reference TC
Output Noise(0.1 Hz to 10 Hz) TBD
Noise Spectral Density
10
10
TBD
TBD
10
TBD
TBD
ppm/°C max
µV p-p typ
TBD
Hz
nV/√ typ
OUTPUT CHARACTERISTICS2
Output Voltage Range3
10
13
2
10
13
2
10
13
2
V min/max
V min/max
ppm FSR/°C max
AVDD/AVSS = 11.4 V
AVDD/AVSS = 16.5 V
Output Voltage TC
Output Voltage Drift VS Time
TBD
TBD
TBD
ppm FSR/1000 Hours
typ
Short Circuit Current
Load Current
10
1
10
1
10
1
mA max
mA max
RISCC = 6 KΩ , See Figure ???
For specified performance
Capacitive Load Stability
RL = ∞
RL = 10 kΩ
DC Output Impedance
DIGITAL INPUTS2
200
TBD
0.3
200
TBD
0.3
200
TBD
0.3
pF max
pF max
Ω max
DVCC = 2.7 V to 5.5 V, JEDEC
compliant
VIH, Input High Voltage
2
2
2
V min
1 Temperature range −40°C to +85°C; typical at +25°C. Device functionality is guaranteed to +105°C with degraded performance.
2 Guaranteed by characterization. Not production tested.
3 Output amplifier headroom requirement is 1.4 V min.
Rev. PrA 15-Nov-04| Page 4 of 27
Preliminary Technical Data
Parameter
A Grade1
0.8
10
B Grade1
C Grade1
Unit
Test Conditions/Comments
VIL, Input Low Voltage
Input Current
Pin Capacitance
0.8
10
10
0.8
10
10
V max
µA max
pF max
Total for All Pins. TA = TMIN to TMAX
.
10
DIGITAL OUTPUTS (D0,D1, SDO) 2
Output Low Voltage
Output High Voltage
0.4
DVCC – 1
0.4
DVCC – 1
0.4
DVCC – 1
V max
V min
DVCC= 5 V 10%, sinking 200 µA
DVCC = 5 V 10%, Sourcing 200
µA
Output Low Voltage
Output High Voltage
0.4
0.4
0.4
V max
V min
DVCC = 2.7 V to 3.6 V, Sinking 200
µA
DVCC = 2.7 V to 3.6 V, Sourcing
200 µA
DVCC – 0.5
DVCC – 0.5
DVCC – 0.5
High Impedance Leakage
Current
High Impedance Output
Capacitance
1
5
1
5
1
5
µA max
pF typ
SDO only
SDO only
TEMP SENSOR
Accuracy
1
5
1.5
5
0/3.0
200
10
1
5
1.5
5
0/3.0
200
10
1
5
1.5
5
0/3.0
200
10
°C typ
°C max
V typ
mV/°C typ
V min/max
µA max
ms typ
At 25°C
−40°C < T <+85°C
Output Voltage @ 25°C
Output Voltage Scale Factor
Output Voltage Range
Output Load Current
Power On Time
POWER REQUIREMENTS
AVDD/AVSS
Current source only.
To within 5°C
11.4/16.5
2.7/5.5
11.4/16.5
2.7/5.5
11.4/16.5
2.7/5.5
V min/max
V min/max
DVCC
Power Supply Sensitivity4
∆VOUT/∆ΑVDD
AIDD
AISS
DICC
−85
3.75
2.75
1
−85
3.75
2.75
1
−85
3.75
2.75
1
dB typ
mA/Channel max
mA/Channel max
mA max
Outputs unloaded
Outputs unloaded
VIH = DVCC, VIL = DGND. TBD mA
typ
Power Dissipation
244
244
244
mW typ
12 V operation output
unloaded
4 Guaranteed by characterization. Not production tested.
Rev. PrA 15-Nov-04| Page 5 of 27
Preliminary Technical Data
AC PERFORMANCE CHARACTERISTICS
AꢁDD = +11.4 ꢁ to +16.5 ꢁ, AꢁSS = −11.4 ꢁ to −16.5 ꢁ, AGND = DGND = REFGND = PGND=ꢂ ꢁ; REFAB = REFCD= 5 ꢁ Ext;
DꢁCC = ꢀ.7 ꢁ to 5.5 ꢁ, RLOAD = 1ꢂ kΩ, CL = ꢀꢂꢂ pF. All specifications TMIN to TMAX, unless otherwise noted. Guaranteed by design and
characterization, not production tested.
Table 2.
Parameter
A Grade B Grade C Grade Unit
Test Conditions/Comments
Full-scale step
DYNAMIC PERFORMANCE
Output Voltage Settling Time
8
8
8
µs typ
10
1
5
5
5
10
1
5
5
5
100
5
5
10
1
5
5
5
100
5
5
µs max
µs max
V/µs typ
nV-s typ
mV max
dB typ
nV-s typ
nV-s typ
nV-s typ
512 LSB step settling @ 16 Bits
Slew Rate
Digital-to-Analog Glitch Energy
Glitch Impulse Peak Amplitude
Channel-to-Channel Isolation
DAC-to-DAC Crosstalk
Digital Crosstalk
100
5
Digital Feedthrough
1
1
Effect of input bus activity on DAC
output under test
Output Noise (0.1 Hz to 10 Hz)
Output Noise (0.1 kHz to 100 kHz)5
1/f Corner Frequency
0.1
45
1
0.1
45
1
LSB p-p typ
µV rms max
kHz typ
Output Noise Spectral Density
60
80
60
80
Hz
nV/√ typ
Hz
nV/√ typ
Measured at 10 kHz
Measured at 10 kHz
Complete System Output Noise Spectral
Density6
5 Guaranteed by design and characterization. Not production tested.
6 Includes noise contributions from integrated reference buffers, 14/16-bit DAC and output amplifier.
Rev. PrA 15-Nov-04| Page 6 of 27
Preliminary Technical Data
TIMING CHARACTERISTICS
AꢁDD = +11.4 ꢁ to +16.5 ꢁ, AꢁSS = −11.4 ꢁ to −16.5 ꢁ, AGND = DGND = REFGND = PGND = ꢂ ꢁ; REFAB = REFCD= 5 ꢁ Ext;
DꢁCC = ꢀ.7 ꢁ to 5.5 ꢁ, RLOAD = 1ꢂ kΩ, CL = ꢀꢂꢂ pF. All specifications TMIN to TMAX, unless otherwise noted.
Table 3.
Parameter7,8,9
ꢀimit at TMIN, TMAX
Unit
Description
t1
t2
t3
t4
33
13
13
13
13
40
5
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
µs max
ns min
µs max
ns max
ns min
ns min
SCLK cycle time
SCLK high time
SCLK low time
SYNC
falling edge to SCLK falling edge setup time
10
th
t5
SYNC
rising edge
24 SCLK falling edge to
t6
SYNC
high time
Minimum
t7
t8
t9
Data setup time
Data hold time
0
20
20
5
SYNC
LDAC
LDAC
LDAC
falling edge
rising edge to
pulse width low
falling edge to DAC output response time
t10
t11
t12
t13
t14
10
20
12
20
8
DAC output settling time
CLR
CLR
pulse width low
pulse activation time
11,12
t15
t16
SCLK rising edge to SDO valid
12
SCLK
SYNC
falling edge to SYNC rising edge
LDAC
12
t17
20
rising edge to
falling edge
7 Guaranteed by design and characterization. Not production tested.
8 All input signals are specified with tr = tf = 5 ns (10% to 90% of DVCC) and timed from a voltage level of 1.2 V.
9 See Figure 2, Figure 3, and Figure 4.
10 Stand-alone mode only.
11 Measured with the load circuit of Figure 5.
12 Daisy-chain mode only.
Rev. PrA 15-Nov-04| Page 7 of 27
Preliminary Technical Data
t1
SCLK
1
2
24
t6
t3
t2
t4
t5
SYNC
t8
t7
SDIN
DB23
DB0
t10
t9
LDAC
t12
t11
V
OUT
LDAC = 0
t12
t11
V
OUT
t13
CLR
t14
V
OUT
Figure ꢀ. Serial Interface Timing Diagram
t1
SCLK
24
48
t3
t2
t5
t6
t16
t4
SYNC
t8
t7
DB23
DB0
DB23
DB0
SDIN
INPUT WORD FOR DAC N
INPUT WORD FOR DAC N+1
INPUT WORD FOR DAC N
t15
DB23
DB0
SDO
t17
UNDEFINED
t10
LDAC
Figure 3. Daisy Chain Timing Diagram
Rev. PrA 15-Nov-04| Page 8 of 27
Preliminary Technical Data
SCLK
24
48
SYNC
DB23
DB0
DB23
DB0
DB0
SDIN
SDO
INPUT WORD SPECIFIES
REGISTER TO BE READ
NOP CONDITION
DB23
UNDEFINED
SELECTED REGISTER DATA
CLOCKED OUT
Figure 4. Readback Timing Diagram
200µA
I
OL
V
V
(MIN) OR
(MAX)
TO OUTPUT
PIN
OH
OL
C
L
50pF
200µA
I
OH
Figure 5. Load Circuit for SDO Timing Diagram
Rev. PrA 15-Nov-04| Page 9 of 27
Preliminary Technical Data
ABSOLUTE MAXIMUM RATINGS
TA = ꢀ5°C unless otherwise noted.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those listed in the operational sections
of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Transient currents of up to 1ꢂꢂ mA will not cause SCR latch-up.
Table 4.
Parameter
Rating
AVDD to AGND, DGND
AVSS to AGND, DGND
DVCC to DGND
Digital Inputs to DGND
Digital Outputs to DGND
REF IN to AGND, PWRGND
REF OUT to AGND
−0.3 V to +17 V
+0.3 V to −17 V
−0.3 V to +7 V
−0.3 V to DVCC + 0.3 V
−0.3 V to DVCC + 0.3 V
−0.3 V to +17 V
AVSS to AVDD
VOUTA,B,C,D to AGND
AGND to DGND
AVSS to AVDD
−0.3 V to +0.3 V
Operating Temperature Range
Industrial
−40°C to +85°C
−65°C to +150°C
150°C
Storage Temperature Range
Junction Temperature (TJ max)
32-Lead TQFP Package,
θJA Thermal Impedance
Reflow Soldering
TBD°C/W
Peak Temperature
220°C
Time at Peak Temperature
10 sec to 40 sec
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. PrA 15-Nov-04| Page 10 of 27
Preliminary Technical Data
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
32
25
1
24
SYNC
SCLK
SDIN
SDO
CLR
LDAC
D0
AGNDA
VOUTA
VOUTB
AGNDB
AGNDC
VOUTC
VOUTD
AGNDD
PIN 1
INDICATOR
AD5744/64
TOP VIEW
(Not to Scale)
D1
8
17
9
16
Figure 6. 3ꢀ-Lead TQFP Pin Configuration Diagram
Table 5. Pin Function Descriptions
Pin No.
Mnemonic
Function
1
SYNC
Active Low Input. This is the frame synchronization signal for the serial interface.
SYNC
While
is low, data is transferred in on the falling edge of SCLK.
2
SCLK13
Serial Clock Input. Data is clocked into the shift register on the falling edge of SCLK.
This operates at clock speeds up to 30 MHz.
3
4
SDIN13
SDO
Serial Data Input. Data must be valid on the falling edge of SCLK.
Serial Data Output. Used to clock data from the serial register in daisy-chain or
readback mode.
5
6
CLR13
LDAC
Active Low Input. Asserting this pin sets the DAC registers to 0x0000.
Load DAC. Logic input. This is used to update the DAC registers and consequently
the analog output. When tied permanently low, the addressed DAC register is
th
LDAC
updated on the 24 clock of the serial register write. If
is held high during the
write cycle, the DAC input register is updated but the output is held off until the
LDAC
falling edge of
. In this mode, all analog outputs can be updated
LDAC
simultaneously on the falling edge of
.
7, 8
D0, D1
D0 and D1 form a digital I/O port. The user can configure these pins as inputs or
outputs that are configurable and readable over the serial interface. When
configured as inputs, these pins have weak internal pull-ups to DVCC.
9
RSTOUT
RSTIN
Reset Logic Output. This is the output from the on-chip voltage monitor used in the
reset circuit. If desired, it may be used to control other system components.
Reset Logic Input. This input allows external access to the internal reset logic.
Applying a Logic 0 to this input resets the DAC output to 0 V. In normal operation,
10
RSTIN
should be tied to Logic 1.
11
12
DGND
DVCC
Digital GND Pin.
Digital Supply Pin. Voltage ranges from 2.7 V to 5.5 V. When programmed as
outputs, D0 and D1 are referenced to DVCC.
13, 31
14
15, 30
AVDD
PGND
AVSS
Positive Analog Supply Pins. Voltage ranges from 11.4 V to 16.5 V.
Ground Reference Point for Analog Circuitry.
Negative Analog Supply Pins. Voltage ranges from –11.4 V to –16.5 V.
13 Internal pull-up device on this logic input. Therefore, it can be left floating and will default to a logic high condition.
Rev. PrA 15-Nov-04| Page 11 of 27
Preliminary Technical Data
Pin No.
Mnemonic
Function
16
ISCC
This pin us used in association with an external resistor to AGND to program the
short-circuit current of the output amplifiers.
17
18
AGNDD
VOUTD
Ground Reference Pin for DAC D Output amplifier.
Analog Output Voltage of DAC D. Buffered output with a nominal full-scale output
range of 10 V. The output amplifier is capable of directly driving a 10 kΩ, 200 pF
load.
19
VOUTC
Analog Output Voltage of DAC C. Buffered output with a nominal full-scale output
range of 10 V. The output amplifier is capable of directly driving a 10 kΩ, 200 pF
load.
20
21
22
AGNDC
AGNDB
VOUTB
Ground Reference Pin for DAC C Output Amplifier.
Ground Reference pin for DAC B Output Amplifier.
Analog Output Voltage of DAC B. Buffered output with a nominal full-scale output
range of 10 V. The output amplifier is capable of directly driving a 10 kΩ, 200 pF
load.
23
VOUTA
Analog Output Voltage of DAC A. Buffered output with a nominal full-scale output
range of 10 V. The output amplifier is capable of directly driving a 10 kΩ, 200 pF
load.
24
25
AGNDA
REFAB
Ground Reference Pin for DAC A Output Amplifier.
External Reference Voltage Input for Channels A and B. Reference input range is 1 V
to 5 V; programs the full-scale output voltage. REFIN = 5 V for specified performance.
26
27
REFCD
External Reference Voltage Input for Channels C and D. Reference input range is 1 V
to 5 V; programs the full-scale output voltage. REFIN = 5 V for specified performance.
Reference Output. This is the buffered reference output from the internal voltage
reference. The internal reference is 5 V 1 mV, with a reference tempco of 10
ppm/°C.
REFOUT
28
29
REFGND
TEMP
Reference Ground Return for the Reference Generator and Buffers.
This pin provides an output voltage proportional to temperature. The output
voltage is 1.5 V typical at 25°C; variation with temperature is 5 mV/°C.
32
2sCOMP
BIN/
Determines the DAC Coding. When set to a logic high, input coding is offset binary.
When set to a logic low, input coding is twos complement. (See Table 6 and Table 7)
Rev. PrA 15-Nov-04| Page 12 of 27
Preliminary Technical Data
TERMINOLOGY
Relative Accuracy
9ꢂ% of the output signal and is given in ꢁ/µs.
For the DAC, relative accuracy or Integral Nonlinearity (INL) is
a measure of the maximum deviation, in LSBs, from a straight
line passing through the endpoints of the DAC transfer
function. A typical INL vs. code plot can be seen in Figure ?.
Gain Error
This is a measure of the span error of the DAC. It is the
deviation in slope of the DAC transfer characteristic from the
ideal, expressed as a percentage of the full-scale range.
Differential Nonlinearity
Total Unadjusted Error
Differential Nonlinearity (DNL) is the difference between the
measured change and the ideal 1 LSB change between any two
adjacent codes. A specified differential nonlinearity of 1 LSB
maximum ensures monotonicity. This DAC is guaranteed
monotonic by design. A typical DNL vs. code plot can be seen
in Figures ?.
Total Unadjusted Error (TUE) is a measure of the output error
taking all the various errors into account. A typical TUE vs.
code plot can be seen in Figure ?.
Zero-Code Error Drift
This is a measure of the change in zero-code error with a
change in temperature. It is expressed in µꢁ/°C.
Monotonicity
A DAC is monotonic, if the output either increases or remains
constant for increasing digital input code. The AD5744/64 is
monotonic over its full operating temperature range
Gain Error Drift
This is a measure of the change in gain error with changes in
temperature. It is expressed in (ppm of full-scale range)/°C.
Bipolar Zero Error
Digital-to-Analog Glitch Impulse
Bipolar zero error is the deviation of the analog output from the
ideal half-scale output of ꢂ ꢁ when the DAC register is loaded
with ꢂx8ꢂꢂꢂ (Offset Binary coding) or ꢂxꢂꢂꢂꢂ (ꢀsComplement
coding)
Digital-to-analog glitch impulse is the impulse injected into the
analog output when the input code in the DAC register changes
state. It is normally specified as the area of the glitch in nꢁ secs
and is measured when the digital input code is changed by
1 LSB at the major carry transition (7FFF Hex to 8ꢂꢂꢂ Hex). See
Figure ?.
Full-Scale Error
Full-scale error is a measure of the output error when full-scale
code is loaded to the DAC register. Ideally the output voltage
should be full scale value – 1 LSB. Full-scale error is expressed
in percentage of full-scale range. A plot of full-scale error vs.
temperature can be seen in Figure ?.
Digital Feedthrough
Digital feedthrough is a measure of the impulse injected into
the analog output of the DAC from the digital inputs of the
DAC but is measured when the DAC output is not updated. It is
specified in nꢁ secs and measured with a full-scale code change
on the data bus, i.e., from all ꢂs to all 1s and vice versa.
Negative Full-Scale Error / Zero Scale Error
Negative full-scale error is the error in the DAC output voltage
when ꢂxꢂꢂꢂꢂ (Offset Binary coding) or ꢂx8ꢂꢂꢂ (ꢀsComplement
coding) is loaded to the DAC register. Ideally the output voltage
should be negative full scale value – 1 LSB.
Power Supply Sensitivity
Power supply sensitivity indicates how the output of the DAC is
affected by changes in the power supply voltage.
Output Voltage Settling Time
DC Crosstalk
Output voltage settling time is the amount of time it takes for
the output to settle to a specified level for a full-scale input
change.
This is the dc change in the output level of one DAC in response
to a change in the output of another DAC. It is measured with a
full-scale output change on one DAC while monitoring another
DAC. It is expressed in µꢁ.
Slew Rate
The slew rate of a device is a limatation in the rate of change of
the output voltage. The output slewing speed of a voltage-
output D/A converter is usually limited by the slew rate of the
amplifier used at its output. Slew rate is measured from 1ꢂ% to
DAC-to-DAC Crosstalk
This is the glitch impulse transferred to the output of one DAC
due to a digital code change and subsequent output change of
Rev. PrA 15-Nov-04| Page 13 of 27
Preliminary Technical Data
another DAC. This includes both digital and analog crosstalk. It
is measured by loading one of the DACs with a full-scale code
LDAC
change (all ꢂs to all 1s and vice versa) with
low and
monitoring the output of another DAC. The energy of the glitch
is expressed in nꢁ-s.
Channel-to-Channel Isolation
This is the ratio of the amplitude of the signal at the output of
one DAC to a sine wave on the reference input of another DAC.
It is measured in dB.
Rev. PrA 15-Nov-04| Page 14 of 27
Preliminary Technical Data
TYPICAL PERFORMANCE
CHARACTERISTICS
Rev. PrA 15-Nov-04| Page 15 of 27
Preliminary Technical Data
SERIAꢀ INTERFACE
GENERAL DESCRIPTION
The AD5744/64 is controlled over a versatile 3-wire serial
interface that operates at clock rates of up to 3ꢂ MHz and is
compatible with SPI, QSPI, MICROWIRE and DSP standards.
The AD5744/64 is a quad 14/16-bit, serial input, bipolar voltage
output DAC. It operates from supply voltages of 11.4 ꢁ to
16.5 ꢁ and has a buffered output voltage of up to 1ꢂ.5 ꢁ.
Data is written to the AD5744/64 in a ꢀ4-bit word format, via a
3-wire serial interface. The device also offers an SDO pin, which
is available for daisy chaining or readback.
Input Shift Register
The input shift register is ꢀ4 bits wide. Data is loaded into the
device MSB first as a ꢀ4-bit word under the control of a serial
clock input, SCLK. The input register consists of a read/write
bit, three register select bits, three DAC address bits and 14/16
data bits as shown in Table 8.The timing diagram for this
operation is shown in Figure ꢀ.
The AD5744/64 incorporates a power-on reset circuit, which
ensures that the DAC registers power up loaded with ꢂxꢂꢂꢂꢂ.
The AD5744/64 also features a digital I/O port that may be
programmed via the serial interface, an analog temperature
sensor, on-chip 1ꢂ ppm/°C voltage reference, on-chip reference
buffers and per channel digital gain and offset registers.
Upon power-up the DAC registers are loaded with zero code
(ꢂxꢂꢂꢂꢂ). The corresponding output voltage depends on the
ꢀsCOMP
ꢀsCOMP
state of the BIN/
pin. If the BIN/
pin is tied to
DAC ARCHITECTURE
DGND then the data coding is ꢀsComplement and the outputs
ꢀsCOMP
The DAC architecture of the AD5744/64 consists of a 14/16-bit
current-mode segmented R-ꢀR DAC. The simplified circuit
diagram for the DAC section is shown in Figure 13.
will power-up to ꢂꢁ. If the BIN/
pin is tied high then
the data coding is Offset binary and the outputs will power-up
to Negative Full-scale.
Standalone Operation
The four MSBs of the 14/16-bit data word are decoded to drive
15 switches, E1 to E15. Each of these switches connects one of
the 15 matched resistors to either AGND or IOUT. The
remaining 1ꢀ bits of the data word drive switches Sꢂ to S11 of
the 1ꢀ-bit R-ꢀR ladder network.
The serial interface works with both a continuous and noncon-
tinuous serial clock. A continuous SCLK source can only be
SYNC
used if
In gated clock mode, a burst clock containing the exact number
SYNC
is held low for the correct number of clock cycles.
of clock cycles must be used and
the final clock to latch the data. The first falling edge of
starts the write cycle. Exactly ꢀ4 falling clock edges must be
must be taken high after
R
R
R
V
ref
SYNC
2R
2R
2R
2R
2R
2R
2R
SYNC
applied to SCLK before
SYNC
is brought back high again; if
th
R/8
is brought high before the ꢀ4 falling SCLK edge, the
E15
E14
E1
S0
S11
S10
write is aborted. If more than ꢀ4 falling SCLK edges are applied
SYNC
before
The input register addressed is updated on the rising edge of
SYNC SYNC
is brought high, the input data will be corrupted.
V
OUT
AGND
. In order for another serial transfer to take place,
4 MSBs DECODED INTO
15 EQUAL SEGMENTS
12 BIT R-2R LADDER
must be brought low again. After the end of the serial data
transfer, data is automatically transferred from the input shift
register to the input register of the addressed DAC.
Figure 7. DAC Ladder Structure
When the data has been transferred into the input register of
the addressed DAC, all DAC registers and outputs can be
REFERENCE BUFFERS
LDAC
SYNC
The AD5744/64 can operate with either an external or internal
reference. The reference inputs (REFAB and REFCD) have an
input range up to 5 ꢁ. This input voltage is then used to provide
a buffered positive and negative reference for the DAC cores.
The positive reference is given by
updated by taking
low while
is high.
+ ꢁREF = ꢀ* ꢁREF
While the negative reference to the DAC cores is given by
-ꢁREF = -ꢀ*ꢁREF
These positive and negative reference voltages (along with the
gain register values) define the output ranges of the DACs.
Rev. PrA 15-Nov-04| Page 16 of 27
Preliminary Technical Data
containing the exact number of clock cycles must be used and
SYNC
68HC11*
AD5744/64*
must be taken high after the final clock to latch the data.
MOSI
SCK
PC7
PC6
SDIN
SCLK
SYNC
LDAC
Readback Operation
Readback mode is invoked by setting the R/ bit = 1 in the
W
W
serial input register write. With R/ = 1, Bits Aꢀ–Aꢂ, in
association with Bits REGꢀ , REG1, and REGꢂ, select the
register to be read. The remaining data bits in the write
sequence are don’t cares. During the next SPI write, the data
appearing on the SDO output will contain the data from the
previously addressed register. For a read of a single register, the
NOP command can be used in clocking out the data from the
selected register on SDO. The readback diagram in Figure 4
shows the readback sequence. For example, to read back the
fine gain register of Channel A on the AD5744/64, the following
sequence should be implemented. First, write ꢂxAꢂXXXX to
the AD5744/64 input register. This configures the AD5744/64
for read mode with the fine gain register of Channel A selected.
Note that all the data bits, DB15 to DBꢂ, are don’t cares. Follow
this with a second write, a NOP condition, ꢂxꢂꢂXXXX. During
this write, the data from the fine gain register is clocked out on
the SDO line, i.e., data clocked out will contain the data from
the fine gain register in Bits DB5 to DBꢂ.
MISO
SDO
SDIN
AD5744/64*
SCLK
SYNC
LDAC
SDO
R
SDIN
AD5744/64*
SCLK
SYNC
LDAC
SIMUꢀTANEOUS UPDATING VIA ꢀDAC
After data has been transferred into the input register of the
DACs, there are two ways in which the DAC registers and DAC
SDO
SYNC
outputs can be updated. Depending on the status of both
LDAC
*ADDITIONAL PINS OMITTED FOR CLARITY
and
.
Figure 8. Daisy chaining the AD5744/64
Individual DAC Updating
LDAC
Daisy-Chain Operation
In this mode,
is held low while data is being clocked into
the input shift register. The addressed DAC output is updated
SYNC
For systems that contain several devices, the SDO pin may be
used to daisy-chain several devices together. This daisy-chain
mode can be useful in system diagnostics and in reducing the
on the rising edge of
Simultaneous Updating of All DACs
LDAC
.
SYNC
number of serial interface lines. The first falling edge of
starts the write cycle. The SCLK is continuously applied to the
SYNC
In this mode,
into the input shift register. All DAC outputs are updated by
LDAC SYNC
is held high while data is being clocked
input shift register when
is low. If more than ꢀ4 clock
taking
low any time after
has been taken high.
LDAC
pulses are applied, the data ripples out of the shift register and
appears on the SDO line. This data is clocked out on the rising
edge of SCLK and is valid on the falling edge. By connecting the
SDO of the first device to the DIN input of the next device in
the chain, a multidevice interface is constructed. Each device in
the system requires ꢀ4 clock pulses. Therefore, the total number
of clock cycles must equal ꢀ4N, where N is the total number of
AD5744/64s in the chain. When the serial transfer to all devices
The update now occurs on the falling edge of
.
SYNC
is complete,
is taken high. This latches the input data in
each device in the daisy chain and prevents any further data
from being clocked into the input shift register. The serial clock
may be a continuous or a gated clock. A continuous SCLK
SYNC
source can only be used if
is held low for the correct
number of clock cycles. In gated clock mode, a burst clock
Rev. PrA 15-Nov-04| Page 17 of 27
Preliminary Technical Data
OUTPUT
I/V AMPLIFIER
Table 7. Ideal output voltage to input Code relationship for the
AD5744
16-BIT
DAC
V
REFIN
V
OUT
Digital Input
Analog Output
Offset Binary Data Coding
DAC
LDAC
MSB
11
ꢀSB VOUT
REGISTER
+2 VREF x (8192/8192)
+2 VREF x (1/8192)
0 V
1111
0000
0000
1111
0000
1111
0000
0000
1111
0000
1111
0001
0000
1111
0000
10
10
01
00
INPUT
REGISTER
-2 VREF x (1/8192)
-2 VREF x (8192/8192)
SCLK
SYNC
SDIN
Twos Complement Data Coding
INTERFACE
LOGIC
SDO
VOUT
MSB
01
ꢀSB
1111
+2 VREF x (8192/8192)
+2 VREF x (1/8192)
0 V
1111
0000
0000
1111
0000
1111
0000
0000
1111
0000
Figure 9. Simplified Serial Interface showing input loading
circuitry for one DAC Channel
00
00
11
10
0001
0000
1111
0000
-2 VREF x (1/8192)
-2 VREF x (8192/8192)
TRANSFER FUNCTION
Table 6 and Table 7 Show the ideal input code to output voltage
relationship for the AD5744/64 for both Offset binary and twos
complement data coding.
The output voltage expression for the AD5764 is given by:
Table 6. Ideal output voltage to input code relationship for the
AD5764
D
⎡
⎤
VOUT = −2×VREFIN + 4×VREFIN
⎢
⎣
⎥
⎦
Digital Input
Analog Output
65536
The output voltage expression for the AD5744 is given by:
Offset Binary Data Coding
MSB
1111
1000
1000
0111
0000
ꢀSB VOUT
D
⎡
⎤
+2 VREF x (32767/32768)
+2 VREF x (1/32768)
0 V
1111
0000
0000
1111
0000
1111
0000
0000
1111
0000
1111
0001
0000
1111
0000
VOUT = −2×VREFIN + 4×VREFIN
⎢
⎣
⎥
⎦
16384
where:
-2 VREF x (1/32768)
-2 VREF x (32767/32768)
D is the decimal equivalent of the code loaded to the DAC.
ꢁREFIN is the reference voltage applied at the REFIN pin.
Twos Complement Data Coding
VOUT
MSB
0111
0000
0000
1111
1000
ꢀSB
1111
ASYNCHRONOUS CꢀEAR (CꢀR)
+2 VREF x (32767/32768)
+2 VREF x (1/32768)
0 V
1111
0000
0000
1111
0000
1111
0000
0000
1111
0000
CLR
is an active low, level sensitive clear that allows the outputs
0001
0000
1111
0000
to be cleared to either ꢂ ꢁ (Offset binary coding) or negative
full scale (twos complement coding). It is necessary to maintain
-2 VREF x (1/32768)
-2 VREF x (32767/32768)
CLR
low for a minimum amount of time (refer to Figure 3) for
CLR
the operation to complete. When the
signal is returned
high, the output remains at the cleared value until a new value is
CLR LDAC
programmed. The
SYNC
signal has priority over
. A clear can also be initiated through software by writing
the command ꢂxꢂ4XXXX to the AD5744/64.
and
Rev. PrA 15-Nov-04| Page 18 of 27
Preliminary Technical Data
Table 8. AD5744/64 Input Register Format
MSB
ꢀSB
DB23
DB22
DB21
DB20
DB19
DB18
DB17
DB16
DB15
DB14
DB13
DB12
DB11
DB10
DB9
DB8
DB7
DB6
DB5
DB4
DB3
DB2
DB1
DB0
W
R/
0
REG2
REG1
REG0
A2
A1
A0
DATA
Table 9. Input Register Bit Functions
Indicates a read from or a write to the addressed register.
W
R/
REG2, REG1, REG0
Used in association with the address bits to determine if a read or write operation is to the data register, offset
register, gain register, or function register.
REG2
REG1
REG0
Function
0
0
0
1
1
0
1
1
0
0
0
0
1
0
1
Function Register
Data Register
Coarse Gain Register
Fine Gain Register
Offset Register
A2, A1, A0
These bits are used to decode the DAC channels
A2
0
A1
0
A0
0
Channel Address
DAC A
0
0
1
DAC B
0
1
0
DAC C
0
1
1
DAC D
1
0
0
ALL DACs
D15 – D0
Data Bits
FUNCTION REGISTER
The Function Register is addressed by setting the three REG bits to ꢂꢂꢂ. The values written to the address bits and the data bits determine
the function addressed. The Functions available through the function register are shown in Table 1ꢂ and
Table 11.
Table 1ꢂ. Function Register Options
REG2 REG1 REG0 A2 A1 A0
DB15 .. DB6
DB5
DB4
NOP, Data = Don’t Care
D1
D1 Value D0
Direction
DB3
DB2
DB1
DB0
0
0
0
0
0
0
0
0
0
0
0
1
Don’t Care
Local-
Ground-
Offset Adjust
D0
Value
SDO
Disable
Direction
0
0
0
0
0
0
1
1
0
0
0
1
CLR, Data = Don’t Care
LOAD, Data = Don’t Care
Rev. PrA 15-Nov-04| Page 19 of 27
Preliminary Technical Data
Table 11. Explanation of Function Register Options
NOP
No operation instruction used in readback operations.
Local-Ground-
Offset Adjust
Set by the user to enable local-ground-offset adjust function.
Cleared by the user to disable local-ground-offset adjust function (default).
Set by the user to enable D0/D1 as outputs.
D0 / D1
Direction
Cleared by the user to enable D0/D1 as inputs (default). Have weak internal pull-ups.
D0 / D1 Value
I/O port status bits. Logic values written to these locations determine the logic outputs on the D0 and D1 pins when
configured as outputs. These bits indicate the status of the D0 and D1 pins when the I/O port is active as an input. When
enabled as inputs, these bits are don’t cares during a write operation.
SDO Disable
Set by the user to disable the SDO output.
Cleared by the user to enable the SDO output (default).
CLR
Addressing this function resets the DAC outputs to 0 V in twos complement mode and negative full scale in binary
mode.
LOAD
Addressing this function updates the DAC registers and consequently the analog outputs.
DATA REGISTER
The Data register is addressed by setting the three REG bits to ꢂ1ꢂ. The DAC address bits select with which DAC Channel the Data
transfer is to take place (Refer to Table 9). The data bits are in positions D15 to Dꢂ for the AD5764 as shown in Table 1ꢀ and D13 to Dꢂ
for the AD5744 as shown in Table 13.
Table 1ꢀ. Programming the AD5764 Data Register
REG2
REG1
REG0
A2
A1
A0
DB15
DB14
DB13
DB13
DB12
DB12
DB11
DB11
DB10
DB9
DB8
DB7
DB6
DB6
DB5
DB5
DB4
DB4
DB3
DB3
DB2
DB2
DB1
DB0
0
1
0
DAC Address
16 Bit DAC Data
Table 13. Programming the AD5744 Data Register
REG2
REG1
REG0
A2
A1
A0
DB15
DB14
DB10
DB9
DB8
DB7
DB1
DB0
0
1
0
DAC Address
14 Bit DAC Data
X
X
COARSE GAIN REGISTER
The Coarse Gain Register is addressed by setting the three REG bits to ꢂ11. The DAC address bits select with which DAC Channel the
Data transfer is to take place (Refer to Table 9). The Coarse Gain Register is a ꢀ-bit register and allows the user to select the output range
of each DAC as shown in Table 15.
Table 14. Programming the Coarse Gain Register
REG2 REG1 REG0 A2 A1 A0 DB15 …. DB2 DB1 DB0
0
1
1
DAC Address
Don’t Care
CG1 CG0
Table 15. Output Range Selection
Output Range
CG1
CG0
10 V
10.25 V
10.5 V
0
0
1
0
1
0
Rev. PrA 15-Nov-04| Page 20 of 27
Preliminary Technical Data
FINE GAIN REGISTER
The Fine Gain Register is addressed by setting the three REG bits to 1ꢂꢂ. The DAC address bits select with which DAC Channel the Data
transfer is to take place (Refer to Table 9). The Fine Gain Register is a 6-bit register and allows the user to adjust the gain of each DAC
channel by -3ꢀ LSBs to +31 LSBs in 1 LSB steps as shown in
Table 16 and
Table 17.
Table 16. Programming AD5764 Fine Gain Register
REG2 REG1 REG0 A2
A1
A0
DB15 …. DB6
DB5 DB4 DB3 DB2 DB1 DB0
1
0
0
DAC Address
Don’t Care
FG5 FG4 FG3 FG2 FG1 FG0
Table 17. Fine Gain Register Options
Gain Adjustment
+31 LSBs
+30 LSBs
FG5 FG4 FG3 FG2 FG1 FG0
0
0
-
1
1
-
1
1
-
1
1
-
1
1
-
1
0
-
No Adjustment
0
-
0
-
0
-
0
-
0
-
0
-
-31 LSBs
-32 LSBs
1
1
0
0
0
0
0
0
0
0
1
0
OFFSET REGISTER
The Offset Register is addressed by setting the three REG bits to 1ꢂ1. The DAC address bits select with which DAC Channel the Data
transfer is to take place (Refer to Table 9). The Offset Register is an 8-bit register and allows the user to adjust the offset of each channel
by – 15.875 LSBs to + 16 LSBs in steps of 1/8 LSB as shown in Table 18 and Table 19.
Table 18. Programming the Offset Register
REG2 REG1 REG0 A2 A1 A0 DB15 …. DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0
1
0
1
DAC Address
Don’t Care
OF7 OF6 OF5 OF4 OF3 OF2 OF1 OF0
Table 19. Offset Register options
Offset Adjustment
+15.875 LSBs
+16.5 LSBs
OF7 OF6 OF5 OF4 OF3 OF2 OF1 OF0
0
0
-
1
1
-
1
1
-
1
1
-
1
1
-
1
1
-
1
1
-
1
0
-
No Adjustment
0
-
0
-
0
-
0
-
0
-
0
-
0
-
0
-
-15.875 LSBs
-16 LSBs
1
1
0
0
0
0
0
0
0
0
0
0
0
0
1
0
Rev. PrA 15-Nov-04| Page 21 of 27
Preliminary Technical Data
AD5744/64 FEATURES
ANAꢀOG OUTPUT CONTROꢀ
The resistor value is calculated as follows;
In many industrial process control applications, it is vital that
the output voltage be controlled during power up and during
brownout conditions. When the supply voltages are changing,
the ꢁOUT pin is clamped to ꢂ ꢁ via a low impedance path. To
prevent the output amp being shorted to ꢂ ꢁ during this time,
transmission gate G1 is also opened. These conditions are
maintained until the power supplies stabilize and a valid word is
written to the DAC register. At this time, Gꢀ opens and G1
closes. Both transmission gates are also externally controllable
60
R =
Isc
If the ISCC pin is left unconnected the short circuit current
limit defaults to 5 mA. It should be noted that limiting the short
circuit current to a small value can affect the slew rate of the
output when driving into a capacitive load, therefore the value
of short-circuit current programmed should take into account
the size of the capacitive load being driven.
RSTIN
RSTIN
input is
via the Reset In (
) control input. For instance, if
RSTIN
is
driven from a battery supervisor chip, the
DIGITAꢀ I/O PORT
driven low to open G1 and close Gꢀ on power-off or during a
brownout. Conversely, the on-chip voltage detector output
The AD5744/64 contains a ꢀ-bit digital I/O port (D1 and Dꢂ);
these bits can be configured as inputs or outputs independently,
and can be driven or have their values read back via the serial
interface. The I/O port signals are referenced to DꢁCC and
DGND. When configured as outputs, they can be used as con-
trol signals to multiplexers or can be used to control calibration
circuitry elsewhere in the system. When configured as inputs,
the logic signals from limit switches, for example can be applied
to Dꢂ and D1 and can be read back via the digital interface.
RSTOUT
(
) is also available to the user to control other parts of
the system. The basic transmission gate functionality is shown
in Figure 1ꢂ.
RSTOUT
RSTIN
VOLTAGE
MONITOR
AND
TEMPERATURE SENSOR
CONTROL
The on-chip temperature sensor provides a voltage output that
is linearly proportional to the Centigrade temperature scale.
The typical accuracy of the temperature sensor is 1°C at +ꢀ5°C
and 5°C over the −4ꢂ°C to +1ꢂ5°C range. Its nominal output
voltage is 1.5ꢁ at +ꢀ5°C, varying at 5 mꢁ/°C, giving a typical
output range of 1.175ꢁ to 1.9 ꢁ over the full temperature range.
Its low output impedance, low self heating, and linear output
simplify interfacing to temperature control circuitry and A/D
converters.
G1
VOUTA
AGNDA
G2
Figure 1ꢂ. Analog Output Control Circuitry
DIGITAꢀ OFFSET AND GAIN CONTROꢀ
ꢀOCAꢀ GROUND OFFSET ADJUST
The AD5744/64 incorporates a digital offset adjust function
The AD5744/64 incorporates a Local Ground Offset Adjust
feature which when enabled in the Function Register adjusts the
DAC outputs for voltage differences between The individual
DAC ground pins and the REFGND pin ensuring that the DAC
output voltages are always with respect to the local DAC ground
pin. For instance if pin AGNDA is at +5mꢁ with respect to the
REFGND pin and ꢁOUTA is measured with respect to
AGNDA then a +5mꢁ error will result, enabling the Local
Ground Offset Adjust feature will offset ꢁOUTA by +5mꢁ
eliminating the error.
with a 16 LSB adjust range and ꢂ.1ꢀ5 LSB resolution. The gain
register allows the user to adjust the AD5744/64’s full-scale
output range. The full-scale output can be programmed to
achieve full-scale ranges of 1ꢂ ꢁ, 1ꢂ.ꢀ5 ꢁ, and 1ꢂ.5 ꢁ. A fine
gain trim is also available, allowing a trim range of 16 LSB in 1
LSB steps.
PROGRAMMABꢀE SHORT-CIRCUIT PROTECTION
The short-circuit current of the output amplifiers can be pro-
grammed by inserting an external resistor between the ISCC
pin and AGND. The programmable range for the current is
5ꢂꢂ µA to 1ꢂ mA, corresponding to a resistor range of 1ꢀꢂ kΩ
to 6 kΩ.
Rev. PrA 15-Nov-04| Page 22 of 27
Preliminary Technical Data
in the voltage reference is reflected in the outputs of the device.
APPLICATIONS INFORMATION
There are four possible sources of error to consider when
choosing a voltage reference for high accuracy applications:
initial accuracy, temperature coefficient of the output voltage,
long term drift and output voltage noise.
TYPICAꢀ OPERATING CIRCUIT
Figure 11 shows the typical operating circuit for the
AD5744/64. The only external components needed for this
precision 14/16-bit DAC are decoupling capacitors on the
supply pins, R-C connection from REFOUT to REFAB and
REFCD and a short circuit current setting resistor. Because the
device incorporates a voltage reference, and reference buffers, it
eliminates the need for an external bipolar reference and
associated buffers. This leads to an overall saving in both cost
and board space.
Initial accuracy error on the output voltage of an external
reference could lead to a full-scale error in the DAC. Therefore,
to minimize these errors, a reference with low initial accuracy
error specification is preferred. Also, choosing a reference with
an output trim adjustment, such as the ADR4ꢀ5, allows a
system designer to trim system errors out by setting the
reference voltage to a voltage other than the nominal. The trim
adjustment can also be used at temperature to trim out any
error.
In the circuit below, ꢁDD and ꢁSS are both connected to 15 ꢁ,
but ꢁDD and ꢁSS can operate with supplies from 11.4 ꢁ to
16.5 ꢁ. In Figure 11, AGNDA is connected to REFGND, but
the option of Force/Sense is included on this device, if required
by the user.
Long term drift is a measure of how much the reference output
voltage drifts over time. A reference with a tight lon-term drift
specification ensures that the overall solution remains relatively
stable over its entire lifetime.
+15V -15V
10 µF
10 µF
The temperature coefficient of a reference’s output voltage
affects INL, DNL and TUE. A reference with a tight
tempaerature coefficient specifiaction should be chosen to
reduce the dependence of the DAC output voltage on ambient
conditions.
100 nF
100 nF
TEMP
+5V
BIN/2SCOMP
32 31 30 29 28 27 26 25
In high accuracy applications, which have a relatively low noise
budget, reference output voltage noise needs to be considered.
Choosing a reference waith as low an output noise voltage as
practical for the system resolution required is important.
Precision voltage references such as the ADR435 (XFET design)
produce low output noise in the ꢂ.1 Hx to 1ꢂ Hz region.
However, as the circuit bandwidth increases, filtering the output
of the reference may be required to minimise the output noise.
1
2
3
4
5
6
7
8
24
23
22
21
20
19
18
17
SYNC
SCLK
SDIN
SDO
SYNC
AGNDA
VOUTA
VOUTB
AGNDB
AGNDC
VOUTC
VOUTD
AGNDD
VOUTA
VOUTB
SCLK
SDIN
SDO
CLR
LDAC
D0
AD5744/64
VOUTC
VOUTD
LDAC
D0
D1
D1
9
10 11 12 13 14 15 16
RSTOUT
RSTIN
6kΩ
Table ꢀꢂ. Partial List of Precision References Recommended for
use with the AD5744/64
10 µF
100 nF
10 µF
Initial
ꢀong-Term
Drift
Temp Drift
0.1 Hz to
Accuracy
(ppm/
10 Hz Noise
Part No.
ADR435
ADR425
ADR02
(mV max) (ppm typ)
°C max)
(µV p-p typ)
+15V
-15V
+5V
6
30
50
50
50
15
3
3.4
3.4
15
5
6
3
Figure 11. Typical operating circuit
5
3
ADR395
AD586
6
25
10
2.5
4
Precision Voltage Reference Selection
To achieve the optimum performance from the AD5744/64 over
it’s full operating temperature range an external voltage
reference must be used. Thought should be given to the
selection of a precision voltage reference. The AD5744/64 has
two reference inputs, REFAB and REFCD. The voltages applied
to the reference inputs are used tomprovide a buffered positiver
and negative reference for the DAC cores. Therefore, any error
Rev. PrA 15-Nov-04| Page 23 of 27
Preliminary Technical Data
DAC is not required, the LDAC pin may be tied permanently
low. The DAC can then be updated on the rising edge of SYNC.
ꢀAYOUT GUIDEꢀINES
In any circuit where accuracy is important, careful
consideration of the power supply and ground return layout
helps to ensure the rated performance. The printed circuit
board on which the AD5744/64 is mounted should be designed
so that the analog and digital sections are separated and
confined to certain areas of the board. If the AD5744/64 is in a
system where
multiple devices require an AGND-to-DGND connection, the
connection should be made at one point only. The star ground
point should be established as close as possible to the device.
DV
CC
µCONTROLLER
CONTROL OUT
TO LDAC
TO SYNC
TO SCLK
TO SDIN
SYNC OUT
The AD5744/64 should have ample supply bypassing of 1ꢂ µF
in
SERIAL CLOCK OUT
parallel with ꢂ.1 µF on each supply located as close to the
package as possible, ideally right up against the device. The 1ꢂ
µF capacitors are the tantalum bead type. The ꢂ.1 µF capacitor
should have low effective series resistance (ESR) and low
effective series inductance (ESI) such as the common ceramic
types, which provide a low impedance path to ground at high
frequencies to handle transient currents due to internal logic
switching.
SERIAL DATA OUT
OPTO-COUPLER
Figure 1ꢀ. Isolated Interface
The power supply lines of the AD5744/64 should use as large a
trace as possible to provide low impedance paths and reduce
the effects of glitches on the power supply line. Fast switching
signals such as clocks should be shielded with digital ground to
avoid radiating noise to other parts of the board, and should
never be run near the reference inputs. A ground line routed
between the SDIN and SCLK lines helps reduce crosstalk
between them (not required on a multilayer board, which has a
separate ground plane, but separating the lines helps). It is
essential to minimize noise on the reference inputs, because it
couples through to the DAC output.
MICROPROCESSOR INTERFACING
Microprocessor interfacing to the AD5744/64 is via a serial bus
that uses standard protocol compatible with microcontrollers
and DSP processors. The communications channel is a 3-wire
(minimum) interface consisting of a clock signal, a data signal,
and a synchronization signal. The AD5744/64 requires a ꢀ4-bit
data word with data valid on the falling edge of SCLK.
For all the interfaces, the DAC output update may be done
automatically when all the data is clocked in, or it may be done
under the control of LDAC. The contents of the DAC register
may be read using the readback function.
Avoid crossover of digital and analog signals. Traces on
opposite sides of the board should run at right angles to each
other. This reduces the effects of feed through the board. A
microstrip technique is by far the best, but not always possible
with a double-sided board. In this technique, the component
side of the board is dedicated to ground plane, while signal
traces are placed on the solder side.
AD5744/64 to MC68HC11 Interface
Figure 13 shows an example of a serial interface between the
AD5744/64 and the MC68HC11 microcontroller. The serial
peripheral interface (SPI) on the MC68HC11 is configured for
master mode (MSTR = 1), clock polarity bit (CPOL = ꢂ), and
the clock phase bit (CPHA = 1). The SPI is configured by
writing to the SPI control register (SPCR)----see the 68HC11
User Manual. SCK of the 68HC11 drives the SCLK of the
AD5744/64, the MOSI output drives the serial data line (DIN)
of
ISOꢀATED INTERFACE
In many process control applications, it is necessary to provide
an isolation barrier between the controller and the unit being
controlled. Opto-isolators can provide voltage isolation in
excess of 3 kꢁ. The serial loading structure of the AD5744/64
makes it ideal for opto-isolated interfaces, because the number
of interface lines is kept to a minimum. Figure 1ꢀ shows a 4-
channel isolated interface to the AD5744/64. To reduce the
number of opto-isolators, if the simultaneous updating of the
the AD5744/64, and the MISO input is driven from SDO. The
SYNC is driven from one of the port lines, in this case PC7.
When data is being transmitted to the AD5744/64, the SYNC
line
Rev. PrA 15-Nov-04| Page 24 of 27
Preliminary Technical Data
(PC7) is taken low and data is transmitted MSB first. Data
appearing on the MOSI output is valid on the falling edge of
SCK. Eight falling clock edges occur in the transmit cycle, so, in
order to load the required ꢀ4-bit word, PC7 is not brought high
until the third 8-bit word has been transferred to the DAC’s
input shift register.
through the SPORT control register and should be configured
as follows: internal clock operation, active low framing, and
ꢀ4-bit word length.
Transmission is initiated by writing a word to the Tx register
after the SPORT has been enabled. As the data is clocked out of
the DSP on the rising edge of SCLK, no glue logic is required to
interface the DSP to the DAC. In the interface shown, the DAC
output is updated using the LDAC pin via the DSP.
Alternatively, the LDAC input could be tied permanently low,
and then the update takes place automatically when TFS is
taken high.
MC68HC11*
AD5744/64*
MISO
MOSI
SCLK
PC7
SDO
SDIN
SCLK
ADSP2101/
ADSP2103*
AD5744/64*
SYNC
DR
DT
SDO
*ADDITIONAL PINS OMITTED FOR CLARITY
SDIN
SCLK
Figure 13. AD5744/64 to MC68HC11 Interface
SCLK
TFS
SYNC
LDAC
LDAC is controlled by the PC6 port output. The DAC can be
updated after each 3-byte transfer by bringing LDAC low. This
example does not show other serial lines for the DAC. If CLR
were used, it could be controlled by port output PC5, for
example.
RFS
FO
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 14. AD5744/64 to ADSPꢀ1ꢂ1/ADSPꢀ1ꢂ3 Interface
AD5744/64 to 8051 Interface
The AD5744/64 requires a clock synchronized to the serial
data. For this reason, the 8ꢂ51 must be operated in Mode ꢂ. In
this mode, serial data enters and exits through RxD, and a shift
clock is output on TxD.
P3.3 and P3.4 are bit programmable pins on the serial port and
are used to drive SYNC and LDAC, respectively.
The 8ꢂ51 provides the LSB of its SBUF register as the first bit in
the data stream. The user must ensure that the data in the SBUF
register is arranged correctly, because the DAC expects MSB
first. When data is to be transmitted to the DAC, P3.3 is taken
low. Data on RxD is clocked out of the microcontroller on the
rising edge of TxD and is valid on the falling edge. As a result,
no glue logic is required between this DAC and the
microcontroller interface.
AD5744/64 to PIC16C6x/7x Interface
The PIC16C6x/7x synchronous serial port (SSP) is configured
as an SPI master with the clock polarity bit set to ꢂ. This is done
by writing to the synchronous serial port control register
(SSPCON). See the PIC16/17 Microcontroller User Manual. In
this example, I/O port RA1 is being used to pulse SYNC and
enable the serial port of the AD5744/64. This microcontroller
transfers only eight bits of data during each serial transfer
operation; therefore, three consecutive write operations are
needed. Figure 15 shows the connection diagram.
PIC16C6x/7x*
AD5744/64*
SDI/RC4
SDO/RC5
SCLK/RC3
RA1
SDO
SDIN
SCLK
The 8ꢂ51 transmits data in 8-bit bytes with only eight falling
clock edges occurring in the transmit cycle. Because the DAC
expects a ꢀ4-bit word, SYNC (P3.3) must be left low after the
first eight bits are transferred. After the third byte has been
transferred, the P3.3 line is taken high. The DAC may be
updated using LDAC via P3.4 of the 8ꢂ51.
SYNC
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 15. AD5744/64 to PIC16C6x/7x Interface
AD5744/64 to ADSP2101/ADSP2103 Interface
An interface between the AD5744/64 and the ADSPꢀ1ꢂ1/
ADSPꢀ1ꢂ3 is shown in Figure 14. The ADSPꢀ1ꢂ1/ADSPꢀ1ꢂ3
should be set up to operate in the SPORT transmit alternate
framing mode. The ADSPꢀ1ꢂ1/ADSPꢀ1ꢂ3 are programmed
Rev. PrA 15-Nov-04| Page 25 of 27
Preliminary Technical Data
EVAꢀUATION BOARD
The AD5744/64 comes with a full evaluation board to aid
designers in evaluating the high performance of the part with a
minimum of effort. All that is required with the evaluation
board is a power supply, and a PC. The AD5744/64 evaluation
kit includes a populated, tested AD5744/64 printed circuit
board. The evaluation board interfaces to the USB interface of
the PC. Software is available with the evaluation board, which
allows the user to easily program the AD5744/64. The software
runs on any PC that has Microsoft Windows® 98/ꢀꢂꢂꢂ/NT/XP
installed.
An application note is available that gives full details on
operating the evaluation board.
Rev. PrA 15-Nov-04| Page 26 of 27
Preliminary Technical Data
OUTLINE DIMENSIONS
1.20
MAX
9.00 SQ
0.75
0.60
0.45
24
17
16
25
TOP VIEW
(PINS DOWN)
7.00
SQ
32
9
1
8
0.15
0.05
0.80
BSC
0.45
0.37
0.30
1.05
1.00
0.95
7°
0°
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MS-026ABA
Figure 16. 3ꢀ-Lead Thin Quad Flatpack [TQFP]
(SU-3ꢀ)
Dimensions shown in millimeters
ORDERING GUIDE
Model
Function
INꢀ
1 LSB Max
Package Description
32-Lead TQFP
32-Lead TQFP
32-Lead TQFP
32-Lead TQFP
32-Lead TQFP
32-Lead TQFP
Package Option
SU-32
SU-32
SU-32
SU-32
AD5764CSU
AD5764BSU
AD5764ASU
AD5744CSU
AD5744BSU
AD5744ASU
Quad 16-Bit DAC
Quad 16-Bit DAC
Quad 16-Bit DAC
Quad 14-Bit DAC
Quad 14-Bit DAC
Quad 14-Bit DAC
2 LSB Max
4 LSB Max
1 LSB Max
2 LSB Max
4 LSB Max
SU-32
SU-32
©
2004 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
PR05303-0-11/04(PrA)
Rev. PrA 15-Nov-04| Page 27 of 27
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