AD713SQ/883B [ADI]

Quad Precision, Low Cost, High Speed, BiFET Op Amp; 四路精密，低成本，高速， BiFET运算放大器


型号：	AD713SQ/883B
厂家：	ADI
描述：	Quad Precision, Low Cost, High Speed, BiFET Op Amp 四路精密，低成本，高速， BiFET运算放大器运算放大器放大器电路
文件：	总14页 (文件大小：454K)
中文：	中文翻译
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Quad Precision, Low Cost,

High Speed, BiFET Op Amp

AD713

FEATURES

CONNECTION DIAGRAMS

Enhanced Replacement for LF347 and TL084

AC PERFORMANCE

1 ms Settling to 0.01% for 10 V Step

20 V/ms Slew Rate

0.0003% Total Harmonic Distortion (THD)

4 MHz Unity Gain Bandwidth

Plastic (N) and

Cerdip (Q) Packages

SOIC (R) Package

DC PERFORMANCE

0.5 mV max Offset Voltage (AD713K)

20 mV/°C max Drift (AD713K)

200 V/mV min Open Loop Gain (AD713K)

2 mV p-p typ Noise, 0.1 Hz to 10 Hz

True 14-Bit Accuracy

Single Version: AD711, Dual Version: AD712

Available in 16-Pin SOIC, 14-Pin Plastic DIP and

Hermetic Cerdip Packages

OUTPUT

–IN

OUTPUT

–IN

+IN

OUTPUT

13 –IN

+IN

AD713

+IN

11 –V

–V

+IN

(TOPVIEW)

AD713

+IN

–IN

(TOPVIEW)

10 +IN

–IN

+IN

–IN

OUTPUT

Standard Military Drawing Available

NC = NO CONNECT

APPLICATIONS

Active Filters

Quad Output Buffers for 12- and 14-Bit DACs

Input Buffers for Precision ADCs

Photo Diode Preamplifier Application

The AD713 is offered in a 16-pin SOIC, 14-pin plastic DIP and

hermetic cerdip package.

PRODUCT DESCRIPTION

PRODUCT HIGHLIGHTS

The AD713 is a quad operational amplifier, consisting of four

AD711 BiFET op amps. These precision monolithic op amps

offer excellent dc characteristics plus rapid settling times, high

slew rates, and ample bandwidths. In addition, the AD713

provides the close matching ac and dc characteristics inherent

to amplifiers sharing the same monolithic die.

1. The AD713 is a high speed BiFET op amp that offers excellent

performance at competitive prices. It upgrades the perfor-

mance of circuits using op amps such as the TL074, TL084,

LT1058, LF347 and OPA404.

2. Slew rate is 100% tested for a guaranteed minimum of

16 V/µs (J, A and S Grades).

The single-pole response of the AD713 provides fast settling:

l µs to 0.01%. This feature, combined with its high dc precision,

makes the AD713 suitable for use as a buffer amplifier for 12-

or 14-bit DACs and ADCs. It is also an excellent choice for use

in active filters in 12-, 14- and 16-bit data acquisition systems.

Furthermore, the AD713’s low total harmonic distortion (THD)

level of 0.0003% and very close matching ac characteristics

make it an ideal amplifier for many demanding audio applications.

3. The combination of Analog Devices’ advanced processing

technology, laser wafer drift trimming and well-matched

ion-implanted JFETs provides outstanding dc precision.

Input offset voltage, input bias current and input offset cur-

rent are specified in the warmed-up condition and are 100%

tested.

4. Very close matching of ac characteristics between the four

amplifiers makes the AD713 ideal for high quality active filter

applications.

The AD713 is internally compensated for stable operation at

unity gain and is available in seven performance grades. The

AD713J and AD713K are rated over the commercial temperature

range of 0°C to 70°C. The AD713A and AD713B are rated

over the industrial temperature of –40°C to +85°C. The

AD713S and AD713T are rated over the military temperature

range of –55°C to +125°C and are available processed to

standard microcircuit drawings.

REV. C

Information furnished by Analog Devices is believed to be accurate and

reliable. However, no responsibility is assumed by Analog Devices for its

use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat

may result from its use. No license is granted by implication or otherwise

under any patent or patent rights of Analog Devices.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.

Tel: 781/329-4700

Fax: 781/326-8703

www.analog.com

(V = ؎15 V @ T = 25؇C unless otherwise noted)

AD713–SPECIFICATIONS

AD713J/A/S

Typ

AD713K/B/T

Typ

Parameter

Conditions

Min

Max

Min

Max

0.5

0.7/0.7/1.0 mV

20/20/15

Unit

INPUT OFFSET VOLTAGE¹

Initial Offset

Offset

vs. Temp

vs. Supply

0.3

0.5

1.5

2/2/2

0.2

0.4

_MINto T_MAX

µV/°C

76/76/76

100

µV/Month

_MINto T_MAX

Long-Term Stability

INPUT BIAS CURRENT²

V_CM= 0 V

_CM= 0 V @ T_MAX

V_CM= ±10 V

_CM= 0 V

V_CM= 0 V @ T_MAX

150

3.4/9.6/154

200

1.7/4.8/77 nA

120

INPUT OFFSET CURRENT

1.7/4.8/77

0.8/2.2/36 nA

MATCHING CHARACTERISTICS

Input Offset Voltage

0.5

0.7

1.8

2.3/2.3/2.3

0.4

0.6

0.8

_MINto T_MAX

1.0/1.0/1.3 mV

–130

Input Offset Voltage Drift

Input Bias Current

Crosstalk

µV/°C

100

–130

–95

f = 1 kHz

f = 100 kHz

–95

FREQUENCY RESPONSE

Small Signal Bandwidth

Full Power Response

Slew Rate

Settling Time to 0.01%

Total Harmonic Distortion

Unity Gain

3.0

4.0

200

1.0

0.0003

3.4

4.0

200

1.0

0.0003

MHz

kHz

V/µs

µs

_O= 20 V p-p

Unity Gain

1.2

f = 1 kHz; R_L≥ 2 kΩ;

V_O= 3 V rms

INPUT IMPEDANCE

Differential

Common Mode

3×10¹²ʈ5.5

ΩʈpF

INPUT VOLTAGE RANGE

Differential³

±20

+14.5, –11.5

±20

+14.5, –11.5

Common-Mode Voltage⁴

T_MINto T_MAX

–11

76/76/76

70/70/70

+13

–11

+13

Common Mode

Rejection Ratio

_CM= ±10 V

_MINto T_MAX

_CM= ±11 V

T_MINto T_MAX

INPUT VOLTAGE NOISE

0.1 Hz to 10 Hz

f = 10 Hz

f = 100 Hz

f = 1 kHz

µV p-p

nV/√Hz

f = 10 kHz

INPUT CURRENT NOISE

OPEN-LOOP GAIN

f = 1 kHz

0.01

400

0.01

400

pA/√Hz

_O= ±10 V; R_L≥ 2 kΩ 150

200

100

V/mV

T_MINto T_MAX

100/100/100

OUTPUT CHARACTERISTICS

Voltage

_L≥ 2 kΩ

+13, –12.5

+13.9, –13.3

+13, –12.5 +13.9, –13.3

_MINto T_MAX

±12/±12/؎12 +13.8, –13.1

؎12

+13.8, –13.1

Current

Short Circuit

POWER SUPPLY

Rated Performance

Operating Range

Quiescent Current

±15

؎4.5

؎18

13.5

؎4.5

؎18

12.0

10.0

120

TRANSISTOR COUNT

# of Transistors

120

NOTES

¹Input Offset Voltage specifications are guaranteed after 5 minutes of operation at T_A= 25°C.

²Bias Current specifications are guaranteed maximum at either input after 5 minutes of operation at T_A= 25°C. For higher temperatures, the current doubles every 10°C.

³Defined as voltage between inputs, such that neither exceeds ±10 V from ground.

⁴Typically exceeding –14.1 V negative common-mode voltage on either input results in an output phase reversal.

Specifications subject to change without notice.

–2–

REV. C

AD713

ABSOLUTE MAXIMUM RATINGS^{1, 2}

ORDERING GUIDE

Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 V

Temperature

Range

Package

Description

Package

Option¹

Internal Power Dissipation²

Model

Input Voltage³. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 18 V

Output Short-Circuit Duration

AD713AQ

AD713BQ

AD713JN

AD713JR-16

AD713JR-16-REEL

–40°C to +85°C

0°C to 70°C

14-Pin Ceramic DIP Q-14

(For One Amplifier) . . . . . . . . . . . . . . . . . . . . . . . . Indefinite

Differential Input Voltage . . . . . . . . . . . . . . . . . . +V_Sand –V_S

Storage Temperature Range (Q) . . . . . . . . . . –65°C to +150°C

Storage Temperature Range (N, R) . . . . . . . . –65°C to +125°C

Operating Temperature Range

AD713J/K . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to 70°C

AD713A/B . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C

AD713S/T . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to +125°C

Lead Temperature Range (Soldering 60 sec) . . . . . . . . . . 300°C

14-Pin Plastic DIP

N-14

16-Pin Plastic SOIC R-16

AD713JR-16-REEL7 0°C to 70°C

AD713KN

0°C to 70°C

14-Pin Plastic DIP

N-14

AD713SQ²

–55°C to +125°C 14-Pin Ceramic DIP Q-14

AD713TQ²

5962-9063301MCA

5962-9063302MCA²–55°C to +125°C 14-Pin Ceramic DIP Q-14

¹N = Plastic DIP; Q = Cerdip; R = Small Outline IC (SOIC).

NOTES

²Not for new designs. Obsolete April 2002.

¹Stresses above those listed under “Absolute Maximum Ratings” may cause perma-

nent damage to the device. This is a stress rating only and functional operation of

the device at these or any other conditions above those indicated in the operational

section of this specification is not implied. Exposure to absolute maximum rating

conditions for extended periods may affect device reliability.

²Thermal Characteristics:

14-Pin Plastic Package:

14-Pin Cerdip Package:

_JC= 30°C/Watt; θ_JA= 100°C/Watt

_JC= 30°C/Watt; θ_JA= 110°C/Watt

16-Pin SOIC Package:

θ_JC= 30°C/

Watt; θ_JA= 100°C/Watt

³For supply voltages less than 18 V, the absolute maximum input voltage is equal

to the supply voltage.

CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily

accumulate on the human body and test equipment and can discharge without detection. Although

the AD713 features proprietary ESD protection circuitry, permanent damage may occur on devices

subjected to high-energy electrostatic discharges. Therefore, proper ESD precautions are

recommended to avoid performance degradation or loss of functionality.

WARNING!

ESD SENSITIVE DEVICE

REV. C

–3–

AD713

–Typical Performance Characteristics

TPC 2. Output Voltage Swing vs.

Supply Voltage

TPC 1. Input Voltage Swing vs.

Supply Voltage

TPC 3. Output Voltage Swing vs.

Load Resistance

TPC 5. Input Bias Current

vs. Temperature

TPC 6. Output Impedance vs.

Frequency, G = 1

TPC 4. Quiescent Current

vs. Supply Voltage

TPC 8. Short-Circuit Current Limit

vs. Temperature

TPC 9. Gain Bandwidth Product

vs. Temperature

TPC 7. Input Bias Current

vs. Common Mode Voltage

–4–

REV. C

Typical Performance Characteristics–AD713

TPC 11. Open-Loop Gain vs.

Supply Voltage

TPC 12. Power Supply Rejection

vs. Frequency

TPC 10. Open-Loop Gain and

Phase Margin vs. Frequency

TPC 14. Large Signal Frequency

Response

TPC 13. Common Mode Rejection

vs. Frequency

TPC 15. Output Swing and

Error vs. Settling Time

TPC 18. Slew Rate vs. Input

Error Signal

TPC 17. Input Noise Voltage

Spectral Density

TPC 16. Total Harmonic Distortion

vs. Frequency

–5–

REV. C

AD713

TPC 19. Crosstalk Test Circuit

TPC 20. Crosstalk vs. Frequency

TPC 21a. Unity Gain Follower

TPC 21b. Unity Gain Follower

Pulse Response (Large Signal)

TPC 22b. Unity Gain Inverter

Pulse Response (Large Signal)

TPC 22a. Unity Gain Inverter

TPC 21c. Unity Gain Follower Pulse

Response (Small Signal)

TPC 22c. Unity Gain Inverter Pulse

Response (Small Signal)

–6–

REV. C

AD713

MEASURING AD713 SETTLING TIME

The error signal is thus clamped twice: once to prevent overload-

ing amplifier A2 and then a second time to avoid overloading the

oscilloscope preamp. A Tektronix oscilloscope preamp type 7A26

was carefully chosen because it recovers from the approximately

0.4 V overload quickly enough to allow accurate measurement

of the AD713’s 1 µs settling time. Amplifier A2 is a very high

speed FET input op amp; it provides a voltage gain of 10, am-

plifying the error signal output of the AD713 under test (providing

an overall gain of 5).

The photos of Figures 2 and 3 show the dynamic response of

the AD713 while operating in the settling time test circuit of

Figure 1. The input of the settling time fixture is driven by a

flat-top pulse generator. The error signal output from the false

summing node of A1, the AD713 under test, is clamped, ampli-

fied by op amp A2 and then clamped again.

Figure 3. Settling Characteristics to –10 V Step.

Upper Trace: Output of AD713 Under Test (5 V/div).

Lower Trace: Amplified Error Voltage (0.01%/ div)

POWER SUPPLY BYPASSING

The power supply connections to the AD713 must maintain a

low impedance to ground over a bandwidth of 4 MHz or more.

This is especially important when driving a significant resistive

or capacitive load, since all current delivered to the load comes

from the power supplies. Multiple high quality bypass capacitors

are recommended for each power supply line in any critical

application. A 0.1 µF ceramic and a 1 µF electrolytic capacitor

as shown in Figure 4 placed as close as possible to the amplifier

(with short lead lengths to power supply common) will assure

adequate high frequency bypassing in most applications. A

minimum bypass capacitance of 0.1 µF should be used for any

application.

Figure 1. Settling Time Test Circuit

Figure 2. Settling Characteristics 0 V to +10 V Step.

Upper Trace: Output of AD713 Under Test (5 V/div).

Lower Trace: Amplified Error Voltage (0.01%/div)

Figure 4. Recommended Power Supply Bypassing

REV. C

–7–

AD713

A HIGH SPEED INSTRUMENTATION AMPLIFIER

CIRCUIT

A HIGH SPEED FOUR OP AMP CASCADED AMPLIFIER

CIRCUIT

The instrumentation amplifier circuit shown in Figure 5 can

provide a range of gains from unity up to 1000 and higher using

only a single AD713. The circuit bandwidth is 1.2 MHz at a

gain of 1 and 250 kHz at a gain of 10; settling time for the entire

circuit is less than 5 µs to within 0.01% for a 10 V step, (G = 10).

Other uses for amplifier A4 include an active data guard and an

active sense input.

Figure 7 shows how the four amplifiers of the AD713 may be

connected in cascade to form a high gain, high bandwidth am-

plifier. This gain of 100 amplifier has a –3 dB bandwidth greater

than 600 kHz.

Figure 7. A High Speed Four Op Amp Cascaded

Amplifier Circuit

Figure 5. A High Speed Instrumentation Amplifier Circuit

Table I provides a performance summary for this circuit. The

photo of Figure 6 shows the pulse response of this circuit for a

gain of 10.

Table I. Performance Summary for the High Speed

Instrumentation Amplifier Circuit

Gain

R_G

Bandwidth

T Settle (0.01%)

20 kΩ

4.04 kΩ

1.2 MHz

1.0 MHz

0.25 MHz

2 µs

5 µs

Figure 8. THD Test Circuit

HIGH SPEED OP AMP APPLICATIONS AND

TECHNIQUES

DAC Buffers (I-to-V Converters)

The wide input dynamic range of JFET amplifiers makes them

ideal for use in both waveform reconstruction and digital-audio

DAC applications. The AD713, in conjunction with the AD1860

DAC, can achieve 0.0016% THD (here at a 4fs or a 176.4 kHz

update rate) without requiring the use of a deglitcher. Just such

a circuit is shown in Figure 9. The 470 pF feedback capacitor

used with IC2a, along with op amp IC2b and its associated

components, together form a 3-pole low-pass filter. Each or all

of these poles can be tailored for the desired attenuation and

phase characteristics required for a particular application. In this

application, one half of an AD713 serves each channel in a two-

channel stereo system.

Figure 6. The Pulse Response of the High Speed

Instrumentation Amplifier. Gain = 10

–8–

REV. C

AD713

Figure 9. A D/A Converter Circuit for Digital Audio

Figure 11. The AD713 as an ADC Buffer

Figure 10. Harmonic Distortion as Frequency for the

Digital Audio Circuit of Figure 9

Most IC amplifiers exhibit a minimum open loop output imped-

ance of 25 Ω, due to current limiting resistors. A few hundred

microamps reflected from the change in converter loading can

introduce errors in instantaneous input voltage. If the A/D con-

version speed is not excessive and the bandwidth of the amplifier

is sufficient, the amplifier’s output will return to the nominal

value before the converter makes its comparison. However,

many amplifiers have relatively narrow bandwidths, yielding

slow recovery from output transients. The AD713 is ideally

suited as a driver for A/D converters since it offers both a wide

bandwidth and a high open loop gain.

Driving the Analog Input of an A/D Converter

An op amp driving the analog input of an A/D converter, such

as that shown in Figure 11, must be capable of maintaining a

constant output voltage under dynamically changing load condi-

tions. In successive approximation converters, the input current

is compared to a series of switched trial currents. The compari-

son point is diode clamped but may vary by several hundred

millivolts, resulting in high frequency modulation of the A/D

input current. The output impedance of a feedback amplifier is

made artificially low by its loop gain. At high frequencies, where

the loop gain is low, the amplifier output impedance can ap-

proach its open loop value.

REV. C

–9–

AD713

Figure 12. Buffer Recovery Time Source Current = 2 mA

Figure 15. Transient Response, R_L= 2 kΩ, C_L= 500 pF

CMOS DAC APPLICATIONS

The AD713 is an excellent output amplifier for CMOS DACs.

It can be used to perform both 2 and 4 quadrant operation. The

output impedance of a DAC using an inverted R-2R ladder

approaches R for codes containing many “1”s, 3R for codes con-

taining a single “1” and infinity for codes containing all zeros.

For example, the output resistance of the AD7545 will modu-

late between 11 kΩ and 33 kΩ. Therefore, with the DAC’s

internal feedback resistance of 11 kΩ, the noise gain will vary

from 2 to 4/3. This changing noise gain modulates the effect of

the input offset voltage of the amplifier, resulting in nonlinear

DAC amplifier performance. The AD713, with its guaranteed

1.5 mV input offset voltage, minimizes this effect achieving

12-bit performance.

Figure 13. Buffer Recovery Time Sink Current = 1 mA

Driving A Large Capacitive Load

The circuit of Figure 14 employs a 100 Ω isolation resistor which

enables the amplifier to drive capacitive loads exceeding 1500 pF;

the resistor effectively isolates the high frequency feedback from

the load and stabilizes the circuit. Low frequency feedback is

returned to the amplifier summing junction via the low pass filter

formed by the 100 Ω series resistor and the load capacitance, C1.

Figure 15 shows a typical transient response for this connection.

Figures 16 and 17 show the AD713 and a 12-bit CMOS DAC,

the AD7545, configured for either a unipolar binary (2-quadrant

multiplication) or bipolar (4-quadrant multiplication) operation.

Capacitor C1 provides phase compensation which reduces over-

shoot and ringing.

Figure 16. Unipolar Binary Operation

Figure 14. Circuit for Driving a Large Capacitance Load

Table II. Recommended Trim Resistor Values vs.

Grades for AD7545 for V_D= 5 V

Trim

Resistor SD

JN/AQ/

KN/BQ/ LN/CQ/

GLN/GCQ/

GUD

500 Ω

150 Ω

200 Ω

68 Ω

100 Ω

33 Ω

20 Ω

6.8 Ω

Figure 17. Bipolar Operation

–10–

REV. C

AD713

Figure 18. A Programmable State Variable Filter Circuit

19 and 21 show the AD713 used in two typical active filters.

The first shows a single AD713 simulating two coupled inductors

configured as a one-third octave bandpass filter. A single section

of this filter meets ANSI class II specifications and handles a

7.07 V rms signal with <0.002% THD (20 Hz–20 kHz).

FILTER APPLICATIONS

A Programmable State Variable Filter

For the state variable or universal filter configuration of Figure

18 to function properly, DACs A1 and B1 need to control the

gain and Q of the filter characteristic, while DACs A2 and B2

must accurately track for the simple expression of f_Cto be true.

This is readily accomplished using two AD7528 DACs and one

AD713 quad op amp. Capacitor C3 compensates for the effects

of op amp gain-bandwidth limitations.

Figure 21 shows a 7-pole antialiasing filter for a 2 ϫ oversam-

pling (88.2 kHz) digital audio application. This filter has <0.05

dB pass band ripple and 19.8 ±0.3 µs delay, dc-20 kHz and will

handle a 5 V rms signal (V_S= ±15 V) with no overload at any

internal nodes.

This filter provides low pass, high pass and band pass outputs

and is ideally suited for applications where microprocessor

control of filter parameters is required. The programmable

range for component values shown is f_C= 0 to 15 kHz and

Q = 0.3 to 4.5.

The filter of Figure 19 can be scaled for any center frequency by

using the formula:

1.11

2πRC

f_C

where all resistors and capacitors scale equally. Resistors R3–R8

should not be greater than 2 kΩ in value, to prevent parasitic

oscillations caused by the amplifier’s input capacitance.

GIC and FDNR FILTER APPLICATIONS

The closely matched and uniform ac characteristics of the

AD713 make it ideal for use in GIC (gyrator) and FDNR (fre-

quency dependent negative resistor) filter applications. Figures

Figure 19. A 1/3 Octave Filter Circuit

–11–

REV. C

AD713

If this is not practical, small lead capacitances (10–20 pF)

should be added across R5 and R6. Figures 20 and 22 show the

output amplitude vs. frequency of these filters.

Figure 22. Relative Output Amplitude vs. Frequency

of Antialiasing Filter

Figure 20. Output Amplitude vs. Frequency of 1/3

Octave Filter

Figure 21. An Antialiasing Filter

–12–

REV. C

AD713

OUTLINE DIMENSIONS

Dimensions shown in inches and (mm).

16-Pin SOIC (R-16) Package

14-Pin Plastic (N-14A) DIP Package

14-Pin Cerdip (Q-14) Package

REV. C

–13–

Revision History

Location

Page

10/01—Data Sheet changed from REV. B to REV. C.

Edits to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Edits to PRODUCT DESCRIPTION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Edits to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3

Edits to METALLIZATION PHOTOGRAPH . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3

–14–

AD713SQ/883B [ADI]

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