AD7781BRZ [ADI]
20-Bit, Pin-Programmable, Low Power Sigma-Delta ADC; 20位，引脚可编程，低功耗Σ-Δ型ADC
| 型号： | AD7781BRZ |
| 厂家： | 
ADI |
| 描述： | 20-Bit, Pin-Programmable, Low Power Sigma-Delta ADC |
| 文件： | 总16页 (文件大小：394K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
20-Bit, Pin-Programmable,
Low Power Sigma-Delta ADC
AD7781
FUNCTIONAL BLOCK DIAGRAM
FEATURES
AV
GND
GAIN
REFIN(+) REFIN(–)
DD
Pin-programmable filter response
Update rate: 10 Hz or 16.7 Hz
Pin-programmable in-amp gain
Pin-programmable power-down and reset
Status function
AIN(+)
DOUT/RDY
SCLK
G = 1
OR 128
20-BIT Σ-Δ
ADC
AIN(–)
DV
DD
Internal clock oscillator
Internal bridge power-down switch
Current
BPDSW
INTERNAL
CLOCK
FILTER
PDRST
AD7781
115 μA typical (gain = 1)
Figure 1.
330 μA typical (gain = 128)
Simultaneous 50 Hz/60 Hz rejection
Power supply: 2.7 V to 5.25 V
−40°C to +105°C temperature range
Independent interface power supply
Packages
14-lead, narrow body SOIC
16-lead TSSOP
2-wire serial interface (read-only device)
SPI compatible
Table 1.
Parameter
Output Data Rate 10 Hz
RMS Noise
C Grade
B Grade
P-P Resolution
C Grade
Gain = 128
Gain = 1
10 Hz 16.7 Hz
16.7 Hz
44 nV
55 nV
65 nV
90 nV
2.4 μV
2.4 μV
2.7 μV
2.7 μV
17.6
17.3
17.1
16.6
18.8
18.7
B Grade
18.8
18.7
Schmitt trigger on SCLK
Settling Time
300 ms
120 ms
300 ms
120 ms
APPLICATIONS
Weigh scales
Pressure measurement
Industrial process control
Portable instrumentation
GENERAL DESCRIPTION
The AD7781 is a complete, low power front-end solution for
bridge sensor products, including weigh scales, strain gages,
and pressure sensors. It contains a precision, low power, 20-bit
sigma-delta (Σ-Δ) ADC, an on-chip, low noise programmable
gain amplifier (PGA), and an on-chip oscillator.
The on-chip PGA has a gain of 1 or 128, supporting a full-scale
differential input of ±± ꢀ or ±3ꢁ mꢀ. The device has two filter
response options. The filter response at the 16.7 Hz update rate
provides superior dynamic performance. The settling time is
120 ms at this update rate. At the 10 Hz update rate, the filter
response provides better than −4± dB of stop-band attenuation.
In load cell applications, this stop-band rejection is useful to
reject low frequency mechanical vibrations of the load cell. The
settling time is 300 ms at this update rate. Simultaneous ±0 Hz/
60 Hz rejection occurs at both the 10 Hz and 16.7 Hz update rates.
Consuming only 330 μA, the AD7781 is particularly suitable for
portable or battery-operated products where very low power is
required. The AD7781 also has a power-down mode that allows
the user to switch off the power to the bridge sensor and power
down the AD7781 when not converting, thus increasing the
battery life of the product.
The AD7781 operates with a power supply from 2.7 ꢀ to ±.2± ꢀ.
It is available in a narrow body, 14-lead SOIC package and in a
16-lead TSSOP package.
For ease of use, all the features of the AD7781 are controlled by
dedicated pins. Each time that a data read occurs, eight status bits
are appended to the 20-bit conversion. These status bits contain a
pattern sequence that can be used to confirm the validity of the
serial transfer.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
©2009 Analog Devices, Inc. All rights reserved.
AD7781
TABLE OF CONTENTS
Features .............................................................................................. 1
Gain.............................................................................................. 11
PDRST
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Timing Characteristics ................................................................ ±
Absolute Maximum Ratings............................................................ 6
Thermal Resistance ...................................................................... 6
ESD Caution.................................................................................. 6
Pin Configurations and Function Descriptions ........................... 7
Typical Performance Characteristics ............................................. 8
Output Noise and Resolution........................................................ 10
Theory of Operation ...................................................................... 11
Filter, Data Rate, and Settling Time ......................................... 11
Power-Down/Reset (
) ................................................... 12
Analog Input Channel ............................................................... 12
Bipolar Configuration................................................................ 12
Data Output Coding .................................................................. 12
Reference ..................................................................................... 12
Bridge Power-Down Switch...................................................... 12
Digital Interface.......................................................................... 13
Applications Information.............................................................. 14
Weigh Scales................................................................................ 14
AD7781 Performance in a Weigh Scale System......................... 14
EMI Recommendations............................................................. 14
Grounding and Layout .............................................................. 1±
Outline Dimensions....................................................................... 16
Ordering Guide .......................................................................... 16
REVISION HISTORY
5/09—Revision 0: Initial Version
Rev. 0 | Page 2 of 16
AD7781
SPECIFICATIONS
AꢀDD = 2.7 ꢀ to ±.2± ꢀ, ꢀREF = AꢀDD, DꢀDD = 2.7 ꢀ to ±.2± ꢀ, GND = 0 ꢀ, all specifications TMIN to TMAX, unless otherwise noted.1
Table 2.
Parameter
Min
Typ
Max
Unit
Test Conditions/Comments
ADC CHANNEL
Output Update Rate (fADC
)
10
16.7
Hz
Hz
FILTER = 1, settling time = 3/fADC
FILTER = 0, settling time = 2/fADC
No Missing Codes2
Resolution, Peak-to-Peak
RMS Noise
20
Bits
See Table 7 and Table 8
See Table 7 and Table 8
Integral Nonlinearity
Offset Error
6
6
200
ppm FSR
ꢀV
ꢀV
ꢀV
ꢀV
nV/°C
nV/°C
nV/°C
% of FS
ppm/°C
dB
Gain = 128 with FILTER = 1
Gain = 1 with FILTER = 1
Gain = 128 with FILTER = 0
Gain = 1 with FILTER = 0
Gain = 128
1
10
10
150
10
0.25
2
Offset Error Drift vs. Temperature
Gain = 1 with FILTER = 1
Gain = 1 with FILTER = 0
Full-Scale Error
Gain Drift vs. Temperature
Power Supply Rejection
100
120
Gain = 128, FILTER = 1, AIN = 7.81 mV
Gain = 128, FILTER = 0, AIN = 7.81 mV
dB
Normal Mode Rejection2
50 Hz, 60 Hz
63
72
75
90
dB
dB
50 Hz 1 Hz, 60 Hz 1 Hz, fADC = 16.7 Hz
50 Hz 1 Hz, 60 Hz 1 Hz, fADC = 10 Hz
Common-Mode Rejection
DC
90
90
110
dB
dB
dB
Gain = 1, AIN = 1 V
Gain = 128, AIN = 7.81 mV
50 Hz 1 Hz, 60 Hz 1 Hz
50 Hz, 60 Hz
ANALOG INPUTS
Differential Input Voltage Range
VREF/gain
V
VREF = REFIN(+) − REFIN(−),
gain = 1 or 128
Gain = 1
Gain = 128, FILTER = 0
Gain = 128, FILTER = 1, AVDD ≤ 3.6 V
Gain = 128, FILTER = 1, AVDD > 3.6 V
Gain = 1
Absolute AIN Voltage Limits2
GND + 100 mV
GND + 450 mV
GND + 1.1
AVDD − 100 mV
AVDD − 1.1
AVDD − 1.1
AVDD − 1.5
V
V
V
V
GND + 1.5
Average Input Current
1
250
3
nA
pA
pA/°C
Gain = 128
Average Input Current Drift
REFERENCE
External REFIN Voltage
AVDD
V
REFIN = REFIN(+) − REFIN(−)
Reference Voltage Range2
Absolute REFIN Voltage Limits2
Average Reference Input Current
Average Reference Input Current
Drift
0.5
AVDD
AVDD + 30 mV
V
V
GND − 30 mV
400
0.15
nA/V
nA/V/°C
Normal Mode Rejection
Common-Mode Rejection
Same as for analog inputs
110
dB
BRIDGE POWER-DOWN SWITCH
(BPDSW)
Controlled via the PDRST pin
RON
9
30
Ω
mA
Allowable Current2
Continuous current
Rev. 0 | Page 3 of 16
AD7781
Parameter
Min
Typ
Max
Unit
Test Conditions/Comments
INTERNAL CLOCK
Frequency
Duty Cycle
64 − 3%
64 + 3%
kHz
%
50:50
LOGIC INPUTS
SCLK, FILTER, GAIN, PDRST2
Input Low Voltage, VINL
0.4
0.8
V
V
V
V
DVDD = 3 V
DVDD = 5 V
DVDD = 3 V
DVDD = 5 V
Input High Voltage, VINH
1.8
2.4
SCLK (Schmitt-Triggered Input)
Hysteresis2
100
140
2
mV
mV
ꢀA
pF
DVDD = 3 V
DVDD = 5 V
VIN = DVDD or GND
All digital inputs
Input Currents
Input Capacitance
10
LOGIC OUTPUT (DOUT/RDY)
2
Output High Voltage, VOH
DVDD − 0.6
4
V
V
V
V
DVDD = 3 V, ISOURCE = 100 ꢀA
DVDD = 5 V, ISOURCE = 200 ꢀA
DVDD = 3 V, ISINK = 100 ꢀA
DVDD = 5 V, ISINK = 1.6 mA
2
Output Low Voltage, VOL
0.4
0.4
Floating-State Leakage Current
Floating-State Output Capacitance
Data Output Coding
POWER REQUIREMENTS3
Power Supply Voltage
AVDD to GND
2
10
ꢀA
pF
Offset binary
2.7
2.7
5.25
5.25
V
V
DVDD to GND
Power Supply Currents
IDD Current
Gain = 1
115
130
300
350
330
420
10
ꢀA
ꢀA
ꢀA
ꢀA
ꢀA
ꢀA
ꢀA
AVDD = 3 V
AVDD = 5 V
AVDD = 3 V
AVDD = 5 V
AVDD = 3 V
AVDD = 5 V
160
400
500
Gain = 128 (B Grade)
Gain = 128 (C Grade)
IDD (Power-Down/Reset Mode)
1 Temperature range is −40°C to +105°C.
2 This specification is not production tested but is supported by characterization data at initial product release.
3 Digital inputs are equal to DVDD or GND.
Rev. 0 | Page 4 of 16
AD7781
TIMING CHARACTERISTICS
AꢀDD = 2.7 ꢀ to ±.2± ꢀ, DꢀDD = 2.7 ꢀ to ±.2± ꢀ, GND = 0 ꢀ, Input Logic 0 = 0 ꢀ, Input Logic 1 = DꢀDD, unless otherwise noted.
Table 3.
Parameter1
Read2
Limit at TMIN, TMAX
Unit
Test Conditions/Comments
t1
t2
t3
100
100
0
60
80
ns min
ns min
ns min
ns max
ns max
ns min
ns max
SCLK high pulse width
SCLK low pulse width
SCLK active edge to data valid delay4
DVDD = 4.75 V to 5.25 V
DVDD = 2.7 V to 3.6 V
SCLK inactive edge to DOUT/RDY high
3
t4
10
130
Reset
t5
100
ns min
PDRST low pulse width
5
t6
FILTER/GAIN change to data valid delay
Update rate = 16.7 Hz
Update rate = 10 Hz
120
300
ms typ
ms typ
1 Sample tested during initial release to ensure compliance. All input signals are specified with tR = tF = 5 ns (10% to 90% of DVDD) and timed from a voltage level of 1.6 V.
2 See Figure 3.
3 The values of t3 are measured using the load circuit of Figure 2 and are defined as the time required for the output to cross the VOL or VOH limits.
4 SCLK active edge is falling edge of SCLK.
5
PDRST
The
high to data valid delay is typically 1 ms longer than t6 because the internal oscillator requires time to power up and settle.
Circuit and Timing Diagrams
I
(1.6mA WITH DV = 5V,
DD
SINK
100µA WITH DV
PDRST
(INPUT)
= 3V)
DD
t5
TO
OUTPUT
PIN
1.6V
50pF
DOUT/RDY
(OUTPUT)
I
(200µA WITH DV = 5V,
DD
SOURCE
100µA WITH DV
= 3V)
DD
Figure 2. Load Circuit for Timing Characterization
Figure 4. Resetting the AD7781
DOUT/RDY
(OUTPUT)
MSB
t3
LSB
t4
GAIN OR FILTER
(INPUT)
t6
t1
DOUT/RDY
(OUTPUT)
SCLK
(INPUT)
t2
Figure 3. Read Cycle Timing Diagram
Figure 5. Changing Gain or Filter Option
Rev. 0 | Page 5 of 16
AD7781
ABSOLUTE MAXIMUM RATINGS
TA = 2±°C, unless otherwise noted.
THERMAL RESISTANCE
θJA is specified for the worst-case conditions, that is, a device
soldered in a circuit board for surface-mount packages.
Table 4.
Parameter
Rating
AVDD to GND
DVDD to GND
−0.3 V to +7 V
−0.3 V to +7 V
−0.3 V to AVDD + 0.3 V
−0.3 V to AVDD + 0.3 V
−0.3 V to DVDD + 0.3 V
−0.3 V to DVDD + 0.3 V
10 mA
−40°C to +105°C
−65°C to +150°C
150°C
Table 5.
Package Type
14-Lead SOIC
16-Lead TSSOP
θJA
θJC
Unit
°C/W
°C/W
Analog Input Voltage to GND
Reference Input Voltage to GND
Digital Input Voltage to GND
Digital Output Voltage to GND
AIN/Digital Input Current
Operating Temperature Range
Storage Temperature Range
Maximum Junction Temperature
Lead Temperature, Soldering Reflow
104.5
150.4
42.9
27.6
ESD CAUTION
260°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Rev. 0 | Page 6 of 16
AD7781
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
NC
SCLK
NC
SCLK
DOUT/RDY
NC
1
2
3
4
5
6
7
14 FILTER
13 PDRST
FILTER
PDRST
DOUT/RDY
NC
AD7781
12 DV
DD
AD7781
DV
AV
DD
DD
TOP VIEW
GAIN
TOP VIEW
11 AV
DD
10 GND
(Not to Scale)
GAIN
(Not to Scale)
AIN(+)
AIN(+)
GND
AIN(–)
9
8
BPDSW
REFIN(–)
AIN(–)
BPDSW
REFIN(–)
REFIN(+)
REFIN(+)
NC = NO CONNECT
NC = NO CONNECT
Figure 6. SOIC Pin Configuration
Figure 7. TSSOP Pin Configuration
Table 6. Pin Function Descriptions
Pin No.
SOIC TSSOP
Mnemonic Description
SCLK
1
2
Serial Clock Input. This serial clock input is for data transfers from the ADC. The SCLK pin has a Schmitt-
triggered input. The serial clock can be active only when transferring data from the AD7781. The data
from the AD7781 can be read as a continuous 32-bit word. Alternatively, SCLK can be noncontinuous
during the data transfer, with the information being transmitted from the ADC in smaller data batches.
2
3
DOUT/RDY Serial Data Output/Data Ready Output. DOUT/RDY serves a dual purpose: as a data ready pin, going low
to indicate the completion of a conversion, and as a serial data output pin to access the data register of
the ADC. Eight status bits accompany each data read (see Figure 22). The DOUT/RDY falling edge can be
used as an interrupt to a processor, indicating that new data is available. If the data is not read after the
conversion, the pin goes high before the next update occurs. The serial interface is reset each time that a
conversion is available. Therefore, the user must ensure that any conversions being transmitted are
completed before the next conversion is available.
3
4
5
6
7
1, 4, 16
NC
GAIN
AIN(+)
AIN(−)
REFIN(+)
No Connect. This pin can be left floating.
5
6
7
8
Gain Select Pin. When GAIN is low, the gain is set to 128. When GAIN is high, the gain is set to 1.
Analog Input. AIN(+) is the positive terminal of the differential analog input pair, AIN(+)/AIN(−).
Analog Input. AIN(−) is the negative terminal of the differential analog input pair, AIN(+)/AIN(−).
Positive Reference Input. An external reference can be applied between REFIN(+) and REFIN(−). The nomi-
nal reference voltage (REFIN(+) − REFIN(−)) is 5 V, but the part can function with a reference of 0.5 V to AVDD
.
8
9
9
10
REFIN(−)
BPDSW
Negative Reference Input.
Bridge Power-Down Switch to GND. When PDRST is high, the bridge power-down switch is closed.
When PDRST is low, the switch is opened.
10
11
12
11
12
13
GND
AVDD
DVDD
Ground Reference Point.
Supply Voltage, 2.7 V to 5.25 V.
Digital Interface Supply Voltage. The logic levels for the serial interface pins and the digital control pins
are related to this supply, which is between 2.7 V and 5.25 V. The DVDD voltage is independent of the
voltage on AVDD; therefore, AVDD can equal 5 V with DVDD at 3 V or vice versa.
13
14
14
15
PDRST
FILTER
Power-Down/Reset. When this pin is low, the ADC is placed in power-down mode, and the low-side power
switch is opened. All the logic on the chip is reset, and the DOUT/RDY pin is tristated. When PDRST is high,
the ADC is taken out of power-down mode. The on-chip clock powers up and settles, and the ADC contin-
uously converts. In addition, the low-side power switch is closed. The internal clock requires approximately
1 ms to power up.
Filter Select Pin. When FILTER is low, the fast settling filter is selected. The update rate is set to 16.7 Hz,
which gives a filter settling time of 120 ms. When FILTER is high, the high rejection filter is selected. The
update rate is set to 10 Hz, which gives a filter settling time of 300 ms. With this filter, the stop-band
(higher than fADC) attenuation is better than −45 dB.
Rev. 0 | Page 7 of 16
AD7781
TYPICAL PERFORMANCE CHARACTERISTICS
524,294
600
400
200
524,293
524,292
524,291
524,290
524,289
524,288
524,287
524,286
0
0
200
400
600
800
1000
524,275
524,277
524,279
CODE
MORE
SAMPLE
Figure 8. C Grade Noise (VREF = AVDD, Update Rate = 16.7 Hz, Gain = 128)
Figure 11. C Grade Noise Distribution Histogram
(VREF = AVDD, Update Rate = 10 Hz, Gain = 128)
524,289
524,288
500
400
300
200
100
524,287
524,286
0
0
200
400
600
800
1000
524,286
524,288
524,290
CODE
524,292
524,294
SAMPLE
Figure 9. C Grade Noise Distribution Histogram
(VREF = AVDD, Update Rate = 16.7 Hz, Gain = 128)
Figure 12. Noise (VREF = AVDD, Update Rate = 16.7 Hz, Gain = 1)
505
524,281
524,280
524,279
524,278
524,277
500
524,276
524,275
495
524,274
0
524,287
524,288
CODE
200
400
600
800
1000
SAMPLE
Figure 13. Noise Distribution Histogram
Figure 10. C Grade Noise (VREF = AVDD, Update Rate = 10 Hz, Gain = 128)
(VREF = AVDD, Update Rate = 16.7 Hz, Gain = 1)
Rev. 0 | Page 8 of 16
AD7781
524,276
524,275
2.0
1.5
1.0
0.5
0
–0.5
–1.0
–1.5
–2.0
524,274
524,273
0
200
400
600
800
1000
–6
–4
–2
0
2
4
6
SAMPLE
V
(V)
IN
Figure 14. Noise (VREF = AVDD, Update Rate = 10 Hz, Gain = 1)
Figure 17. Integral Nonlinearity (VREF = AVDD, Gain = 1)
800
10
8
6
600
400
200
0
4
2
0
–2
–4
–6
–8
–10
–60
524,274
524,275
CODE
–40
–20
0
20
40
60
80
100
120
TEMPERATURE (°C)
Figure 18. Offset vs. Temperature (Gain = 128)
Figure 15. Noise Distribution Histogram
(VREF = AVDD, Update Rate = 10 Hz, Gain = 1)
3.0
2.5
2.0
1.5
1.0
0.5
0
150
100
50
0
–50
–100
–150
–200
–0.5
–1.0
–1.5
–2.0
–2.5
–0.04 –0.03 –0.02 –0.01
0
0.01
0.02
0.03
0.04
–60
–40
–20
0
20
40
60
80
100
120
V
(V)
TEMPERATURE (°C)
IN
Figure 16. Integral Nonlinearity (VREF = AVDD, Gain = 128)
Figure 19. Gain Error vs. Temperature (Gain = 128)
Rev. 0 | Page 9 of 16
AD7781
OUTPUT NOISE AND RESOLUTION
Table 7 and Table 8 show the rms noise of the AD7781 for the two output data rates and gain settings when using a 3 ꢀ and a ± ꢀ reference.
These numbers are typical and are generated with a differential input voltage of 0 ꢀ. The peak-to-peak (p-p) resolution is also listed. The
p-p resolution represents the resolution for which there is no code flicker. These numbers are typical.
Table 7. RMS Noise and Peak-to-Peak Resolution When AVDD = 3 V and VREF = 3 V
Parameter
Update Rate
RMS Noise
C Grade
Gain = 128
Gain = 1
16.7 Hz
10 Hz
16.7 Hz
10 Hz
44 nV
55 nV
65 nV
90 nV
2.4 μV
2.4 μV
2.7 μV
2.7 μV
B Grade
P-P Resolution
C Grade
B Grade
17.6
17.3
17.1
16.6
18.8
18.8
18.7
18.7
Table 8. RMS Noise and Peak-to-Peak Resolution When AVDD = 5 V and VREF = 5 V
Parameter
Update Rate
RMS Noise
C Grade
Gain = 128
Gain = 1
10 Hz
16.7 Hz
10 Hz
16.7 Hz
49 nV
60 nV
69 nV
90 nV
3.0 μV
3.0 μV
2.7 μV
2.7 μV
B Grade
P-P Resolution
C Grade
B Grade
18.2
17.9
17.7
17.3
19.3
19.3
19.4
19.4
Rev. 0 | Page 10 of 16
AD7781
THEORY OF OPERATION
0
–20
The AD7781 is a low power ADC that incorporates a precision,
20-bit, Σ-ꢂ modulator; a PGA; and an on-chip digital filter
intended for measuring wide dynamic range, low frequency
signals. The part provides a complete front-end solution for
bridge sensor applications such as weigh scales and pressure
sensors.
–40
–60
The device has an internal clock and one buffered differential
input. It offers a choice of two update rates (10 Hz or 16.7 Hz)
and two gain settings (1 or 128). These functions are controlled
using dedicated pins, which makes the interface easy to configure.
A 2-wire interface simplifies data retrieval from the AD7781.
–80
–100
–120
FILTER, DATA RATE, AND SETTLING TIME
0
20
40
60
80
100
120
INPUT SIGNAL FREQUENCY (Hz)
The AD7781 has two filter options. When the FILTER pin is
low, the 16.7 Hz filter is selected; when the FILTER pin is high,
the 10 Hz filter is selected. When the polarity of the FILTER pin
is changed, the AD7781 modulator and filter are reset immedi-
Figure 20. Filter Profile with Update Rate = 16.7 Hz (FILTER = 0)
0
–20
RDY
ately. DOUT/
is set high, and the ADC begins conversions
using the selected filter response. The first conversion requires
the total settling time of the filter. Subsequent conversions
occur at the selected update rate. The settling time of the 10 Hz
filter is 300 ms (three conversion cycles), and the settling time
of the 16.7 Hz filter is 120 ms (two conversion cycles).
–40
–60
When a step change occurs on the analog input, the AD7781
requires several conversion cycles to generate a valid conversion.
If the step change occurs synchronous to the conversion period, the
settling time of the AD7781 must be allowed to generate a valid
conversion. If the step change occurs asynchronous to the end
of a conversion, an extra conversion must be allowed to generate
a valid conversion. The data register is updated with all the con-
versions, but, for an accurate result, the user must allow for the
required time.
–80
–100
–120
0
20
40
60
80
100
120
INPUT SIGNAL FREQUENCY (Hz)
Figure 21. Filter Profile with Update Rate = 10 Hz (FILTER = 1)
GAIN
The AD7781 has two gain options: gain = 1 and gain = 128.
When the GAIN pin is low, the gain is set to 128; when the
GAIN pin is high, the gain is set to 1. The acceptable analog
input range is ±ꢀREF/gain. Thus, with ꢀREF = ± ꢀ, the input range
is ±± ꢀ when GAIN is high and ±3ꢁ mꢀ when GAIN is low.
Figure 20 and Figure 21 show the filter response for each filter.
The 10 Hz filter provides more than −4± dB of rejection in the
stop band. The only external filtering required on the analog
inputs is a simple R-C filter to provide rejection at multiples of
the master clock. A 1 kΩ resistor in series with each analog input,
a 0.01 ꢃF capacitor from each input to GND, and a 0.1 ꢃF
capacitor from AIN(+) to AIN(−) are recommended.
When the polarity of the GAIN pin is changed, the AD7781 modu-
RDY
lator and filter are reset immediately. DOUT/
is set high, and
RDY
RDY
the ADC begins conversions. DOUT/
remains high until
When the filter is changed, DOUT/
goes high and remains
the appropriate settling time for the filter elapses (see Figure ±).
Therefore, the user should complete any read operations before
changing the gain. Otherwise, 1s are read back from the AD7781
RDY
The total settling time of the selected filter is required to generate
the first conversion after the gain change; subsequent conversions
occur at the selected update rate.
high until the appropriate settling time for that filter elapses
(see Figure ±). Therefore, the user should complete any read
operations before changing the filter. Otherwise, 1s are read
RDY
because the DOUT/
pin is set high following the gain change.
back from the AD7781 because the DOUT/
following the filter change.
pin is set high
Rev. 0 | Page 11 of 16
AD7781
The output code for any analog input voltage can be represented as
POWER-DOWN/RESET (PDRST)
Code = 2N − 1 × [(AIN × Gain/VREF) + 1]
PDRST
PDRST
The
When
entire ADC is powered down (including the on-chip clock), the
RDY
pin functions as a power-down pin and a reset pin.
is taken low, the AD7781 is powered down. The
where:
AIN is the analog input voltage.
Gain is 1 or 128.
N = 20.
low-side power switch is opened, and the DOUT/
pin is
tristated. The circuitry and serial interface are also reset, which
resets the logic, the digital filter, and the analog modulator.
REFERENCE
PDRST
must be held low for 100 ns minimum to initiate the
reset function (see Figure 4).
PDRST
The AD7781 has a fully differential input capability for the channel.
The common-mode range for these differential inputs is GND to
AꢀDD. The reference input is unbuffered; therefore, excessive R-C
source impedances introduce gain errors. The reference voltage of
REFIN (REFIN(+) − REFIN(−)) is AꢀDD nominal, but the AD7781
is functional with reference voltages of 0.± ꢀ to AꢀDD. In applica-
tions where the excitation (voltage or current) for the transducer
on the analog input also drives the reference voltage for the part,
the effect of the low frequency noise in the excitation source is
removed because the application is ratiometric. If the AD7781
is used in a nonratiometric application, a low noise reference
should be used.
When
is taken high, the AD7781 is taken out of power-
down mode. When the on-chip clock has powered up (1 ms,
typically), the modulator begins sampling the analog input.
The low-side power switch is closed, and the DOUT/
becomes active.
RDY
pin
A reset is automatically performed on power-up.
ANALOG INPUT CHANNEL
The AD7781 has one differential analog input channel. The
input channel feeds into a high impedance input stage of the
amplifier. Therefore, the input can tolerate significant source
impedances and is tailored for direct connection to external
resistive-type sensors such as strain gages.
Recommended 2.± ꢀ reference voltage sources for the AD7781
include the ADR381 and ADR3ꢁ1, which are low noise, low power
references. These references have low output impedances and
are, therefore, tolerant to decoupling capacitors on REFIN(+)
without introducing gain errors in the system. Deriving the
reference input voltage across an external resistor means that
the reference input sees a significant external source impedance.
External decoupling on the REFIN pins is not recommended in
this type of circuit configuration.
The absolute input voltage range is restricted to a range between
GND + 4±0 mꢀ and AꢀDD − 1.1 ꢀ. Care must be taken in setting
up the common-mode voltage to avoid exceeding these limits.
Otherwise, there is degradation in linearity and noise performance.
The low noise in-amp means that signals of small amplitude can
be amplified within the AD7781, which still maintains excellent
noise performance. The amplifier can be configured to have a gain
of 128 or 1, using the GAIN pin. The analog input range is equal
to ±ꢀREF/gain. The common-mode voltage (AIN(+) + AIN(−))/2
must be ≥0.± ꢀ.
BRIDGE POWER-DOWN SWITCH
The bridge power-down switch (BPDSW) is useful in battery-
powered applications where the optimization of system power
consumption is essential. A 3±0 Ω load cell typically consumes
1± mA when excited with a ± ꢀ power supply. To minimize
current consumption, the load cell is disconnected when it is
not being used. The bridge power-down switch can be included
BIPOLAR CONFIGURATION
The AD7781 accepts a bipolar input range. A bipolar input range
does not imply that the part can tolerate negative voltages with
respect to system GND. Signals on the AIN(+) input are refer-
enced to the voltage on the AIN(−) input. For example, if AIN(−)
is 2.± ꢀ, the analog input range on the AIN(+) input is 2.46 ꢀ to
2.±4 ꢀ for a gain of 128.
in series with the load cell. When
is high, the bridge power-
PDRST
down switch is closed, and the load cell measures the strain. When
is low, the bridge power-down switch is opened so no
PDRST
current flows through the load cell. Therefore, the current
consumption of the system is minimized. The bridge power-
down switch has an on resistance of ꢁ Ω maximum. The switch
is capable of withstanding 30 mA of continuous current.
DATA OUTPUT CODING
The AD7781 uses offset binary coding. Thus, a negative full-
scale voltage results in a code of 000...000, a zero differential
input voltage results in a code of 100...000, and a positive full-
scale input voltage results in a code of 111...111.
Rev. 0 | Page 12 of 16
AD7781
When a conversion is complete, the serial interface is reset, and
the new conversion is placed in the data register. Therefore, the
user must ensure that the complete word is read before the next
conversion is complete.
DIGITAL INTERFACE
The serial interface of the AD7781 consists of two signals: SCLK
RDY
and DOUT/
and data transfers occur with respect to the SCLK signal. The
RDY
. SCLK is the serial clock input for the device,
PDRST
RDY
pin is tristated. When
When
PDRST
is low, the DOUT/
DOUT/
pin and as a data output pin. DOUT/
data-word is available in the output register. A 32-bit word is
RDY
pin is dual purpose: it functions as a data ready
is taken high, the internal clock requires approximately
RDY
goes low when a new
1 ms to power up. Following power-up, the ADC continuously
converts. The first conversion requires the total settling time
placed on the DOUT/
pin when sufficient SCLK pulses are
RDY
PDRST
(see Figure 4). DOUT/
goes high when
is taken
applied. This word consists of a 20-bit conversion result followed
by four 0s to generate a 24-bit word. Following this, status bits
are output. Figure 22 shows the status bits, and Table ꢁ describes
the status bits and their functions.
high and returns low only when a conversion is available. The
ADC then converts continuously, and subsequent conversions
are available at the selected update rate. Figure 3 shows the
timing for a read operation from the AD7781.
RDY FILTER ERR
ID1
ID0
GAIN PAT1 PAT0
When the filter response is changed (using the FILTER pin) or
the gain is changed (using the GAIN pin), the modulator and
Figure 22. Status Bits
RDY
filter are reset immediately (see Figure ±). DOUT/
high. The ADC then begins conversions using the selected filter
RDY
is set
RDY
DOUT/
is reset high when the conversion has been read.
RDY
If the conversion is not read, DOUT/
goes high prior to the
response/gain setting. DOUT/
remains high until the appro-
data register update to indicate when not to read from the device.
This ensures that a read operation is not attempted while the reg-
ister is being updated. Each conversion can be read only once. The
data register is updated for every conversion.
priate settling time for that filter has elapsed. Therefore, the user
should complete any read operations before changing the gain or
update rate. Otherwise, 1s are read back from the AD7781 because
RDY
the DOUT/
pin is set high following the gain/filter change.
Table 9. Status Bit Functions
Bit Name
Description
RDY
Ready bit.
0: a conversion is available.
Filter bit.
FILTER
1: 10 Hz filter is selected.
0: 16.7 Hz filter is selected.
Error bit.
ERR
1: an error occurred during conversion. (An error occurs when the analog input is out of range.)
ID bits.
ID1, ID0
ID1
ID0
Function
0
0
Indicates the ID number for the AD7781.
GAIN
Gain bit.
1: gain = 1.
0: gain = 128.
PAT1, PAT0 Status pattern bits. When the user reads data from the AD7781, a pattern check can be performed.
PAT1
PAT0
Function
0
0
1
1
0
x
Indicates that the serial transfer from the ADC was performed correctly (default).
Indicates that the serial transfer from the ADC was not performed correctly.
Indicates that the serial transfer from the ADC was not performed correctly.
Rev. 0 | Page 13 of 16
AD7781
APPLICATIONS INFORMATION
The AD7781 provides a low cost, high resolution analog-to-
digital function. Because the analog-to-digital function is
provided by a Σ-Δ architecture, the part is more immune to
noisy environments, making it ideal for use in sensor measure-
ment and industrial and process control applications.
(the conversion result from the ADC when the maximum load
is applied to the load cell) must be determined. Subsequent
conversions from the AD7781 are then corrected, using the
offset and gain coefficients that were calculated from these
calibrations.
WEIGH SCALES
AD7781 PERFORMANCE IN A WEIGH SCALE SYSTEM
Figure 23 shows the AD7781 being used in a weigh scale
application. The load cell is arranged in a bridge network and
gives a differential output voltage between its OUT+ and OUT−
terminals. Assuming a ± ꢀ excitation voltage, the full-scale
output range from the transducer is 10 mꢀ when the sensitivity
is 2 mꢀ/ꢀ. The excitation voltage for the bridge can be used to
directly provide the reference for the ADC because the refer-
ence input range includes the supply voltage.
If the load cell has a sensitivity of 2 mꢀ/ꢀ and a ± ꢀ excitation
voltage is used, the full-scale signal from the load cell is 10 mꢀ.
When the AD7781 (C grade) operates with a 10 Hz output data
rate and the gain is set to 128, the device has a p-p resolution of
18.2 bits when the reference is equal to ± ꢀ. Postprocessing the
data from the AD7781 using a microprocessor increases the p-p
resolution. For example, an average by 4 in the microprocessor
increases the accuracy by 2 bits. The noise-free counts value is
equal to
A second advantage of using the AD7781 in transducer-based
applications is that the bridge power-down switch (BPDSW)
can be fully utilized in low power applications. The bridge power-
down switch is connected in series with the low side of the bridge.
In normal operation, the switch is closed and measurements
can be taken. In applications where power is of concern, the
AD7781 can be placed in power-down mode, significantly
reducing the power consumed in the application. In addition,
the bridge power-down switch is opened while in power-down
mode, thus avoiding unnecessary power consumption by the
front-end transducer. When the part is taken out of power-down
mode and the bridge power-down switch is closed, the user should
ensure that the front-end circuitry is fully settled before attempting
to read from the AD7781.
Noise-Free Counts = (2Effective Bits) × (FSLC/FSADC
)
where:
Effective Bits = 18.2 bits (AD7781) + 2 bits (due to postprocessing
in the microprocessor).
FSLC is the full-scale signal from the load cell (10 mꢀ).
FSADC is the full-scale input range when gain = 128 and
ꢀ
REF = ± ꢀ (78 mꢀ).
The noise-free counts is equal to
(218.2 + 2) × (10 mꢀ/78 mꢀ) = 1±4,422
This example shows that with a ± ꢀ supply, 1±4,422 noise-free
counts can be achieved with the AD7781.
EMI RECOMMENDATIONS
The load cell has an offset, or tare, associated with it. This tare is
the main component of the system offset (load cell + ADC) and
is similar in magnitude to the full-scale signal from the load cell.
For this reason, calibrating the offset and gain of the AD7781
alone is not sufficient for optimum accuracy; a system calibration
that calibrates the offset and gain of the ADC, plus the load cell,
is required. A microprocessor can be used to perform the calibra-
tions. The offset error (the conversion result from the AD7781
when no load is applied to the load cell) and the full-scale error
For simplicity, the EMI filters are not included in Figure 23.
However, an R-C antialiasing filter should be included on each
analog input. This filter is needed because the on-chip digital
filter does not provide any rejection around the master clock or
multiples of the master clock. Suitable values are a 1 kꢄ resistor
in series with each analog input, a 0.1 ꢃF capacitor from AIN(+)
to AIN(−), and 0.01 ꢃF capacitors from AIN(+)/AIN(−) to GND.
VDD
IN+
AV
GND
DD
REFIN(+)
AIN(+)
OUT–
OUT+
DOUT/RDY
SCLK
G = 1
OR 128
20-BIT Σ-Δ
ADC
AIN(–)
IN–
DV
DD
REFIN(–)
BPDSW
INTERNAL
CLOCK
FILTER
PDRST
GAIN
AD7781
Figure 23. Weigh Scales Using the AD7781
Rev. 0 | Page 14 of 16
AD7781
The ground plane of the AD7781 should be allowed to run under
the AD7781 to prevent noise coupling. The power supply lines
to the AD7781 should use as wide a trace as possible to provide
low impedance paths and reduce the effects of glitches on the
power supply line. Fast switching signals such as clocks should
be shielded with digital ground to avoid radiating noise to other
sections of the board, and clock signals should never be run near
the analog inputs. Avoid crossover of digital and analog signals.
Traces on opposite sides of the board should run at right angles
to each other. This reduces the effects of feedthrough through
the board. A microstrip technique is by far the best, but it is not
always possible with a double-sided board. In this technique,
the component side of the board is dedicated to ground planes,
and the signals are placed on the solder side.
GROUNDING AND LAYOUT
Because the analog input and reference input of the ADC are
differential, most of the voltages in the analog modulator are
common-mode voltages. The excellent common-mode reject-
tion of the part removes common-mode noise on these inputs.
The digital filter provides rejection of broadband noise on the
power supply, except at integer multiples of the modulator
sampling frequency. The digital filter also removes noise from
the analog and reference inputs, provided that these noise sources
do not saturate the analog modulator. As a result, the AD7781
is more immune to noise interference than conventional high
resolution converters. However, because the resolution of the
AD7781 is so high and the noise levels from the AD7781 are so
low, care must be taken with regard to grounding and layout.
Good decoupling is important when using high resolution ADCs.
AꢀDD should be decoupled with 10 μF tantalum capacitors in
parallel with 0.1 μF capacitors to GND. DꢀDD should be decoupled
with 10 μF tantalum capacitors in parallel with 0.1 μF capac-
itors to GND, with the system’s AGND to DGND connection
being close to the AD7781. To achieve the best results from
these decoupling components, place them as close as possible
to the device, ideally right up against the device. All logic chips
should be decoupled with 0.1 μF ceramic capacitors to DGND.
The printed circuit board (PCB) that houses the AD7781 should
be designed so that the analog and digital sections are separated
and confined to certain areas of the board. A minimum etch
technique is generally best for ground planes because it gives
the best shielding.
It is recommended that the GND pin of the AD7781 be tied
to the AGND plane of the system. In any layout, pay attention
to the flow of currents in the system and ensure that the return
paths for all currents are as close as possible to the paths that the
currents took to reach their destinations. Avoid forcing digital
currents to flow through the AGND sections of the layout.
Rev. 0 | Page 15 of 16
AD7781
OUTLINE DIMENSIONS
8.75 (0.3445)
8.55 (0.3366)
8
7
14
1
6.20 (0.2441)
5.80 (0.2283)
4.00 (0.1575)
3.80 (0.1496)
1.27 (0.0500)
BSC
0.50 (0.0197)
0.25 (0.0098)
45°
1.75 (0.0689)
1.35 (0.0531)
0.25 (0.0098)
0.10 (0.0039)
8°
0°
COPLANARITY
0.10
SEATING
PLANE
1.27 (0.0500)
0.40 (0.0157)
0.51 (0.0201)
0.31 (0.0122)
0.25 (0.0098)
0.17 (0.0067)
COMPLIANT TO JEDEC STANDARDS MS-012-AB
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
Figure 24. 14-Lead Standard Small Outline Package [SOIC_N]
Narrow Body
(R-14)
Dimensions shown in millimeters and (inches)
5.10
5.00
4.90
16
9
8
4.50
4.40
4.30
6.40
BSC
1
PIN 1
1.20
MAX
0.15
0.05
0.20
0.09
0.75
0.60
0.45
8°
0°
0.30
0.19
0.65
BSC
SEATING
PLANE
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-153-AB
Figure 25. 16-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-16)
Dimensions shown in millimeters
ORDERING GUIDE
Model
Temperature Range
−40°C to +105°C
−40°C to +105°C
−40°C to +105°C
−40°C to +105°C
−40°C to +105°C
−40°C to +105°C
−40°C to +105°C
−40°C to +105°C
Package Description
14-Lead SOIC_N
14-Lead SOIC_N
16-Lead TSSOP
16-Lead TSSOP
14-Lead SOIC_N
14-Lead SOIC_N
16-Lead TSSOP
16-Lead TSSOP
Package Option
R-14
R-14
RU-16
RU-16
R-14
R-14
RU-16
RU-16
AD7781BRZ1
AD7781BRZ-REEL1
AD7781BRUZ1
AD7781BRUZ-REEL1
AD7781CRZ1
AD7781CRZ-REEL1
AD7781CRUZ1
AD7781CRUZ-REEL1
1 Z = RoHS Compliant Part.
©2009 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D08162-0-5/09(0)
Rev. 0 | Page 16 of 16
相关型号：
AD7782BRU-REEL7
IC 2-CH 24-BIT DELTA-SIGMA ADC, SERIAL ACCESS, PDSO16, PLASTIC, TSSOP-16, Analog to Digital Converter
ADI
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