AD831APZ-REEL7 [ADI]
High-Performance, Low Distortion 500 MHz Mixer;
| 型号： | AD831APZ-REEL7 |
| 厂家： | 
ADI |
| 描述： | High-Performance, Low Distortion 500 MHz Mixer 局域网 PC 射频 微波 |
| 文件： | 总17页 (文件大小：493K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Low Distortion Mixer
AD831
FUNCTIONAL BLOCK DIAGRAM
FEATURES
Doubly Balanced Mixer
Low Distortion
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+24 dBmThird Order Intercept (IP3)
+10 dBm 1 dB Compression Point
Low LO Drive Required: –10 dBm
Bandwidth
500 MHz RF and LO Input Bandwidths
250 MHz Differential Current IF Output
DC to >200 MHz Single-EndedVoltage IF Output
Single- or Dual-Supply Operation
DC Coupled Using Dual Supplies
All Ports May Be DC Coupled
No Lower Frequency Limit—Operation to DC
User-Programmable Power Consumption
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APPLICATIONS
building a quadrature-amplitude modulator or image reject mixer,
the differential current outputs of two AD831s may be summed
by connecting them together.
High Performance RF/IF Mixer
Direct to Baseband Conversion
Image-Reject Mixers
An integral low noise amplifier provides a single-ended voltage
output and can drive such low impedance loads as filters, 50
amplifier inputs, and A/D converters. Its small signal bandwidth
exceeds 200 MHz. A single resistor connected between pins
OUT and FB sets its gain.The amplifier’s low dc offset allows
its use in such direct-coupled applications as direct-to-baseband
conversion and quadrature-amplitude demodulation.
I/Q Modulators and Demodulators
PRODUCT DESCRIPTION
The AD831 is a low distortion, wide dynamic range, monolithic
mixer for use in such applications as RF to IF downconversion
in HF and VHF receivers, the second mixer in DMR base sta-
tions, direct-to-baseband conversion, quadrature modulation and
demodulation, and doppler shift detection in ultrasound imaging
applications. The mixer includes an LO driver and a low noise
output amplifier and provides both user-programmable power
consumption and third order intercept point.
The mixer’s SSB noise figure is 10.3 dB at 70 MHz using its
output amplifier and optimum source impedance. Unlike passive
mixers, the AD831 has no insertion loss and does not require an
external diplexer or passive termination.
A programmable-bias feature allows the user to reduce power
consumption, with a reduction in the 1 dB compression point and
third-order intercept.This permits a tradeoff between dynamic
range and power consumption. For example, the AD831 may be
used as a second mixer in cellular and two-way radio base stations
at reduced power while still providing a substantial performance
improvement over passive solutions.
The AD831 provides a +24 dBm third order intercept point for
–10 dBm LO power, thus improving system performance and
reducing system cost compared to passive mixers, by eliminating
the need for a high power LO driver and its attendant shielding
and isolation problems.
The RF, IF, and LO ports may be dc or ac coupled when the
mixer is operating from ±5V supplies or ac coupled when oper-
ating from a single-supply of 9V minimum.The mixer operates
with RF and LO inputs as high as 500 MHz.
PRODUCT HIGHLIGHTS
1. –10 dBm LO Drive for a +24 dBm Output ReferredThird
Order Intercept Point
The mixer’s IF output is available as either a differential current
output or a single-ended voltage output.The differential output is
from a pair of open collectors and may be ac coupled via a trans-
former or capacitor to provide a 250 MHz output bandwidth. In
downconversion applications, a single capacitor connected across
these outputs implements a low-pass filter to reduce harmonics
directly at the mixer core, simplifying output filtering.When
2. Single-EndedVoltage Output
3. High Port-to-Port Isolation
4. No Insertion Loss
5. Single- or Dual-Supply Operation
6. 10.3 dB Noise Figure
REV.C
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed byAnalog Devices for its
use, nor for any infringements of patents or other rights of third parties
that may result from its use. No license is granted by implication or oth-
erwise under any patent or patent rights of Analog Devices.Trademarks
andregisteredtrademarksarethepropertyoftheirrespectivecompanies.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© 2003 Analog Devices, Inc. All rights reserved.
AD831* PRODUCT PAGE QUICK LINKS
Last Content Update: 02/23/2017
COMPARABLE PARTS
View a parametric search of comparable parts.
DESIGN RESOURCES
• AD831 Material Declaration
• PCN-PDN Information
• Quality And Reliability
• Symbols and Footprints
EVALUATION KITS
• AD831 Evaluation Board
DOCUMENTATION
Data Sheet
DISCUSSIONS
View all AD831 EngineerZone Discussions.
• AD831: Low Distortion Mixer Data Sheet
SAMPLE AND BUY
TOOLS AND SIMULATIONS
• ADIsimPLL™
Visit the product page to see pricing options.
TECHNICAL SUPPORT
• ADIsimRF
Submit a technical question or find your regional support
number.
REFERENCE MATERIALS
Product Selection Guide
• RF Source Booklet
DOCUMENT FEEDBACK
Submit feedback for this data sheet.
This page is dynamically generated by Analog Devices, Inc., and inserted into this data sheet. A dynamic change to the content on this page will not
trigger a change to either the revision number or the content of the product data sheet. This dynamic page may be frequently modified.
(TA = +25C and VS = 5 V unless otherwise noted;
all values in dBm assume 50 load.)
AD831–SPECIFICATIONS
Parameter
Conditions
Min
Typ
Max
Unit
RF INPUT
Bandwidth
–10 dBm Signal Level, IP3 ≥ +20 dBm
10.7 MHz IF and High Side Injection
See Figure 1
400
MHz
1 dB Compression Point
Common-Mode Range
Bias Current
DC Input Resistance
Capacitance
10
dBm
V
µA
k
pF
±1
500
DC Coupled
Differential or Common Mode
160
1.3
2
IF OUTPUT
Bandwidth
Single-EndedVoltage Output, –3dB
Level = 0 dBm,RL = 100
Terminals OUT andVFB Connected
DC Measurement; LO Input Switched ±1
200
0
+15
300
±1.4
75
MHz
dB
mV
V/µs
V
Conversion Gain
Output OffsetVoltage
Slew Rate
OutputVoltage Swing
Short Circuit Current
–40
+40
RL = 100 , Unity Gain
mA
LO INPUT
Bandwidth
–10 dBm Input Signal Level
10.7 MHz IF and High Side Injection
400
MHz
Maximum Input Level
Common-Mode Range
Minimum Switching Level
Bias Current
Resistance
Capacitance
–1
–1
+1
+1
V
V
Differential Input Signal
DC Coupled
Differential or Common Mode
200
17
500
2
mV p-p
µA
50
pF
ISOLATION BETWEEN PORTS
LO-to-RF
LO-to-IF
RF-to-IF
LO = 100 MHz, RS = 50 , 10.7 MHz IF
LO = 100 MHz, RS = 50 , 10.7 MHz IF
RF = 100 MHz, RS = 50 , 10.7 MHz IF
70
30
45
dB
dB
dB
DISTORTION AND NOISE
Third Order Intercept
Second Order Intercept
1 dB Compression Point
Noise Figure, SSB
LO = –10 dBm, f = 100 MHz, IF = 10.7 MHz
Output Referred, ±100 mV LO Input
Output Referred, ±100 mV LO Input
RL = 100 , RBIAS =
Matched Input, RF = 70 MHz, IF = 10.7 MHz
Matched Input, RF = 150 MHz, IF = 10.7 MHz
24
62
10
10.3
14
dBm
dBm
dBm
dB
dB
POWER SUPPLIES
Recommended Supply Range
Dual Supply
Single Supply
±4.5
9
±5.5
11
V
V
Quiescent Current*
For BestThird Order Intercept Point Performance
BIAS Pin Open Circuited
100
125
mA
*Quiescent current is programmable.
Specifications subject to change without notice.
–2–
REV. C
AD831
ABSOLUTE MAXIMUM RATINGS1
SupplyVoltage ±VS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5.5V
InputVoltages
RFHI, RFLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±3V
LOHI, LOLO . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±1V
Internal Power Dissipation2 . . . . . . . . . . . . . . . . . . . .1200 mW
OperatingTemperature Range
AD831A . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
StorageTemperature Range . . . . . . . . . . . . . . –65°C to +150°C
LeadTemperature Range (Soldering 60 sec) . . . . . . . . . . 300°C
NOTES
1 Stresses above those listed underAbsolute Maximum Ratings may cause permanent
damage to the device. This is a stress rating only and functional operation of the
device at these or any other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
2 Thermal Characteristics:
20-Lead PLCC Package: JA = 110°C/W; JC = 20°C/W.
Note that the JA = 110°C/W value is for the package measured while suspended
in still air; mounted on a PC board, the typical value is JA = 90°C/W due to the
conduction provided by theAD831’s package being in contact with the board,which
serves as a heat sink.
ORDERING GUIDE
Temperature
Range
Package
Description
Package
Option
Model
AD831AP
AD831AP-REEL7
AD831AP-EB
–40°C to +85°C
–40°C to +85°C
20-Lead PLCC
20-Lead PLCC
Evaluation Board
P-20A
P-20A
PIN DESCRIPTION
Pin No.
Mnemonic
Description
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
VP
IFN
AN
GND
VN
RFP
RFN
VN
Positive Supply Input
Mixer Current Output
Amplifier Negative Input
Ground
Negative Supply Input
RF Input
PIN CONFIGURATION
20-Lead PLCC
RF Input
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Negative Supply Input
Positive Supply Input
Local Oscillator Input
Local Oscillator Input
Positive Supply Input
Ground
Bias Input
Negative Supply Input
Amplifier Output
Amplifier Feedback Input
Amplifier Output Common
Amplifier Positive Input
Mixer Current Output
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IFP
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000V readily accumulate
on the human body and test equipment and can discharge without detection.Although the AD831 features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
REV. C
–3–
AD831–Typical Performance Characteristics
65
64
63
62
61
60
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TPC 1.Third Order Intercept vs. Frequency,
IF Held Constant at 10.7 MHz
TPC 4. Second Order Intercept vs. Frequency
80
70
60
50
40
30
20
10
0
90
80
70
60
50
40
30
20
10
0
10
100
1000
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
TPC 2. IF-to-RF Isolation vs. Frequency
TPC 5. LO-to-RF Isolation vs. Frequency
60
80
70
60
50
40
30
20
10
0
3 x RF – IF
3 x RF – IF
2 x LO – IF
3 x LO – IF
50
40
30
20
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2 x RF – IF
RF – IF
LO
RF – IF
10
0
10
100
1000
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
TPC 3. LO-to-IF Isolation vs. Frequency
TPC 6. RF-to-IF Isolation vs. Frequency
–4–
REV. C
AD831
12
10
8
1.00
0.75
0.50
0.25
0.00
6
–0.25
–0.50
–0.75
–1.00
4
2
0
10
100
1000
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
TPC 7. 1 dB Compression Point vs. Frequency,
Gain = 1
TPC 10. Gain Error vs. Frequency, Gain = 1
12
10
8
9
8
7
6
5
4
3
2
1
0
6
4
2
0
10
100
1000
10
100
1000
FREQUENCY (MHz)
FREQUENCY (MHz)
TPC 8. 1 dB Compression Point vs. RF Input, Gain = 2
TPC 11. 1 dB Compression Point vs. Frequency, Gain = 4
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IF = 10.7MHz
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TPC 9. Third Order Intercept vs. Frequency,
LO Held Constant at 241 MHz
TPC 12. Input 1 dB Compression Point vs.
Frequency, Gain = 1, 9 V Single Supply
REV. C
–5–
AD831
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400
200
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INPUT RESISTANCE
INPUT CAPACITANCE
4.0
3.5
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2.5
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FREQUENCY (MHz)
TPC 13. InputThird Order Intercept, 9 V Single Supply
TPC 15. Input Impedance vs. Frequency, ZIN = R C
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TPC 16. Noise Figure vs. Frequency,
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–6–
REV. C
AD831
THEORY OF OPERATION
The AD831 consists of a mixer core, a limiting amplifier, a low
noise output amplifier, and a bias circuit (Figure 1).
When the integral output amplifier is used, pins IFN and IFP
are connected directly to pins AFN and AFP; the on-chip load
resistors convert the output current into a voltage that drives
the output amplifier.The ratio of these load resistors to resistors
R1, R2 provides nominal unity gain (0 dB) from RF-to-IF.The
expression for the gain, in decibels, is
The mixer’s RF input is converted into differential currents by
a highly linear, Class A voltage-to-current converter, formed by
transistors Q1, Q2 and resistors R1, R2.The resulting currents
drive the differential pairs Q3, Q4 and Q5, Q6.The LO input is
through a high gain, low noise limiting amplifier that converts the
–10 dBm LO input into a square wave.This square wave drives
the differential pairs Q3, Q4 and Q5, Q6 and produces a high
level output at IFP and IFN—consisting of the sum and differ-
ence frequencies of the RF and LO inputs—and a series of lower
level outputs caused by odd harmonics of the LO frequency mix-
ing with the RF input.
Ê 4ˆ Ê 1ˆ Ê p ˆ
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(1)
Á
˜ Á ˜ Á ˜
2 2
p
Ë
¯ Ë ¯ Ë ¯
where:
4
p
is the amplitude of the fundamental component of a
squarewave.
1
2
is the conversion loss.
An on-chip network supplies the bias current to the RF and LO
inputs when these are ac-coupled; this network is disabled when
the AD831 is dc-coupled.
p
2
is the small signal dc gain of the AD831 when the LO input
is driven fully positive or negative.
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Figure 1. Simplified Schematic Diagram
REV. C
–7–
AD831
Low-Pass Filtering
The mixer has two open-collector outputs (differential currents) at
pins IFN and IFP.These currents may be used to provide nominal
unity RF to IF gain by connecting a center-tapped transformer
(1:1 turns ratio) to pins IFN and IFP as shown in Figure 2.
A simple low-pass filter may be added between the mixer and
the output amplifier by shunting the internal resistive loads
(an equivalent resistance of about 14 with a tolerance of 20%)
with external capacitors; these attenuate the sum component in
a downconversion application (Figure 4). The corner frequency
of this one-pole low-pass filter (f = (2 RCF)–1) should be placed
about an octave above the difference frequency IF. Thus, for a
70 MHz IF, a –3 dB frequency of 140 MHz might be chosen,
using CF = (2 14 140 MHz)–1 82 pF, the nearest
standard value.
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Figure 2. Connections forTransformer Coupling to
the IF Output
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Programming the Bias Current
Because the AD831’s RF port is a Class-A circuit, the maximum
RF input is proportional to the bias current.This bias current
may be reduced by connecting a resistor from the BIAS pin to the
positive supply (Figure 3). For normal operation, the BIAS pin is
left unconnected. For lowest power consumption, the BIAS pin is
connected directly to the positive supply.The range of adjustment
is 100 mA for normal operation to 45 mA total current at minimum
power consumption.
Figure 4. Low-Pass Filtering Using External Capacitors
Using the Output Amplifier
The AD831’s output amplifier converts the mixer core’s differential
current output into a single-ended voltage and provides an output
as high as ±1 V peak into a 50 V load (+10 dBm). For unity gain
operation (Figure 5), the inputs AN and AP connect to the open-
collector outputs of the mixer’s core and OUT connects to VFB.
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Figure 3. Programming the Quiescent Current
Figure 5. Output Amplifier Connected for Unity
Gain Operation
–8–
REV. C
AD831
For gains other than unity, the amplifier’s output at OUT is
connected via an attenuator network to VFB; this determines
the overall gain. Using resistors R1 and R2 (Figure 6), the gain
setting expression is
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Ê R1+ R2ˆ
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Figure 7. Connections for Driving a DoublyTerminated
Band-Pass Filter
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Higher gains can be achieved, using different resistor ratios, but
with concomitant reduction in the bandwidth of this amplifier
(Figure 8). Note also that the Johnson noise of these gain setting
resistors, as well as that of the BPF terminating resistors, is ulti-
mately reflected back to the mixer’s input; thus they should be as
small as possible, consistent with the permissible loading on the
amplifier’s output.
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Figure 6. Output Amplifier Feedback Connections
for Increasing Gain
Driving Filters
12
The output amplifier can be used for driving reverse-terminated
loads. When driving an IF band-pass filter (BPF), for example,
proper attention must be paid to providing the optimal source
and load terminations so as to achieve the specified filter response.
The AD831’s wideband highly linear output amplifier affords an
opportunity to increase the RF to IF gain to compensate for a
filter’s insertion and termination losses.
G =
1
10
8
G =
G =
2
4
6
Figure 7 indicates how the output amplifier’s low impedance
(voltage source) output can drive a doubly terminated band-pass
filter.The typical 10 dB of loss (4 dB of insertion loss and 6 dB
due to the reverse-termination) be made up by the inclusion of a
feedback network that increases the gain of the amplifier by
10 dB (3.162).When constructing a feedback circuit, the signal
path between OUT andVFB should be as short as possible.
4
2
0
10
100
1000
FREQUENCY (MHz)
Figure 8. Output Amplifier 1 dB Compression
Point for Gains of 1, 2, and 4 (Gains of 0 dB, 6 dB,
and 12 dB, Respectively)
REV. C
–9–
AD831
APPLICATIONS
The RF input to the AD831 is shown connected by an impedance
matching network for an assumed source impedance of 50 .
TPC 15 shows the input impedance of the AD831 plotted vs.
frequency. The input circuit can be modeled as a resistance in
parallel with a capacitance. The 82 pF capacitors (CF) connected
from IFN and IFP to VP provide a low-pass filter with a cutoff
frequency of approximately 140 MHz in down-conversion appli-
cations (see the Theory of Operation section for more details).
The LO input is connected single-ended because the limiting
amplifier provides a symmetric drive to the mixer. To minimize
intermodulation distortion, connect pins OUT and VFB by the
shortest possible path. The connections shown are for unity-gain
operation.
Careful component selection, circuit layout, power supply
dc coupling, and shielding are needed to minimize the AD831’s
susceptibility to interference from radio and TV stations, etc. In
bench evaluation, we recommend placing all of the components
in a shielded box and using feedthrough decoupling networks for
the supply voltage.
Circuit layout and construction are also critical, since stray capaci-
tances and lead inductances can form resonant circuits and are a
potential source of circuit peaking, oscillation, or both.
Dual-Supply Operation
Figure 9 shows the connections for dual-supply operation. Supplies
may be as low as ±4.5V but should be no higher than ±5.5V, due
to power dissipation.
At LO frequencies less than 100 MHz, the AD831’s LO power
may be as low as –20 dBm for satisfactory operation. Above
100 MHz, the specified LO power of –10 dBm must be used.
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Figure 9. Connections for ±5 V Dual-Supply Operation Showing Impedance
Matching Network and Gain of 2 for Driving Reverse-Terminated IF Filter
–10–
REV. C
AD831
Single-Supply Operation
In single-supply operation, the COM terminal is the “ground”
reference for the output amplifier and must be biased to half the
supply voltage, which is done by resistors R1 and R2.The OUT
pin must be ac-coupled to the load.
Figure 10 is similar to the dual-supply circuit in Figure 9. Supplies
may be as low as 9V but should not be higher than 11 V, due to
power dissipation. As in Figure 9, both the RF and LO ports are
driven single-ended and terminated.
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Figure 10. Connections for +9 V Single-Supply Operation
REV. C
–11–
AD831
Connections Quadrature Demodulation
The mixers’ inputs may be connected in parallel and a single
termination resistor used if the mixers are located in close prox-
imity on the PC board.
Two AD831 mixers may have their RF inputs connected in parallel
and have their LO inputs driven in phase quadrature (Figure 11)
to provide demodulated in-phase (I) and quadrature (Q) outputs.
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Figure 11. Connections for Quadrature Demodulation
–12–
REV. C
AD831
Table I. AD831 MixerTable, 4.5V Supplies, LO = –9 dBm
LO Level
RF Level
–9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB10771
0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply
VPOS Current
VNEG Current
±4.50V
90 mA
91 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0
1
2
3
4
5
6
7
0
1
2
3
4
5
6
7
–32.7
–32.7
–35.7
–35.7
–21.1
–21.1
–11.6
–11.6
–19.2
–19.2
–35.1
–35.1
–41.9
–41.9
–31.6
–31.6
0.0
–28.5
–37.2
–26.7
–41.5
–28.0
–30.4
–27.2
–34.3
–33.2
–25.2
–34.3
–40.1
–44.8
–45.3
–45.3
–48.2
–42.4
–39.4
–49.4
–57.6
–42.5
–44.9
–51.1
–42.4
–46.2
–40.2
–58.1
–40.2
–61.6
–54.5
–54.5
–57.1
–65.5
–57.5
–46.0
–50.6
–63.7
–62.6
–60.6
–55.8
–69.6
–59.7
–72.7
–55.2
–73.5
–67.1
–67.1
–63.1
–53.6
–69.9
–72.9
–69.9
–71.2
–69.6
–70.1
–74.1
–72.6
–69.7
–73.5
–58.6
–72.7
–53.5
–53.5
–62.6
–68.4
–73.8
–70.8
–72.3
–72.8
–70.7
–73.4
–71.1
–73.2
–74.3
–73.3
–73.0
–72.5
–73.6
–73.6
–57.7
–73.5
–68.6
–72.7
–73.1
–73.5
–73.8
–73.6
–73.0
–73.1
–72.9
–72.4
–74.4
–73.7
–73.8
–73.8
–73.9
–73.8
–63.4
–73.2
–72.6
–73.8
–74.6
–72.6
–74.9
–73.7
–73.6
–73.5
–74.5
–72.9
Table II. AD831 MixerTable, 5V Supplies, LO = –9 dBm
LO Level
RF Level
–9.0 dBm, LO Frequency 130.7 MHz, Data File imdTB13882
0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply
VPOS Current
VNEG Current
±5.00V
102 mA
102 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0
1
2
3
4
5
6
7
0
1
2
3
4
5
6
7
–36.5
–36.5
–46.5
–46.5
–33.0
–33.0
–17.0
–17.0
–23.0
–23.0
–34.2
–34.2
–45.6
–45.6
–37.5
–37.5
0.0
–29.1
–41.2
–38.7
–41.1
–22.9
–38.5
–28.4
–29.0
–35.3
–31.7
–34.3
–47.4
–52.4
–45.9
–45.9
–45.2
–39.4
–47.6
–35.7
–61.5
–38.4
–53.7
–42.3
–43.5
–53.7
–41.5
–52.8
–41.8
–66.3
–46.4
–46.4
–53.0
–40.0
–67.0
–50.0
–43.0
–48.9
–60.9
–57.8
–47.9
–57.0
–50.7
–71.8
–41.0
–67.4
–45.1
–45.1
–56.0
–39.0
–48.7
–48.1
–64.6
–58.4
–53.5
–56.1
–55.7
–63.8
–53.5
–70.5
–51.1
–67.6
–35.2
–35.2
–45.3
–53.0
–54.1
–62.4
–54.1
–67.3
–53.7
–67.0
–57.9
–69.4
–66.6
–73.2
–64.3
–72.9
–63.4
–63.4
–41.1
–66.3
–53.6
–67.2
–66.5
–67.5
–58.8
–72.9
–63.3
–71.2
–61.7
–71.7
–71.4
–73.2
–67.3
–67.3
–65.8
–61.6
–37.8
–66.3
–54.6
–72.9
–62.5
–71.4
–71.7
–70.7
–55.2
–72.1
–57.1
–73.1
REV. C
–13–
AD831
Table III. AD831 MixerTable, 3.5V Supplies, LO = –20 dBm
LO Level
RF Level
–20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 0771
0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply
VPOS Current
VNEG Current
±3.50V
55 mA
57 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0
1
2
3
4
5
6
7
0
1
2
3
4
5
6
7
–45.2
–45.2
–35.7
–35.7
–16.1
–16.1
–21.6
–21.6
–22.3
–22.3
–32.0
–32.0
–36.4
–36.4
–30.3
–30.3
0.0
–29.7
–33.7
–28.2
–47.9
–24.4
–37.5
–26.0
–33.8
–47.4
–32.0
–35.9
–45.2
–49.7
–50.3
–50.3
–49.4
–41.0
–47.4
–51.4
–49.9
–34.7
–48.8
–49.8
–38.5
–48.6
–40.7
–68.5
–51.
–67.9
–48.4
–48.4
–55.7
–52.9
–58.2
–50.0
–45.0
–64.5
–57.0
–62.8
–68.4
–73.4
–55.5
–74.0
–47.7
–71.8
–66.7
–66.7
–59.7
–65.9
–67.2
–78.1
–62.8
–74.2
–58.2
–77.5
–71.5
–74.4
–72.9
–77.9
–63.5
–77.5
–66.9
–66.9
–71.5
–76.3
–73.6
–78.1
–77.6
–78.2
–70.8
–78.1
–70.2
–78.0
–75.8
–77.9
–78.1
–77.9
–78.0
–78.0
–69.7
–78.3
–76.7
–78.3
–78.6
–78.2
–78.8
–78.1
–75.4
–78.0
–78.1
–77.9
–79.0
–77.8
–78.4
–78.4
–78.5
–78.3
–76.9
–78.2
–78.7
–78.2
–79.0
–77.9
–79.1
–77.9
–78.6
–77.8
–78.9
–77.5
Table IV. AD831 MixerTable, 5V Supplies, 1 k Bias Resistor, LO = –20 dBm
LO Level
RF Level
–20.0 dBm, LO Frequency 130.7 MHz, Data File G1T1K 3881
0.0 dBm, RF Frequency 120 MHz
Temperature Ambient
Dut Supply
VPOS Current
VNEG Current
±3.50V
59 mA
61 mA
Intermodulation table RF harmonics (rows) LO harmonics (columns).
First row absolute value of nRF – mLO, and second row is the sum.
0
1
2
3
4
5
6
7
0
1
2
3
4
5
6
7
–60.6
–60.6
–52.3
–52.3
–16.6
–16.6
–12.8
–12.8
–26.0
–26.0
–45.0
–45.0
–38.8
–38.8
–34.1
–34.1
0.0
–27.3
–35.2
–28.7
–41.8
–20.7
–29.8
–32.9
–29.1
–39.2
–35.3
–38.2
–49.0
–47.8
–46.6
–46.6
–48.8
–37.8
–40.1
–47.6
–52.2
–41.7
–57.9
–54.2
–38.6
–50.4
–45.8
–64.1
–47.7
–64.9
–41.3
–41.3
–58.8
–47.9
–59.5
–65.2
–41.8
–62.5
–61.2
–64.2
–58.1
–73.8
–57.5
–72.3
–54.0
–72.6
–53.9
–53.9
–52.5
–61.4
–73.7
–70.6
–68.1
–76.9
–60.3
–76.8
–71.0
–78.6
–63.4
–78.3
–62.3
–78.1
–66.9
–66.9
–65.8
–69.7
–76.6
–72.9
–75.2
–77.4
–65.4
–77.7
–70.0
–78.5
–73.6
–78.4
–68.7
–78.2
–77.4
–77.4
–73.3
–78.6
–73.8
–78.7
–78.8
–78.6
–79.2
–78.6
–73.6
–78.4
–74.9
–78.2
–79.3
–78.2
–78.9
–78.9
–79.0
–78.8
–77.9
–78.7
–78.0
–78.6
–79.3
–78.3
–79.5
–78.3
–79.3
–78.1
–79.3
–78.0
–14–
REV. C
AD831
ꢜꢗꢘꢝꢝꢖꢊꢓ
ꢗꢑꢌꢙꢑꢓꢃꢃꢓꢍꢅꢐ
ꢗꢌꢞꢐꢑꢘꢈꢚꢗꢗꢅꢟ
ꢜꢗꢘꢝꢝꢖꢊꢓ
ꢗꢑꢌꢙꢑꢓꢃꢃꢓꢍꢅꢐ
ꢗꢌꢞꢐꢑꢘꢈꢚꢗꢗꢅꢟ
ꢜꢗꢘꢕꢝꢀꢝꢍ
ꢈꢟꢏꢠꢜꢐꢈꢎꢆꢐꢔ
ꢈꢎꢙꢏꢓꢅꢘꢙꢐꢏꢐꢑꢓꢠꢌꢑ
�ꢀꢁ
ꢂꢀꢁ
ꢀꢒ�
ꢜꢗꢘꢕꢀꢝꢋꢐ
ꢈꢗꢐꢄꢠꢑꢚꢃ
ꢓꢏꢓꢅꢟꢆꢐꢑ
ꢓꢔꢕꢖꢋ
ꢗꢐꢑꢘꢇꢎꢙꢚꢑꢐꢘꢛ
ꢃꢄꢅ
ꢆꢇꢈꢄꢉꢊꢉꢋ
ꢄꢌꢃꢍꢎꢏꢐꢑ
∑
ꢅꢌ
ꢜꢗꢘꢕꢝꢀꢝꢓ
ꢈꢟꢏꢠꢜꢐꢈꢎꢆꢐꢔ
ꢈꢎꢙꢏꢓꢅꢘꢙꢐꢏꢐꢑꢓꢠꢌꢑ
ꢇꢅꢚꢡꢐꢘꢝꢒꢕꢊꢓ
ꢈꢟꢏꢠꢜꢐꢈꢎꢆꢐꢔ
ꢈꢎꢙꢏꢓꢅꢘꢙꢐꢏꢐꢑꢓꢠꢌꢑ
ꢜꢗꢘꢛꢛꢊꢒ
ꢎꢐꢐꢐꢘꢄꢌꢏꢠꢑꢌꢅꢅꢐꢑ
ꢜꢗꢘꢛꢋꢊꢋ
ꢔꢎꢈꢡꢘꢔꢑꢎꢁꢐ
ꢎꢐꢐꢐꢉꢢꢕꢕꢘꢍꢚꢈ
Figure 12. Third Order Intercept Characterization Setup
ꢓꢊꢍꢔꢔꢈꢜꢅ
ꢊꢌꢄꢐꢌꢅꢝꢝꢅꢕꢃꢋ
ꢊꢄꢞꢋꢌꢍꢖꢑꢊꢊꢃꢗ
ꢓꢊꢍꢔꢔꢈꢜꢅ
ꢊꢌꢄꢐꢌꢅꢝꢝꢅꢕꢃꢋ
ꢊꢄꢞꢋꢌꢍꢖꢑꢊꢊꢃꢗ
�ꢀꢁ
ꢂꢀꢁ
ꢝꢡꢃ
ꢚꢎꢖꢡꢟꢜꢟꢉ
ꢓꢊꢍꢇꢔꢀꢔꢕ
ꢀꢛ�
ꢌꢎ
ꢏꢎ
ꢓꢊꢍꢇꢔꢀꢔꢕ
ꢅꢆꢇꢈꢉ
ꢊꢋꢌꢍꢎꢏꢐꢑꢌꢋꢍꢒ
ꢖꢗꢘꢙꢓꢋꢖꢏꢚꢋꢆ
ꢖꢗꢘꢙꢓꢋꢖꢏꢚꢋꢆ
ꢖꢏꢐꢘꢅꢃꢍꢐꢋꢘꢋꢌꢅꢙꢄꢌ
ꢖꢏꢐꢘꢅꢃꢍꢐꢋꢘꢋꢌꢅꢙꢄꢌ
ꢃꢄ
ꢀꢛ�
ꢀꢛ�
ꢑꢖꢋꢆꢍꢎꢄꢌ
ꢝꢡꢃ
ꢚꢎꢖꢡꢟꢜꢟꢉ
ꢏꢎꢟꢙꢄꢟꢌꢎꢠꢍꢃꢄ
ꢃꢄꢟꢙꢄꢟꢌꢎ
ꢝꢄꢁꢋꢍꢖꢊꢋꢡꢙꢌꢑꢝ
ꢅꢘꢅꢃꢗꢚꢋꢌꢍꢎꢄꢌꢍꢏꢎ
ꢝꢋꢅꢖꢑꢌꢋꢝꢋꢘꢙꢖ
ꢀꢛ�
ꢓꢊꢍꢇꢀꢔꢉꢋ
ꢖꢊꢋꢡꢙꢌꢑꢝ
ꢅꢘꢅꢃꢗꢚꢋꢌ
ꢓꢊꢍꢇꢔꢀꢔꢕ
ꢖꢗꢘꢙꢓꢋꢖꢏꢚꢋꢆ
ꢖꢏꢐꢘꢅꢃꢍꢐꢋꢘꢋꢌꢅꢙꢄꢌ
Figure 13. IF-to-RF Isolation Characterization Setup
REV. C
–15–
AD831
OUTLINE DIMENSIONS
20-Lead Plastic Leaded Chip Carrier [PLCC]
(P-20A)
Dimensions shown in inches and (millimeters)
0.180 (4.57)
0.165 (4.19)
0.048 (1.21)
0.042 (1.07)
0.056 (1.42)
0.020 (0.50)
R
0.20 (0.51)
MIN
0.042 (1.07)
3
4
19
0.021 (0.53)
0.013 (0.33)
0.048 (1.21)
0.042 (1.07)
18
14
0.050
(1.27)
BSC
0.330 (8.38)
0.290 (7.37)
BOTTOM
VIEW
TOP VIEW
(PINS DOWN)
0.032 (0.81)
0.026 (0.66)
(PINS UP)
8
9
13
0.020
(0.50)
R
0.040 (1.01)
0.025 (0.64)
0.356 (9.04)
0.350 (8.89)
SQ
0.120 (3.04)
0.090 (2.29)
0.395 (10.02)
0.385 (9.78)
SQ
COMPLIANT TO JEDEC STANDARDS MO-047AA
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
Revision History
Location
Page
6/03–Data Sheet Changed from REV. B to REV. C.
Updated format . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . UNIVERSAL
Changes to Figure 10 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
–16–
REV. C
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