AD8604ARU-REEL_技术文档

Precision CMOS Single-Supply

Rail-to-Rail Input/Output Wideband

Operational Amplifiers

AD8601/AD8602/AD8604

FEATURES

FUNCTIONAL BLOCK DIAGRAM

Low Offset Voltage: 500 ␮V Max

Single-Supply Operation: 2.7 V to 5.5 V

Low Supply Current: 750 ␮A/Amplifier

Wide Bandwidth: 8 MHz

Slew Rate: 5 V/␮s

Low Distortion

No Phase Reversal

Low Input Currents

Unity Gain Stable

14-Lead TSSOP

(RU Suffix)

5-Lead SOT-23

(RT Suffix)

OUT A

؊IN A

؉IN A

V؉

1

2

3

4

5

6

7

V؉

14

13

12

11

10

9

OUT D

؊IN D

؉IN D

V؊

OUT A

5

4

1

2

V؊

AD8601

؉IN

؊IN

3

AD8604

؉IN B

؊IN B

OUT B

؉IN C

؊IN C

OUT C

APPLICATIONS

Current Sensing

Barcode Scanners

PA Controls

8

8-Lead MSOP

(RM Suffix)

Battery-Powered Instrumentation

Multipole Filters

Sensors

ASIC Input or Output Amplifiers

Audio

14-Lead SOIC

(R Suffix)

1

2

3

4

8

7

6

5

OUT A

V؉

؊IN A

OUT B

AD8602

؉IN A

V؊

؊IN B

؉IN B

OUT A

OUT D

1

2

3

4

5

6

7

14

13

12

11

10

9

؊IN A

؉IN A

V؉

؊IN D

؉IN D

V؊

GENERAL DESCRIPTION

The AD8601, AD8602, and AD8604 are single, dual, and quad

rail-to-rail input and output single-supply amplifiers featuring very

low offset voltage and wide signal bandwidth. These amplifiers

use a new, patented trimming technique that achieves superior

performance without laser trimming. All are fully specified to

operate on a 3 V to 5 V single supply.

AD8604

؉IN B

؊IN B

OUT B

؉IN C

؊IN C

OUT C

8-Lead SOIC

(R Suffix)

8

OUT A

1

2

3

4

V؉

8

7

6

5

؊IN A

OUT B

The combination of low offsets, very low input bias currents,

and high speed make these amplifiers useful in a wide variety of

applications. Filters, integrators, diode amplifiers, shunt current

sensors, and high impedance sensors all benefit from the combi-

nation of performance features. Audio and other ac applications

benefit from the wide bandwidth and low distortion. For the

most cost-sensitive applications, the D grades offer this ac per-

formance with lower dc precision at a lower price point.

AD8602

؉IN A

V؊

؊IN B

؉IN B

The AD8601, AD8602, and AD8604 are specified over the

extended industrial (–40°C to +125°C) temperature range. The

AD8601, single, is available in the tiny 5-lead SOT-23 package.

The AD8602, dual, is available in 8-lead MSOP and narrow

SOIC surface-mount packages. The AD8604, quad, is available

in 14-lead TSSOP and narrow SOIC packages.

Applications for these amplifiers include audio amplification for

portable devices, portable phone headsets, bar code scanners,

portable instruments, cellular PA controls, and multipole filters.

The ability to swing rail-to-rail at both the input and output

enables designers to buffer CMOS ADCs, DACs, ASICs, and

other wide output swing devices in single-supply systems.

SOT, MSOP, and TSSOP versions are available in tape and

reel only.

REV. D

Information furnished by Analog Devices is believed to be accurate and

reliable. However, no responsibility is assumed by Analog Devices for its

use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat

may result from its use. No license is granted by implication or otherwise

under any patent or patent rights of Analog Devices. Trademarks and

registered trademarks are the property of their respective owners.

One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.

Tel: 781/329-4700

Fax: 781/326-8703

www.analog.com

AD8601/AD8602/AD8604–SPECIFICATIONS

(V_S= 3 V, V_CM= V_S/2, T_A= 25؇C, unless otherwise noted.)

ELECTRICAL CHARACTERISTICS

A Grade

Typ

D Grade

Typ Max Unit

Parameter

Symbol

Conditions

Min

Max

Min

INPUT CHARACTERISTICS

Offset Voltage (AD8601/AD8602) V_OS

0 V ≤ V_CM≤ 1.3 V

80

500

700

1,100

750

1,800

2,100

600

800

1,600

800

2,200

2,400

60

1,100 6,000 µV

7,000 µV

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

7,000 µV

0 V ≤ V_CM≤ 3 V

*

350

80

1,300 6,000 µV

7,000 µV

1,100 6,000 µV

7,000 µV

1,300 6,000 µV

7,000 µV

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

V_CM= 0 V to 1.3 V

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

Offset Voltage (AD8604)

V_OS

V

_CM= 0 V to 3.0 V

*

350

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

7,000 µV

Input Bias Current

Input Offset Current

I_B

0.2

25

150

0.1

0.2

25

200

pA

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

100

1,000

30

50

500

150

0.1

1,000 pA

I_OS

100

500

3

pA

V

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

Input Voltage Range

0

3

0

Common-Mode Rejection Ratio

Large Signal Voltage Gain

CMRR

A_VO

V_CM= 0 V to 3 V

V_O= 0.5 V to 2.5 V,

R_L= 2 kΩ , V_CM= 0 V

68

83

52

65

dB

30

100

2

20

60

2

V/mV

µV/°C

Offset Voltage Drift

∆V_OS/∆T

OUTPUT CHARACTERISTICS

Output Voltage High

V_OH

V_OL

I_L= 1.0 mA

–40°C ≤ T_A≤ +125°C

I_L= 1.0 mA

2.92

2.88

2.95

20

2.92

2.88

2.95

20

V

mV

mA

Ω

Output Voltage Low

35

50

35

50

–40°C ≤ T_A≤ +125°C

Output Current

Closed-Loop Output Impedance

I_OUT

Z_OUT

30

12

30

12

f = 1 MHz, A_V= 1

POWER SUPPLY

Power Supply Rejection Ratio

Supply Current/Amplifier

PSRR

I_SY

V_S= 2.7 V to 5.5 V

V_O= 0 V

–40°C ≤ T_A≤ +125°C

67

80

680

56

72

680

dB

1,000 µA

1,300 µA

1,000

1,300

DYNAMIC PERFORMANCE

Slew Rate

Settling Time

Gain Bandwidth Product

Phase Margin

SR

t_S

GBP

⌽o

R_L= 2 kΩ

To 0.01%

5.2

<0.5

8.2

50

5.2

<0.5

8.2

50

V/µs

µs

MHz

Degrees

NOISE PERFORMANCE

Voltage Noise Density

e_n

i_n

f = 1 kHz

f = 10 kHz

33

18

0.05

33

18

0.05

nV/√Hz

pA/√Hz

Current Noise Density

*For V_CMbetween 1.3 V and 1.8 V, V_OSmay exceed specified value.

Specifications subject to change without notice.

–2–

REV. D

AD8601/AD8602/AD8604

(V_S= 5.0 V, V_CM= V_S/2, T_A= 25؇C, unless otherwise noted.)

ELECTRICAL CHARACTERISTICS

A Grade

Typ

D Grade

Typ Max Unit

Parameter

Symbol

Conditions

Min

Max

Min

INPUT CHARACTERISTICS

Offset Voltage (AD8601/AD8602) V_OS

0 V ≤ V_CM≤ 5 V

–40°C ≤ T_A≤ +125°C

V_CM= 0 V to 5 V

80

0.2

500

1,300

600

1,700

60

100

1,000

30

1,300 6,000 µV

7,000 µV

1,300 6,000 µV

7,000 µV

Offset Voltage (AD8604)

Input Bias Current

V_OS

I_B

–40°C ≤ T_A≤ +125°C

0.2

200

pA

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

1,000 pA

Input Offset Current

I_OS

0.1

6

25

0.1

6

25

100

500

5

pA

V

–40°C ≤ T_A≤ +85°C

–40°C ≤ T_A≤ +125°C

50

500

5

Input Voltage Range

0

Common-Mode Rejection Ratio

Large Signal Voltage Gain

CMRR

A_VO

V_CM= 0 V to 5 V

V_O= 0.5 V to 4.5 V,

R_L= 2 kΩ, V_CM= 0 V

74

30

89

80

56

20

67

60

dB

V/mV

Offset Voltage Drift

∆V_OS/∆T

2

µV/°C

OUTPUT CHARACTERISTICS

Output Voltage High

V_OH

I_L= 1.0 mA

4.925 4.975

V

I_L= 10 mA

–40°C ≤ T_A≤ +125°C

I_L= 1.0 mA

I_L= 10 mA

–40°C ≤ T_A≤ +125°C

4.7

4.6

4.77

4.7

4.6

4.77

V

Output Voltage Low

V_OL

15

125

30

175

250

15

125

30

175

250

mV

mA

Ω

Output Current

I_OUT

50

10

50

10

Closed-Loop Output Impedance

Z_OUT

f = 1 MHz, A_V= 1

POWER SUPPLY

Power Supply Rejection Ratio

Supply Current/Amplifier

PSRR

I_SY

V_S= 2.7 V to 5.5 V

V_O= 0 V

–40°C ≤ T_A≤ +125°C

67

80

750

56

72

750

dB

1,200 µA

1,500 µA

1,200

1,500

DYNAMIC PERFORMANCE

Slew Rate

Settling Time

Full Power Bandwidth

Gain Bandwidth Product

Phase Margin

SR

t_S

BWp

GBP

⌽o

R_L= 2 kΩ

6

V/µs

To 0.01%

<1.0

360

8.4

55

<1.0

360

8.4

55

µs

< 1% Distortion

kHz

MHz

Degrees

NOISE PERFORMANCE

Voltage Noise Density

e_n

i_n

f = 1 kHz

f = 10 kHz

f = 1 kHz

33

18

0.05

33

18

0.05

nV/√Hz

pA/√Hz

Current Noise Density

Specifications subject to change without notice.

REV. D

–3–

AD8601/AD8602/AD8604

ABSOLUTE MAXIMUM RATINGS*

Package Type

␪

*

␪

Unit

JA

JC

Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V

Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND to V_S

Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . 6 V

Storage Temperature Range

R, RM, RT, RU Packages . . . . . . . . . . . . –65°C to +150°C

Operating Temperature Range

5-Lead SOT-23 (RT)

8-Lead SOIC (R)

8-Lead MSOP (RM)

14-Lead SOIC (R)

14-Lead TSSOP (RU)

230

158

210

120

180

92

43

45

36

35

°C/W

AD8601/AD8602/AD8604 . . . . . . . . . . . . –40°C to +125°C

Junction Temperature Range

*␪_JAis specified for worst-case conditions, i.e., ␪_JAis specified for device in

socket for PDIP packages; ␪_JAis specified for device soldered onto a circuit

board for surface-mount packages.

R, RM, RT, RU Packages . . . . . . . . . . . . –65°C to +150°C

Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C

ESD

. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 kV HBM

*Stresses above those listed under Absolute Maximum Ratings may cause perma-

nent damage to the device. This is a stress rating only; functional operation of the

device at these or any other conditions above those listed in the operational

sections of this specification is not implied. Exposure to absolute maximum rating

conditions for extended periods may affect device reliability.

ORDERING GUIDE

Temperature

Range

Package

Description

Package

Option

Model

Branding

AD8601ART-R2

AD8601ART-REEL

AD8601ART-REEL7

AD8601DRT-R2

AD8601DRT-REEL

AD8601DRT-REEL7

AD8602AR

AD8602AR-REEL7

AD8602AR-R2

AD8602DR

AD8602DR-REEL

AD8602DR-REEL7

AD8602ARM-R2

AD8602ARM-REEL

AD8602DRM-REEL

AD8604AR

AD8604AR-REEL

AD8604AR-REEL7

AD8604DR

AD8604DR-REEL

AD8604ARU

AD8604ARU-REEL

AD8604DRU

–40°C to +125°C

5-Lead SOT-23

8-Lead SOIC

RT-5

R-8

AAA

AAD

8-Lead SOIC

R-8

8-Lead MSOP

14-Lead SOIC

14-Lead TSSOP

RM-8

R-14

RU-14

ABA

ABD

AD8604DRU-REEL

CAUTION

ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily

accumulate on the human body and test equipment and can discharge without detection. Although the

AD8601/AD8602/AD8604 features proprietary ESD protection circuitry, permanent damage may

occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions

are recommended to avoid performance degradation or loss of functionality.

–4–

REV. D

Typical Performance Characteristics–

AD8601/AD8602/AD8604

60

3,000

2,500

2,000

1,500

1,000

V

T

= 5V

= 25؇C TO 85؇C

S

A

V

T

= 3V

= 25؇C

= 0V TO 3V

S

A

50

40

30

V

CM

20

10

0

500

0

؊1.0 ؊0.8 ؊0.6 ؊0.4 ؊0.2

0

1

2

3

4

5

6

7

8

9

10

0.2

0.4

0.6

0.8

1.0

10

INPUT OFFSET VOLTAGE – mV

TCVOS – ␮V/؇C

TPC 1. Input Offset Voltage Distribution

TPC 4. Input Offset Voltage Drift Distribution

1.5

3,000

2,500

2,000

1,500

1,000

V

T

= 3V

= 25؇C

S

A

V

T

= 5V

= 25؇C

= 0V TO 5V

S

A

1.0

0.5

V

CM

0

؊0.5

؊1.0

؊1.5

؊2.0

500

0

0.5

1.0

1.5

2.0

2.5

3.0

؊1.0 ؊0.8 ؊0.6 ؊0.4 ؊0.2

0

0.2

0.4

0.6

0.8

COMMON-MODE VOLTAGE – V

INPUT OFFSET VOLTAGE – mV

TPC 2. Input Offset Voltage Distribution

TPC 5. Input Offset Voltage vs. Common-Mode Voltage

60

50

1.5

V

T

= 5V

= 25؇C

V

T

= 3V

= 25؇C TO 85؇C

S

A

1.0

0.5

40

30

20

10

0

؊0.5

؊1.0

؊1.5

؊2.0

0

1

2

3

4

5

0

1

2

3

4

5

6

7

8

9

COMMON-MODE VOLTAGE – V

TCVOS – ␮V/؇C

TPC 6. Input Offset Voltage vs. Common-Mode Voltage

TPC 3. Input Offset Voltage Drift Distribution

REV. D

–5–

AD8601/AD8602/AD8604

300

30

25

20

15

10

5

V

= 3V

V = 3V

S

250

200

150

100

50

0

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

TEMPERATURE – ؇C

TPC 7. Input Bias Current vs. Temperature

TPC 10. Input Offset Current vs. Temperature

300

250

200

150

100

50

30

V

= 5V

V

= 5V

S

25

20

15

10

5

0

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

TEMPERATURE – ؇C

TPC 8. Input Bias Current vs. Temperature

TPC 11. Input Offset Current vs. Temperature

5

10k

V

T

= 2.7V

= 25؇C

S

A

V

T

= 5V

= 25؇C

S

A

4

3

1k

100

10

SOURCE

SINK

2

1

0

1

0.1

0.001

0.01

0.1

1

10

100

0

0.5

1.0

1.5

2.0

2.5

3.0

3.5

4.0

4.5

5.0

LOAD CURRENT – mA

COMMON-MODE VOLTAGE – V

TPC 9. Input Bias Current vs. Common-Mode Voltage

TPC 12. Output Voltage to Supply Rail vs. Load Current

–6–

REV. D

AD8601/AD8602/AD8604

10k

1k

35

30

25

V

T

= 5V

= 25؇C

S

A

V

= 2.7V

S

SOURCE

SINK

V

@ 1mA LOAD

OL

100

10

20

15

10

1

5

0

0.1

0.001

0.01

0.1

1

10

100

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

LOAD CURRENT – mA

TEMPERATURE – ؇C

TPC 13. Output Voltage to Supply Rail vs. Load Current

TPC 16. Output Voltage Swing vs. Temperature

5.1

2.67

V

= 5V

S

V

= 2.7V

S

5.0

4.9

4.8

4.7

4.6

4.5

2.66

2.65

2.64

2.63

2.62

V

@ 1mA LOAD

OH

V

@ 1mA LOAD

OH

V

@ 10mA LOAD

OH

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

TEMPERATURE – ؇C

TPC 14. Output Voltage Swing vs. Temperature

TPC 17. Output Voltage Swing vs. Temperature

250

V

R

= 3V

= NO LOAD

= 25؇C

S

V

= 5V

S

100

80

L

T

A

200

150

60

45

90

40

20

V

@ 10mA LOAD

OL

135

180

100

50

0

–20

–40

–60

V

@ 1mA LOAD

OL

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

1k

10k

100k

1M

10M

100M

TEMPERATURE – ؇C

FREQUENCY – Hz

TPC 15. Output Voltage Swing vs. Temperature

TPC 18. Open-Loop Gain and Phase vs. Frequency

REV. D

–7–

AD8601/AD8602/AD8604

3.0

2.5

2.0

1.5

V

R

= 5V

= NO LOAD

= 25؇C

S

100

80

L

T

A

V

R

= 2.7V

= 2.6V p-p

= 2k⍀

= 25؇C

= 1

S

IN

60

40

20

45

L

T

A

90

A

V

135

180

0

–20

–40

–60

1.0

0.5

0

1k

10k

100k

1M

10M

1k

10k

100k

1M

10M

100M

FREQUENCY – Hz

TPC 19. Open-Loop Gain and Phase vs. Frequency

TPC 22. Closed-Loop Output Voltage Swing vs. Frequency

6

5

V

T

= 3V

= 25؇C

S

A

= 100

= 10

= 1

V

40

20

0

V

= 5V

S

= 4.9V p-p

= 2k⍀

= 25؇C

= 1

IN

4

3

R

T

L

A

V

2

1

0

1k

10k

100k

1M

10M

100M

1k

10k

100k

1M

10M

FREQUENCY – Hz

TPC 20. Closed-Loop Gain vs. Frequency

TPC 23. Closed-Loop Output Voltage Swing vs. Frequency

200

V

T

= 5V

= 25؇C

V

T

= 3V

= 25؇C

S

180

160

140

120

100

80

A

= 100

= 10

= 1

V

40

20

0

A

= 100

V

A

= 10

V

A

= 1

V

60

40

20

0

1k

10k

100k

1M

10M

100M

100

1k

10k

100k

1M

10M

FREQUENCY – Hz

TPC 21. Closed-Loop Gain vs. Frequency

TPC 24. Output Impedance vs. Frequency

–8–

REV. D

AD8601/AD8602/AD8604

200

180

160

140

120

100

80

160

140

120

100

80

V

T

= 5V

= 25؇C

V

T

= 5V

= 25؇C

S

A

S

A

= 100

V

60

A

= 10

V

40

A

= 1

V

60

20

40

0

20

؊20

0

؊40

100

1k

10k

100k

1M

10M

100

1k

10k

100k

1M

10M

FREQUENCY – Hz

TPC 25. Output Impedance vs. Frequency

TPC 28. Power Supply Rejection Ratio vs. Frequency

70

160

140

120

100

80

V

T

= 3V

= 25؇C

S

A

V

= 2.7V

=

S

60

50

40

30

20

10

0

R

L

T

= 25؇C

= 1

A

V

؊OS

60

40

+OS

20

0

؊20

؊40

1k

10k

100k

1M

10M 20M

10

100

CAPACITANCE – pF

1k

FREQUENCY – Hz

TPC 26. Common-Mode Rejection Ratio vs. Frequency

TPC 29. Small Signal Overshoot vs. Load Capacitance

160

70

V

T

= 5V

= 25؇C

S

A

V

= 5V

=

140

120

100

80

S

60

50

40

30

20

10

0

R

L

T

= 25؇C

= 1

A

V

60

40

20

0

؊20

؊40

؊OS

+OS

1k

10k

100k

1M

10M 20M

10

100

1k

FREQUENCY – Hz

CAPACITANCE – pF

TPC 27. Common-Mode Rejection Ratio vs. Frequency

TPC 30. Small Signal Overshoot vs. Load Capacitance

REV. D

–9–

AD8601/AD8602/AD8604

1.2

0.1

0.01

V

T

= 5V

= 25؇C

S

A

V

= 5V

S

R

= 600⍀

L

1.0

0.8

0.6

0.4

0.2

0

R

= 2k⍀

L

G = 10

R

= 10k⍀

L

R

= 600⍀

R

= 2k⍀

L

G = 1

R

= 10k⍀

L

0.001

0.0001

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

20

100

1k

FREQUENCY – Hz

10k 20k

TEMPERATURE – ؇C

TPC 34. Total Harmonic Distortion + Noise vs. Frequency

TPC 31. Supply Current per Amplifier vs. Temperature

1.0

64

V

= 3V

S

V

T

= 2.7V

= 25؇C

S

A

56

48

40

0.8

0.6

0.4

0.2

32

24

16

8

0

؊40 ؊25 ؊10

5

20

35

50

65

80

95 110 125

0

5

10

15

20

25

FREQUENCY – kHz

TEMPERATURE – ؇C

TPC 32. Supply Current per Amplifier vs. Temperature

TPC 35. Voltage Noise Density vs. Frequency

208

0.8

0.7

0.6

0.5

0.4

0.3

0.2

0.1

0

V

T

= 2.7V

= 25؇C

S

A

182

156

130

104

78

52

26

0

0.5

1.0

1.5

2.0

2.5

1

2

3

4

5

6

FREQUENCY – kHz

SUPPLY VOLTAGE – V

TPC 33. Supply Current per Amplifier vs. Supply Voltage

TPC 36. Voltage Noise Density vs. Frequency

–10–

REV. D

AD8601/AD8602/AD8604

208

182

156

130

V

T

= 5V

= 25؇C

S

V

T

= 5V

= 25؇C

A

S

A

104

78

52

26

0

0.5

1.0

1.5

2.0

2.5

TIME – 1s/DIV

FREQUENCY – kHz

TPC 37. Voltage Noise Density vs. Frequency

TPC 40. 0.1 Hz to 10 Hz Input Voltage Noise

64

V

= 5V

S

V

T

= 5V

= 25؇C

R

C

T

= 10k⍀

= 200pF

= 25؇C

S

L

56

48

40

A

32

24

16

8

200ns/DIV

50.0mV/DIV

0

5

10

15

20

25

FREQUENCY – kHz

TPC 38. Voltage Noise Density vs. Frequency

TPC 41. Small Signal Transient Response

V

= 2.7V

S

V

T

= 2.7V

= 25؇C

S

R

C

T

= 10k⍀

= 200pF

= 25؇C

L

A

50.0mV/DIV

200ns/DIV

TIME – 1s/DIV

TPC 39. 0.1 Hz to 10 Hz Input Voltage Noise

TPC 42. Small Signal Transient Response

REV. D

–11–

AD8601/AD8602/AD8604

V

= 5V

V

= 5V

S

R

A

T

= 10k⍀

= 1

= 25؇C

R

C

A

= 10k⍀

= 200pF

= 1

L

V

L

V

IN

A

V

A

T

= 25؇C

V

OUT

TIME – 400ns/DIV

TIME – 2.0␮s/DIV

TPC 43. Large Signal Transient Response

TPC 46. No Phase Reversal

V

= 2.7V

= 10k⍀

= 200pF

= 1

S

V

= 5V

S

R

C

A

L

R

V

= 10k⍀

= 2V p-p

= 25؇C

L

O

A

V

A

T

= 25؇C

V

IN

+0.1%

ERROR

V

OUT

؊0.1%

ERROR

V

TRACE – 0.5V/DIV

IN

V

TRACE – 10mV/DIV

OUT

TIME – 100ns/DIV

TIME – 400ns/DIV

TPC 44. Large Signal Transient Response

TPC 47. Settling Time

2.0

1.5

V

= 2.7V

= 10k⍀

= 1

S

V

T

= 2.7V

= 25؇C

S

A

R

A

T

L

V

= 25؇C

V

A

IN

1.0

0.1%

0.01%

0.5

V

0

OUT

؊0.5

؊1.0

؊1.5

؊2.0

0.01%

300

350

400

450

500

550

600

TIME – 2.0␮s/DIV

SETTLING TIME – ns

TPC 45. No Phase Reversal

TPC 48. Output Swing vs. Settling Time

–12–

REV. D

AD8601/AD8602/AD8604

Rail-to-Rail Input Stage

5

4

3

2

V

T

= 5V

= 25؇C

The input common-mode voltage range of the AD860x extends

to both positive and negative supply voltages. This maximizes the

usable voltage range of the amplifier, an important feature for

single-supply and low voltage applications. This rail-to-rail

input range is achieved by using two input differential pairs, one

NMOS and one PMOS, placed in parallel. The NMOS pair is

active at the upper end of the common-mode voltage range, and

the PMOS pair is active at the lower end.

S

A

1

0

0.1%

0.01%

؊1

؊2

The NMOS and PMOS input stages are separately trimmed

using DigiTrim to minimize the offset voltage in both differen-

tial pairs. Both NMOS and PMOS input differential pairs are

active in a 500 mV transition region, when the input common-

mode voltage is between approximately 1.5 V and 1 V below the

positive supply voltage. Input offset voltage will shift slightly in

this transition region, as shown in TPCs 5 and 6. Common-

mode rejection ratio will also be slightly lower when the input

common-mode voltage is within this transition band. Compared

to the Burr Brown OPA2340 rail-to-rail input amplifier, shown

in Figure 1, the AD860x, shown in Figure 2, exhibits lower

offset voltage shift across the entire input common-mode range,

including the transition region.

؊3

؊4

؊5

0

200

400

600

800

1,000

SETTLING TIME – ns

TPC 49. Output Swing vs. Settling Time

THEORY OF OPERATION

The AD8601/AD8602/AD8604 family of amplifiers are rail-to-

rail input and output precision CMOS amplifiers that operate

from 2.7 V to 5.0 V of power supply voltage. These amplifiers

use Analog Devices’ DigiTrim^®technology to achieve a higher

degree of precision than available from most CMOS amplifiers.

DigiTrim technology is a method of trimming the offset volt-

age of the amplifier after it has already been assembled. The

advantage in post-package trimming lies in the fact that it cor-

rects any offset voltages due to the mechanical stresses of

assembly. This technology is scalable and used with every

package option, including SOT-23-5, providing lower offset

voltages than previously achieved in these small packages.

0.7

0.4

0.1

؊0.2

؊0.5

؊0.8

؊1.1

؊1.4

The DigiTrim process is done at the factory and does not add

additional pins to the amplifier. All AD860x amplifiers are

available in standard op amp pinouts, making DigiTrim com-

pletely transparent to the user. The AD860x can be used in any

precision op amp application.

The input stage of the amplifier is a true rail-to-rail architecture,

allowing the input common-mode voltage range of the op amp

to extend to both positive and negative supply rails. The voltage

swing of the output stage is also rail-to-rail and is achieved by

using an NMOS and PMOS transistor pair connected in a com-

mon-source configuration. The maximum output voltage swing

is proportional to the output current, and larger currents will

limit how close the output voltage can get to the supply rail.

This is a characteristic of all rail-to-rail output amplifiers. With

1 mA of output current, the output voltage can reach within

20 mV of the positive rail and within 15 mV of the negative rail.

At light loads of >100 kΩ, the output swings within ~1 mV of

the supplies.

0

1

2

3

4

5

V

– V

CM

Figure 1. Burr Brown OPA2340UR Input Offset

Voltage vs. Common-Mode Voltage, 24 SOIC

Units @ 25°C

0.7

0.4

0.1

؊0.2

؊0.5

؊0.8

؊1.1

؊1.4

The open-loop gain of the AD860x is 80 dB, typical, with a load

of 2 kΩ. Because of the rail-to-rail output configuration, the

gain of the output stage and the open-loop gain of the amplifier

are dependent on the load resistance. Open-loop gain will de-

crease with smaller load resistances. Again, this is a characteristic

inherent to all rail-to-rail output amplifiers.

0

1

2

3

4

5

V

– V

CM

Figure 2. AD8602AR Input Offset Voltage vs.

Common-Mode Voltage, 300 SOIC Units @ 25°C

REV. D

–13–

AD8601/AD8602/AD8604

Input Overvoltage Protection

10pF

(OPTIONAL)

As with any semiconductor device, if a condition could exist

that would cause the input voltage to exceed the power supply,

the device’s input overvoltage characteristic must be considered.

Excess input voltage will energize internal PN junctions in the

AD860x, allowing current to flow from the input to the supplies.

4.7M⍀

V

OUT

4.7V/␮A

D1

AD8601

This input current will not damage the amplifier, provided it is

limited to 5 mA or less. This can be ensured by placing a resis-

tor in series with the input. For example, if the input voltage

could exceed the supply by 5 V, the series resistor should be at

least (5 V/5 mA) = 1 kΩ. With the input voltage within the

supply rails, a minimal amount of current is drawn into the

inputs, which, in turn, causes a negligible voltage drop across

the series resistor. Therefore, adding the series resistor will

not adversely affect circuit performance.

Figure 3. Amplifier Photodiode Circuit

High- and Low-Side Precision Current Monitoring

Because of its low input bias current and low offset voltage, the

AD860x can be used for precision current monitoring. The true

rail-to-rail input feature of the AD860x allows the amplifier to

monitor current on either high-side or low-side. Using both

amplifiers in an AD8602 provides a simple method for monitoring

both current supply and return paths for load or fault detec-

tion. Figures 4 and 5 demonstrate both circuits.

Overdrive Recovery

Overdrive recovery is defined as the time it takes the output of

an amplifier to come off the supply rail when recovering from

an overload signal. This is tested by placing the amplifier in a

closed-loop gain of 10 with an input square wave of 2 V p-p while

the amplifier is powered from either 5 V or 3 V.

3V

R2

2.49k⍀

MONITOR

OUTPUT

Q1

The AD860x has excellent recovery time from overload condi-

tions. The output recovers from the positive supply rail within

200 ns at all supply voltages. Recovery from the negative rail is

within 500 ns at 5 V supply, decreasing to within 350 ns when

the device is powered from 2.7 V.

2N3904

3V

R1

100⍀

1/2 AD8602

RETURN TO

Power-On Time

GROUND

R

SENSE

0.1⍀

Power-on time is important in portable applications, where the

supply voltage to the amplifier may be toggled to shut down the

device to improve battery life. Fast power-up behavior ensures

that the output of the amplifier will quickly settle to its final

voltage, improving the power-up speed of the entire system.

Once the supply voltage reaches a minimum of 2.5 V, the AD860x

will settle to a valid output within 1 µs. This turn-on response

time is faster than many other precision amplifiers, which can

take tens or hundreds of microseconds for their outputs to settle.

Figure 4. A Low-Side Current Monitor

R

SENSE

I

L

0.1⍀

V+

3V

R1

100⍀

1/2

AD8602

Using the AD8602 in High Source Impedance Applications

The CMOS rail-to-rail input structure of the AD860x allows

these amplifiers to have very low input bias currents, typically

0.2 pA. This allows the AD860x to be used in any application

that has a high source impedance or must use large value resis-

tances around the amplifier. For example, the photodiode

amplifier circuit shown in Figure 3 requires a low input bias

current op amp to reduce output voltage error. The AD8601

minimizes offset errors due to its low input bias current and low

offset voltage.

Q1

2N3905

MONITOR

OUTPUT

R2

2.49k⍀

Figure 5. A High-Side Current Monitor

Voltage drop is created across the 0.1 Ω resistor that is propor-

tional to the load current. This voltage appears at the inverting

input of the amplifier due to the feedback correction around the

op amp. This creates a current through R1 which, in turn, pulls

current through R2. For the low-side monitor, the monitor

output voltage is given by

The current through the photodiode is proportional to the inci-

dent light power on its surface. The 4.7 MΩ resistor converts

this current into a voltage, with the output of the AD8601

increasing at 4.7 V/µA. The feedback capacitor reduces excess

noise at higher frequencies by limiting the bandwidth of the

circuit to





 R_SENSE



Monitor Output = 3V – R2 ×

× I







^L





(2)

1



R1

BW =



(1)

2π 4.7 MΩ C

(

)

F

Using a 10 pF feedback capacitor limits the bandwidth to approxi-

mately 3.3 kHz.

–14–

REV. D

AD8601/AD8602/AD8604

For the high-side monitor, the monitor output voltage is

The AD8601, AD7476, and AD5320 are all available in space-

saving SOT-23 packages.

 R_SENSE



Monitor Output = R2 ×

× I

L







PC100 Compliance for Computer Audio Applications

Because of its low distortion and rail-to-rail input and output,

the AD860x is an excellent choice for low-cost, single-supply

audio applications, ranging from microphone amplification to

line output buffering. TPC 34 shows the total harmonic distor-

tion plus noise (THD + N) figures for the AD860x. In unity

gain, the amplifier has a typical THD + N of 0.004%, or –86 dB,

even with a load resistance of 600 Ω. This is compliant with the

PC100 specification requirements for audio in both portable

and desktop computers.

(3)



R1

Using the components shown, the monitor output transfer func-

tion is 2.5 V/A.

Using the AD8601 in Single-Supply Mixed-Signal Applications

Single-supply mixed-signal applications requiring 10 or more

bits of resolution demand both a minimum of distortion and a

maximum range of voltage swing to optimize performance. To

ensure that the A/D or D/A converters achieve their best perfor-

mance, an amplifier often must be used for buffering or signal

conditioning. The 750 µV maximum offset voltage of the

AD8601 allows the amplifier to be used in 12-bit applications

powered from a 3 V single supply, and its rail-to-rail input

and output ensure no signal clipping.

Figure 8 shows how an AD8602 can be interfaced with an AC’97

codec to drive the line output. Here, the AD8602 is used as a

unity-gain buffer from the left and right outputs of the AC’97

codec. The 100 µF output coupling capacitors block dc cur-

rent and the 20 Ω series resistors protect the amplifier from

short circuits at the jack.

Figure 6 shows the AD8601 used as an input buffer amplifier to

the AD7476, a 12-bit 1 MHz A/D converter. As with most A/D

converters, total harmonic distortion (THD) increases with

higher source impedances. By using the AD8601 in a buffer

configuration, the low output impedance of the amplifier mini-

mizes THD while the high input impedance and low bias current

of the op amp minimizes errors due to source impedance. The

8 MHz gain-bandwidth product of the AD8601 ensures no

signal attenuation up to 500 kHz, which is the maximum Nyquist

frequency for the AD7476.

5V

V

DD

2

3

C1

R4

20⍀

8

100␮F

28

35

V

DD

1

U1-A

4

R2

2k⍀

LEFT

OUT

AD1881

(AC'97)

3V

5V

REF193

0.1␮F

5

C2

100␮F

SUPPLY

R5

20⍀

36

RIGHT

OUT

1␮F

TANT

10␮F

0.1␮F

7

680nF

U1-B

V

SS

6

R3

2k⍀

4

3

V

DD

5

2

SCLK

SDATA

CS

1

R

V

S

IN

NOTE: ADDITIONAL PINS

OMITTED FOR CLARITY

␮C/␮P

AD8601

U1 = AD8602D

V

GND

IN

Figure 8. A PC100 Compliant Line Output Amplifier

SPICE Model

AD7476/AD7477

SERIAL

INTERFACE

The SPICE macro-model for the AD860x amplifier is available

and can be downloaded from the Analog Devices website at

www.analog.com. The model will accurately simulate a number

of both dc and ac parameters, including open-loop gain,

bandwidth, phase margin, input voltage range, output voltage

swing versus output current, slew rate, input voltage noise,

CMRR, PSRR, and supply current versus supply voltage. The

model is optimized for performance at 27°C. Although it will

function at different temperatures, it may lose accuracy with

respect to the actual behavior of the AD860x.

Figure 6. A Complete 3 V 12-Bit 1 MHz A/D

Conversion System

Figure 7 demonstrates how the AD8601 can be used as an output

buffer for the DAC for driving heavy resistive loads. The AD5320

is a 12-bit D/A converter that can be used with clock frequen-

cies up to 30 MHz and signal frequencies up to 930 kHz. The

rail-to-rail output of the AD8601 allows it to swing within 100 mV

of the positive supply rail while sourcing 1 mA of current. The

total current drawn from the circuit is less than 1 mA, or 3 mW

from a 3 V single supply.

3V

1␮F

V

OUT

4

3

5

2

0V TO 3.0V

4

5

6

1

3-WIRE

SERIAL

INTERFACE

1

AD5320

AD8601

R

L

2

Figure 7. Using the AD8601 as a DAC Output

Buffer to Drive Heavy Loads

REV. D

–15–

AD8601/AD8602/AD8604

OUTLINE DIMENSIONS

14-Lead Thin Shrink Small Outline Package [TSSOP]

(RU-14)

5-Lead Small Outline Transistor Package [SOT-23]

(RT-5)

Dimensions shown in millimeters

5.10

5.00

4.90

2.90 BSC

5

1

4

3

14

8

7

2.80 BSC

1.60 BSC

2

4.50

4.40

4.30

6.40

BSC

PIN 1

0.95 BSC

1

1.90

BSC

1.30

1.15

0.90

PIN 1

1.05

1.00

0.80

0.65

BSC

0.20

0.09

1.20

1.45 MAX

0.22

0.08

0.75

0.60

0.45

MAX

8؇

0؇

0.15

0.05

10؇

5؇

0؇

0.30

0.19

SEATING

PLANE

COPLANARITY

0.10

0.15 MAX

0.60

0.45

0.30

0.50

0.30

SEATING

PLANE

COMPLIANT TO JEDEC STANDARDS MO-153AB-1

COMPLIANT TO JEDEC STANDARDS MO-178AA

14-Lead Standard Small Outline Package [SOIC]

(R-14)

8-Lead Mini Small Outline Package [MSOP]

(RM-8)

Dimensions shown in millimeters and (inches)

Dimensions shown in millimeters

8.75 (0.3445)

8.55 (0.3366)

3.00

BSC

14

1

8

7

8

5

4

4.00 (0.1575)

3.80 (0.1496)

6.20 (0.2441)

5.80 (0.2283)

4.90

BSC

3.00

BSC

1

1.27 (0.0500)

BSC

0.50 (0.0197)

0.25 (0.0098)

1.75 (0.0689)

1.35 (0.0531)

؋

45؇

PIN 1

0.25 (0.0098)

0.10 (0.0039)

0.65 BSC

8؇

0؇

0.51 (0.0201)

0.31 (0.0122)

SEATING

PLANE

1.10 MAX

0.15

0.00

1.27 (0.0500)

0.40 (0.0157)

0.25 (0.0098)

0.17 (0.0067)

COPLANARITY

0.10

0.80

0.60

0.40

8؇

0؇

0.38

0.22

0.23

0.08

COMPLIANT TO JEDEC STANDARDS MS-012AB

CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS

(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR

REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN

SEATING

PLANE

COPLANARITY

0.10

COMPLIANT TO JEDEC STANDARDS MO-187AA

8-Lead Standard Small Outline Package [SOIC]

(R-8)

Dimensions shown in millimeters and (inches)

5.00 (0.1968)

4.80 (0.1890)

8

1

5

4

6.20 (0.2440)

5.80 (0.2284)

4.00 (0.1574)

3.80 (0.1497)

0.50 (0.0196)

0.25 (0.0099)

1.27 (0.0500)

BSC

؋

45؇

1.75 (0.0688)

1.35 (0.0532)

0.25 (0.0098)

0.10 (0.0040)

8؇

0.51 (0.0201)

0.31 (0.0122)

0؇ 1.27 (0.0500)

COPLANARITY

0.10

0.25 (0.0098)

0.17 (0.0067)

SEATING

PLANE

0.40 (0.0157)

COMPLIANT TO JEDEC STANDARDS MS-012AA

CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS

(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR

REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN

–16–

REV. D

AD8601/AD8602/AD8604

Revision History

Location

Page

11/03—Data Sheet changed from REV. C to REV. D.

Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Changes to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4

3/03—Data Sheet changed from REV. B to REV. C.

Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

3/03—Data Sheet changed from REV. A to REV. B.

Change to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Change to FUNCTIONAL BLOCK DIAGRAMS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1

Change to TPC 39 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11

Changes to Figures 4 and 5 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14

Changes to Equations 2 and 3 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14, 15

Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16

REV. D

–17–

–18–

–19–

–20–


型号：	AD8604ARU-REEL
厂家：	ADI
描述：	Precision CMOS Single-Supply Rail-to-Rail Input/Output Wideband Operational Amplifiers 精密CMOS单电源轨到轨输入/输出宽带运算放大器运算放大器放大器电路光电二极管
文件：	总20页 (文件大小：291K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

AD8604ARU-REEL [ADI]

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