AD8630ARZ-REEL7 [ADI]
Zero-Drift, Single-Supply, Rail-to-Rail Input/Output Operational Amplifier; 零漂移，单电源，轨到轨输入/输出运算放大器
| 型号： | AD8630ARZ-REEL7 |
| 厂家： | 
ADI |
| 描述： | Zero-Drift, Single-Supply, Rail-to-Rail Input/Output Operational Amplifier |
| 文件： | 总24页 (文件大小：414K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Zero-Drift, Single-Supply, Rail-to-Rail
Input/Output Operational Amplifier
AD8628/AD8629/AD8630
FEATURES
PIN CONFIGURATIONS
Lowest auto-zero amplifier noise
OUT
V–
1
2
3
5
V+
Low offset voltage: 1 μV
AD8628
Input offset drift: 0.002 μV/°C
Rail-to-rail input and output swing
5 V single-supply operation
TOP VIEW
(Not to Scale)
+IN
4
–IN
High gain, CMRR, and PSRR: 120 dB
Very low input bias current: 100 pA max
Low supply current: 1.0 mA
Overload recovery time: 10 μs
No external components required
Figure 1. 5-Lead TSOT (UJ-5)
and 5-Lead SOT-23 (RT-5)
NC
–IN
+IN
V–
1
2
3
4
8
7
6
5
NC
V+
AD8628
OUT
NC
TOP VIEW
(Not to Scale)
APPLICATIONS
Automotive sensors
NC = NO CONNECT
Pressure and position sensors
Strain gage amplifiers
Medical instrumentation
Thermocouple amplifiers
Precision current sensing
Photodiode amplifier
Figure 2. 8-Lead SOIC_N (R-8)
OUT A
–IN A
+IN A
V–
1
2
3
4
8
7
6
5
V+
AD8629
OUT B
–IN B
+IN B
TOP VIEW
(Not to Scale)
Figure 3. 8-Lead SOIC_N (R-8)
OUT A
–IN A
+IN A
V–
1
2
3
4
8
7
6
5
V+
AD8629
OUT B
–IN B
+IN B
TOP VIEW
(Not to Scale)
Figure 4. 8-Lead MSOP (RM-8)
1
2
3
4
5
6
7
OUT A
–IN A
+IN A
V+
14
13
12
11
OUT D
–IN D
+IN D
V–
AD8630
TOP VIEW
(Not to Scale)
+IN B
–IN B
OUT B
10 +IN C
9
8
–IN C
OUT C
Figure 5. 14-Lead SOIC_N (R-14)
OUT A
–IN A
+IN A
V+
1
2
3
4
5
6
7
14 OUT D
13 –IN D
12 +IN D
11 V–
AD8630
TOP VIEW
(Not to Scale)
+IN B
–IN B
OUT B
10 +IN C
9
8
–IN C
OUT C
Figure 6. 14-Lead TSSOP (RU-14)
Rev. E
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
© 2005 Analog Devices, Inc. All rights reserved.
AD8628/AD8629/AD8630
TABLE OF CONTENTS
General Description......................................................................... 3
Specifications..................................................................................... 4
Electrical Characteristics—Vs = 5.0 V............................................. 4
Electrical Characteristics—Vs = 2.7 V............................................. 5
Absolute Maximum Ratings............................................................ 6
ESD Caution.................................................................................. 6
Typical Performance Characteristics ............................................. 7
Functional Description.................................................................. 15
1/f Noise....................................................................................... 15
Peak-to-Peak Noise .................................................................... 16
Noise Behavior with First-Order Low-Pass Filter.................. 16
Total Integrated Input-Referred Noise
for First-Order Filter.................................................................. 16
Input Overvoltage Protection................................................... 17
Output Phase Reversal............................................................... 17
Overload Recovery Time .......................................................... 17
Infrared Sensors.......................................................................... 18
Precision Current Shunt Sensor ............................................... 19
Output Amplifier for High Precision DACs........................... 19
Outline Dimensions....................................................................... 20
Ordering Guide .......................................................................... 22
REVISION HISTORY
5/05—Rev. D to Rev. E
10/03—Rev. A to Rev. B
Changes to Ordering Guide .......................................................... 22
Changes to General Description .....................................................1
Changes to Absolute Maximum Ratings........................................4
Changes to Ordering Guide.............................................................4
Added TSOT-23 Package .............................................................. 15
1/05—Rev. C to Rev. D
Added AD8630 ...................................................................Universal
Added Figure 5 and Figure 6........................................................... 1
Changes to Caption in Figure 8 and Figure 9 ............................... 7
Changes to Caption in Figure 14.................................................... 8
Changes to Figure 17........................................................................ 8
Changes to Figure 23 and Figure 24............................................... 9
Changes to Figure 25 and Figure 26............................................. 10
Changes to Figure 31...................................................................... 11
Changes to Figure 40, Figure 41, Figure 42................................. 12
Changes to Figure 43 and Figure 44............................................. 13
Changes to Figure 51...................................................................... 15
Updated Outline Dimensions....................................................... 20
Changes to Ordering Guide .......................................................... 22
6/03—Rev. 0 to Rev. A
Changes to Specifications.................................................................3
Changes to Ordering Guide.............................................................4
Change to Functional Description............................................... 10
Updated Outline Dimensions....................................................... 15
10/02—Revision 0: Initial Version
10/04—Rev. B to Rev. C
Updated Formatting...........................................................Universal
Added AD8629 ...................................................................Universal
Added SOIC and MSOP Pin Configurations ............................... 1
Added Figure 48.............................................................................. 13
Changes to Figure 62...................................................................... 17
Added MSOP Package ................................................................... 19
Changes to Ordering Guide .......................................................... 22
Rev. E | Page 2 of 24
AD8628/AD8629/AD8630
GENERAL DESCRIPTION
This amplifier has ultralow offset, drift, and bias current. The
AD8628/AD8629/AD8630 are wide bandwidth auto-zero
amplifiers featuring rail-to-rail input and output swings and low
noise. Operation is fully specified from 2.7 V to 5 V single
supply ( 1.35 V to 2.5 V dual supply).
With an offset voltage of only 1 μV, drift of less than
0.005 μV/°C, and noise of only 0.5 μV p-p (0 Hz to 10 Hz), the
AD8628/AD8629/AD8630 are suited for applications in which
error sources cannot be tolerated. Position and pressure sensors,
medical equipment, and strain gage amplifiers benefit greatly
from nearly zero drift over their operating temperature range.
Many systems can take advantage of the rail-to-rail input and
output swings provided by the AD8628/AD8629/AD8630 to
reduce input biasing complexity and maximize SNR.
The AD8628/AD8629/AD8630 provide benefits previously
found only in expensive auto-zeroing or chopper-stabilized
amplifiers. Using Analog Devices’ topology, these zero-drift
amplifiers combine low cost with high accuracy and low noise.
No external capacitor is required. In addition, the AD8628/
AD8629/AD8630 greatly reduce the digital switching noise
found in most chopper-stabilized amplifiers.
The AD8628/AD8629/AD8630 are specified for the extended
industrial temperature range (−40°C to +125°C). The AD8628
is available in tiny TSOT-23, SOT-23, and the 8-lead narrow
SOIC plastic packages. The AD8629 is available in the standard
8-lead narrow SOIC and MSOP plastic packages. The AD8630
quad amplifier is available in 14-lead narrow SOIC and TSSOP
plastic packages.
Rev. E | Page 3 of 24
AD8628/AD8629/AD8630
SPECIFICATIONS
ELECTRICAL CHARACTERISTICS—VS = 5.0 V
VS = 5.0 V, VCM = 2.5 V, TA = 25°C, unless otherwise noted.
Table 1.
Parameter
Symbol
Conditions
Min
Typ
Max
Unit
INPUT CHARACTERISTICS
Offset Voltage
VOS
IB
1
5
10
μV
μV
pA
pA
nA
pA
pA
V
−40°C ≤ TA ≤ +125°C
Input Bias Current
(AD8630)
30
100
100
300
1.5
200
250
5
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
Input Offset Current
IOS
50
Input Voltage Range
0
Common-Mode Rejection Ratio
CMRR
AVO
VCM = 0 V to 5 V
120
115
125
120
140
130
145
135
0.002
dB
dB
dB
dB
μV/°C
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ, VO = 0.3 V to 4.7 V
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
Large Signal Voltage Gain1
Offset Voltage Drift
OUTPUT CHARACTERISTICS
Output Voltage High
∆VOS/∆T
VOH
0.02
RL = 100 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 100 kΩ to V+
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to V+
−40°C ≤ TA ≤ +125°C
4.99
4.99
4.95
4.95
4.996
4.995
4.98
4.97
1
2
10
15
50
V
V
V
V
mV
mV
mV
mV
mA
mA
mA
mA
Output Voltage Low
VOL
5
5
20
20
Short-Circuit Limit
Output Current
ISC
IO
25
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
40
30
15
POWER SUPPLY
Power Supply Rejection Ratio
PSRR
ISY
VS = 2.7 V to 5.5 V
−40°C ≤ TA ≤ +125°C
VO = 0 V
115
130
0.85
1.0
dB
mA
mA
Supply Current/Amplifier
1.1
1.2
−40°C ≤ TA ≤ +125°C
INPUT CAPACITANCE
Differential
Common-Mode
CIN
1.5
8.0
pF
pF
DYNAMIC PERFORMANCE
Slew Rate
Overload Recovery Time
Gain Bandwidth Product
NOISE PERFORMANCE
Voltage Noise
SR
RL = 10 kΩ
1.0
0.05
2.5
V/μs
ms
MHz
GBP
en p-p
en p-p
en
0.1 Hz to 10 Hz
0.1 Hz to 1.0 Hz
f = 1 kHz
0.5
0.16
22
μV p-p
μV p-p
nV/√Hz
fA/√Hz
Voltage Noise Density
Current Noise Density
in
f = 10 Hz
5
1 Gain testing is highly dependent on test bandwidth.
Rev. E | Page 4 of 24
AD8628/AD8629/AD8630
ELECTRICAL CHARACTERISTICS—VS = 2.7 V
VS = 2.7 V, VCM = 1.35 V, VO = 1.4 V, TA = 25°C, unless otherwise noted.
Table 2.
Parameter
Symbol
Conditions
Min
Typ
Max
Unit
INPUT CHARACTERISTICS
Offset Voltage
VOS
IB
1
5
10
μV
μV
pA
pA
nA
pA
pA
V
−40°C ≤ TA ≤ +125°C
Input Bias Current
(AD8630)
30
100
300
1.5
200
250
2.7
100
1.0
50
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
Input Offset Current
IOS
Input Voltage Range
0
Common-Mode Rejection Ratio
CMRR
AVO
VCM = 0 V to 2.7 V
115
110
110
105
130
120
140
130
0.002
dB
dB
dB
dB
μV/°C
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ, VO = 0.3 V to 2.4 V
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
Large Signal Voltage Gain1
Offset Voltage Drift
OUTPUT CHARACTERISTICS
Output Voltage High
∆VOS/∆T
VOH
0.02
RL = 100 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to ground
−40°C ≤ TA ≤ +125°C
RL = 100 kΩ to V+
−40°C ≤ TA ≤ +125°C
RL = 10 kΩ to V+
−40°C ≤ TA ≤ +125°C
2.68
2.68
2.67
2.67
2.695
2.695
2.68
2.675
1
2
10
15
15
V
V
V
V
mV
mV
mV
mV
mA
mA
mA
mA
Output Voltage Low
VOL
5
5
20
20
Short-Circuit Limit
Output Current
ISC
IO
10
−40°C ≤ TA ≤ +125°C
−40°C ≤ TA ≤ +125°C
10
10
5
POWER SUPPLY
Power Supply Rejection Ratio
PSRR
ISY
VS = 2.7 V to 5.5 V
−40°C ≤ TA ≤ +125°C
VO = 0 V
115
130
0.75
0.9
dB
mA
mA
Supply Current/Amplifier
1.0
1.2
−40°C ≤ TA ≤ +125°C
INPUT CAPACITANCE
Differential
Common-Mode
CIN
1.5
8.0
pF
pF
DYNAMIC PERFORMANCE
Slew Rate
Overload Recovery Time
Gain Bandwidth Product
NOISE PERFORMANCE
Voltage Noise
SR
RL = 10 kΩ
1
0.05
2
V/μs
ms
MHz
GBP
en p-p
en
in
0.1 Hz to 10 Hz
f = 1 kHz
f = 10 Hz
0.5
22
5
μV p-p
nV/√Hz
fA/√Hz
Voltage Noise Density
Current Noise Density
1 Gain testing is highly dependent on test bandwidth.
Rev. E | Page 5 of 24
AD8628/AD8629/AD8630
ABSOLUTE MAXIMUM RATINGS
Table 3.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Parameters
Ratings
Supply Voltage
6 V
Input Voltage
GND − 0.3 V to VS− + 0.3 V
Differential Input Voltage1
Output Short-Circuit Duration to GND
Storage Temperature Range
R, RM, RU, RT, UJ Packages
Operating Temperature Range
Junction Temperature Range
R, RM, RU, RT, UJ Packages
5.0 V
Indefinite
−65°C to +150°C
−40°C to +125°C
Table 4. Thermal Characteristics
Package Type
1
−65°C to +150°C
300°C
θJA
θJC
61
146
43
44
43
23
Unit
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
Lead Temperature Range
(Soldering, 60 sec)
5-Lead TSOT-23 (UJ-5)
5-Lead SOT-23 (RT-5)
8-Lead SOIC_N (R-8)
8-Lead MSOP (RM-8)
14-Lead SOIC_N (R-14)
14-Lead TSSOP (RU-14)
207
230
158
190
105
148
1 Differential input voltage is limited to 5 V or the supply voltage, whichever
is less.
1 θJA is specified for worst-case conditions, that is, θJA is specified for the device
soldered in a circuit board for surface-mount packages. This was measured
using a standard 2-layer board.
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. E | Page 6 of 24
AD8628/AD8629/AD8630
TYPICAL PERFORMANCE CHARACTERISTICS
180
100
V
T
= 2.7V
= 25°C
S
V
V
= 5V
S
160
140
120
100
80
90
80
70
60
50
40
30
A
= 2.5V
CM
= 25°C
T
A
60
40
20
10
20
0
0
–2.5
–2.5
–1.5
–0.5
0.5
1.5
2.5
–1.5
–0.5
0.5
1.5
2.5
INPUT OFFSET VOLTAGE (μV)
INPUT OFFSET VOLTAGE (
μ
V)
Figure 7. Input Offset Voltage Distribution
Figure 10. Input Offset Voltage Distribution
7
6
5
4
3
2
60
50
40
30
20
V
= 5V
V
T
= 5V
S
S
A
+85°C
= –40°C TO +125°C
+25°C
–40°C
10
0
1
0
0
2
4
6
8
10
0
1
2
3
4
5
6
TCVOS (nV/°C)
INPUT COMMON-MODE VOLTAGE (V)
Figure 8. AD8628 Input Bias Current vs. Input Common-Mode
Figure 11. Input Offset Voltage Drift
1k
1500
V
= 5V
V
T
= 5V
= 25°C
S
150°C
125°C
S
A
1000
500
0
100
10
1
SOURCE
SINK
–500
0.1
–1000
–1500
0.01
0.0001
0
1
2
3
4
5
6
0.001
0.01
0.1
1
10
INPUT COMMON-MODE VOLTAGE (V)
LOAD CURRENT (mA)
Figure 9. AD8628 Input Bias Current vs. Input Common-Mode Voltage at 5 V
Figure 12. Output Voltage to Supply Rail vs. Load Current
Rev. E | Page 7 of 24
AD8628/AD8629/AD8630
1k
1000
800
600
400
T
= 25°C
A
V
= 2.7V
S
100
10
SOURCE
SINK
1
0.1
200
0
0.01
0.0001
0.001
0.01
0.1
1
10
0
1
2
3
4
5
6
LOAD CURRENT (mA)
SUPPLY VOLTAGE (V)
Figure 13. Output Voltage to Supply Rail vs. Load Current
Figure 16. Supply Current vs. Supply Voltage
1500
1150
900
V
C
R
= 2.7V
= 20pF
= ∞
V
V
T
= 5V
S
S
60
40
20
0
= 2.5V
L
L
CM
= –40°C TO +150°C
A
φ
= 45°
M
0
45
90
450
135
180
225
100
0
–50
–25
0
25
50
75
100
125
150
175
10k
100k
FREQUENCY (Hz)
1M
10M
TEMPERATURE (°C)
Figure 14. AD8628 Input Bias Current vs. Temperature
Figure 17. Open-Loop Gain and Phase vs. Frequency
1250
1000
750
70
V
= 5V
= 20pF
= ∞
S
T
= 25°C
A
60
50
40
30
20
10
0
C
R
φ
L
L
5V
= 52.1°
M
0
2.7V
45
90
500
135
180
225
250
0
–10
–20
–30
–50
0
50
100
150
200
10k
100k
1M
10M
TEMPERATURE (°C
)
FREQUENCY (Hz)
Figure 18. Open-Loop Gain and Phase vs. Frequency
Figure 15. Supply Current vs. Temperature
Rev. E | Page 8 of 24
AD8628/AD8629/AD8630
70
60
50
40
30
20
10
0
300
270
240
210
180
150
120
90
V
C
R
= 2.7V
= 20pF
= 2kΩ
V = 5V
S
S
L
L
A
= 1
V
A
A
A
= 100
= 10
= 1
V
A
= 100
V
V
V
A = 10
V
–10
–20
–30
60
30
0
1k
10k
100k
1M
10M
100
1k
10k
100k
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 19. Closed-Loop Gain vs. Frequency
Figure 22. Output Impedance vs. Frequency
70
60
50
40
30
20
10
0
V
C
R
= 5V
= 20pF
= 2kΩ
S
L
L
A
A
= 100
= 10
V
V
= ±1.35V
= 300pF
= ∞
S
C
R
A
L
L
V
V
0V
= 1
A
= 1
V
–10
–20
–30
1k
10k
100k
1M
10M
TIME (4μs/DIV)
FREQUENCY (Hz)
Figure 23. Large Signal Transient Response
Figure 20. Closed-Loop Gain vs. Frequency
300
270
240
210
180
150
120
90
V
= 2.7V
S
A
= 1
V
V
= ±2.5V
= 300pF
= ∞
S
C
R
A
L
L
V
A
= 100
V
0V
= 1
A
= 10
60
30
0
V
100
1k
10k
100k
1M
10M
100M
TIME (5μs/DIV)
FREQUENCY (Hz)
Figure 24. Large Signal Transient Response
Figure 21. Output Impedance vs. Frequency
Rev. E | Page 9 of 24
AD8628/AD8629/AD8630
80
70
60
50
40
V
R
= ±2.5V
= 2kΩ
= 25°C
V
= ±1.35V
= 50pF
= ∞
S
S
C
R
A
L
L
L
V
T
A
= 1
0V
30
20
OS–
OS+
10
0
1
10
100
1k
TIME (4μs/DIV)
CAPACITIVE LOAD (pF)
Figure 25. Small Signal Transient Response
Figure 28. Small Signal Overshoot vs. Load Capacitance
V
= ±2.5V
= –50
= 10kΩ
= 0
S
V
= ±2.5V
= 50pF
= ∞
S
A
R
C
V
L
L
C
R
A
L
L
V
V
IN
= 1
CH1 = 50mV/DIV
CH2 = 1V/DIV
0V
0V
0V
V
OUT
TIME (4μs/DIV)
TIME (2μs/DIV)
Figure 26. Small Signal Transient Response
Figure 29. Positive Overvoltage Recovery
100
90
80
70
60
50
40
30
V
R
= ±1.35V
= 2kΩ
= 25°C
S
0V
L
T
A
V
= ±2.5V
= –50
= 10kΩ
= 0
S
A
R
C
V
L
L
V
IN
CH1 = 50mV/DIV
CH2 = 1V/DIV
OS–
V
OUT
OS+
20
10
0
0V
1
10
100
1k
TIME (10μs/DIV)
CAPACITIVE LOAD (pF)
Figure 27. Small Signal Overshoot vs. Load Capacitance
Figure 30. Negative Overvoltage Recovery
Rev. E | Page 10 of 24
AD8628/AD8629/AD8630
140
120
100
80
V
V
C
R
A
= ±2.5V
= 1kHz @ ±3V p-p
= 0pF
= 10kΩ
= 1
S
V
= ±1.35V
IN
S
L
L
V
60
+PSRR
–PSRR
0V
40
20
0
–20
–40
–60
100
1k
10k
100k
1M
10M
10M
1M
TIME (200μs/DIV)
FREQUENCY (Hz)
Figure 31. No Phase Reversal
Figure 34. PSRR vs. Frequency
140
120
100
80
140
120
100
80
V
= ±2.5V
V
= 2.7V
S
S
60
60
+PSRR
40
40
20
20
–PSRR
0
0
–20
–40
–60
–20
–40
–60
100
1k
10k
100k
1M
10M
100
1k
10k
100k
1M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 35. PSRR vs. Frequency
Figure 32. CMRR vs. Frequency
3.0
2.5
2.0
1.5
1.0
140
120
100
80
V
= 5V
S
V
R
= 2.7V
= 10kΩ
= 25°C
= 1
S
L
T
A
A
V
60
40
20
0
–20
–40
–60
0.5
0
100
1k
10k
100k
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 36. Maximum Output Swing vs. Frequency
Figure 33. CMRR vs. Frequency
Rev. E | Page 11 of 24
AD8628/AD8629/AD8630
5.5
5.0
120
105
90
V
= 2.7V
S
NOISE AT 1kHz = 21.3nV
V
R
= 5V
S
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
= 10kΩ
= 25°C
= 1
L
T
A
A
V
75
60
45
30
15
0
0.5
0
100
1k
10k
100k
1M
0
0.5
1.0
1.5
2.0
2.5
FREQUENCY (Hz)
FREQUENCY (kHz)
Figure 37. Maximum Output Swing vs. Frequency
Figure 40. Voltage Noise Density at 2.7 V from 0 Hz to 2.5 kHz
0.60
0.45
0.30
0.15
120
V
= 2.7V
S
V
= 2.7V
S
NOISE AT 10kHz = 42.4nV
105
90
75
0
60
45
–0.15
–0.30
–0.45
–0.60
30
15
0
0
1
2
3
4
5
6
7
8
9
10
0
5
10
15
20
25
TIME (μs)
FREQUENCY (kHz)
Figure 38. 0.1 Hz to 10 Hz Noise
Figure 41. Voltage Noise Density at 2.7 V from 0 Hz to 25 kHz
0.60
0.45
0.30
0.15
120
V
= 5V
S
V
= 5V
S
NOISE AT 1kHz = 22.1nV
105
90
75
0
60
45
–0.15
–0.30
–0.45
–0.60
30
15
0
0
1
2
3
4
5
6
7
8
9
10
0
0.5
1.0
1.5
2.0
2.5
TIME (μs)
FREQUENCY (kHz)
Figure 39. 0.1 Hz to 10 Hz Noise
Figure 42. Voltage Noise Density at 5 V from 0 Hz to 2.5 kHz
Rev. E | Page 12 of 24
AD8628/AD8629/AD8630
120
105
90
150
V
T
= 2.7V
= –40°C TO +150°C
S
A
V
= 5V
S
NOISE AT 10kHz = 36.4nV
100
50
0
75
60
45
I
–
SC
I
+
SC
30
15
0
–50
–100
0
5
10
15
20
25
–50
–25
0
25
50
75
100
125
150
175
FREQUENCY (kHz)
TEMPERATURE (°C)
Figure 43. Voltage Noise Density at 5 V from 0 Hz to 25 kHz
Figure 46. Output Short-Circuit Current vs. Temperature
150
120
V
T
= 5V
S
A
V
= 5V
S
= –40°C TO +150°C
105
90
100
50
0
I
–
SC
75
60
45
30
15
0
–50
I
+
SC
–100
–50
–25
0
25
50
75
100
125
150
175
0
5
10
TEMPERATURE (°C)
FREQUENCY (kHz)
Figure 44. Voltage Noise
Figure 47. Output Short-Circuit Current vs. Temperature
1k
100
10
150
V
= 5V
S
140
130
V
– V @ 1kΩ
OH
CC
V
= 2.7V TO 5V
= –40°C TO +125°C
S
V
– V @ 1kΩ
EE
120
110
OL
T
A
V
– V @ 10kΩ
OH
CC
100
90
V
– V @ 10kΩ
EE
OL
V
– V @ 100kΩ
OH
CC
80
1
V
– V @ 100kΩ
EE
OL
70
60
50
0.10
–50
–25
0
25
50
75
100
125
150
175
–50
–25
0
25
50
75
100
125
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 45. Power Supply Rejection vs. Temperature
Figure 48. Output-to-Rail Voltage vs. Temperature
Rev. E | Page 13 of 24
AD8628/AD8629/AD8630
1k
140
V
= 2.7V
V
= ±2.5V
S
SY
120
100
80
V
– V @ 1kΩ
OH
CC
100
10
V
– V @ 1kΩ
EE
OL
V
– V @ 10kΩ
OH
CC
R1
10kΩ
V
– V @ 10kΩ
EE
60
OL
+2.5V
V+
R2
100Ω
V
– V @ 100kΩ
OH
CC
V–
B
40
+
–
V
IN
28mV p-p
1
A
V
V
– V @ 100kΩ
EE
OUT
OL
V–
V+
20
0
–2.5V
0.10
–50
–25
0
25
50
75
100
125
150
175
1k
10k
100k
FREQUENCY (Hz)
1M
10M
TEMPERATURE (°C)
Figure 50. AD8629/AD8630 Channel Separation
Figure 49. Output-to-Rail Voltage vs. Temperature
Rev. E | Page 14 of 24
AD8628/AD8629/AD8630
FUNCTIONAL DESCRIPTION
The AD8628/AD8629/AD8630 are single-supply, ultrahigh
precision rail-to-rail input and output operational amplifiers.
The typical offset voltage of less than 1 μV allows these amplifi-
ers to be easily configured for high gains without risk of
excessive output voltage errors. The extremely small tempera-
ture drift of 2 nV/°C ensures a minimum of offset voltage error
over their entire temperature range of −40°C to +125°C, making
these amplifiers ideal for a variety of sensitive measurement
applications in harsh operating environments.
1/f NOISE
1/f noise, also known as pink noise, is a major contributor to
errors in dc-coupled measurements. This 1/f noise error term
can be in the range of several μV or more, and, when amplified
with the closed-loop gain of the circuit, can show up as a large
output offset. For example, when an amplifier with a 5 μV p-p
1/f noise is configured for a gain of 1,000, its output has 5 mV of
error due to the 1/f noise. But the AD8628/AD8629/AD8630
eliminate 1/f noise internally, and thereby greatly reduce output
errors.
The AD8628/AD8629/AD8630 achieve a high degree of preci-
sion through a patented combination of auto-zeroing and
chopping. This unique topology allows the AD8628/AD8629/
AD8630 to maintain their low offset voltage over a wide
temperature range and over their operating lifetime. The
AD8628/AD8629/AD8630 also optimize the noise and band-
width over previous generations of auto-zero amplifiers,
offering the lowest voltage noise of any auto-zero amplifier by
more than 50%.
The internal elimination of 1/f noise is accomplished as follows.
1/f noise appears as a slowly varying offset to AD8628/AD8629/
AD8630 inputs. Auto-zeroing corrects any dc or low frequency
offset. Therefore, the 1/f noise component is essentially removed,
leaving the AD8628/AD8629/AD8630 free of 1/f noise.
One of the biggest advantages that the AD8628/AD8629/
AD8630 bring to systems applications over competitive auto-
zero amplifiers is their very low noise. The comparison shown
in Figure 51 indicates an input-referred noise density of
19.4 nV/√Hz at 1 kHz for the AD8628, which is much better
than the LTC2050 and LMC2001. The noise is flat from dc to
1.5 kHz, slowly increasing up to 20 kHz. The lower noise at
low frequency is desirable where auto-zero amplifiers are
widely used.
Previous designs used either auto-zeroing or chopping to add
precision to the specifications of an amplifier. Auto-zeroing
results in low noise energy at the auto-zeroing frequency, at the
expense of higher low frequency noise due to aliasing of wide-
band noise into the auto-zeroed frequency band. Chopping
results in lower low frequency noise at the expense of larger
noise energy at the chopping frequency. The AD8628/AD8629/
AD8630 family uses both auto-zeroing and chopping in a
patented ping-pong arrangement to obtain lower low frequency
noise together with lower energy at the chopping and auto-
zeroing frequencies, maximizing the signal-to-noise ratio (SNR)
for the majority of applications without the need for additional
filtering. The relatively high clock frequency of 15 kHz
simplifies filter requirements for a wide, useful, noise-free
bandwidth.
120
LTC2050
105
(89.7nV/√Hz)
90
75
60
LMC2001
(31.1nV/√Hz)
45
30
The AD8628 is among the few auto-zero amplifiers offered in
the 5-lead TSOT-23 package. This provides a significant
improvement over the ac parameters of the previous auto-zero
amplifiers. The AD8628/AD8629/AD8630 have low noise over
a relatively wide bandwidth (0 Hz to 10 kHz) and can be used
where the highest dc precision is required. In systems with
signal bandwidths of from 5 kHz to 10 kHz, the AD8628/
AD8629/AD8630 provide true 16-bit accuracy, making them
the best choice for very high resolution systems.
15
0
AD8628
(19.4nV/√Hz)
MK AT 1kHz FOR ALL 3 GRAPHS
10 12
0
2
4
6
8
FREQUENCY (kHz)
Figure 51. Noise Spectral Density of AD8628 vs. Competition
Rev. E | Page 15 of 24
AD8628/AD8629/AD8630
50
45
40
35
30
25
20
15
PEAK-TO-PEAK NOISE
Because of the ping-pong action between auto-zeroing and
chopping, the peak-to-peak noise of the AD8628/AD8629/AD8630
is much lower than the competition. Figure 52 and Figure 53
show this comparison.
e
p-p = 0.5μV
n
BW = 0.1Hz TO 10Hz
10
5
0
0
10
20
30
40
50
60
70
80
90
100
FREQUENCY (kHz)
Figure 55. Simulation Transfer Function of the Test Circuit
50
45
40
35
30
25
20
15
TIME (1s/DIV)
Figure 52. AD8628 Peak-to-Peak Noise
e
p-p = 2.3μV
n
BW = 0.1Hz TO 10Hz
10
5
0
0
10
20
30
40
50
60
70
80
90
100
FREQUENCY (kHz)
Figure 56. Actual Transfer Function of the Test Circuit
The measured noise spectrum of the test circuit charted in
Figure 56 shows that noise between 5 kHz and 45 kHz is
successfully rolled off by the first-order filter.
TIME (1s/DIV)
TOTAL INTEGRATED INPUT-REFERRED
NOISE FOR FIRST-ORDER FILTER
Figure 53. LTC2050 Peak-to-Peak Noise
NOISE BEHAVIOR WITH FIRST-ORDER
LOW-PASS FILTER
For a first-order filter, the total integrated noise from the
AD8628 is lower than the LTC2050.
The AD8628 was simulated as a low-pass filter (Figure 55) and
then configured as shown in Figure 54. The behavior of the
AD8628 matches the simulated data. It was verified that noise is
rolled off by first-order filtering. Figure 55 and Figure 56 show
the difference between the simulated and actual transfer
functions of the circuit shown in Figure 54.
10
LTC2050
AD8551
AD8628
1
IN
OUT
100kΩ
1kΩ
470pF
0.1
10
100
1k
10k
3dB FILTER BANDWIDTH (Hz)
Figure 54. Test Circuit: First-Order Low-Pass Filter,
×101 Gain and 3 kHz Corner Frequency
Figure 57. 3 dB Filter Bandwidth in Hz
Rev. E | Page 16 of 24
AD8628/AD8629/AD8630
INPUT OVERVOLTAGE PROTECTION
CH1 = 50mV/DIV
CH2 = 1V/DIV
V
IN
A
= –50
Although the AD8628/AD8629/AD8630 are rail-to-rail input
amplifiers, care should be taken to ensure that the potential
difference between the inputs does not exceed the supply volt-
age. Under normal negative feedback operating conditions, the
amplifier corrects its output to ensure that the two inputs are at
the same voltage. However, if either input exceeds either supply
rail by more than 0.3 V, large currents begin to flow through the
ESD protection diodes in the amplifier.
V
0V
0V
These diodes are connected between the inputs and each supply
rail to protect the input transistors against an electrostatic dis-
charge event, and they are normally reverse-biased. However, if
the input voltage exceeds the supply voltage, these ESD diodes
can become forward-biased. Without current limiting, excessive
amounts of current could flow through these diodes, causing
permanent damage to the device. If inputs are subject to over-
voltage, appropriate series resistors should be inserted to limit
the diode current to less than 5 mA maximum.
V
OUT
TIME (500μs/DIV)
Figure 58. Positive Input Overload Recovery for the AD8628
CH1 = 50mV/DIV
CH2 = 1V/DIV
V
IN
A
= –50
V
0V
0V
OUTPUT PHASE REVERSAL
Output phase reversal occurs in some amplifiers when the input
common-mode voltage range is exceeded. As common-mode
voltage is moved outside of the common-mode range, the
outputs of these amplifiers can suddenly jump in the opposite
direction to the supply rail. This is the result of the differential
input pair shutting down, causing a radical shifting of internal
voltages that results in the erratic output behavior.
V
OUT
TIME (500μs/DIV)
The AD8628/AD8629/AD8630 amplifiers have been carefully
designed to prevent any output phase reversal, provided that
both inputs are maintained within the supply voltages. If one or
both inputs could exceed either supply voltage, a resistor should
be placed in series with the input to limit the current to less
than 5 mA. This ensures that the output does not reverse its
phase.
Figure 59. Positive Input Overload Recovery for LTC2050
CH1 = 50mV/DIV
CH2 = 1V/DIV
= –50
V
IN
A
V
0V
OVERLOAD RECOVERY TIME
Many auto-zero amplifiers are plagued by a long overload
recovery time, often in ms, due to the complicated settling
behavior of the internal nulling loops after saturation of the
outputs. The AD8628/AD8629/AD8630 have been designed so
that internal settling occurs within two clock cycles after output
saturation happens. This results in a much shorter recovery
time, less than 10 μs, when compared to other auto-zero
amplifiers. The wide bandwidth of the AD8628/AD8629/
AD8630 enhances performance when the parts are used to
drive loads that inject transients into the outputs. This is a
common situation when an amplifier is used to drive the input
of switched capacitor ADCs.
0V
V
OUT
TIME (500μs/DIV)
Figure 60. Positive Input Overload Recovery for LMC2001
Rev. E | Page 17 of 24
AD8628/AD8629/AD8630
The results shown in Figure 58 to Figure 63 are summarized in
Table 5.
0V
CH1 = 50mV/DIV
CH2 = 1V/DIV
Table 5. Overload Recovery Time
A
= –50
V
Positive Overload
Recovery (μs)
Negative Overload
Recovery (μs)
V
IN
Product
AD8628
LTC2050
LMC2001
6
9
650
40,000
25,000
35,000
V
OUT
0V
INFRARED SENSORS
Infrared (IR) sensors, particularly thermopiles, are increasingly
being used in temperature measurement for applications as
wide-ranging as automotive climate control, human ear
thermometers, home insulation analysis, and automotive repair
diagnostics. The relatively small output signal of the sensor
demands high gain with very low offset voltage and drift to
avoid dc errors.
TIME (500μs/DIV)
Figure 61. Negative Input Overload Recovery for the AD8628
0V
CH1 = 50mV/DIV
CH2 = 1V/DIV
A
= –50
V
V
IN
OUT
V
If interstage ac coupling is used, as in Figure 64, low offset and
drift prevent the input amplifier’s output from drifting close to
saturation. The low input bias currents generate minimal errors
from the sensor’s output impedance. As with pressure sensors,
the very low amplifier drift with time and temperature elimi-
nate additional errors once the temperature measurement is
calibrated. The low 1/f noise improves SNR for dc measure-
ments taken over periods often exceeding one-fifth of a second.
0V
Figure 64 shows a circuit that can amplify ac signals from
100 μV to 300 μV up to the 1 V to 3 V levels, with gain of
10,000 for accurate A/D conversion.
TIME (500μs/DIV)
Figure 62. Negative Input Overload Recovery for LTC2050
10kΩ
100kΩ
100Ω
100kΩ
5V
5V
0V
CH1 = 50mV/DIV
CH2 = 1V/DIV
100μV – 300μV
10μF
A
= –50
V
1/2 AD8629
IR
1/2 AD8629
V
IN
DETECTOR
10kΩ
f
≈ 1.6Hz
C
V
OUT
TO BIAS
VOLTAGE
Figure 64. AD8629 Used as Preamplifier for Thermopile
0V
TIME (500μs/DIV)
Figure 63. Negative Input Overload Recovery for LMC2001
Rev. E | Page 18 of 24
AD8628/AD8629/AD8630
PRECISION CURRENT SHUNT SENSOR
OUTPUT AMPLIFIER FOR HIGH PRECISION DACS
A precision current shunt sensor benefits from the unique
attributes of auto-zero amplifiers when used in a differencing
configuration, as shown in Figure 65. Current shunt sensors are
used in precision current sources for feedback control systems.
They are also used in a variety of other applications, including
battery fuel gauging, laser diode power measurement and
control, torque feedback controls in electric power steering, and
precision power metering.
The AD8628/AD8629/AD8360 are used as output amplifiers for
a 16-bit high precision DAC in a unipolar configuration. In this
case, the selected op amp needs to have very low offset voltage
(the DAC LSB is 38 μV when operated with a 2.5 V reference)
to eliminate the need for output offset trims. Input bias current
(typically a few tens of picoamperes) must also be very low,
because it generates an additional zero code error when
multiplied by the DAC output impedance (approximately 6
kΩ).
R
0.1Ω
S
R
SUPPLY
L
Rail-to-rail input and output provide full-scale output with very
little error. Output impedance of the DAC is constant and code-
independent, but the high input impedance of the AD8628/
AD8629/AD8630 minimizes gain errors. The amplifiers’ wide
bandwidth also serves well in this case. The amplifiers, with
settling time of 1 μs, add another time constant to the system,
increasing the settling time of the output. The settling time of
the AD5541 is 1 μs. The combined settling time is approxi-
mately 1.4 μs, as can be derived from the following equation:
I
100kΩ
100Ω
e = 1,000 R
100mV/mA
I
S
C
5V
AD8628
100kΩ
100Ω
C
2
2
tS
(
TOTAL
)
=
tS DAC
)
+
(
tS AD8628
)
Figure 65. Low-Side Current Sensing
In such applications, it is desirable to use a shunt with very low
resistance to minimize the series voltage drop; this minimizes
wasted power and allows the measurement of high currents
while saving power. A typical shunt might be 0.1 Ω. At
measured current values of 1 A, the shunt’s output signal is
hundreds of mV, or even V, and amplifier error sources are not
critical. However, at low measured current values in the 1 mA
range, the 100 μV output voltage of the shunt demands a very
low offset voltage and drift to maintain absolute accuracy. Low
input bias currents are also needed, so that injected bias current
does not become a significant percentage of the measured
current. High open-loop gain, CMRR, and PSRR help to
maintain the overall circuit accuracy. As long as the rate of
change of the current is not too fast, an auto-zero amplifier can
be used with excellent results.
2.5V
5V
10μF
0.1μF
0.1μF
SERIAL
INTERFACE
V
REF(REF*) REFS*
AD5541/AD5542
DD
CS
DIN
UNIPOLAR
OUTPUT
OUT
SCLK
LDAC*
AD8628
DGND
AGND
*AD5542 ONLY
Figure 66. AD8628 Used as an Output Amplifier
Rev. E | Page 19 of 24
AD8628/AD8629/AD8630
OUTLINE DIMENSIONS
2.90 BSC
5.00 (0.1968)
4.80 (0.1890)
8
1
5
4
5
1
4
3
6.20 (0.2440)
5.80 (0.2284)
4.00 (0.1574)
3.80 (0.1497)
2.80 BSC
1.60 BSC
2
1.27 (0.0500)
BSC
0.50 (0.0196)
0.25 (0.0099)
PIN 1
× 45°
1.75 (0.0688)
1.35 (0.0532)
0.95 BSC
0.25 (0.0098)
0.10 (0.0040)
1.90
BSC
*
0.90
0.87
0.84
8°
0.51 (0.0201)
0.31 (0.0122)
0° 1.27 (0.0500)
COPLANARITY
0.10
0.25 (0.0098)
0.17 (0.0067)
SEATING
PLANE
0.40 (0.0157)
*
1.00 MAX
0.20
0.08
COMPLIANT TO JEDEC STANDARDS MS-012AA
8°
4°
0°
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
0.10 MAX
0.60
0.45
0.30
0.50
0.30
SEATING
PLANE
*
COMPLIANT TO JEDEC STANDARDS MO-193-AB WITH
THE EXCEPTION OF PACKAGE HEIGHT AND THICKNESS.
Figure 67. 5-Lead Thin Small Outline Transistor Package [TSOT]
Figure 69. 8-Lead Standard Small Outline Package [SOIC_N]
(UJ-5)
Narrow Body
(R-8)
Dimensions shown in millimeters
Dimensions shown in millimeters and (inches)
3.00
BSC
2.90 BSC
8
1
5
4
5
4
3
4.90
BSC
3.00
BSC
2.80 BSC
1.60 BSC
2
PIN 1
PIN 1
0.95 BSC
0.65 BSC
1.90
BSC
1.30
1.15
0.90
1.10 MAX
0.15
0.00
0.80
0.60
0.40
8°
0°
1.45 MAX
0.38
0.22
0.22
0.08
0.23
0.08
COPLANARITY
0.10
SEATING
PLANE
10°
5°
0°
0.15 MAX
0.50
0.30
0.60
0.45
0.30
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-187AA
COMPLIANT TO JEDEC STANDARDS MO-178AA
Figure 68. 5-Lead Small Outline Transistor Package [SOT-23]
Figure 70. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
(RT-5)
Dimensions shown in millimeters
Dimensions shown in millimeters
Rev. E | Page 20 of 24
AD8628/AD8629/AD8630
5.10
5.00
4.90
8.75 (0.3445)
8.55 (0.3366)
14
1
8
7
4.00 (0.1575)
3.80 (0.1496)
6.20 (0.2441)
5.80 (0.2283)
14
8
7
4.50
4.40
4.30
6.40
BSC
1.27 (0.0500)
BSC
0.50 (0.0197)
0.25 (0.0098)
1.75 (0.0689)
1.35 (0.0531)
× 45°
0.25 (0.0098)
0.10 (0.0039)
1
PIN 1
8°
0°
0.51 (0.0201)
0.31 (0.0122)
SEATING
PLANE
0.65
BSC
1.27 (0.0500)
0.40 (0.0157)
1.05
1.00
0.80
COPLANARITY
0.10
0.25 (0.0098)
0.17 (0.0067)
0.20
1.20
MAX
0.09
0.75
0.60
0.45
COMPLIANT TO JEDEC STANDARDS MS-012AB
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
8°
0°
0.15
0.05
0.30
0.19
SEATING
PLANE
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-153AB-1
Figure 71. 14-Lead Standard Small Outline Package [SOIC_N]
Figure 72. 14-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-14)
Narrow Body
(R-14)
Dimensions shown in millimeters and (inches)
Dimensions shown in millimeters
Rev. E | Page 21 of 24
AD8628/AD8629/AD8630
ORDERING GUIDE
Model
AD8628AUJ-R2
Temperature Range
Package Description
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
5-Lead TSOT-23
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead SOIC_N
8-Lead MSOP
Package Option
UJ-5
UJ-5
UJ-5
UJ-5
UJ-5
UJ-5
R-8
R-8
R-8
R-8
R-8
Branding
AYB
AYB
AYB
A0L
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
AD8628AUJ-REEL
AD8628AUJ-REEL7
AD8628AUJZ-R21
AD8628AUJZ-REEL1
AD8628AUJZ-REEL71
AD8628AR
AD8628AR-REEL
AD8628AR-REEL7
AD8628ARZ1
AD8628ARZ-REEL1
AD8628ARZ-REEL71
AD8628ART-R2
AD8628ART-REEL7
AD8628ARTZ-R21
AD8628ARTZ-REEL71
AD8629ARZ1
AD8629ARZ-REEL1
AD8629ARZ-REEL71
AD8629ARMZ-R21
AD8629ARMZ-REEL1
AD8630ARUZ1
AD8630ARUZ-REEL1
AD8630ARZ1
A0L
A0L
R-8
RT-5
RT-5
RT-5
RT-5
R-8
AYA
AYA
A0L
A0L
R-8
R-8
RM-8
RM-8
RU-14
RU-14
R-14
R-14
R-14
A06
A06
8-Lead MSOP
14-Lead TSSOP
14-Lead TSSOP
14-Lead SOIC_N
14-Lead SOIC_N
14-Lead SOIC_N
AD8630ARZ-REEL1
AD8630ARZ-REEL71
1 Z = Pb-free part.
Rev. E | Page 22 of 24
AD8628/AD8629/AD8630
NOTES
Rev. E | Page 23 of 24
AD8628/AD8629/AD8630
NOTES
©2005 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
C02735–0–5/05(E)
Rev. E | Page 24 of 24
相关型号：
AD8631ART-R2
IC OP-AMP, 4000 uV OFFSET-MAX, 5 MHz BAND WIDTH, PDSO5, SOT-23, 5 PIN, Operational Amplifier
ADI
AD8631ART-REEL
IC OP-AMP, 4000 uV OFFSET-MAX, 5 MHz BAND WIDTH, PDSO5, SOT-23, 5 PIN, Operational Amplifier
ADI
AD8631ARTZ-REEL7
IC OP-AMP, 4000 uV OFFSET-MAX, 5 MHz BAND WIDTH, PDSO5, SOT-23, 5 PIN, Operational Amplifier
ADI
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