AD9259ABCPZ-50 [ADI]
Quad, 14-Bit, 50 MSPS Serial LVDS 1.8 V ADC;型号: | AD9259ABCPZ-50 |
厂家: | ADI |
描述: | Quad, 14-Bit, 50 MSPS Serial LVDS 1.8 V ADC 转换器 |
文件: | 总53页 (文件大小:1613K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Quad, 14-Bit, 50 MSPS
Serial LVDS 1.8 V ADC
Data Sheet
AD9259
FEATURES
FUNCTIONAL BLOCK DIAGRAM
AVDD
PDWN
AD9259
T/H
DRVDD
DRGND
4 ADCs integrated into 1 package
98 mW ADC power per channel at 50 MSPS
SNR = 73 dB (to Nyquist)
14
VIN + A
VIN – A
SERIAL
LVDS
D + A
D – A
PIPELINE
ADC
ENOB = 12 bits
SFDR = 84 dBc (to Nyquist)
Excellent linearity
DNL = 0.5 LSB (typical)
INL = 1.5 LSB (typical)
Serial LVDS (ANSI-644, default)
Low power, reduced signal option (similar to IEEE 1596.3)
Data and frame clock outputs
315 MHz full-power analog bandwidth
2 V p-p input voltage range
14
14
VIN + B
VIN – B
PIPELINE
ADC
SERIAL
LVDS
D + B
D – B
T/H
T/H
T/H
VIN + C
VIN – C
SERIAL
LVDS
D + C
D – C
PIPELINE
ADC
14
VIN + D
VIN – D
SERIAL
LVDS
D + D
D – D
PIPELINE
ADC
VREF
FCO+
FCO–
SENSE
+
0.5V
–
DATA RATE
REFT
REFB
REF
SELECT
1.8 V supply operation
Serial port control
MULTIPLIER
SERIAL PORT
INTERFACE
DCO+
DCO–
Full-chip and individual-channel power-down modes
Flexible bit orientation
SCLK/DTP
RBIASAGND CSB SDIO/ODM
CLK+ CLK–
Figure 1.
Built-in and custom digital test pattern generation
Programmable clock and data alignment
Programmable output resolution
Standby mode
The ADC automatically multiplies the sample rate clock for the
appropriate LVDS serial data rate. A data clock output (DCO) for
capturing data on the output and a frame clock output (FCO)
for signaling a new output byte are provided. Individual-channel
power-down is supported and typically consumes less than 2 mW
when all channels are disabled.
APPLICATIONS
Medical imaging and nondestructive ultrasound
Portable ultrasound and digital beam-forming systems
Quadrature radio receivers
Diversity radio receivers
Tape drives
Optical networking
The ADC contains several features designed to maximize
flexibility and minimize system cost, such as programmable
clock and data alignment and programmable digital test pattern
generation. The available digital test patterns include built-in
deterministic and pseudorandom patterns, along with custom user-
defined test patterns entered via the serial port interface (SPI).
Test equipment
GENERAL DESCRIPTION
The AD9259 is available in a RoHS-compliant, 48-lead LFCSP. It is
specified over the industrial temperature range of −40°C to +85°C.
The AD9259 is a quad, 14-bit, 50 MSPS analog-to-digital con-
verter (ADC) with an on-chip sample-and-hold circuit designed
for low cost, low power, small size, and ease of use. The product
operates at a conversion rate of up to 50 MSPS and is optimized for
outstanding dynamic performance and low power in applications
where a small package size is critical.
PRODUCT HIGHLIGHTS
1. Small Footprint. Four ADCs are contained in a small, space-
saving package.
2. Low power of 98 mW/channel at 50 MSPS.
3. Ease of Use. A data clock output (DCO) operates at
frequencies of up to 350 MHz and supports double data
rate (DDR) operation.
4. User Flexibility. The SPI control offers a wide range of flexible
features to meet specific system requirements.
5. Pin-Compatible Family. This includes the AD9287 (8-bit),
AD9219 (10-bit), and AD9228 (12-bit).
The ADC requires a single 1.8 V power supply and LVPECL-/
CMOS-/LVDS-compatible sample rate clock for full performance
operation. No external reference or driver components are
required for many applications.
Rev. E
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.461.3113 ©2006–2011 Analog Devices, Inc. All rights reserved.
AD9259* PRODUCT PAGE QUICK LINKS
Last Content Update: 06/09/2017
COMPARABLE PARTS
View a parametric search of comparable parts.
TOOLS AND SIMULATIONS
• Visual Analog
• AD9259 IBIS Models
EVALUATION KITS
REFERENCE MATERIALS
• AD9259 Evaluation Board
Technical Articles
DOCUMENTATION
Application Notes
• Matching An ADC To A Transformer
• MS-2210: Designing Power Supplies for High Speed ADC
• AN-1142: Techniques for High Speed ADC PCB Layout
• AN-282: Fundamentals of Sampled Data Systems
• AN-345: Grounding for Low-and-High-Frequency Circuits
DESIGN RESOURCES
• AD9259 Material Declaration
• PCN-PDN Information
• Quality And Reliability
• Symbols and Footprints
• AN-501: Aperture Uncertainty and ADC System
Performance
• AN-715: A First Approach to IBIS Models: What They Are
and How They Are Generated
• AN-737: How ADIsimADC Models an ADC
DISCUSSIONS
View all AD9259 EngineerZone Discussions.
• AN-741: Little Known Characteristics of Phase Noise
• AN-742: Frequency Domain Response of Switched-
Capacitor ADCs
SAMPLE AND BUY
Visit the product page to see pricing options.
• AN-756: Sampled Systems and the Effects of Clock Phase
Noise and Jitter
• AN-807: Multicarrier WCDMA Feasibility
• AN-808: Multicarrier CDMA2000 Feasibility
TECHNICAL SUPPORT
Submit a technical question or find your regional support
number.
• AN-812: MicroController-Based Serial Port Interface (SPI)
Boot Circuit
• AN-827: A Resonant Approach to Interfacing Amplifiers to
Switched-Capacitor ADCs
DOCUMENT FEEDBACK
Submit feedback for this data sheet.
• AN-835: Understanding High Speed ADC Testing and
Evaluation
• AN-905: Visual Analog Converter Evaluation Tool Version
1.0 User Manual
• AN-935: Designing an ADC Transformer-Coupled Front
End
Data Sheet
• AD9259: Quad, 14-Bit, 50 MSPS Serial LVDS 1.8 V ADC
Data Sheet
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AD9259
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Analog Input Considerations ................................................... 19
Clock Input Considerations...................................................... 21
Serial Port Interface (SPI).............................................................. 29
Hardware Interface..................................................................... 29
Memory Map .................................................................................. 31
Reading the Memory Map Table.............................................. 31
Reserved Locations .................................................................... 31
Default Values............................................................................. 31
Logic Levels................................................................................. 31
Evaluation Board ............................................................................ 35
Power Supplies............................................................................ 35
Input Signals................................................................................ 35
Output Signals ............................................................................ 35
Default Operation and Jumper Selection Settings................. 36
Alternative Analog Input Drive Configuration...................... 37
Outline Dimensions....................................................................... 51
Ordering Guide .......................................................................... 51
Applications....................................................................................... 1
General Description ......................................................................... 1
Functional Block Diagram .............................................................. 1
Product Highlights ........................................................................... 1
Revision History ............................................................................... 3
Specifications..................................................................................... 4
AC Specifications.......................................................................... 5
Digital Specifications ................................................................... 6
Switching Specifications .............................................................. 7
Timing Diagrams.......................................................................... 8
Absolute Maximum Ratings.......................................................... 10
Thermal Impedance................................................................... 10
ESD Caution................................................................................ 10
Pin Configuration and Function Descriptions........................... 11
Equivalent Circuits ......................................................................... 13
Typical Performance Characteristics ........................................... 15
Theory of Operation ...................................................................... 19
Rev. E | Page 2 of 52
Data Sheet
AD9259
REVISION HISTORY
Changes to Figure 2 to Figure 4...............................................................7
Changes to Figure 10...............................................................................12
Changes to Figure 15 to Figure 17, Figure 22, and Figure 31..........14
Changes to Figure 21 and Figure 22 Captions....................................15
Changes to Figure 41...............................................................................19
Changes to Clock Duty Cycle Considerations Section.....................20
Changes to Power Dissipation and Power-Down Mode Section...21
Changes to Figure 50 to Figure 52 Captions.......................................23
Change to Table 8.....................................................................................23
Changes to Table 9 Endnote ..................................................................24
Changes to Digital Outputs and Timing Section...............................25
Added Table 10.........................................................................................25
Changes to RBIAS Pin Section..............................................................26
Deleted Figure 53 and Figure 54...........................................................26
Changes to Figure 56...............................................................................27
Changes to Hardware Interface Section ..............................................28
Added Figure 57.......................................................................................29
Changes to Table 15.................................................................................29
Changes to Reading the Memory Map Table Section ......................30
Change to Output Signals Section........................................................34
Changes to Figure 60...............................................................................34
Changes to Default Operation and
12/11—Rev. D to Rev. E
Changes to Output Signals Section and Figure 60......................35
Change to Default Operation and Jumper Selection Settings
Section ..............................................................................................36
Change to Figure 63........................................................................39
Added Endnote 2 in Ordering Guide...........................................51
4/10—Rev. C to Rev. D
Changes to Table 16 ........................................................................33
Updated Outline Dimensions........................................................51
Changes to Ordering Guide...........................................................51
11/09—Rev. B to Rev. C
Added EPAD Note to Figure 5 ......................................................11
Changes to Input Signals Section and Figure 60.........................35
Updated Outline Dimensions........................................................51
Changes to Ordering Guide...........................................................51
7/07—Rev. A to Rev. B
Change to General Description.......................................................1
Changes to Figure 2 and Figure 4....................................................7
Changes to the Hardware Interface Section ................................29
Changes to Table 17 ........................................................................48
Jumper Selection Settings Section ...................................................35
Changes to Alternative Analog Input Drive
Configuration Section........................................................................36
Changes to Figure 63...............................................................................38
Changes to Table 17.................................................................................46
Changes to Ordering Guide...................................................................50
5/07—Rev. 0 to Rev. A
Changes to Effective Number of Bits (ENOB)..................................... 4
Changes to Logic Output (SDIO/ODM) .............................................. 5
Added Endnote 3 to Table 3..................................................................... 5
Change to Pipeline Latency ..................................................................... 6
6/06—Revision 0: Initial Version
Rev. E | Page 3 of 52
AD9259
Data Sheet
SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, 2 V p-p differential input, 1.0 V internal reference, AIN = −0.5 dBFS, unless otherwise noted.
Table 1.
Parameter1
Temperature
Min
Typ
Max
Unit
RESOLUTION
14
Bits
ACCURACY
No Missing Codes
Offset Error
Offset Matching
Gain Error
Full
Full
Full
Full
Full
Full
Full
Guaranteed
±1
±2
±0.5
±0.3
±±
mV
±±
mV
±2
% FS
% FS
LSB
LSB
Gain Matching
±0.7
±1.0
±3.5
Differential Nonlinearity (DNL)
Integral Nonlinearity (INL)
TEMPERATURE DRIFT
Offset Error
Gain Error
Reference Voltage (1 V Mode)
REFERENCE
±0.5
±1.5
Full
Full
Full
±2
±17
±21
ppm/°C
ppm/°C
ppm/°C
Output Voltage Error (VREF = 1 V)
Load Regulation at 1.0 mA (VREF = 1 V)
Input Resistance
Full
Full
Full
±5
3
6
±30
mV
mV
kΩ
ANALOG INPUTS
Differential Input Voltage (VREF = 1 V)
Common-Mode Voltage
Differential Input Capacitance
Analog Bandwidth, Full Power
POWER SUPPLY
Full
Full
Full
Full
2
V p-p
V
pF
AVDD/2
7
315
MHz
AVDD
DRVDD
IAVDD
IDRVDD
Full
Full
Full
Full
Full
Full
Full
Full
Full
1.7
1.7
1.±
1.±
1±5
32.5
392
2
1.9
1.9
192.5
34.7
409
4
V
V
mA
mA
mW
mW
mW
dB
Total Power Dissipation (Including Output Drivers)
Power-Down Dissipation
Standby Dissipation2
CROSSTALK
72
−100
−100
CROSSTALK (Overrange Condition)3
dB
1 See the AN-±35 Application Note, Understanding High Speed ADC Testing and Evaluation, at www.analog.com for definitions and for details on how these tests were
completed.
2 Can be controlled via the SPI.
3 Overrange condition is specific with 6 dB of the full-scale input range.
Rev. E | Page 4 of 52
Data Sheet
AD9259
AC SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, 2 V p-p differential input, 1.0 V internal reference, AIN = −0.5 dBFS, unless otherwise noted.
Table 2.
Parameter1
Temperature
Min
Typ
Max
Unit
SIGNAL-TO-NOISE RATIO (SNR)
fIN = 2.4 MHz
fIN = 19.7 MHz
Full
Full
Full
73.5
73.0
72.±
dB
dB
dB
71.0
fIN = 70 MHz
SIGNAL-TO-NOISE AND DISTORTION RATIO (SINAD)
fIN = 2.4 MHz
fIN = 19.7 MHz
Full
Full
Full
72.7
72.2
72.0
dB
dB
dB
70.2
11.5
73
fIN = 70 MHz
EFFECTIVE NUMBER OF BITS (ENOB)
fIN = 2.4 MHz
fIN = 19.7 MHz
Full
Full
Full
11.92
11.±5
11.±
Bits
Bits
Bits
fIN = 70 MHz
SPURIOUS-FREE DYNAMIC RANGE (SFDR)
fIN = 2.4 MHz
fIN = 19.7 MHz
Full
Full
Full
±4
±4
7±
dBc
dBc
dBc
fIN = 70 MHz
WORST HARMONIC (Second or Third)
fIN = 2.4 MHz
fIN = 19.7 MHz
Full
Full
Full
−±±
−±4
−7±
dBc
dBc
dBc
−73
−±0
fIN = 70 MHz
WORST OTHER (Excluding Second or Third)
fIN = 2.4 MHz
fIN = 19.7 MHz
Full
Full
Full
−90
−90
−±±
dBc
dBc
dBc
fIN = 70 MHz
TWO-TONE INTERMODULATION DISTORTION (IMD)—AIN1
AND AIN2 = −7.0 dBFS
fIN1 = 15 MHz, fIN2 = 16 MHz
fIN1 = 70 MHz, fIN2 = 71 MHz
25°C
25°C
±0.0
±0.0
dBc
dBc
1 See the AN-±35 Application Note, Understanding High Speed ADC Testing and Evaluation, at www.analog.com for definitions and for details on how these tests were
completed.
Rev. E | Page 5 of 52
AD9259
Data Sheet
DIGITAL SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, 2 V p-p differential input, 1.0 V internal reference, AIN = −0.5 dBFS, unless otherwise noted.
Table 3.
Parameter1
Temperature
Min
Typ
Max
Unit
CLOCK INPUTS (CLK+, CLK−)
Logic Compliance
CMOS/LVDS/LVPECL
Differential Input Voltage2
Input Common-Mode Voltage
Input Resistance (Differential)
Input Capacitance
Full
Full
25°C
25°C
250
mV p-p
V
kΩ
pF
1.2
20
1.5
LOGIC INPUTS (PDWN, SCLK/DTP)
Logic 1 Voltage
Logic 0 Voltage
Input Resistance
Input Capacitance
Full
Full
25°C
25°C
1.2
1.2
3.6
0.3
V
V
kΩ
pF
30
0.5
LOGIC INPUT (CSB)
Logic 1 Voltage
Logic 0 Voltage
Full
Full
3.6
0.3
V
V
Input Resistance
Input Capacitance
25°C
25°C
70
0.5
kΩ
pF
LOGIC INPUT (SDIO/ODM)
Logic 1 Voltage
Logic 0 Voltage
Full
Full
1.2
0
DRVDD + 0.3
0.3
V
V
Input Resistance
Input Capacitance
25°C
25°C
30
2
kΩ
pF
LOGIC OUTPUT (SDIO/ODM)3
Logic 1 Voltage (IOH = ±00 μA)
Logic 0 Voltage (IOL = 50 μA)
DIGITAL OUTPUTS (D + x, D − x), (ANSI-644)
Logic Compliance
Full
Full
1.79
V
V
0.05
LVDS
Differential Output Voltage (VOD)
Output Offset Voltage (VOS)
Output Coding (Default)
Full
Full
247
1.125
454
1.375
mV
V
Offset binary
LVDS
DIGITAL OUTPUTS (D + x, D − x),
(Low Power, Reduced Signal Option)
Logic Compliance
Differential Output Voltage (VOD)
Output Offset Voltage (VOS)
Output Coding (Default)
Full
Full
150
1.10
250
1.30
mV
V
Offset binary
1 See the AN-±35 Application Note, Understanding High Speed ADC Testing and Evaluation, at www.analog.com for definitions and for details on how these tests were
completed.
2 This is specified for LVDS and LVPECL only.
3 This is specified for 13 SDIO pins sharing the same connection.
Rev. E | Page 6 of 52
Data Sheet
AD9259
SWITCHING SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, 2 V p-p differential input, 1.0 V internal reference, AIN = −0.5 dBFS, unless otherwise noted.
Table 4.
Parameter1, 2
Temp
Min
Typ
Max
Unit
CLOCK3
Maximum Clock Rate
Minimum Clock Rate
Clock Pulse Width High (tEH)
Clock Pulse Width Low (tEL)
OUTPUT PARAMETERS3
Propagation Delay (tPD)
Rise Time (tR) (20% to ±0%)
Fall Time (tF) (20% to ±0%)
FCO Propagation Delay (tFCO
Full
Full
Full
Full
50
MSPS
MSPS
ns
10
10
10
ns
Full
Full
Full
Full
Full
2.0
2.0
2.7
3.5
3.5
ns
ps
ps
ns
ns
300
300
2.7
)
)
4
DCO Propagation Delay (tCPD
tFCO +
(tSAMPLE/2±)
(tSAMPLE/2±)
(tSAMPLE/2±)
±50
4
DCO to Data Delay (tDATA
)
Full
Full
Full
(tSAMPLE/2±) − 300
(tSAMPLE/2±) − 300
(tSAMPLE/2±) + 300
(tSAMPLE/2±) + 300
±150
ps
ps
ps
4
DCO to FCO Delay (tFRAME
)
Data to Data Skew
(tDATA-MAX − tDATA-MIN
)
Wake-Up Time (Standby)
Wake-Up Time (Power-Down)
Pipeline Latency
25°C
25°C
Full
600
375
±
ns
μs
CLK
cycles
APERTURE
Aperture Delay (tA)
Aperture Uncertainty (Jitter)
Out-of-Range Recovery Time
25°C
25°C
25°C
500
<1
2
ps
ps rms
CLK
cycles
1 See the AN-±35 Application Note, Understanding High Speed ADC Testing and Evaluation, at www.analog.com for definitions and for details on how these tests were
completed.
2 Measured on standard FR-4 material.
3 Can be adjusted via the SPI.
4 tSAMPLE/2± is based on the number of bits multiplied by 2; delays are based on half duty cycles.
Rev. E | Page 7 of 52
AD9259
Data Sheet
TIMING DIAGRAMS
N – 1
VIN ± x
tA
N
tEH
tEL
CLK–
CLK+
tCPD
DCO–
DCO+
tFRAME
tFCO
FCO–
FCO+
tPD
tDATA
D – x
D + x
MSB
N – 9
D12
D11
D10
D9
D8
D7
D6
N – 9
D5
N – 9
D4
N – 9
D3
N – 9
D2
N – 9
D1
N – 9
D0
N – 9
MSB
N – 8
D12
N – 8
N – 9 N – 9 N – 9 N – 9 N – 9 N – 9
Figure 2. 14-Bit Data Serial Stream, MSB First (Default)
N – 1
VIN ± x
tA
N
tEH
tEL
CLK–
CLK+
tCPD
DCO–
DCO+
tFRAME
tFCO
FCO–
FCO+
tPD
tDATA
D – x
D + x
MSB
N – 9
D10
N – 9
D9
N – 9
D8
N – 9
D7
N – 9
D6
N – 9
D5
N – 9
D4
N – 9
D3
N – 9
D2
N – 9
D1
N – 9
D0
N – 9
MSB
N – 8
D10
N – 8
Figure 3. 12-Bit Data Serial Stream, MSB First
Rev. E | Page 8 of 52
Data Sheet
AD9259
N – 1
VIN ± x
tA
N
tEH
tEL
CLK–
CLK+
tCPD
DCO–
DCO+
tFRAME
tFCO
FCO–
FCO+
tPD
tDATA
D – x
D + x
LSB
N – 9
D0
D1
D2
D3
D4
D5
D6
N – 9
D7
N – 9
D8
N – 9
D9
N – 9
D10
N – 9
D11
N – 9
D12
N – 9
LSB
N – 8
D0
N – 8
N – 9 N – 9 N – 9 N – 9 N – 9 N – 9
Figure 4. 14-Bit Data Serial Stream, LSB First
Rev. E | Page 9 of 52
AD9259
Data Sheet
ABSOLUTE MAXIMUM RATINGS
Table 5.
Parameter
Rating
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
ELECTRICAL
AVDD to AGND
DRVDD to DRGND
AGND to DRGND
AVDD to DRVDD
Digital Outputs1 to DRGND
CLK+, CLK− to AGND
VIN + x, VIN – x to AGND
SDIO/ODM to AGND
PDWN, SCLK/DTP, CSB to AGND
REFT, REFB, RBIAS to AGND
VREF, SENSE to AGND
ENVIRONMENTAL
Operating Temperature
Range (Ambient)
Maximum Junction
Temperature
−0.3 V to +2.0 V
−0.3 V to +2.0 V
−0.3 V to +0.3 V
−2.0 V to +2.0 V
−0.3 V to +2.0 V
−0.3 V to +3.9 V
−0.3 V to +2.0 V
−0.3 V to +2.0 V
−0.3 V to +3.9 V
−0.3 V to +2.0 V
−0.3 V to +2.0 V
THERMAL IMPEDANCE
Table 6.
Air Flow Velocity (m/sec)
1
θJA
24
21
19
θJB
θJC
Unit
°C/W
°C/W
°C/W
0.0
1.0
2.5
12.6
1.2
−40°C to +±5°C
150°C
1 θJA for a 4-layer PCB with solid ground plane (simulated). Exposed pad
soldered to PCB.
Lead Temperature
(Soldering, 10 sec)
300°C
ESD CAUTION
Storage Temperature
Range (Ambient)
−65°C to +150°C
1 Digital outputs include D + x, D − x, DCO+, DCO−, FCO+, FCO−.
Rev. E | Page 10 of 52
Data Sheet
AD9259
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
PIN 1
INDICATOR
AVDD
AVDD
VIN – D
VIN + D
AVDD
AVDD
CLK–
1
2
36
35
34
33
32
31
30
29
28
27
26
25
AVDD
AVDD
3
VIN – A
VIN + A
AVDD
EXPOSED PADDLE, PIN 0
(BOTTOM OF PACKAGE)
4
5
6
PDWN
AD9259
TOP VIEW
7
CSB
8
CLK+
SDIO/ODM
SCLK/DTP
AVDD
9
AVDD
AVDD
DRGND
DRVDD
10
11
12
DRGND
DRVDD
NOTES
1. THE EXPOSED THERMAL PAD ON THE BOTTOM OF THE PACKAGE PROVIDES THE
ANALOG GROUND FOR THE PART. THIS EXPOSED PAD MUST BE CONNECTED TO
GROUND FOR PROPER OPERATIONAL.
ꢀ
Figure 5.Pin Configuration
Table 7. Pin Function Descriptions
Pin No.
Mnemonic
Description
0
AGND
AVDD
Analog Ground (Exposed Paddle)
1.8 V Analog Supply
1, 2, 5, 6, 9, 10, 27, 32,
35, 36, 39, 45, 46
11, 26
12, 25
3
4
7
DRGND
DRVDD
VIN − D
VIN + D
CLK−
Digital Output Driver Ground
1.8 V Digital Output Driver Supply
ADC D Analog Input Complement
ADC D Analog Input True
Input Clock Complement
8
CLK+
Input Clock True
13
14
15
16
17
18
19
20
21
22
23
24
28
29
D − D
D + D
D − C
D + C
D − B
D + B
D − A
D + A
FCO−
FCO+
DCO−
DCO+
SCLK/DTP
SDIO/ODM
ADC D Digital Output Complement
ADC D Digital Output True
ADC C Digital Output Complement
ADC C Digital Output True
ADC B Digital Output Complement
ADC B Digital Output True
ADC A Digital Output Complement
ADC A Digital Output True
Frame Clock Output Complement
Frame Clock Output True
Data Clock Output Complement
Data Clock Output True
Serial Clock/Digital Test Pattern
Serial Data I/O/Output Driver Mode
Rev. E | Page 11 of 52
AD9259
Data Sheet
Pin No.
30
Mnemonic
CSB
Description
Chip Select Bar
31
33
34
37
3±
40
41
42
43
44
47
4±
PDWN
VIN + A
VIN − A
VIN − B
VIN + B
RBIAS
SENSE
VREF
REFB
Power-Down
ADC A Analog Input True
ADC A Analog Input Complement
ADC B Analog Input Complement
ADC B Analog Input True
External resistor sets the internal ADC core bias current
Reference Mode Selection
Voltage Reference Input/Output
Differential Reference (Negative)
Differential Reference (Positive)
ADC C Analog Input True
REFT
VIN + C
VIN − C
ADC C Analog Input Complement
Rev. E | Page 12 of 52
Data Sheet
AD9259
EQUIVALENT CIRCUITS
DRVDD
V
V
D–
D+
VIN ± x
V
V
DRGND
Figure 9. Equivalent Digital Output Circuit
Figure 6. Equivalent Analog Input Circuit
10Ω
CLK+
10kΩ
10kΩ
1.25V
1kΩ
SCLK/DTP
AND PDWN
10Ω
CLK–
30kΩ
Figure 7. Equivalent Clock Input Circuit
Figure 10. Equivalent SCLK/DTP and PDWN Input Circuit
100Ω
RBIAS
350Ω
SDIO/ODM
30kΩ
Figure 11. Equivalent RBIAS Circuit
Figure 8. Equivalent SDIO/ODM Input Circuit
Rev. E | Page 13 of 52
AD9259
Data Sheet
AVDD
70kΩ
1kΩ
CSB
VREF
6kΩ
Figure 12. Equivalent CSB Input Circuit
Figure 14. Equivalent VREF Circuit
1kΩ
SENSE
Figure 13. Equivalent SENSE Circuit
Rev. E | Page 14 of 52
Data Sheet
AD9259
TYPICAL PERFORMANCE CHARACTERISTICS
0
0
–20
AIN = –0.5dBFS
SNR = 67.31dB
ENOB = 10.89 BITS
SFDR = 77.38dBc
AIN = –0.5dBFS
SNR = 73.8dB
ENOB = 11.97 BITS
SFDR = 83.4dBc
–20
–40
–40
–60
–80
–60
–80
–100
–120
–100
–120
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 15. Single-Tone 32k FFT with fIN = 2.4 MHz, fSAMPLE = 50 MSPS
Figure 18. Single-Tone 32k FFT with fIN = 170 MHz, fSAMPLE = 50 MSPS
0
0
AIN = –0.5dBFS
SNR = 66.87dB
ENOB = 10.82 BITS
AIN = –0.5dBFS
SNR = 72.94dB
ENOB = 11.82 BITS
–20
–20
SFDR = 78.60dBc
SFDR = 74.97dBc
–40
–40
–60
–80
–60
–80
–100
–120
–100
–120
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 16. Single-Tone 32k FFT with fIN = 70 MHz, fSAMPLE = 50 MSPS
Figure 19. Single-Tone 32k FFT with fIN = 190 MHz, fSAMPLE = 50 MSPS
0
0
AIN = –0.5dBFS
SNR = 71.96dB
AIN = –0.5dBFS
SNR = 65.62dB
ENOB = 10.61 BITS
SFDR = 68.11dBc
ENOB = 11.66 BITS
–20
–40
–20
SFDR = 76.68dBc
–40
–60
–60
–80
–80
–100
–120
–100
–120
0
5
10
15
20
25
0
5
10
15
20
25
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 17. Single-Tone 32k FFT with fIN = 120 MHz, fSAMPLE = 50 MSPS
Figure 20. Single-Tone 32k FFT with fIN = 250 MHz, fSAMPLE = 50 MSPS
Rev. E | Page 15 of 52
AD9259
Data Sheet
100
90
80
70
60
90
85
80
75
70
65
fIN = 35MHz
fSAMPLE = 50MSPS
2V p-p, SFDR
2V p-p, SFDR
50
40
2V p-p, SNR
2V p-p, SNR
30
20
10
0
80dB
REFERENCE
60
10
–60
–50
–40
–30
–20
–10
0
15
20
25
30
35
40
45
50
ANALOG INPUT LEVEL (dBFS)
ENCODE (MSPS)
Figure 24. SNR/SFDR vs. Analog Input Level, fIN = 35 MHz, fSAMPLE = 50 MSPS
Figure 21. SNR/SFDR vs. Encode, fIN = 10.3 MHz, fSAMPLE = 50 MSPS
0
90
AIN1 AND AIN2 = –7dBFS
SFDR = 87.76dBc
IMD2 = 90.18dBc
–20
85
IMD3 = 87.27dBc
–40
2V p-p, SFDR
80
–60
–80
75
2V p-p, SNR
70
65
60
–100
–120
0
5
10
15
20
25
10
15
20
25
30
35
40
45
50
FREQUENCY (MHz)
ENCODE (MSPS)
Figure 25. Two-Tone 32k FFT with fIN1 = 15 MHz and fIN2 = 16 MHz,
SAMPLE = 50 MSPS
Figure 22. SNR/SFDR vs. Encode, fIN = 35 MHz, fSAMPLE = 50 MSPS
f
100
0
–20
AIN1 AND AIN2 = –7dBFS
SFDR = 80.37dBc
IMD2 = 79.75dBc
fIN = 10.3MHz
90
fSAMPLE = 50MSPS
80
IMD3 = 84.50dBc
70
60
2V p-p, SFDR
–40
–60
50
40
2V p-p, SNR
–80
30
20
10
0
80dB
REFERENCE
–100
–120
–60
–50
–40
–30
–20
–10
0
0
5
10
15
20
25
ANALOG INPUT LEVEL (dBFS)
FREQUENCY (MHz)
Figure 23. SNR/SFDR vs. Analog Input Level, fIN = 10.3 MHz, fSAMPLE = 50 MSPS
Figure 26. Two-Tone 32k FFT with fIN1 = 70 MHz and fIN2 = 71 MHz,
SAMPLE = 50 MSPS
f
Rev. E | Page 16 of 52
Data Sheet
AD9259
90
85
80
75
70
65
60
55
0.5
0.4
2V p-p, SFDR (dBc)
0.3
0.2
0.1
2V p-p, SNR (dB)
0
–0.1
–0.2
–0.3
–0.4
–0.5
50
1
10
100
1000
0
2000 4000 6000 8000 10000 12000 14000 16000
ANALOG INPUT FREQUENCY (MHz)
CODE
Figure 27. SNR/SFDR vs. Analog Input Frequency, fSAMPLE = 50 MSPS
Figure 30. DNL, fIN = 2.4 MHz, fSAMPLE = 50 MSPS
90
–45.0
–45.5
–46.0
–46.5
–47.0
–47.5
–48.0
85
2V p-p, SFDR
80
75
70
65
60
2V p-p, SINAD
–40
–20
0
20
40
60
80
10
15
20
25
30
35
40
45
50
TEMPERATURE (°C)
FREQUENCY (MHz)
Figure 28. SINAD/SFDR vs. Temperature, fIN = 10.3 MHz, fSAMPLE = 50 MSPS
Figure 31. CMRR vs. Frequency, fSAMPLE = 50 MSPS
1.2
2.0
1.5
1.006 LSB rms
1.0
0.8
0.6
0.4
0.2
0
1.0
0.5
0
–0.5
–1.0
–1.5
–2.0
N – 3
N – 2
N – 1
N
N + 1
N + 2
N + 3
0
2000 4000 6000 8000 10000 12000 14000 16000
CODE
CODE
Figure 29. INL, fIN = 2.4 MHz, fSAMPLE = 50 MSPS
Figure 32. Input-Referred Noise Histogram, fSAMPLE = 50 MSPS
Rev. E | Page 17 of 52
AD9259
Data Sheet
0
0
–1
–2
–3
–4
–5
–6
–7
NPR = 63.89dB
NOTCH = 18.0MHz
NOTCH WIDTH = 3.0MHz
–20
–3dB CUTOFF = 315MHz
–40
–60
–80
–8
–100
–9
–120
0
–10
5
10
15
20
25
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 33. Noise Power Ratio (NPR), fSAMPLE = 50 MSPS
Figure 34. Full-Power Bandwidth vs. Frequency, fSAMPLE = 50 MSPS
Rev. E | Page 1± of 52
Data Sheet
AD9259
THEORY OF OPERATION
low-Q inductors or ferrite beads is required when driving the
The AD9259 architecture consists of a pipelined ADC divided into
three sections: a 4-bit first stage followed by eight 1.5-bit stages and
a final 3-bit flash. Each stage provides sufficient overlap to correct
for flash errors in the preceding stage. The quantized outputs from
each stage are combined into a final 14-bit result in the digital
correction logic. The pipelined architecture permits the first stage
to operate with a new input sample while the remaining stages
operate with preceding samples. Sampling occurs on the rising
edge of the clock.
converter front end at high IF frequencies. Either a shunt
capacitor or two single-ended capacitors can be placed on the
inputs to provide a matching passive network. This ultimately
creates a low-pass filter at the input to limit unwanted
broadband noise. See the AN-742 Application Note, the AN-827
Application Note, and the Analog Dialogue article “Transformer-
Coupled Front-End for Wideband A/D Converters” (Volume
39, April 2005) for more information at www.analog.com. In
general, the precise values depend on the application.
Each stage of the pipeline, excluding the last, consists of a low
resolution flash ADC connected to a switched-capacitor DAC
and an interstage residue amplifier (for example, a multiplying
digital-to-analog converter (MDAC)). The residue amplifier
magnifies the difference between the reconstructed DAC output
and the flash input for the next stage in the pipeline. One bit of
redundancy is used in each stage to facilitate digital correction of
flash errors. The last stage simply consists of a flash ADC.
The analog inputs of the AD9259 are not internally dc-biased.
Therefore, in ac-coupled applications, the user must provide
this bias externally. Setting the device so that VCM = AVDD/2 is
recommended for optimum performance, but the device can
function over a wider range with reasonable performance, as
shown in Figure 36 and Figure 37.
90
fIN = 2.3MHz
fSAMPLE = 50MSPS
SFDR (dBc)
85
80
75
70
65
60
55
50
The output staging block aligns the data, corrects errors, and
passes the data to the output buffers. The data is then serialized
and aligned to the frame and data clocks.
ANALOG INPUT CONSIDERATIONS
SNR (dB)
The analog input to the AD9259 is a differential switched-
capacitor circuit designed for processing differential input
signals. This circuit can support a wide common-mode range
while maintaining excellent performance. By using an input
common-mode voltage of midsupply, users can minimize
signal-dependent errors and achieve optimum performance.
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
ANALOG INPUT COMMON-MODE VOLTAGE (V)
Figure 36. SNR/SFDR vs. Common-Mode Voltage,
fIN = 2.3 MHz, fSAMPLE = 50 MSPS
H
C
90
85
80
75
70
65
60
55
50
PAR
H
VIN + x
fIN = 30MHz
fSAMPLE = 50MSPS
C
SAMPLE
SFDR (dBc)
S
S
S
S
C
SAMPLE
VIN – x
H
C
PAR
SNR (dB)
H
Figure 35. Switched-Capacitor Input Circuit
The clock signal alternately switches the input circuit between
sample mode and hold mode (see Figure 35). When the input
circuit is switched to sample mode, the signal source must be
capable of charging the sample capacitors and settling within
one-half of a clock cycle. A small resistor in series with each
input can help reduce the peak transient current injected from
the output stage of the driving source. In addition, low-Q inductors
or ferrite beads can be placed on each leg of the input to reduce
high differential capacitance at the analog inputs and therefore
achieve the maximum bandwidth of the ADC. Such use of
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
ANALOG INPUT COMMON-MODE VOLTAGE (V)
Figure 37. SNR/SFDR vs. Common-Mode Voltage,
fIN = 30 MHz, fSAMPLE = 50 MSPS
Rev. E | Page 19 of 52
AD9259
Data Sheet
ADT1-1WT
1:1 Z RATIO
For best dynamic performance, the source impedances driving
VIN + x and VIN − x should be matched such that common-
mode settling errors are symmetrical. These errors are reduced
by the common-mode rejection of the ADC. An internal
reference buffer creates the positive and negative reference
voltages, REFT and REFB, respectively, that define the span of
the ADC core. The output common-mode of the reference buffer
is set to midsupply, and the REFT and REFB voltages and span
are defined as
C
R
VIN + x
ADC
AD9259
1
2Vp-p
49.9Ω
C
R
DIFF
AVDD
1kΩ
VIN – x
AGND
C
1kΩ
0.1μF
1
C
IS OPTIONAL.
DIFF
Figure 38. Differential Transformer-Coupled Configuration
for Baseband Applications
REFT = 1/2 (AVDD + VREF)
REFB = 1/2 (AVDD − VREF)
Span = 2 × (REFT − REFB) = 2 × VREF
ADT1-1WT
1:1 Z RATIO
2Vp-p
16nH
16nH 0.1μF
33Ω
VIN + x
65Ω
ADC
It can be seen from these equations that the REFT and REFB
voltages are symmetrical about the midsupply voltage and, by
definition, the input span is twice the value of the VREF voltage.
499Ω
16nH
2.2pF
1kΩ
AD9259
33Ω
VIN – x
AVDD
1kΩ
Maximum SNR performance is achieved by setting the ADC to
the largest span in a differential configuration. In the case of the
AD9259, the largest input span available is 2 V p-p.
0.1μF
1kΩ
Figure 39. Differential Transformer-Coupled Configuration
for IF Applications
Differential Input Configurations
Single-Ended Input Configuration
There are several ways to drive the AD9259 either actively or
passively; however, optimum performance is achieved by driving
the analog input differentially. For example, using the AD8332
differential driver to drive the AD9259 provides excellent perfor-
mance and a flexible interface to the ADC (see Figure 41) for
baseband applications. This configuration is commonly used
for medical ultrasound systems.
A single-ended input may provide adequate performance in cost-
sensitive applications. In this configuration, SFDR and distortion
performance degrade due to the large input common-mode swing.
If the application requires a single-ended input configuration,
ensure that the source impedances on each input are well matched
in order to achieve the best possible performance. A full-scale
input of 2 V p-p can be applied to the ADC’s VIN + x pin while
the VIN − x pin is terminated. Figure 40 details a typical single-
ended input configuration.
For applications where SNR is a key parameter, differential
transformer coupling is the recommended input configuration
(see Figure 38 and Figure 39), because the noise performance of
most amplifiers is not adequate to achieve the true performance
of the AD9259.
AVDD
C
R
VIN + x
0.1µF
AVDD
1kΩ
Regardless of the configuration, the value of the shunt capacitor,
C, is dependent on the input frequency and may need to be
reduced or removed.
2V p-p
49.9Ω
ADC
1
C
DIFF
AD9259
1kΩ
25Ω
R
C
VIN – x
0.1µF
1kΩ
1
C
IS OPTIONAL.
DIFF
Figure 40. Single-Ended Input Configuration
0.1μF
LOP
VIP
AVDD
10kΩ
33Ω
680nH
68pF
187Ω
187Ω
VOH
VOL
0.1μF 120nH
INH
VIN + x
1V p-p
AD8332
10kΩ
AVDD
1kΩ
22pF
+
ADC
AD9259
LNA
VGA
10kΩ
10kΩ
33Ω
LMD
VIN – x
0.1μF
680nH
LPF
LON
VIN
274Ω
18nF
0.1μF
Figure 41. Differential Input Configuration Using the AD8332 with Two-Pole, 16 MHz Low-Pass Filter
Rev. E | Page 20 of 52
Data Sheet
AD9259
CLK+ input circuit supply is AVDD (1.8 V), this input is
designed to withstand input voltages of up to 3.3 V and
therefore offers several selections for the drive logic voltage.
CLOCK INPUT CONSIDERATIONS
For optimum performance, the AD9259 sample clock inputs
(CLK+ and CLK−) should be clocked with a differential signal.
This signal is typically ac-coupled to the CLK+ and CLK− pins
via a transformer or capacitors. These pins are biased internally
and require no additional biasing.
AD9510/AD9511/
AD9512/AD9513/
AD9514/AD9515
0.1µF
CLK+
CLK
OPTIONAL
100Ω
0.1µF
1
50Ω
CLK+
CMOS DRIVER
CLK
Figure 42 shows a preferred method for clocking the AD9259. The
low jitter clock source is converted from a single-ended signal
to a differential signal using an RF transformer. The back-to-
back Schottky diodes across the secondary transformer limit
clock excursions into the AD9259 to approximately 0.8 V p-p
differential. This helps prevent the large voltage swings of the
clock from feeding through to other portions of the AD9259,
and it preserves the fast rise and fall times of the signal, which
are critical to low jitter performance.
ADC
AD9259
0.1µF
CLK–
0.1µF
39kΩ
1
50Ω RESISTOR IS OPTIONAL.
Figure 45. Single-Ended 1.8 V CMOS Sample Clock
AD9510/AD9511/
AD9512/AD9513/
AD9514/AD9515
0.1µF
CLK+
CLK
OPTIONAL
100Ω
0.1µF
1
50Ω
®
Mini-Circuits
CLK+
CMOS DRIVER
CLK
ADT1-1WT, 1:1Z
ADC
AD9259
0.1µF
0.1µF
XFMR
CLK+
CLK+
0.1µF
0.1µF
100Ω
ADC
AD9259
CLK–
50Ω
CLK–
0.1µF
1
50Ω RESISTOR IS OPTIONAL.
SCHOTTKY
DIODES:
HSM2812
0.1µF
Figure 46. Single-Ended 3.3 V CMOS Sample Clock
Figure 42. Transformer-Coupled Differential Clock
Clock Duty Cycle Considerations
Typical high speed ADCs use both clock edges to generate a
variety of internal timing signals. As a result, these ADCs may
be sensitive to the clock duty cycle. Commonly, a 5% tolerance is
required on the clock duty cycle to maintain dynamic performance
characteristics. The AD9259 contains a duty cycle stabilizer (DCS)
that retimes the nonsampling edge, providing an internal clock
signal with a nominal 50% duty cycle. This allows a wide range
of clock input duty cycles without affecting the performance of
the AD9259. When the DCS is on, noise and distortion perfor-
mance are nearly flat for a wide range of duty cycles. However,
some applications may require the DCS function to be off. If so,
keep in mind that the dynamic range performance can be
affected when operated in this mode. See the Memory Map
section for more details on using this feature.
Another option is to ac-couple a differential PECL signal to the
sample clock input pins as shown in Figure 43. The AD9510/
AD9511/AD9512/AD9513/AD9514/AD9515 of clock drivers
offers excellent jitter performance.
AD9510/AD9511/
AD9512/AD9513/
AD9514/AD9515
0.1µF
0.1µF
CLK+
CLK–
CLK
PECL DRIVER
CLK
CLK+
ADC
AD9259
100Ω
0.1µF
0.1µF
CLK–
1
1
240Ω
240Ω
50Ω
50Ω
1
50Ω RESISTORS ARE OPTIONAL.
Figure 43. Differential PECL Sample Clock
AD9510/AD9511/
AD9512/AD9513/
AD9514/AD9515
Jitter in the rising edge of the input is an important concern, and it
is not reduced by the internal stabilization circuit. The duty
cycle control loop does not function for clock rates of less than
20 MHz nominal. The loop has a time constant associated with
it that must be considered in applications where the clock rate
can change dynamically. This requires a wait time of 1.5 µs to
5 µs after a dynamic clock frequency increase (or decrease)
before the DCS loop is relocked to the input signal. During the
period that the loop is not locked, the DCS loop is bypassed and
the internal device timing is dependent on the duty cycle of the
input clock signal. In such applications, it may be appropriate to
disable the duty cycle stabilizer. In all other applications, enabling
the DCS circuit is recommended to maximize ac performance.
0.1µF
0.1µF
CLK+
CLK–
CLK+
CLK
ADC
AD9259
100Ω
LVDS DRIVER
CLK
0.1µF
0.1µF
CLK–
1
50Ω*
50Ω
1
50Ω RESISTORS ARE OPTIONAL
Figure 44. Differential LVDS Sample Clock
In some applications, it is acceptable to drive the sample clock
inputs with a single-ended CMOS signal. In such applications,
CLK+ should be driven directly from a CMOS gate, and the
CLK− pin should be bypassed to ground with a 0.1 μF capacitor
in parallel with a 39 kΩ resistor (see Figure 45). Although the
Rev. E | Page 21 of 52
AD9259
Data Sheet
Clock Jitter Considerations
Power Dissipation and Power-Down Mode
High speed, high resolution ADCs are sensitive to the quality of the
clock input. The degradation in SNR at a given input frequency (fA)
due only to aperture jitter (tJ) can be calculated by
As shown in Figure 48, the power dissipated by the AD9259 is
proportional to its sample rate. The digital power dissipation
does not vary significantly because it is determined primarily by
the DRVDD supply and bias current of the LVDS output drivers.
SNR Degradation = 20 × log 10(1/2 × π × fA × tJ)
200
180
160
140
120
100
80
500
450
400
350
300
250
In this equation, the rms aperture jitter represents the root mean
square of all jitter sources, including the clock input, analog input
signal, and ADC aperture jitter. IF undersampling applications
are particularly sensitive to jitter (see Figure 47).
AVDD CURRENT
The clock input should be treated as an analog signal in cases
where aperture jitter may affect the dynamic range of the AD9259.
Power supplies for clock drivers should be separated from the
ADC output driver supplies to avoid modulating the clock signal
with digital noise. Low jitter, crystal-controlled oscillators are
the best clock sources. If the clock is generated from another
type of source (by gating, dividing, or another method), it
should be retimed by the original clock during the last step.
TOTAL POWER
60
40
DRVDD CURRENT
20
0
10
15
20
25
30
35
40
45
50
ENCODE (MSPS)
Refer to the AN-501 Application Note and to the AN-756
Application Note for more in-depth information about jitter
performance as it relates to ADCs at www.analog.com.
Figure 48. Supply Current vs. fSAMPLE for fIN = 10.3 MHz, fSAMPLE = 50 MSPS
130
RMS CLOCK JITTER REQUIREMENT
120
110
16 BITS
100
90
80
70
60
50
40
30
14 BITS
12 BITS
10 BITS
0.125ps
0.25ps
0.5ps
1.0ps
2.0ps
1
10
100
1000
ANALOG INPUT FREQUENCY (MHz)
Figure 47. Ideal SNR vs. Input Frequency and Jitter
Rev. E | Page 22 of 52
Data Sheet
AD9259
By asserting the PDWN pin high, the AD9259 is placed into
power-down mode. In this state, the ADC typically dissipates
3 mW. During power-down, the LVDS output drivers are placed
into a high impedance state. If any of the SPI features are changed
before the power-down feature is enabled, the chip continues to
function after PDWN is pulled low without requiring a reset. The
AD9259 returns to normal operating mode when the PDWN pin
is pulled low. This pin is both 1.8 V and 3.3 V tolerant.
placed as close to the receiver as possible. If there is no far-end
receiver termination or there is poor differential trace routing,
timing errors may result. To avoid such timing errors, it is
recommended that the trace length be less than 24 inches and
that the differential output traces be close together and at equal
lengths. An example of the FCO and data stream with proper
trace length and position is shown in Figure 49.
In power-down mode, low power dissipation is achieved by
shutting down the reference, reference buffer, PLL, and biasing
networks. The decoupling capacitors on REFT and REFB are
discharged when entering power-down mode and must be
recharged when returning to normal operation. As a result, the
wake-up time is related to the time spent in the power-down
mode: shorter cycles result in proportionally shorter wake-up
times. With the recommended 0.1 μF and 2.2 μF decoupling
capacitors on REFT and REFB, approximately 1 sec is required
to fully discharge the reference buffer decoupling capacitors and
approximately 375 μs is required to restore full operation.
2.5ns/DIV
CH1 500mV/DIV = DCO
CH2 500mV/DIV = DATA
CH3 500mV/DIV = FCO
There are several other power-down options available when
using the SPI. The user can individually power down each
channel or put the entire device into standby mode. The latter
option allows the user to keep the internal PLL powered when
fast wake-up times (~600 ns) are required. See the Memory
Map section for more details on using these features.
Figure 49. LVDS Output Timing Example in ANSI-644 Mode (Default)
An example of the LVDS output using the ANSI-644 standard
(default) data eye and a time interval error (TIE) jitter histogram
with trace lengths less than 24 inches on standard FR-4 material is
shown in Figure 50. Figure 51 shows an example of trace lengths
exceeding 24 inches on standard FR-4 material. Notice that the
TIE jitter histogram reflects the decrease of the data eye opening
as the edge deviates from the ideal position. It is the user’s respon-
sibility to determine if the waveforms meet the timing budget of
the design when the trace lengths exceed 24 inches. Additional SPI
options allow the user to further increase the internal termination
(increasing the current) of all four outputs to drive longer trace
lengths (see Figure 52). Even though this produces sharper rise
and fall times on the data edges and is less prone to bit errors, the
power dissipation of the DRVDD supply increases when this
option is used. In addition, notice in Figure 52 that the histogram
is improved compared with that shown in Figure 51. See the
Memory Map section for more details.
Digital Outputs and Timing
The AD9259 differential outputs conform to the ANSI-644 LVDS
standard on default power-up. This can be changed to a low power,
reduced signal option (similar to the IEEE 1596.3 standard) via the
SDIO/ODM pin or SPI. The LVDS standard can further reduce the
overall power dissipation of the device by approximately 17 mW.
See the SDIO/ODM Pin section or Table 16 in the Memory Map
section for more information. The LVDS driver current is derived
on-chip and sets the output current at each output equal to a
nominal 3.5 mA. A 100 Ω differential termination resistor
placed at the LVDS receiver inputs results in a nominal
350 mV swing at the receiver.
The AD9259 LVDS outputs facilitate interfacing with LVDS
receivers in custom ASICs and FPGAs for superior switching
performance in noisy environments. Single point-to-point net
topologies are recommended with a 100 Ω termination resistor
Rev. E | Page 23 of 52
AD9259
Data Sheet
EYE: ALL BITS
EYE: ALL BITS
ULS: 9599/15599
ULS: 10000/15600
400
200
500
0
0
–200
–400
–500
–1.0ns
–0.5ns
0ns
0.5ns
1.0ns
–1.0ns
–0.5ns
0ns
0.5ns
1.0ns
100
100
50
0
50
0
–150ps –100ps
–50ps
0ps
50ps
100ps
150ps
–100ps
0ps
100ps
Figure 52. Data Eye for LVDS Outputs in ANSI-644 Mode with 100 Ω Internal
Termination on and Trace Lengths Greater than 24 Inches on Standard FR-4,
External 100 Ω Far Termination Only
Figure 50. Data Eye for LVDS Outputs in ANSI-644 Mode with Trace Lengths
Less than 24 Inches on Standard FR-4, External 100 Ω Far Termination Only
EYE: ALL BITS
ULS: 9600/15600
200
The format of the output data is offset binary by default. An
example of the output coding format can be found in Table 8.
To change the output data format to twos complement, see the
Memory Map section.
0
Table 8. Digital Output Coding
(VIN + x) − (VIN − x),
Digital Output Offset Binary
(D13 ... D0)
Code
Input Span = 2 V p-p (V)
163±3 +1.00
11 1111 1111 1111
10 0000 0000 0000
01 1111 1111 1111
00 0000 0000 0000
–200
100
±192
±191
0
0.00
−0.000122
−1.00
–1.0ns
–0.5ns
0ns
0.5ns
1.0ns
Data from each ADC is serialized and provided on a separate
channel. The data rate for each serial stream is equal to 14 bits
times the sample clock rate, with a maximum of 700 Mbps
(14 bits × 50 MSPS = 700 Mbps). The lowest typical conversion
rate is 10 MSPS. However, if lower sample rates are required for
a specific application, the PLL can be set up via the SPI to allow
encode rates as low as 5 MSPS. See the Memory Map section for
details on enabling this feature.
50
0
–150ps –100ps
–50ps
0ps
50ps
100ps
150ps
Figure 51. Data Eye for LVDS Outputs in ANSI-644 Mode with Trace Lengths
Greater than 24 Inches on Standard FR-4, External 100 Ω Far Termination Only
Rev. E | Page 24 of 52
Data Sheet
AD9259
(DDR) capturing. The FCO is used to signal the start of a new
output byte and is equal to the sample clock rate. See the timing
diagram shown in Figure 2 for more information.
Two output clocks are provided to assist in capturing data from
the AD9259. The DCO is used to clock the output data and is
equal to seven times the sample clock (CLK) rate. Data is
clocked out of the AD9259 and must be captured on the rising
and falling edges of the DCO that supports double data rate
Table 9. Flexible Output Test Modes
Output Test Mode
Bit Sequence
Subject to Data
Format Select
Pattern Name
Off (default)
Midscale short
Digital Output Word 1
Digital Output Word 2
0000
0001
N/A
N/A
Same
N/A
Yes
1000 0000 (±-bit)
10 0000 0000 (10-bit)
1000 0000 0000 (12-bit)
10 0000 0000 0000 (14-bit)
0010
0011
0100
+Full-scale short
−Full-scale short
Checkerboard
1111 1111 (±-bit)
Same
Same
Yes
Yes
No
11 1111 1111 (10-bit)
1111 1111 1111 (12-bit)
11 1111 1111 1111 (14-bit)
0000 0000 (±-bit)
00 0000 0000 (10-bit)
0000 0000 0000 (12-bit)
00 0000 0000 0000 (14-bit)
1010 1010 (±-bit)
0101 0101 (±-bit)
10 1010 1010 (10-bit)
1010 1010 1010 (12-bit)
10 1010 1010 1010 (14-bit)
01 0101 0101 (10-bit)
0101 0101 0101 (12-bit)
01 0101 0101 0101 (14-bit)
0101
0110
0111
PN sequence long1
PN sequence short1
One-/zero-word toggle
N/A
N/A
N/A
N/A
Yes
Yes
No
1111 1111 (±-bit)
0000 0000 (±-bit)
11 1111 1111 (10-bit)
1111 1111 1111 (12-bit)
11 1111 1111 1111 (14-bit)
00 0000 0000 (10-bit)
0000 0000 0000 (12-bit)
00 0000 0000 0000 (14-bit)
1000
1001
User input
1-/0-bit toggle
Register 0x19 to Register 0x1A
1010 1010 (±-bit)
10 1010 1010 (10-bit)
1010 1010 1010 (12-bit)
10 1010 1010 1010 (14-bit)
Register 0x1B to Register 0x1C
N/A
No
No
1010
1011
1100
1× sync
0000 1111 (±-bit)
N/A
N/A
N/A
No
No
No
00 0001 1111 (10-bit)
0000 0011 1111 (12-bit)
00 0000 0111 1111 (14-bit)
One bit high
Mixed frequency
1000 0000 (±-bit)
10 0000 0000 (10-bit)
1000 0000 0000 (12-bit)
10 0000 0000 0000 (14-bit)
1010 0011 (±-bit)
10 0110 0011 (10-bit)
1010 0011 0011 (12-bit)
10 1000 0110 0111 (14-bit)
1 All test mode options except PN sequence short and PN sequence long can support ±- to 14-bit word lengths in order to verify data capture to the receiver.
Rev. E | Page 25 of 52
AD9259
Data Sheet
When the SPI is used, the DCO phase can be adjusted in 60°
increments relative to the data edge. This enables the user to
refine system timing margins if required. The default DCO+
and DCO− timing, as shown in Figure 2, is 90° relative to the
output data edge.
Table 10. PN Sequence
Initial
First Three Output Samples
(MSB First)
Sequence
Value
PN Sequence Short
PN Sequence Long
0x0df
0x26e02±
0x37e4, 0x3533, 0x0063
0x191f, 0x35c2, 0x2359
An 8-, 10-, or 12-bit serial stream can also be initiated from the
SPI. This allows the user to implement and test compatibility with
lower resolution systems. When changing the resolution to an
8-, 10-, or 12-bit serial stream, the data stream is shortened. See
Figure 3 for a 12-bit example.
Consult the Memory Map section for information on how
to change these additional digital output timing features
through the SPI.
SDIO/ODM Pin
The SDIO/ODM pin is for use in applications that do not require
SPI mode operation. This pin can enable a low power, reduced
signal option (similar to the IEEE 1596.3 reduced range link
output standard) if it and the CSB pin are tied to AVDD during
device power-up. This option should only be used when the
digital output trace lengths are less than 2 inches from the LVDS
receiver. When this option is used, the FCO, DCO, and outputs
function normally, but the LVDS signal swing of all channels is
reduced from 350 mV p-p to 200 mV p-p, allowing the user to
further reduce the power on the DRVDD supply.
When the SPI is used, all of the data outputs can also be
inverted from their nominal state. This is not to be confused
with inverting the serial stream to an LSB-first mode. In default
mode, as shown in Figure 2, the MSB is first in the data output
serial stream. However, this can be inverted so that the LSB is
first in the data output serial stream (see Figure 4).
There are 12 digital output test pattern options available that
can be initiated through the SPI. This is a useful feature when
validating receiver capture and timing. Refer to Table 9 for the
output bit sequencing options available. Some test patterns have
two serial sequential words and can be alternated in various
ways, depending on the test pattern chosen. Note that some
patterns do not adhere to the data format select option. In
addition, custom user-defined test patterns can be assigned in
the 0x19, 0x1A, 0x1B, and 0x1C register addresses. All test mode
options except PN sequence short and PN sequence long can
support 8- to 14-bit word lengths to verify data capture to the
receiver.
For applications where this pin is not used, it should be tied low.
In this case, the device pin can be left open, and the 30 kΩ internal
pull-down resistor pulls this pin low. This pin is only 1.8 V tolerant.
If applications require this pin to be driven from a 3.3 V logic level,
insert a 1 kΩ resistor in series with this pin to limit the current.
Table 11. Output Driver Mode Pin Settings
Resulting
Resulting
Selected ODM ODM Voltage
Output Standard FCO and DCO
Normal
Operation
10 kΩ to AGND ANSI-644
ANSI-644
(default)
Low power,
reduced
signal option
The PN sequence short pattern produces a pseudorandom bit
sequence that repeats itself every 29 − 1 or 511 bits. A description
of the PN sequence and how it is generated can be found in
Section 5.1 of the ITU-T 0.150 (05/96) standard. The only
difference is that the starting value must be a specific value
instead of all 1s (see Table 10 for the initial values).
(default)
ODM
AVDD
Low power,
reduced
signal option
The PN sequence long pattern produces a pseudorandom bit
sequence that repeats itself every 223 − 1 or 8,388,607 bits. A
description of the PN sequence and how it is generated can be
found in Section 5.6 of the ITU-T 0.150 (05/96) standard. The
only differences are that the starting value must be a specific
value instead of all 1s (see Table 10 for the initial values) and the
AD9259 inverts the bit stream with relation to the ITU standard.
Rev. E | Page 26 of 52
Data Sheet
AD9259
SCLK/DTP Pin
RBIAS Pin
The SCLK/DTP pin is for use in applications that do not require
SPI mode operation. This pin can enable a single digital test
pattern if it and the CSB pin are held high during device power-
up. When SCLK/DTP is tied to AVDD, the ADC channel
outputs shift out the following pattern: 10 0000 0000 0000. The
FCO and DCO function normally while all channels shift out the
repeatable test pattern. This pattern allows the user to perform
timing alignment adjustments among the FCO, DCO, and output
data. For normal operation, this pin should be tied to AGND
through a 10 kΩ resistor. This pin is both 1.8 V and 3.3 V tolerant.
To set the internal core bias current of the ADC, place a resistor
(nominally equal to 10.0 kΩ) to ground at the RBIAS pin. The
resistor current is derived on-chip and sets the AVDD current of
the ADC to a nominal 185 mA at 50 MSPS. Therefore, it is
imperative that at least a 1% tolerance on this resistor be used to
achieve consistent performance.
Voltage Reference
A stable, accurate 0.5 V voltage reference is built into the
AD9259. This is gained up internally by a factor of 2, setting
V
REF to 1.0 V, which results in a full-scale differential input span
of 2 V p-p. The VREF is set internally by default; however, the
VREF pin can be driven externally with a 1.0 V reference to
improve accuracy.
Table 12. Digital Test Pattern Pin Settings
Resulting
Resulting
Selected DTP DTP Voltage
D + x and D − x FCO and DCO
Normal
Operation
10 kΩ to AGND Normal Normal operation
operation
When applying the decoupling capacitors to the VREF, REFT,
and REFB pins, use ceramic low ESR capacitors. These capacitors
should be close to the ADC pins and on the same layer of the
PCB as the AD9259. The recommended capacitor values and
configurations for the AD9259 reference pin are shown in
Figure 53.
DTP
AVDD
10 0000 0000
0000
Normal operation
Additional and custom test patterns can also be observed when
commanded from the SPI port. Consult the Memory Map
section for information about the options available.
Table 13. Reference Settings
CSB Pin
Resulting
Differential
The CSB pin should be tied to AVDD for applications that do
not require SPI mode operation. By tying CSB high, all SCLK
and SDIO information is ignored. This pin is both 1.8 V and
3.3 V tolerant.
Selected Mode SENSE Voltage Resulting VREF (V) Span (V p-p)
External
AVDD
N/A
2 × external
reference
Reference
Internal,
AGND to 0.2 V
1.0
2.0
2 V p-p FSR
Rev. E | Page 27 of 52
AD9259
Data Sheet
External Reference Operation
Internal Reference Operation
The use of an external reference may be necessary to enhance
the gain accuracy of the ADC or to improve thermal drift
characteristics. Figure 56 shows the typical drift characteristics
of the internal reference in 1 V mode.
A comparator within the AD9259 detects the potential at the
SENSE pin and configures the reference. If SENSE is grounded,
the reference amplifier switch is connected to the internal
resistor divider (see Figure 53), setting VREF to 1 V.
When the SENSE pin is tied to AVDD, the internal reference is
disabled, allowing the use of an external reference. The external
reference is loaded with an equivalent 6 kΩ load. An internal
reference buffer generates the positive and negative full-scale
references, REFT and REFB, for the ADC core. Therefore, the
external reference must be limited to a nominal 1.0 V.
The REFT and REFB pins establish the input span of the ADC
core from the reference configuration. The analog input full-
scale range of the ADC equals twice the voltage of the reference
pin for either an internal or an external reference configuration.
If the reference of the AD9259 is used to drive multiple
converters to improve gain matching, the loading of the refer-
ence by the other converters must be considered. Figure 55
depicts how the internal reference voltage is affected by loading.
5
0
–5
VIN + x
VIN – x
REFT
–10
–15
–20
–25
–30
0.1µF
+
ADC
CORE
0.1µF
2.2µF
REFB
0.1µF
VREF
0.1µF
1µF
0.5V
SELECT
LOGIC
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
SENSE
CURRENT LOAD (mA)
Figure 55. VREF Accuracy vs. Load
0.02
0
–0.02
–0.04
–0.06
–0.08
–0.10
–0.12
–0.14
–0.16
–0.18
Figure 53. Internal Reference Configuration
VIN + x
VIN – x
REFT
0.1µF
0.1µF
REFB
+
ADC
CORE
2.2µF
EXTERNAL
REFERENCE
0.1µF
VREF
1
1
1µF
0.1µF
0.5V
–40
–20
0
20
40
60
80
SELECT
LOGIC
AVDD
TEMPERATURE (°C)
Figure 56. Typical VREF Drift
SENSE
1
OPTIONAL.
Figure 54. External Reference Operation
Rev. E | Page 2± of 52
Data Sheet
AD9259
SERIAL PORT INTERFACE (SPI)
The AD9259 serial port interface allows the user to configure
the converter for specific functions or operations through a
structured register space provided in the ADC. This may
provide the user with additional flexibility and customization,
depending on the application. Addresses are accessed via the
serial port and can be written to or read from via the port. Memory
is organized into bytes that can be further divided into fields, as
documented in the Memory Map section. Detailed operational
information can be found in the AN-877 Application Note,
Interfacing to High Speed ADCs via SPI at www.analog.com.
In addition to the operation modes, the SPI port configuration
influences how the AD9259 operates. For applications that do
not require a control port, the CSB line can be tied and held high.
This places the remainder of the SPI pins into their secondary
modes, as defined in the SDIO/ODM Pin and SCLK/DTP Pin
sections. CSB can also be tied low to enable 2-wire mode. When
CSB is tied low, SCLK and SDIO are the only pins required for
communication. Although the device is synchronized during
power-up, the user should ensure that the serial port remains
synchronized with the CSB line when using this mode. When
operating in 2-wire mode, it is recommended to use a 1-, 2-,
or 3-byte transfer exclusively. Without an active CSB line,
streaming mode can be entered but not exited.
There are three pins that define the SPI: SCLK, SDIO, and CSB
(see Table 14). The SCLK pin is used to synchronize the read
and write data presented to the ADC. The SDIO pin is a dual-
purpose pin that allows data to be sent to and read from the
internal ADC memory map registers. The CSB pin is an active
low control that enables or disables the read and write cycles.
In addition to word length, the instruction phase determines if
the serial frame is a read or write operation, allowing the serial
port to be used to both program the chip and read the contents
of the on-chip memory. If the instruction is a readback operation,
performing a readback causes the SDIO pin to change from an
input to an output at the appropriate point in the serial frame.
Table 14. Serial Port Pins
Pin
Function
SCLK
Serial Clock. The serial shift clock input. SCLK is used to
synchronize serial interface reads and writes.
Serial Data Input/Output. A dual-purpose pin. The typical
role for this pin is as an input or output, depending on
the instruction sent and the relative position in the
timing frame.
Data can be sent in MSB- or LSB-first mode. MSB-first mode
is the default at power-up and can be changed by adjusting the
configuration register. For more information about this and
other features, see the AN-877 Application Note, Interfacing to
High Speed ADCs via SPI at www.analog.com.
SDIO
CSB
Chip Select Bar (Active Low). This control gates the read
and write cycles.
HARDWARE INTERFACE
The pins described in Table 14 compose the physical interface
between the user’s programming device and the serial port of
the AD9259. The SCLK and CSB pins function as inputs when
using the SPI. The SDIO pin is bidirectional, functioning as an
input during write phases and as an output during readback.
The falling edge of the CSB in conjunction with the rising edge of
the SCLK determines the start of the framing sequence. During an
instruction phase, a 16-bit instruction is transmitted, followed by
one or more data bytes, which is determined by Bit Field W0 and
Bit Field W1. An example of the serial timing and its definitions
can be found in Figure 58 and Table 15. During normal operation,
CSB is used to signal to the device that SPI commands are to be
received and processed. When CSB is brought low, the device
processes SCLK and SDIO to obtain instructions. Normally,
CSB remains low until the communication cycle is complete.
However, if connected to a slow device, CSB can be brought
high between bytes, allowing older microcontrollers enough
time to transfer data into shift registers. CSB can be stalled
when transferring one, two, or three bytes of data. When W0
and W1 are set to 11, the device enters streaming mode and
continues to process data, either reading or writing, until
CSB is taken high to end the communication cycle. This allows
complete memory transfers without requiring additional instruc-
tions. Regardless of the mode, if CSB is taken high in the middle
of a byte transfer, the SPI state machine is reset and the device
waits for a new instruction.
If multiple SDIO pins share a common connection, care should
be taken to ensure that proper VOH levels are met. Assuming the
same load for each AD9259, Figure 57 shows the number of
SDIO pins that can be connected together and the resulting VOH
level. This interface is flexible enough to be controlled by either
serial PROMS or PIC microcontrollers, providing the user with
an alternative method, other than a full SPI controller, to
program the ADC (see the AN-812 Application Note).
Rev. E | Page 29 of 52
AD9259
Data Sheet
1.800
1.795
1.790
1.785
1.780
1.775
1.770
1.765
1.760
1.755
1.750
1.745
1.740
1.735
1.730
1.725
1.720
If the user chooses not to use the SPI, these dual-function pins
serve their secondary functions when the CSB is strapped to
AVDD during device power-up. See the Theory of Operation
section for details on which pin-strappable functions are
supported on the SPI pins.
For users who wish to operate the ADC without using the
SPI, remove any connections from the CSB, SCLK/DTP, and
SDIO/ODM pins. By disconnecting these pins from the control
bus, the ADC can function in its most basic operation. Each
of these pins has an internal termination that floats to its
respective level.
1.715
0
10
20
30
40
50
60
70
80
90
100
NUMBER OF SDIO PINS CONNECTED TOGETHER
Figure 57. SDIO Pin Loading
tDS
tHI
tCLK
tH
tS
tDH
tLO
CSB
SCLK DON’T CARE
SDIO DON’T CARE
DON’T CARE
R/W
W1
W0
A12
A11
A10
A9
A8
A7
D5
D4
D3
D2
D1
D0
DON’T CARE
Figure 58. Serial Timing Details
Table 15. Serial Timing Definitions
Parameter
Timing (Minimum, ns)
Description
tDS
5
2
40
5
Setup time between the data and the rising edge of SCLK
Hold time between the data and the rising edge of SCLK
Period of the clock
tDH
tCLK
tS
Setup time between CSB and SCLK
tH
2
Hold time between CSB and SCLK
tHI
tLO
tEN_SDIO
16
16
10
Minimum period that SCLK should be in a logic high state
Minimum period that SCLK should be in a logic low state
Minimum time for the SDIO pin to switch from an input to an output relative to the SCLK
falling edge (not shown in Figure 58)
tDIS_SDIO
10
Minimum time for the SDIO pin to switch from an output to an input relative to the SCLK
rising edge (not shown in Figure 58)
Rev. E | Page 30 of 52
Data Sheet
AD9259
MEMORY MAP
READING THE MEMORY MAP TABLE
RESERVED LOCATIONS
Each row in the memory map register table (Table 16) has eight
address locations. The memory map is divided into three sections:
the chip configuration register map (Address 0x00 to Address 0x02),
the device index and transfer register map (Address 0x05 and
Address 0xFF), and the ADC functions register map (Address 0x08
to Address 0x22).
Undefined memory locations should not be written to except
when writing the default values suggested in this data sheet.
Addresses that have values marked as 0 should be considered
reserved and have a 0 written into their registers during power-up.
DEFAULT VALUES
When the AD9259 comes out of a reset, critical registers are
preloaded with default values. These values are indicated in
Table 16, where an X refers to an undefined feature.
The leftmost column of the memory map indicates the register
address number, and the default value is shown in the second
rightmost column. The (MSB) Bit 7 column is the start of the
default hexadecimal value given. For example, Address 0x09, the
clock register, has a default value of 0x01, meaning that Bit 7 = 0,
Bit 6 = 0, Bit 5 = 0, Bit 4 = 0, Bit 3 = 0, Bit 2 = 0, Bit 1 = 0, and
Bit 0 = 1, or 0000 0001 in binary. This setting is the default for
the duty cycle stabilizer in the on condition. By writing a 0 to Bit 6
of this address followed by a 0x01 in Register 0xFF (transfer bit),
the duty cycle stabilizer turns off. It is important to follow each
writing sequence with a transfer bit to update the SPI registers. For
more information on this and other functions, consult the AN-877
Application Note, Interfacing to High Speed ADCs via SPI at
www.analog.com.
LOGIC LEVELS
An explanation of various registers follows: “Bit is set” is
synonymous with “bit is set to Logic 1” or “writing Logic 1 for
the bit.” Similarly, “clear a bit” is synonymous with “bit is set to
Logic 0” or “writing Logic 0 for the bit.”
Rev. E | Page 31 of 52
AD9259
Data Sheet
Table 16. Memory Map Register
Default
Value
(Hex)
Addr.
(MSB)
Bit 7
(LSB)
Bit 0
Default Notes/
Comments
(Hex) Register Name
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
Chip Configuration Registers
00
chip_port_config
0
LSB first
1 = on
0 = off
Soft
reset
1 = on
0 = off
(default)
1
1
Soft
reset
1 = on
0 = off
(default)
LSB first
1 = on
0 = off
0
0x1±
The nibbles
should be
mirrored so that
LSB- or MSB-first
mode is set cor-
rectly regardless
of shift mode.
(default)
(default)
01
02
chip_id
±-bit Chip ID Bits [7:0]
(AD9259 = 0x04), (default)
0x04
Default is unique
chip ID. This is a
read-only
register.
chip_grade
X
Child ID [6:4]
X
X
X
X
Child ID used to
differentiate
graded devices.
This is a read-
only register.
(identify device variants of Chip ID)
100 = 50 MSPS
Device Index and Transfer Registers
Clock
channel
DCO
1 = on
0 = off
Clock
channel
FCO
1 = on
0 = off
Data
Data
Data
Data
Channel
A
0x0F
0x00
Bits are set to
05
device_index_A
X
X
X
Channel Channel Channel
determine which
on-chip device
receives the next
write command.
D
1 = on
C
B
1 = on
1 = on
1 = on
(default) (default) (default) (default)
(default) (default) 0 = off
0 = off
0 = off
0 = off
FF
device_update
X
X
X
X
X
X
SW
Synchronously
transfers data
from the master
shift register to
the slave.
transfer
1 = on
0 = off
(default)
ADC Functions
0±
modes
X
X
X
X
X
X
X
X
X
X
Internal power-down mode
000 = chip run (default)
001 = full power-down
010 = standby
0x00
0x01
Determines
various generic
modes of chip
operation.
011 = reset
09
clock
X
X
Duty
Turns the
cycle
internal duty
cycle stabilizer
on and off.
stabilizer
1 = on
(default)
0 = off
Output test mode—see Table 9 in the
long gen PN short Digital Outputs and Timing section
0x00
When this reg-
ister is set, the
test data is placed
on the output
pins in place of
normal data.
0D
test_io
User test mode
00 = off (default)
Reset PN Reset
01 = on, single alternate 1 = on
gen
1 = on
0000 = off (default)
0001 = midscale short
0010 = +FS short
10 = on, single once
11 = on, alternate once
0 = off
(default) 0 = off
(default) 0011 = −FS short
0100 = checkerboard output
0101 = PN 23 sequence
0110 = PN 9 sequence
0111 = 1-/0-word toggle
1000 = user input
1001 = 1-/0-bit toggle
1010 = 1× sync
1011 = one bit high
1100 = mixed bit frequency
(format determined by output_mode)
Rev. E | Page 32 of 52
Data Sheet
AD9259
Default
Value
(Hex)
Addr.
(MSB)
Bit 7
(LSB)
Bit 0
Default Notes/
Comments
(Hex) Register Name
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
14
output_mode
X
0 = LVDS
ANSI-644
(default)
1 = LVDS
low power
(IEEE
X
X
X
Output
invert
1 = on
0 = off
(default)
00 = offset binary
(default)
01 = twos
0x00
Configures the
outputs and the
format of the
data.
complement
1596.3
similar)
15
output_adjust
X
X
Output driver
termination
00 = none (default)
01 = 200 Ω
10 = 100 Ω
11 = 100 Ω
X
X
X
X
0x00
Determines
LVDS or other
output properties.
Primarily func-
tions to set the
LVDS span and
common-mode
levels in place of
an external
resistor.
On devices that
utilize global
clock divide,
determines
which phase of
the divider
output is used to
supply the
output clock.
Internal latching
is unaffected.
16
output_phase
X
X
X
X
0011 = output clock phase adjust
(0000 through 1010)
0000 = 0° relative to data edge
0001 = 60° relative to data edge
0010 = 120° relative to data edge
0011 = 1±0° relative to data edge (default)
0101 = 300° relative to data edge
0110 = 360° relative to data edge
1000 = 4±0° relative to data edge
1001 = 540° relative to data edge
1010 = 600° relative to data edge
1011 to 1111 = 660° relative to data edge
0x03
19
1A
1B
1C
21
user_patt1_lsb
user_patt1_msb
user_patt2_lsb
user_patt2_msb
serial_control
B7
B6
B5
B4
B3
B2
B1
B9
B1
B9
B0
B±
B0
B±
0x00
0x00
0x00
0x00
0x00
User-defined
pattern, 1 LSB.
B15
B7
B14
B6
B13
B5
B12
B4
B11
B3
B10
B2
User-defined
pattern, 1 MSB.
User-defined
pattern, 2 LSB.
B15
B14
X
B13
X
B12
X
B11
B10
User-defined
pattern, 2 MSB.
LSB first
1 = on
0 = off
<10
MSPS,
low
encode
rate
000 = 14 bits (default, normal bit
stream)
001 = ± bits
010 = 10 bits
011 = 12 bits
Serial stream
control. Default
causes MSB first
and the native
bit stream
(default)
mode
1 = on
0 = off
(default)
100 = 14 bits
(global).
Used to power
down individual
sections of a
22
serial_ch_stat
X
X
X
X
X
X
Channel
output
reset
1 = on
0 = off
Channel
power-
down
1 = on
0 = off
0x00
converter (local).
(default) (default)
Rev. E | Page 33 of 52
AD9259
Data Sheet
Power and Ground Recommendations
Exposed Paddle Thermal Heat Slug Recommendations
When connecting power to the AD9259, it is recommended
that two separate 1.8 V supplies be used: one for analog (AVDD)
and one for digital (DRVDD). If only one supply is available, it
should be routed to the AVDD first and then tapped off and
isolated with a ferrite bead or a filter choke preceded by
decoupling capacitors for the DRVDD. The user can employ
several different decoupling capacitors to cover both high and
low frequencies. These should be located close to the point of
entry at the PC board level and close to the parts, with minimal
trace lengths.
It is required that the exposed paddle on the underside of the
ADC be connected to analog ground (AGND) to achieve the
best electrical and thermal performance of the AD9259. An
exposed continuous copper plane on the PCB should mate to
the AD9259 exposed paddle, Pin 0. The copper plane should
have several vias to achieve the lowest possible resistive thermal
path for heat dissipation to flow through the bottom of the PCB.
These vias should be solder-filled or plugged.
To maximize the coverage and adhesion between the ADC and
PCB, partition the continuous copper plane by overlaying a
silkscreen on the PCB into several uniform sections. This provides
several tie points between the ADC and PCB during the reflow
process, whereas using one continuous plane with no partitions
only guarantees one tie point. See Figure 59 for a PCB layout
example. For detailed information on packaging and the PCB
layout of chip scale packages, see the AN-772 Application Note,
A Design and Manufacturing Guide for the Lead Frame Chip
Scale Package (LFCSP) at www.analog.com.
A single PC board ground plane should be sufficient when
using the AD9259. With proper decoupling and smart parti-
tioning of the PC board’s analog, digital, and clock sections,
optimum performance can be easily achieved.
SILKSCREEN PARTITION
PIN 1 INDICATOR
Figure 59. Typical PCB Layout
Rev. E | Page 34 of 52
Data Sheet
AD9259
EVALUATION BOARD
board individually. Use P501 to connect a different supply for
each section. At least one 1.8 V supply is needed for AVDD_DUT
and DRVDD_DUT; however, it is recommended that separate
supplies be used for analog and digital signals and that each
supply have a current capability of 1 A. To operate the evaluation
board using the VGA option, a separate 5.0 V analog supply
(AVDD_5 V) is needed. To operate the evaluation board using
the SPI and alternate clock options, a separate 3.3 V analog
supply (AVDD_3.3 V) is needed in addition to the other
supplies.
The AD9259 evaluation board provides all of the support cir-
cuitry required to operate the ADC in its various modes and
configurations. The converter can be driven differentially using a
transformer (default) or a AD8332 driver. The ADC can also be
driven in a single-ended fashion. Separate power pins are provided
to isolate the DUT from the drive circuitry of the AD8332. Each
input configuration can be selected by changing the connection
of various jumpers (see Figure 62 to Figure 66). Figure 60 shows
the typical bench characterization setup used to evaluate the ac
performance of the AD9259. It is critical that the signal sources
used for the analog input and clock have very low phase noise
(<1 ps rms jitter) to realize the optimum performance of the
converter. Proper filtering of the analog input signal to remove
harmonics and lower the integrated or broadband noise at the
input is also necessary to achieve the specified noise performance.
INPUT SIGNALS
When connecting the clock and analog source to the evaluation
board, use clean signal generators with low phase noise, such as
Rohde & Schwarz SMA or HP8644 signal generators or the
equivalent, as well as a 1 m, shielded, RG-58, 50 Ω coaxial cable.
Enter the desired frequency and amplitude from the ADC speci-
fications tables. Typically, most Analog Devices, Inc., evaluation
boards can accept approximately 2.8 V p-p or 13 dBm sine wave
input for the clock. When connecting the analog input source, it
is recommended to use a multipole, narrow-band, band-pass
filter with 50 Ω terminations. Good choices of such band-pass
filters are available from TTE, Allen Avionics, and K&L
See Figure 62 to Figure 70 for the complete schematics and
layout diagrams demonstrating the routing and grounding
techniques that should be applied at the system level.
POWER SUPPLIES
This evaluation board has a wall-mountable switching power
supply that provides a 6 V, 2 A maximum output. Connect the
supply to the rated 100 V ac to 240 V ac wall outlet at 47 Hz to
63 Hz. The other end of the supply is a 2.1 mm inner diameter
jack that connects to the PCB at P503. Once on the PC board,
the 6 V supply is fused and conditioned before connecting to
three low dropout linear regulators that supply the proper bias
to each of the various sections on the board.
Microwave, Inc. The filter should be connected directly to the
evaluation board if possible.
OUTPUT SIGNALS
The default setup uses the Analog Devices HSC-ADC-FIFO5-
INTZ to interface with the Analog Devices standard dual-
channel FIFO data capture board (HCS-ADC-EVALCZ). Two
of the eight channels can be evaluated at the same time. For
more information on the channel settings and optional settings
of these boards, visit www.analog.com/FIFO.
When operating the evaluation board in a nondefault condition,
L504 to L507 can be removed to disconnect the switching
power supply. This enables the user to bias each section of the
WALL OUTLET
100V TO 240V AC
47Hz TO 63Hz
6V DC
2A MAX
5.0V
1.8V
1.8V
3.3V
3.3V
–
+
–
+
–
+
–
+
–
+
SWITCHING
POWER
SUPPLY
PC
RUNNING
ADC
ROHDE & SCHWARZ,
ANALYZER
AND SPI
USER
INTERPOSER
BOARD
HSC-ADC-EVALCZ
FIFO DATA
CAPTURE
SMA,
2V p-p SIGNAL
SYNTHESIZER
BAND-PASS
FILTER
XFMR
INPUT
AD9259
EVALUATION BOARD
SOFTWARE
BOARD
CH A TO CH D
14-BIT
ROHDE & SCHWARZ,
SMA,
USB
CONNECTION
SERIAL
CLK
LVDS
2V p-p SIGNAL
SYNTHESIZER
SPI
SPI
SPI
SPI
Figure 60. Evaluation Board Connection
Rev. E | Page 35 of 52
AD9259
Data Sheet
A differential LVPECL clock can also be used to clock the
ADC input using the AD9515 (U202). Populate R225 and
R227 with 0 Ω resistors and remove R217 and R218 to
disconnect the default clock path inputs. In addition, populate
C207 and C208 with a 0.1 μF capacitor and remove C210 and
C211 to disconnect the default clock path outputs. The
AD9515 has many pin-strappable options that are set to a
default mode of operation. Consult the AD9515 data sheet
for more information about these and other options.
DEFAULT OPERATION AND JUMPER SELECTION
SETTINGS
The following is a list of the default and optional settings or
modes allowed on the AD9259 Rev. A evaluation board.
POWER: Connect the switching power supply that is
provided in the evaluation kit between a rated 100 V ac to
240 V ac wall outlet at 47 Hz to 63 Hz and P503.
AIN: The evaluation board is set up for a transformer-
coupled analog input with an optimum 50 Ω impedance
match of 200 MHz of bandwidth (see Figure 61). For more
bandwidth response, the differential capacitor across the
analog inputs can be changed or removed. The common
mode of the analog inputs is developed from the center
tap of the transformer or AVDD_DUT/2.
In addition, an on-board oscillator is available on the OSC201
and can act as the primary clock source. The setup is quick
and involves installing R212 with a 0 Ω resistor and setting
the enable jumper (J205) to the on position. If the user wishes
to employ a different oscillator, two oscillator footprint options
are available (OSC201) to check the ADC performance.
0
PDWN: To enable the power-down feature, short J201 to
AVDD on the PDWN pin.
–2
–3dB CUTOFF = 200MHz
–4
–6
SCLK/DTP: To enable the digital test pattern on the digital
outputs of the ADC, use J204. If J204 is tied to AVDD during
device power-up, Test Pattern 10 0000 0000 0000 is enabled.
See the SCLK/DTP Pin section for details.
–8
–10
–12
–14
–16
SDIO/ODM: To enable the low power, reduced signal option
(similar to the IEEE 1595.3 reduced range link LVDS output
standard), use J203. If J203 is tied to AVDD during device
power-up, it enables the LVDS outputs in a low power,
reduced signal option from the default ANSI-644 standard.
This option changes the signal swing from 350 mV p-p to
200 mV p-p, reducing the power of the DRVDD supply. See
the SDIO/ODM Pin section for more details.
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY (MHz)
Figure 61. Evaluation Board Full-Power Bandwidth
VREF: VREF is set to 1.0 V by tying the SENSE pin to
ground, R237. This causes the ADC to operate in 2.0 V p-p
full-scale range. A separate external reference option using
the ADR510 is also included on the evaluation board.
Populate R231 and R235 and remove C214. Proper use of the
VREF options is noted in the Voltage Reference section.
CSB: To enable processing of the SPI information on the
SDIO and SCLK pins, tie J202 low in the always enable
mode. To ignore the SDIO and SCLK information, tie J202
to AVDD.
Non-SPI Mode: For users who wish to operate the DUT
without using SPI, remove Jumpers J202, J203, and J204.
This disconnects the CSB, SCLK/DTP, and SDIO/ODM
pins from the control bus, allowing the DUT to operate in its
simplest mode. Each of these pins has internal termination
and will float to its respective level.
RBIAS: RBIAS has a default setting of 10 kΩ (R201) to
ground and is used to set the ADC core bias current.
CLOCK: The default clock input circuitry is derived from a
simple transformer-coupled circuit using a high bandwidth
1:1 impedance ratio transformer (T201) that adds a very
low amount of jitter to the clock path. The clock input is
50 Ω terminated and ac-coupled to handle single-ended
sine wave types of inputs. The transformer converts the
single-ended input to a differential signal that is clipped
before entering the ADC clock inputs.
D + x, D − x: If an alternative data capture method to the setup
shown in Figure 60 is used, optional receiver terminations,
R206 to R211, can be installed next to the high speed back-
plane connector.
Rev. E | Page 36 of 52
Data Sheet
AD9259
ALTERNATIVE ANALOG INPUT DRIVE
CONFIGURATION
•
•
Populate R101, R114, R127, and R140 with 0 Ω resistors in
the analog input path.
The following is a brief description of the alternative analog input
drive configuration using the AD8332 dual VGA. If this drive
option is in use, some components may need to be populated, in
which case all the necessary components are listed in Table 17. For
more details on the AD8332 dual VGA, including how it works
and its optional pin settings, consult the AD8332 data sheet.
Populate R105, R113, R118, R124, R131, R137, R151, and
R160 with 0 Ω resistors in the analog input path to connect
the AD8332.
•
Populate R152, R153, R154, R155, R156, R157, R158, R159,
C103, C105, C110, C112, C117, C119, C124, and C126
with 10 kΩ resistors to provide an input common-mode
level to the ADC analog inputs.
To configure the analog input to drive the VGA instead of the
default transformer option, the following components need to
be removed and/or changed.
•
Remove R305, R306, R313, R314, R405, R406, R412, and
R424 to configure the AD8332.
•
Remove R102, R115, R128, R141, R161, R162, R163, R164,
T101, T102, T103, and T104 in the default analog input path.
In this configuration, L301 to L308 and L401 to L408 are
populated with 0 Ω resistors to allow signal connection and
use of a filter if additional requirements are necessary.
Rev. E | Page 37 of 52
AD9259
Data Sheet
AVDD_DUT
R105
DNP
R152
DNP
CH_A
C101
FB102 R108
R104
0Ω
P102
DNP
T101
0.1µF
10Ω 33Ω
VGA INPUT CONNECTION
INH1
1
6
VIN_A
AIN
R106
DNP
CHANNEL A
P101
R101
DNP
R161
2
3
5
4
R109
1kΩ
C103
C104
2.2pF
CM1
CM1
499Ω
DNP
AIN
R107
DNP
R113
DNP
FB101
10Ω
R103
0Ω
C102
0.1µF
R102
64.9Ω
VIN_A
CH_A
CM1
FB103 R110
C105
DNP
R156
DNP
10Ω
33Ω
E101
AVDD_DUT
C106
DNP
R111
1kΩ
C107
0.1µF
R112
1kΩ
AVDD_DUT
AVDD_DUT
R118
DNP
VGA INPUT CONNECTION
INH2
R153
DNP
CH_B
CHANNEL B
P103
FB105 R121
R114
DNP
T102
10Ω 33Ω
1
6
AIN
VIN_B
FB104
10Ω
R119
DNP
R115
64.9Ω
C108
0.1µF
R162
2
3
5
4
R123
1kΩ
P104
DNP
C110
C111
2.2pF
CM2
CM2
499Ω
DNP
R120
DNP
R124
DNP
R116
0Ω
AIN
C109
0.1µF
E102
VIN_B
CH_B
CM2
R117
0Ω
FB106 R122
C112
DNP
R157
DNP
10Ω
33Ω
AVDD_DUT
C113
DNP
R125
1kΩ
C114
0.1µF
R126
1kΩ
AVDD_DUT
AVDD_DUT
R131
DNP
R154
DNP
CH_C
C115
FB108 R134
P106
DNP
R130
0Ω
T103
0.1µF
10Ω 33Ω
VGA INPUT CONNECTION
INH3
1
6
VIN_C
AIN
R132
DNP
CHANNEL C
P105
R127
DNP
R163
2
3
5
4
R135
1kΩ
C117
C118
2.2pF
CM3
CM3
499Ω
DNP
AIN
R133
DNP
R137
DNP
FB107
10Ω
R129
0Ω
C116
0.1µF
R128
64.9Ω
VIN_C
CH_C
CM3
FB109 R136
C119
DNP
R158
DNP
10Ω
33Ω
E103
AVDD_DUT
C120
DNP
R138
1kΩ
C121
0.1µF
R139
1kΩ
AVDD_DUT
AVDD_DUT
R151
DNP
VGA INPUT CONNECTION
INH4
R155
DNP
CH_D
CHANNEL D
P107
FB111 R146
R140
DNP
T104
10Ω 33Ω
1
6
AIN
VIN_D
FB110
R144
DNP
R141
64.9Ω
C122
10Ω
0.1µF
R164
499Ω
2
3
5
4
R148
1kΩ
C124
DNP
C125
CM4
P108
CM4
2.2pF
DNP
R145
DNP
R160
DNP
R143
0Ω
AIN
C123
0.1µF
R142
VIN_D
CH_D
CM4
0Ω
FB112 R147
C126
DNP
R159
DNP
10Ω
33Ω
E104
AVDD_DUT
C127
DNP
R149
1kΩ
C128
0.1µF
R150
1kΩ
AVDD_DUT
DNP: DO NOT POPULATE
Figure 62. Evaluation Board Schematic, DUT Analog Inputs
Rev. E | Page 3± of 52
Data Sheet
AD9259
AVDD_DUT
CW
S 0
S 1
S 2
S 3
S 4
S 5
S 6
S 7
S 8
2 5
1 6
1 5
1 4
1 3
1 2
1 1
1 0
2
2
2
2
1
2
Ω k 1 0
3 3
3 1
1
0 5 R 2
3
V –
D
G N
V S
E T R S
Ω 0 k 1 0
0 4 R 2
P N - Ω D 0 1 0 k
7
R 2 6
9
P N - Ω D k 1 0 0
Ω 0 k 1 0
0 3 R 2
S 9
8
6 6 R 2
0
S 1
3 2
7
E F V R
6
B – N V I
N V + I
B _ V I N
B _ N V I
3 7
3 8
3 9
4 0
4 1
4 2
4 3
4 4
4 5
4 6
4 7
4 8
O
O
D C
D C
+ O D C
2 4
B
– O D C
+ O F C
– O F C
2 3
2 2
2 1
2 0
1 9
1 8
1 7
1 6
1 5
1 4
1 3
D D A V
S A I R B
E S N S E
V R E F
U T _ D D D A V
O
O
F C
F C
T U D S E _ S V E N
C H A
C H A
C H B
C H B
C H C
C H C
A
D +
D –
D +
D –
D +
D –
D +
D –
T U D _
V R E F
A
B F R E
T F R E
D D A V
B
1
B
U T _ D D D A V
U T _ D D D A V
C
D D A V
C
C
N V + I
C _ N V I
C H D
C H D
D
C _ V I N
C – N V I
D
Figure 63. Evaluation Board Schematic, DUT, VREF, Clock Inputs, and Digital Output Interface
Rev. E | Page 39 of 52
AD9259
Data Sheet
POPULATE L301 TO L308 WITH
0Ω RESISTORS OR DESIGN
YOUR OWN FILTER.
R301
DNP
R302
DNP
EXTERNAL VARIABLE GAIN DRIVE
VG
C302
DNP
C301
DNP
VARIABLE GAIN CIRCUIT
L301
0Ω
L302 L303
L304
0Ω
(0V TO 1.0V DC)
VG
0Ω
0Ω
GND
CW
AVDD_5V
C303
C304
L307
0Ω
L306
0Ω
L305 DNP
DNP L308
R320
39kΩ
R319
10kΩ
0Ω
0Ω
R303
DNP
R304
DNP
C305
0.1µF
C306 C307
0.1µF 0.1µF
C308
0.1µF
R306
374Ω
R305
374Ω
R311
C309
1000pF
10kΩ
DNP
C310
0.1µF
R307
187Ω
R308
187Ω
R309
187Ω
R310
187Ω
R312
10kΩ
U301
25
R313
10kΩ
DNP
R314
ENBV
ENBL
HILO
VCM1
VIN1
VIP1
COM1
LOP1
RCLMP
16
26
27
28
29
30
31
32
10kΩ
VG
GAIN
MODE
VCM2
VIN2
VIP2
COM2
LOP2
15
14
13
12
11
10
9
DNP
AD8332
C311
0.1µF
C313
0.1µF
C312
0.1µF
C314
0.1µF
R316
C320
0.1µF
R317
274Ω
C321
0.1µF
274Ω
R315 C315
10kΩ 10µF
C316
0.1µF
C325
0.1µF
C326
10µF
R318
10kΩ
C317
0.018µF
C322
0.018µF
C318
22pF
C323
22pF
L309
120nH
L310
120nH
C319
0.1µF
C324
0.1µF
DNP: DO NOT POPULATE
INH4
INH3
Figure 64. Evaluation Board Schematic, Optional DUT Analog Input Drive and SPI Interface Circuit
Rev. E | Page 40 of 52
Data Sheet
AD9259
_ C H D A S O
0 Ω
R 4 2 7
_ C D H S I A
0 Ω
R 4 2 0
K _ C H S L A
0 Ω
R 4 2 8
B 1 _ C C S H A
0 Ω
R 4 2 6
J401
PICVCC
1
2
PICVCC
GP1
GP0
3
5
4
6
GP1
GP0
MCLR/GP3
7
9
8
10
MCLR/GP3
7 5 4 k . Ω
R 4 1 8
OPTIONAL
PIC PROGRAMMING HEADER
7 5 m ± V H = N I = P O L H I
L O = I = N I L H O P
0 V 5 - . 2 5 V 2 . = E P O L N A S I G E V I A T G N E
V m 0 5
±
V . 0
T V O 0 1 = E L O S P I N G E A I T I V O P S
E D P I M O
N I P P A M R C L
D D A _ 5 V V
N
. R E L I T F N W O U R O Y
N I G E S D R O S R O T S I E S R Ω 0
4 0 L 8 O 4 0 L 1 E T T A L U P O P
H T I
W
C H _ A
F
R 4 1 6
0 1 0 8 . µ
C 4 2 0
2 7 4 Ω
2
L O N
M M C O
H 2 O V
O V L 2
8
1 7
1 8
1 9
V P S 2
7
D D A _ 5 V V
N I H 2
6
C H _ A
C H _ B
N C
2 0
D 2 M L
D 1 M L
5
4
V P S V
O V L 1
D D A _ 5 V V
2 1
2 2
N I H 1
H 1 O V
M M C O
3
2 3
2 4
V P S 1
2
D D A _ 5 V V
1
L O N
1
C H _ B
)
E R W E L P B O S I A D V = 1 O V ( T 0
N A B N L W E R E D W O O P
E
D D A _ 5 V V
0 V 1 O .
T
0 V = E
N R A A I G N O G L
N R A A I G N H G I
0 V 5 - . 2 5 V 2 . = E
I N
I L H O P
B L
A L A N D C H A N R N O C E H F T A N N E R C U C E I I V
A G D R V I N A O I L T P O
Figure 65. Evaluation Board Schematic, Optional DUT Analog Input Drive and SPI Interface Circuit (Continued)
Rev. E | Page 41 of 52
AD9259
Data Sheet
N D G
N D G
1
1
N D G
N D G
1
1
Figure 66. Evaluation Board Schematic, Power Supply Inputs
Rev. E | Page 42 of 52
Data Sheet
AD9259
Figure 67. Evaluation Board Layout, Primary Side
Rev. E | Page 43 of 52
AD9259
Data Sheet
Figure 68. Evaluation Board Layout, Ground Plane
Rev. E | Page 44 of 52
Data Sheet
AD9259
Figure 69. Evaluation Board Layout, Power Plane
Rev. E | Page 45 of 52
AD9259
Data Sheet
Figure 70. Evaluation Board Layout, Secondary Side (Mirrored Image)
Rev. E | Page 46 of 52
Data Sheet
AD9259
Table 17. Evaluation Board Bill of Materials (BOM)1
Manufacturer’s
Manufacturer Part Number
Item
Qty.
1
75
Reference Designator
Device
PCB
Capacitor
Package
PCB
402
Value
1
2
AD9259LFCSP_REVA
PCB
0.1 μF, ceramic,
C101, C102, C107,
C10±, C109, C114,
C115, C116, C121,
C122, C123, C12±,
C201, C203, C204,
C205, C206, C210,
C211, C212, C213,
C216, C217, C21±,
C219, C220, C221,
C222, C223, C224,
C310, C311, C312,
C313, C314, C316,
C319, C320, C321,
C324, C325, C409,
C410, C412, C414,
C416, C417, C419,
C422, C423, C424,
C425, C427, C42±,
C429, C503, C505,
C507, C509, C516,
C517, C51±, C519,
C520, C521, C522,
C523, C524, C525,
C526, C527, C52±,
C529, C530, C531
Murata
GRM155R71C104KA±±D
X5R, 10 V, 10% tol
3
4
C104, C111, C11±,
C125
Capacitor
402
2.2 pF, ceramic,
COG, 0.25 pF tol,
50 V
Murata
GRM1555C1H2R2GZ01B
4
4
1
2
4
4
1
9
C315, C326, C413,
C426
C202
Capacitor
Capacitor
Capacitor
Capacitor
Capacitor
Capacitor
Capacitor
±05
603
402
402
402
1206
603
10 μF, 6.3 V ±10%
ceramic, X5R
2.2 μF, ceramic,
X5R, 6.3 V, 10% tol
1000 pF, ceramic,
X7R, 25 V, 10% tol
0.01± μF, ceramic,
X7R, 16 V, 10% tol
22 pF, ceramic,
NPO, 5% tol, 50 V
10 μF, tantalum,
16 V, 20% tol
Murata
Murata
Murata
AVX
GRM219R60J106KE19D
GRM1±±C70J225KE20D
GRM155R71H102KA01D
0402YC1±3KAT2A
5
6
C309, C411
7
C317, C322, C415,
C420
C31±, C323, C41±,
C421
±
Murata
Rohm
GRM1555C1H220JZ01D
TCA1C106M±R
9
C501
10
C214, C512, C513,
C514, C515, C532,
C533, C534, C535
1 μF, ceramic, X5R, Murata
6.3 V, 10% tol
GRM1±±R61C105KA93D
11
±
C305, C306, C307,
C30±, C405, C406,
C407, C40±
C502, C504, C506,
C50±
Capacitor
±05
0.1 μF, ceramic,
X7R, 50 V, 10% tol
Murata
Murata
GRM21BR71H104KA01L
12
13
14
15
16
4
1
2
1
1
Capacitor
Diode
LED
603
10 μF, ceramic,
X5R, 6.3 V, 20% tol
30 V, 20 mA, dual
Schottky
Green, 4 V, 5 m
candela
GRM1±±R60J106M
HSMS2±12-TRIG
LNJ314G±TRA
SK33-TP
CR201
SOT-23
603
Agilent
Technologies
Panasonic
CR401, CR501
D502
Diode
Diode
DO-214AB 3 A, 30 V, SMC
Micro
Commercial Co.
Micro
D501
DO-214AA 2 A, 50 V, SMC
S2A-TP
Commercial Co.
Rev. E | Page 47 of 52
AD9259
Data Sheet
Manufacturer’s
Manufacturer Part Number
Item
Qty.
Reference Designator
Device
Package
Value
17
1
F501
Fuse
1210
6.0 V, 2.2 A trip-
current resettable
fuse
Tyco/Raychem NANOSMDC110F-2
1±
19
1
FER501
Choke coil
2020
603
10 μH, 5 A, 50 V,
190 Ω @ 100 MHz
10 Ω, test freq
100 MHz, 25% tol,
500 mA
Murata
Murata
DLW5BSN191SQ2L
BLM1±BA100SN1B
12
FB101, FB102, FB103,
FB104, FB105, FB106,
FB107, FB10±, FB109,
FB110, FB111, FB112
Ferrite bead
20
21
22
1
2
4
JP301
Connector
Connector
Connector
2-pin
3-pin
12-pin
100 mil header
jumper, 2-pin
100 mil header
jumper, 3-pin
100 mil header
male, 4 × 3 triple
row straight
Samtec
Samtec
Samtec
TSW-102-07-G-S
TSW-103-07-G-S
TSW-104-0±-G-T
J205, J402
J201 to J204
23
24
25
26
1
J401
Connector
10-pin
1210
402
100 mil header,
male, 2 × 5 double
row straight
10 μH, bead core
3.2 × 2.5 × 1.6
SMD, 2 A
120 nH, test freq
100 MHz, 5% tol,
150 mA
Samtec
Murata
Murata
TSW-105-0±-G-D
BLM31PG500SN1L
LQG15HNR12J02B
NRC10ZOTRF
±
L501, L502, L503, L504, Ferrite bead
L505, L506, L507, L50±
4
L309, L310, L409, L410 Inductor
16
L301, L302, L303, L304, Resistor
L305, L306, L307, L30±,
±05
0 Ω, 1/± W, 5% tol
NIC
Components
L401, L402, L403, L404,
L405, L406, L407, L40±
27
2±
1
5
OSC201
Oscillator
SMT
SMA
Clock oscillator,
50.00 MHz, 3.3 V
Side-mount SMA
for 0.063" board
thickness
Valpey Fisher
VFAC3H-L-50MHz
142-0710-±51
P101, P103, P105,
P107, P201
Connector
Johnson
Components
29
1
P202
Connector
Header
1469169-1, right
angle 2-pair,
25 mm, header
assembly
Tyco
6469169-1
30
31
1
P503
Connector
Resistor
0.1", PCMT SC1153, power
supply connector
Switchcraft
RAPC722X
15
R201, R205, R214,
R215, R221, R239,
R312, R315, R31±,
R411, R414, R417,
R425, R429, R430
402
10 kΩ, 1/16 W,
5% tol
NIC
Components
NRC04J103TRF
32
14
R103, R117, R129,
R142, R216, R217,
R21±, R223, R224,
R237, R420, R426,
R427, R42±
Resistor
402
0 Ω, 1/16 W,
5% tol
NIC
Components
NRC04Z0TRF
33
34
4
4
R102, R115, R12±,
R141
R104, R116, R130,
R143
Resistor
Resistor
402
603
64.9 Ω, 1/16 W,
1% tol
0 Ω, 1/10 W,
5% tol
NIC
Components
NIC
Components
NRC04F64R9TRF
NRC06Z0TRF
Rev. E | Page 4± of 52
Data Sheet
AD9259
Manufacturer’s
Manufacturer Part Number
Item
Qty.
Reference Designator
Device
Package
Value
35
15
R109, R111, R112,
R123, R125, R126,
R135, R13±, R139,
R14±, R149, R150,
R431, R432, R433
Resistor
402
1 kΩ, 1/16 W,
1% tol
NIC
Components
NRC04F1001TRF
36
±
R10±, R110, R121,
R122, R134, R136,
R146, R147
Resistor
402
33 Ω, 1/16 W,
5% tol
NIC
Components
NRC04J330TRF
37
3±
39
40
41
42
4
3
1
1
1
2
R161, R162, R163,
R164
R202, R203, R204
Resistor
402
499 Ω, 1/16 W,
1% tol
100 kΩ, 1/16 W,
1% tol
4.12 kΩ, 1/16 W,
1% tol
49.9 Ω, 1/16 W,
0.5% tol
4.99 kΩ, 1/16 W,
5% tol
10 kΩ, cermet
trimmer
NIC
Components
NIC
Components
NIC
Components
Susumu
NRC04F4990TRF
NRC04F1003TRF
NRC04F4121TRF
RR0510R-49R9-D
NRC04F4991TRF
CT94EW103
Resistor
402
R222
Resistor
402
R213
Resistor
402
R229
Resistor
402
NIC
Components
BC
R230, R319
Potentiometer
3-lead
Components
potentiometer,
1±-turn top adjust,
10%, 1/2 W
43
44
45
1
1
±
R22±
R320
Resistor
Resistor
Resistor
402
402
402
470 kΩ, 1/16 W,
5% tol
39 kΩ, 1/16 W,
5% tol
1±7 Ω, 1/16 W,
1% tol
NIC
Components
NIC
Components
NIC
Components
NRC04J474TRF
NRC04J393TRF
NRC04F1±70TRF
R307, R30±, R309,
R310, R407, R40±,
R409, R410
46
47
4±
4
R305, R306, R405,
R406
R316, R317, R415,
R416
R245, R247, R249,
R251, R253, R255,
R257, R259, R261,
R263, R265
Resistor
Resistor
Resistor
402
402
201
374 Ω, 1/16 W,
1% tol
274 Ω, 1/16 W,
1% tol
NIC
Components
NIC
Components
NRC04F3740TRF
NRC04F2740TRF
ERJ-1GE0R00C
4
11
0 Ω, 1/20 W, 5% tol
Panasonic
49
50
51
52
53
54
55
1
1
1
2
2
1
5
R41±
Resistor
Resistor
Resistor
Resistor
Resistor
Switch
402
4.75 kΩ, 1/16 W,
1% tol
261 Ω, 1/16 W,
1% tol
261 Ω, 1/16 W,
1% tol
243 Ω, 1/16 W,
1% tol
100 Ω, 1/16 W,
1% tol
Light touch,
100GE, 5 mm
ADT1-1WT, 1:1
impedance ratio
transformer
NIC
Components
NIC
Components
NIC
Components
NIC
Components
NRC04J472TRF
NRC04F2610TRF
NRC06F2610TRF
NRC04F2430TRF
NRC04F1000TRF
EVQ-PLDA15
R419
402
R501
603
R240, R241
R242, R243
S401
402
402
NIC
Components
Panasonic
SMD
CD542
T101, T102, T103,
T104, T201
Transformer
Mini-Circuits
ADT1-1WT+
56
2
U501, U503
IC
SOT-223
ADP3339AKC-1.±,
1.5 A, 1.± V LDO
regulator
Analog Devices ADP3339AKCZ-1.±
Rev. E | Page 49 of 52
AD9259
Data Sheet
Manufacturer’s
Manufacturer Part Number
Item
Qty.
Reference Designator
Device
Package
Value
57
2
U301, U401
IC
LFCSP,
CP-32
AD±332ACP,
ultralow noise
precision dual VGA
Analog Devices AD±332ACPZ
5±
59
60
1
1
1
U504
U502
U201
IC
IC
IC
SOT-223
SOT-223
LFCSP,
ADP3339AKC-5
ADP3339AKC-3.3
AD9259BCPZ-50,
quad, 14-bit, 50
MSPS serial LVDS
1.± V ADC
Analog Devices ADP3339AKCZ-5
Analog Devices ADP3339AKCZ-3.3
Analog Devices AD9259BCPZ-50
CP-4±-1
61
1
U203
IC
SOT-23
ADR510ARTZ, 1.0 V, Analog Devices ADR510ARTZ
precision low
noise shunt
voltage reference
62
63
64
65
1
1
1
1
U202
U403
U404
U402
IC
IC
IC
IC
LFCSP
CP-32-2
SC70,
MAA06A
SC70,
MAA06A
±-SOIC
AD9515BCPZ
Analog Devices AD9515BCPZ
NC7WZ07
Fairchild
Fairchild
Microchip
NC7WZ07P6X_NL
NC7WZ16
NC7WZ16P6X_NL
PIC12F629-I/SN
Flash prog
mem 1k × 14,
RAM size 64 × ±,
20 MHz speed,
PIC12F controller
series
1 This BOM is RoHS compliant.
Rev. E | Page 50 of 52
Data Sheet
AD9259
OUTLINE DIMENSIONS
7.10
7.00 SQ
6.90
0.30
0.23
0.18
0.60 MAX
0.60 MAX
PIN 1
INDICATOR
37
36
48
1
PIN 1
INDICATOR
0.50
REF
6.85
*
5.55
5.50 SQ
5.45
6.75 SQ
6.65
EXPOSED
PAD
(BOTTOM VIEW)
25
24
12
13
0.50
0.40
0.30
0.22 MIN
TOP VIEW
5.50 REF
0.80 MAX
0.65 TYP
12° MAX
1.00
0.85
0.80
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.05 MAX
0.02 NOM
COPLANARITY
SECTION OF THIS DATA SHEET.
SEATING
PLANE
0.08
0.20 REF
*
COMPLIANT TO JEDEC STANDARDS MO-220-VKKD-2
WITH EXCEPTION TO EXPOSED PAD DIMENSION.
Figure 71. 48-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
7 mm × 7 mm Body, Very Thin Quad
(CP-48-8)
Dimensions shown in millimeters
ORDERING GUIDE
Temperature
Notes Range
Package
Option
Model1
Package Description
AD9259ABCPZ-50
AD9259ABCPZRL7-50
AD9259-50EBZ
−40°C to +85°C
−40°C to +85°C
48-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
48-Lead Lead Frame Chip Scale Package [LFCSP_VQ] 7”Tape and Reel
Evaluation Board
CP-48-8
CP-48-8
2
1 Z = RoHS Compliant Part.
2 Interposer board (HSC-ADC-FIFO5-INTZ) is required to connect to HSC-ADC-EVALCZ data capture board.
Rev. E | Page 51 of 52
AD9259
NOTES
Data Sheet
©2006–2011 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D05965-0-1 /11(E)
Rev. E | Page 52 of 52
相关型号:
AD9259BCPZRL7-50
IC 4-CH 14-BIT FLASH METHOD ADC, SERIAL ACCESS, QCC48, 7 X 7 MM, ROHS COMPLIANT, MO-220VKKD-2, LFCSP-48, Analog to Digital Converter
ADI
AD9260ASZ
1-CH 16-BIT PROPRIETARY METHOD ADC, PARALLEL ACCESS, PQFP44, LEAD FREE, MS-022AB, MQFP-44
ROCHESTER
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