ADL5375-05-EVALZ [ADI]
400 MHz to 6 GHz Broadband Quadrature Modulator; 400 MHz至6 GHz的宽带正交调制器
| 型号： | ADL5375-05-EVALZ |
| 厂家： | 
ADI |
| 描述： | 400 MHz to 6 GHz Broadband Quadrature Modulator |
| 文件： | 总36页 (文件大小：926K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
400 MHz to 6 GHz
Broadband Quadrature Modulator
Data Sheet
ADL5375
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Output frequency range: 400 MHz to 6 GHz
1 dB output compression: ≥9.4 dBm from 450 MHz to 4 GHz
Output return loss ≤ 12 dB from 450 MHz to 4.5 GHz
Noise floor: −160 dBm/Hz @ 900 MHz
Sideband suppression: ≤−50 dBc @ 900 MHz
Carrier feedthrough: ≤−40 dBm @ 900 MHz
IQ3dB bandwidth: ≥ 750 MHz
IBBP
ADL5375
IBBN
LOIP
LOIN
QUADRATURE
PHASE
SPLITTER
RFOUT
DSOP
Baseband input bias level
ADL5375-05: 500 mV
ADL5375-15: 1500 mV
Single supply: 4.75 V to 5.25 V
24-lead LFCSP_VQ package
QBBN
QBBP
Figure 1.
APPLICATIONS
Cellular communication systems
GSM/EDGE, CDMA2000, W-CDMA, TD-SCDMA
WiMAX/LTE broadband wireless access systems
Satellite modems
GENERAL DESCRIPTION
The ADL5375 is a broadband quadrature modulator designed for
operation from 400 MHz to 6 GHz. Its excellent phase accuracy
and amplitude balance enable high performance intermediate
frequency or direct radio frequency modulation for commu-
nication systems.
broadband digital predistortion transmitters, and multiband
radio designs.
The ADL5375 accepts two differential baseband inputs and
a single-ended LO. It generates a single-ended 50 Ω output.
The two versions offer input baseband bias levels of 500 mV
(ADL5375-05) and 1500 mV (ADL5375-15).
The ADL5375 features a broad baseband bandwidth, along
with an output gain flatness that varies no more than 1 dB
from 450 MHz to 3.5 GHz. These features, coupled with a broad-
band output return loss of ≤−12 dB, make the ADL5375 ideally
suited for broadband zero IF or low IF-to-RF applications,
The ADL5375 is fabricated using an advanced silicon-germanium
bipolar process. It is available in a 24-lead, exposed paddle, lead-
free, LFCSP_VQ package. Performance is specified over a −40°C
to +85°C temperature range. A lead-free evaluation board is
also available.
Rev. C
Document Feedback
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rightsof third parties that may result fromits use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks andregisteredtrademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700 ©2007–2013 Analog Devices, Inc. All rights reserved.
Technical Support
www.analog.com
ADL5375
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
LO Input ...................................................................................... 20
RF Output.................................................................................... 20
Output Disable............................................................................ 21
Applications Information .............................................................. 22
Carrier Feedthrough Nulling.................................................... 22
Sideband Suppression Optimization ....................................... 22
Interfacing the ADF4350 PLL to the ADL5375 ..................... 23
DAC Modulator Interfacing ..................................................... 24
GSM/EDGE Operation ............................................................. 27
W-CDMA Operation................................................................. 28
LO Generation Using PLLs....................................................... 29
Transmit DAC Options ............................................................. 29
Modulator/Demodulator Options ........................................... 29
Evaluation Board ............................................................................ 30
Characterization Setup .................................................................. 33
Outline Dimensions....................................................................... 35
Ordering Guide .......................................................................... 35
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description ......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 7
ESD Caution.................................................................................. 7
Pin Configuration and Function Descriptions............................. 8
Typical Performance Characteristics ............................................. 9
ADL5375-05.................................................................................. 9
ADL5375-15................................................................................ 14
Theory of Operation ...................................................................... 19
Circuit Description..................................................................... 19
Basic Connections .......................................................................... 20
Power Supply and Grounding................................................... 20
Baseband Inputs.......................................................................... 20
REVISION HISTORY
7/13—Rev. B to Rev. C
11/08—Rev. 0 to Rev. A
Changed CP-24-3 to CP-24-7 ...........................................Universal
Change AD9779 to AD9779A ..........................................Universal
Added Endnote, I/Q Input Bias Level and Absolute
Voltage Level Parameters, Table 1 ...................................................6
Added Absolute Voltage Level Parameter, Table 1........................6
9/11—Rev. A to Rev. B
Changes to Features Section............................................................ 1
Replaced Table 1 ............................................................................... 3
Changes to Typical Performance Characteristics Section........... 9
Updated Output Disable Section.................................................. 21
Changes to Application Information Section ............................ 22
Changes to Evaluation Board Section.......................................... 30
Changes to Figure 80...................................................................... 34
Added Exposed Pad Notation to Outline Dimensions ............. 35
12/07—Revision 0: Initial Version
Rev. C | Page 2 of 36
Data Sheet
ADL5375
SPECIFICATIONS
VS = 5 V; TA = 25°C; LO = 0 dBm single-ended drive; baseband I/Q amplitude = 1 V p-p differential sine waves in quadrature with a
500 mV (ADL5375-05) or 1500 mV (ADL5375-15) dc bias; baseband I/Q frequency (fBB) = 1 MHz, unless otherwise noted.
Table 1.
ADL5375-05
ADL5375-15
Parameter
Conditions
Min Typ Max Min Typ
Max Unit
OPERATING FREQUENCY RANGE
Low frequency
High frequency
LO = 450 MHz
400
6000
400
6000
MHz
MHz
Output Power, POUT
Modulator Voltage Gain
Output P1dB
Output Return Loss
Carrier Feedthrough
Sideband Suppression
Quadrature Error
I/Q Amplitude Balance
Second Harmonic
ADL5375-05
VIQ = 1 V p-p differential
RF output divided by baseband input voltage
0.85
−3.1
9.6
−16.4
−47.5
−37.6
1.7
0.47
−3.5
10
−15.2
-42.5
−38
1.49
0.10
−81.5
dBm
dB
dBm
dB
dBm
dBc
Degrees
0.07
−75.9
dB
dBc
POUT − (fLO + (2 × fBB))
POUT =0.85 dBm
ADL5375-15
Third Harmonic
ADL5375-05
POUT = 0.47 dBm
POUT − (fLO + (3 × fBB))
POUT = 0.85 dBm
POUT = 0.47 dBm
−51.5
−81.6
dBc
ADL5375-15
Output IP2
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
65.4
64.7
dBm
Output IP3
Noise Floor
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
I/Q inputs = 0 V differential with a dc bias
only, 20 MHz carrier offset
26.6
23.6
dBm
−160.5
−157.0
dBm/Hz
LO = 900 MHz
Output Power, POUT
Modulator Voltage Gain
Output P1dB
Output Return Loss
Carrier Feedthrough
Sideband Suppression
Quadrature Error
I/Q Amplitude Balance
Second Harmonic
ADL5375-05
VIQ = 1 V p-p differential
RF output divided by baseband input voltage
0.75
−3.2
9.6
−15.7
−45.1
−52.8
0.01
0.41
−3.5
10
−14.7
−39.9
−49.9
0.20
dBm
dB
dBm
dB
dBm
dBc
Degrees
dB
0.07
−75.8
0.10
−77.2
POUT − (fLO + (2 × fBB))
POUT = 0.75 dBm
POUT = 0.41 dBm
POUT − (fLO + (3 × fBB))
POUT = 0.75 dBm
POUT = 0.41 dBm
dBc
ADL5375-15
Third Harmonic
ADL5375-05
−50.7
−72.7
dBc
ADL5375-15
Output IP2
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
62.6
64.5
dBm
Output IP3
Noise Floor
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
I/Q inputs = 0 V differential with a dc bias
only, 20 MHz carrier offset
25.9
23.4
dBm
−160.0
−157.1
dBm/Hz
Rev. C | Page 3 of 36
ADL5375
Data Sheet
ADL5375-05
Min Typ
ADL5375-15
Parameter
Conditions
Max Min Typ
Max Unit
LO = 1900 MHz
Output Power, POUT
Modulator Voltage Gain
Output P1dB
Output Return Loss
Carrier Feedthrough
Sideband Suppression
Quadrature Error
I/Q Amplitude Balance
Second Harmonic
ADL5375-05
VIQ = 1 V p-p differential
RF output divided by baseband input voltage
0.53
−3.4
9.9
−16.2
−40.3
−50.2
0.02
0.49
−3.4
10.5
−15.5
−35.5
−49.4
0.21
0.10
−72.1
dBm
dB
dBm
dB
dBm
dBc
Degrees
0.07
−67.9
dB
dBc
POUT − (fLO + (2 × fBB))
POUT = 0.53dBm
POUT = 0.49dBm
ADL5375-15
Third Harmonic
ADL5375-05
ADL5375-15
POUT − (fLO + (3 × fBB))
POUT = 0.53dBm
POUT = 0.49dBm
−51.8
−62.8
dBc
Output IP2
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
62.6
61
dBm
Output IP3
Noise Floor
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
I/Q inputs = 0 V differential with a dc bias
only, 20 MHz carrier offset
24.3
22.1
−158.2
dBm
−160.0
dBm/Hz
LO = 2150 MHz
Output Power, POUT
Modulator Voltage Gain
Output P1dB
Output Return Loss
Carrier Feedthrough
Sideband Suppression
Quadrature Error
I/Q Amplitude Balance
Second Harmonic
ADL5375-05
VIQ = 1 V p-p differential
RF output divided by baseband input voltage
0.73
−3.2
10.0
−17.1
−39.7
−47.3
−0.16
0.07
0.57
−3.4
10.6
−16.1
−34.2
−50.2
−0.18
0.10
dBm
dB
dBm
dB
dBm
dBc
Degrees
dB
POUT − (fLO + (2 × fBB))
POUT = 0.73 dBm
POUT = 0.57 dBm
POUT − (fLO + (3 × fBB))
POUT = 0.73 dBm
POUT = 0.57 dBm
−71.3
−81.7
dBc
ADL5375-15
Third Harmonic
ADL5375-05
−52.4
−65.3
dBc
ADL5375-15
Output IP2
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
61.6
61.8
dBm
Output IP3
Noise Floor
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
I/Q inputs = 0 V differential with a dc bias
only, 20 MHz carrier offset
24.2
22.3
dBm
−159.5
−157.9
dBm/Hz
LO = 2600 MHz
Output Power, POUT
Modulator Voltage Gain
Output P1dB
Output Return Loss
Carrier Feedthrough
Sideband Suppression
Quadrature Error
VIQ = 1 V p-p differential
RF output divided by baseband input voltage
0.61
−3.4
9.6
−19.3
−36.5
−48.3
−0.37
0.07
0.62
−3.3
10.6
dBm
dB
dBm
dB
dBm
dBc
Degrees
dB
−18
−33.3
−48.5
0.19
0.11
−55.9
I/Q Amplitude Balance
Second Harmonic
POUT − (fLO + (2 × fBB))
−60.9
dBc
Rev. C | Page 4 of 36
Data Sheet
ADL5375
ADL5375-05
ADL5375-15
Parameter
Conditions
Min Typ Max Min Typ
Max Unit
ADL5375-05
ADL5375-15
Third Harmonic
ADL5375-05
ADL5375-15
Output IP2
POUT = 0.61 dBm
POUT = 0.62 dBm
POUT − (fLO + (3 × fBB))
POUT = 0.61 dBm
POUT = 0.62 dBm
−51.3
−57.6
dBc
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
55.0
50.1
dBm
Output IP3
Noise Floor
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
I/Q inputs = 0 V differential with a dc bias
only, 20 MHz carrier offset
22.7
20.7
dBm
−159.0
−157.6
dBm/Hz
LO = 3500 MHz
Output Power, POUT
Modulator Voltage Gain
Output P1dB
Output Return Loss
Carrier Feedthrough
Sideband Suppression
Quadrature Error
I/Q Amplitude Balance
Second Harmonic
ADL5375-05
VIQ = 1 V p-p differential
RF output divided by baseband input voltage
0.21
−3.8
9.6
−20.7
−30.4
−48.3
0.01
0.87
−3.1
10.2
−19.4
−28.6
−48.8
0.13
dBm
dB
dBm
dB
dBm
dBc
Degrees
dB
0.08
−55.8
0.11
−63
POUT − (fLO + (2 × fBB))
POUT = 0.21 dBm
POUT = 0.87 dBm
POUT − (fLO + (3 × fBB))
POUT = 0.21 dBm
POUT = 0.87 dBm
dBc
ADL5375-15
Third Harmonic
ADL5375-05
−50.2
−56.2
dBc
ADL5375-15
Output IP2
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
51.1
57.9
dBm
Output IP3
Noise Floor
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
I/Q inputs = 0 V differential with a dc bias
only, 20 MHz carrier offset
23.1
20.2
dBm
−157.6
−156.3
dBm/Hz
LO = 5800 MHz
Output Power, POUT
Modulator Voltage Gain
Output P1dB
Output Return Loss
Carrier Feedthrough
Sideband Suppression
Quadrature Error
I/Q Amplitude Balance
Second Harmonic
ADL5375-05
VIQ = 1 V p-p differential
RF output divided by baseband input voltage
−1.36
−5.3
4.9
0.16
−3.8
4.4
−8.6
−16.7
−39
−0.50
−0.70
−50
dBm
dB
dBm
dB
dBm
dBc
Degrees
dB
−7.4
−19.5
−38.2
−0.51
−0.05
−52.6
POUT − (fLO + (2 × fBB))
POUT = -1.36 dBm
POUT = 0.16 dBm
dBc
ADL5375-15
Third Harmonic
ADL5375-05
ADL5375-15
POUT − (fLO + (3 × fBB))
POUT = -1.36 dBm
POUT = 0.16 dBm
−45.7
−48.4
dBc
Output IP2
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
39.1
38.7
dBm
Output IP3
Noise Floor
f1BB = 3.5 MHz, f2BB = 4.5 MHz, baseband I/Q
amplitude per tone = 0.5 V p-p differential
I/Q inputs = 0 V differential with a dc bias
only, 20 MHz carrier offset
14.6
11.2
dBm
−153.0
−153.4
dBm/Hz
Rev. C | Page 5 of 36
ADL5375
Data Sheet
ADL5375-05
ADL5375-15
Max Unit
Parameter
Conditions
Min Typ Max Min Typ
LO INPUTS
LO Drive Level
Input Return Loss
Characterization performed at typical level
−6
0
+6
−6
0
+6
dBm
dB
500 MHz < fLO < 3.3 GHz
See Figure 7 and Figure 32 for return loss vs.
frequency
≤−10
≤−10
BASEBAND INPUTS
I/Q Input Bias Level1
Absolute Voltage Level1
Input Bias Current
Input Offset Current
Differential Input
Impedance
Pin IBBP, Pin IBBN, Pin QBBP, Pin QBBN
500
1500
mV
V
µA
µA
kΩ
On Pin IBBP, Pin IBBN, Pin QBBP, Pin QBBN
Current sourcing from each baseband input
0
1
1
2
41
0.1
60
32
0.1
100
Bandwidth (0.1 dB)
LO = 1900 MHz, baseband input =
500 mV p-p sine wave
95
80
MHz
OUTPUT DISABLE
Off Isolation
Pin DSOP
POUT (DSOP low) − POUT (DSOP high)
DSOP high, LO leakage, LO = 2150 MHz
DSOP high to low (90% of envelope)
DSOP low to high (10% of envelope)
84
85
dB
dBm
ns
ns
V
−55
220
100
−53
220
100
Turn-On Settling Time
Turn-Off Settling Time
DSOP High Level (Logic 1)
DSOP Low Level (Logic 0)
POWER SUPPLIES
2.0
2.0
0.8
0.8
V
Pin VPS1 and Pin VPS2
Voltage
4.75
5.25 4.75
5.25
V
Supply Current
DSOP = low
DSOP = high
194
126
203
127
mA
mA
1 The input bias level can vary as long as the voltages on the individual IBBP, IBBN, QBBP, and QBBN pins remain within the specified absolute voltage level.
Rev. C | Page 6 of 36
Data Sheet
ADL5375
ABSOLUTE MAXIMUM RATINGS
Table 2.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Parameter
Rating
Supply Voltage, VPOS
IBBP, IBBN, QBBP, QBBN
LOIP and LOIN
5.5 V
0 V to 2 V
13 dBm
Internal Power Dissipation
ADL5375-05
1500 mW
ADL5375-15
1200 mW
54°C/W
150°C
−40°C to +85°C
−65°C to +150°C
ESD CAUTION
θJA (Exposed Paddle Soldered Down)1
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
1 Per JDEC standard JESD 51-2. For information on optimizing thermal
impedance, see the Thermal Grounding and Evaluation Board
Layout section.
Rev. C | Page 7 of 36
ADL5375
Data Sheet
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
DSOP 1
COMM 2
LOIP 3
LOIN 4
COMM 5
NC 6
18 VPS1
17 COMM
16 RFOUT
15 NC
14 COMM
13 NC
ADL5375
TOP VIEW
(Not to Scale)
NOTES
1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN.
2. CONNECT TO THE GROUND LANE VIA A LOW
IMPEDANCE PATH.
Figure 2. Pin Configuration
Table 3. Pin Function Descriptions
Pin No.
Mnemonic
Description
1
DSOP
Output Disable. A logic high on this pin disables the RF output. Connect this pin to ground or leave it
floating to enable the output.
2, 5, 8, 11, 12,
COMM
Input Common Pins. Connect to the ground plane via a low impedance path.
14, 17, 19, 20, 23
3, 4
LOIP, LOIN
Local Oscillator Inputs.
Single-ended operation: The LOIP pin is driven from the LO source through an ac-coupling capacitor
while the LOIN pin is ac-coupled to ground through a capacitor.
Differential operation: The LOIP and LOIN pins must be driven differentially through ac-coupling
capacitors in this mode of operation.
6, 7, 13, 15,
9, 10, 21, 22
NC
No Connect. These pins can be left open or tied to ground.
QBBN, QBBP,
IBBP, IBBN
Differential In-Phase and Quadrature Baseband Inputs. These high impedance inputs should be dc-
biased to the recommended level depending on the version.
ADL5375-05: 500 mV
ADL5375-15: 1500 mV
These inputs should be driven from a low impedance source. Nominal characterized ac signal swing is
500 mV p-p on each pin. This results in a differential drive of 1 V p-p. These inputs are not self-biased
and have to be externally biased.
16
RFOUT
RF Output. Single-ended, 50 Ω internally biased RF output. RFOUT must be ac-coupled to the load.
18, 24
VPS1, VPS2
Positive Supply Voltage Pins. All pins should be connected to the same supply (VS). To ensure adequate
external bypassing, connect 0.1 µF and 100 pF capacitors between each pin and ground.
EP
Exposed Paddle. Connect to the ground plane via a low impedance path.
Rev. C | Page 8 of 36
Data Sheet
ADL5375
TYPICAL PERFORMANCE CHARACTERISTICS
ADL5375-05
VS = 5 V; TA = 25°C; LO = 0 dBm single-ended drive; baseband I/Q amplitude = 1 V p-p differential sine waves in quadrature with a
500 mV dc bias; baseband I/Q frequency (fBB) = 1 MHz, unless otherwise noted.
12
10
8
5
4
V
= 5.25V
V
S
= 5.0V
S
3
T
= –40°C
T
= +25°C
A
2
A
V
= 4.75V
S
1
6
0
–1
–2
–3
–4
–5
T
= +85°C
A
4
2
0
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 6. SSB Output 1dB Compression Point (OP1dB) vs. LO Frequency (fLO
)
Figure 3. Single-Sideband (SSB) Output Power (POUT) vs.
LO Frequency (fLO) and Temperature
and Supply
90
5
60
120
4
3
1
2
400MHz
150
30
2
25.73 – j8.14Ω
V
= 5.25V
S
3
4
S11
6GHz
75.88 – j76.94Ω
1
400MHz
1
0
0
180
3
4
S22
400MHz
40.01 + j9.20Ω
400MHz
V
= 5.0V
S
–1
–2
–3
–4
–5
2
V
= 4.75V
S22
6GHz
30.52 – j30.09Ω
S
210
330
6GHz
300
6GHz
S11
S22
240
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
270
Figure 7. Smith Chart of LOIP (LOIN AC-Coupled to Ground) S11 and RFOUT
S22 from 450 MHz to 6000 MHz
Figure 4. Single-Sideband (SSB) Output Power (POUT) vs.
LO Frequency (fLO) and Supply
14
0
LOIP
12
10
8
–5
T
= –40°C
A
–10
T
= +85°C
T
= +25°C
A
A
–15
6
RFOUT
–20
–25
–30
4
2
0
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
FREQUENCY (GHz)
Figure 5. SSB Output 1dB Compression Point (OP1dB) vs. LO Frequency (fLO
)
Figure 8. Return Loss of LOIP (LOIN AC-Coupled to Ground) S11 and RFOUT
S22 from 450 MHz to 6000 MHz
and Temperature
Rev. C | Page 9 of 36
ADL5375
Data Sheet
0
–5
0
–10
–20
–30
–40
–50
–60
–70
–80
–10
–15
–20
–25
–30
–35
–40
–45
–50
–55
–60
T
= +25°C
= –40°C
A
T
= +85°C
A
T
= +25°C
A
T
= +85°C
A
T
A
T
= –40°C
A
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 9. Carrier Feedthrough vs. LO Frequency (fLO) and Temperature;
Multiple Devices Shown
Figure 12. Sideband Suppression vs. LO Frequency (fLO) and Temperature After
Nulling at 25°C; Multiple Devices Shown
0
–10
–20
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
10
5
SSB OUTPUT
POWER (dBm)
CARRIER
FEEDTHROUGH (dBm)
T
= +85°C
A
–30
–40
–50
–60
–70
–80
0
–5
–10
–15
T
A
= –40°C
= +25°C
SIDEBAND
T
A
SUPPRESSION (dBc)
SECOND-ORDER
DISTORTION (dBc)
THIRD-ORDER
DISTORTION (dBc)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0.1
1
2
BASEBAND INPUT VOLTAGE (V p-p)
Figure 10. Carrier Feedthrough vs. LO Frequency (fLO) and Temperature After
Nulling at 25°C; Multiple Devices Shown
Figure 13. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. Baseband Differential Input Level
(fLO = 900 MHz)
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
10
0
–10
–20
SSB OUTPUT
POWER (dBm)
CARRIER
FEEDTHROUGH (dBm)
5
T
= +85°C
A
0
–30
–40
–50
–60
–70
–80
–5
–10
–15
SIDEBAND
SUPPRESSION (dBc)
SECOND-ORDER
DISTORTION (dBc)
T
= –40°C
A
THIRD-ORDER
DISTORTION (dBc)
T
= +25°C
A
0.1
1
2
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
BASEBAND INPUT VOLTAGE (V p-p)
Figure 14. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. Baseband Differential Input Level
(fLO = 2150 MHz)
Figure 11. Sideband Suppression vs. LO Frequency (fLO) and Temperature;
Multiple Devices Shown
Rev. C | Page 10 of 36
Data Sheet
ADL5375
30
25
20
15
10
5
0
10
5
SSB OUTPUT
POWER (dBm)
–10
CARRIER
FEEDTHROUGH (dBm)
–20
–30
–40
–50
–60
–70
–80
–90
–100
T
= –40°C
A
0
T
= +25°C
A
–5
–10
–15
T
= +85°C
A
SIDEBAND
SUPPRESSION (dBc)
SECOND-ORDER
DISTORTION (dBc)
THIRD-ORDER
DISTORTION (dBc)
0
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0.1
1
BASEBAND INPUT VOLTAGE (V p-p)
2
Figure 18. OIP3 vs. LO Frequency (fLO) and Temperature (POUT ≈ −5 dBm)
Figure 15. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. Baseband Differential Input Level
(fLO = 3500 MHz)
80
70
60
–10
–20
–30
T
= –40°C
A
50
40
30
20
10
0
T
= +85°C
–40
–50
–60
–70
–80
A
T
= –40°C
A
THIRD-ORDER
T
= +25°C
A
T
= +85°C
A
SECOND-ORDER
T
= +25°C
A
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 19. OIP2 vs. LO Frequency (fLO) and Temperature (POUT ≈ −5 dBm)
Figure 16. Second- and Third-Order Distortion vs. LO Frequency (fLO) and
Temperature (Baseband I/Q Amplitude = 1 V p-p Differential)
–20
–30
–40
–50
–60
–70
–80
2
–20
–30
–40
–50
–60
–70
1.5
SSB OUTPUT
POWER (dBm)
SSB OUTPUT POWER (dBm)
1
0.5
CARRIER
FEEDTHROUGH (dBm)
CARRIER
FEEDTHROUGH (dBm)
0
–0.5
–1.5
–2.5
–3.5
–1
–2
–3
–4
SIDEBAND
SUPPRESSION (dBc)
THIRD-ORDER
SIDEBAND
SUPPRESSION (dBc)
DISTORTION (dBc)
SECOND-ORDER
DISTORTION (dBc)
SECOND-ORDER
DISTORTION (dBc)
–6
–4
–2
0
2
4
6
1
10
BASEBAND FREQUENCY (MHz)
100
LO AMPLITUDE (dBm)
Figure 20. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. LO Amplitude (fLO = 900 MHz)
Figure 17. Second-Order Distortion, Carrier Feedthrough, Sideband
Suppression, and SSB POUT vs. Baseband Frequency (fBB); fLO = 2140 MHz
Rev. C | Page 11 of 36
ADL5375
Data Sheet
–20
–30
–40
2
18
16
14
12
10
8
SSB OUTPUT
POWER (dBm)
1
0
CARRIER
FEEDTHROUGH (dBm)
–50
–60
–70
–80
–1
–2
–3
–4
SIDEBAND
SUPPRESSION (dBc)
6
THIRD-ORDER
DISTORTION (dBc)
4
2
SECOND-ORDER
DISTORTION (dBc)
0
–6
–4
–2
0
2
4
6
–160.5 –160.3 –160.1 –159.9 –159.7 –159.5 –159.3 –159.1
NOISE (dBm/Hz)
LO AMPLITUDE (dBm)
Figure 24. 20 MHz Offset Noise Floor Distribution at fLO = 900 MHz
(I/Q Amplitude = 0 mV p-p with 500 mV DC Bias)
Figure 21. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. LO Amplitude (fLO = 2150 MHz)
–10
–20
–30
–40
–50
–60
–70
1
8
7
6
5
4
3
2
1
0
0
CARRIER
SSB OUTPUT
POWER (dBm)
FEEDTHROUGH (dBm)
–1
–2
–3
–4
–5
SIDEBAND
SUPPRESSION (dBc)
THIRD-ORDER
DISTORTION (dBc)
SECOND-ORDER
DISTORTION (dBc)
–6
–4
–2
0
2
4
6
–160.5
–160.1
–159.7
–159.3
–158.9
–158.5
LO AMPLITUDE (dBm)
NOISE (dBm/Hz)
Figure 22. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. LO Amplitude (fLO = 3500 MHz)
Figure 25. 20 MHz Offset Noise Floor Distribution at fLO = 2140 MHz
(I/Q Amplitude = 0 mV p-p with 500 mV DC Bias)
210
10
9
8
7
6
5
4
3
2
1
0
V
= 5.25V
= 5.0V
S
205
200
195
190
185
180
175
170
165
V
S
V
= 4.75V
S
–158.9
–158.5
–158.1
–157.7
–157.3
–156.9
–156.5
–40
25
TEMPERATURE (°C)
85
NOISE (dBm/Hz)
Figure 26. 20 MHz Offset Noise Floor Distribution at fLO = 3500 MHz
(I/Q Amplitude = 0 mV p-p with 500 mV DC Bias)
Figure 23. Power Supply Current vs. Temperature
Rev. C | Page 12 of 36
Data Sheet
ADL5375
0
86
88
85
83
82
81
80
79
78
–10
–20
–30
–40
–50
–60
–70
–80
SSB OUTPUT POWER ISOLATION (dB)
CARRIER FEEDTHROUGH (dBm)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 27. SSB POUT Isolation and Carrier Feedthrough with DSOP High
Rev. C | Page 13 of 36
ADL5375
Data Sheet
ADL5375-15
VS = 5 V; TA = 25°C; LO = 0 dBm single-ended drive; baseband I/Q amplitude = 1 V p-p differential sine waves in quadrature with a
1500 mV dc bias; baseband I/Q frequency (fBB) = 1 MHz, unless otherwise noted.
5
12
10
8
4
V
= 5.25V
S
V
= 5.0V
S
3
2
T
= +25°C
T
= –40°C
A
A
V
= 4.75V
S
1
0
6
T
= +85°C
A
–1
–2
–3
–4
–5
4
2
0
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 28. Single-Sideband (SSB) Output Power (POUT) vs. LO Frequency (fLO
)
Figure 31. SSB Output 1dB Compression Point (OP1dB) vs. LO Frequency (fLO
)
and Temperature
and Supply
90
5
4
3
2
60
120
S11
1
2
150
30
400MHz
25.07 – j7.11Ω
400MHz
V
= 4.75V
S
3
1
0
V = 5.0V
S
S11
6GHz
96.98 – j74.75Ω
0
180
1
400MHz
3
4
S22
–1
–2
–3
–4
–5
400MHz
6GHz
2
38.63 + j10.34Ω
V
= 5.25V
S
4
S22
6GHz
34.35 – j30.63Ω
210
6GHz
330
S11
S22
240
300
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
270
Figure 29. Single-Sideband (SSB) Output Power (POUT) vs. LO Frequency
(fLO) and Supply
Figure 32. Smith Chart of LOIP (LOIN AC-Coupled to Ground) S11 and RFOUT
S22 from 450 MHz to 6000 MHz
12
0
T
= –40°C
A
10
8
–5
T
= +25°C
A
LOIP
–10
T
= +85°C
A
6
–15
RFOUT
4
–20
–25
–30
2
0
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
FREQUENCY (GHz)
Figure 30. SSB Output 1dB Compression Point (OP1dB) vs. LO Frequency (fLO
)
Figure 33. Return Loss of LOIP (LOIN AC-Coupled to Ground) S11 and RFOUT
S22 from 450 MHz to 6000 MHz
and Temperature
Rev. C | Page 14 of 36
Data Sheet
ADL5375
0
–5
0
–10
–20
–30
–40
–50
–60
–70
–80
–10
–15
–20
–25
–30
–35
–40
–45
–50
–55
–60
T
= +85°C
A
T
= +85°C
A
T
= –40°C
A
T
= –40°C
A
T
= +25°C
A
T
= +25°C
A
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 34. Carrier Feedthrough vs. LO Frequency (fLO) and Temperature;
Multiple Devices Shown
Figure 37. Sideband Suppression vs. LO Frequency (fLO) and Temperature After
Nulling at 25°C; Multiple Devices Shown
0
–10
–20
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
10
5
SSB OUTPUT
POWER (dBm)
CARRIER
FEEDTHROUGH (dBm)
SIDEBAND
SUPPRESSION (dBc)
–30
–40
–50
–60
–70
–80
T
= –40°C
A
0
–5
–10
–15
T
= +85°C
A
T
= +25°C
SECOND-ORDER
A
DISTORTION (dBc)
THIRD-ORDER
DISTORTION (dBc)
0.1
1
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
BASEBAND INPUT VOLTAGE (V p-p)
Figure 38. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. Baseband Differential Input Level
(fLO = 900 MHz)
Figure 35. Carrier Feedthrough vs. LO Frequency (fLO) and Temperature After
Nulling at 25°C; Multiple Devices Shown
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
10
5
0
–10
–20
–30
SSB OUTPUT
POWER (dBm)
CARRIER
FEEDTHROUGH (dBm)
0
SIDEBAND
SUPPRESSION (dBc)
T
= +25°C
T
= –40°C
A
A
–40
–50
–60
–70
–80
–5
–10
–15
T
= +85°C
A
SECOND-ORDER
DISTORTION (dBc)
THIRD-ORDER
DISTORTION (dBc)
0.1
1
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
BASEBAND INPUT VOLTAGE (V p-p)
Figure 39. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. Baseband Differential Input Level
(fLO = 2150 MHz)
Figure 36. Sideband Suppression vs. LO Frequency (fLO) and Temperature;
Multiple Devices Shown
Rev. C | Page 15 of 36
ADL5375
Data Sheet
0
10
5
30
28
26
24
22
20
18
16
14
12
10
8
SSB OUTPUT
POWER (dBm)
–10
CARRIER
FEEDTHROUGH (dBm)
–20
–30
–40
–50
–60
–70
–80
–90
–100
T
= –40°C
A
0
SIDEBAND
SUPPRESSION (dBc)
–5
–10
–15
T
= +25°C
A
SECOND-ORDER
DISTORTION (dBc)
T
= +85°C
A
6
THIRD-ORDER
DISTORTION (dBc)
4
2
0
0.1
1
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
BASEBAND INPUT VOLTAGE (V p-p)
Figure 40. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. Baseband Differential Input Level
(fLO = 3500 MHz)
Figure 43. OIP3 vs. LO Frequency (fLO) and Temperature (POUT ≈ −5 dBm @
LO = 900 MHz)
f
0
–10
–20
70
60
50
40
30
20
10
0
T
= –40°C
A
–30
THIRD-ORDER
–40
T
= +25°C
A
T
= +25°C
A
–50
–60
–70
–80
T
= +85°C
A
T
= +85°C
A
T
= –40°C
A
SECOND-ORDER
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 44. OIP2 vs. LO Frequency (fLO) and Temperature (POUT ≈ −5 dBm @
Figure 41. Second- and Third-Order Distortion vs. LO Frequency (fLO) and
Temperature (Baseband I/Q Amplitude = 1 V p-p Differential)
f
LO = 900 MHz)
–20
–30
–40
–50
–60
–70
–80
–90
2
–20
–30
–40
–50
–60
–70
1.5
SSB OUTPUT POWER (dBm)
CARRIER
FEEDTHROUGH (dBm)
SSB OUTPUT
POWER (dBm)
0.5
1
SIDEBAND
SUPPRESSION (dBc)
–0.5
–1.5
–2.5
–3.5
0
SIDEBAND
SUPPRESSION (dBc)
THIRD-ORDER
DISTORTION (dBc)
CARRIER
FEEDTHROUGH (dBm)
–1
–2
SECOND-ORDER
SECOND-ORDER
DISTORTION (dBc)
DISTORTION (dBc)
–6 –4 –2
0
2
4
6
1
10
100
LO AMPLITUDE (dBm)
BASEBAND FREQUENCY (MHz)
Figure 45. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. LO Amplitude (fLO = 900 MHz)
Figure 42. Second-Order Distortion, Carrier Feedthrough, Sideband
Suppression, and SSB POUT vs. Baseband Frequency (fBB); fLO = 2140 MHz
Rev. C | Page 16 of 36
Data Sheet
ADL5375
18
16
14
12
10
8
–20
2
CARRIER
FEEDTHROUGH (dBm)
SSB OUTPUT
POWER (dBm)
–30
–40
–50
–60
–70
–80
1
SIDEBAND
SUPPRESSION (dBc)
0
THIRD-ORDER
DISTORTION (dBc)
6
–1
–2
4
2
SECOND-ORDER
DISTORTION (dBc)
0
–158.0 –157.8 –157.6 –157.4 –157.2 –157.0 –156.8 –156.6
–6
–4
–2
0
2
4
6
NOISE (dBm/Hz)
LO AMPLITUDE (dBm)
Figure 49. 20 MHz Offset Noise Floor Distribution at fLO = 900 MHz
(I/Q Amplitude = 0 mV p-p with 1500 mV DC Bias)
Figure 46. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. LO Amplitude (fLO = 2150 MHz)
–20
–30
–40
–50
–60
–70
–80
2.0
12
10
8
CARRIER
FEEDTHROUGH (dBm)
1.5
SSB OUTPUT
POWER (dBm)
1.0
SIDEBAND
SUPPRESSION (dBc)
0.5
0
6
–0.5
–1.0
–1.5
–2.0
4
THIRD-ORDER
DISTORTION (dBc)
SECOND-ORDER
DISTORTION (dBc)
2
0
–6
–4
–2
0
2
4
6
–158.5 –158.3 –158.1 –157.9 –157.7 –157.5 –157.3 –157.1
LO AMPLITUDE (dBm)
NOISE (dBm/Hz)
Figure 47. Second- and Third-Order Distortion, Carrier Feedthrough,
Sideband Suppression, and SSB POUT vs. LO Amplitude (fLO = 3500 MHz)
Figure 50. 20 MHz Offset Noise Floor Distribution at fLO = 2140 MHz
(I/Q Amplitude = 0 mV p-p with 1500 mV DC Bias)
0.230
0.220
9
8
7
6
5
4
3
2
1
0
V
= 5.25V
= 5.0V
S
0.210
0.200
0.190
0.180
0.170
0.160
V
S
V
= 4.75V
S
–40
25
85
–157.5
–157.1
–156.7
–156.3
–155.9
–155.5
TEMPERATURE (°C)
NOISE (dBm/Hz)
Figure 48. Power Supply Current vs. Temperature
Figure 51. 20 MHz Offset Noise Floor Distribution at fLO = 3500 MHz
(I/Q Amplitude = 0 mV p-p with 500 mV DC Bias)
Rev. C | Page 17 of 36
ADL5375
Data Sheet
0
88
86
84
82
80
78
76
74
–10
–20
–30
–40
–50
–60
–70
–80
–90
SSB OUTPUT POWER ISOLATION (dB)
CARRIER FEEDTHROUGH (dBm)
0
0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0
LO FREQUENCY (GHz)
Figure 52. SSB POUT Isolation and Carrier Feedthrough with DSOP High
Rev. C | Page 18 of 36
Data Sheet
ADL5375
THEORY OF OPERATION
V-to-I Converter
CIRCUIT DESCRIPTION
The differential baseband inputs (QBBP, QBBN, IBBN, and
IBBP) present a high impedance. The voltages applied to these
pins drive the V-to-I stage that converts baseband voltages into
currents. The differential output currents of the V-to-I stages
feed each of their respective mixers. The dc common-mode
voltage at the baseband inputs sets the currents in the two
mixer cores. Varying the baseband common-mode voltage
influences the current in the mixer and affects overall modula-
tor performance. The recommended dc voltage for the baseband
common-mode voltage is 500 mV dc for the ADL5375-05 and
1500 mV for the ADL5375-15.
The ADL5375 can be divided into five circuit blocks: the LO
interface, the baseband voltage-to-current (V-to-I) converter,
the mixers, the differential-to-single-ended (D-to-S) stage,
and the bias circuit. A block diagram of the device is shown in
Figure 53.
LOIP
PHASE
SPLITTER
LOIN
IBBP
IBBN
Mixers
Σ
RFOUT
DSOP
The ADL5375 has two double-balanced mixers: one for the
in-phase channel (I channel) and one for the quadrature chan-
nel (Q-channel). The output currents from the two mixers sum
together into an internal load. The signal developed across this
load is used to drive the D-to-S stage.
QBBP
QBBN
Figure 53. Block Diagram
The LO interface generates two LO signals in quadrature.
These signals are used to drive the mixers. The I/Q baseband
input signals are converted to currents by the V-to-I stages,
which then drive the two mixers. The outputs of these mixers
combine to feed the output balun, which provides a single-
ended output. The bias cell generates reference currents for
the V-to-I stage.
D-to-S Stage
The output D-to-S stage consists of an on-chip active balun
that converts the differential signal to a single-ended signal.
The balun presents 50 Ω impedance to the output (VOUT).
Therefore, no matching network is needed at the RF output
for optimal power transfer in a 50 Ω environment.
LO Interface
Bias Circuit
The LO interface consists of a polyphase quadrature splitter
and a limiting amplifier. The LO input impedance is set by
the polyphase splitter. Each quadrature LO signal then passes
through a limiting amplifier that provides the mixer with a
limited drive signal.
An on-chip band gap reference circuit is used to generate a
proportional-to-absolute temperature (PTAT) reference current
for the V-to-I stage.
DSOP
The DSOP pin can be used to disable the output stage of the
modulator. If the DSOP pin is connected to ground or left
unconnected, the part operates normally. If the DSOP pin is
connected to the positive voltage supply, the output stage is
disabled and the LO leakage is also reduced.
The LO input can be driven single-ended or differentially.
For applications above 3 GHz, improved OIP2 and LO leakage
may result from driving the LO input differentially.
Rev. C | Page 19 of 36
ADL5375
Data Sheet
BASIC CONNECTIONS
IBBN
IBBP
VPOS
VPOS
S1
C5
0.1µF
C3
100pF
A
B
VPOS
C2
100pF
C4
0.1µF
DSOP
VPS1
1
2
3
4
5
6
18
17
16
15
14
13
C6
100pF
COMM
COMM
LOIP
Z1
RFOUT
ADL5375
LOIP
RFOUT
LOIN
C1
100pF
NC
COMM
C7
100pF
COMM
EXPOSED PADDLE
NC
NC
GND
QBBN
QBBP
Figure 54. Basic Connections for the ADL5375
Figure 54 shows the basic connections for the ADL5375.
All the baseband inputs must be externally dc biased. The
recommended common-mode level is dependent on the
version of the ADL5375.
POWER SUPPLY AND GROUNDING
Pin VPS1 and Pin VPS2 should be connected to the same 5 V
source. Each pin should be decoupled with a 100 pF and
0.1 μF capacitor. These capacitors should be located as close
as possible to the device. The power supply can range between
4.75 V and 5.25 V.
ADL5375-05: 500 mV
ADL5375-15: 1500 mV
LO INPUT
The LO input is designed to be driven from a single-ended
source. The LO source is ac-coupled through a series capacitor
to the LOIP pin while the LOIN pin is ac-coupled to ground
through a second capacitor.
The ten COMM pins should be tied to the same ground plane
through low impedance paths.
The exposed paddle on the underside of the package should
also be soldered to a ground plane with low thermal and
electrical impedance. If the ground plane spans multiple layers
on the circuit board, they should be stitched together with nine
vias under the exposed paddle as illustrated in the Evaluation
Board section. The AN-772 Application Note discusses the
thermal and electrical grounding of the LFCSP (QFN) package
in detail.
The typical LO drive level, which was used for the characterization
of the ADL5375, is 0 dBm.
Differential operation is also possible, in which case both sides
of the differential LO source should be ac-coupled through a
pair of series capacitors to the LOIP and LOIN pins.
RF OUTPUT
BASEBAND INPUTS
The RF output is available at the RFOUT pin (Pin 16), which can
drive a 50 Ω load. The internal balun provides a low dc path to
ground. In most situations, the RFOUT pin must be ac-coupled
to the load.
The baseband inputs (IBBP, IBBN, QBBP, and QBBN) should be
driven from a differential source. The nominal drive level used
in the characterization of the ADL5375 is 1 V p-p differential
(or 500 mV p-p on each pin).
Rev. C | Page 20 of 36
Data Sheet
ADL5375
to just above the KT thermal noise level. Asserting DSOP also
reduces the supply current of the ADL5375 from 200 mA to
127 mA.
OUTPUT DISABLE
The ADL5375 incorporates an output disable pin feature that
shuts down the output amplifier stage to isolate the modulator
from the load. This output is disabled when the voltage on the
DSOP exceeds 2 V. The output is enabled when the DSOP pin is
either tied to ground or left unconnected.
The time delay between when DSOP pin going low and the
output power being restored is approximately 200 ns. The time
delay when DSOP going high and output being disabled is less
than 100 ns.
Asserting DSOP further reduces LO leakage (see Figure 27 and
Figure 52) and drives the broadband noise of the device down
Rev. C | Page 21 of 36
ADL5375
Data Sheet
IN inputs can be slightly different. Using Figure 55 as an
example, after LO leakage nulling, the average dc level on IP
and IN can be 500.25 mV and 499.75 mV.
APPLICATIONS INFORMATION
CARRIER FEEDTHROUGH NULLING
LO leakage results from minute dc offsets that occur on the
differential baseband inputs. In an IQ modulator, non-zero
differential offsets mix with the LO and result in LO leakage to
the RF output. In addition to this effect, some of the signal
power at the LO input couples directly to the RF output (this
may be a result of bond-wire to bond-wire coupling or coupling
through the silicon substrate). The net LO leakage at the RF
output is the vector combination of the signals that appear at
the output as a result of these two effects.
The same applies to the Q-channel. For the ADL5375-15, the
same theory applies except that
V
IBBP = VIBBN = 1500 mV.
It is often desirable to perform a one-time carrier null. This is
usually performed at a given frequency. After this factory
calibration, the IQ modulator operates over a frequency range
on each side of the calibration frequency. The nulled LO leakage
level degrades somewhat because the LO frequency is moved
away from the calibration frequency. Despite this degradation,
the overall LO leakage across a frequency band can be expected
to be better than when no nulling is performed. This assumes
an operating frequency band that is in the 30 MHz to 60 MHz
range.
The device’s nominal carrier feedthrough can be nulled by
adding small external differential offset voltages on the I and Q
inputs.
Nulling the carrier feedthrough is a multistep process. Initially,
with the I-channel offset held constant (at 0 mV), the Q-
channel offset is varied until a minimum LO leakage level is
obtained. This Q-channel offset voltage is then held constant,
while the offset on the I-channel is adjusted until a new
minimum is reached. Through two iterations of this process,
the LO leakage can be reduced to an arbitrarily low level. This
level is only limited by the available offset voltage steps and by
the modulator’s noise floor. Figure 55 illustrates the typical
relationship between LO leakage and dc offset at 1900 MHz. In
this case, differential offset voltages of approximately +0.5 mV
and −0.5 mV on the I and Q inputs, respectively, result in the
lowest carrier feedthrough. It is important to note that the
required offset nulling voltage changes in polarity and
magnitude from device to device and overtemperature and
frequency. To ensure that all devices in a mass production
environment can be adequately nulled, an offset adjustment
range of approximately 10 mV should be provided.
–57
LO leakage nulling is discussed further in AN-1039, Correcting
Imperfections in IQ Modulators to Improve RF Signal Fidelity.
SIDEBAND SUPPRESSION OPTIMIZATION
Sideband suppression results from relative gain and relative
phase offsets between the I-channel and Q-channel and can
be suppressed through adjustments to those two parameters.
Figure 56 illustrates how sideband suppression is affected by
the gain and phase imbalances.
0
–10
2.5dB
–20
1.25dB
0.5dB
–30
–40
–50
–60
–70
–80
0.25dB
0.125dB
0.05dB
0.025dB
0.0125dB
Q OFFSET SWEEP
I OFFSET SWEEP
0dB
–62
–67
–72
–77
–82
–87
–92
–90
0.01
0.1
1
10
100
PHASE ERROR (Degrees)
Figure 56. Sideband Suppression vs. Quadrature Phase Error for
Various Quadrature Amplitude Offsets
Figure 56 underlines the fact that adjusting only one parameter
improves the sideband suppression only to a point, unless the
other parameter is also adjusted. For example, if the amplitude
offset is 0.25 dB, improving the phase imbalance by better than
1° does not yield any improvement in the sideband suppression.
For optimum sideband suppression, an iterative adjustment
between phase and amplitude is required.
–1.0 –0.8 –0.6 –0.4 –0.2
0
0.2
0.4
0.6
0.8
1.0
I AND Q OFFSET VOLTAGE (µV)
Figure 55. Example of Typical Carrier Feedthrough vs. DC Offset Voltage
The sideband suppression nulling can be performed either
through adjusting the gain for each channel or through the
modification of the phase and gain of the digital data coming
from the baseband signal processor.
It is important to note that the carrier feedthrough is not
affected by the dc bias levels (also called the common-mode
level) on the I and Q inputs. A differential offset voltage must
be applied, so after nulling, the average voltage on the IP and
Rev. C | Page 22 of 36
Data Sheet
ADL5375
Sideband suppression is discussed further in AN-1100, Wireless
Transmitter IQ Balance and Sideband Suppression, as well as in
AN-1039, Correcting Imperfections in IQ Modulators to Improve
RF Signal Fidelity.
of Figure 57. Because filtering of the third harmonic is most
critical, and to ensure wide frequency range coverage, the 3 dB
corner of the filters have been set to approximately 1.2~1.5
times the maximum desired LO frequency. A Chebyshev filter
topology at 100 Ω differential source impedance and 50 Ω
differential load impedance was used for optimal performance.
3.3V
INTERFACING THE ADF4350 PLL TO THE ADL5375
With an output frequency range of 137.5 to 4.4 GHz, a high
performance integrated VCO and an LO output power level
that can be programmed from −4 dBm to +5 dBm, the
ADF4350 wideband synthesizer is ideally suited to drive the
ADL5375 LO port.
120pF
120pF
0.1µF
C1a
L1
C2a
L2
C3a
1nF
Z
BIAS
12
13
3
4
LOIP
RF
RF
A+
Care must be taken to adequately suppress the harmonics of the
LO signal from the PLL. VCOs typically have a third harmonic
power of approximately −10 dBc. A large third harmonic on the
LO degrades the quality of the quadrature generation inside the
IQ Modulator. The third harmonic should be suppressed to a
level of –30 dBc or lower to prevent quadrature degradation. So
approximately 20 dB of attenuation is required to get the third
harmonic below −30 dBc. Figure 57 shows PLL modulator
OUT
R1
BIAS
C1c
L1
C2c
L2
C3c
1nF
Z
A–
OUT
LOIN
C1a
C2a
C3a
ADF4350
ADL5375
Figure 57. PLL-Modulator Interface Schematic
interfaces schematic that for this operation at four different
frequencies, and Table 4 shows the optimized components value
Table 4. PLL Modulator Interface Components Values (DNI = Do Not Insert)
Frequency Range (MHz)
Zbias (nH) R1 (Ω) L1 (nH) L2 (nH) C1a (pF) C1c (pF) C2a C2c (pF) C3a (pF) C3c (pF)
500 to 1300
850 to 2450
1250 to 2800
2800 to 4400
27
19
7.5
3.9
100
100
100
100
3.9
2.7
0 Ω
0 Ω
3.9
2.7
3.6
0 Ω
DNI
3.3
DNI
DNI
4.7
DNI 5.6
DNI
3.3
1.5
3.3
DNI
DNI
DNI
4.7
2.2
DNI
DNI
DNI
DNI
DNI
DNI DNI
DNI
Rev. C | Page 23 of 36
ADL5375
Data Sheet
The two pull-up inductors of the Zbias provide two 50 Ω source
impedances in combination with R1 resistor in parallel for the
filter. While the ADL5375 is specified to be driven by a single-
ended LO, the LOIP and LOIN input pins are naturally
differential. Therefore, the differential LO drive from the
ADF4350 is more desirable.
AD9122
ADL5375-05
67
21
IOUT1P
IBBP
RBIP
50Ω
RBIN
50Ω
66
59
22
9
IOUT1N
IOUT2N
IBBN
The output power from the ADF4350 can be set to −4 dBm,
−1 dBm,+2 dBm, and +5 dBm using Register 4 Bits[D2:D1] and
−6 dBm to +7 dBm LO drive level for ADL5375 is recommended.
QBBN
RBQN
50Ω
If the physical distance between the PLL and the IQ modulator
is significant, the filter should be placed adjacent to the IQ
modulator, and two 50 Ω traces should be run between the
devices (since there is a 50 Ω impedance looking from each of
the filter inputs back to each of the PLL outputs).
RBQP
58
10
50Ω
IOUT2
QBBP
Figure 58. Interface Between the AD9122 and ADL5375-05 with 50 Ω
Resistors to Ground to Establish the 500 mV DC Bias for the ADL5375-05
Baseband Inputs
The ADL5375 evaluation board can be reconfigured for
differential drive and also includes component pads in its LO
path to accommodate a harmonic filter. The ADF4350 evaluation
board can also be configured to provide a differential output and
can be connected directly to the ADL5375 evaluation board.
The AD9122 output currents have a swing that ranges from 0 mA
to 20 mA. With the 50 Ω resistors in place, the ac voltage swing
going into the ADL5375-05 baseband inputs ranges from 0 V to
1 V. A full-scale sine wave out of the AD9122 can be described
as a 1 V p-p single-ended (or 2 V p-p differential) sine wave
with a 500 mV dc bias.
Optimizing the interface between a PLL LO and I/Q modulator
is discussed further in CN-0134 Broadband Low EVM Direct
Conversion Transmitter: How to Optimize the Interface
Between a PLL LO and I/Q Modulator.
Limiting the AC Swing
There are situations in which it is desirable to reduce the ac
voltage swing for a given DAC output current. This can be
achieved through the addition of another resistor to the interface.
This resistor is placed in the shunt between each side of the
differential pair, as shown in Figure 59. It has the effect of
reducing the ac swing without changing the dc bias already
established by the 50 Ω resistors.
DAC MODULATOR INTERFACING
Driving the ADL5375-05 with a TXDAC®
The ADL5375-05 is designed to interface with minimal
components to members of the Analog Devices, Inc. TxDAC
families. These dual-channel differential current output DACs
feature an output current swing from 0 mA to 20 mA. The
interface described in this section can be used with any DAC
that has a similar output.
AD9122
ADL5375-05
67
21
IOUT1P
IBBP
RBIP
An example of an interface using the AD9122 TxDAC is shown
in Figure 58. The baseband inputs of the ADL5375-05 require a
dc bias of 500 m V. The nominal midscale current on each of the
outputs of the AD9122 is 10 mA. Therefore, a single 50 Ω resis-
tor to ground from each of the DAC outputs results in an average
current of 10 mA flowing through each of the resistors, thus
producing the desired 500 mV dc bias for the inputs to the
ADL5375-05.
50Ω
RLI
100Ω
RBIN
50Ω
66
59
22
9
IOUT1N
IOUT2N
IBBN
QBBN
RBQN
50Ω
RLQ
100Ω
RBQP
50Ω
58
10
IOUT2
QBBP
Figure 59. AC Voltage Swing Reduction Through the Introduction
of a Shunt Resistor Between Differential Pair
Rev. C | Page 24 of 36
Data Sheet
ADL5375
0
–10
–20
–30
–40
–50
–60
36
30
24
18
12
6
The value of this ac voltage swing limiting resistor is chosen
based on the desired ac voltage swing. Figure 60 shows the
relationship between the swing-limiting resistor and the peak-
to-peak ac swing that it produces when 50 Ω bias-setting
resistors are used. The differential peak-to-peak swing at the
modulator input is
MAGNITUDE
GROUP DELAY
[
2×RB ×RL
]
VSIGNAL = IFS
×
2×RB + RL
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
100
1
10
FREQUENCY (MHz)
Figure 62. Frequency Response for DAC Modulator Interface with
10 MHz Third-Order Bessel Filter
Complex IF Operation
The ADL5375 can be used with a DAC, generating a complex-
IF (CIF), as well as a zero-IF signal (ZIF). The −1 dB bandwidth
of the ADL5375 is approximately more than 400 MHz
(Figure 63 and Figure 64 show the baseband frequency response
of the ADL5375, facilitating high CIF and providing sufficient
flat bandwidth for digital predistortion (DPD) algorithms).
Using a CIF places the LO leakage and the undesired sideband
outside the signal band at the modulator output where they can
be easily removed with a bandpass filter.
0
10
100
1000
10000
R
(Ω)
L
Figure 60. Relationship Between the AC Swing-Limiting Resistor and the
Peak-to-Peak Voltage Swing with 50 Ω Bias-Setting Resistors
Filtering
It is necessary to place an antialiasing filter between the DAC
and modulator to filter out Nyquist images, common mode
noise, and broadband DAC noise. The interface for setting up
the biasing and ac swing discussed in the Limiting the AC
Swing section lends itself well to the introduction of such a
filter. The filter can be inserted between the dc bias setting
resistors and the ac swing-limiting resistor. With this configuration,
the dc bias setting resistors and the signal scaling resistors
conveniently set the source and load resistances for the filter.
1
0
–1
–2
–3
–4
–5
–6
Figure 61 shows a third-order, Bessel low-pass filter with a 3 dB
frequency of 10 MHz. Matching input and output impedances
make the filter design easier, so the shunt resistor chosen is
100 Ω, producing an ac swing of 1 V p-p differential. The
frequency response of this filter is shown in Figure 62.
1
10
100
1k
BASEBAND FREQUENCY (MHz)
AD9122
IOUT1P
ADL5375-05
LPI
771.1nH
67
21
Figure 63. ADL5375-05 Baseband Frequency Response Normalized to
Response for 1 MHz
IBBP
RBIP
50Ω
53.62pF
C1I
350.1pF
LNI
771.1nH
RSLI
100Ω
C2I
RBIN
50Ω
66
59
22
9
IOUT1N
IOUT2N
IBBN
LNQ
771.1nH
QBBN
RBQN
50Ω
RSLQ
100Ω
53.62pF
C1Q
350.1pF
LPQ
771.1nH
C2Q
RBQP
50Ω
58
10
IOUT2
QBBP
Figure 61. DAC Modulator Interface with
10 MHz Third-Order, Bessel Filter
Rev. C | Page 25 of 36
ADL5375
Data Sheet
0
–5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
1
0
–1
–2
–3
–4
–5
–10
–15
–20
–25
0
1M
10M
FREQUENCY (Hz)
100M
500M
–6
1
10
100
1k
Figure 66. Frequency Response for DAC Modulator Interface with 300 MHz
Fifth-Order Butterworth Filter
BASEBAND FREQUENCY (MHz)
Figure 64. ADL5375-15 Baseband Frequency Response Normalized to
Response for 1 MHz
Driving the ADL5375-15 with a TXDAC
The ADL5375-15 requires a 1500 mV dc bias and therefore
requires a slightly more complex interface that performs a dc
level shift on the baseband signals. It is necessary to level-shift
the DAC output from a 500 mV dc bias to the 1500 mV dc bias
that the ADL5375-15 requires.
In CIF applications, a low-pass filter between the DAC and
modulator is still favored to filter out images, noises discussed
in the Filtering section as well as to preserve dc bias level from
DAC to ADL5375-05. Figure 65 shows a fifth order Butterworth
filter with a 300 MHz corner frequency and the frequency
response of this filter is shown in Figure 66.
Level-shifting can be achieved with either a passive network
or an active circuit. A passive network of resistors is shown
in Figure 67. In this network, the dc bias of the DAC remains at
500 mV while the input to the ADL5375-15 is 1500 mV. It should
be noted that this passive level-shifting network introduces
approximately 2 dB of loss in the ac signal.
Even a purely differential filter can work well, splitting the filter
capacitors into two and grounding at filter topology as like C2
and C4 in Figure 65 divert common mode currents to ground
and result in additional common-mode rejection of high
frequency signals to a purely differential filter.
C2PI
AD9122
ADL5375-15
22pF
C4PI
3pF
RSIN
L2PI
AD9122
IOUT1P
ADL5375-05
1kΩ
67
21
33nH
67
66
21
22
IOUT1P
IBBP
IBBP
L1PI
33nH
RBIP
RLIP
RBIP
50Ω
45.3Ω
3480Ω
C1I
3.6pF
C3I
6pF
RSLI
100Ω
L1NI
33nH
5V
RBIN
50Ω
RBIN
45.3Ω
RLIN
3480Ω
RSIP
1kΩ
IOUT1N
IBBN
66
59
22
9
L2NI
33nH
C2NI
22pF
C4NI
3pF
IOUT1N
IOUT2N
IBBN
RSQN
1kΩ
QBBN
C2NQ
22pF
RBQN
45.3Ω
RLQN
3480Ω
C4NQ
3pF
L2NQ
33nH
5V
59
58
9
IOUT2N
IOUT2
QBBN
QBBP
RSQP
1kΩ
RBQP
45.3Ω
RLQP
3480Ω
L1NQ
33nH
58
10
RBQN
50Ω
IOUT2
QBBP
RSLQ
100Ω
C1Q
3.6pF
C3Q
6pF
L1PQ
33nH
RBQP
50Ω
10
Figure 67. Passive Level-Shifting Network For Biasing ADL5375-15
from TxDAC
L2PQ
33nH
C2PQ
22pF
C4PQ
3pF
The active level shifting circuit involves the use of the ADA4938
dual-differential amplifier. This device has a VOCM pin that
sets the output dc bias. Through this pin, the output common-
mode of the amplifier can be easily set to the requisite 1.5 V for
biasing the ADL5375-15 baseband inputs.
Figure 65. Recommended DAC Modulator Interface Topology with
FC = 300 MHz Fifth-Order, Butterworth Filter
Rev. C | Page 26 of 36
Data Sheet
ADL5375
Using the AD9122 DAC For Carrier Feedthrough and
Unwanted Sideband Nulling
The AD9122 features an auxiliary DACs (Register 0x42,
Register 0x43, Register 0x46, and Register 0x47) or the digital
dc offset adjustments (Register 0x3C through Register 0x3F)
that can be used to null the carrier feedthrough by applying the
dc offset voltage at each main DAC channels. Unwanted
sideband suppression can be done by adjusting the I/Q phase
(Register 0x38 through Register 0x3B) and DAC FS (Register
0x40 and Register 0x44) registers.
GSM/EDGE OPERATION
Figure 69. ADL5375-05 GSM/EDGE(8-PSK) 6 Carriers Adjacent and Alternate
Channel Power Performance at 950 MHz; Output Power(1 Carrier/100 KHz) =
−24.4 dBm LO Drive = 0 dBm
The performance of the ADL5375-05 in a Multi-Carriers
GSM/EDGE environment is shown in Figure 68 and Figure 69.
Figure 68 illustrates the 6 MHz offset noise floor of the
The performance of the ADL5375 in a GSM/EDGE environ-
ment is shown in Figure 70 and Figure 71.
ADL5375-05 at the six carriers MCGSM/EDGE(8-PSK) operating
condition vs. output power, and Figure 69 demonstrates IMD
performance of the same six carriers MCGSM/EDGE(8-PSK)
for the ADL5375-05 at 950 MHz. It is configured, as shown at
Figure 65, for this measurement. The AD9122 is set at −3 dB
digital FS back off, FDATA = 368.64 MSPS, 2× interpolation, and
PLL and inverse sync off. Complex IF at 174.32 MHz is generated
at NCO of the AD9122 and fed into the ADL5375-05 through a
fifth order Butterworth filter. Special care must be taken not to
be affected by the noise power of images through proper DAC
setup at the selection of IF Frequency, FDATA, FDAC, and so on for
such a low IMD and noise level measurement. Be sure to load
clean LO signals and use equipment that allows enough
dynamic range capability and noise correction feature to
compensated the noise originated by equipment itself.
Figure 70 illustrates the 6 MHz offset noise of the ADL5375-05
and ADL5375-15 vs. output power at 940 MHz. Figure 71
demonstrates how the 6 MHz offset noise is affected by variations
in LO drive level for both version of the ADL5375 at 940 MHz.
–99
–100
–101
–102
ADL5375-15
–103
–104
ADL5375-05
–105
–73
–74
–75
–76
–77
–78
–79
–80
–81
–82
–83
–84
–104.0
–104.5
–105.0
–105.5
–106.0
–106.5
–107.0
–107.5
–106
–107
–5
–4
–3
–2
–1
0
OUTPUT POWER (dBm)
Figure 70. GSM/Edge (8-PSK) 6 MHz Offset Noise at 940 MHz vs. Output
Power, LO Drive = 0 dBm
–30
–28
–26
–24
–22
OUTPUT POWER (1 CARRIER/100kHz) (dBm)
Figure 68. ADL5375-05 GSM/EDGE(8-PSK) 6 Carriers 6 MHz Offset Noise Floor
at 950 MHz vs Output Power(1 Carrier/100 KHz), LO Drive = 0 dBm
Rev. C | Page 27 of 36
ADL5375
Data Sheet
–101
–102
–103
–104
–105
–106
–107
–108
–59
–61
–63
–65
–67
–69
–71
–73
–75
–77
–79
–81
–83
–85
–87
ADJACENT CPR
ADL5375-15
ADL5375-05
ALTERNATE CPR
–109
0
–20
–18
–16
–14
–12
–10
–8
–6
–4
1
2
3
4
5
6
7
OUTPUT POWER (dBm)
LO DRIVE (dBm)
Figure 73. ADL5375-15 Single-Carrier W-CDMA Adjacent and Alternate
Channel Power vs. Output Power at 2140 MHz; LO Power = 0 dBm
Figure 71. GSM/Edge (8-PSK) 6 MHz Offset Noise at 940 MHz vs. LO Drive,
Output Power = 0 dBm
Figure 72 and Figure 73 show that both versions of the ADL5375
are able to deliver about or better than −73 dB ACPR at an
output power of −10 dBm.
W-CDMA OPERATION
The ADL5375 is suitable for W-CDMA operation. Figure 72
and Figure 73 show the adjacent and alternate channel power
ratios for the ADL5375-05 and ADL5375-15, respectively, at an
LO frequency of 2140 MHz.
Figure 74 illustrate the sensitivity of the EVM to variations in
LO drive at 2140 MHz for the ADL5375-05 and ADL5375-15.
6.0
5.5
5.0
4.5
–59
–61
–63
–65
–67
–69
–71
–73
–75
–77
–79
–81
–83
–85
–87
ADJACENT CPR
4.0
ADL5375-15
3.5
3.0
ADL5375-05
2.5
2.0
1.5
1.0
0.5
0
ALTERNATE CPR
–6
–4
–2
0
2
4
6
–20
–18
–16
–14
–12
–10
–8
–6
–4
LO DRIVE (dBm)
OUTPUT POWER (dBm)
Figure 74. Single Carrier W-CDMA Composite EVM vs. LO Drive at 2140 MHz;
Output Power = −10 dBm
Figure 72. ADL5375-05 Single-Carrier W-CDMA Adjacent and Alternate
Channel Power vs. Output Power at 2140 MHz; LO Power = 0 dBm
The EVM exhibits improvements with a local feedthrough nulling
operation.
Rev. C | Page 28 of 36
Data Sheet
ADL5375
All DACs listed have nominal bias levels of 0.5 V and use the
same simple DAC modulator interface that is shown in Figure 75.
LO GENERATION USING PLLS
Analog Devices has a line of PLLs that can be used for generating
the LO signal. Table 5 lists the PLLs together with their maximum
frequency and phase noise performance.
MODULATOR/DEMODULATOR OPTIONS
Table 8 lists other Analog Devices modulators and demodulators.
Table 5. Analog Devices PLL Selection
Table 8. Modulator/Demodulator Options
Frequency
Range
(MHz)
Phase Noise @ 1 kHz Offset
Frequency, fIN (MHz) and 200 kHz PFD (dBc/Hz)
Modulator/
Part No. Demodulator
Part
Comments
ADF4110 550
ADF4111 1200
ADF4112 3000
ADF4113 4000
ADF4116 550
ADF4117 1200
ADF4118 3000
−91 @ 540 MHz
−87 @ 900 MHz
−90 @ 900 MHz
−91 @ 900 MHz
−89 @ 540 MHz
−87 @ 900 MHz
−90 @ 900 MHz
AD8345
AD8346
AD8349
Modulator
Modulator
Modulator
140 to 1000
800 to 2500
700 to 2700
20 to 2400
ADL5390 Modulator
External
quadrature
ADL5385 Modulator
ADL5386 Modulator
50 to 2200
50 to 2200
Includes VVA and
AGC
The ADF4350 is a fractional-N PLL which offers broadband
operation from 137.5 MHz to 4.4 GHz and contains an integrated
high performance VCO.
ADL5370 Modulator
ADL5371 Modulator
ADL5372 Modulator
ADL5373 Modulator
ADL5374 Modulator
AD8347
AD8348
ADL5387 Demodulator
ADL5380 Demodulator
ADL5382 Demodulator
300 to 1000
500 to 1500
1500 to 2500
2300 to 3000
3000 to 4000
800 to 2700
50 to 1000
Table 6. ADF4350 Phase Noise at Various Frequencies
Phase Noise @ 10 kHz (dBc/Hz)
25 MHz PFD, 40 KHz Loop BW
Frequency
(MHz)
Demodulator
Demodulator
Part
ADF4350 2200
ADF4350 3300
ADF4350 4400
−97
−92
−90
50 to 2000
400 to 6000
700 to 2700
700 to 1000
AD8340
Vector
modulator
Vector
modulator
TRANSMIT DAC OPTIONS
AD8341
1500 to 2400
The AD9122 recommended in the previous sections of this data
sheet is by no means the only DAC that can be used to drive the
ADL5375. There are other appropriate DACs, depending on the
level of performance required. Table 7 lists the dual TxDAC
offered by Analog Devices.
Table 7. Dual TxDAC Selection
Part
Resolution (Bits) Update Rate (MSPS Minimum)
AD9709
AD9761
AD9763
AD9765
AD9767
AD9773
AD9775
AD9777
AD9776
AD9778
8
125
40
10
10
12
14
12
14
16
12
14
125
125
125
160
160
160
1000
1000
1000
AD9779A 16
Rev. C | Page 29 of 36
ADL5375
Data Sheet
EVALUATION BOARD
Populated RoHS-compliant evaluation boards are available
for evaluation of the ADL5375. The ADL5375 package has an
exposed paddle on the underside. This exposed paddle should
be soldered to the board for good thermal and electrical grounding.
The evaluation board is designed to minimize LO feedthrough
to RFOUT through PCB by placing LO block on the underside.
And it can be configured to allow differential LO driving through
balun or direct interfacing to the PLL evaluation board. It also
reserves component pads in its LO path to accommodate a
harmonic filter. One side placement of baseband inputs is to
interface directly to DAC evaluation board. The ADL5375
evaluation board also includes an RF driver amplifier. The
modulator output can be measured directly at the MOD_OUT
SMA connector. Alternatively, by removing R1, and installing a
0 Ω resistor in the R2 pad, the modulator’s output can be fed to
the RF driver amplifier.
The evaluation board ships, installed with an ADL5320 driver
amplifier (400 MHz to 2700 MHz RF driver amplifier). This
device requires external matching components (C100 and C101)
and is tuned by default for operation from 1805 MHz to 2170 MHz.
For details on tuning component values for other frequencies,
please refer to the ADL5320 data sheet (the driver amplifier section
of the ADL5375 Evaluation Board is identical to the ADL5320
Evaluation Board). For higher frequency operation, the ADL5320
should be replaced by the ADL5321, which is specified to operate
from 2.3 GHz to 4 GHz. If a broadband matched device is desired,
the ADL5601 (15 dB) or ADL5602 (20 dB) broadband gain blocks
can be used.
IBBN
IBBP
AGND
AGND
R7
100Ω
VPOS
C4
VPOS_AMP
RED
R13
0Ω
C2
100pF
VPOS
0.1µF
VPOS
C5
C3
C9 10µF
AGND
0.1µF
100pF
VPOS
RED
AGND
AGND
AGND
AGND
AGND
AGND
C10 10nF
AGND
AMP_IN
S1
(2)
DSOP
YELLOW
MOD_OUT
A
B
C11 22pF
AGND
R6
10kΩ
U2
ADL5320
R15
49.9Ω
R21*
0Ω
R1***
D.N.I
VPS1
DSOP
COMM
LOIP
L1
15nH
AGND
1
2
3
4
5
6
18
R14
R18
0Ω
C12
22pF
COMM
RFOUT
4
C6
0Ω
3
17
16
15
14
13
R2
0Ω
1
2
AMP_OUT
AGND
3
LOIP
AGND
LOIN
λ3
λ4
λ2
100pF
λ1
ADL5375
C18
D.N.I
C17
D.N.I
C16
D.N.I
TC1-1-43A+**
LOIN
C100 (C3)
0.5pF
C1
100pF
C101 (C7)
1.5pF
NC
COMM
6
1
AGND
U1
T1
C7
100pF
COMM
R16
D.N.I
R19
D.N.I
EXPOSED PADDLE
AGND
AGND
AGND
NC
NC
R20 D.N.I
R17*
0Ω
R22**
D.N.I
AGND
AGND
NC
6
AGND
AGND
5
2
4
3
1
GND
BLACK
AGND
JOHANSON
TECHNOLOGY**
T2 3600BL14M050
T2A 5400BL15B050
AGND
R12
100Ω
* SINGLE-ENDED LO DRIVING AT LOIP.
** DIFFERENTIAL LO DRIVING AT LOIP WITH T1 OR T2.
*** ADL5320 STAND-ALONE TEST.
QBBN
AGND
QBBP
AGND
Figure 75. ADL5375 Evaluation Board Schematic
Rev. C | Page 30 of 36
Data Sheet
ADL5375
Table 9. Evaluation Board Description and Configuration Options
Default Condition/Option
Settings
Component
Description
VPOS, GND Test Points
S1 Switch, R6, R15
Power supply and ground test points for clip leads
DSOP output disable select
Red = 5 V, black = GND
Position A = output enabled
Position B = output disabled
R15 = 49.9 Ω (0603)
R6 = 10 kΩ (0603)
R7, R12
C16 to C18, R14, R16, R18,
R19
AC limiting resistors
LO input filter components
R7, R12 = 100 Ω (0603)
R14 , R18 = 0 Ω (0603)
R16, R19, C16 to C18 = open
(0603)
C6, C7
LO driving capacitor
C6, C7 = 100 pF (0402)
R17 = 0 Ω (0603)
LOIP SMA, R17, R20, R21,
R22, T1, T2, T2A
Single-ended local oscillator input
R20 = open (0402)
R21 = 0 Ω (0402)
R22 = open (0603)
T1, T2, T2A = open
R16, R19 = 0 Ω (0603)
LOIN SMA, R16, R17, R19,
R20,
Optional differential LO input at LOIN
R21, R22, T1, T2, T2A
R20, R21 = 0 Ω (0402)
R17, R22 = open (0603)
T1, T2, T2A = open
R17 = open (0603)
LOIP SMA, T1 (or T2, T2A),
R17, R20, R21, R22
Optional differential LO driving with Balun at LOIP
R20, R21 = open (0402)
R22 = 0 Ω (0603)
T1 = TC1-1-43A+ or
T2 = 3600BL14M050 or T2A =
5400BL15B050
C100, C101
Frequency tuning capacitors for RF driver amplifier
Tuning for 1805 MHz to
2170 MHz
Refer to the ADL5320 datasheet for the exact position according to the frequency
C100 = 0.5 pF (0402) C101 =
1.5 pF (0402)
C1
R1
AC-coupling capacitor connects ADL5375 RF output to MOD_OUT RF connector or to C1 = 100 pF (0402)
ADL5320 RF input
Resistor connects ADL5375 RF output to MOD_OUT (AMP_IN) SMA
To check ADL5375 performance itself, a 0 Ω should be inserted at R1 and open R2.
To check ADL5320 performance itself, a 0 Ω should be inserted at R1 and R2
Resistor connects ADL5375 RF output to ADL5320 RF input
R1 = open (0402)
R2
R2 = 0 Ω (0402)
U1
U2
L1
ADL5375 quadrature modulator
SOT-89 RF driver amplifier
DC bias Inductor
ADL5375-05 or ADL5375-15
ADL5320
L1 = 15 nH(0603)
C2, C3 = 100 pF (0402)
C4, C5 = 0.1 µF (0402)
C9 = 10 µF (1206)
C10 = 10 nF (0603)
C11 = 22 pF (0603)
R13 = 0 Ω (0603)
C2, C3, C4, C5, C9, C10, C11
Power supply bypassing capacitors
R13
Resistor to share power supply between the ADL5375 and the ADL5320. To turn
on the ADL5320, a 0 Ω resistor should be installed in this location.
Rev. C | Page 31 of 36
ADL5375
Data Sheet
Thermal Grounding and Evaluation Board Layout
The package for the ADL5375 features an exposed paddle on
the underside that should be well soldered to a low thermal
and electrical impedance ground plane. This paddle is typically
soldered to an exposed opening in the solder mask on the
evaluation board. Figure 78 illustrates the dimensions used in
the layout of the ADL5375 footprint on the ADL5375 Evaluation
Board (1 mil. = 0.0254 mm).
Notice the use of nine via holes on the exposed paddle. These
ground vias should be connected to all other ground layers on
the evaluation board to maximize heat dissipation from the
device package.
12 mil.
23 mil.
25 mil.
82 mil.
Figure 76. Evaluation Board Layout, Top Layer
12 mil.
19.7 mil.
98.4 mil.
133.8 mil.
Figure 78. Dimensions for Evaluation Board Layout for the ADL5375 Package
Under these conditions, the thermal impedance of the ADL5375
was measured to be approximately 30°C/W in still air.
Figure 77. Evaluation Board Layout, Bottom Layer
Rev. C | Page 32 of 36
Data Sheet
ADL5375
CHARACTERIZATION SETUP
AEROFLEX IFR 3416
250kHz TO 6GHz SIGNAL GENERATOR
ROHDE & SCHWARTZ
SPECTRUM ANALYZER
FSU 20Hz TO 8GHz
RF
OUT
FREQ 1MHz LEVEL 0dBm
GAIN 0.5V
GAIN 0.5V
BIAS 0.5V
BIAS 0.5V
LO
CONNECT TO BACK OF UNIT
I OUT I/AM Q OUT Q/FM
RF
IN
+6dBm
0°
90°
I
Q
AGILENT 34401A
MULTIMETER
MOD TEST SETUP
0.194 ADC
MOD
IP
IN
LO
VPOS +5V
QP
QN
AGILENT E3631A
POWER SUPPLY
OUTPUT
OUT
VPOS GND
5.000
0.194A
6V
±25V
+
COM
–
–
+
Figure 79. Characterization Bench Setup
The primary setup used to characterize the ADL5375 is shown
in Figure 79. This setup was used to evaluate the product as a
single-sideband modulator. The aeroflex signal generator supplied
the LO and differential I and Q baseband signals to the device
under test (DUT). The typical LO drive was 0 dBm. The I-channel
is driven by a sine wave, and the Q-channel is driven by a cosine
wave. The lower sideband is the single-sideband (SSB) output.
The majority of characterization for the ADL5375 was performed
using a 1 MHz sine wave signal with a 500 mV (ADL5375-05)
or 1500 mV (ADL5375-15) common-mode voltage applied to
the baseband signals of the DUT. The baseband signal path was
calibrated to ensure that the VIOS and VQOS offsets on the baseband
inputs were minimized as close as possible to 0 V before
connecting to the DUT. See the Carrier Feedthrough Nulling
section for the definitions of VIOS and VQOS
.
Rev. C | Page 33 of 36
ADL5375
Data Sheet
TEKTRONIX AFG3252
DUAL FUNCTION
ARBITRARY FUNCTION GENERATOR
AEROFLEX IFR 3416
250kHz TO 6GHz SIGNAL GENERATOR
CH1 1MHz
AMPL 500mV p-p
PHASE 0°
RF
OUT
CH2 1MHz
AMPL 500mV p-p
PHASE 90°
LEVEL 0dBm
LO
90°
0°
I Q
SINGLE-TO-DIFFERENTIAL
CIRCUIT BOARD
AGILENT E3631A
POWER SUPPLY
MOD TEST RACK
Q IN AC
5.000
0.350A
MOD
CHAR BD
6V
±25V
COM
Q IN DCCM
TSEN
–
–
+
+
IP
IN
IP
LO
GND
VPOSB VPOSA
IN
IN1
AGND
IN1
QP
OUTPUT
OUT
GND
VN1
VP1
–5V
+5V
VPOS +5V
QN
VPOS
QP
QN
I IN DCCM
I IN AC
AGILENT E3631A
POWER SUPPLY
ROHDE & SCHWARTZ
SPECTRUM ANALYZER
FSU 20Hz TO 8GHz
0.500
0.010A
6V
±25V
+
COM
–
–
+
RF
IN
VCM = 0.5V
AGILENT 34401A
MULTIMETER
0.200 ADC
Figure 80. Setup for Baseband Frequency Sweep and Undesired Sideband Nulling
The setup used to evaluate baseband frequency sweep and
undesired sideband nulling of the ADL5375 is shown in Figure 80.
The interface board has circuitry that converts the single-ended
I input and Q input from the arbitrary function generator to
differential I and Q baseband signals with a dc bias of 500 mV
(ADL5375-05) or 1500 mV (ADL5375-15). Undesired sideband
nulling was achieved through an iterative process of adjusting
amplitude and phase on the Q-channel. See Sideband
Suppression Optimization section for a detailed description on
sideband nulling.
Rev. C | Page 34 of 36
Data Sheet
ADL5375
OUTLINE DIMENSIONS
4.10
4.00 SQ
3.90
0.30
0.25
0.18
PIN 1
INDICATOR
PIN 1
INDICATOR
24
19
0.50
BSC
1
6
18
EXPOSED
PAD
2.65
2.50 SQ
2.45
13
12
7
0.50
0.40
0.30
0.25 MIN
TOP VIEW
BOTTOM VIEW
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.80
0.75
0.70
0.05 MAX
0.02 NOM
SECTION OF THIS DATA SHEET.
COPLANARITY
0.08
0.20 REF
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-220-WGGD.
Figure 81. 24-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
4 mm × 4 mm Body, Very Very Thin Quad
(CP-24-7)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
Temperature Range
−40°C to +85°C
−40°C to +85°C
Package Description
Package Option
CP-24-7
CP-24-7
Ordering Quantity
ADL5375-05ACPZ-R7
ADL5375-05ACPZ-WP
ADL5375-05-EVALZ
ADL5375-15ACPZ-R7
ADL5375-15ACPZ-WP
ADL5375-15-EVALZ
24-Lead LFCSP_WQ, 7”Tape and Reel
24-Lead LFCSP_WQ, Waffle Pack
Evaluation Board
1,500
64
−40°C to +85°C
−40°C to +85°C
24-Lead LFCSP_WQ, 7”Tape and Reel
24-Lead LFCSP_WQ, Waffle Pack
Evaluation Board
CP-24-7
CP-24-7
1,500
64
1 Z = RoHS Compliant Part.
Rev. C | Page 35 of 36
ADL5375
NOTES
Data Sheet
©2007–2013 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D07052-0-7/13(C)
Rev. C | Page 36 of 36
相关型号：
ADL5375ACPZ-15-R7
RF/Microwave Modulator/Demodulator, 400 MHz - 6000 MHz RF/MICROWAVE QUADRAPHASE MODULATOR, 4 X 4 MM, ROHS COMPLIANT, MO-220-VGGD-8, LFCSP-24
ADI
©2020 ICPDF网 联系我们和版权申明