ADP1610 [ADI]
1.2 MHz DC-DC Step-Up Switching Converter; 1.2 MHz的DC- DC升压转换器
| 型号： | ADP1610 |
| 厂家： | 
ADI |
| 描述： | 1.2 MHz DC-DC Step-Up Switching Converter |
| 文件： | 总16页 (文件大小：1082K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
1.2 MHz DC-DC Step-Up Switching Converter
ADP1610
FEATURES
GENERAL DESCRIPTION
Fully integrated 1.2 A , 0.2 Ω, power switch
Pin-selectable 700 kHz or 1.2 MHz PWM frequency
92% efficiency
Adjustable output voltage up to 12 V
3% output regulation accuracy
Adjustable soft start
Input undervoltage lockout
MSOP 8-lead package
The ADP1610 is a dc-to-dc step-up switching converter with an
integrated 1.2 A, 0.2 Ω power switch capable of providing an
output voltage as high as 12 V. With a package height of less that
1.1 mm, the ADP1610 is optimal for space-constrained
applications such as portable devices or thin film transistor
(TFT) liquid crystal displays (LCDs).
The ADP1610 operates in pulse-width modulation (PWM)
current mode with up to 92% efficiency. Adjustable soft start
prevents inrush currents at startup. The pin-selectable switching
frequency and PWM current-mode architecture allow excellent
transient response, easy noise filtering, and the use of small,
cost-saving external inductors and capacitors.
APPLICATIONS
TFT LC bias supplies
Portable applications
Industrial/instrumentation equipment
The ADP1610 is offered in the Pb-free 8-lead MSOP and
operates over the temperature range of −40°C to +85°C.
FUNCTIONAL BLOCK DIAGRAM
COMP
IN
1
6
ERROR
AMP
ADP1610
REF
g
m
BIAS
FB
2
SW
5
F/F
R
Q
RAMP
GEN
S
DRIVER
COMPARATOR
RT
7
OSC
8
3
SS
SD
SOFT START
CURRENT
SENSE
AMPLIFIER
4
GND
Figure 1.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.326.8703
www.analog.com
© 2004 Analog Devices, Inc. All rights reserved.
ADP1610
TABLE OF CONTENTS
Specifications..................................................................................... 3
Choosing the Input and Output Capacitors ........................... 11
Diode Selection........................................................................... 12
Loop Compensation .................................................................. 12
Soft Start Capacitor.................................................................... 13
Application Circuits................................................................... 13
DC-DC Step-Up Switching Converter with True Shutdown14
TFT LCD Bias Supply................................................................ 14
Sepic Power Supply .................................................................... 14
Layout Procedure ........................................................................... 15
Outline Dimensions....................................................................... 16
Ordering Guide .......................................................................... 16
Absolute Maximum Ratings............................................................ 4
ESD Caution.................................................................................. 4
Pin Configuration and Function Descriptions............................. 5
Typical Performance Characteristics ............................................. 6
Theory of Operation ...................................................................... 10
Current-Mode PWM Operation .............................................. 10
Frequency Selection ................................................................... 10
Soft Start ...................................................................................... 10
On/Off Control........................................................................... 10
Setting the Output Voltage ........................................................ 10
REVISION HISTORY
10/04—Revision 0: Initial Version
Rev. 0 | Page 2 of 16
ADP1610
SPECIFICATIONS
VIN = 3.3 V, TA = −40°C to +85°C, unless otherwise noted.
All limits at temperature extremes are guaranteed by correlation and characterization using standard statistical quality control (SQC),
unless otherwise noted.
Table 1.
Parameter
Symbol
Conditions
Min
Typ
Max
Unit
SUPPLY
Input Voltage
Quiescent Current
Nonswitching State
Shutdown
VIN
2.5
5.5
V
IQ
IQSD
VFB = 1.3 V, RT = VIN
VSD = 0 V
390
0.01
600
10
µA
µA
Switching State1
IQ
SW
fSW = 1.23 MHz, no load
1
2
mA
OUTPUT
Output Voltage
Load Regulation
Overall Regulation
REFERENCE
VOUT
VIN
12
V
ILOAD = 10 mA to 150 mA, VOUT = 10 V
Line, load, temperature
0.05
mV/mA
%
±3
Feedback Voltage
Line Regulation
ERROR AMPLIFIER
Transconductance
Voltage Gain
VFB
1.212
−0.15
1.230
1.248
+0.15
V
%/V
VIN = 2.5 V to 5.5 V
gm
AV
100
60
µA/V
dB
∆I = 1 µA
FB Input Bias Current
SWITCH
VFB = 1.23 V
10
nA
SW On Resistance
SW Leakage Current
Peak Current Limit2
OSCILLATOR
RON
ISW = 1.0 A
VSW = 12 V
200
0.01
2.0
400
20
mΩ
µA
A
ICLSET
fOSC
Oscillator Frequency
RT = GND
RT = IN
COMP = open, VFB = 1 V, RT = GND
0.49
0.89
78
0.7
1.23
83
0.885
1.6
90
MHz
MHz
%
Maximum Duty Cycle
SHUTDOWN
DMAX
Shutdown Input Voltage Low
Shutdown Input Voltage High
Shutdown Input Bias Current
VIL
VIH
ISD
Nonswitching state
Switching state
VSD = 3.3 V
0.6
1
V
V
µA
2.2
0.01
3
SOFT START
SS Charging Current
UNDERVOLTAGE LOCKOUT3
UVLO Threshold
VSS = 0 V
VIN rising
µA
2.2
2.4
2.5
V
UVLO Hysteresis
220
mV
1 This parameter specifies the average current while switching internally and with SW (Pin 5) floating.
2 Guaranteed by design and not fully production tested.
3 Guaranteed by characterization.
Rev. 0 | Page 3 of 16
ADP1610
ABSOLUTE MAXIMUM RATINGS
Table 2.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only and functional operation of the device at these or
any other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability. Absolute maximum ratings apply individually
only, not in combination. Unless otherwise specified, all other
voltages are referenced to GND.
Parameter
Rating
IN, COMP, SD, SS, RT, FB to GND
SW to GND
−0.3 V to +6 V
14 V
RMS SW Pin Current
1.2 A
Operating Ambient Temperature Range
Operating Junction Temperature Range
Storage Temperature Range
θJA, Two Layers
−40°C to +85°C
−40°C to +125°C
−65°C to +150°C
206°C/W
θJA, Four Layers
142°C/W
Lead Temperature Range (Soldering, 60 s)
300°C
IN
R
C
C
C
V
OUT
C
IN
COMP
IN
1
6
ERROR
AMP
L1
ADP1610
R1
REF
BIAS
FB
2
D1
R2
SW
V
5
OUT
F/F
C
OUT
R
Q
RAMP
GEN
S
DRIVER
V
IN
COMPARATOR
RT
1.2MHz
700kHz
7
OSC
3
8
SD
SS
CURRENT
SENSE
AMPLIFIER
SOFT START
C
SS
4
GND
Figure 2. Block Diagram and Typical Application Circuit
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. 0 | Page 4 of 16
ADP1610
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
COMP
FB
1
2
3
4
8
7
6
5
SS
RT
IN
ADP1610
TOP VIEW
SD
(Not to Scale)
GND
SW
Figure 3. Pin Configuration
Table 3. Pin Function Descriptions
Pin No. Mnemonic Description
1
COMP
Compensation Input. Connect a series resistor-capacitor network from COMP to GND to compensate the
regulator.
2
FB
Output Voltage Feedback Input. Connect a resistive voltage divider from the output voltage to FB to set the
regulator output voltage.
3
4
5
SD
Shutdown Input. Drive SD low to shut down the regulator; drive SD high to turn it on.
Ground.
Switching Output. Connect the power inductor from the input voltage to SW and connect the external rectifier
from SW to the output voltage to complete the step-up converter.
GND
SW
6
7
8
IN
RT
SS
Main Power Supply Input. IN powers the ADP1610 internal circuitry. Connect IN to the input source voltage.
Bypass IN to GND with a 10 µF or greater capacitor as close to the ADP1610 as possible.
Frequency Setting Input. RT controls the switching frequency. Connect RT to GND to program the oscillator to
700 kHz, or connect RT to IN to program it to 1.2 MHz.
Soft Start Timing Capacitor Input. A capacitor from SS to GND brings up the output slowly at power-up.
Rev. 0 | Page 5 of 16
ADP1610
TYPICAL PERFORMANCE CHARACTERISTICS
100
100
V
V
V
= 5.5V
= 3.3V
= 2.5V
V
F
= 10V
V
F
= 7.5V
= 1.2MHz
IN
OUT
OUT
V
= 5.5V
IN
= 700kHz
SW
90
80
70
SW
L = 10µH
L = 4.7µH
90
80
70
60
50
IN
IN
V
= 3.3V
IN
V
= 2.5V
IN
60
50
40
30
20
10
0
40
30
1
1
1
10
100
1000
1
10
100
1000
LOAD CURRENT (mA)
LOAD CURRENT (mA)
Figure 4. Output Efficiency vs. Load Current
Figure 7. Output Efficiency vs. Load Current
100
90
2.4
V
= 5.5V
= 3.3V
= 2.5V
IN
V
= 10V
OUT
F = 1.2MHz
L = 4.7µH
V
V
IN
IN
2.2
2.0
1.8
1.6
V
= 5.5V
= 3.3V
IN
80
70
V
IN
60
50
40
V
= 2.5V
IN
30
20
10
0
1.4
1.2
10
100
1000
–40
–15
10
35
60
85
LOAD CURRENT (mA)
AMBIENT TEMPERATURE (°C)
Figure 5. Output Efficiency vs. Load Current
Figure 8. Current Limit vs. Ambient Temperature, VOUT = 10 V
100
90
1.4
1.2
V
= 7.5V
= 700kHz
OUT
V
V
= 5.5V
IN
F
SW
L = 10µH
RT = V
IN
V
= 3.3V
IN
= 2.5V
IN
80
1.0
0.8
70
60
50
0.6
RT = GND
0.4
40
30
V
V
= 10V
= 3.3V
0.2
0
OUT
IN
10
100
1000
–40
–15
10
35
60
85
LOAD CURRENT (mA)
AMBIENT TEMPERATURE (°C)
Figure 6. Output Efficiency vs. Load Current
Figure 9. Oscillatory Frequency vs. Ambient Temperature
Rev. 0 | Page 6 of 16
ADP1610
4.4
1.2
1.0
0.8
0.50
0.45
0.40
F
V
= 700kHz
= 1.3V
SW
FB
RT = V
IN
V
= 5.5V
IN
0.35
0.30
0.6
0.4
V
= 3.3V
= 2.5V
RT = GND
IN
IN
V
0.25
0.20
0.2
0
V
= 10V
3.0
OUT
2.5
3.5
4.0
4.5
5.0
5.5
–40
–15
10
35
60
85
SUPPLY VOLTAGE (V)
AMBIENT TEMPERATURE (°C)
Figure 13. Quiescent Current vs. Ambient Temperature
Figure 10. Oscillatory Frequency vs. Supply Voltage
0.60
0.55
0.50
350
F
V
= 1.23kHz
= 1.3V
SW
FB
V
= 2.5V
300
250
200
150
IN
V
= 3.3V
IN
V
= 5.5V
IN
V
= 5.5V
IN
0.45
0.40
V
= 3.3V
= 2.5V
IN
IN
100
50
0
V
0.35
0.30
–40
–15
10
35
60
85
–40
–15
10
35
60
85
AMBIENT TEMPERATURE (°C)
AMBIENT TEMPERATURE (°C)
Figure 14. Quiescent Current vs. Ambient Temperature
Figure 11. Switch Resistance vs. Ambient Temperature
2.0
1.245
F
V
= 1.23kHz
= 1V
SW
FB
1.24
1.235
1.23
1.8
1.6
1.4
1.2
1.0
V
= 5.5V
IN
1.225
V
V
= 3.3V
= 2.5V
IN
1.22
1.215
1.21
0.8
0.6
IN
–40
–15
10
35
60
85
–40 –25 –10
5
20
35
50
65
80
95 110 125
AMBIENT TEMPERATURE (°C)
AMBIENT TEMPERATURE (°C)
Figure 15. Supply Current vs. Ambient Temperature
Figure 12. FB Regulation Voltage vs. Ambient Temperature
Rev. 0 | Page 7 of 16
ADP1610
1.4
F
CH1 = IL 200mA/DIV
CH2 = V 5V/DIV
V
V
I
= 3.3V
IN
= 700kHz
= 1V
SW
= 10V
= 20mA
SW
OUT
LOAD
1.3
1.2
1.1
1.0
0.9
0.8
0.7
0.6
V
FB
F
= 700kHz
SW
L = 10µH
V
= 5.5V
IN
2
V
V
= 3.3V
= 2.5V
IN
IN
1
0.5
0.4
CH1 10.0mVΩ CH2 5.00V
M400ns
136.000ns
A CH2
10.0V
–40
–15
10
35
60
85
T
AMBIENT TEMPERATURE (°C)
Figure 16. Supply Current vs. Ambient Temperature
Figure 19. Switching Waveform in Discontinuous Conduction
3.5
3.0
2.5
2.0
V
C
C
= 3.3V, V
= 10V
IN
OUT
V
= 3.3V
IN
= 10µF, L = 10µH, R = 130Ω
OUT
= 270pF, F
C
SD = 0.4V
= 700kHz
200mV/DIV
C
SW
CH1 = V
CH2 = I
OUT,
200mA/DIV
OUT,
1
1.5
1.0
2
0.5
0
CH1 200mV
CH2 10.0mVΩ M200µs
A CH2
7.60mV
–40
15
70
125
TEMPERATURE (°C)
Figure 17. Supply Current in Shutdown vs. Ambient Temperature
Figure 20. Load Transient Response, 700 kHz , VOUT = 10 V
V
C
C
= 3.3V, V
= 10V
IN
OUT
CH1 = IL 500mA/DIV
CH2 = V 5V/DIV
V
V
I
= 3.3V
IN
= 10µF, L = 4.7µH, R = 220kΩ
OUT
= 150pF, F
C
= 10V
= 200mA
SW
OUT
LOAD
= 1.2MHz
C
SW
CH1 = V
CH2 = I
, 200mV/DIV
OUT
F
= 700kHz
SW
, 200mA/DIV
OUT
L = 10µH
1
2
2
1
CH1 10.0mVΩ CH2 5.00V
M400ns
136.000ns
A CH2
10.0V
CH1 200mV
CH2 10.0mVΩ M200µs
A CH2
7.60mV
T
Figure 18. Switching Waveform in Continuous Conduction
Figure 21. Load Transient Response, 1.2 MHz, VOUT = 10 V
Rev. 0 | Page 8 of 16
ADP1610
2
4
2
4
CH1 = IL 1A/DIV
V
V
= 3.3V
CH1 = IL 1A/DIV
V
V
= 3.3V
IN
IN
CH2 = V
CH3 = V
= 10V
CH2 = V
CH3 = V
= 10V
IN
OUT
IN
OUT
3
1
3
1
I
= 0.2A
I
= 0.2A
= 0nF
OUT
OUT
OUT
OUT
CH4 = S , F
= 700kHz
C
= 0nF
CH4 = S , F
= 700kHz
C
SS
W
SW
SS
W
SW
CH1 10.0mVΩ CH2 2.00V
CH3 10.0V CH4 10.00V
M100µs
A CH2
680mV
CH1 10.0mVΩ CH2 2.00V
CH3 10.0V CH4 10.00V
M100µs
405.600µs
A CH2
1.72V
T
414.800µs
T
Figure 24. Start-Up Response from Shutdown, SS = 0 nF
Figure 22. Start-Up Response from VIN, SS = 0 nF
2
4
2
4
CH1 = IL 1A/DIV
CH2 = SD
I
V
V
= 0.2A
= 3.3V
CH1 = IL 1A/DIV
V
V
= 3.3V
OUT
IN
CH2 = V
CH3 = V
= 10V
IN
IN
OUT
3
1
3
1
CH3 = V
= 10V
I
= 0.2A
C = 10nF
SS
OUT
OUT
OUT
OUT
CH4 = S , F
= 700kHz
C = 10nF
CH4 = S , F
= 700kHz
W
SW
SS
W
SW
CH1 10.0mVΩ CH2 2.00V
CH3 10.0V CH4 10.00V
M100µs
405.600µs
A CH2
1.72V
CH1 10.0mVΩ CH2 2.00V
CH3 10.0V CH4 10.00V
M100µs
A CH2
680mV
T
T
414.800µs
Figure 25. Start-Up Response from Shutdown, SS = 10 nF
Figure 23. Start-Up Response from VIN, SS = 10 nF
Rev. 0 | Page 9 of 16
ADP1610
THEORY OF OPERATION
The ADP1610 current-mode step-up switching converter
converts a 2.5 V to 5.5 V input voltage up to an output voltage as
high as 12 V. The 1.2 A internal switch allows a high output
current, and the high 1.2 MHz switching frequency allows tiny
external components. The switch current is monitored on a
pulse-by-pulse basis to limit it to 2 A.
ON/OFF CONTROL
SD
SD
input turns the ADP1610 regulator on or off. Drive
The
low to turn off the regulator and reduce the input current to
SD
10 nA. Drive
high to turn on the regulator.
When the dc-dc step-up switching converter is turned off, there
is a dc path from the input to the output through the inductor
and output rectifier. This causes the output voltage to remain
slightly below the input voltage by the forward voltage of the
rectifier, preventing the output voltage from dropping to zero
when the regulator is shut down. Figure 28 shows the applica-
tion circuit to disconnect the output voltage from the input
voltage at shutdown.
CURRENT-MODE PWM OPERATION
The ADP1610 uses current-mode architecture to regulate the
output voltage. The output voltage is monitored at FB through a
resistive voltage divider. The voltage at FB is compared to the
internal 1.23 V reference by the internal transconductance error
amplifier to create an error current at COMP. A series resistor-
capacitor at COMP converts the error current to a voltage. The
switch current is internally measured and added to the stabiliz-
ing ramp, and the resulting sum is compared to the error
voltage at COMP to control the PWM modulator. This current-
mode regulation system allows fast transient response, while
maintaining a stable output voltage. By selecting the proper
resistor-capacitor network from COMP to GND, the regulator
response is optimized for a wide range of input voltages, output
voltages, and load conditions.
SETTING THE OUTPUT VOLTAGE
The ADP1610 features an adjustable output voltage range of VIN
to 12 V. The output voltage is set by the resistive voltage divider
(R1 and R2 in Figure 2) from the output voltage (VOUT) to the
1.230 V feedback input at FB. Use the following formula to
determine the output voltage:
V
OUT = 1.23 × (1 + R1/R2)
(1)
Use an R2 resistance of 10 kΩ or less to prevent output voltage
errors due to the 10 nA FB input bias current. Choose R1 based
on the following formula:
FREQUENCY SELECTION
The ADP1610’s frequency is user-selectable to operate at either
700 kHz to optimize the regulator for high efficiency or to
1.2 MHz for small external components. Connect RT to IN for
1.2 MHz operation, or connect RT to GND for 700 kHz
operation. To achieve the maximum duty cycle, which might be
required for converting a low input voltage to a high output
voltage, use the lower 700 kHz switching frequency.
V
− 1.23
⎛
⎞
OUT
R1 = R2 × ⎜
⎟
⎟
(2)
⎜
1.23
⎝
⎠
INDUCTOR SELECTION
The inductor is an essential part of the step-up switching
converter. It stores energy during the on-time, and transfers that
energy to the output through the output rectifier during the off-
time. Use inductance in the range of 1 µH to 22 µH. In general,
lower inductance values have higher saturation current and
lower series resistance for a given physical size. However, lower
inductance results in higher peak current that can lead to
reduced efficiency and greater input and/or output ripple and
noise. Peak-to-peak inductor ripple current at close to 30% of
the maximum dc input current typically yields an optimal
compromise.
SOFT START
To prevent input inrush current at startup, connect a capacitor
from SS to GND to set the soft start period. When the ADP1610
is in shutdown ( is at GND) or the input voltage is below the
SD
2.4 V undervoltage lockout voltage, SS is internally shorted to
GND to discharge the soft start capacitor. Once the ADP1610 is
turned on, SS sources 3 µA to the soft start capacitor at startup.
As the soft start capacitor charges, it limits the voltage at COMP.
Because of the current-mode regulator, the voltage at COMP is
proportional to the switch peak current, and, therefore, the
input current. By slowly charging the soft start capacitor, the
input current ramps slowly to prevent it from overshooting
excessively at startup.
For determining the inductor ripple current, the input (VIN) and
output (VOUT) voltages determine the switch duty cycle (D) by
the following equation:
VOUT − VIN
D =
(3)
VOUT
Rev. 0 | Page 10 of 16
ADP1610
Table 4. Inductor Manufacturers
Vendor
Part
L (µH)
2.2
4.7
10
Max DC Current
Max DCR (mΩ)
Height (mm)
Sumida
847-956-0666
www.sumida.com
CMD4D11-2R2MC
CMD4D11-4R7MC
CDRH4D28-100
CDRH5D18-220
CR43-4R7
0.95
0.75
1.00
0.80
1.15
1.04
1.40
1.00
1.14
0.76
116
216
128
290
109
182
60
1.2
1.2
3.0
2.0
3.5
3.5
2.9
2.9
2.0
2.0
22
4.7
10
CR43-100
Coilcraft 847-639-6400
www.coilcraft.com
Toko 847-297-0070
www.tokoam.com
DS1608-472
DS1608-103
D52LC-4R7M
D52LC-100M
4.7
10
75
4.7
10
87
150
Using the duty cycle and switching frequency, fSW, determine the
on-time by the following equation:
The output capacitor maintains the output voltage and supplies
current to the load while the ADP1610 switch is on. The value
and characteristics of the output capacitor greatly affect the
output voltage ripple and stability of the regulator. Use a low
ESR output capacitor; ceramic dielectric capacitors are
preferred.
D
fSW
tON
=
(4)
The inductor ripple current (∆IL) in steady state is
For very low ESR capacitors such as ceramic capacitors, the
ripple current due to the capacitance is calculated as follows.
Because the capacitor discharges during the on-time, tON, the
charge removed from the capacitor, QC, is the load current
multiplied by the on-time. Therefore, the output voltage ripple
(∆VOUT) is
VIN ×tON
∆IL =
(5)
(6)
L
Solving for the inductance value, L,
VIN ×tON
L =
∆IL
QC
COUT
IL ×tON
COUT
∆VOUT
=
=
(8)
Make sure that the peak inductor current (the maximum input
current plus half the inductor ripple current) is below the rated
saturation current of the inductor. Likewise, make sure that the
maximum rated rms current of the inductor is greater than the
maximum dc input current to the regulator.
where:
OUT is the output capacitance,
C
IL is the average inductor current,
For duty cycles greater than 50%, which occur with input
voltages greater than one-half the output voltage, slope
compensation is required to maintain stability of the current-
mode regulator. For stable current-mode operation, ensure that
D
fSW
(9)
tON
=
and
the selected inductance is equal to or greater than LMIN
:
VOUT −VIN
D =
(10)
VOUT −VIN
1.8 A× fSW
VOUT
L > LMIN
=
(7)
Choose the output capacitor based on the following equation:
IL ×(VOUT −VIN
fSW ×VOUT ×∆VOUT
CHOOSING THE INPUT AND OUTPUT CAPACITORS
)
The ADP1610 requires input and output bypass capacitors to
supply transient currents while maintaining constant input and
output voltage. Use a low ESR (equivalent series resistance),
10 µF or greater input capacitor to prevent noise at the
ADP1610 input. Place the capacitor between IN and GND as
close to the ADP1610 as possible. Ceramic capacitors are
preferred because of their low ESR characteristics. Alternatively,
use a high value, medium ESR capacitor in parallel with a 0.1 µF
low ESR capacitor as close to the ADP1610 as possible.
COUT
≥
(11)
Table 5. Capacitor Manufacturers
Vendor
Phone No.
Web Address
AVX
Murata
Sanyo
408-573-4150
714-852-2001
408-749-9714
408-573-4150
www.avxcorp.com
www.murata.com
www.sanyovideo.com
www.t-yuden.com
Taiyo–Yuden
Rev. 0 | Page 11 of 16
ADP1610
The regulator loop gain is
DIODE SELECTION
The output rectifier conducts the inductor current to the output
capacitor and load while the switch is off. For high efficiency,
minimize the forward voltage drop of the diode. For this reason,
Schottky rectifiers are recommended. However, for high voltage,
high temperature applications, where the Schottky rectifier
reverse leakage current becomes significant and can degrade
efficiency, use an ultrafast junction diode.
VFB
VIN
VOUT VOUT
(14)
×GMEA × ZCOMP ×GCS × ZOUT
AVL
=
×
where:
A
V
V
V
G
VL is the loop gain.
FB is the feedback regulation voltage, 1.230 V.
OUT is the regulated output voltage.
IN is the input voltage.
Make sure that the diode is rated to handle the average output
load current. Many diode manufacturers derate the current
capability of the diode as a function of the duty cycle. Verify
that the output diode is rated to handle the average output load
current with the minimum duty cycle. The minimum duty cycle
of the ADP1610 is
MEA is the error amplifier transconductance gain.
Z
COMP is the impedance of the series RC network from COMP to
GND.
G
CS is the current sense transconductance gain (the inductor
current divided by the voltage at COMP), which is internally set
by the ADP1610.
VOUT −VIN−MAX
DMIN
=
(12)
VOUT
Z
OUT is the impedance of the load and output capacitor.
where VIN-MAX is the maximum input voltage.
To determine the crossover frequency, it is important to note
that, at that frequency, the compensation impedance (ZCOMP) is
dominated by the resistor, and the output impedance (ZOUT) is
dominated by the impedance of the output capacitor. So, when
solving for the crossover frequency, the equation (by definition
of the crossover frequency) is simplified to
Table 6. Schottky Diode Manufacturers
Vendor
Motorola
Diodes, Inc.
Sanyo
Phone No.
Web Address
602-244-3576
805-446-4800
310-322-3331
www.mot.com
www.diodes.com
www.irf.com
VFB
V
1
(15)
IN
| A | =
×
× GMEA× RCOMP×G ×
=1
VL
CS
LOOP COMPENSATION
VOUT VOUT
2π × fC ×COUT
The ADP1610 uses external components to compensate the
regulator loop, allowing optimization of the loop dynamics for a
given application.
where:
fC is the crossover frequency.
COMP is the compensation resistor.
Solving for RCOMP
The step-up converter produces an undesirable right-half plane
zero in the regulation feedback loop. This requires compensat-
ing the regulator such that the crossover frequency occurs well
below the frequency of the right-half plane zero. The right-half
plane zero is determined by the following equation:
R
,
2π × fC ×COUT ×VOUT ×VOUT
VFB ×VIN × GMEA × GCS
(16)
(17)
R COMP
=
2
⎛
⎜
⎜
⎝
⎞
⎟
⎟
⎠
VIN
VOUT
RLOAD
2π×L
FZ (RHP) =
×
(13)
For VFB = 1.23, GMEA = 100 µS, and GCS = 2 S,
2.55×104 × fC ×COUT ×VOUT ×VOUT
RCOMP
=
where:
FZ(RHP) is the right-half plane zero.
VIN
Once the compensation resistor is known, set the zero formed
by the compensation capacitor and resistor to one-fourth of the
crossover frequency, or
R
LOAD is the equivalent load resistance or the output voltage
divided by the load current.
To stabilize the regulator, make sure that the regulator crossover
frequency is less than or equal to one-fifth of the right-half
plane zero and less than or equal to one-fifteenth of the
switching frequency.
2
(18)
CCOMP
=
π× fC ×RCOMP
where CCOMP is the compensation capacitor.
Rev. 0 | Page 12 of 16
ADP1610
Table 7. Recommended External Components for Popular Input/Output Voltage Conditions
VIN (V)
VOUT (V)
fSW (MHz)
0.700
1.23
0.700
1.23
0.700
1.23
0.700
1.23
L (µH)
4.7
2.7
10
4.7
10
4.7
10
4.7
10
COUT (µF)
CIN (µF)
R1 (kΩ)
30.9
30.9
63.4
63.4
88.7
88.7
63.4
63.4
88.7
88.7
R2 (kΩ)
RComp (kΩ)
Ccomp (pF)
520
150
820
180
420
100
390
100
IOUT_MAX (mA)
600
600
350
350
250
250
450
450
3.3
5
5
9
9
12
12
9
9
12
12
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
10
50
90.9
71.5
150
130
280
84.5
178
140
5
0.700
1.23
10
10
10
10
10
10
220
100
350
350
4.7
300
ERROR AMP
COMP
REF
g
1
m
Table 8. Typical Soft Start Period
FB
2
VIN (V)
VOUT (V)
COUT (µF)
CSS (nF)
tSS (ms)
0.3
2
2.5
8.2
3.5
15
0.4
1.5
0.62
2
R
C
C2
3.3
5
5
9
9
12
12
9
9
12
12
10
10
10
10
10
10
10
10
20
100
20
100
20
100
20
100
20
100
C
C
Figure 26. Compensation Components
The capacitor, C2, is chosen to cancel the zero introduced by
output capacitance ESR.
5
Solving for C2,
10
10
ESR×COUT
C2 =
(19)
Conversely, if fast startup is a requirement, the soft start
capacitor can be reduced or even removed, allowing the
ADP1610 to start quickly, but allowing greater peak switch
RCOMP
For low ESR output capacitance such as with a ceramic capaci-
tor, C2 is optional. For optimal transient performance, the RCOMP
and CCOMP might need to be adjusted by observing the load
transient response of the ADP1610. For most applications, the
compensation resistor should be in the range of 30 kΩ to
400 kΩ, and the compensation capacitor should be in the range
of 100 pF to 1.2 nF. Table 7 shows external component values
for several applications.
current (see Figure 22 to Figure 25)
.
APPLICATION CIRCUITS
The circuit in Figure 27 shows the ADP1610 in a step-up
configuration. The ADP1610 is used here to generate a 10 V
regulator with the following specifications: VIN = 2.5 V to 5.5 V,
VOUT = 10 V, and IOUT ≤ 400 mA.
4.7µH
SOFT START CAPACITOR
L
The voltage at SS ramps up slowly by charging the soft start
capacitor (CSS) with an internal 3 µA current source. Table 8
listed the values for the soft start period, based on maximum
output current and maximum switching frequency.
D1
ADP1610
3.3V
10V
6
3
7
5
2
1
IN
SW
ON
R1
71.3kΩ
SD
RT
SS
FB
R2
C
IN
10µF
The soft start capacitor limits the rate of voltage rise on the
COMP pin, which in turn limits the peak switch current at
startup. Table 8 shows a typical soft start period, tSS, at
maximum output current, IOUT_MAX, for several conditions.
10kΩ
C
OUT
10µF
8
COMP
R
COMP
220kΩ
C
GND
4
SS
22nF
C
COMP
150pF
A 20 nF soft start capacitor results in negligible input current
overshoot at startup, and so is suitable for most applications.
However, if an unusually large output capacitor is used, a longer
soft start period is required to prevent input inrush current.
Figure 27. 3.3 V to 10 V Step-Up Regulator
The output can be set to the desired voltage using Equation 2.
Use Equation 16 and 17 to change the compensation network.
Rev. 0 | Page 13 of 16
ADP1610
R3
200Ω
DC-DC STEP-UP SWITCHING CONVERTER WITH
TRUE SHUTDOWN
VGH
22V
D5
BZT52C22
C4
10nF
R4
200Ω
BAV99
D8
C3
10µF
D5
D4
C5
10nF
VGL
–5V
D9
BZT52C5VIS
C6
10µF
Some battery-powered applications require very low standby
current. The ADP1610 typically consumes 10 nA from the
input, which makes it suitable for these applications. However,
the output is connected to the input through the inductor and
the rectifying diode, allowing load current draw from the input
while shut down. The circuit in Figure 28 enables the ADP1610
to achieve output load disconnect at shutdown. To shut down
the ADP1610 and disconnect the output from the input, drive
SD
BAV99
D3
D7
C2
1µF
C1
10nF
BAV99
D2
4.7µH
L
D1
ADP1610
3.3V
10V
6
3
7
5
IN
SW
FB
the
pin below 0.4 V.
ON
R1
71.3kΩ
SD
RT
SS
2
1
4.7µH
L
R2
10kΩ
C
IN
10µF
C
OUT
10µF
D1
ADP1610
8
Q1 FDC6331
A
COMP
3.3V
10V
R
COMP
220kΩ
6
3
7
5
2
1
IN
SW
FB
C
GND
4
SS
22nF
R3
10kΩ
R1
C
COMP
71.3kΩ
SD
RT
SS
150pF
Q1
B
R2
C
IN
10µF
10kΩ
Figure 29. TFT LCD Bias Supply
C
OUT
10µF
8
COMP
R
OFF
COMP
220kΩ
SEPIC POWER SUPPLY
C
GND
4
SS
22nF
C
COMP
150pF
The circuit in Figure 30 shows the ADP1610 in a single-ended
primary inductance converter (SEPIC) topology. This topology
is useful for an unregulated input voltage, such as a battery-
powered application in which the input voltage can vary
between 2.7 V to 5 V, and the regulated output voltage falls
within the input voltage range.
Figure 28. Step-Up Regulator with True Shutdown
TFT LCD BIAS SUPPLY
Figure 29 shows a power supply circuit for TFT LCD module
applications. This circuit has +10 V, −5 V, and +22 V outputs.
The +10 V is generated in the step-up configuration. The −5 V
and +22 V are generated by the charge-pump circuit. During the
step-up operation, the SW node switches between 10 V and
ground (neglecting forward drop of the diode and on resistance
of the switch). When the SW node is high, C5 charges up to
10 V. C5 holds its charge and forward-biases D8 to charge C6
to −10 V. The Zener diode, D9, clamps and regulates the output
to −5 V.
The input and the output are dc-isolated by a coupling capaci-
tor, C1. In steady state, the average voltage of C1 is the input
voltage. When the ADP1610 switch turns on and the diode
turns off, the input voltage provides energy to L1, and C1
provides energy to L2. When the ADP1610 switch turns off and
the diode turns on, the energy in L1 and L2 is released to charge
the output capacitor, COUT, and the coupling capacitor, C1, and
to supply current to the load.
4.7µH
The VGH output is generated in a similar manner by the
charge-pump capacitors, C1, C2, and C4. The output
voltage is tripled and regulated down to 22 V by the
Zener diode, D5.
L1
C1
10µF
ADP1610
2.5V–5.5V
3.3V
6
3
7
5
IN
SW
ON
R1
SD
RT
SS
16.8kΩ
4.7µH
L2
C
2
1
IN
FB
10µF
C
10µF
OUT
8
COMP
R
COMP
C
60kΩ
GND
4
R2
10kΩ
SS
22nF
C
COMP
1nF
Figure 30. 3.3 V DC-DC Converter
Rev. 0 | Page 14 of 16
ADP1610
LAYOUT PROCEDURE
To get high efficiency, good regulation, and stability, a well-
designed printed circuit board layout is required. Where
possible, use the sample application board layout as a model.
Follow these guidelines when designing printed circuit boards
(see Figure 1):
•
•
•
Keep the low ESR input capacitor, CIN, close to IN and
GND.
Keep the high current path from CIN through the inductor
L1 to SW and PGND as short as possible.
Keep the high current path from CIN through L1, the
rectifier D1, and the output capacitor COUT as short as
possible.
•
•
Keep high current traces as short and as wide as possible.
Place the feedback resistors as close to the FB pin as
possible to prevent noise pickup.
Figure 32. Sample Application Board (Top Layer)
•
•
Place the compensation components as close as possible to
COMP.
Avoid routing high impedance traces near any node
connected to SW or near the inductor to prevent radiated
noise injection.
Figure 33. Sample Application Board (Silkscreen Layer)
Figure 31. Sample Application Board (Bottom Layer)
Rev. 0 | Page 15 of 16
ADP1610
Preliminary Technical Data
OUTLINE DIMENSIONS
3.00
BSC
8
1
5
4
4.90
BSC
3.00
BSC
PIN 1
0.65 BSC
1.10 MAX
0.15
0.00
0.80
0.60
0.40
8°
0°
0.38
0.22
0.23
0.08
COPLANARITY
0.10
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-187AA
Figure 34. 8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters
ORDERING GUIDE
Model
ADP1610ARMZ-R71
Temperature Range
−40°C to +85°C
Package Description
Package Option
Branding
8-Lead Mini Small Outline Package [MSOP]
RM-8
P03
1 Z = Pb-free part.
©
2004 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D04472–0–10/04(0)
Rev. 0 | Page 16 of 16
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