ADP3000AR-12 [ADI]
Micropower Step-Up/Step-Down Fixed 3.3 V, 5 V, 12 V and Adjustable High Frequency Switching Regulator; 微功率升压/降压型固定3.3 V ， 5 V ， 12 V和可调式高频开关稳压器
| 型号： | ADP3000AR-12 |
| 厂家： | 
ADI |
| 描述： | Micropower Step-Up/Step-Down Fixed 3.3 V, 5 V, 12 V and Adjustable High Frequency Switching Regulator |
| 文件： | 总12页 (文件大小：344K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Micropower Step-Up/Step-Down
Fixed 3.3 V, 5 V, 12 V and Adjustable
High Frequency Switching Regulator
a
ADP3000
FUNCTIONAL BLOCK DIAGRAM
FEATURES
Operates at Supply Voltages from 2 V to 30 V
Works in Step-Up or Step-Down Mode
Very Few External Components Required
High Frequency Operation Up to 400 kHz
Low Battery Detector on Chip
User Adjustable Current Limit
Fixed and Adjustable Output Voltage
8-Pin DIP and SO-8 Package
SET
A1
A0
V
IN
I
GAIN BLOCK/
ERROR AMP
LIM
SW1
1.245V
REFERENCE
400kHz
OSCILLATOR
Small Inductors and Capacitors
DRIVER
SW2
COMPARATOR
APPLICATIONS
ADP3000
Notebook, Palmtop Computers
Cellular Telephones
Hard Disk Drives
R1
R2
GND
SENSE
Portable Instruments
Pagers
6.8µH
IN5817
V
IN
3.3V @
180mA
2V–3.2V
100µF
10V
120Ω
GENERAL DESCRIPTION
1
2
The ADP3000 is a versatile step-up/step-down switching
regulator that operates from an input supply voltage of 2 V to
12 V in step-up mode and up to 30 V in step-down mode.
I
V
LIM
IN
SW1
3
8
ADP3000-3.3V
The ADP3000 operates in Pulse Frequency Mode (PFM) and
consumes only 500 µA, making it highly suitable for applica-
tions that require low quiescent current.
FB
(SENSE)
C1
100µF
10V
+
GND
5
SW2
4
The ADP3000 can deliver an output current of 100 mA at
3 V from a 5 V input in step-down configuration and 180 mA at
3.3 V from a 2 V input in step-up configuration.
C1, C2: AVX TPS D107 M010R0100
L1: SUMIDA CD43-6R8
The auxiliary gain amplifier can be used as a low battery detector,
linear regulator undervoltage lockout or error amplifier.
Figure 1. Typical Application
The ADP3000 operates at 400 kHz switching frequency. This
allows the use of small external components (inductors and
capacitors), making the device very suitable for space constrained
designs.
V
IN
R
120Ω
5V–6V
C1
100µF
10V
LIM
1
2
3
I
V
SW1
LIM
IN
8
4
FB
ADP3000
L1
10µH
V
SW2
OUT
R2
GND
5
3V
100mA
150kΩ
1%
CL
100µF
10V
+
D1
1N5818
R1
110kΩ
1%
C1, C2: AVX TPS D107 M010R0100
L1: SUMIDA CD43-100
Figure 2. Step-Down Mode Operation
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703
World Wide Web Site: http://www.analog.com
© Analog Devices, Inc., 1997
(0؇C ≤ T ≤ +70؇C, V = 3 V unless otherwise noted)*
ADP3000–SPECIFICATIONS
A
IN
ADP3000
Typ
Parameter
Conditions
Symbol
Min
Max
Units
INPUT VOLTAGE
Step-Up Mode
Step-Down Mode
VIN
2.0
12.6
30.0
V
V
SHUTDOWN QUIESCENT CURRENT
VFB > 1.43 V; VSENSE > 1.1 × VOUT IQ
500
µA
COMPARATOR TRIP POINT
VOLTAGE
ADP30001
1.20
1.245
1.30
V
OUTPUT SENSE VOLTAGE
ADP3000-3.32
3.135 3.3
3.465
5.25
12.60
V
V
V
ADP3000-52
ADP3000-122
VOUT
4.75
5.00
11.40 12.00
COMPARATOR HYSTERESIS
OUTPUT HYSTERESIS
ADP3000
8
12.5
mV
ADP3000-3.3
ADP3000-5
ADP3000-12
32
32
75
50
50
120
mV
mV
mV
OSCILLATOR FREQUENCY
DUTY CYCLE
fOSC
D
350
65
400
80
2
450
kHz
%
VFB > VREF
SWITCH ON TIME
ILIM Tied to VIN, VFB = 0
TA = +25°C
tON
1.5
2.55
µs
SWITCH SATURATION VOLTAGE
STEP-UP MODE
V
V
IN = 3.0 V, ISW = 650 mA
IN = 5.0 V, ISW = 1 A
VSAT
0.5
0.8
1.1
0.75
1.1
1.5
V
V
V
STEP-DOWN MODE
VIN = 12 V, ISW = 650 mA
ADP3000 VFB = 0 V
VSET = VREF
FEEDBACK PIN BIAS CURRENT
SET PIN BIAS CURRENT
GAIN BLOCK OUTPUT LOW
IFB
160
200
0.15
330
400
0.4
nA
nA
V
ISET
VOL
ISINK = 300 µA
VSET = 1.00 V
REFERENCE LINE REGULATION
5 V ≤ VIN ≤ 30 V
2 V ≤ VIN ≤ 5 V
0.02
0.2
0.15
0.6
%/V
%/V
GAIN BLOCK GAIN
RL = 100 kΩ3
AV
1000 6000
V/V
µA
GAIN BLOCK CURRENT SINK
CURRENT LIMIT
VSET ≤ 1 V
ISINK
ILIM
300
400
220 Ω from ILIM to VIN
mA
CURRENT LIMIT TEMPERATURE
COEFFICIENT
–0.3
1
%/°C
µA
SWITCH OFF LEAKAGE CURRENT
Measured at SW1 Pin
10
VSW1 = 12 V, TA = +25°C
MAXIMUM EXCURSION BELOW GND
TA = +25°C
I
SW1 ≤ 10 µA, Switch Off
–400
–350
mV
NOTES
1This specification guarantees that both the high and low trip point of the comparator fall within the 1.20 V to 1.30 V range.
2The output voltage waveform will exhibit a sawtooth shape due to the comparator hysteresis. The output voltage on the fixed output versions will always be within the
specified range.
3100 kΩ resistor connected between a 5 V source and the AO pin.
*All limits at temperature extremes are guaranteed via correlation using standard statistical methods.
Specifications subject to change without notice.
REV. 0
–2–
ADP3000
PIN DESCRIPTIONS
Function
ABSOLUTE MAXIMUM RATINGS
Input Supply Voltage, Step-Up Mode . . . . . . . . . . . . . . . 15 V
Input Supply Voltage, Step-Down Mode . . . . . . . . . . . . . 36 V
SW1 Pin Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 50 V
SW2 Pin Voltage . . . . . . . . . . . . . . . . . . . . . . . . –0.5 V to VIN
Feedback Pin Voltage (ADP3000) . . . . . . . . . . . . . . . . . .5.5 V
Switch Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .1.5 A
Maximum Power Dissipation . . . . . . . . . . . . . . . . . . 500 mW
Operating Temperature Range . . . . . . . . . . . . . 0°C to +70°C
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Lead Temperature (Soldering, 10 sec) . . . . . . . . . . . .+300°C
Thermal Impedance
Mnemonic
ILIM
For normal conditions this pin is connected to
VIN. When lower current is required, a resistor
should be connected between ILIM and VIN.
Limiting the switch current to 400 mA is
achieved by connecting a 220 Ω resistor.
VIN
Input Voltage.
SW1
Collector of power transistor. For step-down
configuration, connect to VIN. For step-up
configuration, connect to an inductor/diode.
SO-8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 170°C/W
N-8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 120°C/W
SW2
Emitter of power transistor. For step-down
configuration, connect to inductor/diode.
For step-up configuration, connect to ground.
Do not allow this pin to go more than a diode
drop below ground.
PIN CONFIGURATIONS
8-Lead Plastic DIP
(N-8)
8-Lead SOIC
(SO-8)
GND
AO
Ground.
1
2
3
4
8
7
6
5
1
2
3
4
8
7
6
5
I
FB (SENSE)*
SET
I
FB (SENSE)*
SET
Auxiliary Gain (GB) output. The open col-
lector can sink 300 µA. It can be left open
if not used.
LIM
LIM
ADP3000
TOP VIEW
(Not to Scale)
ADP3000
TOP VIEW
(Not to Scale)
V
V
IN
IN
SW1
SW2
AO
SW1
SW2
AO
GND
GND
SET
SET Gain amplifier input. The amplifier’s
positive input is connected to SET pin and its
negative input is connected to 1.245 V. It can
be left open if not used.
* FIXED VERSIONS
* FIXED VERSIONS
FB/SENSE
On the ADP3000 (adjustable) version, this pin
is connected to the comparator input. On the
ADP3000-3.3, ADP3000-5 and ADP3000-12,
the pin goes directly to the internal resistor
divider that sets the output voltage.
ORDERING GUIDE
Output
Voltage
Package
Option
Model
ADP3000AN-3.3
ADP3000AR-3.3
3.3 V
3.3 V
N-8
SO-8
ADP3000AN-5
ADP3000AR-5
5 V
5 V
N-8
SO-8
ADP3000AN-12
ADP3000AR-12
12 V
12 V
N-8
SO-8
ADP3000AN
ADP3000AR
Adjustable
Adjustable
N-8
SO-8
N = plastic DIP, SO = small outline package.
SET
SET
A2
A0
A1
A0
V
V
IN
IN
I
I
GAIN BLOCK/
ERROR AMP
GAIN BLOCK/
ERROR AMP
LIM
LIM
SW1
SW1
1.245V
REFERENCE
1.245V
REFERENCE
A1
OSCILLATOR
OSCILLATOR
DRIVER
DRIVER
SW2
SW2
COMPARATOR
COMPARATOR
ADP3000
ADP3000
R1
R2
GND
FB
GND
SENSE
Figure 3a. Functional Block Diagram for Adjustable Version
Figure 3b. Functional Block Diagram for Fixed Version
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the ADP3000 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
REV. 0
–3–
ADP3000–Typical Characteristics
2.5
1400
1200
1.4
1.2
1.0
0.8
V
= 5V @ T = +25°C
A
IN
2.0
QUIESCENT CURRENT @ T = +25°C
A
1000
800
600
400
200
0
1.5
1.0
0.5
0
V
= 12V @ T = +25°C
A
V
= 5V @ T = +25
°
C
IN
IN
A
0.6
0.4
0.2
0.0
V
= 3V @ T = +25°C
A
IN
V
= 2V @ T = +25°C
A
IN
0.1 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.5
0.8
0.9
1.5
3
6
9
12 15 18 21 24 27 30
0.1
0.2
0.3
0.4
0.5
0.6
SWITCH CURRENT – A
INPUT VOLTAGE – V
SWITCH CURRENT – A
Figure 4. Switch ON Voltage vs.
Switch Current in Step-Up Mode
Figure 6. Quiescent Current vs.
Input Voltage
Figure 5. Saturation Voltage vs.
Switch Current in Step-Down Mode
406
1.8
0.8
V
= 12V
T = +25°C
A
OSCILLATOR FREQUENCY –
V
= 5V
IN
T
= 0°C
IN
A
1.6
@ T = +25°C
405
404
403
402
401
400
399
396
A
0.7
0.6
0.5
0.4
0.3
0.2
T
= 0°C
A
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
T
= +25°C
A
T
= +85°C
A
T
A
= +85°C
0.1
0
1
10
100
1k
2
4
6
8
10 12 15 18 21 24 27 30
1
10
100
1k
INPUT VOLTAGE – V
R
– Ω
LIM
R
– Ω
LIM
Figure 8b. Maximum Switch Current
vs. RLIM in Step-Down Mode (12 V)
Figure 7. Oscillator Frequency vs.
Input Voltage
Figure 8a. Maximum Switch Current
vs. RLIM in Step-Down Mode (5 V)
2.30
2.25
2.20
2.15
2.10
2.05
2.00
1.95
1.90
1.85
1.80
1.8
440
430
420
410
400
390
380
370
360
350
V
= 3V
IN
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
T
= 0°C
A
T
= +25°C
A
T
= +85°C
A
340
330
–40
0
25
70
C (T
85
1
10
100
1k
–40
0
25
70
C (T
85
R
– Ω
TEMPERATURE –
°
)
LIM
A
TEMPERATURE –
°
)
A
Figure 8c. Maximum Switch Current
vs. RLIM in Step-Up Mode (3 V)
Figure 10. Switch ON Time vs.
Temperature
Figure 9. Oscillator Frequency vs.
Temperature
REV. 0
–4–
ADP3000
100
90
80
70
60
50
40
30
20
10
0
0.56
0.54
0.52
0.50
0.48
0.46
0.44
0.42
1.25
1.20
1.15
1.10
1.05
1.00
0.95
0.90
V
= 12V @ I = 0.65A
SW
IN
V
= 3V @ I
= 0.65A
IN
SW
–40
0
25
70
C (T
85
–40
0
25
70
C (T )
A
85
–40
0
25
70
C (T
85
TEMPERATURE –
°
)
TEMPERATURE –
°
TEMPERATURE –
°
)
A
A
Figure 11. Duty Cycle vs.
Temperature
Figure 12. Saturation Voltage vs.
Temperature in Step-Up Mode
Figure 13. Switch ON Voltage vs.
Temperature in Step-Down Mode
250
700
350
300
250
200
150
100
50
V
= 20V
IN
600
500
400
300
200
100
0
200
150
100
50
0
–40
0
–40
0
25
70
C (T
85
–40
0
25
70
C (T
85
0
25
70
85
TEMPERATURE –
°
)
TEMPERATURE –
°
)
A
TEMPERATURE – °C (T
)
A
A
Figure 14. Feedback Bias Current
vs. Temperature
Figure 15. Quiescent Current vs.
Temperature
Figure 16. Set Pin Bias Current vs.
Temperature
REV. 0
–5–
ADP3000
THEORY OF OPERATION
APPLICATIONS INFORMATION
COMPONENT SELECTION
Inductor Selection
For most applications the inductor used with the ADP3000 will
fall in the range between 4.7 µH to 33 µH. Table I shows
recommended inductors and their vendors.
The ADP3000 is a versatile, high frequency, switch mode
power supply (SMPS) controller. The regulated output
voltage can be greater than the input voltage (boost or step-up
mode) or less than the input (buck or step-down mode). This
device uses a gated oscillator technique to provide high perfor-
mance with low quiescent current.
When selecting an inductor, it is very important to make sure
that the inductor used with the ADP3000 is able to handle a
current that is higher than the ADP3000’s current limit without
saturation.
A functional block diagram of the ADP3000 is shown in
Figure 3a. The internal 1.245 V reference is connected to one
input of the comparator, while the other input is externally
connected (via the FB pin) to a resistor divider connected to
the regulated output. When the voltage at the FB pin falls below
1.245 V, the 400 kHz oscillator turns on. A driver amplifier
provides base drive to the internal power switch and the switching
action raises the output voltage. When the voltage at the FB
pin exceeds 1.245 V, the oscillator is shut off. While the
oscillator is off, the ADP3000 quiescent current is only 500 µA.
The comparator’s hysteresis ensures loop stability without
requiring external components for frequency compensation.
As a rule of thumb, powdered iron cores saturate softly, whereas
Ferrite cores saturate abruptly. Rod or “open” drum core
geometry inductors saturate gradually. Inductors that saturate
gradually are easier to use. Even though rod or drum core
inductors are attractive in both price and physical size, these
types of inductors must be handled with care because they have
high magnetic radiation. Toroid or “closed” core geometry
should be used when minimizing EMI is critical.
In addition, inductor dc resistance causes power loss. It is best
to use low dc resistance inductors so that power loss in the
inductor is kept to the minimum. Typically, it is best to use an
inductor with a dc resistance lower than 0.2 Ω.
The maximum current in the internal power switch can be set
by connecting a resistor between VIN and the ILIM pin. When
the maximum current is exceeded, the switch is turned OFF.
The current limit circuitry has a time delay of about 0.3 µs. If
an external resistor is not used, connect ILIM to VIN. This
yields the maximum feasible current limit. Further information
on ILIM is included in the “Applications” section of this data
sheet. The ADP3000 internal oscillator provides typically 1.7
µs ON and 0.8 µs OFF times.
Table I. Recommended Inductors
V
endor
Series
Core Type
Phone Numbers
Coiltronics OCTAPAC
Coiltronics UNIPAC
Toroid
Open
(407) 241-7876
(407) 241-7876
An uncommitted gain block on the ADP3000 can be con-
nected as a low battery detector. The inverting input of the
gain block is internally connected to the 1.245 V reference.
The noninverting input is available at the SET pin. A resistor
divider, connected between VIN and GND with the junction
connected to the SET pin, causes the AO output to go LOW
when the low battery set point is exceeded. The AO output is
an open collector NPN transistor that can sink in excess of
300 µA.
Sumida
Sumida
CD43, CD54
CDRH62, CDRH73, Semi-Closed
CDRH64 Geometry
Open
(847) 956-0666
(847) 956-0666
Capacitor Selection
For most applications, the capacitor used with the ADP3000
will fall in the range between 33 µF to 220 µF. Table II shows
recommended capacitors and their vendors.
For input and output capacitors, use low ESR type capacitors
for best efficiency and lowest ripple. Recommended capacitors
include AVX TPS series, Sprague 595D series, Panasonic HFQ
series and Sanyo OS-CON series.
The ADP3000 provides external connections for both the
collector and emitter of its internal power switch, which permits
both step-up and step-down modes of operation. For the step-
up mode, the emitter (Pin SW2) is connected to GND and the
collector (Pin SW1) drives the inductor. For step-down mode,
the emitter drives the inductor while the collector is connected
to VIN.
When selecting a capacitor, it is important to make sure the
maximum capacitor ripple current rms rating is higher than the
ADP3000’s rms switching current.
The output voltage of the ADP3000 is set with two external
resistors. Three fixed voltage models are also available:
ADP3000–3.3 (+3.3 V), ADP3000–5 (+5 V) and ADP3000–12
(+12 V). The fixed voltage models include laser-trimmed
voltage-setting resistors on the chip. On the fixed voltage models
of the ADP3000, simply connect the feedback pin (Pin 8)
directly to the output voltage.
It is best to protect the input capacitor from high turn-on cur-
rent charging surges by derating the capacitor voltage by 2:1.
For very low input or output voltage ripple requirements,
Sanyo OS-CON series capacitors can be used since this type of
capacitor has very low ESR. Alternatively, two or more tanta-
lum capacitors can be used in parallel.
REV. 0
–6–
ADP3000
The delay through the current limiting circuit is approximately
0.3 µs. If the switch ON time is reduced to less than 1.7 µs,
accuracy of the current trip-point is reduced. Attempting to
program a switch ON time of 0.3 µs or less will produce
spurious responses in the switch ON time. However, the
ADP3000 will still provide a properly regulated output voltage.
Table II. Recommended Capacitors
Vendor
Series
Type
Phone Numbers
AVX
Sanyo
Sprague
Panasonic
TPS
OS-CON
595D
Surface Mount
Through-Hole
Surface Mount
Through-Hole
(803) 448-9411
(619) 661-6835
(603) 224-1961
(201) 348-5200
HFQ
PROGRAMMING THE GAIN BLOCK
The gain block of the ADP3000 can be used as a low battery
detector, error amplifier or linear post regulator. The gain block
consists of an op amp with PNP inputs and an open-collector
NPN output. The inverting input is internally connected to the
ADP3000’s 1.245 V reference, while the noninverting input is
available at the SET pin. The NPN output transistor will sink in
excess of 300 µA.
DIODE SELECTION
The ADP3000’s high switching speed demands the use of
Schottky diodes. Suitable choices include the 1N5817, 1N5818,
1N5819, MBRS120LT3 and MBR0520LT1. Do not use fast
recovery diodes because their high forward drop lowers effi-
ciency. Neither general-purpose diodes nor small signal diodes
should be used.
Figure 18 shows the gain block configured as a low battery
monitor. Resistors R1 and R2 should be set to high values to
reduce quiescent current, but not so high that bias current in
the SET input causes large errors. A value of 33 kΩ for R2 is a
good compromise. The value for R1 is then calculated from the
formula:
PROGRAMMING THE SWITCHING CURRENT LIMIT
OF THE POWER SWITCH
The ADP3000’s RLIM pin permits the cycle by cycle switch
current limit to be programmed with a single external resistor.
This feature offers major advantages which ultimately decrease
the component cost and P.C.B. real estate. First, it allows the
ADP3000 to use low value, low saturation current and physi-
cally small inductors. Additionally, it allows the ADP3000 to
use a physically small surface mount tantalum capacitor with a
typical ESR of 0.1 Ω to achieve an output ripple as low as 40
mV to 80 mV, as well as low input ripple.
VLOBATT –1.245V
R1=
1.245V
R2
where VLOBATT is the desired low battery trip point. Since the
gain block output is an open-collector NPN, a pull-up resistor
should be connected to the positive logic power supply.
As a rule of thumb, the current limit is usually set to approximately
3 to 5 times the full load current for boost applications and
about 1.5–3 times of the full load current in buck applications.
5V
R
L
The internal structure of the ILIM circuit is shown in Figure 17.
Q1 is the ADP3000’s internal power switch, which is paralleled
by sense transistor Q2. The relative sizes of Q1 and Q2 are
scaled so that IQ2 is 0.5% of IQ1. Current flows to Q2 through
both an internal 80 Ω resistor and the RLIM resistor. The voltage
on these two resistors biases the base-emitter junction of the
oscillator-disable transistor, Q3. When the voltage across R1
and RLIM exceeds 0.6 V, Q3 turns on and terminates the output
pulse. If only the 80 Ω internal resistor is used (i.e. the ILIM pin
is connected directly to VIN), the maximum switch current will
be 1.5 A. Figure 8a gives values for lower current-limit values.
47kΩ
V
IN
ADP3000
1.245V
REF
R1
V
BATT
AO
TO
SET
PROCESSOR
R2
33kΩ
GND
1.6MΩ
R
HYS
V
– 1.245V
LB
R1 =
37.7µA
V
= BATTERY TRIP POINT
LB
Figure 18. Setting the Low Battery Detector Trip Point
R
LIM
(EXTERNAL)
V
IN
I
V
LIM
IN
80Ω
(INTERNAL)
R1
Q3
I
Q1
ADP3000
SW1
200
Q1
DRIVER
Q2
400kHz
OSC
POWER
SWITCH
SW2
Figure 17. ADP3000 Current Limit Operation
REV. 0
–7–
ADP3000
The circuit of Figure 18 may produce multiple pulses when
approaching the trip point due to noise coupled into the SET
input. To prevent multiple interrupts to the digital logic,
hysteresis can be added to the circuit (Figure 18). Resistor RHYS
with a value of 1 MΩ to 10 MΩ, provides the hysteresis. The
addition of RHYS will change the trip point slightly, so the new
value for R1 will be:
Step-Down
1
VO
VIN – VCE
2 IO
ISW
PD
=
ISW VCESAT 1+
+ I
[
V
[
]
]
Q
IN
,
β
SAT
(
)
where: ISW is ILIMIT in the case of current limit is programmed
externally or maximum inductor current in the case of
current limit is not programmed eternally.
VLOBATT –1.245V
R1=
VCE(SAT) = Check this value by applying ISW to Figure 8b.
1.2 V is typical value.
1.245V
R2
VL −1.245V
RL + RHYS
−
D = 0.75 (Typical Duty Ratio for a Single Switching
where VL is the logic power supply voltage, RL is the pull-up
resistor, and RHYS creates the hysteresis.
Cycle).
VO = Output Voltage.
IO = Output Current.
POWER TRANSISTOR PROTECTION DIODE IN STEP-
DOWN CONFIGURATION
When operating the ADP3000 in the step-down mode, the
output voltage is impressed across the internal power switch’s
emitter-base junction when the switch is off. In order to protect
the switch, a Schottky diode must be placed in a series with
SW2 when the output voltage is set to higher than 6 V. Figure
19 shows the proper way to place the protection diode, D2.
The selection of this diode is identical to the step-down commut-
ing diode (see Diode Selection section for information).
V
IN = Input Voltage.
IQ = 500 µA (Typical Shutdown Quiescent Current).
β = 30 (Typical Forced Beta).
The temperature rise can be calculated from:
∆T = PD ×θJA
where:
∆T = Temperature Rise.
PD = Device Power Dissipation.
θJA = Thermal Resistance (Junction-to-Ambient).
V
IN
D1, D2 = 1N5818 SCHOTTKY DIODES
+
R3
C2
1
2
3
As example, consider a boost converter with the following
specifications:
V
> 6V
OUT
I
V
SW1
LIM
IN
FB
8
4
VIN = 2 V, IO = 180 mA, VO = 3.3 V.
ADP3000
D2
D1
L1
R2
R1
SW2
I
SW = 0.8 A (Externally Programmed).
GND
5
+
C1
With Step-Up Power Dissipation Equation:
(2)(0.8)
30
2
3.3
(4) 0.18
0.8
PD = 0.82 × 1+
0.75 1–
+ 500E − 6
[
2
][ ]
[
]
Figure 19. Step-Down Model VOUT > 6.0 V
THERMAL CONSIDERATIONS
Power dissipation internal to the ADP3000 can be approximated
with the following equations.
= 185 mW
Using the SO-8 Package: ∆T = 185 mW (170°C/W) = 31.5°C.
Using the N-8 Package: ∆T = 185 mW (120°C/W) = 22.2°C.
At a 70°C ambient, die temperature would be 101.45°C for
SO-8 package and 92.2°C for N-8 package. These junction
temperatures are well below the maximum recommended
junction temperature of 125°C.
Step-Up
VIN ISW
VIN 4IO
VO ISW
P
D = ISW 2R +
D 1–
+ I
[
V
Q IN
]
[
]
β
Finally, the die temperature can be decreased up to 20% by
using a large metal ground plate as ground pickup for the
ADP3000.
where: ISW is ILIMIT in the case of current limit programmed
externally, or maximum inductor current in the case of
current limit not programmed externally.
R = 1 Ω (Typical RCE(SAT)).
D = 0.75 (Typical Duty Ratio for a Single Switching
Cycle).
VO = Output Voltage.
IO = Output Current.
VIN = Input Voltage.
IQ = 500 µA (Typical Shutdown Quiescent Current).
β = 30 (Typical Forced Beta)
REV. 0
–8–
ADP3000
Typical Application Circuits
L1
15µH
L1
1N5817
6.8µH 1N5817
V
IN
4.5V → 5.5V
V
V
IN
2V → 3.2V
OUT
V
OUT
+
C1
100µF
10V
12V
50mA
124Ω
+
C1
100µF
10V
3.3V
180mA
120Ω
1
2
1
2
I
LIM
V
IN
I
LIM
V
IN
3
8
SW1
3
8
SW1
ADP3000-12V
ADP3000-3.3V
SENSE
SENSE
+
SW2
4
C2
GND
5
+
SW2
4
C2
100µF
10V
GND
5
100µF
16V
L1 = SUMIDA CD54-150
L1 = SUMIDA CD43-6R8
C1, C2 = AVX TPS D107 M010R100
TYPICAL EFFICIENCY = 75%
C1 = AVX TPS D107 M010R0100
C2 = AVX TPS E107 M016R0100
TYPICAL EFFICIENCY = 75%
Figure 23. 4.5 V to 12 V/ 50 mA Step-Up Converter
Figure 20. 2 V to 3.3 V/180 mA Step-Up Converter
V
IN
L1
6.8µH 1N5817
5V → 6V
+
V
C1
100µF
10V
IN
120Ω
V
OUT
2V → 3.2V
+
C1
100µF
10V
5V
100mA
120Ω
1
2
3
I
V
SW1
LIM
1
IN
2
FB
8
4
I
LIM
V
IN
L1
10µH
3
8
SW1
ADP3000-ADJ
ADP3000-5V
SW2
GND
V
OUT
SENSE
R2
150kΩ
3V
100mA
5
GND
5
+
SW2
4
C2
100µF
10V
+
C2
100µF
10V
L1 = SUMIDA CD43-100
D1
IN5817
R1
110kΩ
C1, C2 = AVX TPS D107 M010R100
TYPICAL EFFICIENCY = 75%
L1 = SUMIDA CD43-6R8
C1, C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 80%
Figure 24. 5 V to 3 V/100 mA Step-Down Converter
Figure 21. 2 V to 5 V/100 mA Step-Up Converter
V
L1
IN
6.8µH 1N5817
10V → 13V
V
+
IN
C1
33µF
20V
250Ω
V
OUT
2.7V → 4.5V
+
C1
100µF
10V
5V
150mA
120Ω
1
2
3
I
V
SW1
1
2
LIM
IN
SENSE
I
8
4
LIM
V
IN
L1
10µH
3
8
SW1
ADP3000-5V
ADP3000-5V
SW2
V
GND
5
SENSE
OUT
5V
+
GND
5
SW2
4
C2
100µF
10V
250mA
C2
+
L1 = SUMIDA CD43-100
D1
100µF
10V
C1 = AVX TPS D336 M020R0200
C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 77%
IN5817
L1 = SUMIDA CD43-6R8
C1, C2 = AVX TPS D107 M010R100
TYPICAL EFFICIENCY = 80%
Figure 25. 10 V to 5 V/250 mA Step-Down Converter
Figure 22. 2.7 V to 5 V/150 mA Step-Up Converter
REV. 0
–9–
ADP3000
V
IN
5V
+
C1
47µF
16V
240Ω
1
2
3
I
V
SW1
LIM
IN
SENSE
8
4
L1
15µH
ADP3000-5V
SW2
GND
+
C2
5
D1
IN5817
100µF
10V
V
OUT
L1 = SUMIDA CD53-150
–5V
100mA
C1 = AVX TPS D476 M016R0150
C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 60%
Figure 26. 5 V to –5 V/100 mA Inverter
(SUMIDA – CDRH62)
2.5V → 4.2V
330kΩ
100kΩ
120Ω
6.8µH
2N2907
IN5817
+
–
100µF
10V
I
V
LIM
IN
V
IN1
IN2
O1
3V
100mA
AVX-TPS
100kΩ
10kΩ
1µF
6V
(MLC)
SET
SW1
100µF
10V
AVX-TPS
+
–
33nF
348kΩ
1%
1MΩ
ADP3302AR1
90kΩ
ADP3000
1µF
6V
(MLC)
90kΩ
FB
A
O
SD
200kΩ
1%
V
3V
100mA
O2
GND SW2
GND
Figure 27. 1 Cell LI-ION to 3 V/200 mA Converter with Shutdown at VIN ≤ 2.5 V
AT V ≤ 2.5V
IN
80
SHDN IQ = 500µA
I
= 50mA + 50mA
O
75
70
65
I
= 100mA + 100mA
O
V
IN
(V)
2.6
3.0
3.4
3.8
4.2
Figure 28. Typical Efficiency of the Circuit of Figure 27
REV. 0
–10–
ADP3000
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead Plastic DIP
(N-8)
8-Lead SOIC
(SO-8)
0.1968 (5.00)
0.1890 (4.80)
0.430 (10.92)
0.348 (8.84)
8
5
8
1
5
4
0.1574 (4.00)
0.1497 (3.80)
0.2440 (6.20)
0.2284 (5.80)
0.280 (7.11)
0.240 (6.10)
4
1
0.325 (8.25)
0.300 (7.62)
0.060 (1.52)
0.015 (0.38)
PIN 1
PIN 1
0.0688 (1.75)
0.0532 (1.35)
0.0196 (0.50)
x 45°
0.195 (4.95)
0.115 (2.93)
0.0098 (0.25)
0.0040 (0.10)
0.210 (5.33)
MAX
0.0099 (0.25)
0.130
(3.30)
MIN
0.160 (4.06)
0.115 (2.93)
8°
0°
0.015 (0.381)
0.008 (0.204)
0.0500
(1.27)
BSC
0.0192 (0.49)
0.0138 (0.35)
SEATING
PLANE
0.100
(2.54)
BSC
0.022 (0.558)
0.014 (0.356)
0.070 (1.77)
0.045 (1.15)
SEATING
PLANE
0.0098 (0.25)
0.0075 (0.19)
0.0500 (1.27)
0.0160 (0.41)
REV. 0
–11–
–12–
相关型号：
SI9130DB
5- and 3.3-V Step-Down Synchronous ConvertersWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9135LG-T1
SMBus Multi-Output Power-Supply ControllerWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9135LG-T1-E3
SMBus Multi-Output Power-Supply ControllerWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9135_11
SMBus Multi-Output Power-Supply ControllerWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9136_11
Multi-Output Power-Supply ControllerWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9130CG-T1-E3
Pin-Programmable Dual Controller - Portable PCsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9130LG-T1-E3
Pin-Programmable Dual Controller - Portable PCsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9130_11
Pin-Programmable Dual Controller - Portable PCsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9137
Multi-Output, Sequence Selectable Power-Supply Controller for Mobile ApplicationsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9137DB
Multi-Output, Sequence Selectable Power-Supply Controller for Mobile ApplicationsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9137LG
Multi-Output, Sequence Selectable Power-Supply Controller for Mobile ApplicationsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
SI9122E
500-kHz Half-Bridge DC/DC Controller with Integrated Secondary Synchronous Rectification DriversWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
-
VISHAY
©2020 ICPDF网 联系我们和版权申明