EVAL-AD7631CBZ [ADI]
18-Bit, 250 kSPS, Differential Programmable Input PulSAR® ADC; 18位， 250 kSPS时，差分可编程输入PulSAR® ADC
| 型号： | EVAL-AD7631CBZ |
| 厂家： | 
ADI |
| 描述： | 18-Bit, 250 kSPS, Differential Programmable Input PulSAR® ADC |
| 文件： | 总32页 (文件大小：681K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
18-Bit, 250 kSPS, Differential
Programmable Input PulSAR® ADC
AD7631
FEATURES
FUNCTIONAL BLOCK DIAGRAM
TEMP REFBUFIN REF REFGND VCC VEE DVDD DGND
Multiple pins/software-programmable input ranges
+5 V (10 V p-p), +10 V (20 V p-p), 5 V (20 V p-p),
10 V (40 V p-p)
Pins or serial SPI-compatible input ranges/mode selection
Throughput: 250 kSPS
INL: 1.5 LSB typical, 2.5 LSB maximum ( 9.5 ppm of FSR)
18-bit resolution with no missing codes
Dynamic range: 102.5 dB
OVDD
AGND
AD7631
REF
OGND
AVDD
PDREF
PDBUF
IN+
AMP
SERIAL DATA
PORT
REF
SERIAL
CONFIGURATION
PORT
18
SWITCHED
CAP DAC
D[17:0]
BUSY
RD
IN–
PARALLEL
INTERFACE
SNR: 101 dB @ 2 kHz
THD: −112 dB @ 2 kHz
iCMOS® process technology
5 V internal reference: typical drift 3 ppm/°C; TEMP output
No pipeline delay (SAR architecture)
Parallel (18-/16-/8-bit bus) and serial 5 V/3.3 V interface
SPI-/QSPI™-/MICROWIRE™-/DSP-compatible
Power dissipation
CS
CLOCK
CNVST
PD
D0/OB/2C
D1/A0
CONTROL LOGIC AND
CALIBRATION CIRCUITRY
RESET
D2/A1
BIPOLAR TEN
MODE0
MODE1
Figure 1.
Table 1. 48-Lead PulSAR Selection
73 mW @ 250 kSPS
10 mW @ 1 kSPS
Pb-free, 48-lead LQFP and 48-lead LFCSP (7 mm × 7 mm)
100 to
250
(kSPS)
500 to
570
570 to
1000
Res
(Bits)
>1000
(kSPS)
Input Type
(kSPS)
(kSPS)
Bipolar
14
14
AD7951
AD7952
APPLICATIONS
Process controls
High speed data acquisition
Digital signal processing
Spectrum analysis
ATE
Differential
Bipolar
Unipolar
16
AD7651
AD7660
AD7661
AD7650
AD7652
AD7664
AD7666
AD7653
AD7667
GENERAL DESCRIPTION
Bipolar
16
16
AD7610
AD7663
AD7665
AD7612
AD7671
The AD7631 is an 18-bit, charge redistribution, successive
approximation register (SAR), architecture analog-to-digital
converter (ADC) fabricated on Analog Devices, Inc.’s iCMOS
high voltage process. The device is configured through hardware
or via a dedicated write-only serial configuration port for input
range and operating mode. The AD7631 contains a high speed
18-bit sampling ADC, an internal conversion clock, an internal
reference (and buffer), error correction circuits, and both serial
Differential
Unipolar
AD7675
AD7676
AD7677
AD7621
AD7622
AD7623
Simultaneous/
16
AD7654
AD7655
Multichannel
Unipolar
Differential
Unipolar
18
18
AD7678
AD7631
AD7679
AD7674
AD7634
AD7641
AD7643
CNVST
and parallel system interface ports. A falling edge on
Differential
Bipolar
samples the fully differential analog inputs on IN+ and IN−.
The AD7631 features four different analog input ranges. Power is
scaled linearly with throughput. Operation is specified from
−40°C to +85°C.
Rev. A
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700 www.analog.com
Fax: 781.461.3113 ©2007–2011 Analog Devices, Inc. All rights reserved.
AD7631
TABLE OF CONTENTS
Features .............................................................................................. 1
Driver Amplifier Choice ........................................................... 20
Voltage Reference Input/Output .............................................. 21
Power Supplies............................................................................ 22
Conversion Control ................................................................... 23
Interfaces.......................................................................................... 24
Digital Interface.......................................................................... 24
Parallel Interface......................................................................... 24
Serial Interface............................................................................ 25
Master Serial Interface............................................................... 25
Slave Serial Interface .................................................................. 26
Hardware Configuration........................................................... 29
Software Configuration............................................................. 29
Microprocessor Interfacing....................................................... 30
Application Information................................................................ 31
Layout Guidelines....................................................................... 31
Evaluating Performance ............................................................ 31
Outline Dimensions....................................................................... 32
Ordering Guide .......................................................................... 32
Applications....................................................................................... 1
General Description......................................................................... 1
Functional Block Diagram .............................................................. 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Timing Specifications .................................................................. 5
Absolute Maximum Ratings............................................................ 7
ESD Caution.................................................................................. 7
Pin Configuration and Function Descriptions............................. 8
Typical Performance Characteristics ........................................... 12
Terminology .................................................................................... 16
Theory of Operation ...................................................................... 17
Overview...................................................................................... 17
Converter Operation.................................................................. 17
Transfer Functions...................................................................... 18
Typical Connection Diagram ................................................... 18
Analog Inputs.............................................................................. 19
REVISION HISTORY
3/11—Rev. 0 to Rev. A
Changes to Resolution Parameter, Table 2.................................... 3
Changes to Figure 4 and Table 6..................................................... 8
Added Exposed Pad Notation to Outline Dimensions ............. 32
2/07—Revision 0: Initial Version
Rev. A | Page 2 of 32
AD7631
SPECIFICATIONS
AVDD = DVDD = 5 V; OVDD = 2.7 V to 5.5 V; VCC = 15 V; VEE = −15 V; VREF = 5 V; all specifications TMIN to TMAX, unless otherwise noted.
Table 2.
Parameter
Conditions/Comments
Min
Typ
Max
Unit
RESOLUTION
18
Bits
ANALOG INPUTS
Differential Voltage Range, VIN
0 V to 5 V
0 V to 10 V
5 V
10 V
Operating Voltage Range
0 V to 5 V
0 V to 10 V
(VIN+) − (VIN−
)
VIN = 10 V p-p
VIN = 20 V p-p
VIN = 20 V p-p
VIN = 40 V p-p
VIN+, VIN− to AGND
−VREF
+VREF
V
V
V
V
−2 VREF
−2 VREF
−4 VREF
+2 VREF
+2 VREF
+4 VREF
−0.1
−0.1
−5.1
−10.1
+5.1
+10.1
+5.1
V
V
V
V
5 V
10 V
+10.1
Common-Mode Voltage Range
5 V
10 V
VIN+, VIN−
VREF/2 − 0.1
VREF − 0.2
−0.1
VREF/2
VREF
0
VREF/2 + 0.1
VREF + 0.2
+0.1
V
V
V
Bipolar Ranges
Analog Input CMRR
Input Current
fIN = 100 kHz
250 kSPS throughput
See Analog Inputs section
75
dB
μA
801
Input Impedance
THROUGHPUT SPEED
Complete Cycle
Throughput Rate
DC ACCURACY
Integral Linearity Error2
No Missing Codes
Differential Linearity Error2
Transition Noise
Unipolar Zero Error
Bipolar Zero Error
Zero-Error Temperature Drift
Bipolar Full-Scale Error
Unipolar Full-Scale Error
Full-Scale Error Temperature Drift
Power Supply Sensitivity
AC ACCURACY
4.0
250
μs
kSPS
250 kSPS throughput
−2.5
18
−1
1.5
0.75
0.5
+2.5
+2.5
LSB3
Bits
LSB
LSB
−0.06
−0.03
+0.06
+0.03
%FS
%FS
ppm/°C
%FS
%FS
ppm/°C
LSB
−0.09
−0.07
+0.09
+0.07
0.5
3
AVDD = 5 V 5%
Dynamic Range
VIN = 0 to 5 V, fIN = 2 kHz, −60 dB
VIN = all other input ranges, fIN = 2 kHz, −60 dB
VIN = 0 to 5 V, fIN = 2 kHz
VIN = all other input ranges, fIN = 2 kHz
fIN = 2 kHz
fIN = 2 kHz
fIN = 2 kHz
VIN = 0 V to 5 V
100
100
99.5
100
101.8
102.5
100.5
101
100
112
dB4
dB
dB
dB
dB
dB
dB
MHz
Signal-to-Noise Ratio
Signal-to-(Noise + Distortion), SINAD
Total Harmonic Distortion
Spurious-Free Dynamic Range
−3 dB Input Bandwidth
SAMPLING DYNAMICS
Aperture Delay
113
45
2
5
ns
ps rms
ns
Aperture Jitter
Transient Response
Full-scale step
500
Rev. A | Page 3 of 32
AD7631
Parameter
Conditions/Comments
PDREF = PDBUF = low
REF @ 25°C
–40°C to +85°C
AVDD = 5 V 5%
1000 hours
Min
Typ
Max
Unit
INTERNAL REFERENCE
Output Voltage
Temperature Drift
Line Regulation
Long-Term Drift
Turn-On Settling Time
REFERENCE BUFFER
REFBUFIN Input Voltage Range
EXTERNAL REFERENCE
Voltage Range
Current Drain
TEMPERATURE PIN
Voltage Output
Temperature Sensitivity
Output Resistance
DIGITAL INPUTS
Logic Levels
4.965
5.000
3
15
50
10
5.035
V
ppm/°C
ppm/V
ppm
ms
CREF = 22 μF
PDREF = high
2.4
2.5
2.6
V
PDREF = PDBUF = high
REF
250 kSPS throughput
4.75
5
250
AVDD + 0.1
V
μA
@ 25°C
311
1
4.33
mV
mV/°C
kΩ
VIL
VIH
IIL
IIH
−0.3
2.1
−1
+0.6
OVDD + 0.3
+1
+1
V
V
μA
μA
−1
DIGITAL OUTPUTS
Data Format
Pipeline Delay5
VOL
Parallel or serial 18-bit
ISINK = 500 μA
ISOURCE = −500 μA
0.4
V
V
VOH
OVDD − 0.6
POWER SUPPLIES
Specified Performance
AVDD
DVDD
OVDD
VCC
VEE
Operating Current7
AVDD
4.756
4.75
2.7
5
5
5.25
5.25
5.25
15.75
0
V
V
V
V
V
7
15
−15
−15.75
@ 250 kSPS throughput
With Internal Reference8
With Internal Reference Disabled8
DVDD
OVDD
VCC
8.5
6.1
4
0.1
1.4
0.8
0.7
mA
mA
mA
mA
mA
mA
mA
VCC = 15 V, with internal reference buffer
VCC = 15 V
VEE = −15 V
VEE
Power Dissipation
@ 250 kSPS throughput
With Internal Reference8
With Internal Reference Disabled8
In Power-Down Mode9
TEMPERATURE RANGE10
Specified Performance
94
73
10
120
100
mW
mW
μW
PD = high
TMIN to TMAX
−40
+85
°C
1 In all input ranges, the input current scales with throughput. See the Analog Inputs section.
2 Linearity is tested using endpoints, not best fit. All linearity is tested with an external 5 V reference.
3 LSB means least significant bit. All specifications in LSB do not include the error contributed by the reference.
4 All specifications in decibels are referred to a full-scale range input, FSR. Tested with an input signal at 0.5 dB below full-scale, unless otherwise specified.
5 Conversion results are available immediately after completed conversion.
6 4.75 V or VREF − 0.1 V, whichever is larger.
7 Tested in parallel reading mode.
8 With internal reference, PDREF = PDBUF = low; with internal reference disabled, PDREF = PDBUF = high. With internal reference buffer, PDBUF = low.
9 With all digital inputs forced to OVDD.
10 Consult sales for extended temperature range.
Rev. A | Page 4 of 32
AD7631
TIMING SPECIFICATIONS
AVDD = DVDD = 5 V; OVDD = 2.7 V to 5.5 V; VCC = 15 V; VEE = −15 V; VREF = 5 V; all specifications TMIN to TMAX, unless otherwise noted.
Table 3.
Parameter
Symbol Min
Typ
Max
Unit
CONVERSION AND RESET (See Figure 35 and Figure 36)
Convert Pulse Width
Time Between Conversions
CNVST Low to BUSY High Delay
BUSY High All Modes (Except Master Serial Read After Convert)
Aperture Delay
End of Conversion to BUSY Low Delay
Conversion Time
t1
t2
t3
t4
t5
t6
t7
t8
t9
10
4.0
ns
μs
ns
μs
ns
ns
μs
ns
ns
35
1.68
2
10
1.68
Acquisition Time
RESET Pulse Width
2.32
10
PARALLEL INTERFACE MODES (See Figure 37 and Figure 39)
CNVST Low to DATA Valid Delay
DATA Valid to BUSY Low Delay
Bus Access Request to DATA Valid
Bus Relinquish Time
1.65
t10
t11
t12
t13
μs
ns
ns
ns
20
2
40
15
MASTER SERIAL INTERFACE MODES1 (See Figure 41 and Figure 42)
CS Low to SYNC Valid Delay
t14
t15
t16
t17
t18
t19
t20
t21
t22
t23
t24
t25
t26
t27
t28
t29
t30
10
10
10
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
CS Low to Internal SDCLK Valid Delay1
CS Low to SDOUT Delay
CNVST Low to SYNC Delay, Read During Convert
SYNC Asserted to SDCLK First Edge Delay
Internal SDCLK Period2
530
3
30
15
10
4
5
5
45
Internal SDCLK High2
Internal SDCLK Low2
SDOUT Valid Setup Time2
SDOUT Valid Hold Time2
SDCLK Last Edge to SYNC Delay2
CS High to SYNC HIGH-Z
10
10
10
CS High to Internal SDCLK HIGH-Z
CS High to SDOUT HIGH-Z
BUSY High in Master Serial Read After Convert2
CNVST Low to SYNC Delay, Read After Convert
SYNC Deasserted to BUSY Low Delay
See Table 4
1.5
μs
ns
25
SLAVE SERIAL/SERIAL CONFIGURATION INTERFACE MODES1
(See Figure 44, Figure 45, and Figure 47)
External SDCLK, SCCLK Setup Time
External SDCLK Active Edge to SDOUT Delay
SDIN/SCIN Setup Time
t31
t32
t33
t34
t35
t36
t37
5
2
5
5
25
10
10
ns
ns
ns
ns
ns
ns
ns
18
SDIN/SCIN Hold Time
External SDCLK/SCCLK Period
External SDCLK/SCCLK High
External SDCLK/SCCLK Low
1 In serial interface modes, the SYNC, SDSCLK, and SDOUT timings are defined with a maximum load CL of 10 pF; otherwise, the load is 60 pF maximum.
2 In serial master read during convert mode. See Table 4 for serial master read after convert mode.
Rev. A | Page 5 of 32
AD7631
Table 4. Serial Clock Timings in Master Read After Convert Mode
DIVSCLK[1]
0
0
1
1
DIVSCLK[0]
Symbol
0
1
0
1
Unit
ns
ns
ns
ns
ns
ns
ns
ns
SYNC to SDCLK First Edge Delay Minimum
Internal SDCLK Period Minimum
Internal SDCLK Period Maximum
Internal SDCLK High Minimum
Internal SDCLK Low Minimum
SDOUT Valid Setup Time Minimum
SDOUT Valid Hold Time Minimum
SDCLK Last Edge to SYNC Delay Minimum
BUSY High Width Maximum
t18
t19
t19
t20
t21
t22
t23
t24
t28
3
20
60
90
30
25
20
8
20
120
180
60
55
20
35
35
5.00
20
30
45
15
10
4
5
5
2.55
240
360
120
115
20
90
90
8.20
7
3.40
μs
1.6mA
I
OL
TO OUTPUT
PIN
1.4V
C
L
60pF
2V
0.8V
tDELAY
500µA
I
OH
tDELAY
NOTES
1. IN SERIAL INTERFACE MODES, THE SYNC, SDCLK,
AND SDOUT ARE DEFINED WITH A MAXIMUM LOAD
2V
2V
0.8V
0.8V
C
OF 10pF; OTHERWISE, THE LOAD IS 60pF MAXIMUM.
L
Figure 2. Load Circuit for Digital Interface Timing,
SDOUT, SYNC, and SDCLK Outputs, CL = 10 pF
Figure 3. Voltage Reference Levels for Timing
Rev. A | Page 6 of 32
AD7631
ABSOLUTE MAXIMUM RATINGS
Table 5.
Parameter
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Rating
Analog Inputs/Outputs
IN+1, IN−1 to AGND
REF, REFBUFIN, TEMP,
REFGND to AGND
Ground Voltage Differences
AGND, DGND, OGND
Supply Voltages
VEE − 0.3 V to VCC + 0.3 V
AVDD + 0.3 V to
AGND − 0.3 V
0.3 V
AVDD, DVDD, OVDD
AVDD to DVDD, AVDD to OVDD
DVDD to OVDD
−0.3 V to +7 V
7 V
7 V
ESD CAUTION
VCC to AGND, DGND
VEE to GND
Digital Inputs
–0.3 V to +16.5 V
+0.3 V to −16.5 V
−0.3 V to OVDD + 0 .3 V
20 mA
PDREF, PDBUF
Internal Power Dissipation2
Internal Power Dissipation3
Junction Temperature
Storage Temperature Range
700 mW
2.5 W
125°C
−65°C to +125°C
1 See the Analog Inputs section.
2 Specification is for the device in free air: 48-lead LFQP; θJA = 91°C/W and θJC = 30°C/W.
3 Specification is for the device in free air: 48-lead LFCSP; θJA = 26°C/W.
Rev. A | Page 7 of 32
AD7631
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
48 47 46 45 44 43 42 41 40 39 38 37
1
36
35
34
33
32
31
30
29
28
27
26
25
AGND
BIPOLAR
CNVST
PD
PIN 1
2
3
AVDD
MODE0
MODE1
D0/OB/2C
OGND
4
RESET
CS
5
AD7631
6
RD
TOP VIEW
7
OGND
TEN
(Not to Scale)
8
BUSY
D1/A0
D2/A1
9
D17/SCCS
D16/SCCLK
D15/SCIN
D14/HW/SW
10
11
12
D3
D4/DIVSCLK[0]
D5/DIVSCLK[1]
13 14 15 16 17 18 19 20 21 22 23 24
NOTES
1. FOR THE LEAD FRAME CHIP SCALE PACKAGE (LFCSP), THE EXPOSED PAD
SHOULD BE CONNECTED TO VEE. THIS CONNECTION IS NOT REQUIREDTO
MEET THE ELECTRICAL PERFORMANCES.
Figure 4. Pin Configuration
Table 6. Pin Function Descriptions
Pin No.
Mnemonic
Type1 Description
1, 42
AGND
P
Analog Power Ground Pins. Ground reference point for all analog I/O. All analog I/O should be
referenced to AGND and should be connected to the analog ground plane of the system. In addition,
the AGND, DGND, and OGND voltages should be at the same potential.
2, 44
3, 4
AVDD
MODE[0:1]
P
DI
Analog Power Pins. Nominally 4.75 V to 5.25 V and decoupled with 10 μF and 100 nF capacitors.
Data Input/Output Interface Mode Selection.
Interface Mode
MODE1
Low
Low
High
High
MODE0
Low
High
Low
Description
0
1
2
3
18-bit interface
16-bit interface
8-bit (byte) interface
Serial interface
High
5
D0/OB/2C
DI/O2 In 18-bit parallel mode, this output is used as Bit 0 of the parallel port data output bus, and the data
coding is straight binary. In all other modes, this pin allows the choice of straight binary or twos
complement.
When OB/2C = high, the digital output is straight binary.
When OB/2C = low, the MSB is inverted resulting in a twos complement output from its internal
shift register.
6, 7, 17
OGND
D1/A0
D2/A1
D3
P
Input/Output Interface Digital Power Ground. Ground reference point for digital outputs. Should
be connected to the system digital ground ideally at the same potential as AGND and DGND.
When MODE[1:0] = 0, this pin is Bit 1 of the parallel port data output bus. In all other modes, this
input pin controls the form in which data is output as shown in Table 7.
When MODE[1:0] = 0, this pin is Bit 2 of the parallel port data output bus.
When MODE[1:0] = 1 or 2, this input pin controls the form in which data is output as shown in Table 7.
8
DI/O
DI/O
DO
9
10
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 3 of the parallel port data output bus.
This pin is always an output, regardless of the interface mode.
Rev. A | Page 8 of 32
AD7631
Pin No.
Mnemonic
D[4:5] or
DIVSCLK[0:1]
Type1 Description
11, 12
DI/O
When MODE[1:0] = 0, 1, or 2, these pins are Bit 4 and Bit 5 of the parallel port data output bus.
When MODE[1:0] = 3, serial data clock division selection. When using serial master read after convert
mode (EXT/INT = low, RDC/SDIN = low), these inputs can be used to slow down the internally generated
serial clock that clocks the data output. In other serial modes, these pins are high impedance outputs.
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 6 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Data Clock Source Select. In serial mode, this input is used to select the
internally generated (master) or the external (slave) serial data clock for the AD7631 output data.
When EXT/INT = low (master mode), the internal serial data clock is selected on SDCLK output.
When EXT/INT = high (slave mode), the output data is synchronized to an external clock signal (gated by CS)
connected to the SDCLK input.
13
14
D6 or
EXT/INT
DO/I
D7 or
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 7 of the parallel port data output bus.
DI/O
INVSYNC
When MODE[1:0] = 3, Serial Data Invert Sync Select. In serial master mode (MODE[1:0] = 3,
EXT/INT = low), this input is used to select the active state of the SYNC signal.
When INVSYNC = low, SYNC is active high.
When INVSYNC = high, SYNC is active low.
15
16
D8 or
INVSCLK
DI/O
DI/O
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 8 of the parallel port data output bus.
When MODE[1:0] = 3, Invert SDCLK/SCCLK Select. This input is used to invert both SDCLK and SCCLK.
When INVSCLK = low, the rising edge of SDCLK/SCCLK are used.
When INVSCLK = high, the falling edge of SDCLK/SCCLK are used.
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 9 of the parallel port data output bus.
D9 or
RDC or
When MODE[1:0] = 3, Serial Data Read During Convert. In serial master mode (MODE[1:0] = 3,
EXT/INT = low), RDC is used to select the read mode. See the Master Serial Interface section.
When RDC = low, the current result is read after conversion. Note the maximum throughput is
not attainable in this mode.
When RDC = high, the previous conversion result is read during the current conversion.
SDIN
When MODE[1:0] = 3, Serial Data In. In serial slave mode (MODE[1:0] = 3, EXT/INT = high), SDIN can
be used as a data input to daisy-chain the conversion results from two or more ADCs onto a single
SDOUT line. The digital data level on SDIN is output on SDOUT with a delay of 16 SDCLK periods after
the initiation of the read sequence.
18
19
20
21
OVDD
DVDD
DGND
P
Input/Output Interface Digital Power. Nominally at the same supply as the supply of the host
interface 2.5 V, 3 V, or 5 V and decoupled with 10 ꢀF and 100 nF capacitors.
Digital Power. Nominally at 4.75 V to 5.25 V and decoupled with 10 ꢀF and 100 nF capacitors. Can
be supplied from AVDD.
Digital Power Ground. Ground reference point for digital outputs. Should be connected to system
digital ground ideally at the same potential as AGND and OGND.
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 10 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Data Output. In all serial modes, this pin is used as the serial data output
synchronized to SDCLK. Conversion results are stored in an on-chip register. The AD7631 provides
the conversion result, MSB first, from its internal shift register. The data format is determined by
the logic level of OB/2C.
P
P
D10 or
SDOUT
DI/O
When EXT/INT = low (master mode), SDOUT is valid on both edges of SDCLK.
When EXT/INT = high (slave mode):
When INVSCLK = low, SDOUT is updated on SDCLK rising edge.
When INVSCLK = high, SDOUT is updated on SDCLK falling edge.
22
D11 or
SDCLK
DI/O
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 11 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Data Clock. In all serial modes, this pin is used as the serial data clock
input or output, dependent on the logic state of the EXT/INT pin. The active edge where the data
SDOUT is updated depends on the logic state of the INVSCLK pin.
Rev. A | Page 9 of 32
AD7631
Pin No.
Mnemonic
Type1 Description
23
D12 or
SYNC
DO
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 12 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Data Frame Synchronization. In serial master mode (MODE[1:0] = 3,
EXT/INT= low), this output is used as a digital output frame synchronization for use with the
internal data clock.
When a read sequence is initiated and INVSYNC = low, SYNC is driven high and remains high while
the SDOUT output is valid.
When a read sequence is initiated and INVSYNC = high, SYNC is driven low and remains low while
the SDOUT output is valid.
24
25
D13 or
RDERROR
DO
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 13 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Data Read Error. In serial slave mode (MODE[1:0] = 3, EXT/INT = high),
this output is used as an incomplete data read error flag. If a data read is started and not completed when
the current conversion is completed, the current data is lost and RDERROR is pulsed high.
D14 or
DI/O
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 14 of the parallel port data output bus.
HW/SW
When MODE[1:0] = 3, Serial Configuration Hardware/Software Select. In serial mode, this input is
used to configure the AD7631 by hardware or software. See the Hardware Configuration section and
Software Configuration section.
When HW/SW = low, the AD7631 is configured through software using the serial configuration register.
When HW/SW = high, the AD7631 is configured through dedicated hardware input pins.
26
27
D15 or
SCIN
DI/O
DI/O
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 15 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Configuration Data Input. In serial software configuration mode (HW/SW =
low), this input is used to serially write in, MSB first, the configuration data into the serial configuration
register. The data on this input is latched with SCCLK. See the Software Configuration section.
D16 or
SCCLK
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 16 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Configuration Clock. In serial software configuration mode (HW/SW = low)
this input is used to clock in the data on SCIN. The active edge where the data SCIN is updated
depends on the logic state of the INVSCLK pin. See the Software Configuration section.
28
29
D17 or
SCCS
DI/O
DO
When MODE[1:0] = 0, 1, or 2, this output is used as Bit 17 of the parallel port data output bus.
When MODE[1:0] = 3, Serial Configuration Chip Select. In serial software configuration mode
(HW/SW = low), this input enables the serial configuration port. See the Software Configuration section.
BUSY
Busy Output. Transitions high when a conversion is started and remains high until the conversion is
complete and the data is latched into the on-chip shift register. The falling edge of BUSY can be used
as a data-ready clock signal. Note that in master read after convert mode (MODE[1:0] = 3, EXT/INT = low,
RDC = low) the busy time changes according to Table 4.
30
TEN
DI2
Input Range Select. Used in conjunction with BIPOLAR per the following.
Input Range (V)
BIPOLAR TEN
0 to 5
0 to 10
5
Low
Low
High
High
Low
High
Low
High
10
31
32
RD
CS
DI
DI
Read Data. When CS and RD are both low, the interface parallel or serial output bus is enabled.
Chip Select. When CS and RD are both low, the interface parallel or serial output bus is enabled. CS
is also used to gate the external clock in slave serial mode (not used for serial configurable port).
33
34
RESET
PD
DI
Reset Input. When high, reset the AD7631. Current conversion, if any, is aborted. The falling edge of
RESET resets the data outputs to all zeros (with OB/2C = high) and clears the configuration register.
See the Digital Interface section. If not used, this pin can be tied to OGND.
Power-Down Input. When PD = high, power down the ADC. Power consumption is reduced and
conversions are inhibited after the current one is completed. The digital interface remains active
during power down.
DI2
35
36
CNVST
DI
Conversion Start. A falling edge on CNVST puts the internal sample-and-hold into the hold state and
initiates a conversion.
Input Range Select. See description for Pin 30.
BIPOLAR
DI2
Rev. A | Page 10 of 32
AD7631
Pin No.
Mnemonic
Type1 Description
37
REF
AO/I
Reference Input/Output. When PDREF/PDBUF = low, the internal reference and buffer are enabled
producing 5 V on this pin. When PDREF/PDBUF = high, the internal reference and buffer are disabled,
allowing an externally supplied voltage reference up to AVDD volts. Decoupling with at least a 22 ꢀF
capacitor is required with or without the internal reference and buffer. See the Voltage Reference
Input/Output section.
38
39
REFGND
IN−
AI
AI
Reference Input Analog Ground. Connected to analog ground plane.
Analog Input. Referenced to IN+.
In the 0 V to 5 V input range, IN− is between 0 V and VREF V centered about VREF/2. In the 0 V to 10 V
range, IN− is between 0 V and 2 VREF V centered about VREF
.
In the 5 V and 10 V ranges, IN− is true bipolar up to 2 VREF V ( 5 V range) or 4 VREF V ( 10 V range)
and centered about 0 V.
In all ranges, IN− must be driven 180° out of phase with IN+.
40
41
43
VCC
VEE
IN+
P
P
AI
High Voltage Positive Supply. Normally +7 V to +15 V.
High Voltage Negative Supply. Normally 0 V to −15 V (0 V in unipolar ranges).
Analog Input. Referenced to IN−.
In the 0 V to 5 V input range, IN+ is between 0 V and VREF V centered about VREF/2. In the 0 V to 10 V
range, IN+ is between 0 V and 2 VREF V centered about VREF
.
In the 5 V and 10 V ranges, IN+ is true bipolar up to 2 VREF V ( 5 V range) or 4 VREF V ( 10 V range)
and centered about 0 V.
In all ranges, IN+ must be driven 180° out of phase with IN−.
45
46
47
48
49
TEMP
AO
AI
Temperature Sensor Analog Output. When the internal reference is enabled (PDREF = PDBUF = low),
this pin outputs a voltage proportional to the temperature of the AD7631. See the Voltage Reference
Input/Output section.
Reference Buffer Input. When using an external reference with the internal reference buffer (PDBUF = low,
PDREF = high), applying 2.5 V on this pin produces 5 V on the REF pin. See the Voltage Reference
Input/Output section.
Internal Reference Power-Down Input.
When low, the internal reference is enabled.
When high, the internal reference is powered down, and an external reference must be used.
Internal Reference Buffer Power-Down Input.
When low, the buffer is enabled (must be low when using internal reference).
When high, the buffer is powered down.
Exposed Pad. The exposed pad is not connected internally. It is recommended that the pad be soldered
to VEE.
REFBUFIN
PDREF
PDBUF
EPAD3
DI
DI
NC
1 AI = analog input; AI/O = bidirectional analog; AO = analog output; DI = digital input; DI/O = bidirectional digital; DO = digital output; P = power, NC = no internal
connection.
2
SW
In serial configuration mode (MODE[1:0] = 3, HW/
= low), this input is programmed with the serial configuration register and this pin is a don’t care. See the
Hardware Configuration section and the Software Configuraion section.
3 LFCSP_VQ package only.
Table 7. Data Bus Interface Definition
MODE MODE1 MODE0
2C D1/A0 D2/A1 D[3] D[4:9] D[10:11] D[12:15] D[16:17] Description
D0/OB/
R[0]
0
1
1
2
2
2
2
3
0
0
0
1
1
1
1
1
0
1
1
0
0
0
0
1
R[1]
R[2]
R[3]
R[3]
R[1]
R[4:9]
R[4:9]
R[10:11]
R[10:11]
R[12:15]
R[12:15]
R[16:17]
R[16:17]
18-bit parallel
16-bit high word
16-bit low word
8-bit high byte
8-bit midbyte
8-bit low byte
8-bit low byte
Serial interface
OB/2C
OB/2C
OB/2C
OB/2C
OB/2C
OB/2C
OB/2C
A0 = 0 R[2]
A0 = 1 R[0]
A0 = 0 A1 = 0
A0 = 0 A1 = 1
A0 = 1 A1 = 0
A0 = 1 A1 = 1
All High-Z
All zeros
All High-Z
All High-Z
All High-Z
All High-Z
R[10:11]
R[2:3]
R[12:15]
R[4:7]
R[16:17]
R[8:9]
R[0:1]
All zeros
R[0:1]
All zeros
Serial interface
Rev. A | Page 11 of 32
AD7631
TYPICAL PERFORMANCE CHARACTERISTICS
AVDD = DVDD = 5 V; OVDD = 5 V; VCC = 15 V; VEE = −15 V; VREF = 5 V; TA = 25°C.
2.5
2.0
2.5
f
= 250kSPS
POSITIVE DNL = 0.68 LSB
NEGATIVE DNL = –0.75 LSB
f
= 250kSPS
POSITIVE INL = 1.15 LSB
NEGATIVE INL = –0.94 LSB
S
S
2.0
1.5
1.5
1.0
1.0
0.5
0.5
0
0
–0.5
–1.0
–1.5
–2.0
–2.5
–0.5
–1.0
–1.5
–2.0
–2.5
0
65536
131072
CODE
196608
262144
0
65536
131072
CODE
196608
262144
Figure 5. Integral Nonlinearity vs. Code, Bipolar 10 V Range
Figure 8. Differential Nonlinearity vs. Code, Bipolar 10 V Range
60
60
NEGATIVE DNL
POSITIVE DNL
NEGATIVE INL
POSITIVE INL
50
50
40
30
20
10
0
40
30
20
10
0
–2.0 –1.6 –1.2 –0.8 –0.4
0
0.4
0.8
1.2
1.6
2.0
–2.0 –1.6 –1.2 –0.8 –0.4
0
0.4
0.8
1.2
1.6
2.0
DNL DISTRIBUTION (LSB)
INL DISTRIBUTION (LSB)
Figure 9. Differential Nonlinearity Distribution, Bipolar 5 V Range
(86 Devices)
Figure 6. Integral Nonlinearity Distribution, Unipolar 10 V Range
(86 Devices)
60000
70000
56811
σ = 0.75
σ = 0.80
54874
59925
60000
50000
40000
30000
20000
10000
0
50000
40000
34164
32769
30000
20000
10000
11838
20000
6901
2172
1997
349
294
25
20
0
0
5
0
0
0
0
0
0
0
1FFFC
1FFFE
20002
20004
20006
1FFFE
20000
20002
20004
20006
20008
CODE IN HEX
CODE IN HEX
Figure 10. Histogram of 261,120 Conversions of a DC Input
at the Code Transition, Bipolar 5 V Range
Figure 7. Histogram of 261,120 Conversions of a DC Input
at the Code Center, Bipolar 5 V Range
Rev. A | Page 12 of 32
AD7631
103.0
102.5
102.0
101.5
101.0
100.5
100.0
0
–20
±5V
fS = 250kSPS
fIN = 20.1kHz
SNR = 98.3dB
THD = –116.8dB
SFDR = 121dB
SINAD = 97.8dB
SNR
SINAD
±10V
–40
–60
0V TO 10V
–80
–100
–120
–140
–160
–180
0V TO 5V
–60
–50
–40
–30
–20
–10
0
0
50
100
150
200
250
300
FREQUENCY (kHz)
INPUT LEVEL (dB)
Figure 11. FFT 20 kHz, Bipolar 5 V Range, Internal Reference
Figure 14. SNR and SINAD vs. Input Level (Referred to Full Scale)
100
98
96
94
92
90
88
86
84
82
80
18.0
–70
140
120
100
80
SFDR
17.5
17.0
16.5
16.0
15.5
15.0
14.5
14.0
13.5
13.0
–80
–90
SNR
SINAD
ENOB
–100
–110
–120
–130
–140
SECOND
HARMONIC
THD
60
40
20
THIRD
HARMONIC
0
1000
1
10
100
1000
1
10
100
FREQUENCY (kHz)
FREQUENCY (kHz)
Figure 12. SNR, SINAD, and ENOB vs. Frequency, Unipolar 5 V Range
Figure 15. THD, Harmonics, and SFDR vs. Frequency, Unipolar 5 V Range
103
103
±5V
±10V
±5V
±10V
102
101
100
99
102
101
100
99
0V TO 10V
0V TO 10V
0V TO 5V
0V TO 5V
98
98
97
–55
97
–55
–35
–15
5
25
45
65
85
105
125
–35
–15
5
25
45
65
85
105
125
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 16. SINAD vs. Temperature
Figure 13. SNR vs. Temperature
Rev. A | Page 13 of 32
AD7631
–104
–108
–112
–116
–120
–124
–128
132
128
124
120
116
112
108
104
±10V
±5V
0V TO 10V
0V TO 5V
0V TO 5V
±10V
0V TO 10V
±5V
5
–132
–55
–35
–15
25
45
65
85
105
125
–55
–35
–15
5
25
45
65
85
105
125
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 20. SFDR vs. Temperature (Excludes Harmonics)
Figure 17. THD vs. Temperature
5.0080
5.0060
5.0040
5.0020
5.0000
4.9980
4.9960
4.9940
4.9920
20
16
12
8
ZERO/OFFSET ERROR
4
0
POSITIVE
FULL-SCALE ERROR
–4
–8
–12
–16
NEGATIVE
FULL-SCALE ERROR
–20
–55
–35
–15
5
25
45
65
85
105
125
–55
–35
–15
5
25
45
65
85
105
125
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 18. Zero/Offset Error, Positive and Negative Full-Scale Error vs.
Temperature, All Normalized to 25°C
Figure 21. Typical Reference Voltage Output vs. Temperature (3 Devices)
60
50
40
30
20
10
0
100000
10000
DVDD
1000
100
AVDD
10
VCC +15V
1
VEE –15V
0.1
0.01
OVDD
PDREF = PDBUF = HIGH
10000 100000 1000000
SAMPLING RATE (SPS)
0.001
0
1
2
3
4
5
6
7
8
10
100
1000
REFERENCE DRIFT (ppm/°C)
Figure 19. Reference Voltage Temperature Coefficient Distribution (247 Devices)
Figure 22. Operating Currents vs. Sample Rate
Rev. A | Page 14 of 32
AD7631
50
45
40
35
30
25
20
15
10
5
700
600
500
400
300
200
100
0
PD = PDBUF = PDREF = HIGH
OVDD = 2.7V @ 85°C
OVDD = 2.7V @ 25°C
VEE, –15V
VCC, +15V
DVDD
OVDD = 5V @ 85°C
OVDD
AVDD
OVDD = 5V @ 25°C
0
0
50
100
(pF)
150
200
–55
–35
–15
5
25
45
65
85
105
TEMPERATURE (°C)
C
L
Figure 23. Power-Down Operating Currents vs. Temperature
Figure 24. Typical Delay vs. Load Capacitance CL
Rev. A | Page 15 of 32
AD7631
TERMINOLOGY
Least Significant Bit (LSB)
Total Harmonic Distortion (THD)
The least significant bit, or LSB, is the smallest increment that
can be represented by a converter. For a fully differential input
ADC with N bits of resolution, the LSB expressed in volts is
THD is the ratio of the rms sum of the first five harmonic
components to the rms value of a full-scale input signal and is
expressed in decibels.
VINp-p
LSB (V) =
2N
Signal-to-(Noise + Distortion) Ratio (SINAD)
SINAD is the ratio of the rms value of the actual input signal to
the rms sum of all other spectral components below the Nyquist
frequency, including harmonics but excluding dc. The value for
SINAD is expressed in decibels.
Integral Nonlinearity Error (INL)
Linearity error refers to the deviation of each individual code
from a line drawn from negative full-scale through positive full-
scale. The point used as negative full-scale occurs a ½ LSB
before the first code transition. Positive full-scale is defined as a
level 1½ LSBs beyond the last code transition. The deviation is
measured from the middle of each code to the true straight line.
Spurious-Free Dynamic Range (SFDR)
The difference, in decibels (dB), between the rms amplitude of
the input signal and the peak spurious signal.
Effective Number of Bits (ENOB)
Differential Nonlinearity Error (DNL)
ENOB is a measurement of the resolution with a sine wave
input. It is related to SINAD and is expressed in bits by
In an ideal ADC, code transitions are 1 LSB apart. Differential
nonlinearity is the maximum deviation from this ideal value. It
is often specified in terms of resolution for which no missing
codes are guaranteed.
ENOB = [(SINADdB − 1.76)/6.02]
Aperture Delay
Bipolar Zero Error
Aperture delay is a measure of the acquisition performance
CNVST
measured from the falling edge of the
input to when
The difference between the ideal midscale input voltage (0 V)
and the actual voltage producing the midscale output code.
the input signal is held for a conversion.
Transient Response
Unipolar Offset Error
The time required for the AD7631 to achieve its rated accuracy
after a full-scale step function is applied to its input.
The first transition should occur at a level ½ LSB above analog
ground. The unipolar offset error is the deviation of the actual
transition from that point.
Reference Voltage Temperature Coefficient
Full-Scale Error
The reference voltage temperature coefficient is derived from
the typical shift of output voltage at 25°C on a sample of parts at
The last transition (from 111…10 to 111…11 in straight binary
format) should occur for an analog voltage 1½ LSB below the
nominal full scale. The full-scale error is the deviation in LSB
(or % of full-scale range) of the actual level of the last transition
from the ideal level and includes the effect of the offset error.
Closely related is the gain error (also in LSB or % of full-scale
range), which does not include the effects of the offset error.
the maximum and minimum reference output voltage (VREF
)
measured at TMIN, T (25°C), and TMAX. It is expressed in ppm/°C as
VREF (Max)–VREF (Min)
TCVREF (ppm/°C) =
×106
VREF (25°C) × (TMAX –TMIN
)
where:
Dynamic Range
V
V
V
REF (Max) = maximum VREF at TMIN, T (25°C), or TMAX.
Dynamic range is the ratio of the rms value of the full scale to
the rms noise measured for an input typically at −60 dB. The
value for dynamic range is expressed in decibels.
REF (Min) = minimum VREF at TMIN, T (25°C), or TMAX
.
REF (25°C) = VREF at 25°C.
TMAX = +85°C.
MIN = –40°C.
Signal-to-Noise Ratio (SNR)
T
SNR is the ratio of the rms value of the actual input signal to the
rms sum of all other spectral components below the Nyquist
frequency, excluding harmonics and dc. The value for SNR is
expressed in decibels.
Rev. A | Page 16 of 32
AD7631
THEORY OF OPERATION
IN+
AGND
LSB
SWITCHES
CONTROL
SW+
MSB
131,072C
65,536C
65,536C
4C
4C
2C
2C
C
C
C
C
BUSY
REF
CONTROL
LOGIC
COMP
REFGND
OUTPUT
CODE
131,072C
MSB
SW–
LSB
CNVST
AGND
IN–
Figure 25. ADC Simplified Schematic
OVERVIEW
CONVERTER OPERATION
The AD7631 is a very fast, low power, precise, 18-bit ADC
using successive approximation, capacitive digital-to-analog
(CDAC) architecture.
The AD7631 is a successive approximation ADC based on a
charge redistribution DAC. Figure 25 shows the simplified
schematic of the ADC. The CDAC consists of two identical
arrays of 18 binary weighted capacitors, which are connected
to the two comparator inputs.
The AD7631 can be configured at any time for one of four input
ranges with inputs in parallel and serial hardware modes or by a
dedicated write-only, SPI-compatible interface via a configuration
register in serial software mode. The AD7631 uses Analog
Devices’ patented iCMOS high voltage process to accommodate
0 V to +5 V (10 V p-p), 0 V to +10 V (20 V p-p), 5 V (20 V p-p),
and 10 V (40 V p-p) input ranges on the fully differential IN+
and IN− inputs without the use of conventional thin films. Only
one acquisition cycle, t8, is required for the inputs to latch to
the correct configuration. Resetting or power cycling is not
required for reconfiguring the ADC.
During the acquisition phase, terminals of the array tied to the
comparator’s input are connected to AGND via SW+ and SW−.
All independent switches are connected to the analog inputs.
Therefore, the capacitor arrays are used as sampling capacitors
and acquire the analog signal on IN+ and IN− inputs. A
conversion phase is initiated once the acquisition phase is
CNVST
complete and the
input goes low. When the conversion
phase begins, SW+ and SW− are opened first. The two capacitor
arrays are then disconnected from the inputs and connected to the
REFGND input. Therefore, the differential voltage between the
inputs (IN+ and IN−) captured at the end of the acquisition
phase is applied to the comparator inputs, causing the comparator
to become unbalanced. By switching each element of the
capacitor array between REFGND and REF, the comparator
input varies by binary weighted voltage steps (VREF/2, VREF/4
through VREF/262,144). The control logic toggles these switches,
starting with the MSB first, to bring the comparator back into a
balanced condition.
The AD7631 is capable of converting 250,000 samples per
second (250 kSPS) and power consumption scales linearly with
throughput, making it useful for battery-powered systems.
The AD7631 provides the user with an on-chip track-and-hold,
successive approximation ADC that does not exhibit any pipe-
line or latency, making it ideal for multiple, multiplexed channel
applications.
For unipolar input ranges, the AD7631 typically requires three
supplies: VCC, AVDD (which can supply DVDD), and OVDD
(which can be interfaced to either 5 V, 3.3 V, or 2.5 V digital logic).
For bipolar input ranges, the AD7631 requires the use of the
additional VEE supply.
After the completion of this process, the control logic generates
the ADC output code and brings the BUSY output low.
The device is housed in a Pb-free, 48-lead LQFP or a tiny,
48-lead, 7 mm × 7 mm LFCSP that combines space savings with
flexibility. In addition, the AD7631 can be configured as either a
parallel or serial SPI-compatible interface.
Rev. A | Page 17 of 32
AD7631
TRANSFER FUNCTIONS
TYPICAL CONNECTION DIAGRAM
2C
Figure 27 shows a typical connection diagram for the AD7631
using the internal reference, serial data interface, and serial
configuration port. Different circuitry from that shown in
Figure 27 is optional and is discussed in the following sections.
Using the D0/OB/ digital input or via the configuration
register, except in 18-bit parallel interface mode, the AD7631
offers two output codings: straight binary and twos
complement. See Figure 26 and Table 8 for the ideal transfer
characteristic and digital output codes for the different analog
input ranges, VIN. Note that when using the configuration
2C
register, the D0/OB/ input is a don’t care and should be tied
to either high or low.
111...111
111...110
111...101
000...010
000...001
000...000
–FSR + 1 LSB
+FSR – 1 LSB
+FSR – 1.5 LSB
ANALOG INPUT
–FSR
–FSR + 0.5 LSB
Figure 26. ADC Ideal Transfer Function
Table 8. Output Codes and Ideal Input Voltages
VREF = 5 V
Digital Output Code
V
IN = 0 V to 5 V VIN = 0 V to 10 V VIN
=
5 V
VIN = 10 V
Description
FSR − 1 LSB
FSR − 2 LSB
Midscale + 1 LSB
Midscale
(10 V p-p)
+4.999962 V
+4.999924 V
+38.15 μV
0 V
(20 V p-p)
+9.999924 V
+9.999847 V
−76.29 μV
0 V
(20 V p-p)
+9.999924 V
+9.999847 V
−76.29 μV
0 V
(40 V p-p)
+19.999847 V
+19.999695 V
+152.59 μV
0 V
Straight Binary
0x3FFFF1
0x3FFFE
Twos Complement
0x1FFFF1
0x1FFFE
0x20001
0x00001
0x20000
0x00000
Midscale − 1 LSB
−FSR + 1 LSB
−FSR
−38.15 μV
−4.999962 V
−5 V
−76.29 μV
−9.999924 V
−10 V
−76.29 μV
−9.999924 V
−10 V
−152.59 μV
−19.999847 V
−20 V
0x1FFFF
0x00001
0x000002
0x3FFFF
0x20001
0x200002
1 This is also the code for overrange analog input.
2 This is also the code for underrange analog input.
Rev. A | Page 18 of 32
AD7631
DIGITAL
SUPPLY (5V)
NOTE 5
DIGITAL
10Ω
INTERFACE
SUPPLY
ANALOG
SUPPLY (5V)
(2.5V, 3.3V, OR 5V)
10µF
100nF
10µF
10µF
100nF
100nF
AVDD AGND DGND
VCC
DVDD
OVDD
OGND
®
+7V TO +15.75V
MicroConverter
/
SUPPLY
MICROPROCESSOR/
DSP
BUSY
100nF
10µF
10µF
SDCLK
SDOUT
SERIAL
PORT 1
100nF
SCCLK
–7V TO –15.75V
SUPPLY
SERIAL
PORT 2
VEE
SCIN
NOTE 6
NOTE 3
REF
SCCS
C
REF
22µF
REFBUFIN
REFGND
NOTE 7
NOTE 4
33Ω
100nF
D
CNVST
AD7631
D0/OB/2C
NOTE 2
U1
OVDD
ANALOG
INPUT+
MODE[1:0]
15Ω
IN+
HW/SW
BIPOLAR
C
2.7nF
C
TEN
CLOCK
IN–
NOTE 3
PDREF PDBUF
NOTE 2
U1
ANALOG
INPUT–
PD
RD
CS RESET
15Ω
C
2.7nF
C
DGND
AGND
NOTE 1
NOTE 8
NOTES
1. ANALOG INPUTS ARE DIFFERENTIAL (ANTIPHASE). SEE ANALOG INPUTS SECTION.
2. THE AD8021 IS RECOMMENDED. SEE DRIVER AMPLIFIER CHOICE SECTION.
3. THE CONFIGURATION SHOWN IS USING THE INTERNAL REFERENCE. SEE VOLTAGE REFERENCE INPUT/OUTPUT SECTION.
4. A 22µF CERAMIC CAPACITOR (X5R, 1206 SIZE) IS RECOMMENDED (FOR EXAMPLE, PANASONIC ECJ4YB1A226M).
SEE VOLTAGE REFERENCE INPUT/OUTPUT SECTION.
5. OPTIONAL, SEE POWER SUPPLIES SECTION.
6. THE VCC AND VEE SUPPLIES SHOULD BE VCC = [VIN(MAX) + 2V] AND VEE = [VIN(MIN) – 2V] FOR BIPOLAR INPUT RANGES.
FOR UNIPOLAR INPUT RANGES, VEE CAN BE 0V. SEE POWER SUPPLIES SECTION.
7. OPTIONAL LOW JITTER CNVST, SEE CONVERSION CONTROL SECTION.
8. A SEPARATE ANALOG AND DIGITAL GROUND PLANE IS RECOMMENDED, CONNECTED TOGETHER DIRECTLY UNDER THE ADC.
SEE LAYOUT GUIDELINES SECTION.
Figure 27. Typical Connection Diagram Shown with Serial Interface and Serial Programmable Port
Input Structure
ANALOG INPUTS
Figure 28 shows an equivalent circuit for the input structure of
the AD7631.
Input Range Selection
In parallel mode and serial hardware mode, the input range is
selected by using the BIPOLAR (bipolar) and TEN (10 V range)
inputs. See Table 6 for pin details and the Hardware
0V TO 5V
RANGE ONLY
AVDD
VCC
Configuration section and the Software Configuration section for
programming the mode selection with either pins or the
configuration register. Note that when using the configuration
register, the BIPOLAR and TEN inputs are don’t cares and
should be tied high or low.
D1
D2
D3
C
R
IN
IN
IN+ OR IN–
VEE
C
D4
PIN
AGND
Figure 28. Simplified Analog Input
Rev. A | Page 19 of 32
AD7631
The four diodes, D1 to D4, provide ESD protection for the analog
inputs, IN+ and IN−. Care must be taken to ensure that the analog
input signal never exceeds the supply rails by more than 0.3 V,
because this causes the diodes to become forward-biased and to
start conducting current. These diodes can handle a forward-
biased current of 120 mA maximum. For instance, these conditions
could eventually occur when the input buffer’s U1 supplies are
different from AVDD, VCC, and VEE. In such a case, an input
buffer with a short-circuit current limitation can be used to protect
the part although most op amps’ short-circuit current is <100 mA.
Note that D3 and D4 are only used in the 0 V to 5 V range to
allow for additional protection in applications that are switching
from the higher voltage ranges.
amount of THD that can be tolerated. The THD degrades as a
function of the source impedance and the maximum input
frequency, as shown in Figure 30.
–70
200Ω
–90
100Ω
33Ω
–110
15Ω
This analog input structure of the AD7631 is a true differential
structure allowing the sampling of the differential signal between
IN+ and IN−. By using this differential input, small signals
common to both inputs are rejected, as shown in Figure 29,
which represents the typical CMRR over frequency.
–130
25
50
75
100
0
FREQUENCY (kHz)
Figure 30. THD vs. Analog Input Frequency and Source Resistance
120
DRIVER AMPLIFIER CHOICE
0V TO 10V
Although the AD7631 is easy to drive, the driver amplifier must
meet the following requirements:
100
±5V
0V TO 5V
80
•
For multichannel, multiplexed applications, the driver
amplifier and the AD7631 analog input circuit must be
able to settle for a full-scale step of the capacitor array
at a 18-bit level (0.0004%). For the amplifier, settling at
0.1% to 0.01% is more commonly specified. This differs
significantly from the settling time at a 18-bit level and
should be verified prior to driver selection. The AD8021 op
amp combines ultralow noise with high gain bandwidth and
meets this settling time requirement even when used with
gains of up to 13.
±10V
60
40
20
0
1
10
100
1000
10000
FREQUENCY (kHz)
Figure 29. Analog Input CMRR vs. Frequency
•
The noise generated by the driver amplifier needs to be
kept as low as possible to preserve the SNR and transition
noise performance of the AD7631. The noise coming from
the driver is filtered by the external, 1-pole, low-pass filter,
as shown in Figure 27. The SNR degradation due to the
amplifier is
During the acquisition phase for ac signals, the impedance of
the analog inputs, IN+ and IN−, can be modeled as a parallel
combination of Capacitor CPIN and the network formed by
the series connection of RIN and CIN. CPIN is primarily the pin
capacitance. RIN is typically 5 kΩ and is a lumped component
comprised of serial resistors and the on resistance of the switches.
SNRLOSS
=
C
IN is primarily the ADC sampling capacitor and, depending on
⎛
⎞
⎟
the input range selected, is typically 48 pF in the 0 V to 5 V range,
typically 24 pF in the 0 V to 10 V and 5 V ranges, and typically
12 pF in the 10 V range. During the conversion phase, when the
⎜
VNADC
⎜
⎟
⎟
⎟
⎠
20log
⎜
⎜
⎝
π
2
π
2
2
VNADC
+
f−3dB (NeN+ )2 + f−3dB (NeN−
)
2
switches are opened, the input impedance is limited to CPIN
.
where:
Because the input impedance of the AD7631 is very high, it can
be directly driven by a low impedance source without gain
error. To further improve the noise filtering achieved by the
AD7631 analog input circuit, an external, one-pole RC filter
between the amplifier’s outputs and the ADC analog inputs
can be used, as shown in Figure 27. However, large source
impedances significantly affect the ac performance, especially
the THD. The maximum source impedance depends on the
V
NADC is the noise of the ADC, which is
2VINp-p
2 2
SNR
VNADC
=
20
10
f
–3dB is the cutoff frequency of the input filter (3.9 MHz).
Rev. A | Page 20 of 32
AD7631
15Ω
VCC
VEE
OUT+
OUT–
N is the noise factor of the amplifier (1 in buffer
configuration).
IN+
2.7nF
R
R
F
G
AD7631
ANALOG IN
INPUT
e
N+ and eN− are the equivalent input voltage noise densities
15Ω
U2
IN–
ADA4922-1
REF
of the op amps connected to IN+ and IN−, in nV/√Hz.
This approximation can be utilized when the resistances
used around the amplifiers are small. If larger resistances are
used, their noise contributions should also be root-sum
squared.
2.7nF
REF
R2
R1
10µF
100nF
Figure 31. Single-to-Differential Driver Using the ADA4922-1
•
The driver needs to have a THD performance suitable to
that of the AD7631. Figure 15 shows the THD vs. frequency
that the driver should exceed.
For unipolar 5 V and 10 V input ranges, the internal (or
external) reference source can be used to level shift U2 for
the correct input span. If using an external reference, the values
for R1/R2 can be lowered to reduce resistive Johnson noise
(1.29E − 10 × √R). For the bipolar 5 V and 10 V input
ranges, the reference connection is not required because the
common-mode voltage is 0 V. See Table 10 for the different
input ranges for R1/R2.
The AD8021 meets these requirements and is appropriate for
almost all applications. The AD8021 needs a 10 pF external
compensation capacitor that should have good linearity as an
NPO ceramic or mica type. Moreover, the use of a noninverting
+1 gain arrangement is recommended and helps to obtain the
best signal-to-noise ratio.
Table 10.R1/R2 Configuration
The AD8022 can also be used when a dual version is needed
and a gain of 1 is present. The AD829 is an alternative in
applications where high frequency performance (above 100 kHz)
is not required. In applications with a gain of 1, an 82 pF
Input Range (V) R1 (Ω) R2 (Ω) Common-Mode Voltage (V)
5
2.5 k
2.5 k
2.5 k
Open
100
2.5
5
10
5, 10
0
compensation capacitor is required. The AD8610 is an option
when low bias current is needed in low frequency applications.
This circuit can also be made discretely, and thus more flexible,
using any of the recommended low noise amplifiers in Table 9.
Again, to preserve the SNR of the converter, the resistors RF and
RG should be kept low.
Because the AD7631 uses a large geometry, high voltage input
switch, the best linearity performance is obtained when using
the amplifier at its maximum full power bandwidth. Gaining
the amplifier to make use of the more dynamic range of the
ADC results in increased linearity errors. For applications
requiring more resolution, the use of an additional amplifier
with gain should precede a unity follower driving the AD7631.
See Table 9 for a list of recommended op amps.
VOLTAGE REFERENCE INPUT/OUTPUT
The AD7631 allows the choice of either a very low temperature
drift internal voltage reference, an external reference, or an
external buffered reference.
The internal reference of the AD7631 provides excellent
performance and can be used in almost all applications.
However, the linearity performance is guaranteed only with
an external reference.
Table 9. Recommended Driver Amplifiers
Amplifier
Typical Application
AD829
15 V supplies, very low noise, low frequency
12 V supplies, very low noise, high frequency
12 V supplies, very low noise, high frequency, dual
12 V supplies, low noise, high frequency,
single-ended-to-differential driver
AD8021
AD8022
ADA4922-1
Internal Reference (REF = 5 V)(PDREF = Low,
PDBUF = Low)
To use the internal reference, the PDREF and PDBUF inputs
must be low. This enables the on-chip band gap reference, buffer,
and TEMP sensor resulting in a 5.00 V reference on the REF pin.
AD8610/
AD8620
13 V supplies, low bias current, low frequency,
single/dual
The internal reference is temperature-compensated to 5.000 V
35 mV. The reference is trimmed to provide a typical drift of
3 ppm/°C. This typical drift characteristic is shown in Figure 19.
Single-to-Differential Driver
For single-ended sources, a single-to-differential driver, such
as the ADA4922-1, can be used because the AD7631 needs to
be driven differentially. The 1-pole filter using R = 15 Ω and
C = 2.7 nF provides a corner frequency of 3.9 MHz.
Rev. A | Page 21 of 32
AD7631
TEMP
External 2.5 V Reference and Internal Buffer (REF = 5 V)
(PDREF = High, PDBUF = Low)
ADG779
TEMPERATURE
SENSOR
IN+
To use an external reference with the internal buffer, PDREF
should be high and PDBUF should be low. This powers down
the internal reference and allows the 2.5 V reference to be applied
to REFBUFIN producing 5 V on the REF pin. The internal
reference buffer is useful in multiconverter applications because
a buffer is typically required in these applications to avoid
reference coupling amongst the different converters.
ANALOG INPUT
AD7631
C
C
Figure 32. Use of the Temperature Sensor
POWER SUPPLIES
The AD7631 uses five sets of power supply pins:
•
•
•
•
•
AVDD: analog 5 V core supply
External 5 V Reference (PDREF = High, PDBUF = High)
VCC: analog high voltage positive supply
VEE: high voltage negative supply
DVDD: digital 5 V core supply
To use an external reference directly on the REF pin, PDREF
and PDBUF should both be high. PDREF and PDBUF power
down the internal reference and the internal reference buffer,
respectively. For improved drift performance, an external
reference, such as the ADR445 or ADR435, is recommended.
OVDD: digital input/output interface supply
Reference Decoupling
Core Supplies
Whether using an internal or external reference, the AD7631
voltage reference input (REF) has a dynamic input impedance;
therefore, it should be driven by a low impedance source with
efficient decoupling between the REF and REFGND inputs. This
decoupling depends on the choice of the voltage reference but
usually consists of a low ESR capacitor connected to REF and
REFGND with minimum parasitic inductance. A 22 μF (X5R,
1206 size) ceramic chip capacitor (or 47 μF low ESR tantalum
capacitor) is appropriate when using either the internal
reference or the ADR445/ADR435 external reference.
The AVDD and DVDD supply the AD7631 analog and digital
cores, respectively. Sufficient decoupling of these supplies is
required consisting of at least a 10 ꢀF capacitor and a 100 nF
capacitor on each supply. The 100 nF capacitors should be
placed as close as possible to the AD7631. To reduce the number
of supplies needed, the DVDD can be supplied through a simple
RC filter from the analog supply, as shown in Figure 27.
High Voltage Supplies
The high voltage bipolar supplies, VCC and VEE, are required
and must be at least 2 V larger than the maximum input voltage.
For example, if using the 10 V range, the supplies should be
12 V minimum. This allows for 40 V p-p fully differential
input ( 10 V on each input IN+ and IN−). Sufficient decoupling of
these supplies is also required consisting of at least a 10 ꢀF
capacitor and a 100 nF capacitor on each supply. For unipolar
operation, the VEE supply can be grounded with some slight
THD performance degradation.
The placement of the reference decoupling is also important to
the performance of the AD7631. The decoupling capacitor should
be mounted on the same side as the ADC right at the REF pin
with a thick PCB trace. The REFGND should also connect to
the reference decoupling capacitor with the shortest distance
and to the analog ground plane with several vias.
For applications that use multiple AD7631s or other PulSAR
devices, it is more effective to use the internal reference buffer
to buffer the external 2.5 V reference voltage.
Digital Output Supply
The OVDD supplies the digital outputs and allows direct interface
with any logic working between 2.3 V and 5.25 V. OVDD should
be set to the same level as the system interface. Sufficient
decoupling is required consisting of at least a 10 ꢀF capacitor and
a 100 nF capacitor with the 100 nF placed as close as possible
to the AD7631.
The voltage reference temperature coefficient (TC) directly
impacts full scale; therefore, in applications where full-scale
accuracy matters, care must be taken with the TC. For instance,
a 4 ppm/°C TC of the reference changes full scale by 1 LSB/°C.
Temperature Sensor
The TEMP pin measures the temperature of the AD7631. To
improve the calibration accuracy over the temperature range, the
output of the TEMP pin is applied to one of the inputs of the
analog switch (such as ADG779), and the ADC itself is used to
measure its own temperature. This configuration is shown
in Figure 32.
Rev. A | Page 22 of 32
AD7631
Power Sequencing
Power Down
The AD7631 is independent of power supply sequencing and is
very insensitive to power supply variations on AVDD over a wide
frequency range, as shown in Figure 33.
75
Setting PD = high powers down the AD7631, thus reducing
supply currents to their minimums, as shown in Figure 23.
When the ADC is in power-down, the current conversion
(if any) is completed and the digital bus remains active. To
further reduce the digital supply currents, drive the inputs to
OVDD or OGND.
70
65
60
55
50
45
40
35
30
Power-down can also be programmed with the configuration
register. See the Software Configuration section for details. Note
that when using the configuration register, the PD input is a don’t
care and should be tied to either high or low.
CONVERSION CONTROL
CNVST
The AD7631 is controlled by the
input. A falling edge
CNVST
on
is all that is necessary to initiate a conversion. A
detailed timing diagram of the conversion process is shown in
Figure 35. Once initiated, it cannot be restarted or aborted, even
by the power-down input, PD, until the conversion is complete.
1
10
100
1000
10000
FREQUENCY (kHz)
CNVST
CS RD
Figure 33. AVDD PSRR vs. Frequency
The
signal operates independently of
and
signals.
Power Dissipation vs. Throughput
t2
In impulse mode, the AD7631 automatically reduces its power
consumption at the end of each conversion phase. During the
acquisition phase, the operating currents are very low, which allows
a significant power savings when the conversion rate is reduced
(see Figure 34). This feature makes the AD7631 ideal for very
low power, battery-operated applications.
t1
CNVST
BUSY
t4
t3
t5
t6
It should be noted that the digital interface remains active even
during the acquisition phase. To reduce the operating digital supply
currents even further, drive the digital inputs close to the power
rails, that is, OVDD and OGND.
MODE
ACQUIRE
CONVERT
t7
ACQUIRE
t8
CONVERT
Figure 35. Basic Conversion Timing
1000
CNVST
Although
is a digital signal, it should be designed with
special care with fast, clean edges and levels with minimum
overshoot, undershoot, or ringing.
100
10
CNVST
The
trace should be shielded with ground and a low value
(such as 50 Ω) serial resistor termination should be added close
to the output of the component that drives this line.
CNVST
For applications where SNR is critical, the
have very low jitter. This can be achieved by using a dedicated
CNVST CNVST
with a
signal should
oscillator for
generation, or by clocking
high frequency, low jitter clock, as shown in Figure 27.
PDREF = PDBUF = HIGH
1
1
10
100
1000
10000
100000 1000000
SAMPLING RATE (kSPS)
Figure 34. Power Dissipation vs. Sample Rate
Rev. A | Page 23 of 32
AD7631
INTERFACES
CS = RD = 0
CNVST
DIGITAL INTERFACE
t1
The AD7631 has a versatile digital interface that can be set up as
either a serial or a parallel interface with the host system. The
serial interface is multiplexed on the parallel data bus. The
AD7631 digital interface also accommodates 2.5 V, 3.3 V, or 5 V
logic. In most applications, the OVDD supply pin is connected
to the host system interface 2.5 V to 5.25 V digital supply. Finally,
t10
BUSY
t4
t3
t11
DATA
BUS
PREVIOUS CONVERSION DATA
NEW DATA
2C
by using the D0/OB/ input pin, both twos complement or
straight binary coding can be used, except for a 18-bit parallel
interface.
Figure 37. Master Parallel Data Timing for Reading (Continuous Read)
Slave Parallel Interface
CS
RD
, control the interface. When at least
Two signals,
one of these signals is high, the interface outputs are in high
CS
and
In slave parallel reading mode, the data can be read either after
each conversion, which is during the next acquisition phase, or
during the following conversion, as shown in Figure 38 and
Figure 39, respectively. When the data is read during the
conversion, it is recommended that it is read-only during the
first half of the conversion phase. This avoids any potential
feedthrough between voltage transients on the digital interface
and the most critical analog conversion circuitry.
impedance. Usually,
multicircuit applications and is held low in a single AD7631
RD
allows the selection of each AD7631 in
design.
the data bus.
is generally used to enable the conversion result on
RESET
The RESET input is used to reset the AD7631. A rising edge on
RESET aborts the current conversion (if any) and tristates the
data bus. The falling edge of RESET resets the AD7631 and clears
the data bus and configuration register. See Figure 36 for the
RESET timing details.
CS
RD
t9
RESET
BUSY
BUSY
DATA
BUS
DATA
BUS
CURRENT
CONVERSION
t8
t12
t13
CNVST
Figure 38. Slave Parallel Data Timing for Reading (Read After Convert)
Figure 36. RESET Timing
CS = 0
PARALLEL INTERFACE
CNVST,
t1
The AD7631 is configured to use the parallel interface when the
MODE[1:0] pins = 0, 1, or 2 for 18-/16-/8-bit interfaces,
respectively, as shown in Table 7.
RD
Master Parallel Interface
BUSY
t4
CS
RD
low, thus
Data can be continuously read by tying
and
t3
requiring minimal microprocessor connections. However, in
this mode, the data bus is always driven and cannot be used in
shared bus applications (unless the device is held in RESET).
Figure 37 details the timing for this mode.
DATA
BUS
PREVIOUS
CONVERSION
t12
t13
Figure 39. Slave Parallel Data Timing for Reading (Read During Convert)
Rev. A | Page 24 of 32
AD7631
18-Bit Interface (Master or Slave)
MASTER SERIAL INTERFACE
The 18-bit interface is selected by setting MODE[1:0] = 0.
In this mode, the data output is straight binary.
The pins multiplexed on D[12:4] and used for master serial
INT
interface are: DIVSCLK[1:0], EXT/
RDC, SDOUT, SDCLK, and SYNC.
, INVSYNC, INVSCLK,
16-Bit and 8-Bit Interface (Master or Slave)
INT
Internal Clock (MODE[1:0] = 3, EXT/
= Low)
In the 16-bit (MODE[1:0] = 1) and 8-bit (MODE[1:0] = 2)
interfaces, Pin A0 and Pin A1 allow a glueless interface to a
16- or 8-bit bus, as shown in Figure 40 (refer to Table 7 for more
details). By connecting Pin A0 and Pin A1 to an address line(s),
the data can be read in two words for a 16-bit interface or three
bytes for an 8-bit interface. This interface can be used in both
master and slave parallel reading modes.
The AD7631 is configured to generate and provide the serial
INT
data clock, SDCLK, when the EXT/
pin is held low. The
AD7631 also generates a SYNC signal to indicate to the host
when the serial data is valid. The SDCLK and the SYNC signals
can be inverted, if desired, using the INVSCLK and INVSYNC
inputs, respectively. Depending on the input, RDC, the data
can be read during the following conversion or after each
conversion. Figure 41 and Figure 42 show detailed timing
diagrams of these two modes.
CS, RD
A1
A0
Read During Convert (RDC = High)
Setting RDC = high allows the master read (previous
conversion result) during conversion mode. Usually, because
the AD7631 is used with a fast throughput, this mode is the
most recommended serial mode. In this mode, the serial clock
and data switch on and off at appropriate instances, minimizing
potential feedthrough between digital activity and critical
conversion decisions. In this mode, the SDCLK period changes
because the LSBs require more time to settle, and the SDCLK is
derived from the SAR conversion cycle. In this mode, the
AD7631 generates a discontinuous SDCLK of two different
periods, and the host should use an SPI interface.
HI-Z
HI-Z
HI-Z
HIGH
LOW
D[17:2]
WORD
WORD
HI-Z
t13
HIGH
BYTE
MID
BYTE
LOW
BYTE
D[17:10]
t12
t12
t12
Figure 40. 8-Bit and16-Bit Parallel Interface
SERIAL INTERFACE
The AD7631 is configured to use the serial interface
when MODE[1:0]= 3. The AD7631 has a serial interface
Read After Convert (RDC = Low, DIVSCLK[1:0] = [0 to 3])
Setting RDC = low allows the read after conversion mode.
Unlike the other serial modes, the BUSY signal returns low after
the 18 data bits are pulsed out and not at the end of the conversion
phase, resulting in a longer BUSY width (see Table 4 for BUSY
timing specifications). The DIVSCLK[1:0] inputs control the
SDCLK period and SDOUT data rate. As a result, the maximum
throughput cannot be achieved in this mode. In this mode, the
AD7631 also generates a discontinuous SDCLK; however, a
fixed period and hosts supporting both SPI and serial ports can
also be used.
(SPI-compatible) multiplexed on the data pins D[17:4].
Data Interface
The AD7631 outputs 18 bits of data, MSB first, on the SDOUT pin.
This data is synchronized with the 18 clock pulses provided on
the SDCLK pin. The output data is valid on both the rising and
falling edge of the data clock.
Serial Configuration Interface
The AD7631 can only be configured through the serial
configuration register in serial mode as the serial configuration
pins are also multiplexed on the data pins D[17:14]. See the
Hardware Configuration section and the Software Configuration
section for more information.
Rev. A | Page 25 of 32
AD7631
EXT/INT = 0 RDC/SDIN = 1 INVSCLK = INVSYNC = 0
MODE[1:0] = 3
CS, RD
CNVST
t1
t3
BUSY
SYNC
t17
t25
t19
t14
t20 t21
t24
t26
t15
SDCLK
SDOUT
1
2
3
16
17
18
t18
t27
X
D17
D16
t23
D2
D1
D0
t16
t22
Figure 41. Master Serial Data Timing for Reading (Read Previous Conversion During Convert)
EXT/INT = 0 RDC/SDIN = 0 INVSCLK = INVSYNC = 0
MODE[1:0] = 3
CS, RD
t3
CNVST
BUSY
t28
t30
t29
t25
SYNC
t18
t14
t19
t24
t20
t21
2
t26
1
3
16
17
18
SDCLK
SDOUT
t15
t27
D17
D16
t23
D2
D1
D0
X
t16
t22
Figure 42. Master Serial Data Timing for Reading (Read After Convert)
While the AD7631 is performing a bit decision, it is important
that voltage transients be avoided on digital input/output pins,
or degradation of the conversion result may occur. This is
particularly important during the last 550 ns of the conversion
phase because the AD7631 provides error correction circuitry
that can correct for an improper bit decision made during
the first part of the conversion phase. For this reason, it is
recommended that any external clock provided is a
discontinuous clock that transitions only when BUSY is low,
or, more importantly, that it does not transition during the
last 450 ns of BUSY high.
SLAVE SERIAL INTERFACE
The pins multiplexed on D[13:6] used for slave serial
INT
interface are: EXT/
and RDERROR.
, INVSCLK, SDIN, SDOUT, SDCLK,
INT
External Clock (MODE[1:0] = 3, EXT/
= High)
INT
Setting the EXT/
= high allows the AD7631 to accept an
externally supplied serial data clock on the SDCLK pin. In this
mode, several methods can be used to read the data. The external
CS
CS
RD
serial clock is gated by . When
and are both low, the
data can be read after each conversion or during the following
conversion. A clock can be either normally high or normally
low when inactive. For detailed timing diagrams, see Figure 44
and Figure 45.
Rev. A | Page 26 of 32
AD7631
BUSY
OUT
External Discontinuous Clock Data Read After
Conversion
BUSY
BUSY
Though the maximum throughput cannot be achieved using
this mode, it is the most recommended of the serial slave modes.
Figure 44 shows the detailed timing diagrams for this method.
After a conversion is completed, indicated by BUSY returning low,
AD7631
AD7631
#2
#1
(UPSTREAM)
(DOWNSTREAM)
DATA
OUT
RDC/SDIN SDOUT
RDC/SDIN SDOUT
CS
RD
the conversion result can be read while both
and
are low.
CNVST
CS
CNVST
CS
Data is shifted out MSB first with 18 clock pulses and, depending
on the SDCLK frequency, can be valid on the falling and rising
edges of the clock.
SDCLK
SDCLK
SDCLK IN
One advantage of this method is that conversion performance is
not degraded because there are no voltage transients on the digital
interface during the conversion process. Another advantage is
the ability to read the data at any speed up to 40 MHz, which
accommodates both the slow digital host interface and the fastest
serial reading.
CS IN
CNVST IN
Figure 43. Two AD7631 Devices in a Daisy-Chain Configuration
External Clock Data Read During Previous Conversion
Figure 45 shows the detailed timing diagrams for this method.
During a conversion, while both
CS
RD
and
are low, the result
Daisy-Chain Feature
of the previous conversion can be read. The data is shifted out,
MSB first, with 18 clock pulses and is valid on both the falling
and rising edges of the clock. The 18 bits have to be read before
the current conversion is completed; otherwise, RDERROR is
pulsed high and can be used to interrupt the host interface to
prevent incomplete data reading.
In addition, in the read after convert mode, the AD7631 provides a
daisy-chain feature for cascading multiple converters together
using the serial data input pin, SDIN. This feature is useful for
reducing component count and wiring connections when desired,
for instance, in isolated multiconverter applications. See Figure 44
for the timing details.
To reduce performance degradation due to digital activity, a fast
discontinuous clock of at least 40 MHz is recommended to ensure
that all the bits are read during the first half of the SAR
conversion phase.
An example of the concatenation of two devices is shown
in Figure 43.
CNVST
Simultaneous sampling is possible by using a common
signal. Note that the SDIN input is latched on the opposite edge
of SDCLK used to shift out the data on SDOUT (SDCLK
falling edge when INVSCLK = low). Therefore, the MSB of
the upstream converter follows the LSB of the downstream
converter on the next SDCLK cycle. In this mode, the 40 MHz
SDCLK rate cannot be used because the SDIN to SDCLK setup
time, t33, is less than the minimum time specified. (SDCLK
to SDOUT delay, t32, is the same for all converters when
simultaneously sampled). For proper operation, the SDCLK
edge for latching SDIN (or ½ period of SDCLK) needs to be
The daisy-chain feature should not be used in this mode because
digital activity occurs during the second half of the SAR
conversion phase likely resulting in performance degradation.
External Clock Data Read After/During Conversion
It is also possible to begin to read data after conversion and
continue to read the last bits after a new conversion is initiated.
This method allows the full throughput and the use of a slower
SDCLK frequency. Again, it is recommended to use a
discontinuous SDCLK whenever possible to minimize
potential incorrect bit decisions. The use of a slower SDCLK,
such as 13 MHz, can be used.
t1/2SDCLK = t32 +t33
Or the maximum SDCLK frequency needs to be
1
fSDCLK
=
2(t32 +t33 )
If not using the daisy-chain feature, the SDIN input should
always be tied either high or low.
Rev. A | Page 27 of 32
AD7631
MODE[1:0] = 3 EXT/INT = 1 INVSCLK = 0 RD = 0
CS
BUSY
t31
t35
t36
t31
SDCLK
X*
1
2
3
4
16
17
18
19
20
21
t32
t37
SDOUT
SDIN
D17
X17
X17
Y17
X16
Y16
D16
X16
D15
D2
X2
D1
X1
D0
X0
t16
X15
t33
*A DISCONTINUOUS SDCLK IS RECOMMENDED.
t34
Figure 44. Slave Serial Data Timing for Reading (Read After Convert)
MODE[1:0] = 3 EXT/INT = 1 INVSCLK = 0
RD = 0
CS
CNVST
BUSY
t35
t36
18
t31
t31
SDCLK
X*
X*
X*
X*
X*
X*
1
2
3
17
t32
t37
D1
DATA = SDIN
t27
SDOUT
D17
D0
D16
t16
*A DISCONTINUOUS SDCLK IS RECOMMENDED.
Figure 45. Slave Serial Data Timing for Reading (Read Previous Conversion During Convert)
Rev. A | Page 28 of 32
AD7631
throughput is required, the SCP can be written to during
HARDWARE CONFIGURATION
conversion; however, it is not recommended to write to the SCP
during the last 600 ns of conversion (BUSY = high) or performance
degradation can result. In addition, the SCP can be accessed in
both serial master and serial slave read during and read after
convert modes.
The AD7631 can be configured at any time with the dedicated
2C
hardware pins BIPOLAR, TEN, D0/OB/ , and PD for parallel
mode (MODE[1:0] = 0, 1, or 2) or serial hardware mode
SW
(MODE[1:0] = 3, HW/
= high). Programming the AD7631
for mode selection and input range configuration can be done
before or during conversion. Like the RESET input, the ADC
requires at least one acquisition time to settle, as indicated in
Figure 46. See Table 6 for pin descriptions. Note that these
inputs are high impedance when using the software
configuration mode.
Note that at power-up, the configuration register is undefined.
The RESET input clears the configuration register (sets all bits
to 0), therefore placing the configuration to 0 V to 5 V input,
normal mode, and twos complemented output.
Table 11. Configuration Register Description
SOFTWARE CONFIGURATION
Bit Mnemonic Description
8
START
SCCS
START bit. With the SCP enabled (
= low),
The pins multiplexed on D[17:14] used for software
when START is high, the first rising edge of
SCCLK (INVSCLK = low) begins to load the
register with the new configuration.
SW
SCCS
configuration are: HW/ , SCIN, SCCLK, and
. The
AD7631 is programmed using the dedicated write-only
serial configurable port (SCP) for conversion mode, input range
selection, output coding, and power-down using the serial
configuration register. See Table 11 for details of each bit in the
configuration register. The SCP can only be used in serial software
mode selected with MODE[1:0] = 3 and HW/
the port is multiplexed on the parallel interface.
7
BIPOLAR
Input Range Select. Used in conjunction with
Bit 6, TEN, per the following.
Input Range (V)
BIPOLAR
Low
Low
High
High
TEN
Low
High
Low
High
0 to 5
0 to 10
5
SW
= low because
10
SCCS
The SCP is accessed by asserting the port’s chip select,
,
6
5
TEN
PD
Input Range Select. See Bit 7, BIPOLAR.
Power Down.
PD = low, normal operation.
PD = high, power down the ADC. The SCP is
accessible while in power down. To power up
the ADC, write PD = low on the next
configuration setting.
Reserved.
Reserved.
and then writing SCIN synchronized with SCCLK, which (like
SDCLK) is edge sensitive depending on the state of INVSCLK.
See Figure 47 for timing details. SCIN is clocked into the
configuration register MSB first. The configuration register is
an internal shift register that begins with Bit 8, the START bit.
The 9th SCCLK edge updates the register and allows the new
settings to be used. As indicated in the timing diagram, at least one
acquisition time is required from the 9th SCCLK edge. Bits [1:0] are
reserved bits and are not written to while the SCP is being updated.
4
3
2
RSV
RSV
2C
OB/
Output coding.
2C
OB/ = low, use twos complement output.
2C
OB/ = high, use straight binary output.
The SCP can be written to at any time, up to 40 MHz, and it is
recommended to write to while the AD7631 is not busy
converting, as detailed in Figure 47. In this mode, the full
670 kSPS is not attainable because the time required for SCP
access is (t31 + 9 × 1/SCCLK + t8) minimum. If the full
1
0
RSV
RSV
Reserved.
Reserved.
HW/SW = 1
PD = 0
t8
t8
CNVST
BUSY
BIPOLAR,
TEN
D0/OB/2C,
PD
Figure 46. Hardware Configuration Timing
Rev. A | Page 29 of 32
AD7631
MODE[1:0] = 3 INVSCLK = 0
BIPOLAR = 0 OR 1
TEN = 0 OR 1
t8
HW/SW = 0
PD = 0
CNVST
BUSY
t31
SCCS
t31
t35
t36
5
SCCLK
1
2
3
4
6
7
8
9
t37
t34
SCIN
X
X
OB/2C
BIPOLAR
TEN
PD
X
START
X
t33
Figure 47. Serial Configuration Port Timing
MICROPROCESSOR INTERFACING
The AD7631 is ideally suited for traditional dc measurement
applications supporting a microprocessor and ac signal processing
applications interfacing to a digital signal processor. The
AD7631 is designed to interface with a parallel 8-bit or 18-bit wide
interface, or with a general-purpose serial port or I/O ports on a
microcontroller. A variety of external buffers can be used with
the AD7631 to prevent digital noise from coupling into the ADC.
The reading process can be initiated in response to the end-of-
conversion signal (BUSY going low) using an interrupt line of
the DSP. The serial peripheral interface (SPI) on the ADSP-219x
is configured for master mode (MSTR) = 1, clock polarity bit
(CPOL) = 0, clock phase bit (CPHA) = 1, and SPI interrupt enable
(TIMOD) = 0 by writing to the SPI control register (SPICLTx).
It should be noted that to meet all timing requirements, the SPI
clock should be limited to 17 Mbps allowing it to read an ADC
result in less than 1 μs. When a higher sampling rate is desired,
use one of the parallel interface modes.
SPI Interface
The AD7631 is compatible with SPI and QSPI digital hosts and
DSPs, such as Blackfin® ADSP-BF53x and ADSP-218x/ADSP-219x.
Figure 48 shows an interface diagram between the AD7631 and
the SPI-equipped ADSP-219x. To accommodate the slower
speed of the DSP, the AD7631 acts as a slave device, and data must
be read after conversion. This mode also allows the daisy-chain
feature. The convert command could be initiated in response to
an internal timer interrupt.
DVDD
AD7631*
ADSP-219x*
MODE[1:0]
BUSY
CS
PFx
EXT/INT
SPIxSEL (PFx)
MISOx
SDOUT
SDCLK
CNVST
RD
SCKx
PFx OR TFSx
INVSCLK
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 48. Interfacing the AD7631 to SPI Interface
Rev. A | Page 30 of 32
AD7631
APPLICATION INFORMATION
The DVDD supply of the AD7631 can be either a separate
LAYOUT GUIDELINES
supply or come from the analog supply, AVDD, or from the
digital interface supply, OVDD. When the system digital supply
is noisy, or fast switching digital signals are present and no
separate supply is available, it is recommended to connect the
DVDD digital supply to the analog supply AVDD through an
RC filter, and to connect the system supply to the interface
digital supply OVDD and the remaining digital circuitry. See
Figure 27 for an example of this configuration. When DVDD is
powered from the system supply, it is useful to insert a bead to
further reduce high frequency spikes.
While the AD7631 has very good immunity to noise on the
power supplies, exercise care with the grounding layout. To
facilitate the use of ground planes that can be easily separated,
design the printed circuit board that houses the AD7631 so that
the analog and digital sections are separated and confined to
certain areas of the board. Digital and analog ground planes
should be joined in only one place, preferably underneath the
AD7631, or as close as possible to the AD7631. If the AD7631 is
in a system where multiple devices require analog-to-digital
ground connections, the connections should still be made at
one point only, a star ground point, established as close as
possible to the AD7631.
The AD7631 has four different ground pins: REFGND, AGND,
DGND, and OGND.
To prevent coupling noise onto the die, avoid radiating noise,
and reduce feedthrough:
•
REFGND senses the reference voltage and, because it carries
pulsed currents, should be a low impedance return to the
reference.
• Do not run digital lines under the device.
•
AGND is the ground to which most internal ADC analog
signals are referenced; it must be connected with the least
resistance to the analog ground plane.
• Do run the analog ground plane under the AD7631.
CNVST
• Do shield fast switching signals, such as
or clocks,
with digital ground to avoid radiating noise to other sections
of the board and never run them near analog signal paths.
•
•
DGND must be tied to the analog or digital ground plane
depending on the configuration.
• Avoid crossover of digital and analog signals.
OGND is connected to the digital system ground.
• Run traces on different but close layers of the board, at right
angles to each other, to reduce the effect of feedthrough through
the board.
The layout of the decoupling of the reference voltage is important.
To minimize parasitic inductances, place the decoupling capacitor
close to the ADC and connect it with short, thick traces.
The power supply lines to the AD7631 should use as large a
trace as possible to provide low impedance paths and reduce the
effect of glitches on the power supply lines. Good decoupling is
also important to lower the impedance of the supplies presented
to the AD7631 and to reduce the magnitude of the supply
spikes. Decoupled ceramic capacitors, typically 100 nF, should
be placed on each of the power supplies pins, AVDD, DVDD,
OVDD, VCC, and VEE. The capacitors should be placed close
to, and ideally right up against, these pins and their corresponding
ground pins. Additionally, low ESR 10 μF capacitors should be
located near the ADC to further reduce low frequency ripple.
EVALUATING PERFORMANCE
A recommended layout for the AD7631 is outlined in the
EVAL-AD7631CBZ evaluation board documentation. The
evaluation board package includes a fully assembled and tested
evaluation board, documentation, and software for controlling
the board from a PC via the EVAL-CONTROL BRD3.
Rev. A | Page 31 of 32
AD7631
OUTLINE DIMENSIONS
9.20
9.00 SQ
8.80
0.75
0.60
0.45
1.60
MAX
37
48
36
1
PIN 1
7.20
TOP VIEW
(PINS DOWN)
7.00 SQ
6.80
1.45
1.40
1.35
0.20
0.09
7°
3.5°
0°
0.08
COPLANARITY
25
12
0.15
0.05
13
24
SEATING
PLANE
0.27
0.22
0.17
VIEW A
0.50
BSC
LEAD PITCH
VIEW A
ROTATED 90° CCW
COMPLIANT TO JEDEC STANDARDS MS-026-BBC
Figure 49. 48-Lead Low Profile Quad Flat Package [LQFP]
(ST-48)
Dimensions shown in millimeters
0.30
0.23
0.18
7.00
BSC SQ
0.60 MAX
0.60 MAX
PIN 1
INDICATOR
37
36
48
1
PIN 1
INDICATOR
EXPOSED
5.25
5.10 SQ
4.95
TOP
VIEW
6.75
BSC SQ
PAD
(BOTTOM VIEW)
0.50
0.40
0.30
25
24
12
13
0.25 MIN
5.50
REF
0.80 MAX
0.65 TYP
1.00
0.85
0.80
12° MAX
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
0.05 MAX
0.02 NOM
COPLANARITY
0.08
0.50 BSC
SECTION OF THIS DATA SHEET.
0.20 REF
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-220-VKKD-2
Figure 50. 48-Lead Lead Frame Chip Scale Package [LFCSP_VQ]
7 mm × 7 mm Body, Very Thin Quad
(CP-48-1)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
AD7631BCPZ
AD7631BCPZRL
AD7631BSTZ
AD7631BSTZRL
EVAL-AD7631CBZ
EVAL-CONTROL BRD3
Notes Temperature Range
−40°C to +85°C
Package Description
Package Option
CP-48-1
CP-48-1
ST-48
ST-48
48-Lead Lead Frame Chip Scale Package (LFCSP_VQ)
48-Lead Lead Frame Chip Scale Package (LFCSP_VQ)
48-Lead Low Profile Quad Flat Package (LQFP)
48-Lead Low Profile Quad Flat Package (LQFP)
Evaluation Board
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
2
3
Controller Board
1 Z = RoHS Compliant Part.
2 This board can be used as a standalone evaluation board or in conjunction with the EVAL-CONTROL BRD3 for evaluation/demonstration purposes.
3 This board allows a PC to control and communicate with all Analog Devices evaluation boards ending with the CB designators.
©2007–2011 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D06588-0-3/11(A)
Rev. A | Page 32 of 32
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