ISO254P [BB]
Precision, Powered, Three-Port Isolated PROGRAMMABLE GAIN AMPLIFIER; 精度，供电，三端口隔离的可编程增益放大器
| 型号： | ISO254P |
| 厂家： | 
BURR-BROWN CORPORATION |
| 描述： | Precision, Powered, Three-Port Isolated PROGRAMMABLE GAIN AMPLIFIER |
| 文件： | 总9页 (文件大小：165K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
®
ISO254
ISO254
Precision, Powered, Three-Port Isolated
PROGRAMMABLE GAIN AMPLIFIER
FEATURES
DESCRIPTION
● RATED
ISO254 is a precision three-port isolated program-
mable gain instrumentation amplifier incorporating a
novel duty cycle modulation-demodulation technique
and has excellent accuracy. Internal input protection
can withstand up to ±40V input differential without
damage. The signal is transmitted digitally across a
differential capacitive barrier. With digital modulation
the barrier characteristics do not affect signal integrity.
This results in excellent reliability and good high
frequency transient immunity across the barrier. The
DC/DC converter, amplifier and barrier capacitors are
housed in a plastic DIP.
1500Vrms Continuous
2500Vrms for One Minute
100% TESTED FOR PARTIAL DISCHARGE
● PROGRAMMABLE GAINS OF
1, 10, 100, 1000
● LOW NONLINEARITY: ±0.01% typ
● LOW INPUT BIAS CURRENT: ±5nA max
● LOW INPUT OFFSET VOLTAGE:
625µV max
● INPUTS PROTECTED TO ±40V
● BIPOLAR OPERATION: VO = ±10V
● SYNCHRONIZATION CAPABILITY
● 28-PIN PLASTIC DIP: 0.6" Wide
This amplifier is easy to use as no external compo-
nents are required. A power supply range of 11V to
18V makes this amplifier ideal for a wide range of
applications.
2
1
APPLICATIONS
A1
A0
● INDUSTRIAL PROCESS CONTROL
Transducer Isolator, Thermocouple
Isolator, RTD Isolator, Pressure Bridge
Isolator, Flow Meter Isolator
ISO254
+VIN
3
4
VOUT
PGA
14
● POWER MONITORING
–VIN
● MEDICAL INSTRUMENTATION
● ANALYTICAL MEASUREMENTS
● BIOMEDICAL MEASUREMENTS
● DATA ACQUISITION
Com1
+VS1
–VS1
Com2
+VS2
–VS2
26
28
27
25
13
12
11
10
● TEST EQUIPMENT
GND1
GND2
● GROUND LOOP ELIMINATION
GND3 SYNC +VS3
17 16 15
©1996 Burr-Brown Corporation
PDS-1308B
Printed in U.S.A. April, 1996
SPECIFICATIONS
At TA = +25°C, +VS3 = 15V, RL = 2kΩ, and 220nF capacitors on all generated supplies, unless otherwise noted.
ISO254P
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
ISOLATION
Voltage Rated Continuous:
AC
100% Test (AC 50Hz)
Rated One Min
Isolation-Mode Rejection
DC
T
MIN to TMAX
1500
2500
2500
Vrms
Vrms
Vrms
1s; Partial Discharge ≤ 5pC
120
95
dB
dB
AC 50Hz
1500Vrms
Barrier Impedance
Leakage Current
1014 || 2
1.4
Ω || pF
µArms
VISO = 240Vrms, 50Hz
2
GAIN
Gain Error
G = 1
G = 10
G = 100
G = 1000
G = 1
0.15
0.15
0.15
0.2
±15
±15
±15
±15
±0.01
±0.01
0.01
±0.01
±0.3
±0.3
%
%
Gain vs Temperature
Nonlinearity
ppm/°C
ppm/°C
ppm/°C
ppm/°C
%
G = 10
G = 100
G = 1000
G = 1
G = 10
G = 100
G = 1000
±0.102
±0.104
%
INPUT OFFSET VOLTAGE
Initial Offset
vs Temperature
CMRR
±(0.125 +101/G)
mV
µV/°C
dB
±(1 + 510/G)
90
1
vs Supply
mV/V
INPUT
Voltage Range
Bias Current
vs Temperature
Offset Current
vs Temperature
±10
V
nA
pA/°C
nA
pA/°C
±5
±5
±8
±8
OUTPUT
Voltage Range
Current Drive
±10
±5
V
mA
Capacitive Load Drive
Ripple Voltage
0.1
25
µF
mVp-p
FREQUENCY RESPONSE
Small Signal Bandwidth
G = 1
G = 10
G = 100
G = 1000
50
30
10
1
0.5
80
380
490
1650
kHz
kHz
kHz
kHz
V/µs
µs
µs
µs
µs
Slew Rate
Settling Time, 0.1%
G = 1
G = 10
G = 100
G = 1000
POWER SUPPLIES
Rated Voltage
Voltage Range
Quiescent Current
Rated Output Voltage
15
V
V
mA
V
11
25
13
12
18
55
40
14.5
13.2
35
No Load
50mA Load On Two Supplies
16
V
Load Regulation
Line Regulation
SYNC Frequency
Output Voltage Ripple
mV/mA
V/V
MHz
mV
1
1
1.4
50
TEMPERATURE RANGE
Operating
Storage
–40
–40
85
85
°C
°C
®
2
ISO254
ABSOLUTE MAXIMUM RATINGS
PIN CONFIGURATION
Supply Voltage ................................................................................... +18V
VIN, Analog Input Voltage Range ....................................................... ±40V
Com1 to GND1 .................................................................................... ±1V
Com2 to GND2 .................................................................................... ±1V
Continuous Isolation Voltage ..................................................... 1500Vrms
..................................................................................... 2500Vrms one min
IMV, dv/dt ...................................................................................... 20kV/µs
Junction Temperature ...................................................................... 150°C
Storage Temperature ........................................................ –40°C to +85°C
Lead Temperature (soldering, 10s)................................................ +300°C
Output Short Duration .......................................... Continuous to Common
A0
A1
1
2
3
4
28 +VS1
–VS1
27
26
25
–VIN
+VIN
Com1
GND1
GND2
–VS2
10
11
12
13
14
ELECTROSTATIC
DISCHARGE SENSITIVITY
+VS2
GND3
SYNC
+VS3
17
16
15
Com2
VOUT
Any integrated circuit can be damaged by ESD. Burr-Brown
recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling
and installation procedures can cause damage.
ESD damage can range from subtle performance degrada-
tion to complete device failure. Precision integrated circuits
may be more susceptible to damage because very small
parametric changes could cause the device not to meet
published specifications.
PACKAGE INFORMATION
PACKAGE DRAWING
NUMBER(1)
PRODUCT
PACKAGE
ISO254P
28-Pin Plastic DIP
335
NOTE: (1) For detailed drawing and dimension table, please see end of data
sheet, or Appendix C of Burr-Brown IC Data Book.
ORDERING INFORMATION
PRODUCT
PACKAGE
ISO254P
28-Pin Plastic DIP
TYPICAL PERFORMANCE CURVES
At TA = +25°C, +VS3 = 15V, RL = 2kΩ, and 220nF capacitors on all generated supplies, unless otherwise noted.
PSRR vs FREQUENCY
(G = 10)
PSRR vs FREQUENCY
(G = 1)
80
60
40
20
0
80
60
40
20
0
1
10
100
1k
10k
100k
1
10
100
1K
10K
100K
Frequency (Hz)
Frequency (Hz)
The information provided herein is believed to be reliable; however, BURR-BROWN assumes no responsibility for inaccuracies or omissions. BURR-BROWN assumes
no responsibility for the use of this information, and all use of such information shall be entirely at the user's own risk. Prices and specifications are subject to change
without notice. No patent rights or licenses to any of the circuits described herein are implied or granted to any third party. BURR-BROWN does not authorize or warrant
any BURR-BROWN product for use in life support devices and/or systems.
®
3
ISO254
TYPICAL PERFORMANCE CURVES (CONT)
At TA = +25°C, +VS3 = 15V, RL = 2kΩ, and 220nF capacitors on all generated supplies, unless otherwise noted.
ISOLATION LEAKAGE CURRENT vs FREQUENCY
(V = 240Vrms)
IMR vs FREQUENCY
120
100
80
1k
100
10
60
40
1
1
10
100
1k
10k
1
10
100
1k
10k
100k
Frequency (Hz)
Frequency (Hz)
SINE RESPONSE
(f = 1kHz, G = 1)
SIGNAL RESPONSE vs CARRIER FREQUENCY
10
5
10
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
0
–5
5
0
–5
–10
0
100k 200k 300k 400k 500k 600k 700k 800k
Frequency (Hz)
0
500
1000
1500
2000
Time (µs)
PULSE RESPONSE
(f = 1kHz, G = 1)
SINE RESPONSE
(f = 10kHz, G = 1)
10
5
10
5
0
0
–5
–5
5
0
5
0
–5
–5
–10
–10
0
500
1000
0
50
100
150
200
Time (µs)
Time (µs)
®
4
ISO254
TYPICAL PERFORMANCE CURVES (CONT)
At TA = +25°C, +VS3 = 15V, RL = 2kΩ, and 220nF capacitors on all generated supplies, unless otherwise noted.
PULSE RESPONSE
(f = 10kHz, G = 1)
GAIN vs FREQUENCY
G = 1000
10
5
60
40
G = 100
G = 10
0
20
–5
5
0
0
G = 1
–20
–40
–5
–10
1
10
100
1k
Frequency (Hz)
10k
100k
1M
0
20
40
Time (µs)
60
80
100
INPUT COMMON-MODE RANGE
vs OUTPUT VOLTAGE
COMMON-MODE REJECTION vs FREQUENCY
120
15
10
5
G ≥ 10
G ≥ 10
G = 1
100
80
G =1000
G = 1
–
VD/2
VD/2
VCM
VO
0
+
–
+
G = 100
G = 1
–5
–10
–15
G = 10
60
10
100
1k
10k
100k
–15
–10
–5
0
5
10
15
Frequency (Hz)
Output Voltage (V)
INPUT BIAS AND INPUT OFFSET CURRENT
vs TEMPERATURE
ISOLATION MODE VOLTAGE
vs FREQUENCY
2
1
Max DC Rating
2.1k
1.0k
Max AC
Rating
±IB
Degraded
Performance
0
IOS
100
10
–1
Typical
Performance
–2
–75
–50
–25
0
25
50
75
100
125
100
1k
10k
100k
1M
10M
100M
Temperature (°C)
Frequency (Hz)
®
5
ISO254
INPUT COMMON-MODE RANGE
BASIC OPERATION
The linear common-mode range of the input circuitry of the
ISO254 is approximately ±12.7V (or 2.3V from the power
supplies). As the output voltage increases, however, the
linear input range will be limited by the output voltage swing
of the internal amplifiers. Thus, the linear common-mode
range is related to the output voltage of the complete input
amplifier—see performance curves “Input Common-Mode
Range vs Output Voltage.”
ISO254 is a precision, powered, three-port isolated program-
mable-gain amplifier. The input and output sections are
galvanically isolated by matched and EMI shielded capaci-
tors built into the plastic package. The DC/DC converter
input is also galvanically isolated from both the input and
output supplies.
SIGNAL AND POWER CONNECTIONS
A combination of common-mode and differential input
voltage can cause the output voltage of the internal amplifi-
ers to saturate. For applications where input common-mode
range must be maximized, limit the output voltage swing by
selecting a lower gain of the programmable-gain input.
Figure 1 shows proper power and signal connections. The
power supply input pin +VS3 should be bypassed with a
2.2µF tantalum capacitor and the outputs VS1 and VS2 with
220nF ceramic capacitors located as close to the amplifier as
possible. All ground connections should be run indepen-
dently to a common point. Signal Common on the output
section provides a low-impedance point for sensing signal
ground in noisy applications. Com1 and Com2 must have a
path to ground for signal current return and should be
maintained within ±1V of GND1 and GND2 respectively.
Input-overload can produce an output voltage that appears
normal. For example, an input voltage of +20V on one input
and +40V on the other input will exceed the linear common-
mode range of both input amplifiers. Since both input
amplifiers are saturated to nearly the same output voltage
limit, the difference voltage measured by the output ampli-
fier will be near zero. The output of the programmable-gain
amplifier will be near 0V even though both inputs are
overloaded.
GAIN
A1
A0
1
10
100
1000
0
0
1
1
0
1
0
1
2
1
A1
A0
ISO254
4
3
+VIN
VOUT 14
VIN
PGA
VOUT
–VIN
26 Com1
+VS1
Com2 13
28
27 –VS1
GND1
+VS2 12
–VS2 11
+15VOUT
–15VOUT
+15VOUT
–15VOUT
GND2 10
25
GND3 SYNC +VS3
17 16 15
VCM
220nF
220nF
2.2µF
220nF
220nF
SYNC +15V
FIGURE 1. Basic Connections.
®
6
ISO254
INPUT PROTECTION
When connecting up to eight ISO254’s without a driver the
unit with the highest natural frequency will determine the
synchronized running frequency. The SYNC pin is sensitive
to capacitive loading: 150pF or less is recommended. If
unused, the SYNC pin should be left open. Avoid shorting
the SYNC pin directly to ground or supply potentials;
otherwise damage may result.
The inputs of the programmable-gain amplifiers are indi-
vidually protected for voltages up to ±40V. Internal circuitry
on each input provides low series impedance under normal
signal conditions. If the input is overloaded, the protection
circuitry limits the input current to a safe value (approxi-
mately 1.5mA). The inputs are protected even if no power
supply is present.
Soft start circuitry protects the MOSFET switches during
startup. This is accomplished by holding the gate-to-source
voltage of both MOSFET switches low until the free-run-
ning oscillator is fully operational. In addition, soft start
circuitry and input current sensing also protects the switches.
This current limiting keeps the MOSFET switches operating
in their safe operating area under fault conditions or exces-
sive loads. When either of these conditions occur, the peak
input current exceeds a safe limit. The result is an approxi-
mate 5% duty cycle, 300µs drive period to the MOSFET
switches. This protects the internal MOSFET switches as
well as the external load from any thermal damage. When
the fault or excessive load is removed, the converter resumes
normal operation. A delay period of approximately 50µs
incorporated in the current sensing circuitry allows the
output filter capacitors to fully charge after a fault is re-
moved. This delay period corresponds to a filter capacitance
of no more than 1µf at either of the output pins. This
provides full protection of the MOSFET switches and also
sufficiently filters the output ripple voltage. The current
sensing circuitry is designed to provide thermal protection
for the MOSFET switches over the operating temperature
range as well. When these conditions are exceeded, the unit
will go into its shutdown mode.
DC/DC CONVERTER
ISO254 provides a reliable solution to the need for integral
power. The high isolation rating being achieved by careful
design and attention to the physical construction of the
transformer. In addition to the high dielectric strength a low
leakage coating increases the isolation voltage range. The
soft start oscillator/driver design eliminates high inrush
currents during turn-on. Input current sensing protects both
the converter and the load from possible thermal damage
during a fault condition. The DC/DC converter is synchro-
nized to the amplifier and when multiple ISO254’s are used,
each channel can be synchronized via the SYNC pin.
The DC/DC converter consists of a free-running oscillator,
control and switch driver circuitry, MOSFET switches, a
transformer, rectifier diodes and filter capacitors all con-
tained within the ISO254 package. The control circuitry
consists of current limiting, soft start and synchronization
features. In instances where several ISO254’s are used in a
system, beat frequencies developed between the ISO254’s
are a potential source of low frequency noise in the supply
and ground paths. This noise may couple into the signal path
and can be avoided by synchronizing the individual ISO254’s
together by tying the SYNC pins together or using the circuit
in Figure 2 to drive the SYNC pins from an external source.
OUTPUT CURRENT RATINGS
The total current which can be drawn from each output
supply on the ISO254 is a function of the total power drawn
from all outputs. For example if three outputs are not used
then maximum current can be drawn from one output. In all
cases, the total maximum current that can be drawn from any
combination of outputs is:
MC1472
+15V
or Equivalent
Peripheral
Driver
+5V
330Ω
I1+
+ I1– + I2+ + I2– ≤ 50mΑ
2N3904
TTL
SYNC
+VS3, GND3
ISO254
ISO254
620Ω
The waveform of the ground return current is an 800kHz
sawtooth. A capacitor between +VS3 and GND3 provides a
bypass for the AC portion of this current. The power should
never be instantaneously interrupted to the ISO254 (i.e., a
break in the line to +VS3 either by accidental or switch
means.) Normal power down of the +VS3 supply is not
considered instantaneous. Should a rapid break in input
power occur the internal transformers voltage will rapidly
rise to maintain current flow and may cause internal damage
to the ISO254.
16
17
15
15
2N3904
100Ω
16
17
To Other
ISO254’s
FIGURE 2. External SYNC drive.
®
7
ISO254
SYNCHRONIZED OPERATION
Due to effects of very high-frequency signals, typical IMV
performance can be achieved only when dV/dT of the
isolation mode voltage falls below 1000V/µs. For conve-
nience, this is plotted in the typical performance curves
for the ISO254 as a function of voltage and frequency for
sinusoidal voltages. When dV/dT exceeds 1000V/µs but
falls below 20kV/µs, performance may be degraded. At rates
of change above 20kV/µs, the amplifier may be damaged,
but the barrier retains its full integrity. Lowering the power
supply voltage below 15V may decrease the dV/dT to
500V/µs for typical performance, but the maximum dV/dT
of 20kV/µs remains unchanged.
ISO254 can be synchronized to an external signal source.
This capability is useful in eliminating troublesome beat
frequencies in multi-channel systems and in rejecting AC
signals and their harmonics. To use this feature, tie all sync
pins together or apply an external signal to the SYNC pin.
ISO254 can be synchronized to an external oscillator over
the range 1-1.4MHz (this corresponds to a modulation fre-
quency of 500kHz to 700kHz as SYNC is internally divided
by 2).
CARRIER FREQUENCY CONSIDERATIONS
Leakage current is determined solely by the impedance of
the barrier and transformer capacitance and is plotted in the
“Isolation Leakage Current vs Frequency” curve.
ISO254 amplifiers transmit the signal across the ISO-barrier
by a duty-cycle modulation technique. This system works
like any linear amplifier for input signals having frequencies
below one half the carrier frequency, fC. For signal frequen-
cies above fC/2, the behavior becomes more complex. The
“Signal Response vs Carrier Frequency” performance curve
describes this behavior graphically. The upper curve illus-
trates the response for input signals varying from DC to fC/
2. At input frequencies at or above fC/2, the device generates
an output signal component that varies in both amplitude
and frequency, as shown by the lower curve. The lower
horizontal scale shows the periodic variation in the fre-
quency of the output component. Note that at the carrier
frequency and its harmonics, both the frequency and ampli-
tude of the response go to zero. These characteristics can be
exploited in certain applications.
ISOLATION VOLTAGE RATINGS
Because a long-term test is impractical in a manufacturing
situation, the generally accepted practice is to perform a
production test at a higher voltage for some shorter time.
The relationship between actual test voltage and the continu-
ous derated maximum specification is an important one.
Historically, Burr-Brown has chosen a deliberately conser-
vative one: VTEST = (2 x ACrms continuous rating) +
1000V for 10 seconds, followed by a test at rated ACrms
voltage for one minute. This choice was appropriate for
conditions where system transients are not well defined.
Recent improvements in high-voltage stress testing have
produced a more meaningful test for determining maximum
permissible voltage ratings, and Burr-Brown has chosen to
apply this new technology in the manufacture and testing of
the ISO254.
It should be noted that for the ISO254, the carrier frequency
is nominally 400kHz and the –3dB point of the amplifier is
50kHz. Spurious signals at the output are not significant
under these circumstances unless the input signal contains
significant components above 200kHz.
When periodic noise from external sources such as system
clocks and DC/DC converters are a problem, ISO254 can be
used to reject this noise. The amplifier can be synchronized
to an external frequency source, fEXT, placing the amplifier
response curve at one of the frequency and amplitude nulls
indicated in the “Signal Response vs Carrier Frequency”
performance curve.
Partial Discharge
When an insulation defect such as a void occurs within an
insulation system, the defect will display localized corona or
ionization during exposure to high-voltage stress. This ion-
ization requires a higher applied voltage to start the
discharge and lower voltage to maintain it or extinguish it
once started. The higher start voltage is known as the
inception voltage, while the extinction voltage is that level
of voltage stress at which the discharge ceases. Just as the
total insulation system has an inception voltage, so do the
individual voids. A voltage will build up across a void until
its inception voltage is reached, at which point the void will
ionize, effectively shorting itself out. This action redistrib-
utes electrical charge within the dielectric and is known as
partial discharge. If, as is the case with AC, the applied
voltage gradient across the device continues to rise, another
partial discharge cycle begins. The importance of this
phenomenon is that, if the discharge does not occur, the
insulation system retains its integrity. If the discharge be-
gins, and is allowed to continue, the action of the ions and
electrons within the defect will eventually degrade any
organic insulation system in which they occur. The measure-
ment of partial discharge is still useful in rating the devices
ISOLATION MODE VOLTAGE
Isolation Mode Voltage (IMV) is the voltage appearing
between isolated grounds GND1 and GND2. The IMV can
induce errors at the output as indicated by the plots of IMV
vs Frequency. It should be noted that if the IMV frequency
exceeds fC/2, the output will display spurious outputs in a
manner similar to that described above, and the amplifier
response will be identical to that shown in the “Signal
Response vs Carrier Frequency” performance curve. This
occurs because IMV-induced errors behave like input-
referred error signals. To predict the total IMR, divide the
isolation voltage by the IMR shown in “IMR vs Frequency”
performance curve and compute the amplifier response to
this input-referred error signal from the data given in the
“Signal Response vs Carrier Frequency” performance curve.
®
8
ISO254
and providing quality control of the manufacturing process.
The inception voltage for these voids tends to be constant, so
that the measurement of total charge being redistributed
within the dielectric is a very good indicator of the size of the
voids and their likelihood of becoming an incipient failure.
The bulk inception voltage, on the other hand, varies with
the insulation system, and the number of ionization defects
and directly establishes the absolute maximum voltage (tran-
sient) that can be applied across the test device before
destructive partial discharge can begin. Measuring the bulk
extinction voltage provides a lower, more conservative volt-
age from which to derive a safe continuous rating. In
production, measuring at a level somewhat below the ex-
pected inception voltage and then de-rating by a factor
related to expectations about system transients is an ac-
cepted practice.
measurement of RF noise to detect ionization. This method
was not quantitative with regard to energy of the discharge,
and was not sensitive enough for small components such as
isolation amplifiers. Now, however, manufacturers of HV
test equipment have developed means to quantify partial
discharge. VDE in Germany, an acknowledged leader in
high-voltage test standards, has developed a standard test
method to apply this powerful technique. Use of partial
discharge testing is an improved method for measuring the
integrity of an isolation barrier.
To accommodate poorly-defined transients, the part under
test is exposed to voltage that is 1.6 times the continuous-
rated voltage and must display less than or equal to 5pC
partial discharge level in a 100% production test.
APPLICATIONS
The ISO254 isolation amplifiers are used in three categories
of applications:
Partial Discharge Testing
Not only does this test method provide far more qualitative
information about stress-withstand levels than did previous
stress tests, but it provides quantitative measurements from
which quality assurance and control measures can be based.
Tests similar to this test have been used by some manufac-
turers, such as those of high-voltage power distribution
equipment, for some time, but they employed a simple
• Accurate isolation of signals from high voltage ground
potentials
• Accurate isolation of signals from severe ground noise and
• Fault protection from high voltages in analog measure-
ments
+15V
2.2nF
1nF
+15 (+VS2
)
15
+VS3
17
0.1µF
GND3
4
3
+VIN
16kΩ
16kΩ
14
VOUT
VSIGNAL
(0 - 5V)
OPA27
1nF
–VIN
0.1µF
ISO254
26
28
27
13
12
11
VOUT = 2VIN
COM1
+VS1
COM2
+VS2
–15 (–VS2
)
20kΩ
–VS1
–VS2
220nF
220nF
20kΩ
220nF
220nF
25
10
GND1
AO
GND2
A1
1
2
FIGURE 3. Noise Reduction in Data Acquisition System.
®
9
ISO254
相关型号：
©2020 ICPDF网 联系我们和版权申明