Q68000-A8483_技术文档

IL300

LINEAR OPTOCOUPLER

FEATURES

Dimensions in inches (mm)

• Couples AC and DC signals

• 0.01% Servo Linearity

Pin One I.D.

4

3

2

7

1

8

• Wide Bandwidth, >200 KHz

• High Gain Stability, ±0.005%/C

• Low Input-Output Capacitance

• Low Power Consumption, < 15mw

• Isolation Test Voltage, 5300 VAC

8

7

6

5

1

2

3

4

.268 (6.81)

.255 (6.48)

K1

K2

,

5

6

RMS

1 sec.

.390 (9.91)

.379 (9.63)

• Internal Insulation Distance, >0.4

mm

for VDE

.305 Typ.

(7.75) Typ.

.045 (1.14)

.030 (.76)

.150 (3.81)

.130 (3.30)

• Underwriters Lab File #E52744

• VDE Approval #0884 (Optional with

Option 1, Add -X001 Sufﬁx)

• IL300G Replaced by IL300-X006

.135 (3.43)

.115 (2.92)

4° Typ.

10 ° Typ.

3°–9°

APPLICATIONS

• Power Supply Feedback Voltage/

Current

• Medical Sensor Isolation

• Audio Signal Interfacing

.040 (1.02)

.030 (.76 )

.022 (.56)

.018 (.46)

.012 (.30)

.008 (.20)

.100 (2.54) Typ.

• Isolate Process Control Transducers

• Digital Telephone Isolation

DESCRIPTION (continued)

The magnitude of this current is directly proportional to the feedback transfer gain

(K1) times the LED drive current (V /R1=K1 • I ). The op-amp will supply LED cur-

IN

F

DESCRIPTION

rent to force sufﬁcient photocurrent to keep the node voltage (Vb) equal to Va

The IL300 Linear Optocoupler consists of

an AlGaAs IRLED irradiating an isolated

feedback and an output PIN photodiode

in a bifurcated arrangement. The feed-

back photodiode captures a percentage

of the LED's ﬂux and generates a control

The output photodiode is connected to a non-inverting voltage follower ampliﬁer. The

photodiode load resistor, R2, performs the current to voltage conversion. The output

ampliﬁer voltage is the product of the output forward gain (K2) times the LED current

and photodiode load, R2 (V =I • K2 • R2).

O

F

Therefore, the overall transfer gain (V /V ) becomes the ratio of the product of the

O

IN

output forward gain (K2) times the photodiode load resistor (R2) to the product of the

feedback transfer gain (K1) times the input resistor (R1). This reduces to V /V =

signal (IP ) that can be used to servo the

1

O

IN

LED drive current. This technique com-

pensates for the LED's non-linear, time,

and temperature characteristics. The out-

put PIN photodiode produces an output

(K2 • R2)/(K1 • R1). The overall transfer gain is completely independent of the LED

forward current. The IL300 transfer gain (K3) is expressed as the ratio of the ouput

gain (K2) to the feedback gain (K1). This shows that the circuit gain becomes the

product of the IL300 transfer gain times the ratio of the output to input resistors [V /

O

signal (IP ) that is linearly related to the

2

V =K3 (R2/R1)].

IN

servo optical ﬂux created by the LED.

The time and temperature stability of the

input-output coupler gain (K3) is insured

by using matched PIN photodiodes that

accurately track the output ﬂux of the

LED.

Figure 1.Typical application circuit

IL300

K2

1

8

7

6

Va

V

+

CC

+

Vin

2

3

4

U1

A typical application circuit (Figure 1)

uses an operational ampliﬁer at the circuit

input to drive the LED. The feedback

photodiode sources current to R1 con-

nected to the inverting input of U1. The

photocurrent, IP1, will be of a magnitude

Vb

K1

I

V

-

F

CC

-

V

CC

V

U2

out

V

c

+

5

lp 1

R2

lp 2

R1

to satisfy the relationship of (IP1=V /R1).

IN

5–1

IL300 Terms

Absolute Maximum Ratings

KI—Servo Gain

Symbol

Min.

Max.

Unit

The ratio of the input photodiode current (I ) to the LED cur-

P1

Emitter

rent(I ). i.e., K1 = I / I .

F

P1

F

Power Dissipation

P

160

mW

LED

K2—Forward Gain

The ratio of the output photodiode current ( I ) to the LED

(T =25°C)

A

P2

Derate Linearly from 25°C

2.13

60

mW/°C

mA

current (I ), i.e., K2 = I / I .

F

P2

F

Forward Current

lf

K3—Transfer Gain

The Transfer Gain is the ratio of the Forward Gain to the Servo

gain, i.e., K3 = K2/K1.

Surge Current

(Pulse width <10µs)

lpk

250

mA

∆K3—Transfer Gain Linearity

Reverse Voltage

V

5

V

R

The percent deviation of the Transfer Gain, as a function of

LED or temperature from a speciﬁc Transfer Gain at a ﬁxed

LED current and temperature.

Thermal Resistance

Junction Temperature

Detector

Rth

470

100

°C/W

°C

T

J

Photodiode

A silicon diode operating as a current source. The output cur-

rent is proportional to the incident optical ﬂux supplied by the

LED emitter. The diode is operated in the photovoltaic or pho-

toconductive mode. In the photovoltaic mode the diode func-

tions as a current source in parallel with a forward biased

silicon diode.

Power Dissipation

Derate linearly from 25°C

P

50

mA

DET

0.65

50

mW/°C

V

Reverse Voltage

Junction Temperature

Thermal Resistance

Coupler

V

R

The magnitude of the output current and voltage is depen-

dant upon the load resistor and the incident LED optical ﬂux.

When operated in the photoconductive mode the diode is

connected to a bias supply which reverse biases the silicon

diode. The magnitude of the output current is directly propor-

tional to the LED incident optical ﬂux.

T

100

1500

°C

J

Rth

°C/W

Total Package

Dissipation at 25°C

P

210

mW

T

LED (Light Emitting Diode)

Derate linearly from 25°C

Storage Temperature

Operating Temperature

Isolation Test Voltage

Isolation Resistance

2.8

mW/°C

°C

An infrared emitter constructed of AlGaAs that emits at 890

nm operates efﬁciently with drive current from 500 µA to 40

mA. Best linearity can be obtained at drive currents between

5 mA to 20 mA. Its output ﬂux typically changes by –0.5%/°C

over the above operational current range.

T

–55

150

100

S

T

–55

°C

OP

5300

VAC

RMS

12

11

V

=500 V, T =25°C

10

Ω

IO

A

V

=500 V, T =100°C

IO

A

IL300

5–2

Characteristics (T =25°C)

A

Symbol

Min.

Typ.

Max.

1.50

10

Unit

Test Condition

LED Emitter

Forward Voltage

V

1.25

-2.2

1

V

I =10 mA

F

V Temperature Coefficient

∆V /∆°C

mV/°C

µA

pF

F

Reverse Current

I

V =5 V

R

Junction Capacitance

Dynamic Resistance

Switching Time

C

15

6

V =0 V, f=1 MHz

F

J

∆V /∆I

Ω

I =10 mA

F

t

1

µs

∆I =2 mA, I =10 mA

F Fq

R

F

∆I =2 mA, I =10 mA

F

Fq

Detector

Dark Current

I

1

25

nA

V

=-15 V, I =0 µA

D

det F

Open Circuit Voltage

Short Circuit Current

Junction Capacitance

Noise Equivalent Power

Coupled Characteristics

V

500

70

mV

µA

I =10 mA

F

D

I

I =10 mA

F

SC

C

12

pF

V =0 V, f=1 MHz

F

J

14

NEP

4 x 10

W/√Hz

V

=15 V

det

K1, Servo Gain (I /I )

K1

0.0050

0.0036

0.56

0.007

70

0.011

1.65

I =10 mA, V =-15 V

F det

P1

F

Servo Current, see Note 1, 2

K2, Forward Gain (I /I )

I 1

µA

I =10 mA, V =-15 V

F det

P

K2

0.007

70

I =10 mA, V =-15 V

F det

P2

F

Forward Current

I 2

µA

I =10 mA, V =-15 V

F det

P

K3, Transfer Gain (K2/K1)

See Note 1, 2

K3

1.00

K2/K1

I =10 mA, V =-15 V

F det

Transfer Gain Linearity

Photoconductive Operation

Frequency Response

Phase Response at 200 KHz

Rise Time

∆K3

±0.25

±0.5

%

I =1 to 10 mA

F

I =1 to 10 mA, T =0°C to 75°C

F

A

BW (-3 db)

200

-45

KHz

Deg.

µs

I =10 mA, MOD=±4 mA, R =50 Ω,

Fq L

V

=-15 V

det

t

1.75

R

Fall Time

µs

F

Package

Input-Output Capacitance

Common Mode Capacitance

Common Mode Rejection Ratio

C

1

pF

dB

V =0 V, f=1 MHz

F

IO

0.5

130

V =0 V, f=1 MHz

F

cm

CMRR

f=60 Hz, R =2.2 KΩ

L

2. Bin Categories: All IL300s are sorted into a K3 bin, indicated by an

alpha character that is marked on the part. The bins range from “A”

through “J”.

Notes

1. Bin Sorting:

K3 (transfer gain) is sorted into bins that are ±5%, as follows:

The IL300 is shipped in tubes of 50 each. Each tube contains only

one category of K3. The category of the parts in the tube is marked

on the tube label as well as on each individual part.

Bin A=0.557–0.626

Bin B=0.620–0.696

Bin C=0.690–0.773

Bin D=0.765–0.859

Bin E=0.851–0.955

Bin F=0.945–1.061

Bin G=1.051–1.181

Bin H=1.169–1.311

Bin I=1.297–1.456

Bin J=1.442–1.618

3. Category Options: Standard IL300 orders will be shipped from the

categories that are available at the time of the order. Any of the ten

categories may be shipped. For customers requiring a narrower

selection of bins, four different bin option parts are offered.

IL300-DEFG: Order this part number to receive categories D,E,F,G

only.

IL300-EF: Order this part number to receive categories E, F only.

IL300-E: Order this part number to receive category E only.

IL300-F: Order this part number to receive category F only

K3=K2/K1. K3 is tested at I =10 mA, V =–15 V.

F

det

IL300

5–3

Figure 6. Normalized servo photocurrent vs. LED

Figure 2. LED forward current vs. forward voltage

current and temperature

35

30

25

20

15

10

5

3.0

Normalized to:IP1 @ I =10 mA,

F

T =25°C,

V =–15 V

A

2.5

2.0

1.5

1.0

0.5

0.0

0°C

D

25°C

50°C

75°C

0

1.0

0

5

10

15

20

25

1.1

1.2

1.3

1.4

IF - LED Current - mA

VF - LED Forward Voltage - V

Figure 3. LED forward current vs. forward voltage

Figure 7. Normalized servo photocurrent vs. LED

current and temperature

100

10

Normalized to IP1 @ I =10 mA,

F

T =25°C,

A

V =–15 V

D

10

1

.1

0°C

25°C

50°C

75°C

.01

.1

1.0

1

10

100

1.1

1.2

1.3

1.4

IF - LED Current - mA

VF - LED Forward Voltage - V

Figure 8. Servo gain vs. LED current and temperature

Figure 4. Servo photocurrent vs. LED current and

temperature

1.2

300

0°

25°

V =–15 V

D

0°C

1.0

250

200

150

100

50

25°C

50°C

75°C

50°

75°

0.8

0.6

0.4

0.2

0.0

85°

0

.1

1

10

100

1

10

100

IF - LED Current - mA

Figure 9. Normalized servo gain vs. LED current

and temperature

Figure 5. Servo photocurrent vs. LED current

and temperatureFigure

1.2

1000

0°

V =–15 V

Vd = -15V

25°

D

1.0

0°C

50°

75°

25°C

50°C

75°C

0.8

100

10

1

100°

0.6

0.4

Normalized to:

0.2

I =10 mA, T =25°C

F

A

0.0

.1

1

10

100

.1

1

10

100

IF - LED Current - mA

IL300

5–4

Figure 14. Common mode rejection

Figure 10.Transfer gain vs. LED current and temperature

-60

1.010

0°C

-70

1.005

-80

-90

25°C

1.000

50°C

-100

-110

75°C

0.995

-120

-130

0.990

10

100

1000

10000

100000 1000000

0

5

10

15

20

25

F - Frequency - Hz

IF - LED Current - mA

Figure 15. Photodiode junction capacitance vs. reverse

voltage

Figure 11. Normalized transfer gain vs. LED current

and temperature

1.010

14

12

10

8

Normalized to I =10 mA, T =25°C

F

A

0°C

1.005

25°C

1.000

0.995

0.990

50°C

75°C

6

4

2

0

2

4

6

8

10

0

5

10

15

20

25

Voltage - V

det

IF - LED Current - mA

Application Considerations

Figure 12. Amplitude response vs. frequency

In applications such as monitoring the output voltage from a

line powered switch mode power supply, measuring bioelectric

signals, interfacing to industrial transducers, or making ﬂoating

current measurements, a galvanically isolated, DC coupled

interface is often essential. The IL300 can be used to construct

an ampliﬁer that will meet these needs.

5

I =10 mA, Mod=±2 mA (peak)

F

0

R =1 KΩ

L

-5

The IL300 eliminates the problems of gain nonlinearity and drift

induced by time and temperature, by monitoring LED output

ﬂux.

-10

R =10 KΩ

L

-15

-20

A PIN photodiode on the input side is optically coupled to the

LED and produces a current directly proportional to ﬂux falling

on it . This photocurrent, when coupled to an ampliﬁer, provides

the servo signal that controls the LED drive current.

4

5

6

10

F - Frequency - Hz

The LED ﬂux is also coupled to an output PIN photodiode. The

output photodiode current can be directly or ampliﬁed to sat-

isfy the needs of succeeding circuits.

Figure 13. Amplitude and phase response vs. frequency

5

45

dB

Isolated Feedback Ampliﬁer

PHASE

0

The IL300 was designed to be the central element of DC cou-

pled isolation ampliﬁers. Designing the IL300 into an ampliﬁer

that provides a feedback control signal for a line powered

switch mode power is quite simple, as the following example

will illustrate.

-5

-45

-90

-135

-10

-15

-20

I

=10 mA

See Figure 17 for the basic structure of the switch mode supply

using the Siemens TDA4918 Push-Pull Switched Power Supply

Control Chip. Line isolation and insulation is provided by the

high frequency transformer. The voltage monitor isolation will

be provided by the IL300.

Fq

Mod=±4 mA

T =25°C

RL=50 Ω

A

-180

7

3

4

5

6

10

F - Frequency - Hz

IL300

5–5

Figure 16. Isolated control ampliﬁer

The isolated ampliﬁer provides the PWM control signal which

is derived from the output supply voltage. Figure 16 more

closely shows the basic function of the ampliﬁer.

+

R1

ISO

AMP

+1

To Control

Input

Voltage

Monitor

The control ampliﬁer consists of a voltage divider and a non-

inverting unity gain stage. The TDA4918 data sheet indicates

that an input to the control ampliﬁer is a high quality operational

ampliﬁer that typically requires a +3V signal. Given this infor-

mation, the ampliﬁer circuit topology shown in Figure 18 is

selected.

-

R2

For best input offset compensation at U1, R2 will equal R3. The

value of R1 can easily be calculated from the following.

The power supply voltage is scaled by R1 and R2 so that

there is +3 V at the non-inverting input (Va) of U1. This voltage

is offset by the voltage developed by photocurrent ﬂowing

through R3. This photocurrent is developed by the optical ﬂux

created by current ﬂowing through the LED. Thus as the

scaled monitor voltage (Va) varies it will cause a change in the

LED current necessary to satisfy the differential voltage

needed across R3 at the inverting input.

V_MONITOR

R1= R2 --------------------------- – 1

V_a

5V

20KΩ= 30KΩ ------ – 1

3V

The ﬁrst step in the design procedure is to select the value of

The value of R5 depends upon the IL300 Transfer Gain (K3). K3

is targeted to be a unit gain device, however to minimize the

part to part Transfer Gain variation, Siemens offers K3 graded

R3 given the LED quiescent current (I ) and the servo gain

Fq

(K1). For this design, I =12 mA. Figure 4 shows the servo pho-

Fq

tocurrent at I is found to be 100 µA. With this data R3 can be

Fq

±5

into

% bins. R5 can determined using the following equa-

calculated.

V_b

tion,

3V

100µA

V_OUT

R3 (R1 + R2)

R3=

=

= 30KΩ

-----------------

------

R5=

•

I_Pl

--------------------------- ------------------------------------

V_MONITOR

R2K3

Or if a unity gain amplifer is being designed (VMONI-

TOR=VOUT, R1=0), the euation simpliﬁes to:

R3

R5= -------

K3

Figure 17. Switch mode power supply

DC OUTPUT

AC/DC

RECTIFIER

110/

220

MAIN

AC/DC

RECTIFIER

SWITCH

XFORMER

SWITCH

MODE

REGULATOR

TDA4918

CONTROL

ISOLATED

FEEDBACK

Figure 18. DC coupled power supply feedback ampliﬁer

R1

20 KΩ

IL300

1

2

3

4

8

7

6

5

7

3

R4

100 Ω

V

+

monitor

CC

6

Va

Vb

U1

LM201

K2

R2

30 KΩ

2

1

K1

-

4

8

V

CC

100 pF

V

To

out

control

input

R3

30 KΩ

R5

30 KΩ

IL300

5–6

Table 1 gives the value of R5 given the production K3 bins.

Figure 20. Linearity error vs. input voltage

0.025

Table 1. R5 selection

0.020

LM201

Bins

Min.

Max.

K3

R5

Resistor

KΩ

1%

0.015

0.010

0.005

0.000

-0.005

-0.010

-0.015

Typ.

0.59

0.66

0.73

0.81

0.93

1.00

1.11

1.24

1.37

1.53

KΩ

A

B

C

D

E

F

G

H

I

0.560

0.623

0.693

0.769

0.855

0.950

1.056

1.175

1.304

1.449

0.623

0.693

0.769

0.855

0.950

1.056

1.175

1.304

1.449

1.610

50.85

45.45

41.1

51.1

45.3

41.2

37.4

32.4

30.0

27.0

24.0

22.0

19.4

37.04

32.26

30.00

27.03

24.19

21.90

19.61

4.0

4.5

5.0

5.5

6.0

Vin - Input Voltage - V

The AC characteristics are also quite impressive offering a -3

dB bandwidth of 100 KHz, with a -45° phase shift at 80 KHz as

shown in Figure 21.

Figure 21. Amplitude and phase power supply control

2

45

J

0

The last step in the design is selecting the LED current limiting

resistor (R4). The output of the operational ampliﬁer is targeted

to be 50% of the Vcc, or 2.5 V. With an LED quiescent current of

dB

-2

-4

-45

-90

-135

PHASE

12 mA the typical LED (V ) is 1.3 V. Given this and the opera-

F

tional output voltage, R4 can be calculated.

.

V_{op a mp}– V_F

2.5V – 1.3V

-6

-8

R4= -------------------------------- = ------------------------------ = 1 0 0 Ω

I_Fq

12mA

The circuit was constructed with an LM201 differential opera-

tional ampliﬁer using the resistors selected. The ampliﬁer was

compensated with a 100 pF capacitor connected between pins

1 and 8.

-180

6

3

4

5

10

F - Frequency - Hz

The same procedure can be used to design isolation ampliﬁers

that accept biploar signals referenced to ground. These ampliﬁ-

ers circuit conﬁgurations are shown in Figure 22. In order for the

ampliﬁer to respond to a signal that swings above and below

ground, the LED must be prebiased from a separate source by

using a voltage reference source (Vref1). In these designs, R3

can be determined by the following equation.

The DC transfer charateristics are shown in Figure 19. The

ampliﬁer was designed to have a gain of 0.6 and was mea-

sured to be 0.6036. Greater accurracy can be achieved by

adding a balancing circuit, and potentiometer in the input

divider, or at R5. The circuit shows exceptionally good gain lin-

earity with an RMS error of only 0.0133% over the input voltage

range of 4 V–6 V in a servo mode; see Figure 20.

V_{re f1}

V _{re f1}

R3= ------------ = ---------------

I_P1K1I_Fq

Figure 19.Transfer gain

3.75

Vout = 14.4 mV + 0.6036 x Vin

3.50

LM 201 Ta = 25°C

3.25

3.00

2.75

2.50

2.25

4.0

4.5

5.0

5.5

6.0

Vin - Input Voltage - V

IL300

5–7

Figure 22. Non-inverting and inverting ampliﬁers

Non-Inverting Input Non-Inverting Output

+Vref2

R5

–Vcc

Vin

R1

7

IL300

3

+

1

2

3

4

8

7

6

5

Vcc

R6

100Ω

6

2

7

–

+

R2

2

Vcc

6

Vcc

–Vcc

+Vcc

–

Vo

4

20pF

3

–Vcc

4

R3

–Vref1

R4

Inverting Output

Inverting Input

Vin

R1

7

3

+

–

Vcc

+Vref2

8

100Ω

6

IL300

1

2

3

4

R2

2

+Vcc

Vcc

7

3

+

7

6

5

Vcc

4

6

Vcc

20pF

Vout

2

–Vcc

4

–

R3

+Vref1

–Vcc

R4

Table 2. Optolinear ampliﬁers

Amp[iﬁer

Input

Output

Gain

Offset

Inverting

V_OUTK3 R4 R2

=

V_ref1R4 K3

R3

Non-Inverting

V_ref2=

V_INR3 (R1+R2)

Non-Inverting

Inverting

Non-Inverting

Inverting

V_OUTK3 R4 R2 (R5+R6)

V_INR3 R5 (R1 +R2)

–V_ref1R4 (R5+R6) K3

R3 R6

=

V_ref2

=

V_OUT–K3 R4 R2 (R5+R6)

V_ref1R4 (R5+R6) K3

R3 R6

Inverting

=

V_ref2

=

V_INR3 R5 (R1 +R2)

Non-Inverting

V_OUT–K3 R4 R2

=

–V_ref1R4 K3

R3

V_ref2

=

V_INR3 (R1 +R2)

These ampliﬁers provide either an inverting or non-inverting

transfer gain based upon the type of input and output ampliﬁer.

Table 2 shows the various conﬁgurations along with the spe-

ciﬁc transfer gain equations. The offset column refers to the

calculation of the output offset or Vref2 necessary to provide a

zero voltage output for a zero voltage input. The non-inverting

input ampliﬁer requires the use of a bipolar supply, while the

inverting input stage can be implemented with single supply

operational ampliﬁers that permit operation close to ground.

For best results, place a buffer transistor between the LED and

output of the operational ampliﬁer when a CMOS opamp is

used or the LED I drive is targeted to operate beyond 15 mA.

Fq

Finally the bandwidth is inﬂuenced by the magnitude of the

closed loop gain of the input and output ampliﬁers. Best band-

widths result when the ampliﬁer gain is designed for unity.

IL300

5–8


型号：	Q68000-A8483
厂家：	ETC
描述：	EINFACHKOPPLER MIT 2 DIODEN AUSGAENGEN EINFACHKOPPLER麻省理工学院2 DIODEN AUSGAENGEN\n
文件：	总8页 (文件大小：141K)
中文：	中文翻译
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Q68000-A8483 [ETC]

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