IMD700A-Q064X128-AA [INFINEON]
MOTIX™ 电机控制器 IMD700A 是英飞凌的完全可编程电机控制器,将XMC1404 微控制器与6EDL7141 三相栅极驱动器 IC集成在一个封装中,以支持使用 BLDC 或 PMSM 电机开发下一代电池供电产品。 集成精密电源和电流分流放大器后,许多外围电路不再需要,从而减少了 PCB 空间,提高了系统封装的可能性。;型号: | IMD700A-Q064X128-AA |
厂家: | Infineon |
描述: | MOTIX™ 电机控制器 IMD700A 是英飞凌的完全可编程电机控制器,将XMC1404 微控制器与6EDL7141 三相栅极驱动器 IC集成在一个封装中,以支持使用 BLDC 或 PMSM 电机开发下一代电池供电产品。 集成精密电源和电流分流放大器后,许多外围电路不再需要,从而减少了 PCB 空间,提高了系统封装的可能性。 电池 放大器 PC 电机 栅极驱动 控制器 微控制器 驱动器 |
文件: | 总155页 (文件大小:8472K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
MOTIX™ IMD70xA
BLDC Integrated Controller and Smart 3 Phase Gate Driver
Datasheet
Product Feature Summary
General Features
o
Fully programmable drives optimized ARM® Cortex-M0 microcontroller (XMC1404 @ 48MHz main clock)
with additional MATH Co-processor (96MHz)
o
o
o
o
o
o
3 phase smart gate driver: 1.5A sink/ 1.5A source peak gate driver currents
3 current sense amplifiers with integrated gain and offset generation
Integrated synchronous buck converter controller and LDO for complete BLDC system supply
5.5V to 60V operating voltage
Supports trapezoidal commutation (6 or 12 steps) and FOC algorithms
20 GPIOs plus up to 12 analog inputs
ARM® Cortex-M0, 32 bits microcontroller (XMC1404)
•
CPU Subsystem
o
o
o
o
o
o
o
o
o
32 bit ARM® Cortex-M0 (core clock 48MHz)
MATH Co-Processor (96MHz) for optimized 32 bit division and 24 bit trigonometric calculations
0.84 DMIPS/MHz (Dhrystone 2.1) at 48 MHz
Nested Vectored Interrupt Controller (NVIC) with 64 interrupt nodes
Internal slow and fast oscillators without the need of PLL
Real time clock module
Window watchdog
Up to 128kB of Flash (with ECC) and 16kB of RAM (with parity)
Internal oscillator
•
•
Serial Communication Modules
o
o
Four USIC channels, each of them configurable as UART, SPI, IIC and more
MultiCAN module (2 CAN nodes)
Analog Frontend Peripherals
o
12 bit A/D Converters (up to 12 analog inputs), 2 sample and hold stages up to 1.1MSamples/s
with adjustable gain
o
4 fast, general purpose analog comparators
•
Industrial Control Peripherals
o
o
2x4 16-bit 96 MHz CCU4 timers for signal monitoring and PWM
2x4 16-bit 96 MHz CCU8 timers for complex PWM, complementary high/low side switches and 3
phase inverter control
o
2x POSIF for Hall and quadrature encoders, motor positioning
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On-Chip Debug Support
o
o
4 hardware breakpoints
ARM serial wire debug, single-pin debug interfaces
Programming Support
o
o
Single-pin bootloader
Secure bootstrap loader SBSL (optional)
Three Phase Programmable Gate Driver
o
o
o
o
1.5A sink/ 1.5A source peak gate driver currents
Programmable driving voltage (7V, 10V, 12V, 15V)
Independently programmable high side/low side slew rate control
100% duty cycle
Integrated Power Supply System
o
o
High efficiency synchronous buck converter with programmable switching frequency.
Linear regulator (5V or 3.3V) with 300mA current capability supplying XMC1404 and other
external components (DVDD)
o
Dual charge pump for supplying gate driver even at low supply voltage
Three Current Sense Amplifiers
o
o
o
Integrated adjustable gain and offset
Flexible protection and behavior programming
Configurable for low side RDSON sensing
Protection features:
o
o
o
o
o
o
Easy brake mode with programmable braking response
Over-Current Protection (OCP) on current sense amplifiers (programmable)
Over-Current Protection (OCP) for buck converter and DVDD linear regulator (programmable)
Under-Voltage Lockouts (UVLO) for all internal/external supplies
Over-Voltage Fault (OVLO) reporting for buck converter and DVDD linear regulator
Over-Temperature warning and shutdown (OTW, OTS) in gate driver and microcontroller
Thermally enhanced 64pin VQFN package
Potential Applications
•
•
•
•
•
•
Battery powered power tools and gardening tools
Robotic lawn mowers
E-bikes
Robotics, RC toys, consumer drones and multi-copters
Pumps and fans
Other 3 Phase BLDC and PMSM motors
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Product Description
MOTIX™ IMD70xA is a controller specifically designed for 3 phase BLDC or PMSM drives applications. IMD70xA
integrates a fully programmable XMC1404 ARM® Cortex®-M0 microcontroller from Infineon XMC1400 family with
6EDL7141, a 60V three phase smart gate driver with integrated power supply. Both devices integrated allow an
ultra-compact design for drives applications up to 60V including not only the microcontroller and a flexible 3
phase gate driver, but also the complete power supply required in the system (synchronous buck converter and
LDO), 3 current sense amplifiers, protections and a remarkable set of configurations to adjust to specific needs.
XMC1404, ARM® Cortex®-M0 based microcontroller, incorporates dedicated features to improve motor drives
control. Features like the MATH Co-Processor, a hardware unit clocked at 96MHz, enhances the calculation of
divisions and trigonometric functions like ‘Arctan’, commonly used in Field Oriented Control of PMSM.
Additionally, XMC1404 inherits most of the high end peripherals found in XMC4000 family (ARM® Cortex®-M4),
like PWM timers-CCU8 and CCU4-, Position interface (POSIF) or serial communication modules including CAN,
ensuring best in class control.
With up to 20 dedicated general purpose pins and up to 12 analog inputs, the user has full flexibility to
implement specific functions externally like serial communications, security or safety related functions or
auxiliary functions like LEDs, buttons or displays.
Internally, XMC1404 and 6EDL7141 are connected to ensure proper operation. These interconnects enable SPI
communication between both devices for configurability and status reporting of 6EDL7141, 6 PWM signals for
driving the motor, nFAULT reporting pin to inform the microcontroller of any possible fault on the power side,
an enable driver pin, and a brake pin that can be also accessed externally for a double brake path.
6EDL7141 smart gate driver provides on the one side a flexible gate driving scheme and on the other side the
necessary robustness and protection features to avoid failures in demanding drives systems. The gate driver
outputs are placed strategically to allow best layout practices in power circuits.
In 6EDL7141, separate charge pumps for low and high side gate drivers support 100% duty cycle and low
voltage supply operation. Supplies for the gate drivers are programmable to one of the following levels: 7V,
10V, 12V or 15V. Additionally, the slew rate of the driving signal can be programmed with fine granularity to
reduce EMI emissions.
An integrated synchronous buck converter provides an efficient supply of current to the rest of the system.
However, drives systems require high precision current measurements, involving a very precise ADC reference
voltage. For that purpose, 6EDL7141 uses a linear voltage regulator (up to 300mA), powered by the buck
converter to supply XMC1404 and other components in the system. With this advanced power supply
architecture, not only the best possible signal quality is achieved, but also the power efficiency is optimized at
any input voltage.
6EDL7141 also integrates three current sense amplifiers for accurate current measurements that support bi-
directional low side current sensing with programmable gain. RDSON sensing is supported through internal
connection of the phase nodes to the current sense amplifiers inputs. Low noise, low settling times and high
accuracy are the main features of the integrated operational amplifiers. An internal buffer can be used to offset
the sense amplifier outputs for optimizing the dynamic range. The outputs of the current sense amplifiers can
be connected to ADC inputs in XMC1404 for accurate current sensing. Additional signal conditioning is therefore
possible with external RC filter. The ADC can on top provide a gain factor that can be combined with the
amplifiers one for best performance.
The device provides numerous protection features for improving application robustness during adverse
conditions, like monitoring of power supply voltages as well as system parameters. The failure behavior,
threshold voltages and filter times of the supervisions of the device are adjustable via SPI. Monitored aspects
include motor currents, gate drive voltages and currents and device temperature. When a fault occurs, the
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device stops driving and pulls nFAULT pin low, in order to prevent MOSFET damage and motor overheating.
Those signals are connected internally to XMC1404 to inform the processor that a fault has happened. The
microcontroller can request more information on the fault via SPI commands.
In order to increase robustness in drives applications, inverter, motor and supply related pins in IMD70xA can
withstand voltages of up to 90V. Motor related pins can even withstand negative voltage transients down to -8V
without compromising functionality allowing faster switching of the inverter MOSFETs, therefore reducing
switching losses.
System Block Diagram
Figure 1 shows a simplified system block diagram where MOTIX™ IMD70xA is used as 3-phase BLDC controller
Hall-sensored BLDC motor control system.
Figure 1
Simplified System Block Diagram
Package Description
MOTIX™ IMD70xA is integrated in a VQFN64 9mm x 9mm package with an exposed pad. The device and package
information is shown in Table 1.
Table 1
Device and package information
Part Number
IMD700A
Package
Body Size
Lead Pitch
0.5 mm
PG-VQFN-64-8
PG-VQFN-64-8
9.0 mm × 9.0 mm
9.0 mm × 9.0 mm
IMD701A
0.5 mm
Note:
Refer to XMC1400 Reference Manual for full description of the device including registers and
interconnects. Latest version can be found at Infineon website (www.infineon.com )
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Table of contents
Table of contents
Product Feature Summary............................................................................................................... 1
Potential Applications..................................................................................................................... 2
Product Description........................................................................................................................ 3
System Block Diagram .................................................................................................................... 4
Package Description ....................................................................................................................... 4
Table of contents............................................................................................................................ 5
1
Pin Configuration ................................................................................................................... 8
Pin Assignment........................................................................................................................................8
Pin Definition and Functions ..................................................................................................................9
Interconnects Pin Description ..............................................................................................................13
Interconnects Block Diagram ...............................................................................................................13
1.1
1.2
1.3
1.4
2
2.1
2.2
2.3
2.3.1
2.4
2.5
General Product Characteristics .............................................................................................15
Device Overview ....................................................................................................................................15
Absolute Maximum Ratings ..................................................................................................................15
Recommended Operating Conditions..................................................................................................18
XMC Pin Reliability in Overload........................................................................................................19
ESD Robustness.....................................................................................................................................20
Thermal Resistance...............................................................................................................................20
Electrical Characteristics ......................................................................................................................21
MOTIX™ 6EDL7141 Electrical Characteristics ..................................................................................21
XMC1404 Electrical Characteristics .................................................................................................30
Electrical Characteristic Graphs ...........................................................................................................33
XMC1404 Port I/O Alternate Functions Description .............................................................................40
XMC1404 Pin Definitions and Alternate Functions .........................................................................41
Port Pins for Boot Modes .................................................................................................................45
XMC1404 Chip Identification Number ..................................................................................................45
2.6
2.6.1
2.6.2
2.7
2.8
2.8.1
2.8.2
2.9
3
Drives Optimized Microcontroller Features: XMC1404 Overview.................................................46
4
4.1
4.1.1
4.1.2
4.1.3
4.1.4
4.1.5
MOTIX™ 6EDL7141 Three Phase Integrated Smart Gate Driver....................................................47
PWM Modes............................................................................................................................................47
PWM with 6 Independent Inputs – 6PWM........................................................................................48
PWM with 3 Independent Inputs – 3PWM........................................................................................49
PWM with 1 Input and Commutation Pattern – 1PWM ...................................................................50
PWM with 1 Input and Commutation with Hall Sensor Inputs – 1PWM with Hall Sensors............53
PWM with 1 Input and Commutation with Hall Sensor Inputs and Alternating Recirculation –
1PWM with Hall Sensors and Alternating Recirculation .................................................................56
PWM Braking Modes.........................................................................................................................58
Dead Time Insertion.........................................................................................................................60
Gate Driver Architecture........................................................................................................................61
Slew Rate Control..................................................................................................................................63
Slew Rate Control Parameters and Usage ......................................................................................63
Gate Driver Voltage Programmability...................................................................................................67
Charge Pump Configuration .................................................................................................................68
Charge Pump Clock Frequency Selection .......................................................................................68
Charge Pump Clock Spread Spectrum Feature ..............................................................................69
Charge Pump Pre-Charge for VCCLS ...............................................................................................69
Charge Pump Tuning .......................................................................................................................69
4.1.6
4.1.7
4.2
4.3
4.3.1
4.4
4.5
4.5.1
4.5.2
4.5.3
4.5.4
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4.6
Gate Driver and Charge Pumps Protections.........................................................................................69
4.6.1
4.6.2
4.6.3
VCCLS Under-Voltage Lock-Out (VCCLS UVLO)...............................................................................69
VCCHS Under-Voltage Lock-Out (VCCHS UVLO)..............................................................................70
Floating Gate Strong Pull Down ......................................................................................................70
5
5.1.1
5.1.2
MOTIX™ 6EDL7141 Power Supply Subsystem............................................................................72
Synchronous Buck Converter Description ......................................................................................72
DVDD Linear Regulator.....................................................................................................................74
6
MOTIX™ 6EDL7141 Current Sense Amplifiers ............................................................................76
RDSON Sensing Mode vs Leg Shunt Mode ..........................................................................................77
Current Shunt Amplifier Timing Mode ............................................................................................78
Current Shunt Amplifier Blanking Time ..........................................................................................80
Current Sense Amplifier Internal Offset Generation.......................................................................82
Overcurrent Comparators and DAC for Current Sense Amplifiers .................................................82
Current Sense Amplifier Gain Selection ..........................................................................................85
Current Sense Amplifier DC Calibration ..........................................................................................85
Auto-Zero Compensation of Current Sense Amplifier ....................................................................86
6.1.1
6.1.2
6.1.3
6.1.4
6.1.5
6.1.6
6.1.7
6.1.8
7
7.1
7.2
7.2.1
7.2.2
7.2.3
7.3
7.3.1
7.3.2
MOTIX™ 6EDL7141 House-Keeping Functions ...........................................................................89
Hall Comparators ..................................................................................................................................89
Watchdog Timer ....................................................................................................................................89
Buck converter watchdog................................................................................................................90
General Purpose Watchdog .............................................................................................................90
Locked-Rotor Protection Watchdog Timer .....................................................................................90
Gate Driver ADC Module-Analog to Digital Converter..........................................................................91
6EDL7141 ADC Measurement Sequencing and On Demand Conversion.......................................93
Die Temperature Sensor..................................................................................................................93
8
MOTIX™ 6EDL7141 Protections and Faults Handling ..................................................................94
9
9.1.1
9.1.2
MOTIX™ 6EDL7141 Programming-OTP and SPI interface............................................................99
MOTIX™ 6EDL7141 OTP User Programming Procedure: Loading Custom Default Values ..........100
MOTIX™ 6EDL7141 SPI Communication........................................................................................101
10
Device Start-up and Functional States................................................................................... 107
MOTIX™ 6EDL7141 Power Supply Start-up.........................................................................................107
Power Supply System Start-up......................................................................................................107
Gate Driver and CSAMP Start-up ...................................................................................................107
Device Functional States.....................................................................................................................110
10.1
10.1.1
10.1.2
10.2
11
Register Map....................................................................................................................... 113
XMC1404 Registers ..............................................................................................................................113
MOTIX™ 6EDL7141 Smart Gate Driver Register Map ..........................................................................113
MOTIX™ 6EDL7141 Registers Programmability ..................................................................................114
MOTIX™ 6EDL7141 Register Map.........................................................................................................117
11.1
11.2
11.3
11.4
Faults Status Register ..............................................................................................................................................117
Temperature Status Register ..................................................................................................................................118
Power Supply Status Register .................................................................................................................................119
Functional Status Register ......................................................................................................................................120
OTP Status Register .................................................................................................................................................121
ADC Status Register .................................................................................................................................................122
Charge Pumps Status Register................................................................................................................................122
Device ID Register ....................................................................................................................................................123
Faults Clear Register ................................................................................................................................................123
Power Supply Configuration Register.....................................................................................................................124
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ADC Configuration Register .....................................................................................................................................126
PWM Configuration Register....................................................................................................................................127
Sensor Configuration Register ................................................................................................................................128
Watchdog Configuration Register ...........................................................................................................................129
Watchdog Configuration Register 2 ........................................................................................................................130
Gate Driver Current Control Register ......................................................................................................................131
Gate Driver Pre-Charge Current Control Register...................................................................................................133
TDRIVE Source Control Register..............................................................................................................................134
TDRIVE Sink Control Register ..................................................................................................................................134
Dead Time Register..................................................................................................................................................135
Charge Pump Configuration Register .....................................................................................................................136
Current Sense Amplifier Configuration Register ....................................................................................................137
Current Sense Amplifier Configuration Register 2..................................................................................................139
OTP Program Register .............................................................................................................................................141
12
Application Description........................................................................................................ 142
Recommended External Components ...............................................................................................142
PCB Layout Recommendations ..........................................................................................................142
Typical Applications............................................................................................................................146
12.1
12.2
12.3
13
14
ESD Protection.................................................................................................................... 149
Package Information ........................................................................................................... 152
Revision history........................................................................................................................... 154
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Pin Configuration
1
Pin Configuration
1.1
Pin Assignment
In Figure 2, the pinout of MOTIX™ IMD70xA is presented.
Figure 2
Pin configuration
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Pin Configuration
1.2
Pin Definition and Functions
Details regarding the pins of IMD70xA are shown in Table 1.
I: Input, O: output, IO: Input and/or Output, D: Digital, A: Analog, AD: Analog and/or Digital, P: Power, G: Ground.
Table 1
Pin Definition
XMC
Pin # Pin Name
IO
Type
Description
Port
GPIO0/
P4.4
General purpose digital I/O. Standard bi-directional
pads
1
P4.4 IO
P4.5 IO
D -(STD_INOUT)
D -(STD_INOUT)
GPIO1/
P4.5
General purpose digital I/O. standard bi-directional
pads
2
Microcontroller voltage supply. DVDD is generated
from DVDD linear regulator in 6EDL7141 (pin 23 and
56) and must be connected to all DVDD pins. This
voltage can be used to supply external components
as well. Connect a capacitor to DGND in every DVDD
pin.
VDD/
IO
3
DVDD
P
VDDP
GPIO2/
P4.6
4
5
6
7
P4.6 IO
P4.7 IO
P4.8 IO
P4.10 IO
D -(STD_INOUT) General purpose digital I/O
D -(STD_INOUT) General purpose digital I/O
D -(STD_INOUT) General purpose digital I/O
GPIO3/
P4.7
GPIO4/
P4.8
GPIO5/
P4.10
D -(STD_INOUT) General purpose digital I/O
A/D -
GPIO6_AI
N0/P2.0
8
9
P2.0
P2.1
I
I
(STD_INOUT/A
N)
Analog input
A/D -
(STD_INOUT/A
N)
GPIO7_AI
N1/P2.1
Analog input
10
11
12
13
14
15
16
17
AIN2/P2.2
AIN3/P2.3
AIN4/P2.4
AIN5/P2.5
AIN6/P2.6
AIN7/P2.7
AIN8/P2.8
AIN9/P2.9
P2.2
P2.3
P2.4
P2.5
P2.6
P2.7
P2.8
P2.9
I
I
I
I
I
I
I
I
A - (STD_IN/AN) Analog input
A - (STD_IN/AN) Analog input
A - (STD_IN/AN) Analog input
A - (STD_IN/AN) Analog input
A - (STD_IN/AN) Analog input
Analog input
A - (STD_IN/AN)
A - (STD_IN/AN) Analog input
A - (STD_IN/AN) Analog input
A/D -
GPIO8_AI
N10/P2.10
Dual functionality pin. Analog input and general
purpose digital I/O
18
P2.10 IO
(STD_INOUT/A
N)
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Pin Configuration
XMC
Port
Pin # Pin Name
IO
Type
Description
A/D -
(STD_INOUT/A
N)
GPIO9_AI
19
Dual functionality pin. Analog input and general
purpose digital I/O
P2.11 IO
P2.12 IO
P2.13 IO
N11/P2.11
A/D -
(STD_INOUT/A
N)
GPIO10/P
2.12
20
General purpose digital I/O
General purpose digital I/O
A/D -
(STD_INOUT/A
N)
GPIO11/P
2.13
21
VSS/
VSSP
Ground connection for digital section. Supply GND,
ADC reference GND
22
23
DGND
DVDD
P
P
Microcontroller voltage supply. DVDD is generated
from DVDD linear regulator in 6EDL7141 (pin 23 and
56) and must be connected to all DVDD pins. This
voltage can be used to supply external components
as well. Connect a capacitor to DGND in every DVDD
pin.
VDD/
IO
VDDP
D (High
Current)
After start-up, pin is used for motor braking. Active
low
24
25
26
nBRAKE
PVDD
PH
P1.31)
I
-
-
P
Power supply of the device
Buck phase node voltage. Connect to output
inductor
O
-
P
Power ground used for buck converter, charge
pumps and gate drivers
27
28
PGND
VDDB
-
-
G
P
Buck output voltage. Connect capacitor between
VDDB and PGND.
-
Bottom connection of the charge pump flying
capacitor 1
29
30
31
32
33
CP1L
CP1H
CP2L
CP2H
VCCLS
-
-
-
-
-
-
-
-
-
-
P
P
P
P
P
Top connection of the charge pump flying capacitor 1
Bottom connection of the charge pump flying
capacitor 2
Top connection of the charge pump flying capacitor 2
Output of low side charge pump. Connect a capacitor
from VCCLS to PGND.
Output of high side charge pump. Connect a
capacitor from VCCHS to PVDD or PGND.
34
35
VCCHS
GHC
-
-
-
P
A
High side gate driving signal for phase C. Not
connected or connected to PVDD if not used
O
High side source connection (phase node) for phase
C.
Positive input of shunt amplifier C for RDSON sensing.
Not connected if not used
36
SHC
N.C.
-
-
IO
A
37
Not connected
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Pin Configuration
XMC
Port
Pin # Pin Name
IO
Type
Description
Low side gate driving signal for phase C. Not
connected if not used
38
39
GLC
SLC
-
O
A
Low side source connection for phase C.
Positive input of shunt amplifier C for shunt sensing.
Short to PGND if not used
-
IO
A
Current sense amplifier negative input for phase C.
Short to PGND or DGND if not used
40
41
CSNC
CSNB
-
-
I
I
A
A
Current sense amplifier negative input for phase B.
Short to PGND or DGND if not used
Low side source connection for phase B.
42
SLB
-
IO
O
A
A
Positive input of shunt amplifier B for shunt sensing.
Short to PGND if not used
Low side gate driving signal for phase B. Not
connected if not used
43
44
GLB
N.C.
-
-
Not connected
High side source connection (phase node) for phase
B.
Positive input of shunt amplifier B for RDSON sensing.
Not connected if not used
45
SHB
-
IO
A
High side gate driving signal for phase B. Not
connected or connected to PVDD if not used
46
47
GHB
GHA
-
-
O
O
A
A
High side gate driving signal for phase A. Not
connected or connected to PVDD if not used
High side source connection (phase node) for phase
A.
Positive input of shunt amplifier A for RDSON sensing.
Not connected if not used
48
SHA
-
IO
A
49
50
GLA
SLA
-
-
O
A
A
Not connected
Low side gate driving signal for phase A. Not
connected if not used
IO
Current sense amplifier negative input for phase A.
Short to PGND or DGND if not used
51
52
53
CSNA
CSOA
CSOB
-
-
-
I
A
A
A
Current sense amplifier output for phase A. Not
connected if not used
O
O
Current sense amplifier output for phase B. Not
connected if not used
Current sense amplifier output for phase C. Not
connected if not used
54
55
CSOC
CE
-
-
O
I
A
D
Chip Enable. Starts up the device upon rising edge
Microcontroller voltage supply. DVDD is generated
from DVDD linear regulator in 6EDL7141 (pins 23 and
56) and must be connected to all DVDD pins. This
voltage can be used to supply external components
VDD/
VDDP
56
DVDD
-
P
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Pin Configuration
XMC
Port
Pin # Pin Name
IO
Type
Description
as well. Connect a capacitor to DGND in every DVDD
pin. XCM1404 I/O port supply
D -
GPIO12/P0
.10
General purpose digital I/O. Can be used as high
precision crystal/oscillator input
57
P0.10 IO
P0.11 IO
(STD_INOUT/cl
ock_IN)
D -
GPIO13/P0
.11
General purpose digital I/O. Can be used as high
precision crystal/oscillator input
58
(STD_INOUT/cl
ock_O)
GPIO14/P0
.12
GPIO15_D
BG0/P0.14
59
P0.12 IO
P0.14 IO
P0.15 IO
P4.1 IO
P4.2 IO
P4.3 IO
D -(STD_INOUT) General purpose digital I/O
General purpose digital I/O. This is SWD pin for
60
D -(STD_INOUT)
D -(STD_INOUT)
D -(STD_INOUT)
D -(STD_INOUT)
D -(STD_INOUT)
microcontroller debug I/F
GPIO16_D
61
General purpose digital I/O. This is SWCLK pin for
microcontroller debug I/F
BG1/P0.15
GPIO17/P4
General purpose digital I/O. Can be used as Hall
sensor input for POSIF module
62
.1
GPIO18/P4
General purpose digital I/O. Can be used as Hall
sensor input for POSIF module
63
.2
GPIO19/P4
General purpose digital I/O. Can be used as Hall
sensor input for POSIF module
64
.3
Ground connection for digital section. Solder to PCB.
Exposed Die Pad The exposed die pad is connected
internally to VSSP. For proper operation, it is
mandatory to connect the exposed pad to the board
ground
ePad DGND
VSS
-
G
1. Dual path for braking: internal connection of P1.3 through gate driver die
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Datasheet
Pin Configuration
1.3
Interconnects Pin Description
Table 2 shows a list of details of the interconnected pins between XMC1404 controller and 6EDL7141
Table 2
Interconnects between devices
XMC
Port Pin
6EDL7141
XMC Pad Type
6EDL7141 Pin Description
Pin
P0.7
STD_INOUT (standard
bi-directional pads)
EN_DRV
Input digital. Enables the gate driver section and
internal circuitry based on the configuration. Internal
pull-down.
P0.4
P0.3
P0.1
P0.0
P3.4
P3.3
P3.2
P3.1
P3.0
P1.0
STD_INOUT (standard
bi-directional pads)
nSCS
SCLK
SDO
Input digital. Active low. Chip select for SPI
communication
STD_INOUT (standard
bi-directional pads)
Input digital. Internal pull down. SPI Clock signal from
XMC (master)
STD_INOUT (standard
bi-directional pads)
Output digital. Internal pull down. SPI data input for
XMC (master)
STD_INOUT (standard
bi-directional pads)
SDI
Input digital. Internal pull down. SPI data output for
XMC (master)
STD_INOUT (standard
bi-directional pads)
nFAULT
INHA
INLA
INHB
INLB
INHC
Output digital. When low indicates a fault in 6EDL7141.
Active low
STD_INOUT (standard
bi-directional pads)
Input digital. PWM input high side phase A. Internal
pull down
STD_INOUT (standard
bi-directional pads)
Input digital. PWM input low side phase A. Internal pull
down
STD_INOUT (standard
bi-directional pads)
Input digital. PWM input high side phase B. Internal
pull down
STD_INOUT (standard
bi-directional pads)
Input digital. PWM input low side phase B. Internal pull
down
High Current (high
current bi-directional
pads)
Input digital. PWM input high side phase C. Internal
pull down
P1.1
High Current (high
current bi-directional
pads)
INLC
AZ
Input digital. PWM input low side phase C. Internal pull
down
P1.2
High Current (high
current bi-directional
pads)
Controller can use this pin to control Auto-Zero
function.
P1.3 1)
High Current (high
current bi-directional
pads)
nBRAKE
Input digital. Active low. Used for motor braking
function in 6EDL7141. Pull up required via XMC P1.3
1. Dual path for braking: external connection of IMD70xA via pin 24
1.4
Interconnects Block Diagram
A block diagram showing the interconnection between XMC1404 and 6EDL7141 is given in Figure 3
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Pin Configuration
Figure 3
IMD70xA Interconnects block diagram
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Datasheet
General Product Characteristics
2
General Product Characteristics
2.1
Device Overview
Table 3 shows the XMC1404 configuration regarding peripherals, core and memory.
Table 3
XMC1404 Feature Overview
Features IMD700A-Q064x0128
IMD701A-Q064x0128
Controller supply voltage
CPU Clock Frequency
Flash size (Kbytes)
3.3V
48 MHz
128
5V
48 MHz
128
16
SRAM size (Kbytes)
MATH co-processor
16
1
1
Auxiliary Timers (CCU4
units/timers/outputs)
2/8/8
2/8/8
PWM Timers (CCU8
units/timers/outputs)
2/8/321)
2
2/8/321)
2
Hall Sensor/Encoder Interface
(POSIF units)
Serial Communication (channels)
MultiCAN+ (nodes/MOs)
ADC (kernels/inputs)
Analog Comparators
BCCU (units)
4
4
2/32
2/12
4
2/32
2/12
4
1
1
LEDTS (units)
3
3
1. Depending on pin availability. See Table 13 for possible pin functionality
2.2
Absolute Maximum Ratings
Table 4 shows the absolute maximum ratings for the device. Ratings are intended in the temperature range Tj=-
40oC to Tj=115oC. All voltages are referred to ground (PGND for buck converter, charge pumps and gate driver
related parameters and DGND for the rest), positive currents are flowing into the pin (unless otherwise
specified).
Table 4
Absolute Maximum Ratings
Parameter Symbol
PVDD
Values
Unit
Condition
Min
Typ
Max
Supply voltage
-0.3
70
2
V
During start-up
During active mode
Supply voltage slew
rate
SRPVDD
V/μs
0.25
7
CE pin voltage
VCE
-0.3
-0.3
V
V
Power ground to
digital ground voltage
PGND – DGND
0.3
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General Product Characteristics
Values
Parameter
Symbol
Unit
Condition
Min
Typ
Max
Low side gate driver
supply voltage
VCCLS
VCCHS
-0.3
20
90
V
This is same as PVCC
VCCHS = PVDD + PVCC
VCCHS voltage
PVDD-
0.3
V
VCCHS-VSHx voltage
VCCHS-VGHx voltage
VCCHS-VSHx
VCCHS-VGHx
VSHx
90
90
70
70
8
V
V
V
Source high side
voltage
-8
DC voltage
-10
-8
500ns pulse max
DC voltage
Source low side
voltage/Shunt
amplifier positive
input voltage
VSLx
V
-10
8
500ns pulse max
Gate high side voltage VGHx
-8
VCCHS+0.3
VCCHS+0.3
VCCLS+0.3
VCCLS+0.3
16
V
V
V
DC voltage,
-10
-8
500ns pulse max,
DC voltage
Gate low side voltage
VGLx
-10
-0.3
-2
500ns pulse max
DC, Tj = 25 oC
Gate to Source high
side voltage
VGHx - VSHx
16
500ns pulse max, Tj = 25
oC
Gate to Source low
side voltage
VGLx - VSLx
-0.3
-2
16
16
V
DC, Tj = 25 oC
500ns pulse max, Tj = 25
oC
Shunt amplifier
negative input voltage
VCSN
-0.3
-0.3
DVDD+0.3
9
Flying capacitor 1
voltage
VCP1H - VCP1L,
V
CP1L pin voltage
CP1H pin voltage
VCP1L
VCP1H
-0.3
-0.3
9
V
V
20
Flying capacitor 2
voltage
VCP2H - VCP2L
-0.3
70
V
CP2L pin voltage
CP2H pin voltage
VCP2L
VCP2H
-0.3
-0.3
20
90
V
V
Buck converter output
voltage
VDDB
VPH
-0.3
9
V
-0.3
-5
V
V
DC condition
Buck converter phase
voltage continuous
70
6
Less than 20 ns pulse
DVDD regulator output
voltage
DVDD
-0.3
V
Current sense
amplifier output
voltage
DVDD
+ 0.3
VCSOx
-0.3
V
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General Product Characteristics
Values
Typ Max
Parameter
Symbol
Unit
mA
Condition
Min
Maximum current for
6EDL7141 digital pins
IDIG_IN_MAX
-1
1
Maximum current for
6EDL7141 analog
inputs
IAN_IN_MAX
VGPIO_INx
-1
10
mA
V
Voltage on GPIOx
digital pins with
respect to DGND)
Voltage on AINx 1)
XMC1404 Port 2 pins
with respect to DGND
-0.5
–
–
DVDD + 0.5
or max. 6
Whichever is lower
VAINx
-0.3
-0.5
DVDD + 0.3
V
V
–
Voltage on other AINx
–
DVDD + 0.5
or max. 6
Whichever is lower
XMC1404 pins 2)
VAINx
with respect to DGND
Input current on
GPIOx/AINx pin during
overload condition
IGPIO/AIN
-10
-50
–
–
10
mA
mA
Absolute maximum
sum of all input
currents in
IGPIO/AIN
+50
GPIOx/ADC_INx pins
during overload
condition
Maximum current for
GPIOx digital pins
IGPIO_DIG_IN_MAX
IAN_IN_MAX
TJ
-1
-1
1
mA
mA
oC
Maximum current for
XMC1404 analog
inputs (AINx)
10
115
Junction temperature
range
-40
-55
Storage temperature
range
TS
125
145
oC
oC
Case temperature
TCASE
1. Excluding port pins P2.[1,2,6,7,8,9,11].
2. Applicable to port pins P2.[1,2,6,7,8,9,11].
Note:
Stresses above the ones listed here may cause permanent damage to the device. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability. These are
stress ratings only which do not imply functional operation of the device at these or any other
conditions beyond those indicated under Recommended Operating Conditions.
Note:
Absolute Maximum Ratings are not subject to production test, specified by design.
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General Product Characteristics
2.3
Recommended Operating Conditions
Operating at TA = 25 oC. All voltages are referred to ground (PGND for buck converter, charge pumps and gate
driver related parameters and DGND for the rest), positive currents are flowing into the pin (unless otherwise
specified).
Values are design targets to be confirmed after silicon characterization.
Table 5
Recommended operating conditions
Values
Parameter
Symbol
PVDD
Unit
Condition
Min
Typ Max
Supply voltage
5.5
60
2
V
During start-up
Supply voltage slew rate SRPVDD
V/μs
0.25
6
During active mode
CE pin voltage range
VCE
0
V
V
External supply voltage
regulator output voltage
DVDD
5.5
-0.3
-5
DC condition
Buck phase voltage
continuous
VPH
60
V
Less than 20 ns pulse
Inverter phase voltage
VSHx
-8
60
75
High side gate driver
supply voltage
VCCHS
-0.3
7
V
V
VCCLS,
VCCHS-PVDD
Gate driver supply
voltage (PVCC)
Programmable via SPI. This
value is equal to PVCC
15
Gate driver maximum
operating frequency
fPWM_GD
200
0.3
kHz
V
Shunt amplifier input
voltage range
Sense amplifier configured for
shunt resistor sensing
VSLx, VCSNx
-0.3
0
Current sense amplifier
output pins voltage
range
VCSOx
DVDD
DVDD
5
V
Digital GPIOx or AIN pin
voltage range
VGPIOX/AINx
-0.3
-5
V
Short circuit current of
all XMC digital outputs
ISC
mA
Absolute sum of short
circuit currents of the
XMC device
∑ISC_D
25
mA
Junction temperature
range
TJ
-40
115
°C
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General Product Characteristics
2.3.1
XMC Pin Reliability in Overload
When receiving signals from higher voltage devices, low-voltage devices experience overload currents and
voltages that go beyond their own IO power supplies specification.
Table 6 defines overload conditions that will not cause any negative reliability impact if all the following
conditions are met:
•
•
Full operation life-time is not exceeded
Operating Conditions are met for
o
o
pad supply levels (DVDD)
temperature
If an XMC pin current is outside of the Recommended Operating Conditions but within the overload conditions,
then the parameters of this pin as stated in the Recommended Operating Conditions can no longer be
guaranteed. Operation is still possible in most cases but with relaxed parameters.
Note:
Note:
An overload condition on one or more pins does not require a reset.
A series resistor at the pin to limit the current to the maximum permitted overload current is
sufficient to handle failure situations like short to battery.
Table 6
Overload Parameters
Values
Min. Typ. Max.
Note /
Test Condition
Parameter
Symbol
Unit
mA
IOV
Input current on any XMC port pin
during overload condition
-5
–
5
IOVS
Absolute sum of all XMC input circuit
currents during overload condition
–
–
25
mA
Figure 4 shows the path of the input currents during overload via the ESD protection structures. The diodes
against DVDD and ground are a simplified representation of these ESD protection structures.
Figure 4
XMC1404 Input Overload Current via ESD structures
Table 7 and Table 8 list input voltages that can be reached under overload conditions. Note that the absolute
maximum input voltages as defined in the Absolute Maximum Ratings must not be exceeded during overload.
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General Product Characteristics
Table 7
PN-Junction Characteristics for Positive Overload for XMC1404 pins
Pad Type
IOV=5mA
Standard, High-current, AINx/DIG_IN
VIN = VDVDD + 0.5V
VAINx = VDVDD + 0.5V
VAREF = VDVDD + 0.5V – XMC1404 analog reference
P2.[1,2,6:9,11]
VAIN_P2 = VDVDD + 0.3V
Table 8
PN-Junction Characteristics for Negative Overload for XMC1404 pins
IOV=5mA
Pad Type
Standard, High-current, AINx/DIG_IN
VIN = VDGND - 0.5V
VAINx = VDGND -0.5V
VAREF = VDGND -0.5V – XMC1404 analog reference
VAINP2= VDGND +0.3V
P2.[1,2,6:9,11]
2.4
ESD Robustness
ESD robustness related data is listed in Table 9.
Table 9
ESD robustness data1)
Symbol
Values
Min
Parameter
Unit
Condition
Typ
Max
ESD robustness all
pins
2000
V
HBM2)
|VESD_HBM
|VESD_CDM
|VESD_CDM_CORNER
|
ESD robustness all
pins
500
750
V
V
CDM3)
|
ESD robustness
(corner pins)
CDM3) for cornet pins only
|
1) Not subject to production test, specified by design
2) ESD robustness, Human Body Model (HBM) according to ANSI/ESDA/JEDEC JS001 (1.5kΩ, 100 pF)
3) ESD robustness, Charge Device Model (CDM) according to ANSI/ESDA/JEDEC JS-002
2.5
Thermal Resistance
Note:
This thermal data was generated in accordance with JEDEC JESD51 standards. For more
information, go to www.jedec.org.
Table 10
Thermal resistance parameters
Values
Parameter
Symbol
Unit
Condition
Min
Typ
Max
Junction-to-ambient
thermal resistance
RθJA
Ta = 25 °C, FR4 PCB, size:
76.2 114.3 1.57 mm3,
stack 2S2P
29.5
°C/W
Junction-to-case (top)
thermal resistance
RθJC(top)
Ta = 25 °C
18.9
°C/W
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General Product Characteristics
Values
Typ
Parameter
Symbol
RθJC(bot)
Unit
Condition
Ta = 25 °C
Min
Max
Junction-to-case
(bottom) thermal
resistance
6.45
°C/W
2.6
Electrical Characteristics
MOTIX™ 6EDL7141 Electrical Characteristics
2.6.1
PVDD = 5.5 to 60 V, T = 25°C, unless specified under test condition. All voltages are referred to ground (PGND for
A
buck converter, charge pumps and gate driver related parameters and DGND for the rest), positive currents are
flowing into the pin (unless otherwise specified).
Table 11
Electrical characteristics
Values
Typ
Parameter
Symbol
Unit
Condition
Min
Max
Power Supply (PVDD)
Supply voltage
PVDD
5.5
15
60
55
V
PVDD current, ACTIVE
mode including
XMC14042)
VEN_DRV > VEN_DRV_TH, VCE > VCE_TH_R
,
IPVDD_ACTIVE
mA
PVDD = 40V, typical application.
PVDD current ,
VEN_DRV < VEN_DRV_TH , VCE > VCE_TH_R
PVDD = 13V, typical application
,
STANDBY mode
IPVDD_STANDBY 10.5
15
20
mA
µA
including XMC14042)
PVDD current, OFF
mode (STOP state)
including XMC14042)
VEN_DRV < VEN_DRV_TH , VCE < VCE_TH_R.
PVDD = 13V, typical application
IPVDD_OFF
5
Gate Driver Output
Generated from charge pump. Gate
driver supply voltage
programmable via SPI
Low side gate driver
supply voltage target
VCCLS
VCCHS
7
15
V
Generated from charge pump. Gate
driver supply voltage
programmable via SPI according to
VCCLS
High side gate driver
supply voltage target
10.8
74.3
V
V
High side gate driver
output
VCCLS
- 0.7
VGHx-SHx
VGLx-SLx
0
0
More details in section 2.7
More details in section 2.7
Low side gate driver
output
VCCLS V
A
Peak source current
(high side and low
side drivers)
Current flowing from pin. Gate
driver current programmable via
SPI
IGD_SRC_PEAK
1.5
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General Product Characteristics
Values
Typ
Parameter
Symbol
Unit
Condition
Min
Max
Peak sink current
(high side and low
side drivers)
Current into the pin. Gate driver
current programmable via SPI
IGD_SNK_PEAK
1.5
A
250
50
Low side gate driver
High side gate driver
Hold gate current1)
IHOLD
mA
%
Source and sink
current accuracy
IGD_ACCURACY
-20
20
Charge pump clock
frequency
fCP_CLK
190
1600 kHz
Programmable via SPI
Charge pump clock
accuracy
fCP_CLK_ACC
-5
0
5
%
%
Charge pump clock accuracy
Charge pump clock
frequency spread
spectrum1)
fCP_CLK_SS
30
60
30
60
30
PVDD ≥ 9.5 V operation
PVDD < 9.5 V operation
PVDD ≥ 9.5 V operation
PVDD < 9.5 V operation
High side gate driver
average current
IGD_VCCHS
IGD_VCCLS
mA
mA
Low side gate driver
average current
CCP1/2 = 220 nF, CVCCLS=1 μF, ILOAD <50
μA, PVCC = 12 V. PVDD ≥ 10 V.
Depends on capacitance values and
features like charge pump pre-
charge
250
µs
Charge pump ramp
up time1)
tCP_START
CCPx = 220 nF, CVCCLS=1 μF, ILOAD <50
μA, PVCC = 12 V. PVDD < 10 V.
Depends on capacitance values and
features like charge pump pre-
charge
1
ms
Gate driver PWM
frequency
fPWM_GD
200
kHz
ns
Applies to INHx and INLx pins. Pre-
charge current disabled, current
setting to 1.5A
Input pin pulse width tINx_PW
80
This is the minimum dead time
value possible. If input signals have
dead time lower than this, this
value applies otherwise input PWM
signal dead time is used. Value is
programmable via SPI.
tDT_RISE
tDT_FALL
,
Dead-time1)
120
70
ns
Gate to Source
passive weak pull-
down resistor
Datasheet
RGS_PD_WEAK
100
130
kΩ
Always active
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General Product Characteristics
Values
Typ
Parameter
Symbol
Unit
Condition
Min
Max
Pull-down resistor enabled when
Gate to Source active
strong pull-down
resistor
EN_DRV or PVDD are off and VGxy
–
RGS_PD_STRONG 0.25
1
2
kΩ
VSxy ≥ 2 V. Both high side and low
side drivers
Propagation delay
INHx to GHx
tPROP_HS
tPROP_LS
140
140
200
200
ns
ns
Dead time not considered
Dead time not considered
Propagation delay
INLx to GLx
Propagation delay
matching high-low
side1)
tPROP_MATCH_HL
0
25
ns
Channel-to-channel
propagation delay
matching1)
tPROP_MATCH_CH
0
0
10
10
ns
ns
Channel-to-channel
dead time matching1)
tDT_MATCH_CH
Threshold voltage referred to:
Gate to source
comparator
threshold
For pull down GHx - SHx (resp. GLx-
SLx for low side driver).
For pull up VCCHS - GHx (resp.
VCCLS - GLx for low side driver)
VGS_CPM_TH
250
500
mV
ns
Gate to source
comparator deglitch
time1)
tVGS_CMP_DEGLI
TCH
Synchronous Buck Converter
PVCC_SETPT=b’11, PVDD ≥ 8 V,
IVDDB = 0 A
6.5
Buck converter
output target voltage
PVCC_SETPT=b’10, PVDD ≥ 8.5 V,
IVDDB = 0 A
VDDBNOM
7.0
8.0
V
PVCC_SETPT=b’0x, PVDD ≥ 9.5 V,
IVDDB = 0 A
PVCC_SETPT=b’11,
5.5 V ≤ PVDD < 8 V
Buck with fixed 90% duty cycle.
VDDB dependent on IVDDB. Min
value defined at IVDDB = 200mA
condition
4.6
4.6
6.5
Buck regulator
output voltage at low VDDBNOM_LV
input voltage (PVDD)
V
PVCC_SETPT=b’10,
5.5 V ≤ PVDD < 8.5 V
Buck with fixed 90% duty cycle.
VDDB depends on IVDDB. Min value
defined at IVDDB = 200mA condition
7.0
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General Product Characteristics
PVCC_SETPT=b’0x,
5.5 V ≤ PVDD < 9.5 V
4.6
8.0
Buck with fixed 90% duty cycle.
VDDB depends on IVDDB. Min value
defined at IVDDB = 200mA condition
PVDD > VDDBNOM + 2.5 V, IVDDB
transient from 60 mA to 540 mA
(10% to 90% load transient), CVDDB
= 47 µF, L = 22 µH, fBUCK_SW = 500
kHz
-10
9
5
%
%
Buck converter
output voltage load
ΔVDDBLOAD
PVDD > VDDBNOM + 2.5 V, IVDDB
transient from 60 mA to 540 mA
(10% to 90% load transient), CVDDB
= 47 µF, L = 10 µH, fBUCK_SW = 1000
kHz
regulation1)
-9.5
PVDD ≥ 9.5 V. VDDB supplies
charge pumps, DVDD linear
regulator and VDDB pin
600
200
mA
mA
Buck converter
maximum average
current
IVDDB_MAX
PVDD at low input voltage range
(VDDBNOM_LV). VDDB supplies
charge pumps, DVDD linear
regulator and VDDB pin
Buck converter
maximum duty cycle
DCBUCK_MAX
95
%
Ω
Ω
Buck converter high
side switch RDSON
RDSON_BUCK_HS 0.7
1.4
2.2
Buck converter low
side switch RDSON
RDSON_BUCK_LS 0.3
440
850
0.45
500
1.0
590
Buck switching
frequency
Configurable via OTP write. May
vary during load steps.
fBUCK_SW
kHz
µs
1000 1150
1500
Buck converter soft
start timing
Actual value depends on buck
output filter
tVDDB_SFT_START
Linear Regulator DVDD
3.3
IMD700A part number
IMD701A part number
Regulator target
output voltage
DVDD
V
5.0
Output voltage
accuracy
DVDDACC
-2.5
2.5
%
DVDD load current
IDVDD
300
mA
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Datasheet
General Product Characteristics
DVDD load current
IDVDD_LIM
50
450
10
mA Programmable via SPI
limit
mV
mV
µs
Static line regulation ΔDVDDLINE
Static load regulation ΔDVDDLOAD
VDDB=6.5 V...8 V, IDVDD=300 mA
VDDB=DVDD+1.5 V, IDVDD = 1 mA to
300 mA step
40
Analog programming
tAN_T
25
CS_GAIN
pins period
Programmable via SPI. Delay
between VDDB UVLO until DVDD
ramp up start
DVDD turn on delay
tDVDD_TON_DLY 200
800
µs
Configurable via SPI- Current
limited by IDVDD_I_LIM. If due to larger
CDVDD values, programmed timing is
not achievable, start-up time is
DVDD soft start
timing
tDVDD_SFT_
START
µs
100
1600
defined by 푡퐷푉퐷퐷_푆퐹푇_푆푇퐴푅푇
=
퐶
∗ 퐷푉퐷퐷
ꢀꢁꢀꢀ
퐼
ꢀꢁꢀꢀ_ꢂ_퐿ꢂ푀
Current Sense Amplifier
Configured either via external resistor
or SPI
Closed loop gain
Gain error1)
GCS
4
64
V/V
GCS_ERROR
-1
1
%
Measured at SLx-CSNx=0.025 V
Gain=32, inputs shorted
Offset input referred1) VCS_OS
200
5
600
µV
ΔVCS_OS
ΔT
/
μV/
oC
Offset temperature
drift1)
Current sense
blanking time
tCS_BLANK
0
8
µs
Programmable via SPI
Time from input signal step to 1% of
final output voltage. Input voltage
step of 0.2 V. Gain 4 to 24
600
Amplifier output
settling time 1)
tCSO_SETTLING
ns
Settling time from input signal step to
1% of final output voltage. Input
voltage step of 0.2 V. Gain 32 to 64
1000
Unity gain
MHz
dB
GBW
5
8
bandwidth1)
Common mode
rejection ratio1)
CMRR
60
80
Gain=8, fSW from 0 Hz to 80 kHz
60
40
Gain=8, f<1 MHz
Power supply
PSRR
ICSN
dB
rejection ratio 1)
Gain=8, f<10 MHz
Current drawn into pin
Input bias current
50
μA
Datasheet
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Datasheet
General Product Characteristics
Common mode input
VCS_COM
-0.3
-0.3
0.3
0.3
0.3
V
V
V
range1)
Differential mode
input range
VCS_DIFF
DVDD-
0.3
Current sense output
VCSO
voltage range
Output voltage slew
V/μ
s
Gain=8, RL=470 Ω, CL=330 pF. VSLx = +/-
250 mV
10
SRCSO
-10
rate1)
Propagation delay
from gate driver (Gxy)
130
400
CSAMP in shunt mode
tCSAMP_PROP
ns
V
transition to CSOx
CSAMP in RDSON mode
activation1)
Output target voltage VCS_REF
reference for current
sense amplifier
1/4*
DVDD
1/2*
DVDD
(offset)-VREF
1.5
Output voltage
reference for current
sense amplifier
(offset) –VREF-
accuracy
VCS_REF_ACC
-1.5
%
Output short circuit
limit
ICS_SC
20
mA Pin CSOx shorted to ground
1.7
2
Normal mode
µs
Auto-Zero active time tAUTO_ZERO
Rdson sensing mode
100
200
If GHx is switching
µs
tAUTO_ZERO
Auto-Zero cycle time
_CYCLE
If GHx is not switching
AZ external Auto-
100
3.5
Zero signal
fAZ_CP_CLK_OFF
5
kHz
µs
frequency1)
AZ external Auto-
Zero signal pulse
width1)
tAZ_EXT_PW
0.1
Current Sense Amplifier Over-Current Protection Comparator and DAC
Current sense over-
current comparator
VCS_OC_HYST
5
mV
hysteresis
Over-current
comparator input
offset
-12
0
12
8
mV
µs
Over-current deglitch tCS_OCP_DEGLIT
time
Programmable via SPI
CH
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General Product Characteristics
Current Sense Input
referred OCP
threshold positive
VCS_OCP_THP
20
300
mV
Programmable via SPI
target level
Current sense input
referred OCP
threshold negative
target level
Over-current
VCS_OCP_THN
-300
0
-20
10
mV
µs
Programmable via SPI
Programmable via SPI:
tOCP_BLANK
blanking time
Gate Driver Analog to Digital Converter (ADC)
ADC resolution
ADC gain error
ADC_N
εGAIN
7
bits
%
-0.5
2
0.5
2
ADC offset error
ADC input clock
ADC conversion time
LSB
MHz
µs
εADC_OFFS_ERR
fADC_CLK
tCONV
12.5
1.28
Logic Level Digital Inputs (CE, EN_DRV)
Internal pull-down
resistor to GND CE
RPD_CE
350
2.7
625
500
850
kΩ
kΩ
VCE > 2V
Internal pull-down
resistor to GND
EN_DRV
RPD_EN_DRV
T
= -40 oC to 125 oC. This is the
A
minimum CE pin voltage above
which, any device (operated
within recommended conditions)
CE threshold voltage
rising
VCE_TH_R
V
V
will activate the device operation.
T
= -40 oC to 125 oC. This is the
A
maximum CE pin voltage below
which, any device (operated
within recommended conditions)
will stop the device operation.
CE threshold voltage
falling
VCE_TH_F
0.6
10
CE pin sink current
ICE_SNK
µA
V
Current flowing into CE pin
0.5*
DVD
D
EN_DRV threshold
voltage
VEN_DRV_TH
EN_DRV threshold
voltage hysteresis
VEN_DRV_TH_HY
S
4
%
Applies to VEN_DRV_TH thresholds
6EDL7141 OTP Programming
OTP programming
supply
PVDDOTP_PR
OG
Below this value an OTP blocking
will occur
13
V
OTP programming
temperature
Above this value an OTP blocking
will occur
TOTP_PROG
150
°C
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General Product Characteristics
Watchdog
Applies to buck converter input
selection only. Not configurable
value
Watchdog buck
tWD_BUCK
1.5
ms
converter input time
Overload Protections Gate Driver
PVDD UVLO threshold
VPVDD_UVLO_R
4.95
4.85
5.6
5.1
5.0
5.8
4.5
5.25
5.15
6.0
V
V
V
V
rising
PVDD UVLO threshold
falling
VPVDD_UVLO_F
VCCHS UVLO
threshold rising
VHS_UVLO_R
VCCHS UVLO
threshold falling
VHS_UVLO_F
4.3
4.7
VCCLS UVLO
VLS_UVLO_R
6.1
4.3
6.4
4.5
6.7
4.7
V
V
threshold rising
VCCLS UVLO
VLS_UVLO_F
threshold falling
Overload Protections Power Supply System
VDDB UVLO rising
threshold
VVDDB_UVLO_R
VVDDB_ UVLO_F
VVDDB_OVLO_R
4.2
4.1
105
4.3
4.2
108
4.4
4.3
111
V
VDDB UVLO falling
threshold
V
VDDB OVLO rising
threshold
%
Percentage of target output value
Percentage of target output value
VDDB OVLO falling
threshold
VVDDB_OVLO_F
102
105
108
%
A
1.0
1.3
50
fBUCK_SW = 500kHz
fBUCK_SW = 1MHz
Buck OCP (inductor
current) threshold
IBUCK_OCP_TH
Buck OCP hysteresis
IBUCK_OCP_HYS
VDVDD_UVLO_R
mA
%
DVDD UVLO rising
threshold
85
Percentage of target output value
Percentage of target output value
Percentage of target output value
DVDD UVLO falling
threshold
VDVDD_UVLO_F
VDVDD_OVLO_R
VDVDD_OVLO_F
IDVDD_I_LIM
75
%
DVDD OVLO rising
threshold
110
105
%
DVDD OVLO falling
threshold
%
DVDD target output
current limit
50
450
mA
Configurable via SPI
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Datasheet
General Product Characteristics
TJ=-40 oC to 125 oC, limit setting to
50mA
TJ=-40 oC to 125 oC, for other limit
settings
-30
-18
10
8
%
%
DVDD target output
current limit
accuracy
IDVDD_I_ACC
Gate Driver Over-Temperature Protection
Over-temperature
shut-down threshold
OTSTH
OTSHYS
OTWTH
150
10
oC
oC
oC
OTS Hysteresis
Over-temperature
warning threshold
125
Measured via internal ADC
Over-temperature
warning hysteresis
OTWHYS
10
oC
SPI Timing Requirements1)
Clock period
tCLK
77
20
20
10
ns
ns
ns
ns
Clock high time
Clock low time
tCLKH
tCLKL
tSET_SDI
SDI input data setup
time
SDI input data hold
time
tHD_SDI
10
0
ns
ns
SDO output data
delay time
tDLY_SDO
20
SCLK high to SDO valid
SDO rise and fall time tRF_SDO
10
50
50
ns
ns
ns
ns
ns
ns
nSCS enable time
nSCS disable time,
nSCS hold time
tEN_nSCS
tDIS_nSCS
tHD_nSCS
tSET_nSCS
tSEQ_nSCS
nSCS low to SDO transition
nSCS high to SDO high impedance
Falling SCLK to rising nSCS
50
nSCS setup time
50
Falling nSCS to rising SCLK
Rising nSCS to falling nSCS
nSCS sequential
delay time
450
1. Not subject to production test
2. For more details on XMC1404 power consumption, see XMC1400 datasheet. The consumption of XMC1404 is
dependent on the specific usage of the device
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Datasheet
General Product Characteristics
2.6.2
XMC1404 Electrical Characteristics
Table 12 provides the characteristics of the input/output pins of the XMC1404.
The parameters listed in this section represents partly the characteristics of the XMC1400 and partly its system
requirements. To aid interpreting the parameters easily when evaluating them for a design, they are indicated
by the abbreviations in the“Symbol” column:
•
CC: such parameters indicate Controller Characteristics, which are distinctive feature of the XMC1404 and
must be regarded for a system design.
•
SR: such parameters indicate System Requirements, which must be provided by the application system in
which the XMC1404 is designed in.
Note:
Note:
These parameters are not subject to production test, but verified by design and/or characterization.
Unless otherwise stated, input DC and AC characteristics, including peripheral timings, assume that
the input pads operate with the standard hysteresis.
Table 12
Input/Output Characteristics (Recommended Operating Conditions apply)
Parameter
Symbol
Limit Values
Min
Unit Test Conditions
Max.
Output low voltage
on port pins (with
standard pads)
VOLP CC
1.0
V
V
IOL = 11 mA
IOL = 5 mA
0.4
0.32
V
V
IOL = 10 mA
IOH = -10 mA
Output high voltage
on port pins (with
standard pads)
VOHP CC
DVDD – 1.0
–
DVDD-0.4
–
V
IOH = -4.5 mA
CMOS Mode
Input low voltage on VILPS SR
port pins (Standard
Hysteresis)
0.19 x DVDD V
Input high voltage on VIHPS SR
port pins (standard
hysteresis)
0.7 x DVDD
–
–
V
V
V
CMOS Mode
CMOS Mode
CMOS Mode
Input low voltage on VILPL SR
port pins (large
hysteresis)
0.08 xDVDD
Input high voltage on VIHPL SR
port pins (large
0.85 xDVDD
–
hysteresis)
Datasheet
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Datasheet
General Product Characteristics
Rise/fall time on
standard pad1)
tR, tF CC
HYS CC
–
12
ns
50 pF, DVDD = 5V 2)
Input hysteresis on
port pin except P2.3 -
P2.93)
0.08 xDVDD
–
V
V
CMOS mode standard hysteresis
CMOS mode, large hysteresis
0.5 xDVDD
0.75 xDVDD
Input hysteresis on
port pin P2.3 - P2.93)
HYS_P2
CC
0.08 xDVDD
–
V
V
CMOS mode standard hysteresis
CMOS mode, large hysteresis
0.35 xDVDD 0.75 xDVDD
Pin capacitance
(digital
inputs/outputs)
CIO
CC
CC
–
10
pF
µA
Pull-up current on
port pins
IPUP
–
-80
–
VIH,min
VIL,max
VIL,max
-95
–
Pull-down current on IPDP
port pins
CC
40
µA
95
-1
–
VIH,min
Input leakage current IOZP
except P0.114)
CC
1
µA
µA
V
0 < VIN < DVDD,
TA
105 oC
Input leakage current IOZP1 CC
for P0.114)
-10
–
1
0 < VIN < DVDD,
TA
105 oC
Voltage on any pin
during DVDD power
off
VPO
SR
0.3
Maximum current per IMP
pin (excluding P1,
SR
-10
-10
11
50
mA
mA
–
–
DVDD and VSS) 5)
Maximum current per IMP1A SR
high current pins
Maximum current
into VDDP
IMVDD SR
TBD
mA
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General Product Characteristics
Maximum current out IMVSS SR
of VSS
TBD
mA
1. Rise/Fall time parameters are taken with 10% - 90% of supply.
2. Additional rise/fall time valid for C = 50 pF - C = 100 pF @ 0.150 ns/pF at 5 V supply voltage.
L
L
3. Hysteresis is implemented to avoid meta stable states and switching due to internal ground bounce. It cannot
be guaranteed that it suppresses switching due to external system noise.
4. An additional error current (IINJ) will flow if an overload current flows through an adjacent pin.
5. However, for applications with strict low power-down current requirements, it is mandatory that no active
voltage source is supplied at any GPIO pin when VDDP is powered off.
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General Product Characteristics
2.7
Electrical Characteristic Graphs
Following graphs provide information on the behavior of the device at different conditions. This data is not
subject to production test. T
A
= 25°C, unless otherwise specified. All voltages are referred to ground (PGND for
buck converter, charge pumps and gate driver related parameters and DGND for the rest).
Note:
More details on XMC1404 consumption can be found in XMC1404 Datasheet
Figure 5
Current consumption on PVDD pin vs PVDD when both CE and EN_DRV are below active
thresholds.
Figure 6
Current consumption on PVDD vs PVDD voltage during STANDBY state - CE is above active
threshold and EN_DRV is below
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General Product Characteristics
Figure 7
Current Consumption on PVDD vs PVDD voltage during ACTIVE state – CE and EN_DRV are
above active threshold
Figure 8
VCCLS average voltage vs VCCLS load (DC) for different PVCC configurations at PVDD 18V. XMC
active and executing code. Typical application with CCP1(2) = 220nF and CVCCLS/HS = 1uF. VCCHS
load 20mA.
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General Product Characteristics
Figure 9
VCCLS average voltage vs VCCLS load (DC) for different PVCC configurations at PVDD 10V. XMC
active and executing code. Typical application with CCP1(2) = 220nF and CVCCLS/HS = 1uF. VCCHS
load 20mA.
Figure 10 VCCLS average voltage vs VCCLS load (DC) for different PVCC configurations at PVDD 5.5V. XMC
active and executing code. Typical application with CCP1(2) = 220nF and CVCCLS/HS = 1uF. VCCHS
load 20mA.
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General Product Characteristics
Figure 11 VCCHS average voltage vs VCCHS load (DC) for different PVCC configurations at PVDD 18V. XMC
active and executing code. Typical application with CCP1(2) = 220nF and CVCCLS/HS = 1uF. VCCLS
load 20mA.
Figure 12 VCCHS average voltage vs VCCHS load (DC) for different PVCC configurations at PVDD 10V. XMC
active and executing code. Typical application with CCP1(2) = 220nF and CVCCLS/HS = 1uF. VCCLS
load 20mA
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General Product Characteristics
Figure 13 VCCHS average voltage vs VCCHS load (DC) for different PVCC configurations at PVDD 5.5V.
XMC active and executing code. Typical application with CCP1(2) = 220nF and CVCCLS/HS = 1uF.
VCCLS load 20mA
Figure 14
DVDD 3.3V output voltage vs DVDD load for IMD700A
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General Product Characteristics
Figure 15
DVDD 5.0V output voltage vs DVDD load for IMD701A
Figure 16
Buck converter average output voltage (VDDB) vs PVDD voltage. Typical configuration,
with VDDB load 200mA and DVDD load of 50mA, buck converter switching frequency
500kHz, PVDD 18V.
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General Product Characteristics
Figure 17
Buck converter average output voltage (VDDB) vs VDDB load (IVDDB) for different PVCC
and buck switching frequency operations. Typical configuration with PVDD 18V.
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General Product Characteristics
2.8
XMC1404 Port I/O Alternate Functions Description
The method presented in Table 13 is used to describe the I/O functions of each PORT pin:
Table 13
Function
Port I/O Function Description
Outputs
Inputs
ALT1
ALTn
MODA.OUT
Input
MODC.INA
MODA.INA
Input
P0.0
Pn.y
MODA.OUT
MODC.INB
Figure 18
Simplified Port Structure of XMC Pins
Pn.y is the port pin name, defining the control and data bits/registers associated with it. As GPIO, the port is
under software control. Its input value is read via Pn_IN.y, Pn_OUT defines the output value.
Up to nine alternate output functions (ALT1 to ALT9) can be mapped to a single port pin, selected by
Pn_IOCR.PC. The output value is directly driven by the respective module, with the pin characteristics
controlled by the port registers (within the limits of the connected pad).
The port pin input can be connected to multiple peripherals. Most peripherals have an input multiplexer to
select between different possible input sources.
The input path is also active while the pin is configured as output. This allows to feedback an output to on-
chip resources without wasting an additional external pin.
Please refer to the Table 14 for the complete Port I/O function mapping.
Datasheet
16
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General Product Characteristics
2.8.1
XMC1404 Pin Definitions and Alternate Functions
In XMC1404 microcontroller, pins can be configured to perform different input and/or output functions. Each pin is connected internally to a de-multiplexer
that allows that particular pin to be routed to different peripherals in the microcontroller. Input and/or output configurations are possible on most pins.
Table 14 shows the different functions that are possible for XMC1404 pins in IMD70xA.
Table 14
Pin definitions and alternate functions for XMC1404
Functi Outputs
ons
Inputs
Input
Pin
ALT1
ALT2
ALT3
ALT4
ALT5
ALT6
ALT7
ALT8
ALT9
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
P0.0
ERU0.P LEDTS0.L ERU0.G CCU40. CCU80. USIC0_CH USIC0_C CCU81. USIC1_C BCCU0. CCU40.
USIC1_ USIC0_
CH1.DX CH0.DX
USIC0_
CH1.DX
2A
DOUT0
INE7
OUT0
OUT0
OUT00
0.SELO0
H1.SEL
O0
OUT00
H1.DOU TRAPIN IN0AC
T0
B
0A
2A
P0.1
P0.3
P0.4
P0.7
ERU0.P LEDTS0.L ERU0.G CCU40. CCU80. BCCU0.
DOUT1 INE6 OUT1 OUT1 OUT01 OUT8
SCU.VD USIC1_C USIC1_C
ROP H1.SCLK H1.DOU
OUT T0
ERU0.P LEDTS0.L ERU0.G CCU40. CCU80. VADC0.EM CCU80. USIC1_C USIC1_C
DOUT3 INE4 OUT3 OUT3 OUT03 UX01 OUT11 H1.SCLK H0.DOU
OUT T0
BCCU0. LEDTS0.L LEDTS0 CCU40. CCU80. VADC0.EM WWDT.E USIC1_C CAN.N0
CCU40.
IN1AC
USIC1_ USIC1_
CH1.DX CH1.DX
0B
1A
CCU40.
IN3AC
USIC1_
CH0.DX
0B
CCU41. CCU80
IN0AB IN0AB
CAN.N0
_RXDA
OUT0
INE3
.COL3
OUT1
OUT13
UX00SERVI _OUT
C
H1.SEL
O0
_TXD
BCCU0. LEDTS0.L LEDTS0 CCU40. CCU80. USIC0_CH USIC0_C VADC0.E CCU41.
OUT3 INE0 .COL0 OUT1 OUT10 0.SCLKOU H1.DOU MUX12O
T0 UT1
P0.10/ BCCU0. LEDTS1.L LEDTS0 ACMP0. CCU80. USIC0_CH USIC0_C CCU81.
CCU40. CCU41.
I N1AB I N3AB
USIC0_ USIC0_ USIC0_
CH0.DX CH1.DX CH1.DX
1C
USIC0_
CH0.DX
2C
T
0D
1C
CCU80. CCU81.I
IN2AB N2AB
USIC0_
CH1.DX
2C
XTAL1 OUT6
INE2
.COL5
OUT
OUT22
0.SELO1
H1.SEL
OUT22
O1
P0.11/ BCCU0. LEDTS1.L LEDTS0 USIC0_ CCU80. USIC0_CH USIC0_C CCU81.
USIC0_
CH0.DX
2D
USIC0_
CH1.DX
2D
XTAL2 OUT7
INE3
.COL4
CH0.MC OUT23
LKOUT
0.SELO2
H1.SEL
O2
OUT23
P0.12
P0.14
P0.15
BCCU0. LEDTS1.L LEDTS0 LEDTS1 CCU80. USIC0_CH CCU80.
OUT6 INE4 .COL3 .COL3 OUT33 0.SELO3 OUT20
CAN.N1 BCCU0. CCU40. CCU40. CCU40. CCU81.I CCU40.I CCU80.I USIC0_ CCU80.I CCU80.I CAN.N1 CCU80.I
_TXD
TRAPIN IN0AA IN1AA IN2AA N0AU
A
N3AA
N0AA
CH0.DX N1AA
2E
N2AA
_RXDA N3AA
BCCU0. LEDTS1.L LEDTS0 LEDTS1 CCU80. USIC0_CH USIC0_C
CAN.N0
_TXD
CCU81.I POSIF0. USIC0_ USIC0_ USIC1_
N2AU IN1B CH0.DX CH0.DX CH1.DX
0A 1A 5B
CCU81.I POSIF0. USIC0_
CAN.N0
_RXDC
OUT7
INE6
.COL1
.COL1
OUT31
0.DOUT0
H0.SCLK
OUT
BCCU0. LEDTS1.L LEDTS0 LEDTS1 CCU80. USIC0_CH USIC0_C
CAN.N0
_TXD
USIC1_ USIC1_ CAN.N0
CH1.DX CH1.DX _RXDD
OUT8
INE7
.COL0
.COL0
OUT30
0.DOUT0
H1.MCL
KOUT
N3AU
IN2B
CH0.DX
0B
3B
4B
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Datasheet
General Product Characteristics
Functi Outputs
ons
Inputs
Input
Pin
ALT1
ALT2
ALT3
ALT4
ALT5
ALT6
ALT7
ALT8
ALT9
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
P1.0
BCCU0. CCU40.O LEDTS0 LEDTS1 CCU80. ACMP1.OU USIC0_C CCU81. CAN.N0
POSIF0. USIC0_
CAN.N0
_RXDG
OUT0
UT0
.COL0
.COLA
OUT00
T
H0.DOU OUT00
T0
_TXD
IN2A
CH0.DX
0C
P1.1
P1.2
P1.3
P2.0
P2.1
P2.2
P2.3
P2.4
P2.5
P2.6
P2.7
P2.8
ERU1.P CCU40.O LEDTS0 LEDTS1 CCU80. USIC0_CH USIC0_C CCU81. CAN.N0
POSIF0. USIC0_ USIC0_
USIC0_ CAN.N0
CH1.DX _RXDH
2E
DOUT1
UT1
.COL1
.COL0
OUT01
0.DOUT0
H1.SEL
O0
OUT01
_TXD
IN1A
CH0.DX CH0.DX
0D 1D
ERU1.P CCU40.O LEDTS0 LEDTS1 CCU80. ACMP2.OU USIC0_C CCU81. CAN.N1
POSIF0.
IN0A
USIC0_
CH1.DX
0B
CAN.N1
_RXDG
DOUT2
UT2
.COL2
.COL1
OUT10
T
H1.DOU OUT10
T0
_TXD
ERU1.P CCU40.O LEDTS0 LEDTS1 CCU80. USIC0_CH USIC0_C CCU81. CAN.N1
DOUT3 UT3 .COL3 .COL2 OUT11 1.SCLKOU H1.DOU OUT11 _TXD
T0
ERU0.G LEDTS1 CCU80. USIC0_CH USIC0_C CCU81. CAN.N0
USIC0_ USIC0_ CAN.N1
CH1.DX CH1.DX _RXDH
T
0A
1A
ERU0.P CCU40.
DOUT3 OUT0
VADC0.
G0CH5
USIC0_ USIC0_
CH0.DX CH0.DX
USIC0_ CAN.N0 ERU0.0B
CH1.DX _RXDE
2F
OUT3
.COL5
OUT20
0.DOUT0
H0.SCLK OUT20
OUT
_TXD
0
0E
1E
ERU0.P CCU40.
DOUT2 OUT1
ERU0.G LEDTS1 CCU80. USIC0_CH USIC0_C CCU81. CAN.N0 ACMP2. VADC0.
USIC0_
CH0.DX
0F
USIC0_ USIC0_ USIC0_
CH0.DX CH0.DX CH1.DX
USIC0_ USIC0_ CAN.N0 ERU0.1B
CH1.DX CH1.DX _RXDF
3A 4A
OUT2
.COL6
OUT21
0.DOUT0
H1.SCLK OUT21
OUT
_TXD
I NP
G0CH6
0
ACMP2. VADC0.
I NN G0CH7
ORC0. USIC1_
ERU0.0B
1
AI N
CH0.DX
5E
3A
4A
5A
VADC0. ORC1. USIC1_ USIC1_ USIC1_ USIC0_ USIC0_ USIC0_
G1CH5 AI N CH0.DX CH0.DX CH1.DX CH0.DX CH1.DX CH1.DX
3E 4E 5C 5B 3C 4C
VADC0. ORC2. USIC1_ USIC1_ USIC0_ USIC0_ USIC1_ USIC0_
G1CH6 AI N CH1.DX CH1.DX CH0.DX CH0.DX CH0.DX CH1.DX
ERU0.1B
1
ERU0.0
A1
3C
4C
3B
4B
5F
5B
VADC0. ORC3. USIC1_
USIC0_
CH0.DX
5D
USIC0_ USIC0_
CH1.DX CH1.DX
ERU0.1
A1
G1CH7 AI N
CH1.DX
5D
3E
4E
ACMP1. VADC0.
ORC4. USIC1_ USIC1_ USIC0_ USIC0_ USIC0_
AI N CH1.DX CH1.DX CH0.DX CH0.DX CH1.DX
ERU0.2
A1
INN
G0CH0
3E
4E
3E
4E
5D
ACMP1.
INP
VADC0. ORC5. USIC1_
USIC0_
CH0.DX
5C
USIC0_ USIC0_ USIC0_
CH0.DX CH0.DX CH1.DX
USIC0_ USIC0_
CH1.DX CH1.DX
ERU0.3A
1
G1CH1 AIN
CH1.DX
5E
3D
4D
ACMP0. VADC0. VADC0. ORC6.
I NN G0CH1 G1CH0 AI N
ERU0.3B
1
3D
4D
5C
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Datasheet
General Product Characteristics
Functi Outputs
ons
Inputs
Input
Pin
ALT1
ALT2
ALT3
ALT4
ALT5
ALT6
ALT7
ALT8
ALT9
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
P2.9
ACMP0. VADC0. VADC0. ORC7.
USIC0_
CH0.DX
5A
USIC0_ USIC0_
CH1.DX CH1.DX
ERU0.3B
0
INP
G0CH2 G1CH4 AI N
3B
B
P2.10
P2.11
P2.12
P2.13
P3.0
P3.1
P3.2
P3.3
P3.4
P4.1
P4.2
P4.3
ERU0.P CCU40.O ERU0.G LEDTS1 CCU80. ACMP0.OU USIC0_C
CAN.N1
_TXD
VADC0. VADC0.
G0CH3 G1CH2
USIC0_ USIC0_ USIC0_
CH0.DX CH0.DX CH1.DX
CAN.N1 ERU0.2B
_RXDE
DOUT1
UT2
OUT1
.COL4
OUT30
T
H1.DOU
T0
0
3C
4C
0F
ERU0.P CCU40.O ERU0.G LEDTS1 CCU80. USIC0_CH USIC0_C
DOUT0 UT3 OUT0 .COL3 OUT31 1.SCLKOU H1.DOU
T0
ACMP2.OU USIC1_C LEDTS2.
CAN.N1 ACMP.R VADC0. VADC0.
_TXD
USIC0_ USIC0_ CAN.N1 ERU0.2B
CH1.DX CH1.DX _RXDF
0E 1E
EF
G0CH4 G1CH3
1
T
BCCU0. VADC0.E
OUT3 MUX00
USIC1_ USIC1_
CH0.SC CH1.SC
LKOUT LKOUT
ACMP3.
INN
USIC1_ USIC1_ USIC1_ USIC1_
CH0.DX CH0.DX CH1.DX CH1.DX
ERU1.3A
2
T
H1.DOU COL6
T0
3A
4A
0C
1B
BCCU0. CCU40.O USIC1_ CCU81.
VADC0.EM USIC1_C CCU81. CCU41. ACMP3.
USIC1_
CH0.DX
5A
USIC1_
CH1.DX
0D
ERU1.3A
3
OUT4
UT3
CH0.MC OUT31
LKOUT
UX01
H1.DOU OUT33
T0
OUT3
INP
BCCU0. USIC1_C USIC1_ LEDTS2 CCU80. ACMP1.OU USIC1_C CCU81. CCU41O BCCU0. CCU41. CCU41. CCU41. CCU41.I CCU81.I CCU81.I CCU81.I USIC1_ USIC1_ CCU81.I ERU1.0A
OUT0
H1.DOUT CH1.SC .COLA
LKOUT
OUT21
T
H0.SEL
O1
OUT21
UT0
TRAPIN IN0AA IN1AA IN2AA N3AA
C
N0AA
N1AA
N2AA
CH1.DX CH1DX N3AA
0E 1D
1
0
BCCU0. USIC1_C
LEDTS2 CCU80. ACMP3.OU USIC1_C CCU81. CCU41.
USIC1_ USIC1_
CH0.DX CH1.DX
ERU1.1A
1
OUT1
H1.DOUT
0
.COL0
OUT20
T
H0.SEL
O0
OUT20
OUT1
2F
0F
BCCU0. USIC1_C
LEDTS2 CCU80. ACMP2.OU USIC1_C CCU81. CCU41.
USIC1_ USIC1_ USIC1_ USIC1_
CH0.DX CH0.DX CH1.DX CH1.DX
ERU1.2A
1
OUT2
H1.SCLK
.COL1
OUT11
T
H0.SCLK OUT11
OUT2
OUT
OUT
3C
4C
3D
4D
BCCU0. USIC1_C
LEDTS2 CCU80. ACMP0.OU USIC1_C CCU81. CCU41.
USIC1_
CH0.DX
0E
USIC1_ USIC1_
CH0.DX CH0.DX
USIC1_
CH1.DX
2A
USIC1_
CH1.DX
2B
ERU1.1A
3
OUT5
H0.DOUT
0
.COL2
OUT10
T
H1.SEL
O0
OUT10
OUT3
BCCU0. USIC1_C USIC1_ LEDTS2 CCU80. USIC1_CH USIC1_C CCU81.
OUT6 H0.DOUT CH0.SC .COL3 OUT01 1.MCLKOU H1.SEL OUT01
LKOUT O1
LEDTS2 ERU1.G CCU40. ACMP3. USIC1_C CCU81. CCU41.
.COL4 OUT1 OUT1 OUT
ERU1.2A
3
0
T
0F
1E
BCCU0. ERU1.P
OUT8 DOUT1
CCU40. CCU41. CCU80.
IN1BA IN1AC I N1AU
POSIF1. USIC1_
H1.SEL
O2
OUT11
OUT1
IN0B
CH0.DX
5C
BCCU0. ERU1.PD CCU81. ERU1.G CCU40. ACMP2.OU USIC1_C CCU81. CCU41.
CCU40. CCU41. CCU80. CCU81.I POSIF1. USIC1_
IN2BA IN2AC IN2AU N1AB
OUT4
OUT2
OUT20 OUT2
OUT2
T
H1.SEL
O3
OUT12
OUT2
IN1B
CH0.DX
5D
BCCU0. ERU1.P
OUT5 DOUT3
CCU81. ERU1.G CCU40. ACMP0.OU USIC1_C CCU81. CCU41.
CCU40. CCU41. CCU80.
IN3BA IN3AC IN3AU
POSIF1.
IN2B
USIC1_
CH0.DX
1B
OUT21 OUT3
OUT3
T
H0.SCLK OUT13
OUT
OUT3
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Datasheet
General Product Characteristics
Functi Outputs
ons
Inputs
Input
Pin
ALT1
ALT2
ALT3
ALT4
ALT5
ALT6
ALT7
ALT8
ALT9
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
Input
P4.4
BCCU0. LEDTS2.L
OUT0 INE0
LEDTS1 CCU80. USIC1_CH
. COLA OUT00 0.DOUT0
CCU81. CCU41.
OUT00 OUT0
CCU41.
IN0AV
USIC1_
CH0.DX
0C
USIC1_
CH1.DX
5F
ERU1.0A
2
P4.5
P4.6
P4.7
P4.8
P4.10
BCCU0. LEDTS2.L
OUT8 INE1
LEDTS1 CCU80. USIC1_CH USIC1_C CCU81. CCU41.
CCU41.
IN1AV
USIC1_ USIC1_
CH0.DX CH0.DX
ERU1.1A
2
.COL6
OUT01
0.DOUT0
H0.SCLK OUT01
OUT
OUT1
0D
1C
BCCU0. LEDTS2
OUT2 .LINE2
CCU81. LEDTS1 CCU80.
OUT10 .COL5 OUT10
USIC1_C CCU81. CCU41.
CCU41.
IN2AV
CCU81.I
N0AB
USIC1_
CH0.DX
1D
USIC1_
CH0.DX
2A
USIC1_
CH0.DX
2B
USIC1_ USIC1_
CH0.DX CH1.DX
ERU1.2A
2
H0.SCLK OUT02
OUT2
OUT
BCCU0. LEDTS2
OUT5 .LINE3
CCU81. LEDTS1 CCU80.
OUT11 .COL4 OUT11
USIC1_C CCU81. CCU41.
CCU41.
IN3AV
ERU1.0A
3
H0.SEL
O0
OUT03
OUT3
BCCU0. LEDTS2.L LEDTS2 LEDTS1 CCU80. CCU40.OU USIC1_C CCU81. CAN.N1
CCU40. CCU41.
IN0AV IN0BA
CAN.N1
_RXDC
OUT7
INE4
.COL3
.COL3
OUT30
T0
H0.SEL
O1
OUT30
_TXD
LEDTS2.L LEDTS2 LEDTS1 CCU80. CCU40.OU USIC1_C CCU81. CCU81. BCCU0. CCU40. CCU41.
INE6
CCU81.I
N3AB
.COL1
.COL1
OUT00
T2
H0.SEL
O3
OUT32
OUT00
TRAPIN IN2AV IN2BA
D
2D
5A
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Datasheet
General Product Characteristics
2.8.2
Port Pins for Boot Modes
Port functions can be overruled by the boot mode selected. The type of boot mode is selected via BMI (Refer to
latest reference manual for the complete description at Infineon website: www.infineon.com. At the time of
creation of this document, latest version can be found here: XMC1400 Reference Manual). Table 15 shows the
port pins used for the various boot modes.
Table 15
XMC1404 Pin
P0.14
XMC1404 Port Pin for Boot Modes in IMD70xA
IMD70xA Pin
Boot
Boot Description
GPIO15_DBG0/P0.14
SWDIO_0
SPD_0
RX/TX
RX
Debug mode (SWD)
Debug mode (SPD)
ASC BSL half-duplex mode
ASC BSL full-duplex mode
CAN BSL mode
RX
P0.15
GPIO16_DBG1/P0.15
SWDCLK_0
TX
Debug mode (SWD)
ASC BSL full-duplex mode
CAN BSL mode
TX
P4.6
P4.7
GPIO2/P4.6
GPIO3/P4.7
HWCON0
HWCON1
Boot Pins (Boot from pins mode must be
selected)
2.9
XMC1404 Chip Identification Number
The Chip Identification Number in XMC1404 allows embedded software to identify the device and its features. It
is an 8 words value with the most significant 7 words stored in Flash configuration sector 0 (CS0) at address
location: 1000 0F00
H
(MSB) - 1000 0F1B (LSB). The least significant word and most significant word of the Chip
H
Identification Number are the value of registers DBGROMID and IDCHIP, respectively.
Table 16
Device Identification Number
XMC1404 DVDD
Derivative
Part
Number
Flash
Supply
Voltage
(V)
Value
Marking
Size
IMD700A - 128kB
Q064x128
3.3
2700100A 07FF00FF 1E071FF7 30BFF00F 00000D00
00001000 00021000 10204083H
AA
AA
IMD701A - 128kB
Q064x128
5.0
2701100A 07FF00FF 1E071FF7 30BFF00F 00000D00
00001000 00021000 10204083H
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Datasheet
Drives Optimized Microcontroller Features: XMC1404 Overview
3
Drives Optimized Microcontroller Features: XMC1404
Overview
IMD70xA integrates a fully programmable XMC1404 device. Following are the main features of this device:
ARM® Cortex-M0 32 bits microcontroller (XMC1404)
•
CPU Subsystem
o
o
o
o
o
o
o
o
o
32 bit ARM® Cortex-M0 (core clock 48MHz)
MATH Co-Processor (96MHz) for optimized 32 bit division and 24 bit trigonometric calculations
0.84 DMIPS/MHz (Dhrystone 2.1) at 48 MHz
Nested Vectored Interrupt Controller (NVIC) with 64 interrupt nodes
Internal slow and fast oscillators without the need of PLL
Real time clock module
Window watchdog
Up to 128kB of Flash (with ECC) and 16kB of RAM (with parity)
Internal oscillator
•
•
Serial Communication Modules
o
o
Four USIC channels, each of them configurable as UART, SPI, IIC and more
MultiCAN module (2 CAN nodes)
Analog Frontend Peripherals
o
12 bit A/D Converters (up to 12 analog inputs), 2 sample and hold stages up to 1.1MSamples/s
with adjustable gain
o
4 fast, general purpose analog comparators
•
Industrial Control Peripherals
o
o
2x4 16-bit 96 MHz CCU4 timers for signal monitoring and PWM
2x4 16-bit 96 MHz CCU8 timers for complex PWM, complementary high/low side switches and 3
phase inverter control
o
2x POSIF for Hall and quadrature encoders, motor positioning
•
•
On-Chip Debug Support
o
o
4 hardware breakpoints
ARM serial wire debug, single-pin debug interfaces
Programming Support
o
o
Single-pin bootloader
Secure bootstrap loader SBSL (optional)
Note:
Refer to XMC1400 Reference Manual for full description of the XMC1400 including register map and
descriptions. For latest version, refer to Infineon website (www.infineon.com )
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MOTIX™ 6EDL7141 Three Phase Integrated Smart Gate Driver
4
MOTIX™ 6EDL7141 Three Phase Integrated Smart Gate Driver
6EDL7141 main core block is comprised of a complete three phase gate driver optimized for motor control
applications. This gate driver is a floating driver capable of driving with configurable slew rate and driving
voltage, a 3 phase 2 level inverter with up to 1.5A of both sourcing and sinking peak currents.
Programmable charge pumps supply the gate drivers ensuring 100% duty cycle and configurable driving
voltage for maximum optimization of the gate driver.
Numerous protections are included to ensure safe operation of the gate driver system under stress conditions
including a best in class phase node (VSHx) tolerance to negative voltage spikes (see Absolute Maximum Ratings
table). This is of great importance for example during high side MOSFET turn off transition.
Configurations and settings are shared by all three half bridge drivers. This section describes the following
features of the integrated three phase gate driver:
•
•
•
•
•
•
PWM Modes
Gate Driver Architecture
Slew Rate Control
Gate Driver Voltage Programmability
Charge Pump Configurations
Gate Driver and Charge Pump Protections
4.1
PWM Modes
MOTIX™ 6EDL7141 implements additional intelligence that allows the user to simplify the PWM generation on
the XMC1404 side. That together with integrated protection features results in a highly robust and faster
development for drives applications. An intelligent dead time unit will ensure no shoot through happens at any
condition. A highly configurable braking mode provides safe reaction to motor or system events.
Following PWM modes can be selected via bitfield PWM_MODE:
1. 6PWM
2. 3PWM
3. 1PWM and commutation pattern
4. 1PWM with Hall sensor commutation
Note:
Note:
Given the interconnection between 6EDL7141 and XMC1404, PWM Mode ‘1PWM with Hall sensors
inputs’ as provided in standalone 6EDL7141 is not possible. However, XMC1404 can create a copy
of the Hall sensor inputs via firmware and benefit from some of the 6EDL7141 provided features
like dead time insertion or rotor locked detection if necessary. Possible delays or mismatches are
user (firmware) responsibility.
It is possible to use only one or two phases instead of the 3 phases, like for instance in a full bridge
configuration. In such case, it is recommended to keep INHx and INLx signals of the unused phases
shorted to DGND and the GHx, GLx, SHx and SLx signals open.
The PWM signals need to be generated in pins P1.0, P1.1, P3.0, P3.1, P3.2, P3.3 according to Figure 3, by
XMC1404 timer CCU8 which is a dedicated PWM timer for motor control. Thanks to the alternate functions, both
CCU80 and CCU81 are possible to be used providing further flexibility in terms of connectivity, as an example,
input signals for both units are different, so start, stop, load or other timer commands can be triggered by
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MOTIX™ 6EDL7141 Three Phase Integrated Smart Gate Driver
different sources depending on the unit selection. A CTRAP function (setting to passive all timer output) can be
connected via GPIOP14/P0.12 to input section of CCU80 timer as well as to other CCU4 timers.
Following subsections provide further details on each of the PWM modes and sub-modes.
4.1.1
PWM with 6 Independent Inputs – 6PWM
When the PWM_MODE register in 6EDL7141 is set to b'0 then the device is configured for 6 independent PWM
inputs. In this mode XMC1404 must provide 3 pairs of complementary PWM signals with dead time between
high side and low side PWM. A minimum dead time will be observed for safety reasons in the gate driver, in
order to avoid strong shoot through condition.
nBRAKE pin can be used for braking the motor in a controlled manner. See 4.1.6 for more information on
braking modes.
Table 17 shows the truth table for 6PWM mode while Figure 19 shows a system diagram for this mode.
Table 17
Truth table for 6PWM mode.
INHx
INLx
nBRAKE
GHx
GLx
SHx
1
1
0
0
X
1
0
1
0
X
1
1
1
1
0
LOW
LOW
High-Z
HIGH
HIGH
LOW
LOW
HIGH
LOW
LOW
LOW
High-Z
Brake cfg.
Brake cfg.
Brake cfg.
Note:
Note:
X means any level
Brake function can be configured to switch on all low side MOSFETs, all high side MOSFETs,
alternate between these two options or set all outputs to high Z
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MOTIX™ 6EDL7141 Three Phase Integrated Smart Gate Driver
Figure 19
6PWM mode scheme
4.1.2
PWM with 3 Independent Inputs – 3PWM
MOTIX™ 6EDL7141 can be configured to 3PWM mode by setting PWM_MODE bitfield to value b'001. In such
case, only 1 PWM signal (high side) per phase is necessary. The device will automatically generate the low side
signals according to Table 18 and will insert a configurable dead time. Dead time is independently
programmable for high to low (fall of phase node voltage) and low to high (rise of phase voltage) transitions
through bitfields DT_RISE and DT_FALL.
INLx signals are ignored in this mode.
nBRAKE pin can be used for braking the motor. See 4.1.6 for more information on braking modes.
Figure 20 depicts a system diagram for this PWM mode.
Table 18
Truth table for 3PWM mode.
INHx
INLx
nBRAKE
GHx
GLx
SHx
1
0
X
X
0
0
1
X
1
1
1
0
HIGH
LOW
HIGH
LOW
HIGH
LOW
LOW
LOW
High-Z
Brake cfg.
Brake cfg.
Brake cfg.
Note:
X means any level
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MOTIX™ 6EDL7141 Three Phase Integrated Smart Gate Driver
Note:
Brake function can be configured to switch on all low side MOSFETs, all high side MOSFETs,
alternate between these two options or set all outputs to high Z
Figure 20
3PWM mode scheme
4.1.3
PWM with 1 Input and Commutation Pattern – 1PWM
When the PWM_MODE register is set to b'010 then the PWM section in 6EDL7141 is configured to 1PWM mode.
In this case, the duty cycle and frequency of signal INHA is used to determine the duty cycle (or amplitude) and
the frequency of the PWM outputs generated. The rest of inputs are captured to decide the commutation
pattern or state of the outputs. INHC signal can be used to implement 12 step trapezoidal commutation. Dead
time is automatically inserted according to programmed values in bitfields DT_RISE and DT_FALL.
Figure 21 shows a schematic diagram of 1PWM mode.
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Datasheet
MOTIX™ 6EDL7141 Three Phase Integrated Smart Gate Driver
Figure 21
1PWM mode scheme
Additionally, the user has the option to select between two main commutation schemes programmable via
register bitfield PWM_FREEW_CFG:
•
Diode freewheeling – bitfield PWM_FREEW_CFG =b’1: in this case, the freewheeling current will flow through
the low side MOSFETs body diodes. The truth table for this mode is shown in Table 19.
•
Active freewheeling – bitfield PWM_FREEW_CFG =b’0: in this case the low side MOSFETs will be switched
synchronously to reduce conduction losses on the body diode conduction. The truth table for this mode is
shown in Table 20.Note:
12 Step Trapezoidal Commutation
Input INHC can be optionally used to create a 12 step trapezoidal or block commutation. This method energizes
up to two phases at the same time in contrast to 6 step, where only one is active at any time. In 12 step
trapezoidal commutation, torque ripple is improved and the angle created between stator and rotor flux
vectors can be controlled within 30 degree accuracy instead of 60degree in 6 step trapezoidal commutation.
This method improves motor efficiency and torque ripple, however requires additional position information.
This information can be processed by a the integrated XMC1404 to produce signals INHA, INLA, INHB, INLB and
INHC according to Table 19 or Table 20. As can be seen, from a system perspective, the INHC signal must toggle
at every 30degree rotation (electrical).
In case the INHC signal is not toggled, the device will apply the commutation as shown in to Table 19 or Table
20. As an example, if INHC is left low, a classic 6 step trapezoidal commutation pattern will be produced. In case
INHC is pulled high, the pattern will show a 30 degree advanced with respect to a standard 6 step trapezoidal
commutation. The user can use this variants or toggle the INHC pin every 30 degree of rotation to create a 12
step commutation pattern.
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nBRAKE pin can be used for braking the motor. See 4.1.6 for more information on braking modes.
Here is a summary of inputs and output functionalities:
•
•
•
•
•
•
INHA - PWM input, defines PWM output duty cycle and frequency
INLA, INHB, INLB - Provide timing for modulation pattern changes
INHC – Signalizes 12 step states. Must toggle every electrical 30degree
INLC – This input is ignored in this mode. Recommended pull down.
nBRAKE signal – When active, will force the motor to brake.
GHA, GLB, GHB, GLB, GHC, GLC – Complementary PWM Output signals
Table 19 shows the possible states for this PWM mode using diode freewheeling while Table 20 shows the
states in case of active freewheeling.
Table 19
Truth table for 1PWM mode with diode freewheeling.
INPTUS
OUTPUTS
SHB
INLA,
State INHB,
INLB,
nBRAKE GHA
GLA
GHB
GLB
GHC
GLC
SHA
SHC
INHC
AB
AB_CB
CB
011
010
010
110
110
100
100
101
101
001
001
011
111
000
0
1
0
1
0
1
0
1
0
1
0
1
X
X
1
1
1
1
1
1
1
1
1
1
1
1
1
1
PWM
PWM
LOW
LOW
LOW
LOW
LOW
LOW
LOW
PWM
PWM
PWM
PWM
LOW
LOW
LOW
LOW
HIGH
HIGH
HIGH
HIGH
HIGH
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
PWM
PWM
PWM
PWM
PWM
LOW
LOW
LOW
LOW
HIGH
HIGH
HIGH
HIGH
LOW
LOW
LOW
LOW
LOW
LOW
LOW
HIGH
HIGH
LOW
LOW
PWM
PWM
PWM
PWM
PWM
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
HIGH
HIGH
HIGH
HIGH
HIGH
HIGH
LOW
HIGH
HIGH
-
LOW
LOW
LOW
LOW
-
-
HIGH
HIGH
HIGH
HIGH
HIGH
-
CB_CA
CA
LOW
LOW
LOW
LOW
LOW
-
CA_BA
BA
HIGH
HIGH
HIGH
HIGH
HIGH
-
BA_BC
BC
LOW
LOW
LOW
LOW
LOW
LOW
-
BC_AC
AC
HIGH
HIGH
HIGH
HIGH
-
AC_AB
Align
Stop
LOW
LOW
-
Brake Brake Brake Brake Brake
cfg. cfg. cfg. cfg. cfg.
Brake Brake Brake Brake
cfg. cfg. cfg. cfg.
X
Brake
XXX
0
Note:
Note:
X means any level
SHx when HIGH means that SHx pin is switching between GND and the DC bus voltage or battery
voltage according to PWM signals. ‘-‘ represents floating state, meaning both high side and low side
MOSFETs are OFF
Note:
Brake function can be configured to switch on all low side MOSFETs, all high side MOSFETs,
alternate between these two options or set all outputs to high Z
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Table 20
Truth table for 1PWM mode with active freewheeling.
INPTUS
INLA,
OUTPUTS
State INHB,
INLB,
nBRAKE GHA
GLA
GHB
GLB
GHC
GLC
SHA
SHB
SHC
INHC
AB
AB_CB
CB
011
010
010
110
110
100
100
101
101
001
001
011
111
000
0
1
0
1
0
1
0
1
0
1
0
1
X
X
1
1
1
1
1
1
1
1
1
1
1
1
1
1
PWM
PWM
LOW
LOW
LOW
LOW
LOW
LOW
LOW
PWM
PWM
PWM
PWM
LOW
!PWM
!PWM
LOW
LOW
LOW
LOW
LOW
LOW
PWM
PWM
PWM
PWM
PWM
LOW
LOW
LOW
LOW
HIGH
HIGH
HIGH
HIGH
LOW
LOW
PWM
PWM
PWM
PWM
PWM
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
HIGH
HIGH
-
LOW
LOW
LOW
LOW
-
-
!PWM
!PWM
!PWM
!PWM
!PWM
LOW
HIGH
HIGH
HIGH
HIGH
HIGH
-
CB_CA
CA
HIGH
HIGH
HIGH
HIGH
HIGH
LOW
LOW
LOW
LOW
LOW
LOW
-
CA_BA
BA
!PWM
!PWM
!PWM
!PWM
!PWM
LOW
HIGH
HIGH
HIGH
HIGH
HIGH
-
BA_BC
BC
HIGH
HIGH
HIGH
HIGH
HIGH
HIGH
LOW
LOW
LOW
LOW
LOW
LOW
LOW
-
BC_AC
AC
!PWM
!PWM
!PWM
!PWM
LOW
HIGH
HIGH
HIGH
HIGH
-
AC_AB
Align
Stop
HIGH
HIGH
LOW
LOW
LOW
-
Brake Brake Brake Brake Brake Brake Brake Brake Brake
cfg. cfg cfg cfg. cfg. cfg. cfg. cfg. cfg.
Brake
XXX
0
X
Note:
Note:
X means any level
SHx when HIGH means that SHx pin is switching between GND and the DC bus voltage or battery
voltage. ‘-‘ is floating state, meaning both high side and low side MOSFETs are OFF.
Note:
Brake function can be configured to switch on all low side MOSFETs, all high side MOSFETs,
alternate between these two options or set all outputs to high Z.
4.1.4
PWM with 1 Input and Commutation with Hall Sensor Inputs – 1PWM with
Hall Sensors
MOTIX™ 6EDL7141 integrates three Hall sensor comparators to detect pattern of movement in the motor. This
can be used for rotor locked detection but can also be utilized to drive the PWM commutation pattern
automatically. In order to use this mode, user could use Hall sensor inputs connected to XMC1404 and replicate
those signals, e.g. via GPIO handling in firmware, into 6EDL7141 inputs. This will enable usage of 6EDL7141
logic for PWM pattern generation as well as locked rotor detection.
To enable this PWM_MODE bitfield needs to be configured to value b'011.The truth table presented in Table 21
dictates the commutation pattern. In this mode, Hall sensor inputs decide the switching pattern of the PWM
output signals. The duty cycle and frequency of the output signals is determined by INHA duty cycle and
frequency.
Dead time is inserted automatically according to programmed values in DT_RISE and DT_HALL.
In a similar way as in other PWM modes, the user has the option to select between two main commutation
schemes programmable via bitfield PWM_FREEW_CFG in PWM_CFG register: diode and active freewheeling. No
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truth table is shown for diode mode. This can be constructed by substituting “!PWM” cells in Table 21 by
“LOW”.
Similarly to other PWM modes, nBRAKE pin can be used for braking the motor. See 4.1.6 for more information
on braking modes.
Figure 22
1PWM mode with hall sensors. Self-controlled pattern switching
Table 21
INPUTS
Truth table for 1 PWM mode with active freewheeling.
OUTPUTS
INLx
[A,B,C] Dir
INHC-
nBRAKE
GHA
GLA
GHB
GLB
GHC
GLC
SHA
SHB
SHC
101
100
110
010
011
001
101
100
110
010
1
1
1
1
1
1
0
0
0
0
1
1
1
1
1
1
1
1
1
1
PWM
LOW
LOW
LOW
LOW
PWM
LOW
LOW
PWM
PWM
!PWM LOW
LOW PWM
LOW
LOW
HIGH HIGH
-
LOW
!PWM LOW
!PWM LOW
HIGH
LOW
-
HIGH LOW
HIGH PWM
HIGH LOW
LOW
HIGH
-
-
LOW
PWM
!PWM LOW
HIGH
HIGH
-
LOW
LOW
HIGH PWM
HIGH LOW
!PWM
LOW
-
LOW
!PWM LOW
HIGH LOW
HIGH LOW
LOW
PWM
!PWM LOW
-
HIGH
HIGH
-
LOW
LOW
HIGH PWM
HIGH LOW
!PWM
LOW
-
LOW
!PWM LOW
!PWM LOW
HIGH LOW
LOW
LOW
HIGH HIGH
-
LOW
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INPUTS
INLx
OUTPUTS
INHC-
nBRAKE
GHA
GLA
LOW
GHB
GLB
GHC
GLC
SHA
SHB
SHC
[A,B,C] Dir
011
001
0
0
1
1
LOW
LOW
PWM
!PWM LOW
!PWM LOW
HIGH
LOW
-
HIGH LOW
HIGH
HIGH PWM
LOW
-
Brake Brake Brake Brake Brake Brake Brake Brake Brake
XXX
X
0
cfg.
cfg.
cfg.
cfg.
cfg.
cfg.
cfg.
cfg.
cfg.
111
000
X
X
1
1
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
-
-
-
-
-
-
Note:
Note:
Note:
X means any level. XXX means any other combination on inputs not shown
Grey cells represent forbidden states and should be avoided
SHx when HIGH means that SHx pin is switching between GND and the DC bus voltage or battery
voltage. ‘-‘ represents floating state, meaning both high side and low side MOSFETs are OFF
Note:
Note:
For diode freewheeling mode, substitute “!PWM” cells by “LOW”
Brake function can be configured to switch on all low side MOSFETs, all high side MOSFETs,
alternate between these two options or set all outputs to high Z
These are the signals functionality for this mode:
•
•
INHA - PWM input, defines duty cycle and frequency of PWM output signals
INLA, INLB, INLC - Hall Sensor Inputs (HA, HB, HC) will define the PWM output pattern depending on motor
position.
•
•
•
nBRAKE signal – when active, the device will force a brake event.
INHC - Direction control. Provided by a microcontroller, will define direction of motor rotation.
GHA, GLA, GHB, GLB, GHC, GLC – PWM output signals, high side and low sides.
A schematic representation of the commutation states is presented in Figure 23.
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Figure 23
6 states switching overview. Diode freewheeling mode is represented here for
simplification. Single direction considered.
4.1.5
PWM with 1 Input and Commutation with Hall Sensor Inputs and
Alternating Recirculation – 1PWM with Hall Sensors and Alternating
Recirculation
Thermal management in power tools systems is a key factor for achieving higher power densities. A more
advance thermal management might allow smaller heat sink components or smaller PCB area. This PWM mode
focuses on distributing the MOSFET stress more evenly between all MOSFETs in the inverter. This concept
alternates the recirculation of the freewheeling current between high side and low side MOSFETs. This is
achieved by extending the truth table shown in Table 21 into Table 22.
On the first rotation (electrical), the inverter will recirculate the current through the high side MOSFETS (PWM
modulated MOSFET) and the low side MOSFET will be always ON. In the second electrical rotation, the low side
MOSFETs will recirculate the freewheeling current (PWM modulated MOSFET), and therefore, the high side is
the one fully ON. This cycle repeats in further rotations. A graphical representation for the switching states is
presented in Figure 24. In this figure, states A to F represent high side modulation while states G to L represent
the low side modulation. The state machine will return to state A after state L, starting over again the cycle.
PWM_FREEW_CFG configures this mode as well either as diode or active freewheeling. No truth table is shown
for diode mode. This can be constructed by substituting “!PWM” cells with LOW in Table 22.
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Table 22
INPUTS
Truth table for 1 PWM mode with active freewheeling and alternating recirculation
OUTPUTS
INLx
[A,B,C]
nBRAKE Fully ON GHA
GLA
GHB
GLB
GHC
GLC
SHA
SHB
SHC
INHC (Dir)=1
101
1
1
1
1
1
1
1
1
1
1
1
1
Low side PWM
Low side LOW
Low side LOW
Low side LOW
Low side LOW
Low side PWM
High side HIGH
High side LOW
High side !PWM
High side !PWM
High side LOW
High side HIGH
!PWM
LOW
HIGH
HIGH
LOW
!PWM
LOW
LOW
PWM
PWM
LOW
LOW
LOW
PWM
PWM
LOW
LOW
LOW
LOW
HIGH
HIGH
LOW
!PWM
!PWM
LOW
!PWM
!PWM
LOW
HIGH
HIGH
LOW
LOW
LOW
LOW
PWM
PWM
LOW
LOW
LOW
PWM
PWM
LOW
!PWM
!PWM
LOW
HIGH
HIGH
LOW
HIGH
HIGH
LOW
!PWM
!PWM
LOW
PWM
PWM
LOW
LOW
LOW
LOW
HIGH
-
-
LOW
LOW
-
100
HIGH
HIGH
-
110
LOW
LOW
-
010
HIGH
HIGH
-
011
LOW
LOW
-
001
HIGH
HIGH
-
101
LOW
LOW
-
100
HIGH
HIGH
-
110
LOW
LOW
-
010
HIGH
HIGH
-
011
LOW
LOW
001
HIGH
INHC (Dir)=0
101
1
1
1
1
1
1
1
1
1
1
1
1
Low side LOW
Low side LOW
Low side PWM
Low side PWM
Low side LOW
Low side LOW
High side !PWM
High side LOW
High side HIGH
High side HIGH
High side LOW
High side !PWM
HIGH
LOW
!PWM
!PWM
LOW
HIGH
PWM
LOW
LOW
LOW
LOW
PWM
LOW
LOW
LOW
LOW
PWM
PWM
LOW
!PWM
!PWM
LOW
HIGH
HIGH
LOW
HIGH
HIGH
LOW
!PWM
!PWM
LOW
PWM
PWM
LOW
LOW
LOW
PWM
PWM
LOW
LOW
LOW
LOW
HIGH
HIGH
LOW
!PWM
!PWM
LOW
!PWM
!PWM
LOW
HIGH
HIGH
LOW
LOW
LOW
LOW
PWM
PWM
LOW
LOW
-
-
HIGH
HIGH
-
100
LOW
LOW
-
110
HIGH
HIGH
-
010
LOW
LOW
-
011
HIGH
HIGH
-
001
LOW
LOW
-
101
HIGH
HIGH
-
100
LOW
LOW
-
110
HIGH
HIGH
-
010
LOW
LOW
-
011
001
HIGH
HIGH
LOW
Brake
cfg.
Brake
cfg.
Brake
cfg.
Brake
cfg.
Brake
cfg.
Brake
cfg.
Brake
cfg.
Brake
cfg.
Brake
cfg.
XXX
0
X
111
000
1
1
1
1
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
LOW
-
-
-
-
-
-
Note:
X means any level. Grey cells represent forbidden states and should be avoided
Note:
SHx when HIGH means that SHx pin is switching between GND and the DC bus voltage or battery
voltage. ‘-‘ represents floating state, meaning both high side and low side MOSFETs are OFF
Note:
For diode freewheeling mode, substitute “!PWM” cells by “LOW”
Note:
Brake function can be configured to switch on all low side MOSFETs, all high side MOSFETs,
alternate between these two options or set all outputs to high Z
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Figure 24
12 states switching overview for alternating recirculation. 6 new states are included (G to
L) compared to other 1PWM modes. Diode clamping is represented here for simplification.
Single direction considered
4.1.6
PWM Braking Modes
In all PWM modes presented in section 4.1, the device can go into a controlled braking mode. This braking
mode will drive PWM signals in a way that the motor goes to a safe state in a controlled manner. This is of
critical importance for some power tools applications where a sudden or uncontrolled braking can destroy
elements of the tool or become a hazard to the user safety. Following events can trigger the braking action:
•
Pull down of pin nBRAKE
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•
•
Overcurrent protection (OCP) fault on current sense amplifiers -programmable
Watchdog timer fault-programmable
From them, pin nBRAKE is the only that can be actively used by, for example an additional microcontroller to
start a braking event. All other 3 are the reaction to a fault-detection.
Pin nBRAKE shall be high for normal operation of the motor. However, as soon as low level is detected in it, the
gate driver logic will activate high side MOSFETs or low side MOSFETs therefore braking the motor actively.
Braking circuitry can be configured as illustrated in Figure 25 in the following modes by programming bitfield
BRAKE_CFG in register PWM_CFG:
•
•
•
Low side MOSFET braking: upon a braking event, all low side MOSFET will be activated and all high side
MOSFET switched off.
High side MOSFET braking: upon a braking event, all high side MOSFET will be activated and all low side
MOSFET switched off
Alternate braking mode: upon every new braking event, the system alternates between high side MOSFET
braking and low side MOSFET braking. With alternate braking, stress on MOSFETs is distributed equally,
therefore improving system robustness.
•
Non-power braking-high impedance (high Z) outputs: upon a braking event all switches are forced to high Z
mode. Currents present in motor windings will recirculate through MOSFET body diodes or other available
structures in the inverter. This mode is recommended if a MOSFET short occurs in the inverter.
In IMD70xA, XMC1404 can modify brake related bitfields during run time of the system to adapt to given
conditions.
Figure 25
System overview for the different braking modes supported
Before the braking action starts, the gate driver prepares the inverter as fast as possible for a safe braking.
Depending on the inverter state at the moment of the braking request, the device will need to switch off some
MOSFETs and insert dead times. For example, if the braking signal arrives when phase A is, high side switched-
off and low side switched-on, and assuming a high side braking configuration, then will immediately switch off
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the low side MOSFET, insert the configured dead time and finally switch on the high side MOSFET of phase A
with the rest of high side MOSFETs.
4.1.6.1
Double nBRAKE Path
During normal operation (after UVLO DVDD), the pin nBRAKE is an input (inverted logic) that can be pulled down
to initiate a brake event, bringing the motor to a standstill in a controlled way. If the pin is set high, the PWM will
resume and propagate normally the PWM inputs to the outputs. There are two sources for activating the brake
events in IMD70xA:
•
•
XMC1404 internal connection (P1.3--> nBRAKE): integrated XMC1404 can toggle the GPIO to activate or
deactivate the braking action.
IMD70xA pin 24 (nBRAKE): an external source like another controller or some logic, can trigger in parallel the
braking event.
This is done to support increased flexibility in the braking scheme. Internally, both sources are electrically
connected. A possible system diagram making use of the double braking path is shown Figure 26.
Figure 26
nBRAKE double path pin usage example: internal via XMC1404 controller P1.3 pin, and
external via pin nBRAKE
4.1.7
Dead Time Insertion
The PWM unit in 6EDL7141 inserts automatically a dead time between complementary signals (GHx –GLx).
DT_RISE bitfield defines the dead time period for rising transition (of phase node voltage) while DT_FALL
defines independently the period for the falling transition. A minimum dead time (see Electrical Characteristics
table for detailed values and conditions) will always be observed to avoid strong shoot through condition.
Figure 27 shows a detailed signal diagram of a 1PWM mode dead time insertion including the timing definitions.
A propagation time (tPROP_HS and tPROP_LS) elapses between the input signal and the actual gate driver output
signals. These timing definitions are applicable to all other PWM modes.
Dead time and slew rate control features are designed in a safe way so that a change in slew rate will update in
a synchronous manner to the PWM switching. This hinders any possible shoot through during the possible
update of the slew rate during operation due to miss-alignment of timings.
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Note:
The application software, must ensure that dead time is sufficient for the slew rate configuration
and the MOSFETs selection. Current sense amplifier OCP can be used to detect excessive current in
the system.
Figure 27
PWM insertion ideal timing diagram for 1PWM mode.
4.2
Gate Driver Architecture
Three identical pairs of high side and low side drivers are integrated. High and low side drivers are designed
with the same architecture. However, supply domains for both sections are developed differently. Precise
charge pumps are utilized to supply both drivers, VCCLS to the low side gate drivers, and VCCHS to the high side
gate drivers. An overview of the general architecture is shown in Figure 28.
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Figure 28
Gate driver architecture overview
The low side section of the gate driver is supplied by VCCLS. When the device is under normal operation, VCCLS
is “PVCC” volts above ground. VCCLS voltage is generated by “LS Charge Pump” from VDDB voltage –integrated
buck converter output voltage. An external “flying” capacitor CCP1 is required for the charge pump to work
properly.
The high side section of the gate driver is supplied by VCCHS. A separated charge pump generates “PVCC” volts
above PVDD for properly bias of the high side MOSFET drivers. Similarly to low side section, a “flying” capacitor
CCP2 is necessary for proper operation of the charge pump. PVCC voltage is programmable via SPI registers and
defines the gate driving voltage of the inverter power MOSFETs.
Additional decoupling capacitors CVCCLS and CVCCHS are required for VCCLS and VCCHS pins respectively. These
and other required components recommended values are shown in Table 30.
The selection of those capacitors will have an impact i different parameters in the charge pump including the
voltage ripple in VCCLS/HS, as well as the start-up time or the maximum load that the gate driver can sustain.
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4.3
Slew Rate Control
Control of MOSFET VDS rise and fall times is one of the most important parameters for optimizing drive systems,
affecting critical factors like:
•
•
•
Switching losses,
Dead time optimization,
VDS ringing with possible avalanche event in MOSFETs. Avalanche is a critical factor in MOSFETs that can lead
to device destruction or reliability issues,
•
•
•
EMI design and optimizations,
Control of negative spike in SHx pins,
Possible snubber design (MOSFET snubber or bridge bypass capacitors)
MOTIX™ 6EDL7141 is capable of adjusting the slew rate of the MOSFET switching (VDS). Slew rate control
functionality controls independently the rise (low to high) and fall (high to low) slew rates of the drain-to-
source voltage by adjusting the gate current applied to MOSFET gate.
Note:
Rg resistors might be used, however, user must consider the voltage drop on the resistor when
driving the MOSFET with the constant current provided by 6ELD7141
4.3.1
Slew Rate Control Parameters and Usage
User can configure the gate driver current and timings with following parameters via SPI accessible registers:
•
•
•
•
•
IHS_SRC – bitfield IHS_SRC: gate driver current value for switching ON high side MOSFETs
IHS_SINK – bitfield IHS_SINK: gate driver current value for switching OFF high side MOSFETs
ILS_SRC – bitfield ILS_SRC: gate driver current value for switching ON low side MOSFETs
ILS_SINK – bitfield ILS_SINK: gate driver current value for switching OFF low side MOSFETs
IPRE_SRC – bitfield IPRE_SRC: pre-charge gate driver current value for switching ON both high and low side
MOSFETs. Needs to be enabled via bitfield IPRE_EN, otherwise pre-charge will be set to max current.
•
•
•
•
•
IPRE_SNK – bitfield IPRE_SNK: pre-discharge gate driver current value for switching OFF both high and low
side MOSFETs. Needs to be enabled via bitfield IPRE_EN, otherwise pre-discharge will be set to max current.
TDRIVE1 – bitfield TDRIVE1: amount of time that IPRE_SRC is applied. Shared configuration between high and low
side drivers
TDRIVE2 – bitfield TDRIVE2: amount of time that IHS_SRC and ILS_SRC are applied. Shared configuration between high
and low side drivers
TDRIVE3 – bitfield TDRIVE3: amount of time that IPRE_SNK is applied. Shared configuration between high and low
side drivers
TDRIVE4 – bitfield TDRIVE4: amount of time that IHS_SINK and ILS_SINK are applied. Shared configuration between
high side and low side drivers
The driving implementation is presented in Figure 29. This represents a 6PWM mode in which the XMC1404
inserts a specific dead time between INHx and INLx signals. The driving scheme is applicable to other PWM
modes. Propagation delays are not depicted for simplification of the diagram (see Figure 27 for details on
propagation delay).
Once the gate is commanded to apply a change to the output, the gate driver will apply a constant current
defined by the user programmable value IPRE_SRC for a time defined by TDRIVE1. After TDRIVE1 period, the MOSFET gate
voltage should ideally have reached the threshold voltage (VGS(th)). After TDRIVE1, the gate driver applies next gate
current configuration for a period defined by TDRIVE2. The current applied in this period is decisive to determine
both dI/dt and dV/dt of the MOSFETs as it will charge the Qsw of the MOSFETs. User can alternatively decide to
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reduce this period to cover only Qgd portion, therefore controlling dI/dt region with the TDRIVE1 period for
independent control. To ensure proper fine tuning, 6EDL7141 offers separate configuration registers for the
high side and low side (IHS_SRC and ILS_SRC respectively).
Once TDRIVE2 period is elapsed, the gate driver applies full current (1.5A) to ensure fastest turn on of the MOSFET.
This will fully charge the MOSFET gate (Qod = Qg – Qsw – Qg(th))) till the programmed PVCC value.
A similar process takes place in the discharge of the MOSFET
Attention:
Consider that slew rate variation affects the actual dead time value. User must select dead
time accordingly
VGS Comparators
MOTIX™ 6EDL7141 integrates gate to source comparators. These are used to detect when the Vgs signal is
almost at the target value PVCC, i.e. VGSX ≥ PVCC - VGS_CPM_TH during charging phase and VGSX ≤ VGS_CPM_TH during the
discharge phase. When any of these happen, the comparator trips and sets the gate current to IHOLD value. This
is to reduce power consumption and help reducing the possible impact of the self-turn-on effect, for example
when the high side MOSFET is turning on while the low side MOSFET is off. In this case, the hold current in the
low side MOSFET will help tightening down the gate of that MOSFET to the source with IHOLD strength. In Figure
29 IHOLD is shown as dashed and depending on VGS value will be applied sooner or later. In Figure 30 the
thresholds for activating IHOLD current are shown.
The comparator integrates a deglitching stage that avoids noise to activate the comparator erroneously during
noisy events. The deglitching time is defined by tVGS_CMP_DEGLITCH
.
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Figure 29
Slew rate control timing for a complete switching cycle on a 6PWM mode-dead time
assumed to be inserted by XMC1404. Propagation delays (INxy→Gxy) not considered for
simplification. Parameters on red refer to programmable values
Figure 30 shows a detail of the charging and discharging transitions for a high side MOSFET. Similar applies to a
low side MOSFET. The different gate charge areas of the MOSFET are shown. Thanks to the flexible timing
structure and the high TDRIVEX resolution, user has full control of the gate current applied during critical charge
areas like Qsw which is the key parameter controlling the MOSFET Vds slew rate. This at the same time can be
done while maintaining fast charging of other areas like Qod which typically is relatively large compared to Qsw
and therefore, as it does not affect neither dV/dt nor dI/dt, can be accelerated by increasing gate current.
Additionally, the pre-charge area (Qgs(th)), depending on the particular MOSFET, can benefit from a larger gate
current than the one applied to the Qsw region where maximum control is required. Thanks to the pre-charge
current configuration, higher gate currents can be selected for Qgs(th) reducing importantly the pre-charge
timing, which otherwise could have needed several hundreds of ns to reach to Vgs(th)
.
The pre-charge current can be selected from 17 different values. 16 defined by IPRE_SRC/SNK and additionally 1.5A,
which is the maximum peak current capability of the gate driver. In case of large MOSFETs, Qgs(th) during turn on
or Qod (Qod = Qg – Qsw-Qgs(th)) during turn off, might benefit from using the whole gate driver capability. In order to
enable the full strength during the pre-charge area, register I_PRE _EN has to be set in register
IDRIVE_PRE_CFG.
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Note:
Note:
When transitioning from one current setting to another, user can experience some transition
period until new current value is up and stable. During this period, the current might become
lower than programmed for a brief period before reaching the target value.
When the gate to source voltage is getting close to the target voltage, either PVCC when charging
or PGND when discharging, the gate driver will not be able to fully maintain the target IG current.
This effect deviates from the ideal behavior shown before and can follow similar behavior to the
dashed lines in Figure 30. This is independent from the IHOLD values described before.
Figure 30
Detail of MOSFET gate charge during the charging and discharging transitions
In cases where Qg(th) is too small to apply a larger current than the one used for slew rate control, user can set
TDRIVE2 to value 0. This will results in the gate driver start driving the MOSFETs with TDRIVE1 and once the period is
elapsed it will apply 1.5A ignoring TDRIVE2 configuration. This ensures optimal settings for both large and small
MOSFETs and right fit for different technologies like OptiMOS™ or StrongIRFET™. Similarly, TDRIVE2, TDRIVE3 and/or
TDRIVE4 can be set to 0 resulting in those configurations being skipped. Figure 31 shows an example of this
behavior where TDRIVE2 = 0 while other TDRIVEX settings are different than zero.
Note:
When driving with a single timing setting the charge or the discharge phases, it is recommended to
use either TDRIVE1 or TDRIVE3 as driving periods and make TDRIVE2 or TDRIVE4 equal to 0. The opposite is
possible, however might result in selected timing (TDRIVE2 or TDRIVE4) becoming slightly shorter than
the programmed value due to internal propagation delays. User must decide which solution fits
better to the application
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Figure 31
Detail of MOSFET gate charge during the charging and discharging transitions. TDRIVE2=0
example
4.4
Gate Driver Voltage Programmability
Different drives systems might benefit from different MOSFET technologies. An example is the common usage
of logic level MOSFET vs standard or normal level MOSFETs, which show a higher threshold voltage (Vgs(th)). For
the same gate to source voltage, a logic level MOSFET presents lower RDSON value than a normal level MOSFET.
Increasing the driving voltage helps reducing the RDSON of the MOSFET channel during conduction and as a
result the conduction losses of the system. This is shown in Figure 32. However, increasing the driving voltage
increases the rise switching times (rise and fall) leading eventually to higher switching losses. User must choose
the right driving voltage depending on the system conditions.
Figure 32
Typical RDSON vs VGS characteristic in MOSFETs. Higher VGS voltage reduces the RDSON of the
MOSFET
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6EDL7141 allows designers to adjust the MOSFET driving voltage (PVCC voltage) via SPI registers. The same
value PVCC applies to both high and low side charge pumps with four possible values: 7V, 10V, 12V, 15V. This is
done via bitfield PVCC_SETPT.
Note:
It is expected that the high side charge pump produces a lower voltage due to internal circuitry
(diode).
Figure 33 shows an ideal example of how supply voltage of the driver and slew rate control can play a role
together in an ideal turn on of a low side MOSFET. Section A of the figure shows how to set the slew rate of VGS
external MOSFET, by programming different current values (in this case ILS_RISE). Section B shows the case in
which, provided a fixed gate driver current ILS_SRC, PVCC is varied.
Figure 33
Gate driver slew rate configurability in an ideal low side MOSFET switching: A) given a
fixed supply voltage (PVCC=12V), variable ILS_RISE B) Fixing the charging current, changes in
PVCC produce different rise times
4.5
Charge Pump Configuration
User can adjust charge pumps operation in MOTIX™ 6EDL7141 depending on the specific needs. Following
sections describe this configurations.
4.5.1
Charge Pump Clock Frequency Selection
Charge pumps are based on switched capacitor circuits that work at a given switching frequency. 6EDL714
offers the possibility to choose four different clock frequencies via SPI programming of bitfield CP_CLK_CFG in
register CP_CFG. The selection of charge pump capacitors both flying and tank capacitors must be chosen
according to this configuration and both affect start-up time of VCCLS and VCCHS rails as well as possible
voltage ripple in those pins.
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4.5.2
Charge Pump Clock Spread Spectrum Feature
When activated, this feature introduces artificially a frequency variation (see Electrical Characteristics table for
values) into the charge pump clock signal. The frequency at which the charge pump operates will vary between
those limits reducing the emission intensity on the target frequency value by distributing that energy over a
wider range of frequencies.
4.5.3
Charge Pump Pre-Charge for VCCLS
Pre-charge of the charge pumps is a feature that, if enabled via SPI register, pre-charges the VCCLS rail right
below the buck converter output voltage (VDDB) before the EN_DRV pin is activated. This pre-charge takes
place only the first time after a power up (CE cycle) sequence.
In this case, when EN_DRV is activated to enable the driver stage, the charge pumps need to ramp up the
voltage in CVCCLS from the existing pre-charge voltage until the PVCC selected value, therefore reducing
considerably the start-up time for the charge pump when compared to the default situation in which CVCCLS
needs to charge the whole PVCC voltage.
To enable the pre charge of VCCLS, bitfield CP_PRECHARGE_EN in register SUPPLY_CFG must be set.
4.5.4
Charge Pump Tuning
The start-up time for the charge pumps, defined as the time that the VCCLS voltage requires to get to the target
programmed voltage (PVCC Set point), depends on several factors:
•
•
•
Target voltage programmed via PVCC_SETPT register: the higher the longer the start-up time
Charge pump clock frequency: higher clock frequency results in faster start-up time
Charge pump tank capacitors (CVCCLS, CVCCHS): using VCCLS as example, a smaller value of CVCCLS will result in:
o
o
Higher VCCLS ripple
Faster start-up time
•
Charge pump flying capacitors (CCP1, CCP2): smaller capacitors lead to slower start-up time
The selection of those parameters have an impact as well in the VCCLS and VCCHS voltage ripple. If fast start-up
time is not a design target, it is recommended to increase the CVCCLS value to reduce ripple and to improve load
transients. For a given CVCCLS value, the selection of CCP1 will impact also the ripple in VCCLS and start-up time.
If start-up time needs to be optimized, charge pump pre-charge feature is recommended. This is explained in
section 4.5.
The start-up behavior of the charge pumps and rest of power supply is shown in detail in section 10.1
4.6
Gate Driver and Charge Pumps Protections
The gate driver includes following protections:
•
•
•
•
VCCLS UVLO
VCCHS UVLO
Floating Gate Driver Pull Down
Dead Time insertion - This is explained in section 4.1.7
4.6.1
VCCLS Under-Voltage Lock-Out (VCCLS UVLO)
The UVLO prevents the gate driver from propagating PWM signals if the drive voltage is not above the UVLO
threshold as specified in the Electrical characteristics table.
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During start-up, the charge pump voltage VCCLS will ramp up until the UVLO rising threshold is crossed
releasing the UVLO status, allowing then the PWM to propagate.
In case of overload of VCCLS rail beyond the specified maximum load of the charge pump, the VCCLS will drop.
Eventually, the VCCLS voltage can cross the VCCLS UVLO falling threshold leading to both the immediate stop
of the PWM signal being transmitted to the MOSFETs by setting the gate driver in Hi-Z (high impedance) mode
and also reporting a fault to the Fault handler. Consequently, the nFAULT pin will be pulled down so the
XMC1404 can decide how to proceed.
4.6.2
VCCHS Under-Voltage Lock-Out (VCCHS UVLO)
Similarly to VCCLS, a UVLO mechanism is integrated for VCCHS voltage rail. The UVLO rising and falling
thresholds can be found in the Electrical Characteristics table.
During start-up, the charge pump voltage VCCHS will ramp up until the UVLO rising threshold is crossed
releasing the UVLO status, allowing then the PWM to propagate.
In case of overload of VCCHS rail beyond the specified maximum load of the charge pump, the VCCHS voltage
will start dropping. VCCHS voltage can then cross the VCCHS UVLO falling threshold leading to both the
immediate configuration of the gate driver to Hi-Z (high impedance mode) and also to the reporting to the Fault
handler. As a result of the VCCHS UVLO, the nFAULT pin will be pulled down so XMC1404 can decide how to
proceed.
4.6.3
Floating Gate Strong Pull Down
MOSFETs in an inverter can be exposed to non-zero gate voltage levels when the controllers or gate drivers are
off. Sometimes those voltages are enough to activate or partially activate the MOSFETs leading to system
failure or destruction if for example, a high side MOSFET and a low side MOSFET in an inverter leg activate at
the same time. In order to prevent this behavior is common to assemble weak pull downs (in the order of 100kΩ
resistors) between gate and source of the MOSFET to ensure that when the gate driver is off, the gate is pulled
down to the source avoiding any turn on or partial turn on. As it is weak pull down, this does not have
noticeable impact when the gate driver is active and driving MOSFETs normally.
These six RG-S resistors however require a good amount of PCB area and need to be placed in a location where
the power layout needs to be optimized with no compromises.
In order to address this, 6EDL7141 gate driver integrates a floating gate strong pull down mechanism that
includes both a passive and an active pull down:
•
•
Weak Pull Down: a weak pull down (RGS_PD_WEAK) is always connected between gate and source of each gate
driver output. This ensures a weak pull downs during states where the gate driver is off, either because
EN_RV is turned off or because the device is fully off (CE off). This mechanism is similar to the ones described
above (RG-S).
Strong Pull Down: additionally, during those gate driver off periods, if the external gate to source voltage
increase for any reason as mentioned, an extra pull down, much stronger (RGD_PD_STRONG) is activated ensuring a
tight pull down and hindering any possible partial turn on.
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Figure 34
Floating gate driver pull down resistors. Strong pull down activates when gate driver is off
and gate to source voltage increases
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5
MOTIX™ 6EDL7141 Power Supply Subsystem
The device embeds an advanced power supply system comprised of:
•
•
•
•
Synchronous buck converter including both power switches
DVDD linear voltage regulator pre-programmed to 3.3V (IMD700A) or 5V (IMD701A)
Charge pump for low side gate driver (described in 4)
Charge pump for high side gate driver (described in 4)
MOTIX™ IMD70xA has been designed for lowest Bill of Material (BOM). The synchronous buck converter does not
require external components like diodes, voltage dividers or bootstrap capacitors yet at the same time reduces
the low side conduction losses as it utilizes a NMOS instead of a diode.
The overall goal of the buck converter is to support the rest of the power supply system. With the help of an
external filter (LC), it supplies both (high side and low side) charge pumps and the integrated DVDD voltage
regulator. This architecture increases the efficiency of the device greatly compared to an only linear regulator
system, yet maintains a very compact system solution. Furthermore, allows working at high supply voltage
rating (PVDD).
DVDD linear voltage regulator is integrated to provide accurate and stable voltage to XMC1404 and other
external components. In Figure 35, a schematic diagram of the complete power converter architecture and
interconnections is showed.
Figure 35
Block diagram of power converter architecture
Designers can use VDDB pin to supply external components as long as the current limits of the buck converter-
including charge pumps and linear regulator- are not exceeded. Nevertheless, over-current protections (OCP)
are implemented for both buck converter and the linear regulator, preventing any damage to the device when
overloading VDDB pin. Additional over-temperature protections (OTS, OTW) are integrated to ensure the device
is under correct thermal conditions at any time.
5.1.1
Synchronous Buck Converter Description
Although integrated in the same package, the synchronous buck converter is designed completely independent
of the rest of the gate driver circuitry. This makes the supply system robust against gate driver failures. As an
example, the buck converter and linear regulator will still operate even if a failure occurs in the gate driver
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section (e.g. VCCLS UVLO), ensuring right operation of circutis in the system supplied by the buck converter or
LDO integrated.
The control method utilized is Adaptive Constant ‘ON’ Time (ACOT). In contrast to a pure constant ON time
control method, ACOT allows for ON time variations during transitions to avoid large frequency jumps.
Together with feedforward techniques, this buck converter can operate almost at fixed switching frequency.
Two different switching frequencies (500 kHz and 1 MHz) can be selected via SPI –BK_FREQ bitfield-for the buck
converter. The recommended inductor and capacitor for each configuration is provided in section 12.1.
Recommended values for the inductor and capacitor are shown in Table 30.
Note:
It is recommended to only modify the buck converter frequency via OTP
A detailed figure of both synchronous buck converter and linear voltage regulator circuits is depicted in Figure
36.
Figure 36
Detail of integrated synchronous buck converter controller and linear regulator
5.1.1.1
Buck Converter Output Voltage Dependency on PVCC_SETPT
An important feature of the buck converter is the ability to automatically adjust VDDB target value depending
on PVCC (target gate driver voltage) configured by user via SPI commands. This is done to optimize power
losses in the device. For example, if the driving voltage PVCC is 7V, the target voltage of the buck converter is
automatically set to 6.5V given and still the charge pumps will have enough room to reach PVCC = 7V on a
‘doubler’ configuration. The relationship between VDDB and PVCC is shown in Table 23.
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Table 23
Buck converter output target voltage vs PVCC_SETPT setting
PVCC_SETPT bitfield
PVCC target voltage (V)
VDDB (V)
b’11
b’10
b’00
b’01
7
6.5
7
10
12
15
8
8
Another important factor to consider in the synchronous buck converter output target voltage is PVDD or
supply voltage. If PVDD is low enough so VDDBNOM_LV rating applies (see Electrical Characteristics table), then the
buck converter cannot ensure the target output voltage as provide in Table 23. In this situation, the buck
converter enters a ‘limiter’ mode in which the duty cycle saturates to DCBUCK_MAX (see Electrical characteristics
table). If buck converter loading increases or PVDD voltage reduces further, VDDB voltage will drop. On the
lower end, VDDB UVLO falling threshold protects from lower limits.
Therefore, depending on PVDD voltage, it is possible that VDDB cannot reach the target voltage, limiting as a
consequence the actual PVCC voltage, which even in a doubler configuration might not be sufficient. The
approximate possible PVCC voltage (= VCCLS) in the doubler configuration is given by the minimum between
the target PVCC voltage or twice VDDB minus 1 V as shown in following equation:
푃ꢃꢄꢄ푚푎푥 ≈ min(푃ꢃꢄꢄ ꢅꢆ푟푔푒푡 ꢃ표푙푡ꢆ푔푒, 2 ∗ ꢃꢇꢇ퐵 − 1ꢃ)
(1)
As an example, if PVDD = 7.5V, VDDB ≈ 6.5V (limited by low PVDD), if PVCC_SETPT targets 15V, the doubler on
the charge pump will be able to reach maximum of approximately 2* VDDB-1V ≈ 12V. If then PVDD rises to 12V,
the VCCLS will be able to regulate to 15V as this value is below/equal to the value = 2* VDDB (8V) -1V = 15V.
See 2.7 for more details on relationship between VCCLS, VCCHS and PVDD.
5.1.1.2
Synchronous Buck Converter Protections
Following protections are implemented to ensure correct operation of the buck converter:
•
•
Output Under-Voltage Lock-Out (UVLO). See Electrical Characteristics table for specific values
Output Over-Voltage Lock-Out (OVLO). See Electrical Characteristics table for specific values. If the value is
reached the buck converter will switch off both high side and low side MOSFETs interrupting any further
energy transfer to the output.
•
Over-Current Protection (OCP) cycle by cycle. Given a situation in which the current increases till the OCP
level (see Electrical Characteristics table for details), the buck converter controller will truncate the high side
FET PWM signal until next PWM period start. The low side FET will be driven accordingly after insertion of
dead time. The OCP level reduces as well if PVDD is below 7.465V to ensure proper device operation.
Once the OCP event takes place, a counter will start counting for each consecutive period that the peak
current is reached. After 16 periods, the Buck OCP fault is triggered and nFAULT pin (see Table 25) will be set
low to inform the XMC1404 that can proceed with correcting actions. The Buck converter will continue
operation in current limitation to ensure XMC controller is supplied. If the OCP does not trigger for 3
consecutive PWM periods, the counter will reset and will not trigger the Buck OCP fault. If the Buck OCP
fault is activated, the bitfield BK_OCP_FLT in register FAULT_ST will be set.
5.1.2
DVDD Linear Regulator
The integrated linear regulator generates the voltage rail DVDD that can supply XMC1404.
Attention:
User must connect externally all DVDD pins as there is no internal connection for DVDD inside.
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DVDD linear regulator can be used as well to provide an offset to the current sense amplifiers integrated,
allowing negative current measurements. See 6.1.4 for more details.
The linear regulator is soft started during ramp up of the device as depicted in Figure 56 after a delay time
tDVDD_TON_DLY once the buck converter has reached its UVLO level (VVDDB_THH_UV) and analog programming of
CS_GAIN is finished. The DVDD ramp up timing can be configured via SPI via bitfield DVDD_SFTSTRT.
A schematic view of DVDD linear regulator and the interaction with the buck converter is presented in in Figure
36.
DVDD voltage is be used to supply the integrated XMC1404 controller and can be used to supply additional
elements in the circuit like Hall sensors, LEDs, etc. A programmable OCP mechanism is provided to avoid
damage to the LDO due to excesive current demand.
5.1.2.1
DVDD Linear Regulator OCP
DVDD OCP can be configured between 4 different levels by writing register DVDD_OCP_CFG. If the OCP for DVDD
is reached, a fault will be reported on pin nFAULT. The DVDD OCP works in two different stages:
1. Pre-warning mode at 66% of selected OCP level: nFAULT pin will be pulled down to signal the controller
that an OCP warning has occurred. If the current level reduces before reaching 100% level, the operation will
continue normally releasing the nFAULT pin. The pre-warning allows some extra time for XMC1404 to make a
decision on how to react to the possible OCP event.
2. Current limiting mode at 100% of selected OCP level: if current increases beyond the configured OCP level,
the DVDD regulator will start limiting the current provided. This will cause a DVDD voltage drop, eventually
resulting in a DVDD UVLO fault if DVDD UVLO threshold is crossed (see the Electrical Characteristics table for
more details). Thanks to this limitation, possible shorts on DVDD rail will not affect rest of the system keeping
these other components safe.
Figure 37
DVDD OCP behavior including pre-warning and current limiting modes
Note:
The OCP in DVDD is suppressed during ramp up of the device to avoid that initial charge of DVDD
decoupling capacitors (eventually large capacitors) triggers the OCP fault
Over-temperature faults (OTS, OTW) provide an additional level of protection. These will trip if too high
temperature is developed in the device, for example when the DVDD linear regulator or the buck converter
demand excessive load current.
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6
MOTIX™ 6EDL7141 Current Sense Amplifiers
The device integrates three current sense amplifiers that can be used to measure the current in the power
inverter via shunt resistors. Single, double or triple shunt measurement are supported as shown in Figure 38.
CS_EN bitfield enables each current sense amplifier individually. The output of the current sense amplifiers can
be connected to the ADC inputs (AINx pin) of IMD70xA via optional RC filters to remove high frequency
components. Gain and offset are generated internally and must be programmed via SPI commands.
Figure 38
Single (A), dual (B)and triple (C) shunt current sensing configurations are supported
The current sense amplifier block contains the following sub-blocks explained in detail this section:
•
Current sense amplifier: connected to external shunt resistor or internally to SHx and SLx pins for RDSON
sensing configuration. This module amplifies the shunt voltage or VDS voltage to a more appropriate voltage
level for a microcontroller ADC. It allows as well blanking the signal synchronized to PWM transitions, during
periods where noise is disturbing the measurement. Gain must be set via SPI programming in IMD70xA, no
resistor configuration is possible.
•
•
Output buffer: allows adding a variable offset voltage to the sense amplifier output. The offset amount can
be set to 4 different values by programming the internally generated level. With this implementation,
negative current in current shunts can be measured. Additionally permits to optimize the controller ADC
dynamic range according to system conditions.
Positive Over-Current comparator: used for detecting the over-current condition on motor winding for
positive shunt voltage This comparator can be used to apply PWM truncation in trapezoidal commutation
schemes, limiting the motor current to the configured OCP threshold.
•
•
Negative Over-Current comparator: used for detecting the over-current condition on motor winding for
negative shunt currents
OCP Digital-to-Analog Converter (DAC): used for programming the threshold of the over-current
comparators. One for positive level and a second one for negative level. Programming of DAC levels is shared
among different OCP comparators.
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Current sense amplifiers are able to “Auto-Zero” during operation and ensures best accuracy of measurements
during lifetime of the device. Additionally, the device includes a current sense amplifier user calibration mode
that can be used to calculate residual offset before the driver is enabled (EN_DRV low), therefore ensuring
current in the inverter and in the shunts are zero. XMC1404 can remove this initial residual value from future
measurements to improve accuracy.
Figure 39 shows these blocks and their interconnections.
Figure 39
Current sense amplifier simplified block diagram
6.1.1
RDSON Sensing Mode vs Leg Shunt Mode
Current sense amplifiers in MOTIX™ 6EDL7141 can be configured as leg shunt or RDSON sensing, where the ‘ON’
resistance of the MOSFETs is used as shunt in a ‘lossless’ measurement approach.
In RDSON mode, 6EDL7141 connects the drain of the low side MOSFET to the positive input of the current sense
amplifier. The negative input is connected to the source as shown in Figure 40. This is in contrast to the external
shunt configuration shown in Figure 41, where the positive input of the current sense amplifier is connected to
the source of the low side MOSFET. Internal series resistors help filtering possible noise before the amplification
takes place. Depending on the circuits and board design, a small filtering capacitor between SLx and CSNx pins
can help cleaning up the current signal.
Note:
Note:
RDSON mode is only possible in 3 shunt mode (mode C in Figure 38)
In RDSON mode, the CSAMP is forced to be CS_TMODE = 0, meaning the current sense amplifiers are
only active when low side is ON (GL ON mode).Writes different than b’0, will be ignored by the
internal logic.
Note:
Temperature compensation for the RDSON measurement, if required, must happen via XMC1404
algorithms not provided here.
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Figure 40
System diagram of a low side RDSON current sensing configuration utilizing integrated
current sense amplifiers
Figure 41
System diagram of an external shunt current sensing configuration utilizing integrated
current sense amplifiers
6.1.2
Current Shunt Amplifier Timing Mode
Often in drives applications, the current is sampled via leg shunts. IN this case, the voltage in the shunt that
needs to be amplified appears only when the low side MOSFET is turned on. In other cases, it might be useful to
propagate the signal continuously. IMD70xA supports four different modes of operation of the current sense
amplifiers regarding when the output pin CSOx is connected to the amplifierstage. These four modes are:
•
Always OFF: current sense amplifier output disabled. This is achieved by disabling the amplifier in register
CSAMP_CFG via bitfield CS_EN.
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•
GL ON: in this mode, CSOx pin is connected to the amplifier only when the same leg or phase GLx signal is
active. In single shunt mode, CSOx will be connected according to the OR’ing of all two or three GLx signals. If
two or three amplifiers are enabled, then the signals for enabling CSox will be dedicated to that GLx signal.
This mode is forced if RDSON sensing is selected to avoid possible overvoltage damage in the internal circuitry.
In order to enable this mode, the amplifier must be enabled via CS_EN bitfield in CSAMP_CFG register and the
timing mode selected via write to CS_TMODE bitfield in SENSOR_CFG.
•
GH OFF: similarly to GL ON, this modes connects the CSOx outputs during GL ON period but extends that
connection to the dead times both rising and falling. This is same than GH OFF. In some cases like during
diode recirculation current, the diode might carry current that can be useful especially in cases where the
PWM pulses are very narrow. Same as GL ON, single shunt will logic OR the GLx activations and three shunt
modes will activate according to each GLx signal only. In order to enable this mode, the amplifier must be
enabled via CS_EN bitfield in CSAMP_CFG register and the timing mode selected via write to CS_TMODE
bitfield in SENSOR_CFG.
•
Always ON: this mode connects continuously the activated amplifier CSOx signals to the amplifier
independently of PWM signals. In order to enable this mode, the amplifier must be enabled via CS_EN bitfield
in CSAMP_CFG register and the mode selected via write to CS_TMODE bitfield in SENSOR_CFG.
Figure 42 (cases 1 and 2) shows a comparison of the current sense amplifier working in both modes GL ON and
GH OFF.
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Figure 42
Current sense amplifier ideal timing mode examples. Mode GL ON and GH OFF operation in
a half bridge example with leg shunt current sense configuration-3 active amplifiers. GH
OFF can potentially propagate current information when the diode recirculates current.
Auto Zero injected on GHx rising (internal sync.)
6.1.3
Current Shunt Amplifier Blanking Time
A programmable blanking period can be configured in the current sense amplifiers. The goal of adding some
blanking time is to avoid propagating a distorted signal to the microcontroller ADCs during MOSFET switching
transitions. Since both, phase node voltage SHx and SLx pins (CSNy) are subject to ringing due to the switching
activity, the blanking module disconnects the inputs for a configurable time (CS_BLANK). This action occurs in
synchronicity with GHx signals (rising and falling edges) driving the external MOSFETs.
During the blanking time, pin CSO will show Voffset voltage until the programmed blanking time period expires
and inputs are connected again to the current sense amplifier. Two examples are shown in Figure 43. Example
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A) represents a trapezoidal commutation scheme with 1 shunt similar to the one in Figure 61. In such case the
high side of one phase (phase B) is switching, while the low side of another phase (phase A) is always ON,
allowing the current to flow through the motor windings. As the low side MOSFET of phase A is ON for 120
degree of rotation, the current sense amplifier is amplifying the shunt voltage continuously except blanking
and recirculation periods. These blanking periods corresponds to both high side and low side rising edges
(ORing of all phases). In this case the voltage across the shunt is positive.
The example in B) corresponds to a generic half bridge configuration (e.g. synchronous buck converter). In this
case, when high side is turned on, the current in the inductor increase, while in the complementary cycle when
the high side switches off and the low side turns on after dead time, the current flows through the low side and
starts decreasing. During the low side conduction, the current sense amplifier generates the shown output
proportional to the voltage across the shunt, in this case negative.
Figure 43
Timing diagram of a current measurement utilizing blanking time feature for suppressing
current spikes during MOSFET switching. A) Trapezoidal commutation with 1 shunt
configuration. B) Generic half bridge configuration.
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6.1.4
Current Sense Amplifier Internal Offset Generation
6EDL7141 integrates an internal linear voltage regulator (DVDD) that can be used for offset generation in all
integrated current sense amplifiers. The generated DVDD voltage can be scaled down to different
programmable values to adjust the desired offset voltage level. Bitfield CS_REF_CFG controls this scaling
factor.
XMC1404 generates internally the reference for the integrated ADC out of the supply voltage. In this way the
microcontroller can accurately measure in a ratio-metric way the output of the current sense amplifiers
increasing noise immunity. Figure 44 shows a block diagram representing this implementation. Only internal
offset generation is possible in IMD70xA.
Figure 44
Current sense amplifier offset generation block diagram
6.1.5
Overcurrent Comparators and DAC for Current Sense Amplifiers
Two overcurrent comparators are implemented for monitoring the current in both positive and negative
direction with an extensive level of programmability. Figure 45 shows a schematic diagram of this
implementation. Both comparators monitor the current flowing through the shunts. The triggering level is
independent from the gain setting of the shunt amplifiers and is defined as the voltage across the shunt. The
comparator features a hysteresis (specified as VOC_HYST) for consistent operation.
Positive and negative triggering levels for the comparator are set with two independent Digital to Analog
Converters (DAC). These DACs are programmed via bitfields CS_OCP_PTHR for positive overcurrent protection
and CS_OCP_NTHR for negative overcurrent protection. For possible threshold levels see the registers
description in section 11.
The output of the comparators can be deglitched by programming register CS_OCP_DEGLTICH before reaching
the Fault handler, where the fault will be processed (See section 6.1.8) and eventually will pull down nFAULT
pin reporting a fault to XMC1404.
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Alternatively, the comparator output propagates to the PWM modules. PWM truncation can be enabled via
bitfield CS_TRUNK_DIS. If PWM truncation is activated, the PWM module immediately interrupts the PWM
signal without having to wait for the XMC1404 to make such decision if the OCP level is reached. This ensures
fastest possible reaction time to the OCP event. Truncation is detailed in section 0.
CS_OCPFLT_CFG in register CSAMP_CFG allows the user to set a target number of consecutive events (PWM
cycles with current above OCP threshold) that will activate OCP fault. This means the user can configure the
device to wait for several PWM periods before declaring a fault.
Figure 45
Current sense amplifier protections schematic block diagram
6.1.5.1
OCP Use Cases
The reaction to an OCP event is programmable via SPI. Following scenarios might be useful for different
applications:
•
•
•
Apply PWM truncation immediately after OCP event and report on nFAULT pin after OCP event- deglitching
is disabled if truncation is enabled.
Disable reporting and keep truncation of PWM. This can be useful during events where the reporting
function to the microcontroller might not be necessary.
Trigger a configurable brake action upon OCP event. If truncation is not desired, the brake event can be
configured to e.g. brake the motor by shorting all low side MOSFETs. By using the deglitch function, the
possible noise in the analog signal can be filter out to avoid false trip of the OCP. This configuration can be
useful for FOC (Field Oriented Control) schemes given the flexibility. Braking is explained in more detail in
sections 4.1.6 and 6.1.8.
•
Disable OCP protection, both nFAULT reporting and truncation of PWM. In such case, OCP is ignored. This
might be useful for transition states or stop procedures as well.
These configurations can be adjusted also during ACTIVE state of the device. It is also possible to select whether
the OCP fault trips on a single event or more and whether is latched or not via bitfield CS_OCP_LATCH.
6.1.5.2
OCP Fault Reporting
In case of OCP fault, 6EDL7141 can report the fault by pulling down pin nFAULT. Internally, IMD70xA connects
this pin to P3.4 pin in XMC1404. XMC code can poll this GPIO pin to be informed of the fault and make a
decision.
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CS_OCPFLT_CFG in register CSAMP_CFG allows the user to set a target number of consecutive events (PWM
cycles with current above OCP threshold) that will activate OCP fault. This means the user can configure the
device to wait for several PWM periods before declaring a fault and therefore be more conservative. Three
options are possible: no fault, trigger immediately (i.e. trigger on all events) or trigger on a number of counts (8
or 16). The logic for the counting mode works as follows:
1. Every time that an OCP event occurs, a counter increments. All three phases have dedicated counters.
2. If any counter (ORing) reaches the target value configured in CS_OCPFLT_CFG, then the fault is asserted and
nFAULT pin is pulled low.
3. If before reaching the target value, the OCP event does not occur for 3 consecutive PWM cycles, the counter is
reset to value 0, starting over next time an OCP event takes place.
6.1.5.3
OCP Fault Latching
The OCP fault can be configured as latched or non-latched. This defines how the fault is cleared via register
write. If configured as latched:
•
•
and in counting mode (8 or 16): fault cannot be cleared until there is one whole PWM period without fault
and in immediate or on all events mode: fault can be cleared only after the fault condition is released.
If not latched, the fault can be cleared any time. If conditions is still present after clear, the fault will be set
again after the clear event.
Independently of the latch configuration, the status register will show that the fault happened.
6.1.5.4
PWM Truncation
PWM truncation is a method to intrinsically limit the current flowing into the motor by switching off the PWM
signal immediately after OCP detection. In this way, the GHx signals (all three) are pulled down automatically
when the configured peak current level is reached. Low side remains unaffected until the PWM resets,
increasing current in the motor again. This happens in a PWM cycle by cycle base. An example of how PWM
truncation works, is depicted in detail in Figure 46.
Note:
Truncation occurs always on high side except for 1PWM mode with alternate recirculation, where
the truncation occurs in low side during high side recirculation periods.
If PWM truncation is active, PWM truncation takes place upon OCP event in all phases. For example, if the
protection is triggered in current sense amplifier A, then PWM signals in phases A, B and C will be truncated.
This will enable single shunt systems to utilize any of the current sense amplifiers.
Blanking is applied to truncation logic on both rising and falling edge of high side as described in Figure 43, see
register CS_BLANK for blanking times. Blanking from all phases are OR’ed and prevent any miss-triggering of
the PWM truncation during the blanking time selected by the user.
If truncation is enabled, the deglitching filter is automatically disabled. This means, if truncation is enabled, the
nFAULT pin signalizes simply that a PWM truncation has occurred.
Attention:
Depending on the PWM modulation utilized, PWM truncation might not provide the desired
results. In modulation schemes where it is possible more than one phase are energizing the
motor at a given time like SVM FOC (Space Vector Modulated Field Oriented Control), it is
recommended to disable truncation and use OCP fault instead.
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Figure 46
Positive OCP PWM truncation detail. IM refers to motor current.
6.1.6
Current Sense Amplifier Gain Selection
During start-up of the system, user must program the desired gain of the current sense amplifier. To do this,
user must write bitfield CS_GAIN_ANA to ensure digital programming of the gain and write as well CS_GAIN
bitfield to set the actual gain. The actual value can be read in CS_GAIN_ST which reports the current gain value
programmed. Gain of the shunt amplifiers can be programmed to one of the following values: 4, 8, 12, 16, 20,
24, 32 and 64.
Attention:
Analog gain programming is not supported in IMD70xA devices. Default configuration is set to
analog programming in 6EDL7141 and user must ensure to first change to digital
programming and second to program desired gain before starting operation
6.1.7
Current Sense Amplifier DC Calibration
MOTIX™ 6EDL7141 features a calibration method for the current sense amplifiers. This helps eliminate any
unwanted offset in the output of the operational amplifiers before starting motor operation for example.
The activation of the DC calibration mode (only during ACTIVE state-EN_DRV high) via register CS_EN_DCCAL
programming, will short the inputs of the amplifiers. Once the DC calibration is enabled, the output on CSOx
pins can then be measured by precise ADC channels in XMC1404 AINx pins to record any possible offset in the
system. Any excess voltage in CSOx pin from internal VREF voltage can be subtracted by XMC1404 embedded
code from any future measurements. It is recommended to perform DC calibration before the PWM is started,
when the current in the shunts, is known to be zero. This algorithm must be implemented by user.
Once the offset value is captured, XMC1404 must set CS_EN_DCCAL bitfield again to ‘0’ to finalize the
calibration process and reconnect the operation amplifier to the input pins. Then the PWM signals can start-up.
Note:
During calibration mode, if Auto-Zero is enable it will be executed every 100µs instead of 200µs.
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6.1.8
Auto-Zero Compensation of Current Sense Amplifier
Current sense amplifiers tend to accumulate offset during operation if they are not corrected. This can be due
to temperature or the aging effects. The Auto-Zero feature of the current sense amplifiers provides an
automatic way of compensating any possible drifts in the amplifiers. Internally the amplifier shorts the inputs
to correct any possible offset excess for a tAUTO_ZERO period of time. CSOx pin will hold the voltage before the
Auto-Zero start during Auto-Zero period.
The Auto-Zero feature can be as well disabled via register bitfield AZ_DIS in register CSAMP_CFG.
6.1.8.1
Internal Auto-Zero
If configured as internally triggered or synchronized (by writing register bitfield CS_AZ_CFG), the Auto-Zero
period starts with GHx signal rising edge after at least 100µsec from last Auto-Zero period (x depends on the
activated current sense amplifier, A, B or C). The synchronized start of Auto-Zero period is chosen to interfere
minimum possible with the shunt current sensing. When the high side MOSFET turns on, the low side MOSFET is
off and therefore no signal should be present in the shunt in normal conditions, therefore not affecting the
sampling of relevant information in the signal. Details of signals behavior example can be seen in Figure 42 or in
Figure 47.
Figure 47
Auto-Zero operating modes. Auto-Zero occurs upon next GHx rising edge after timer has
reached 100µs. Auto-Zero period will then rest the timer again
During start-up, the Auto-Zero function automatically activates to ensure that the amplifiers are optimized
before the ACTIVE state is entered. This happens during charge pump start-up, this is from EN_DRV turn on until
charge pump UVLO is reached.
If no GHx rising edge happens for a given time (tAUTO_ZERO_CYCLE), for example if the low side is fully turned on for a
long period in a 6-step commutation, then an internal watchdog will force an Auto-Zero compensation. Auto-
Zero continuous during STANDBY state.
Note:
When the Auto-Zero period finishes and the CSOx reconnects to the amplifier, it is expected to see a
minor voltage glitch. This can be blanked or filtered out for example before the signal is provided
to an ADC.
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6.1.8.2
External Auto-Zero Synchronization via AZ Pin
User can enable external synchronization of the Auto-Zero function by writing register bitfield CS_AZ_CFG. In
such case, the internal synchronization with GHx signals is disabled and the falling edge of pin AZ becomes the
trigger for Auto-Zero correction period. This is depicted in Figure 48.
In IMD70xA, pin AZ is internally connected to pin P1.2. If externally triggered, XMC1404 can decide according to
the particular current sense method when to execute the Auto-Zero correction by activating P1.2. Thanks to
this feature the Auto-Zero effect can be moved, for example, far from the ADC sampling in XMC benefitting from
the corrections but still being able to sample without the interference of the Auto-Zero process.
Figure 48 Auto-Zero functionality with external synchronization. AZ pin falling edge will trigger the
Auto-Zero correction period
6.1.8.3
External Auto-Zero Synchronization via AZ Pin with Enhanced Sensing
MOTIX™ 6EDL7141 to stop the clock (clock gating) of the charge pump modules according to AZ pin state. If this
feature is activated, the charge pumps clock will be gated from the rising edge of AZ pin until end of Auto-Zero
period that starts after falling edge of same pin. The effect of the clock gating is the reduction of possible
switching noise that can couple into PCB sensitive signals like CSOx or other ADC measured voltages by
XMC1404.
Attention:
During clock gating period, the charge pump stops operation. As a result, VCCLS and VCCHS
rails stops regulation and can drop their regulated voltages. In most cases, VCCLS and VCCHS
capacitors will maintain enough voltage to keep driving efficiently the MOSFETs. User must
check that Recommended Operating Conditions and MOTIX™ 6EDL7141 Electrical
Characteristics are respected. UVLO protections on both VCCLS and VCCHS are present in
case a malfunction takes place, protecting the inverter
The operation of charge pump clock gating mode is shown in Figure 49.
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Figure 49
Signal diagram for the enhanced sensing mode using external synchronization of Auto-
Zero function. The charge pump clock is gated to reduce switching noise coupling during
periods where sensitive measurements are performed in the system like the ADC in
XMC1404 or other external sampling circuits
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7
MOTIX™ 6EDL7141 House-Keeping Functions
7.1
Hall Comparators
Hall comparators are designed to be used in 1PWM mode with Hall sensors or emulated signals from XMC1404,
described in section 4.1.4 as well as for ‘locked rotor’ detection functionality described in 7.2.3.
The Hall inputs are digitally deglitched. That means those inputs ignore any extra Hall transitions for a
configurable period of time. This is selected in bitfield HALL_DEGLITCH that can be accessed via SPI
commands. This prevents PWM noise from being coupled into the Hall inputs, which can result in erroneous
commutation.
The polarity of the Hall sensor inputs can be read at any time in register FUNCT_ST, bitfield HALLIN_ST.
7.2
Watchdog Timer
MOTIX™ 6EDL7141 integrates three independent watchdog timers that are SPI configurable. These are
protection features used to ensure the correct functionality of different modules inside and outside the device,
e.g. to ensure that XMC1404 is having correct behaviour by serving or ‘kicking’ the watchdog. To configure
watchdog timers two registers are available: WD_CFG and WD_CFG2. The three independent watchdog timers
are:
•
•
•
Buck converter watchdog:
General purpose watchdog
Rotor locked watchdog
Each watchdog timer core unit includes a digital timer (watchdog timer). A source signal is connected to that
timer which resets whenever a toggle occurs on the signal. Otherwise the timer keeps counting up. If the
watchdog timer limit is reached without a reset input, then a fault takes place and action will be performed
according to Table 25.
The reaction to a watchdog fault is programmable to following actions:
•
•
•
•
Reporting to status register only.
Reporting to status register and nFAULT pin connected internally to XMC1404 (pin P3.4).
Trigger a configurable braking event.
Select whether watchdog fault is latched or not.
An example of watchdog operation is presented in Figure 50. In this example, a generic signal ‘WD_Input’ is
resetting the counter periodically (for example when reading the status register). If the input signal stops
toggling, the watchdog timer expires after the watchdog period resulting in a watchdog fault.
Figure 50
Watchdog operation diagram
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7.2.1
Buck converter watchdog
During start-up of the device, this watchdog monitors VDDB UVLO signal. When UVLO of VDDB is asserted, the
watchdog is cleared. If UVLO of VDDB is not asserted within the watchdog period (tWD_BUCK_T), the system will
stop (STOP state in the state machine is described in section Device Start-up and Functional States) and stay
disabled until a power cycle takes place. This watchdog can be used for safe start-up debugging. To enable this
feature WD_CFG2, bitfield WD_BK_DIS needs to be accessed.
7.2.2
General Purpose Watchdog
This watchdog timer can be configured to use different general purpose inputs (timer reset signal) via register
WD_INSEL. Possible inputs are:
•
EN_DRV: this is the default input. Due to connectivity between XMC1404 and 6EDL7141, it is not possible to
generate a clock in EN_DRV pin. Therefore, this input must not be used.
•
DVDD start-up: during start-up, if this input is selected, the watchdog will be cleared upon DVDD UVLO signal
assertion. If DVDD has not reached the correct value before the watchdog period, the DVDD regulator will
retry to start. The number of attempts to restart DVDD regulator when start-up fails, can be configured in
WD_DVDD _RSTRT_ATT. Additionally, the time between restarts attempts is set in bitfield
WD_DVDD_RSTRT_DLY
•
•
Charge pumps start-up: similarly, the start-up time of the charge pumps (both) can be monitored. The UVLO
signal of both VCCHS and VCCLS will clear the watchdog, otherwise, a fault will be reported. To select this
input, bitfield in WD_INSEL has to be set accordingly.
Status register SPI read action: in this configuration, the watchdog resets every time the FAULT_ST status
register is read via a SPI command. In this way, it checks that XMC1404 is active and that the SPI
communication is working adequately.
The general purpose watchdog timer needs to be enabled via WD_EN bitfield. Watchdog period programmed
din WD_TIMER_T.
Brake on General Purpose Watchdog Fault
The general purpose watchdog timer can be configured to trigger a brake event when the comparator trips.
This is activated in bitfield WD_BRAKE and is only possible when ‘Status register read’ is chosen as input. The
brake event can be configured to either brake the motor by shorting all high side MOSFETs, all low side
MOSFETs, alternate between those options or set all MOSFETs to high Z. This is explained in more detail in
sections 4.1.6. This is configured in bitfields BRAKE_CFG in PWM_CFG register.
7.2.3
Locked-Rotor Protection Watchdog Timer
MOTIX™ 6EDL7141 provides a locked or stalled rotor protection function by integrating a dedicated watchdog
timer. The rotor locked watchdog timer inputs are signals INLA, INLB and INLC. XMC1404 firmware needs to
provide the Hall sensor signal copy into those pins. This protection is only possible when using Hall sensor
based control schemes or 1PWM modes.
Locked or stalled rotor can occur in the event of a mechanical malfunction or excessive load torque that causes
the motor to stop rotating while enabled. The locked rotor function can be enabled by setting the bitfield
WD_RLOCK_EN to b’01.
A locked rotor condition is detected if the Hall pattern is maintained for tLOCKED period. The tLOCKED time is
configured via SPI (bitfield WD_RLOCK_T).
In order to increase robustness, an especial case of rotor locked detection is implemented. In some cases, the
motor stalls in a position in which the Hall sensors can still provide a cyclic or repeated toggling. In some cases
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vibration or bending of the motor can cause this effect, in other cases, the Hall sensors get stalled close to the
magnets. The internal logic detects this condition as rotor locked. An example is of such Hall sensor inputs
sequence that would report a fault is the following:
100, 101, 100, 101, 100, 101, …..
As soon as the locked rotor condition is detected, the device sets bitfields WD_FLT and RLOCK_FLT of the
FAULT_ST register to b'01. Upon detection of locked rotor condition the device enters high impedance state
(high Z). Additionally, nFAULT pin will be pulled down. XMC1404 can read this signal (internally connected) and
request a status update to the device or execute other corrective actions.
Hall Sensor Malfunction
In case of Hall sensor failure, the rotor locked protection can help to bring the motor to a safe state. The
malfunction of 2 or 3 Hall sensors (erroneous operation of the GPIOs emulating the Hall sensors) will cause a
rotor lock fault in 6EDL7141, however, a single Hall sensor failure cannot be detected as malfunction and does
not trigger a fault.
The rotor locked condition can be reset by toggling EN_DRV (switch off and on again).
Hall Comparators when PWM Signals are on Hold
If the PWM input signals generated by the controller stop switching while the rotor locked protection is
enabled, 6EDL7141 will recognize this as a failure and it will trigger the rotor locked protection after tLOCKED
period. In case this behavior is not desired, the user code in the controller that stopped the PWM switching
must be preceded by a command (SPI) to disable the rotor locked protection.
7.3
Gate Driver ADC Module-Analog to Digital Converter
MOTIX™ 6EDL7141 integrates an ADC based on SAR architecture with 7 bits resolution. This ADC can be used to
do redundant measurements to those executed in the XMC1404 controller or to measure gate driver related
voltages. XMC1404 can request the results of these internal measurements via SPI reads of ADC_ST register. The
ADC can measure following inputs during ACTIVE mode:
•
Automatically in ADC conversion sequence:
o
o
o
o
On die temperature sensor (see 7.3.2)
PVDD: supply voltage
VCCLS: low side gate driver supply
VCCHS: high side gate driver supply
•
Other (on demand) conversion inputs selected via bitfield ADC_OD_INSEL :
o
o
o
IDIGITAL: device digital section current consumption
DVDD: linear regulator output voltage
VDDB: buck converter output voltage
Those ADC inputs are continuously converted in sequence. After each conversion is finished, the result of the
conversion can be processed through integrated digital filters. These are moving average filters with
configurable number of samples. PVDD uses a dedicated filter (ADC_FILT_CFG_PVDD) while the rest share a
second filter (ADC_FILT_CFG). The complete architecture of the ADC module is depicted in Figure 51.
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Figure 51
ADC module block diagram
Table 24 summarizes the ADC inputs characteristic including the scaling factors. These scaling factors can be
used by XMC1404 firmware to calculate back the real analog values in volts, amperes or degree Celsius.
Table 24
ADC measurements overview
Measurement On demand Bitfield
conversion
Filter -
register
Scaling factor
ADC_FILT_CF
G_PVDD
PVDD
N
N
PVDD_VAL
TEMP_VAL
= (0.581 ∗ 푃ꢃꢇꢇ푉퐴ꢈ + 5.52) ꢃ
ADC_FILT_CF
G
Temperature
= (2 ∗ ꢅ퐸ꢉ푃_ꢃꢊꢋ − 94)℃
16
ADC_FILT_CF
G
VCCLS
N
VCCLS_VAL
= ꢃꢄꢄꢋꢌ_ꢃꢊꢋ ∗
ꢃ
127
16
ADC_FILT_CF
G
VCCHS
N
Y
VCCHS_VAL
ADC_OD_VAL
ADC_OD_VAL
= ꢃꢄꢄ퐻ꢌ_ꢃꢊꢋ ∗
ꢃ
127
Device current
ADC_FILT_CF
G
= (0.24 ∗ ꢊꢇꢄ_푂ꢇ_ꢃꢊꢋ)ꢍꢊ
(IPVDD
)
ꢇꢃꢇꢇ푇퐴푅퐺ꢎ푇
= ꢊꢇꢄ_푂ꢇ_ꢃꢊꢋ ∗
127
ADC_FILT_CF
G
DVDD
VDDB
Y
ꢃ
ꢃ
ꢃꢇꢇ퐵푇퐴푅퐺ꢎ푇
= ꢊꢇꢄ_푂ꢇ_ꢃꢊꢋ ∗
127
ADC_FILT_CF
G
Y
ADC_OD_VAL
For example, if DVDD voltage is the desired parameter, XMC1404 will read via SPI register ADC_OD_VAL. With
DVDD equal to 5V (IMD701A example) if the reading was 0x78=120 decimal value. XMC1404 controller can easily
calculate the following:
ꢇꢃꢇꢇ = ꢊꢇꢄ_푂ꢇ_ꢃꢊꢋ ∗ ꢏ.ꢐ푉 = 120 ∗ ꢏ.ꢐ푉 = 4.72ꢃ
(7)
ꢒ
ꢑ
ꢓꢑꢔ
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7.3.1
6EDL7141 ADC Measurement Sequencing and On Demand Conversion
In ACTIVE state, the ADC converts repeatedly in loop the following sequence of 6 measurements:
1. PVDD
2. Temperature sensor
3. PVDD
4. VCCLS
5. PVDD
6. VCCHS
This is shown in Figure 52. Results of those conversions will be placed in the dedicated result registers that can
be read via SPI by the XMC1404. PVDD result is reported in SUPPLY_ST register, VCCLS and VCCHS are reported
in register CP_ST and the temperature measurement is reported in register TEMP_ST.
Additional to the standard sequence, the user can select to have other signals converted on demand. Any of
this “on demand” conversion inputs, can be injected once in the standard sequence. This is done by selecting
the signal to be converted in bitfield ADC_OD_INSEL, and setting to ‘1’ the request bitfield ADC_OD_REQ.
Note:
The write of ADC_CFG bitfields must happen in a single SPI write. A write to a single bitfield will
overwrite the rest to the default value, so the full desired register value must be given in a single
write or via read-modify-write sequence.
If an on demand conversion is requested, the ADC waits to finish (End Of Conversion) any running conversion.
Then the requested on demand conversion is started. When the on demand conversion is finished, bitfield
ADC_OD_RDY is set. XMC1404 code can poll this bitfield to make sure the result register contains newest value
of the requested conversion. The result of the on demand conversion is located in bitfield ADC_OD_VAL and the
sequence continuous right where it was interrupted after the EOC of the on demand conversion. This is
illustrated in Figure 52.
Figure 52
ADC sequencing and interruption by extended conversion request of VDDB signal
7.3.2
Die Temperature Sensor
An especially useful ADC measurement is the temperature of the die. The temperature of the device can be read
via SPI by accessing bitfield TEMP_VAL in TEMP_ST register. The value is measured with a resolution of 2
degrees Celsius. Additionally, over-temperature warning and faults are implemented. In register SENSOR_CFG
(OTS_DIS), the over-temperature shut down protection can be disabled. The threshold values are provided in
Table 11. The occurrence of these faults can be detected by reading bitfields OTW_FLT and OTS_FLT.
According to Table 24, an example reading of 0x4A = 74 would convert into:
ꢅ푒ꢍ푝푒푟ꢆ푡푢푟푒 = ꢅ퐸ꢉ푃_ꢃꢊꢋ ∗ 2°ꢄ − 94°ꢄ = 74 ∗ 2°ꢄ − 94°ꢄ = 54°ꢄ
(8)
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8
MOTIX™ 6EDL7141 Protections and Faults Handling
MOTIX™ 6EDL7141 contains an extensive number of protections. These are:
•
Over-Current Protections (OCP) for:
o
o
o
DVDD linear regulator
Buck converter
Motor leg shunt OCP
•
Under-Voltage Lock Out (UVLO) protection for:
o
o
o
o
Gate driver supply voltage both high side and low side drivers
Supply voltage PVDD
DVDD linear regulator output voltage
Buck converter output voltage
•
•
•
•
•
DVDD linear regulator Over Voltage Lock Out (OVLO) protections
Rotor locked detection based on Hall sensor inputs
Configurable watchdog
Over-Temperature Shutdown (OTS) and Warning (OTW)
OTP memory fault.
An arbitration state machine, takes all the fault inputs from the specific fault blocks and decides which fault
needs to be serviced first in case several faults occur at same time (same clock cycle). Once a fault is
acknowledged, the system takes the specific action as shown in Table 25 and the arbitration round stops until
the fault is cleared.
The state machine is split in two main independent arbitration sections:
•
•
Supply faults (B0 to B4). B0 is highest priority.
Other faults (F0 to F7). The fault that happens first will be dealt first and others will be ignored until this fault
is removed. If more than one fault happens at the same time, then the one with the highest priority will be
processed. (F0 is highest priority).
The resultant actions from both sections are OR'ed on nFAULT.
Additionally to any possible actions like switching off PWM signal, status bits will be updated to inform
XMC1404 of any warning or/and fault occurrence. This is done regardless of priority and those status bits can be
read via SPI commands by the microcontroller in the system.
Note: It is highly recommended to understand faults reason by reading the status registers and clear faults as soon
as they occur so new events can be captured. This is done by writing register FAULTS_CLR via SPI
interface
Following registers provide information on the status of the device faults:
•
FAULT_ST: holds most of functional related faults. A fault might be triggered only after a number of
events of a malfunction. Status will immediately record the event information.
•
•
•
•
TEMP_ST: provides status on temperature warning and the temperature reading itself
SUPPLY_ST: reports on status of all supplies UVLO/OVLO and OCPs
FUNC_ST: status of OCP faults for each of current sense amplifiers, Hall sensors, wrong hall pattern.
OTP_ST: programming and reading of OTP related faults
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In order to clear faults the user has to write via SPI the bitfield CLR_FAULTS in FAULTS_CLR register. However,
to clear a latched fault, a write to CLR_LATCH register is required.
If ‘Motor leg shunt OCP’ fault is programmed to be latched the fault cannot be cleared until:
•
If in OCP counting mode (8, 16 periods) there is one whole PWM period without an OCP event or STANDBY
state is entered.
•
If in immediate trigger mode then it can be cleared after the fault is gone.
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Table 25
Name
6EDL7141 faults and protections table
Programma
nFAULT
report
Description
Latched
Active State
Prio
Action(s)
bility
Charge pump
low side UVLO
fault
DEV_
ACTIVE
F1 & F2
(shared)
•
External MOSFET outputs set to Hi-Z independently of
fault handling. Weak pulldown of all gate driver outputs
VCCLS
UVLO
-
N
Y
Y
Charge pump
high side UVLO
fault
DEV_
ACTIVE
F1 & F2
(shared)
•
External MOSFET outputs set to Hi-Z independently of
fault handling. Weak pulldown of all gate driver outputs
VCCHS
UVLO
-
-
N
N
All states after
DVDD ok
(after
DVDD
OVLO
DVDD OVLO
fault
Y
Y
B1
B3
No action. XMC1404 to perform user action
No action. XMC1404 to perform user action
STANDBY)
All states after
DVDD ok
(after
DVDD
OCP
Threshold
level
DVDD OCP fault
N
STANDBY)
•
External MOSFET outputs set to Hi-Z. Weak pulldown of
all gate driver outputs
Y
•
•
•
Waits for power cycle (CE pin low and high)
Buck converter continues operation
When DVDD UVLO happens the functional state machine
changes from DEV_ACTIVE to DVDD_STOP. Please refer to
section Device Start-up and Functional Statesfor details.
From the application perspective, this faults is highest
priority. Requires a power cycle (CE toggle)
(howeve
r is
nFAULT
supplied
by
N(requires
power
cycle-CE
toggle)
All states after
BUCK_
START
DVDD
UVLO
DVDD UVLO
fault
B0 and
F0
-
-
DVDD)
All states after
DVDD ok
(after
Buck Converter
Over Current
Protection
•
No action. XMC1404 to perform user action. Protection is
blanked during start-up of charge pumps
BUCK
OCP
N
Y
B2
STANDBY)-
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Programma
bility
nFAULT
report
Name
Description
Latched
Active State
Prio
Action(s)
Fault blanked
during charge
pump start
Motor
Current sense
Threshold
level, count ble-
on number
of trips,
reaction,
PWM
Programma
Y
DEV_
ACTIVE
F4
•
•
PWM truncation if configured.
If fault is configured as “Latched” then: sets driver into Hi-
Z. Weak pulldown of all gate driver outputs.
Brake as defined in PWM_CFG register when
CS_OCP_BRAKE register enabled. Fault latched if braking
active
leg shunt amplifier Over
OCP
[2:0]
Current
Protection for
each phase
Latched if
brake on
OCP is
•
active
truncation
•
•
External MOSFETs outputs set to High Z. Weak pulldown
of all gate driver outputs
Requires toggle of EN_DRV to re-start normal operation
again
Locked rotor
watchdog
overflow
DEV_
ACTIVE
Locked
rotor
Timing
Y
Y
F5
If input:
−
EN_DRV - Hi-Z. Weak pulldown of all gate driver
outputs
Buck input- No action required from user or device.
If charge pump input – nFAULT reported. Driver won’t
Programma Y (with
ble-Latched input
Watchdog timer Timing,
Depending on
input, either
START-UP or
Watch
dog
timers
−
−
overflow.
reaction.
Depending
on input
if brake on
watchdog
fault is
EN_DRV
only,
otherwis DEV_ACTIVE
e not)
F6
F3
Several inputs
programmable
start-up.
−
Others: brake as defined in PWM_CFG register when
WD_BRAKE register enabled. Always latched if braked
enabled
enabled
OTS
Over
-
Y
Y
DEV_
ACTIVE
•
External MOSFET outputs set to Hi-Z. Weak pulldown of
all gate driver outputs
Temperature
Shutdown
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Programma
bility
nFAULT
report
Name
Description
Latched
Active State
Prio
Action(s)
OTW
Over
Temperature
Warning
-
N
N (only
status
register
report)
DEV_
ACTIVE
F8
No action. XMC1404 to perform user action
OTP read fault
or OTP user
programming
error
•
•
External MOSFETs outputs set to Hi-Z
Weak pulldown of all gate driver outputs
OTP
Fault
-
Y
Y
All states
F7
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9
MOTIX™ 6EDL7141 Programming-OTP and SPI interface
Programming of 6EDL7141 features in MOTIX™ IMD70xA requires accessing internal registers via SPI interface
shown in Figure 53.
The configuration of 6EDL7141 features, including gain of amplifiers, driving voltage for gate drivers or fault
reactions, is stored in registers while the device is active. The configuration of those functions can be changed
during run time operation via SPI commands. These registers are volatile memory cells and therefore, its
information will be lost every time the power supply is removed from the device.
For this reason, 6EDL7141 integrates an OTP NVM (One Time Programmable Non-Volatile Memory) that stores a
given default configuration even when power supply is not available. Initially the device is programmed with
the default register settings provided in section 11. During startup phase of the device (see state machine
flowchart in Figure 58), the configuration in the OTP will be copied or mirrored into registers. These registers
are the ones that govern the actual behavior of the device. This is shown in Figure 53.
Figure 53
6EDL7141 programming overview
In case the default (“out of the fab”) configuration of the device stored in OTP is not the desired one, the
designer can select a different configuration for its application and store it indefinitely in the OTP memory
(hard-copy). See section 9.1.1 for detailed procedure. This action can be done only once. A second write to the
OTP is not possible. However, configurations can be overwritten on volatile registers after start-up via SPI
commands as mentioned above.
The user configuration can be tracked thanks to a software ID bitfield -USER_ID- located in OTP_PROG register.
Note:
It is therefore recommended that every writing action to the registers is followed by a confirmation
read to ensure that written and read data in registers match and thus confirming correct
programming.
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9.1.1
MOTIX™ 6EDL7141 OTP User Programming Procedure: Loading Custom
Default Values
The OTP is used for user configuration storage. The OTP module implements a double error correction, plus
one additional error detection when programming it.
OTP programming must only occur in a controlled environment. This requires the user to ensure that
programming happens at the correct supply voltage, this is PVDD> PVDDOTP_PROG. Also the temperature must be
below TOTP_PROG. Internally both parameters are monitored. This means that if programming is attempted
outside of these parameters it will not be started. If this blocking occurs, then bitfield OTP_PROG_BLOCK will
be set to ‘1’ to indicate that one of the parameter is outside of the required range. Default values (as given in
bold in section 11.4) will be used after start-up in such situation. Further programming attempts are possible.
OTP_PROG_BLOCK will be reset either when the programming finishes successfully or after a power down.
Following programming steps should be performed to write OTP with a specific configuration:
1. Start device into STANDBY mode (EN_DRV< VEN_DRV_TH
)
2. Write registers to the desired default values via SPI write commands
3. Program these values into OTP using OTP_PROG bitfield
a. If the temperature is higher than TOTP_PROG or PVDD> PVDDOTP_PROG, then programming does not start
and OTP_PROG_BLOCK is set to ‘1’. Conditions might be modified and the programming can be
attempted again. If the programming fails twice, the device will be blocked signaled by
OTP_USED=b’1, OTP_PASS = b’0
b. If temperature and PVDD values are in range, programming starts, copying register parameters into
the OTP memory. This can only be done once.
4. (Recommended) Check if OTP programming succeeded via bitfields OTP_USED and OTP_PASS or
OTP_PROG_FAIL:
a. If the programming of the OTP failed, then the device will be locked until a power cycle (CE pin
pulled down and up) takes place. Signaled by OTP_USED=b’1 and OTP_PASS = b’0 or simply
OTP_PROG_FAIL =b’1. Further programming of OTP is not possible. Memory content is considered
corrupted and therefore the part should be discarded.
b. If programming succeeded, then normal function will continue. This is signaled by OTP_USED = b’01
and OTP_PASS = b’01 or simply OTP_PROG_FAIL = b’0. It is recommended to perform a power cycle
(CE pin pulled down and up) for new values to take effect after a successful programming
Trying to write an already programmed OTP will be ignored.
An OTP programming failure (wrong copy of registers into OTP memory) will force the device to enter STOP
state during read out (see Figure 58). In such case, the fault is reported on nFAULT pin and XC1404 can perform
a status read of 6EDL7141 to provide status of memory by reading bitfields OTP_USED, OTP_PASS, or
OTP_PROG_FAIL, and OTP_PROG_BLOCK. The OTP possible statuses are described in Table 26.
If the user chooses to program OTP during start-up of the XMC1404 software, this should check each time that
OTP_USED = b’01 before programming again. Otherwise incorrect programming could occur.
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Table 26
OTP programming status
OTP_ OTP_ OTP_PRO OTP_PRO Status Description
USED PASS G_BLOCK G_FAIL
Device status
Non-programmed device
0
0
0
0
Default values used
User programming was successful.
Upon start-up, the newly programmed
default values will be loaded into
registers for custom configuration
Successful programming
of OTP
1
1
X
X
Programming blocked
due to PVDD or
temperature conditions
Part can be reprogrammed once
condition are within limits
0
0
1
0
Programming started but
failed due to PVDD or
temperature conditions
1
1
0
0
1
0
1
1
Part must be discarded
Part must be discarded
Programming started but
failed due to OTP issue
9.1.2
MOTIX™ 6EDL7141 SPI Communication
All communication between XMC1404 and 6EDL7141 happens through the internal connection between both
devices as shown in Interconnects Pin Description table. The SPI module in 6ELD7141is used to program the
configuration registers and therefore to command the device for example to change settings or program OTP
memory.
6EDL7141 SPI module is based on a 4-pin configuration. Data sampling happens during the falling edge of the
SPI clock signal. This protocol can easily be implemented in XMC1404 USIC peripheral when configuring it as
SSC channel. User must ensure that XMC1404 is properly configured according following write and read
protocols.
All communication happens in a 24 bit length shift register.
•
•
•
7 bit address
16 bit data byte
1 bit command
Data is shifted in with MSB first.
Two commands are defined:
•
•
1 – Register write
0 – Register read
Figure 54 and Figure 55 show respectively write and read operations with SPI interface.
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Figure 54 SPI write operation
Figure 55 SPI read operation
9.1.2.1
SPI Communication Example
If for example, user wants to write new values TDRIVE1 = 50ns (0x01) and TDRIVE2 = 2540ns (0xFE), to register
TDRIVE_SRC_CFG (address 0x19), then the content of the register needs to be 0xFE01 by collating TDRIVE2 and
TDRIVE1 values. The microcontroller then needs to write following command in the SPI bus (SDI signal) once
nSCS signal is pulled down:
Binary: b 1001 1001 1111 1110 0000 0001
Hexadecimal: 0x99 FE 01
If after write, a read is necessary, the following sequence must be applied by the microcontroller. This will read
TDRIVE_SRC_CFG register by writing SDI signal:
Binary: b 0001 1001 ---- ---- ---- ----
Hexadecimal: 0x19 -- --
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9.1.2.2
XMC1404 SPI Configuration Recommendation
In this section it is described the recommended configuration of XMC1404 USIC channel to communicate with
6EDL7141 interface. For this purpose, XMC Low Level Drivers have been used. APIs supported in by that library
can be identified by the prefix “XMC_”, like XMC_GPIO_Init(). Three APIs are shown here:
•
•
•
USIC SPI channel Initialization
Read command
Write command
USIC SPI channel Initialization
/****************************************************************************
* DATA STRUCTURES
****************************************************************************/
uint8_t error_SPI;
/* SPI configuration structure */
XMC_SPI_CH_CONFIG_t spi_config =
{
.baudrate = SPI_BAUD_RATE,
.bus_mode = XMC_SPI_CH_BUS_MODE_MASTER,
.selo_inversion = XMC_SPI_CH_SLAVE_SEL_INV_TO_MSLS,//Slave select active
low
.parity_mode = XMC_USIC_CH_PARITY_MODE_NONE
};
/* GPIO SPI TX pin configuration */
XMC_GPIO_CONFIG_t tx_pin_config =
{
.mode = XMC_GPIO_MODE_OUTPUT_PUSH_PULL_ALT9 //Pin selection ALT9
};
/* GPIO SPI DX pin configuration */
XMC_GPIO_CONFIG_t dx_pin_config =
{
.mode = XMC_GPIO_MODE_INPUT_TRISTATE
};
/* GPIO SPI SELO pin configuration */
XMC_GPIO_CONFIG_t selo_pin_config =
{
.mode = XMC_GPIO_MODE_OUTPUT_PUSH_PULL_ALT8, //Pin selection ALT8
};
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/* GPIO SPI SCLKOUT pin configuration */
XMC_GPIO_CONFIG_t clk_pin_config =
{
.mode = XMC_GPIO_MODE_OUTPUT_PUSH_PULL_ALT8, //Pin selection ALT8
};
/* API to initialize USIC SPI peripherals */
void spi_master_init(XMC_USIC_CH_t * const channel)
{
/* Initialize GPIO */
XMC_GPIO_Init(MOSI_PIN, &tx_pin_config);
XMC_GPIO_Init(MISO_PIN, &dx_pin_config);
XMC_GPIO_Init(SELO_PIN, &selo_pin_config);
XMC_GPIO_Init(SCLK_PIN, &clk_pin_config);
/* Initialize SPI master*/
XMC_SPI_CH_Init(channel, &spi_config);
XMC_SPI_CH_SetWordLength(channel, SPI_WORD_LENGTH);
XMC_SPI_CH_SetFrameLength(channel, SPI_FRAME_LENGTH);
XMC_SPI_CH_SetBitOrderMsbFirst(channel);
XMC_SPI_CH_EnableSlaveSelect(channel, XMC_SPI_CH_SLAVE_SELECT_0); //Falling
sclk sampling and no polarity inversion
XMC_SPI_CH_ConfigureShiftClockOutput(channel,
XMC_SPI_CH_BRG_SHIFT_CLOCK_PASSIVE_LEVEL_0_DELAY_DISABLED,
XMC_SPI_CH_BRG_SHIFT_CLOCK_OUTPUT_SCLK); //Slave select is active low to
communicate with 6EDL7141
XMC_SPI_CH_SetSlaveSelectPolarity(channel,
XMC_SPI_CH_SLAVE_SEL_INV_TO_MSLS);
/* Initialize FIFO */
XMC_USIC_CH_RXFIFO_Configure(channel, 40, XMC_USIC_CH_FIFO_SIZE_8WORDS, 2);
//receive from SPI slave: limit is 1, when FIFO is full with 2 word and a 3nd
is received, the event happens.
//this is used in main to while until 3 words are received
XMC_USIC_CH_TXFIFO_Configure(channel, 32, XMC_USIC_CH_FIFO_SIZE_8WORDS, 0);
/* Configure input multiplexer */
XMC_SPI_CH_SetInputSource(channel, XMC_SPI_CH_INPUT_DIN0,
USIC1_C1_DX0_P0_0); //P0.0 DX0A, 6EDL_SPI_LINK SPI pin assignment
/* Start operation. */
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XMC_SPI_CH_Start(channel);
error_SPI = 0;
}
Read Command
/*The RegAddr is the address of register to read. Data parameter is a pointer
to store the two bytes of data read from the register */
uint16_t Read_Word_16b(uint8_t RegAddr)
{
XMC_USIC_CH_RXFIFO_Flush(SPI_MAS_CH);
SPI_MAS_CH->IN[0] = RegAddr & REG_READ;
SPI_MAS_CH->IN[0] = 0x00;
SPI_MAS_CH->IN[0] = 0x00;
uint32_t timeout_counter = 0;
while ((XMC_USIC_CH_RXFIFO_GetEvent(SPI_MAS_CH) &
XMC_USIC_CH_RXFIFO_EVENT_STANDARD) == 0) /*wait for received data /2 words*/
{
if (++timeout_counter > SPI_TIMEOUT)
{
error_SPI = 1;
break;
}
};
XMC_USIC_CH_RXFIFO_ClearEvent(SPI_MAS_CH,XMC_USIC_CH_RXFIFO_EVENT_STANDARD);
SPI_MAS_CH->OUTR; //data read of invalid data
uint8_t data_high = SPI_MAS_CH->OUTR; //data read of MSB
uint8_t data_low = SPI_MAS_CH->OUTR; //data read of LSB
return ((data_high << 8) + data_low);
}
Write Command
/* To write data to register via SPI channel.
The RegAddr is the address of register to write to.
Data parameter is a pointer which stored the two bytes of data written to
the register */
void Write_Word_16b(uint8_t RegAddr, uint16_t data)
{
XMC_USIC_CH_RXFIFO_Flush(SPI_MAS_CH);
SPI_MAS_CH->IN[0] = RegAddr | REG_WRITE;
SPI_MAS_CH->IN[0] = (uint8_t)(data >> 8);
SPI_MAS_CH->IN[0] = (uint8_t)data;
uint32_t timeout_counter = 0;
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while ((XMC_USIC_CH_RXFIFO_GetEvent(SPI_MAS_CH) &
XMC_USIC_CH_RXFIFO_EVENT_STANDARD) == 0) //wait for received data /2 words
{
if (++timeout_counter > SPI_TIMEOUT)
{
error_SPI = 1;
break;
}
};
XMC_USIC_CH_RXFIFO_ClearEvent(SPI_MAS_CH,XMC_USIC_CH_RXFIFO_EVENT_STANDARD);
SPI_MAS_CH->OUTR; //data read to clear buffer
SPI_MAS_CH->OUTR; //data read to clear buffer
SPI_MAS_CH->OUTR; //data read to clear buffer
}
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Device Start-up and Functional States
10
Device Start-up and Functional States
10.1
MOTIX™ 6EDL7141 Power Supply Start-up
6EDL7141power supply section start-up can be divided in two main periods:
•
•
Power supply start-up: initiated by CE rise, leads to ramp up of VDDB and DVDD rails.
Gate Driver and CSAMP start-up: begins with EN_DRV rise and results in charge pumps ramp up and current
sense amplifiers activation
10.1.1
Power Supply System Start-up
Given a steady battery supply voltage (PVDD), the input pin CE will control the startup of the power supply
system. Figure 56 shows graphically the ramp up of buck converter voltage once CE voltage goes above VCE_TH_R
value. If external filter capacitor is too large, the ramp up time might be exceeding the values provided in Table
11 (tVDDB_SFT_START). The integrated watchdog can be enabled to monitor and debug the start-up of VDDB, DVDD or
charge pumps.
Soft-start for the buck converter is automatically implemented using an integrated DAC for generating the
target reference. Once VDDB has reached its UVLO voltage, analog programming starts. This initiates a period
of tAN_T duration in which CS_GAIN pin is read internally. The analog programming can be disabled via OTP
programming, therefore reducing the start-up time.
After these analog programming period(s) have elapsed, another OTP programmable delay
(DVDD_TON_DELAY) is inserted (tDVDD_TON_DLY) before the DVDD voltage starts ramping up. Longer delays allow
the buck converter voltage to stabilize before the DVDD starts charging. If faster start-up time is required, the
delay can be shortened taking into consideration the buck output voltage and the external components used
(LBUCK, CBUCK). DVDD will ramp up in a configurable time (DVDD_SFTSTART). Tuning of this value can help
ensuring proper start-up.
10.1.2
Gate Driver and CSAMP Start-up
Once DVDD is up and stable, XMC1404 firmware starts execution until it decides to enable the gate driver.
EN_DRV pin needs to be set above VEN_DRV_TH value to enable the driver section. Before this, no PWM signal will
transfer to the gate of the MOSFETs. Once EN_DRV is set above VEN_DRV_TH, both low side and high side charge
pumps ramp up to the target value PVCC. This time will depend on the different configurations (capacitors,
charge pump frequency, PVCC voltage) as explained in 4.5.
The high side charge pump will start after enough voltage is built in the low side charge pump. After both high
side and low side charge pumps UVLOs are reached, the PWM path is activated and the gate driver can output
signals to the power MOSFET.
Note:
Depending on timing of PWM send to inputs and charge pump capacitor values, the gate driver
could start driving the MOSFETs while the charge pumps are not fully at target voltage if the PWM
signal is activated early. User can delay the start of PWM signals until charge pumps are fully
charged if this is required
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Figure 56 Start-up behavior of supply voltages at steady PVDD supply. EN_DRV and CE_EN functionality.
DVDD_SFTSTRT is an SPI programmable parameter
If CE is generated from PVDD, for example via a voltage divider as shown in Figure 61, the start-up behavior will
follow the one in Figure 57 or similar. In such case, it is important to notice that the device will not start –i.e. the
buck converter will not start switching - until both PVDD UVLO is released and the CE rising voltage thresholds
(VCE_TH_R) are crossed, as can be seen in flowchart in Figure 58. The order of CE and PVDD can swap with similar
results.
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Figure 57
Start-up behavior detail when PVDD is ramping up and CE is created with a voltage divider
from PVDD. Device will only turn on after events 1 and 2 occur, starting up the buck
converter controller
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10.2
Device Functional States
The functionality of the device is governed by a state machine. A flowchart of this state machine is shown in
Figure 58.
Figure 58
Flowchart diagram for power states of device
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Following main states and substates can be considered for IMD70xA:
Off State
•
DEV_OFF - This state is the default state when in reset.
Power Supply Start-up States
•
•
•
POWER_START_UP, OTP_READ - In this state voltage in PVDD is ramping up and checked by the 6EDL7141.
Once ok, the OTP memory in 6EDL7141 is read. This is done before enabling any further blocks to ensure
configuration is known. If a fault is signaled by the OTP block then the STOP state will be entered.
BUCK_START - The buck converter is enabled in this state and the VDDB needs to be correct before leaving
this state. If the VDDB has not reached the target voltage in a certain time, then the buck will be shut down
and the device set in the STOP state.
CS_GAIN_READ - The device will sense pin CS_GAIN (optionally programmable) to program the current sense
amplifier gain if analog programming is selected. This is, if CS_GAIN_ANA is set to ‘0’ then the CS gain will be
set by the register CS_GAIN. In case of digital programming the state is skipped. In IMD70x gain of current
sense amplifiers must be set digitally via SPI commands, which will skip this state in the state machine.
•
•
DVDD_START – at this point, once the buck converter output is stable, the linear voltage regulator for DVDD is
ramped up according the start-up delay and soft start programming. At the end of this state, DVDD is at target
voltage and stable. With this, the start-up procedure of the device finishes and enters a wait state until
EN_DRV signal arrives from a XMC1404. This will start the standby section.
STOP - If this state is entered it is because a serious fault with either the buck converter DVDD start-up. The
device will not operate until a power cycle or EN_DRV toggle takes place. SPI cannot be used during this state.
XMC1404 Hardware Controlled Start-up:
This state is entered automatically after power up of the microcontroller. This part is generic and it ensures
basic configuration of the controller internal circuitry. The hardware setup needs to ensure fulfillment of
requirements specified in the Absolute max table in order to enable reliable start-up of the microcontroller
before control is handed over to the user software/application. The sequence where boot code gets executed
is considered a part of the hardware controlled phase of the startup sequence. For details of the setup
requirements, please refer to XMC1400 Reference Manual.
XMC1404 Software Controlled Start-up:
The software controlled startup phase is the part where the application specific configuration gets applied
with user software. It involves several steps that are critical for proper operation of the microcontroller in the
application context and may also involve some optional configuration actions in order to improve system
performance and stability in the application context.
Power-up of the microcontroller gets performed by applying DVDD supply (for details of the supply
requirements, please refer to XMC1400 Reference Manual).The connection between pin 3 (DVDD input) and
pins 23 and 56 (DVDD output/input) must be done at the PCB level to ensure XMC is properly powered, there
is no internal connection internally in IMD70xA.
When XMC supply voltage reaches a stable threshold level, the power-on reset is released.
Next, after the on-chip oscillators in XMC generate a stable clock output, the system reset is released
automatically and the Start-up Software (SSW) code starts to run in the controller. The system reset can be
triggered from various sources like software controlled CPU reset register or a watchdog time-out-triggered
reset.
After reset release, internal XMC clock signals MCLK and PCLK are running at 8MHz and most of the
peripherals’ clocks are disabled except for CPU, memories and PORT. It is recommended to disable the clock
of the unused modules in order to reduce power consumption.
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Start-up Software (SSW) execution: after the reset is de-asserted, CPU starts to execute the SSW code from
the ROM memory. To indicate the start of the SSW execution, the pull up device in P0.14 is enabled. Pull up
device is disabled during reset. SSW reads the Boot Mode Index (BMI) stored in Flash and decide the startup
modes elected by the user. The Boot Mode Index is 2 Byte value stored in Flash and holding information
about start-up mode and debug configuration of the device. For more details about the various startup
modes and handling of BMI, please refer to XMC1400 Reference Manual.
To handle the initial hardfault error during the SSW execution, SSW installs “jump to itself” instruction at
SRAM location 2000’000CH as temporary HardFault handler – until the user code installs its own. It is installed
upon master reset only. During SSW execution, the SRAM area between 2000’00C0H and 2000’0200H is
reserved for usage by XMC1404 SSW, therefore the user software should not store in this area data which
must be preserved throughout (non-power) resets.
GATE_DRIVE_STANDBY
•
CHARGE_PUMP_START - The charge pumps are enabled. If target voltages are reached, the device moves
to DEV_ACTIVE.
ACTIVE
•
DEV_ACTIVE (or ACTIVE)
In this state the driver is ready to be used. The PWM path is enabled. If EN_DRV signal goes low during active
the device turns off both charge pumps and disables the PWM path by going into the STANDBY section.
•
DVDD_STOP - This state is entered from states after DVDD has been powered and DVDD rail fails. Device stops
operation and requires a CE toggle or power cycle to restart. Buck converter and ADC remains active.
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Register Map
11
Register Map
11.1
XMC1404 Registers
For the configuration registers of XMC1404 microcontroller, refer the specific sections fully described in latest
XMC1404 reference manual at Infineon website (www.infineon.com). At the time of creation of this document,
latest version can be found here: XMC1400 Reference Manual.
11.2
MOTIX™ 6EDL7141 Smart Gate Driver Register Map
Table 27 shows a complete list of 6EDL7141 registers accessible via SPI interface. Registers are explained in
detail in this section.
Table 27
Register map overview
Long Name
Short Name
FAULT_ST
TEMP_ST
Offset Address Page Link
Fault and warning status
00H
01H
02H
03H
04H
05H
06
117
118
119
120
121
122
122
123
123
124
126
127
128
129
130
131
133
133
134
136
Temperature status
SUPPLY_ST
FUNC_ST
Power supply status
Functional status
OTP_ST
OTP status
ADC_ST
ADC status
CP_ST
Charge pumps status
DEVICE_ID
FAULT_CLR
SUPPLY_CFG
ADC_CFG
Device ID
07H
10H
11H
12H
13H
14H
15H
16H
17H
18H
19H
1AH
1BH
1CH
Fault clear
Power supply configuration
ADC configuration
PWM_CFG
SENSOR_CFG
WD_CFG
PWM configuration
Sensor configuration
Watchdog configuration
Watchdog configuration 2
Gate driver current configuration
Pre-charge gate driver current configuration
Gate driver sourcing timing configuration
Gate driver sinking timing configuration
Dead time configuration
Charge pump configuration
WD_CFG2
IDRIVE_CFG
IDRIVE_PRE_CFG
TDRIVE_SRC_CFG
TDRIVE_SINK_CFG
DT_CFG
CP_CFG
136
137
139
141
CSAMP_CFG
CSAMP_CFG2
Current sense amplifier configuration
Current sense amplifier configuration 2
1DH
1EH
OTP_PROG
OTP program
1F
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Register Map
11.3
MOTIX™ 6EDL7141 Registers Programmability
The programmable registers in 6EDL7141 can be programmed at any time after SPI interface is active, however,
some of the bitfield changes will not have an effect until certain conditions occur. This is to protect from wrong
behaviors or to avoid glitches in the operation. Three categories are defined:
1. Always programmable: programming these bitfields will have an effect immediately after programming in
any state of the device. The effect can be synchronized with PWM or braking events for some cases.
2. Standby programmable: programming these bitfields will have an effect only when EN_DRV level is low. If
programmed when EN_DRV is high, the register will show the new value, but effect will not be applied until
EN_DRV is pulled down. This is to avoid system malfunctions. Therefore these registers are recommended
to be programmed before EN_DRV is activated.
3. OTP only: programming these bitfields will have an effect only if programmed in OTP and after device new
power up (PVDD). These are settings affecting the start-up of the device, namely bitfields whose effect takes
place even before DVDD ramps up, therefore must be burned into OTP to be effective on next power up.
As an example, if during ACTIVE state a write happens to a ‘Standby’ value, the value will be written and reads
to this register will return the written value, however, the value is not (shadow) transferred to actual effective
register until the device state machine goes into STANDBY state.
Table 28 provides a categorization for every configuration of the device (‘w’ type bitfield)
Table 28
Register programmability
Register Name
Bitfield Name
PVCC_SETPT
Programmability
SUPPLY_CFG
Standby
CS_REF_CFG
Standby
DVDD_OCP_CFG
DVDD_SFTSTRT
BK_FREQ
Always
OTP only
Standby
DVDD_TON_DELAY
CP_PRE_CHARGE_EN
ADC_OD_REQ
ADC_OD_INSEL
ADC_EN_FILT
ADC_FILT_CFG
ADC_FILT_CFG_PVDD
PWM_MODE
PWM_FREEW_CFG
BRAKE_CFG
OTP only
Standby
ADC_CFG
PWM_CFG
Always – no OTP field, just register
Always – no OTP field, just register
Always – no OTP field, just register
Always
Always
Standby
Always
Always
Standby
Always
Always
Always
Standby
Standby
Standby
PWM_RECIRC
HALL_DEGLITCH
OTS_DIS
SENSOR_CFG
WD_CFG
CS_TMODE
WD_EN
WD_INSEL
WD_FLTCFG
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Register Map
Register Name
Bitfield Name
WD_TIMER_T
WD_BRAKE
WD_EN_LATCH
WD_DVDD_RSTRT_ATT
WD_DVDD_RSTRT_DLY
WD_RLOCK_EN
WD_RLOCK_T
WD_BK_DIS
IHS_SRC
Programmability
Standby
WD_CFG2
Standby
Standby
Standby
Standby
Always
Always
OTP only
IDRIVE_CFG
Always
IHS_SNK
Always
ILS_SRC
Always
ILS_SNK
Always
IDRIVE_PRE_CFG
I_PRE_SRC
I_PRE_SNK
I_PRE_EN
Always
Always
Always
TDRIVE_SRC_CFG
TDRIVE_SINK_CFG
DT_CFG
TDRIVE1
Always
TDRIVE2
Always
TDRIVE3
Always
TDRIVE4
Always
DT_RISE
Always
DT_FALL
Always
CP_CFG
CP_CLK_ CFG
CP_CLK_ SS_DIS
CS_GAIN
Always
Standby
CSAMP_CFG
Always – recommended to stop PWM first
CS_GAIN_ANA
Standby (change to digital mode)-change to
analog mode only possible if written in OTP –
do not change value, analog programming
not possible in IMD70xA
CS_EN
Always
CS_BLANK
Always – recommended to stop PWM first
CS_EN_DCCAL
CS_OCP_DEGLITCH
CS_OCPFLT_CFG
CS_OCP_PTHR
CS_OCP_NTHR
CS_OCP_LATCH
CS_MODE
Standby
Standby
Standby
Always
CSAMP_CFG2
Always
Standby
Standby
Standby
Always
CS_OCP_BRAKE
CS_TRUNC_DIS
VREF_INSEL
Standby
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Register Map
Register Name
Bitfield Name
CS_AZ_CFG
Programmability
Always
CS_NEG_OCP_DIS
OTP_PROG
Always
OTP_PROG
Standby (programming of OTP only in
Standby)
USER_ID
Always
Table 29
Register read/write coding description
Code
res
r
Access type
No access
Read
Description
Reserved
Read only. A write produces no action
Read or write by user
rw
w
Read/Write
Write
Write only. A read returns 0
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Register Map
11.4
MOTIX™ 6EDL7141 Register Map
Faults Status Register
If the status of one of the bits switches to value b’1, the corresponding fault/warning has occurred. To clear the
fault use the clear faults bit in the FAULTS_CLR register
FAULT_ST
Address:
00H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
DVDD_ DVDD DVDD
OV_FL _UV_ _OCP
OTP_ WD_ RLOC OTW_ OTS_ BK_OCP
FLT FLT K_FLT FLT FLT _FLT
CP_
FLT
0
CS_OCP_FLT
T
FLT _ FLT
res
r
r
r
r
r
r
r
r
r
r
r
Field
Bits
Type
Description
CS_OCP_FL
T
2:0
r
Current sense amplifier OCP fault status
OCP (shunt amplifier OCP) fault status
bXX0: No fault on phase A
bXX1: Fault on phase A
bX0X: No Fault on phase B
bX1X: Fault on phase B
b0XX: No Fault on phase C
b1XX: Fault on phase C
CP_ FLT
3
r
Charge pumps fault status
Charge pump low side and high side combined fault status
b0: No fault has occurred
b1: A fault has occurred
DVDD_OCP_
FLT
4
5
r
r
DVDD OCP (Over-Current Protection) fault status
DVDD linear voltage regulator Over-Current-Protection fault status
b0: No fault has occurred
b1: A fault has occurred
DVDD UVLO (Under-Voltage Lock-Out) fault status
DVDD UVLO fault status
DVDD_UV_F
LT
b0: No fault has occurred
b1: A fault has occurred
DVDD_OV_F
LT
6
7
r
r
DVDD OVLO (Over-Voltage Lock-Out)fault status
DVDD OVLO fault status
b0: No fault has occurred
b1: A fault has occurred
BK_OCP_FL
T
Buck OCP fault status
Buck Over-Current-Protection fault status
b0: No fault has occurred
b1: A fault has occurred
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Register Map
OTS_FLT
8
r
r
r
Over-temperature shutdown fault status
Over temperature shutdown event status
b0: No fault has occurred
b1: A fault has occurred
OTW_FLT
9
Over-temperature warning status
Over temperature warning signal status
b0: No warning signal has occurred
b1: A warning signal has occurred
RLOCK_FLT 10
Locked rotor fault status
Locked Rotor fault status using hall sensors
b0: No fault has occurred
b1: A fault has occurred
WD_FLT
11
r
Watchdog fault status
Watchdog status
b0: No fault has occurred
b1: A fault has occurred
OTP_FLT
0
12
r
OTP status
OTP (One Time Programmable) memory fault status
b0: No fault has occurred
b1: A fault has occurred
Reserved
15:13
res
A read always returns 0
Temperature Status Register
This register contains the 6EDL7141 die temperature value
TEMP_ST
Address:
01H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
0
TEMP_VAL
res
r
Field
Bits
Type
Description
Temperature reading
TEMP_VAL
6:0
r
Temperature value in step of 2 degrees
b000000: -94 degrees Celsius
..... every 2 degrees Celsius
b1111111: 160 degrees Celsius
Reserved
A read always returns 0
0
15:7
res
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Register Map
Power Supply Status Register
This registers contains status of power supply related blocks
SUPPLY_ST
Address:
02H
Power Supply Status
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
VDDB_ VDDB_ DVDD DVDD_VCCHS_VCCLS
OVST UVST _OVST UVST UVST _UVST
0
PVDD_VAL
res
r
r
r
r
r
r
r
Field
Bits
Type
Description
VCCLS_UVS
T
0
r
Charge Pump low side UVLO status
b0: Below threshold
b1: Above threshold
VCCHS_UVS
T
1
2
3
4
5
r
r
r
r
r
r
r
Charge Pump high side UVLO status
b0: Below threshold
b1: Above threshold
DVDD UVLO status
b0: Below threshold
b1: Above threshold
DVDD_UVST
DVDD_OVST
VDDB_UVST
VDDB_OVST
PVDD_VAL
0
DVDD OVLO (Over-Voltage Lock-Out) status
b0: Below threshold
b1: Above threshold
VDDB UVLO status
b0: Below threshold
b1: Above threshold
VDDB OVLO status
b0: Below threshold
b1: Above threshold
12:6
PVDD ADC result reading value
This bitfields holds the analog to digital conversions value for PVDD
input voltage
15:13
Reserved
A read always returns 0
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Register Map
Functional Status Register
Status of various functional signals.
FUNCT_ST
Address:
03H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
DVDD_ HALLP
ST OL_ST
0
CS_GAIN_ST
HALLIN_ST
res
r
r
r
r
Field
Bits
Type
Description
Hall sensor inputs status -
HALLIN_ST
2:0
r
HALL sensor input pins status for each phase.
b0: signal is low
b1: signal is high
bit 0: Phase A
bit 1: Phase B
bit 2: Phase C
HALLPOL_S
T
3
4
r
r
Hall sensor polarity equal indicator
Status bit that indicate if all phases of the hall sensors have the same
polarity at the same time.
b0: Hall sensors have different polarity
b1: Hall sensors have the same polarity
DVDD_ST
DVDD set point status
DVDD set point read value.
Note: For IMD700A the DVDD rail is forced to be 3.3V and for IMD701A
is forced to 5.0V
b0: 3.3 V – value for IMD700A
b1: 5.0 V – value for IMD701A
CS_GAIN_ST 7:5
r
Status of the current sense amplifiers gain
Shows the value of the current sense amplifier gain independently of
whether programmed digitally or via external resistor
b000: 4 V/V
b001: 8 V/V
b010: 12 V/V
b011: 16 V/V
b100: 20 V/V
b101: 24 V/V
b110: 32 V/V
b111: 64 V/V
Reserved
0
15:8
r
A read always returns 0
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Register Map
OTP Status Register
OTP memory status information is found in this register.
OTP_ST
Address:
04H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
OTP_
PROG
_BLOCK
r
OTP_PR
OG_FAIL
OTP_ OTP_
PASS USED
0
res
r
r
r
Field
Bits
0
Type
Description
OTP used
This bitfield shows if OTP memory has been written by user or still
holds factory defaults:
b0: OTP memory is not used: factory defaults
OTP_USED
OTP_PASS
r
r
b1: OTP memory is used: new custom values loaded
1
User OTP programming status
Is set if user OTP programming has passed without error.
b0: Not programmed or not passed.
b1: Programming passed without error.
OTP_PROG_
BLOCK
2
3
r
User OTP programming blocked
Signals if OTP programming has been attempted when voltage or
temperature outside range.
b0: Programming was not blocked
b1: Programming blocked
OTP_PROG_
FAIL
r
OTP Programming fail
If set, indicates that the programming of the OTP has failed.
b0: No failure.
b1: Programming failed
Reserved
0
15:4
res
A read always returns 0
Datasheet
121
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MOTIX™ IMD70xA
Datasheet
Register Map
ADC Status Register
ADC status registers.
ADC_ST
Address:
05H
Default Name Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
ADC_O
D_RDY
0
ADC_OD_VAL
res
r
r
Field
ADC_OD_RD
Y
Bits
0
Type
r
Description
ADC on demand conversion result ready
This bitfields indicates if ADC result for one of the extended
conversions is ready to be read
b0: Not ready
b1: Ready
ADC_OD_VA 7:1
r
ADC on demand result value
L
ADC result value for on demand conversions
Reserved
0
15:8
res
A read always returns 0
Charge Pumps Status Register
Charge pumps status registers.
CP_ST
Address:
06H
Default Name Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
0
VCCLS_VAL
VCCHS_VAL
res
r
r
Field
VCCHS_VAL 6:0
Bits
Type
r
Description
VCCHS ADC result reading value
This bitfields holds the analog to digital conversions value for VCCHS
voltage
VCCLS_VAL
0
13:7
r
VCCLS ADC result reading value
This bitfields holds the analog to digital conversions value for VCCLS
voltage
Reserved
A read always returns 0
15:14
res
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
Device ID Register
Device ID
DEVICE_ID
Address:
07H
Device ID
Reset Value
0006H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
0
DEV_ID
res
r
Field
Bits
3:0
Type
r
Description
Device ID
DEV_ID
Device identifier for user version control
Reserved
0
15:4
r
A read always returns 0
Faults Clear Register
Clear different faults in the device.
FAULTS_CLR
Address:
10H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CLR_ CLR_
LATCH FLTS
0
res
w
w
Field
Bits
Type
Description
Clear all faults
CLR_FLTS
CLR_LATCH
0
0
w
Setting this bitfield will clear all faults in the device excluding latched
faults. A reading always returns 0.
b0: No action.
b1: Clear all fault status bits except latched ones
Clear all latched faults
Setting this bitfield will clear all (and only) latched faults in the device.
A reading always returns 0.
b0: No action.
b1: Clear latched fault status bits
1
w
Reserved
15:2
res
A read always returns 0
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
Power Supply Configuration Register
This register contains bitfields to configure and control power supplies in the device.
SUPPLY_CFG
Address:
Reset Value
11H
6000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CP_PRE
CHARG
E_EN
rw
DVDD_TON BK_
DVDD_OCP_
CFG
PVCC_
SETPT
0
DVDD_SFTSTRT
CS_REF_ CFG
_DELAY
FREQ
rw
rw
res
rw
rw
rw
rw
Field
Bits
Type
Description
PVCC_SETP 1:0
rw
PVCC set point
T
Configures the target PVCC (gate driving voltage) voltage level
b00: 12V
b01: 15V
b10: 10V
b11: 7V
CS_REF_CF
G
3:2
rw
rw
Current sense reference configuration (internal VREF voltage)
Selects the VREF voltage that is applied as offset in all 3 current shunt
amplifiers:
b00: ½ DVDD
b01: 5/12 DVDD
b10: 1/3 DVDD
b11: ¼ DVDD
DVDD_OCP_ 5:4
DVDD OCP threshold configuration
CFG
DVDD OCP threshold selection. Pre-waring occurs at 66% of the
selected value.
b00: 450mA
b01: 300mA
b10: 150mA
b11: 50mA
DVDD_SFTS 9:6
rw
DVDD soft-start configuration
TRT
DVDD linear regulator soft start programming 100us stepping 100us up
to 1.6ms
b0000: 100 us
b0001: 200 us
.......
100 us steps
.......
b1111: 1.6 ms
Reserved
0
11:10
res
A read always returns 0
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
BK_FREQ
12
rw
rw
Buck converter switching frequency selection
This bitfield configures the switching frequency of the buck converter
b0- Low frequency (500kHz)
b1: High frequency (1MHz)
DVDD_TON_ 14:13
DVDD turn on delay configuration
DELAY
The device will wait for the configured time before turning on the
DVDD starting counting from VDDB UVLO during start-up of the device
b00 - 200us
b01 - 400us
b10 - 600us
b11 - 800us
CP_PRECHA 15
RGE_EN
rw
Charge pump pre-charge configuration
Enables during start-up the pre-charge of the charge pump
1'b0 : pre-charge disabled
1'b1 : pre-charge enabled
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
ADC Configuration Register
Note:
The complete content of the register must be written at once (read-modify-write). Writing a single
bitfield at a time will set to default all other bitfields.
Configuration of ADC related functions.
ADC_CFG
Address:
12H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
ADC_
OD_RE
ADC_FILT_ ADC_FILT_ ADC_E ADC_OD_
0
CFG_PVDD
CFG
N_FILT INSEL
Q
w
res
rw
rw
rw
rw
Field
Bits
Type
Description
ADC on demand conversion request
Setting this bitfield will inject an additional measurement in the
standard sequence. This additional measurement is selected in
ADC_IN_SEL bitfield. A read always return 0.
ADC_OD_RE
Q
0
w
b0: No action.
b1: Request the conversion of the signal selected in ADC_IN_SEL
ADC_OD_IN 2:1
SEL
rw
ADC input selection for on demand conversions
This bitfield configures the input to the ADC:
b00: IDIGITAL: device digital area current consumption
b01: DVDD
b10: VDDB
b11: Reserved
ADC_EN_FIL
T
3
w
Enable filtering for on demand ADC measurement
Enables moving averaging filter for on demand ADC measurements. A
read always return 0
b0: No action.
b1: Enable filtering
ADC_FILT_C 5:4
rw
ADC generic filtering configuration
FG
Selects the moving averaging filter characteristic for the ADC
measurements except PVDD measurements:
b00: 8 samples averaging filter
b01: 16 samples averaging filter
b10: 32 samples averaging filter
b11: 64 Samples averaging filter
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
ADC_FILT_C 7:6
FG_PVDD
rw
PVDD ADC measurement result filtering configuration
This bitfield selects the moving averaging filter characteristic for PVDD
measurement:
b00: 32 samples
b01: 16 samples
b10: 8 samples
b11: 1 sample
Reserved
0
15:8
res
A read always returns 0
PWM Configuration Register
Configuration of PWM related configurations.
PWM_CFG
Address:
13H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
PWM_
FREEW_
CFG
PWM_ BRAKE
0
PWM_MODE
RECIRC
_CFG
res
rw
rw
rw
rw
Field
Bits
Type
Description
PWM_MODE 2:0
rw
PWM commutation mode selection
PWM Mode selection:
b000: 6PWM mode
b001: 3PWM mode
b010: 1PWM mode
b011: 1PWM with Hall sensors – not possible due to interconnects –
do not use
b100: b111: Reserved
PWM_FREE
W_CFG
3
rw
rw
PWM freewheeling configuration
This bitfield selects which rectification or freewheeling is desired (only
for 1 PWM input modes)
b0: Active freewheeling
b1: Diode freewheeling
BRAKE_CFG 5:4
Brake configuration
Brake scheme configuration.
b00: Low Side
b01: High Side
b10: High Z (no power)
b11: Brake toggle-alternates between low and high side braking on
every braking event
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
PWM_RECIR
C
6
rw
PWM recirculation selection (only if PWM_MODE = b011:)
Setting this bitfield will activate the alternating recirculation feature of
the 1PWM with Hall Sensors and Alternating Recirculation PWM mode.
Only functional if PWM_MODE=b011.
b0: Disable alternating recirculation mode
b1: Enable alternating recirculation mode
Reserved
0
15:7
res
A read always returns 0
Sensor Configuration Register
Sensors configuration.
SENSOR_CFG
Address:
14H
Reset Value
0001H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
OTS_
DIS
0
CS_TMODE
HALL_DEGLITCH
res
rw
rw
rw
Field
Bits
Type
Description
Hall Sensor deglitch
HALL_DEGLI 3:0
rw
TCH
Deglitch time configuration for Hall sensor inputs in steps of 640ns
b0000: 0ns
b0001: 640 ns
… in steps of 640 ns
b1111- 9600 ns
OTS_DIS
4
rw
rw
Over-temperature shutdown disable
This bitfield allows to disable the shutdown feature due to over
temperature in the device:
b0: Enable shutdown protection
b1: Disable shutdown protection
CS_TMODE
6:5
Current sense amplifier timing mode
This bitfield configures how the current sense amplifier operates
regarding the timing related to the PWM signals:
b00: CS amplifier outputs are active when GLx signal is high
b01: CS amplifier outputs are active when GHx signal is low
b1x: CS amplifier outputs are always active
Reserved
0
15:7
res
A read always returns 0
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
Watchdog Configuration Register
Watchdog controls.
WD_CFG
Address:
15H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
WD_FL
TCFG
rw
0
WD_TIMER_T
WD_INSEL
WD_EN
res
rw
rw
rw
Field
WD_EN
Bits
Type
Description
0
rw
Watchdog enable
Watchdog timer enable
b0: Watchdog timer is disabled
b1: Watchdog timer is enabled
WD_INSEL
3:1
rw
Watchdog input selection
This bitfield selects the input to the watchdog timer among following
options:
b000: EN_DRV pin (measure input signal frequency)-Not possible due
to interconnects between XMC1404 and 6EDL7141, must be
reprogrammed to other value if watchdog is needed.
b001: Reserved
b010: DVDD (linear regulator)
b011: VCCLS and VCCHS, (charge pumps)
b100: Status register read – candidate for default
b101: Reserved
b110: Reserved
b111: Reserved
WD_FLTCFG
4
rw
rw
Watchdog fault configuration
This bitfield controls the reaction to a watchdog fault event:
b00: Status register only
b01: Status register and pull down of nFAULT pin
WD_
14:5
Watchdog timer period value
TIMER_T
This bitfields configures the period of the watchdog timer. After this
time is elapsed with no re-start of the timer by the watchdog input, a
watchdog fault is triggered. In 100us steps. Not applicable for VDDB
(buck) watchdog input.
b0000000000: 100 us
b0000000001: 200 us
......
b1111111111: 102.4ms
Reserved
A read always returns 0
0
15
res
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
Watchdog Configuration Register 2
Watchdog configurations register extension.
WD_CFG2
Address:
16H
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
WD_
WD_DVDD WD_
WD_
BK_DIS
WD_
BRAKE
0
WD_RLOCK_T RLOCK WD_DVDD_RSTRT_DLY _RSTRT_A EN_
_EN
rw
TT
LATCH
res
rw
rw
rw
rw
rw
rw
Field
Bits
Type
Description
Brake on watchdog timer overflow
This bitfields provides the option to configure a braking event when
the watchdog overflow occurs
WD_BRAKE
0
rw
b0: Normal reaction to fault
b1: Brake on watchdog fault (Automatically latched). The braking
mode is configured in PWM_CFG register. Status register is updated
accordingly
Enable latching of watchdog fault
Enable latching of watch dog fault
b0: Fault not latched
WD_EN_LAT
CH
1
rw
rw
b1: Fault latched
Restart delay for DVDD
Number of restart attempts for DVDD WD
b00: 0 attempts
WD_DVDD_
RSTRT_ATT
3:2
b01: 1 attempt
b10: 2 attempts
b11: 3 attempts
DVDD restart delay
Time after WD trigger signal until restart is attempted again for DVDD.
In steps of 0.5ms
b0000: 0.5 ms
b0001: 1 ms
……
b1110: 7.5 ms
b1111: 8 ms
WD_DVDD_
RSTRT_DLY
7:4
rw
rw
Enable rotor locked detection
Enable rotor lock dedicated watchdog timer input
b0: Disabled
WD_RLOCK_
EN
8
b1: Enabled
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
Rotor locked watchdog timeout
Watchdog timer period value (overflow value). In steps of 1s
b000: 1 second
b001: 2 s
WD_RLOCK_
T
11:9
rw
……….
b111: 8 s
Buck watchdog disable
Buck watchdog (start-up) disable
b0: Buck watchdog enabled
b1: Buck watchdog disabled
WD_BK_DIS 12
rw
Reserved
A read always returns 0
0
15:13
res
Gate Driver Current Control Register
Gate driver current settings for slew rate control.
IDRIVE_CFG
Address:
17H
Reset Value
BBBBH
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
ILS_SINK
ILS_SRC
IHS_SINK
IHS_SRC
res
rw
rw
rw
Field
Bits
Type
Description
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
High-side source current
IHS_SRC
3:0
rw
High side gate driver rise or pull-up gate current applied during period
TDRIVE2
b0000 - 10mA
b0001 - 20mA
b0010 - 30mA
b0011 - 40mA
b0100 - 50mA
b0101 - 60mA
b0110 - 80mA
b0111 – 100mA
b1000 - 125mA
b1001 - 150mA
b1010 - 175mA
b1011 - 200mA
b1100 - 250mA
b1101 – 300mA
b1110 – 400mA
b1111 – 500mA
High-side sink current
IHS_SINK
7:4
rw
High-side gate driver fall or pull-down gate current applied during
period TDRIVE4
Same coding as IHS_SRC
Low-side source current
Low side gate driver rise or pull-up gate current applied during period
TDRIVE2
ILS_SRC
11:8
rw
rw
Same coding as IHS_SRC
Low-side sink current
Low side gate driver fall or pull-down gate current applied during
period TDRIVE4
ILS_SINK
15:12
Same coding as IHS_SRC
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
Gate Driver Pre-Charge Current Control Register
Low side gate driver control parameters
IDRIVE_PRE_CFG
Address:
18H
Reset Value
00BBH
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
I_PRE
_EN
0
I_PRE_SINK
I_PRE_SRC
res
rw
rw
rw
Field
Bits
Type
Description
Pre-charge source current setting (TDRIVE1
)
I_PRE_SRC
3:0
rw
Rise or pull-up gate current applied during pre-charge phase (TDRIVE1
)
b0000 - 10mA
b0001 - 20mA
b0010 - 30mA
b0011 - 40mA
b0100 - 50mA
b0101 - 60mA
b0110 - 80mA
b0111 - 100mA
b1000 - 125mA
b1001 - 150mA
b1010 - 175mA
b1011 - 200mA
b1100 - 250mA
b1101 – 300mA
b1110 – 400mA
b1111 – 500mA
Pre-charge sink current setting (TDRIVE3
Fall or pull-down current during pre-charge phase (TDRIVE3
Same coding as I_PRE_SRC
)
I_PRE_SINK 7:4
rw
rw
)
Gate driver pre-charge mode enable
Enables extra pre-charge current configurations. In case of disabled,
1.5A are applied during Tdrive1 and Tdrive3 periods
I_PRE_EN
8
b0: Pre-charge current enabled. Values I_PRE_SINK and I_PRE_SRC
are applied during TDRIVE1 and TDRIVE3 respectively
Reserved
0
15:9
res
A read always returns 0
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
TDRIVE Source Control Register
TDRIVE1 and TDRIVE2 configuration registers for ate driver sourcing mode.
TDRIVE_SRC_CFG
Address:
19H
Reset Value
FF00H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
TDRIVE2
TDRIVE1
rw
rw
Field
Bits
Type
Description
TDRIVE1 timing
TDRIVE1
7:0
rw
TDRIVE1 value for high and low side. First turn on or pre-charge period
b00000000 - 0ns
b00000001 - 50ns (values between 0ns and 50ns not allowed)
10ns steps
b11111111 - 2590ns
TDRIVE2
15:8
rw
TDRIVE2 timing
TDRIVE2 value for high and low side.
b00000000 - 0ns
b00000001 - 10ns
10ns steps
b11111111 - 2550ns
TDRIVE Sink Control Register
Tdrive3 and Tdrive4 configuration registers for ate driver sourcing mode.
TDRIVE_SINK_CFG
Address:
1AH
Reset Value
FF00H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
TDRIVE4
TDRIVE3
rw
rw
Field
Bits
Type
rw
Description
TDRIVE3 timing
TDRIVE3
7:0
TDRIVE3 value for high and low side. First turn off or pre-discharge period
b00000000 - 0ns
b00000001 - 50ns (values between 0ns and 50ns not allowed)
10ns steps
b11111111 - 2590ns
Datasheet
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Datasheet
Register Map
TDRIVE4
15:8
rw
TDRIVE4timing
TDRIVE4 value for high and low side.
b00000000 - 0ns
b00000001 - 10ns
10ns steps
b11111111 - 2550ns
Dead Time Register
Dead time configurations.
DT_CFG
Address:
1BH
Reset Value
3131H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
DT_FALL
DT_RISE
rw
rw
Field
Bits
Type
rw
Description
DT_RISE
7:0
Dead time rise (of phase node voltage)
Dead time rise (low to high) value
b00000000: 120 ns
b00000001: 200 ns
In steps of 80ns
…
b00110001: 4040ns
…
b10010101: 12040 ns
b10010110: b11111111: Unused (defaults to 120ns)
DT_FALL
15:8
rw
Dead time fall (of phase node voltage)
Dead time fall (high to low) value
b00000000: 120 ns
b00000001: 200 ns
In steps of 80ns
…
b00110001: 4040ns
…
b10010101: 12040 ns
b10010110: b11111111: Unused (defaults to 120ns)
Datasheet
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MOTIX™ IMD70xA
Datasheet
Register Map
Charge Pump Configuration Register
Charge pump related controls.
CP_CFG
Address:
1CH
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CP_CLK CP_CLK_CF
0
_SS_DIS
G
res
rw
rw
Field
Bits
Type
Description
Charge pump clock frequency configuration
This bitfield configures the charge pump clock switching frequency.
CP_CLK_
CFG
1:0
rw
b00: 781.25 kHz
b01: 390.6 kHz
b10: 195.3 kHz
b11: 1.5625 MHz
CP_CLK_SS_
DIS
2
rw
Charge pump clock spread spectrum disable
b0: Spread spectrum is enabled
b1: Spread spectrum disabled
Reserved
0
15:3
res
A read always returns 0
Datasheet
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Datasheet
Register Map
Current Sense Amplifier Configuration Register
Current sense amplifier configurations.
CSAMP_CFG
Address:
1DH
Reset Value
0028H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CS_
GAIN_
ANA
rw
CS_OCPFLT_ CS_OCP_ CS_ EN_
CS_BLANK
CS_EN
CS_GAIN
CFG
DEGLITCH DCCAL
rw
rw
rw
rw
rw
rw
Field
Bits
Type
Description
Gain of current sense amplifiers
CS_GAIN
2:0
rw
Selects gain of current sense amplifier when digitally programmed
b000: 4 V/V
b001: 8 V/V
b010: 12 V/V
b011: 16 V/V
b100: 20 V/V
b101: 24 V/V
b110: 32 V/V
b111: 64 V/V
CS_GAIN_AN
A
3
rw
rw
CS Gain analogue programming enable
Change to b0 to program GAIN digitally – due to interconnects of
XMC1404 and 6EDL7141, analog programming is not possible and
CS_GAIN must be programmed digitally
CS Gain analogue programming enable
b0: Gain is selected via register configuration (CS_GAIN bitfield)
b1: Gain is defined by CS_GAIN pin resistor
CS_EN
6:4
Enable of each current shunt amplifier
Enable of each current shunt amplifier
bit 0: phase A
bit 1: phase B
bit 2: phase C
b0: Amplifier disabled
b1: Amplifier enabled
Datasheet
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Datasheet
Register Map
CS_BLANK
10:7
rw
Current shunt amplifier blanking time
Current shunt amplifier blanking time
b0000: 0 ns
b0001: 50 ns
b0010: 100 ns
b0011: 200 ns
b0100: 300 ns
b0101: 400 ns
b0110: 500 ns
b0111: 600 ns
b1000: 700 ns
b1001: 800 ns
b1010: 900 ns
b1011: 1 us
b1100: 2 us
b1101: 4 us
b1110: 6 us
b1111: 8 us
CS_EN_DCC 11
AL
rw
rw
Enable DC Calibration of CS amplifier
DC calibration of CS amplifier
b0: No calibration is executed
b1: DC calibration mode executed: all power stages in high Z: powered
but not driving
CS_OCP_DE 13:12
Current sense amplifier OCP deglitch
GLITCH
OCP deglitch timing configuration of the OCP on current sense
amplifiers-deglitch disabled (bypassed) if CS_TRUNC_DIS = b0
(register CSAMP_CFG2)
b00: 0 μs
b01: 2 μs
b10: 4 μs
b11: 8 μs
CS_OCPFLT
_CFG
15:14
rw
Current sense amplifier OCP fault trigger configuration
OCP fault trigger configuration
b00: Count 8 OCP events
b01: Count 16 OCP events
b10: Trigger on all OCP events
b11: No fault trigger (PWM Truncation continues as defined in bitfield
CS_TRUNC_DIS in register CSAMP_CFG2)
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Register Map
Current Sense Amplifier Configuration Register 2
Current sense amplifier configurations extension register.
CSAMP_CFG2
Address:
1EH
Reset Value
0833H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
CS_NE
G_OCP
_DIS
rw
CS_TR
UNC_D
CS_
OCP_
LATCH
rw
CS_AZ_CF
G
VREF_
INSEL
CS_OCP CS_
_BRAKE MODE
CS_OCP_NTHR
CS_OCP_PTHR
IS
rw
rw
rw
rw
rw
rw
rw
Field
Bits
Type
Description
CS_OCP_PT 3:0
HR
rw
Current sense amplifier OCP positive thresholds
This bitfield configures the threshold level for the positive OCP
4'b0000: 300mV
4'b0001: 250mV
4'b0010: 225mV
4'b0011: 200mV
4'b0100: 175mV
4'b0101: 150mV
4'b0110: 125mV
4'b0111: 100mV
4'b1000: 90mV
4'b1001: 80mV
4'b1010: 70mV
4'b1011: 60mV
4'b1100: 50mV
4'b1101: 40mV
4'b1110: 30mV
4'b1111: 20mV
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Register Map
CS_OCP_NT 7:4
HR
rw
Current sense amplifier OCP negative thresholds
This bitfield configures the threshold level for the negative OCP
4'b0000: -300mV
4'b0001: -250mV
4'b0010: -225mV
4'b0011: -200mV
4'b0100: -175mV
4'b0101: -150mV
4'b0110: -125mV
4'b0111: -100mV
4'b1000: -90mV
4'b1001: -80mV
4'b1010: -70mV
4'b1011: -60mV
4'b1100: -50mV
4'b1101: -40mV
4'b1110: -30mV
4'b1111: -20mV
CS_OCP_LA
TCH
8
9
rw
OCP latch choice
OCP fault can be selected with this bitfield to be a latched:
b0: Unlatched
b1: Latched
CS_MODE
rw
rw
Current sense amplifier sensing mode
Select between shunt resistor and RDSON sensing modes
b0: Shunt resistor
b1: RDSON sensing-CS_TMODE forced to be GL ON only
CS_OCP_BR 10
AKE
Current sense amplifier brake on OCP configuration
Brake on OCP
b0: No braking upon OCP fault.
b1: Brake on OCP fault (fault set to latched). The braking mode is
configured in PWM_CFG register
CS_TRUNC_ 11
DIS
rw
rw
PWM truncation disable
Disables the truncation of PWM when an OCP occurs. This does not
affect fault triggering.
b00: PWM truncation enabled
b01: PWM truncation disabled
VREF_INSEL 12
VREF source selection – DO NOT CHANGE – VREF external not
possible
This bitfield controls whether the current sense amplifier buffer offset
(reference) is generated internally or is applied externally through the
device pin VREF
b0: Use internal – DO NOT CHANGE
b1: Use external – This configuration is not possible
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Register Map
CS_NEG_OC 13
P_DIS
rw
rw
Current sense negative OCP disable
This bitfield disables the negative Over Current Protection in the
current shunt amplifiers including both the PWM truncation and fault
reporting
b0: Negative OCP fault is enabled
b1: Negative OCP fault is disabled
CS_AZ_CFG
15:14
Current sense Auto-Zero configuration
This bitfield configures the Auto-Zero feature
b00: Auto-Zero enabled with internal synchronization
b01: Auto-Zero disabled
b10: Auto-Zero enabled with external synchronization
b11: Auto-Zero enabled with external synchronization and charge
pump clock gating
OTP Program Register
OTP program command and user ID.
OTP_PROG
Address:
1FH
Reset Value
0000H
15
14
13
12
11
10
9
8
7
6
5
4
3
2
1
0
OTP_
0
USER_ID
PROG
res
rw
w
Field
Bits
Type
Description
Program OTP
OTP_PROG
0
w
Setting this bitfield will start programming of OTP
USER_ID
0
4:1
rw
User ID
Space for user to enter an ID into OTP for version control
Reserved
A read always returns 0
15:5
res
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Application Description
12
Application Description
12.1
Recommended External Components
MOTIX™ IMD70xA requires some external components for proper operation. Recommended components and
values are listed in Table 30.
Table 30
Recommended external components
Element Pin1
Pin2
Recommended value Rating
Notes
CPVDD
PVDD
PGND
4.7µF
According to PVDD
CDVDD
DVDD
DGND
PGND
10µF + 0.1µF
16V
CVCCHS
VCCHS
1µF < CVCCHS < 2.2µF
25V if connected
to PVDD or
Depending on VCCHS ripple
and start-up requirements
according to
(PVDD+PVCC) if
connected to
PGND
CVCCLS
VCCLS
PGND
1µF < CVCCLS < 4.7µF
25V
Depending on VCCLS ripple
and start-up requirements
CCP1
CCP2
LBUCK
CP1H
CP2H
PH
CP1L
CP2L
VDDB
220nF< CCP1 <1µF
220nF< CCP2 <1µF
22µH
16V or 25V
0.47µF recommended
According to PVDD 0.47µF recommended
According to max
peak current
500kHz configuration
10µH
47 µF
47 µF
1MHz configuration
500kHz configuration
1MHz configuration
CBUCK
VDDB
PGND
16V
12.2
PCB Layout Recommendations
Layout is critical to ensure high quality signal and sensing. Different recommendations are provided in this
section for best electrical, thermal and EMI results.
Grounding and Supply
PGND is the ground used for the following sections in 6EDL7141:
•
•
•
Buck converter
Charge pumps
Gate drivers for low and high side
DGND is used for:
•
•
•
•
XMC1404,
Digital logic in 6EDL7141,
Current sense amplifiers
DVDD
It is recommended to cover well components that refer to PGND with PGND solid planes and to cover DGND
referred components with DGND solid plane. Also ensure that there is no overlap between PGND and DGND
planes to avoid cross coupling.
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However, PGND and DGND have be connected to the same electrical potential and must be connected to each
other in one place in the PCB. The location depends on many factors. Sometimes close to the negative (return)
of the supply or battery can lead to best results.
Decoupling capacitors for supply pin (PVDD) should be as close as possible to the pin 25 (PVDD) and pin 27
(PGND). It can as well be helpful to use a small 0.1uF capacitor for high frequency glitches suppression.
Generally speaking shielding of signals like gate signals but also sensing signals is important to avoid coupling
and noise injection from other noisy areas.
If battery is expected suddenly drop close to the UVLO level of PVDD, it is recommended to have large
capacitors that can maintain the supply voltage during those transients. Eventually, a diode (e.g. Schottky) can
be used in series with PVDD and before the decoupling capacitor. This can avoid that the PVDD decoupling
capacitors discharge to the battery or other circuits when the battery transient crosses below the PVDD UVLO
level of 6EDL7141.
Similarly, CE pin if derived from the battery voltage with voltage dividers, might be affected by these transients.
It can be a good idea to use a small capacitor in CE pin to ensure noise is not switching off the device. Current
consumption of CE pin is extremely low. If the only way to discharge the CE capacitor is through 6EDL7141, the
device might stay on for long periods. It could be useful to design a discharge path in case this is a problem.
Thermal design
Depending on the configuration of the device and the usage of the different integrated power converters like
synchronous buck, LDO or charge pump, the device will present different power losses that will translate into
self-heating. User can choose for example the LDO output voltage: selecting 5V instead of 3.3V will reduce the
losses in the LDO module. Another example: the buck converter output voltage (which is the input for the LDO),
can be configured according to the gate driving voltage needs. If 12V/15V are not required, user can configure
the buck converter to produce 7V output voltage, reducing the losses as well in the LDO when compared with
the standard case 8V.
In order to dissipate the generated heat to the PCB is critical to have a solid connection of the device to the
thermal pad (DGND pad). It is as well highly recommended to have a good amount of thermal vias that can
transfer efficiently the heat from the pad to the PCB. An example is presented in Figure 59.
As a general rule, thicker PCB layers (2 oz/ft2-70μm- or above) can help dissipate faster any heat generated
inside the device.
Buck Converter and DVDD
The relatively high switching frequency and high voltage switching (PVDD to PGND) of the buck converter
makes it a sensitive block in the device to pay extra attention during design phase.
Main goal is to reduce buck switching loop as much as possible (VPH-Inductor-Capacitor-VDDB). In 6EDL7141,
most elements in the synchronous buck are integrated mitigating the EMI emissions, like external diode or low
side MOSFET as well as the feedback or reference resistors.
Apart from the loop itself, it is very important to reduce in particular the VPH traces to the shortest possible and
avoid any large copper amount in the inductor connection. This node is switching PVDD voltage at high
frequency and therefore can be a source of noise in other elements especially this trace must be as far as
possible from sensitive analog sensing like current sensing.
Figure 59 shows a possible buck converter layout with minimized VPH trace and buck loop area.
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Application Description
Figure 59
Buck converter layout recommendation. VPH trace and buck loop area (highlighted) must
be minimized
DVDD linear regulator must be decoupled with capacitors placed as close as possible to the DVDD pins and
connect as short as possible to DGND on the other terminal. Other components supplied by DVDD voltage are
recommended to use additional decoupling local capacitors at those components. This is helpful to suppress
possible noise captured by the routing of those traces.
Gate Driver and Charge Pumps
Maintain as symmetric as possible gate signals including symmetry between phases (similar length for phase A,
B and C) to avoid propagation delay mismatches. Keep as well gate current loops as short as possible and try to
have as close as possible send and return signals.
The source signals of low side SLx, are shared between source of low side MOSFETs and top side sensing for
shunt elements. It is recommended to optimize for the current sensing (symmetric tap of shunt terminal and
parallel routing till current sense inputs), however, if current sense is not used, optimizing for gate driver
performance is a good option.
Charge pump loops should be as small as possible, the charge pump flying capacitors must be placed close to
the pins 29, 30, 31 and 32. Similar for the tank capacitors in VCCHS (pin 34) and VCCLS (pin 33). It is possible to
place some of these capacitors in different layers as long as distance to the device is shortest possible.
Figure 60 shows and example of 6EDL7141 layout highlighting gate driver signals for high side and low side of
phase A and the current sensing in a dual MOSFETs inverter.
Gate resistor can be used, however, user must know that the slew rate control of 6EDL7141 provides means to
tune how fast MOSFETs switch in a programmable manner. Having Rg resistors will add additional voltage drop
between 6EDL7141 and the gate of the MOSFET. Similarly, snubber elements (in parallel with MOSFETs) and
bypass capacitors (high side drain to low side source) in the inverter can be used, nevertheless, the flexibility of
the slew rate controller allows to remove those minimizing the BOM specially in a busy area of the layout, so
more space can be used for the power section for example for better heat distribution in the PCB.
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Application Description
Figure 60
Gate driver and current sensing layout example. Signals are routed in a middle layer.
Current Sensing:
RC filter at SLx and CSNx must be done with care and is not preferred. R1 and R2 as shown in 0, present voltage
drop due to amplifier bias current and/or gate driver current, which affect the Rshunt current sensing accuracy.
R1 limits the current of low-side (LS) gate driver and acts in fact as Rg. A parallel capacitor (C1 as shown below)
between SLx and CSNx can be used. This can increase switching noise during MOSFET switching, at the same
time improve steady state value. Larger C values will accentuate this effect. Depending on application this
value can be adjusted. The parallel capacitor should be close to the SLx and CSNx inputs pins on PCB and
values between 100pF to 1nF can be a good starting point.
It is strongly recommended to use RC filter between current sense amplifier outputs (CSOx) and the ADC inputs
in XMC1404 (AINx pins). Typical cut off frequency of 1MHz can be a good compromise between filtering
capability and dynamic behavior, but user must decide depending on overall performance target.
Kelvin connection of shunt resistor is highly recommended as shown in Figure 60. Traces of SLx (red) and CSNx
(blue) are routed in a middle layer in this case and covered with solid ground planes.
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Application Description
Current sense amplifier input filtering
12.3
Typical Applications
MOTIX™ IMD70xA is a controller with integrated 3-phase gate driver IC to be used with external power MOSFETs
for BLDC motor control applications. IMD70xA integrates as well a synchronous buck converter and a linear
voltage regulator to provide power for charge pumps (gate drivers), XMC1404 and other external sensors. It
integrates as well 3 current sense amplifiers with programmable gain. This can be used for single, double or
triple shunt applications. This current information is used by XMC1404 to control the motor and to enhance the
system protection.
Hall sensors can directly be connected to IMD70xA (through XMC1404 POSIF interface) inputs. An example
configuration of this solution is presented in Figure 61. In this case, IMD70xA uses a single current sense
amplifier.
Alternatively, Figure 62 shows a typical schematic for sensorless motor control method for BLDC motors. All 3
integrated current sense amplifiers are used to amplify the current flowing through current shunts. Current
sense amplifier outputs are connected to the microcontroller ADC inputs so XMC1404 can control either torque,
speed or position of the motor.
These 2 examples show only a basic set up. GPIOs and ADC inputs can be used for purpose like communication
with other systems (e.g. SPI, UART, I2C), measurement of other magnitudes in the drive or for general purpose
I/O like buttons or reading of a potentiometer.
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Application Description
Figure 61
Example IMD701A schematic for trapezoidal or trapezoidal commutation control of BLDC
motors using a single shunt configuration and 3 Hall sensors. Only minimum set up shown.
GPIOs and ADC inputs can be used for auxiliary and general purpose (communication, LEDs,
buttons, etc.). Voltage dividers and capacitors voltage rating must be calculated for the
specific target PVDD voltage
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Figure 62
Example IMD701A schematic for sensorless control of BLDC motors using 3 shunts for
current measurement. Voltage dividers and capacitors voltage rating must be calculated for
the specific target PVDD voltage
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ESD Protection
13
ESD Protection
Following diagrams show ESD protections and pin internal diagrams for different pins of the device.
Figure 63
ESD protection diagram for power supply related pins
Figure 64
Pin diagram for gate driver output pins
Figure 65
ESD protection and pin diagram for XMC pins
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ESD Protection
Figure 66
ESD protection and pin diagram for CE pin
Figure 67
ESD protection and pin diagram for nBRAKE pin
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ESD Protection
Figure 68
ESD protection and pin diagram for current sense amplifier related pins
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Package Information
14
Package Information
Figure 69
PG-VQFN-64-8 package outline
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Package Information
Figure 70
PG-VQFN-64-8 PCB footprint dimensions
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Revision history
Revision history
Major changes since the last revision
Version
Description of change
V1.00
V1.02
First public version
Datasheet update
•
•
•
•
•
Several editorial changes and typos
Clarification on CE pin voltage thresholds in Electrical Characteristics table
Added ‘Thermal design’ section in PCB layout recommendations
Changed SPI min clock period to 77ns in Table 11
Changed DVDD OCP limit accuracy (IDVDD_I_ACC) and added different specification for
different OCP limit settings.
•
•
Removed pull down comment on nSCS pin in Table 2.
Typo in Table 2, SDI and SDO XMC reference to input/output functions were swapped
Datasheet
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Edition 2022-09-16
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相关型号:
IMD701A-Q064X128-AA
MOTIX™ 电机控制器 IMD701A 是英飞凌的完全可编程电机控制器,将XMC1404 微控制器与6EDL7141 三相栅极驱动器 IC集成在一个封装中,以支持使用 BLDC 或 PMSM 电机开发下一代电池供电产品。 集成精密电源和电流分流放大器后,许多外围电路不再需要,从而减少了 PCB 空间,提高了系统封装的可能性。
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