IR2157 [INFINEON]
FULLY INTEGRATED BALLAST CONTROL IC; 完全集成的镇流器控制IC型号: | IR2157 |
厂家: | Infineon |
描述: | FULLY INTEGRATED BALLAST CONTROL IC |
文件: | 总20页 (文件大小:309K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
ADVANCED INFORMATION
Data Sheet No. PD60108B
IR2157
FULLY INTEGRATED BALLAST CONTROL IC
Features
Thermal overload protection
Programmable deadtime
•
Programmable preheat time & frequency
•
•
•
•
•
•
•
•
•
•
•
•
Programmable ignition ramp
Protection from failure-to-strike
Lamp filament sensing & protection
Protection from operation below resonance
Protection from low-line condition & automatic
restart (mimics a magnetic ballast)
Integrated 600V level-shifting gate driver
Internal 15.6V zener clamp diode on VCC
True micropower startup (150uA)
Latch immunity protection on all leads
ESD protection on all leads
Packages
Description
The IR2157 is a fully integrated, fully protected 600V ballast control IC designed to
drive virtually all types of rapid start fluorescent lamp ballasts. Externally program-
mable features such as preheat time & frequency, ignition ramp characteristics, and
running mode operating frequency provide a high degree of flexibility for the ballast
design engineer. Comprehensive protection features such as protection from failure
of a lamp to strike, filament failures, low dc bus conditions, thermal overload, or lamp
failure during normal operation, as well as an automatic restart function, have been
included in the design. The heart of this control IC is a variable frequency oscillator
with externally programmmable deadtime. Precise control of a 50% duty cycle is
accomplished using a T-flip-flop. The IR2157 is available in both 16 pin DIP and 16
pin narrow body SOIC packages.
16 Lead SOIC
(narrow body)
16 Lead PDIP
Typical Connection
+ Rectified AC Line
+ VBUS
R2
R1
C1
RSupply
VDC
CPH
RPH
RT
HO
VS
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
Q1
RGHS
CBLOCK
LRES
CPH
CBS
VB
CSNUBBER
CIGN
RPH
N/C
VCC
COM
LO
DBOOT
RSNUBBER
RT
RRUN
RUN
CT
CSTART RSTART
CRES
CVCC
D1
D2
CT
RDT
DT
Q2
RGLS
SD
CS
R4
R5
R3
C2
R CS
VBUS return
ADVANCEDINFORMATION
IR2157
Power Turned On
UVLO Mode
1/2-Bridge Off
IQCC 150
A
µ
C PH = 0V
Oscillator Off
(UV+)
VCC < 9.5V
(VCC Fault or Power Down)
VCC > 11.4V
SD > 2.0V
(Lamp Removal)
or
VCC < 9.5V
(Power Turned Off)
and
VDC > 5.1V
and
SD < 1.7V
and
(Bus OK)
or
VDC < 3.0V
(dc Bus/ac Line Fault or Powe
(Lamp OK)
or
(Tjmax
)
SD > 2.0V
TJ < 175C
(Lamp Fault or Lamp Remova
FAULT Mode
TJ > 175C
(Over-Temperature)
PREHEAT Mode
Fault Latch Set
1/2-Bridge Off
1/2-Bridge @ f PH
C P H Charging @ I PH = 1
RPH = 0V
µ
A
IQCC 150
µ
A
CPH = 0V
VCC = 15.6V
Oscillator Off
RUN = Open Circuit
CS Disabled
CPH > 4.0V
(End of PREHEAT Mode)
CS > 1.0V
(Failure to Strike Lamp
or Hard Switching)
or
TJ > 175C
(Over-Temperature)
IGNITION RAMP Mode
fPH ramps to f MIN
C P H Charging @ I PH = 1
RPH = Open Circuit
RUN = Open Circuit
µ
A
CS 1V Threshold Enabled
CS > 1.0V
(Over-Current or Hard Switching)
CPH > 5.1V
(End of IGNITION RAMP)
or
CS < 0.2V
(No-Load or Below Resonance)
or
RUN Mode
TJ > 175C
(Over-Temperature)
fMIN Ramps to f RUN
C P H Charges to 7.6V Clamp
RPH = Open Circuit
RUN
= 0V
CS 0.2V Threshold Enabled
2
ADVANCEDINFORMATION
IR2157
Absolute Maximum Ratings
Absolute maximum ratings indicate sustained limits beyond which damage to the device may occur. All voltage param-
eters are absolute voltages referenced to COM, all currents are defined positive into any lead. The thermal resistance and
power dissipation ratings are measured under board mounted and still air conditions.
Symbol Definition
Min.
Max.
Units
V
High side floating supply voltage
-0.3
625
B
S
V
High side floating supply offset voltage
High side floating output voltage
V
- 25
V + 0.3
B
B
S
V
V
HO
V
- 0.3
V + 0.3
B
V
LO
Low side output voltage
-0.3
V + 0.3
CC
I
Maximum allowable output current due to miller effect
-500
-5
500
OMAX
mA
I
RT
R
pin current
T
5
V
C pin voltage
T
-0.3
-5
V
+ 0.3
CC
V
CT
I
CPH pin current
5
mA
CPH
V
RPH pin voltage
-0.3
-0.3
-0.3
-0.3
-0.3
—
V
CC
V
CC
+ 0.3
RPH
V
RUN
RUN pin voltage
+ 0.3
V
Deadtime pin voltage
Current sense pin voltage
Shutdown pin voltage
Supply current (note 1)
Allowable offset voltage slew rate
5.5
DT
V
V
5.5
5.5
CS
V
SD
I
20
mA
CC
dV/dt
-50
—
50
V/ns
P
Package power dissipation @ T ≤ +25°C (16 lead PDIP)
1.60
1.25
75
D
A
(16 lead SOIC)
—
Rth
Thermal resistance, junction to ambient
(16 lead PDIP)
(16 lead SOIC)
—
JA
°C/W
—
100
150
150
300
T
Junction temperature
-55
-55
—
J
T
Storage temperature
°C
S
L
T
Lead temperature (soldering, 10 seconds)
Note 1:
This IC contains a zener clamp structure between the chip V
and COM which has a nominal breakdown
CC
voltage of 15.6V. Please note that this supply pin should not be driven by a DC, low impedance power source
greater than the V
specified in the Electrical Characteristics section.
CLAMP
3
ADVANCEDINFORMATION
IR2157
Recommended Operating Conditions
For proper operation the device should be used within the recommended conditions.
Symbol Definition
Min.
Max.
Units
V
High side floating supply voltage
Steady state high side floating supply offset voltage
Supply voltage
V
- 0.7
V
Bs
CC
CLAMP
600
V
V
-3.0
S
V
CC
V
V
CCUV+
CLAMP
I
Supply current
note 2
10
mA
V
CC
V
V
DC
lead voltage
0
220
1.0
-500
0
VCC
—
DC
C
C lead capacitance
T
pF
T
R
Deadtime resistance
—
-50
450
450
1
DT
kΩ
uA
I
RT
R
T
lead current (note 3)
I
RPH lead current (note 3)
RUN lead current (note 3)
Shutdown lead current
Current sense lead current
Junction temperature
uA
uA
RPH
I
0
RUN
I
-1
mA
mA
oC
SD
I
-1
1
CS
T
-40
125
J
Electrical Characteristics
V
CC
= V = V
= 15V +/- 0.25V, R = 40.0kΩ, C = 470 pF, RPH and RUN leads no connection, V
= 0.0V, R
=
DT
BS
BIAS
T
T
CPH
6.1kΩ, V = 0.5V, V = 0.0V, C = 1000pF, T = 25oC unless otherwise specified.
CS
SD
L
A
Supply Characteristics
Symbol Definition
Min.
Typ.
Max. Units Test Conditions
V
V
CC
supply undervoltage positive going
—
11.4
—
V
rising from 0V
CCUV+
CC
threshold
V
CCUV-
V
CC
supply undervoltage positive going
—
9.6
—
V
falling from 15V
V
CC
threshold
V
I
V
supply undervoltage lockout hysteresis
—
—
—
1.8
150
200
—
—
—
HYSTUV
QCCUV
CC
UVLO mode quiescent current
V
= 10V rising
CC
I
Fault-mode quiescent current (undervoltage
lockout, shutdown, over-current, over-temp)
µA
QCCFLT
I
Quiescent V supply current
—
—
—
3.8
—
—
—
R
no connection, C
T T
QCC
CC
connected to COM
=36kΩ, R
mA
V
I
V
CC
supply current, f= 50kHz
4.5
R
=
DT
QCC50K
T
5.6kΩ, C =220pF
T
V
V
CC
zener clamp voltage
15.6
I
= 10mA
CC
CLAMP
Note 2: Enough current should be supplied into the VCC lead to keep the internal 15.6V zener clamp diode on this lead
regulating its voltage.
Note 3: Due to the fact that the RT input is a voltage-controlled current source, the total RT pin current is sum of all of
the parallel current sources connected to that pin. For optimum oscillator current mirror performance, this total
current should be kept between 50mA and 500mA. During the preheat mode, the total current flowing out of
the RT pin consists of the RPH pin current plus the current due to the RT resistor. During the run mode, the
total RT pin current consists of the RUN pin current plus the the current due to the RT resistor.
4
ADVANCEDINFORMATION
IR2157
Electrical Characteristics (cont.)
Floating Supply Characteristics
Symbol Definition
Min. Typ.
Max. Units Test Conditions
I
I
Quiescent V supply current
BS
Quiescent V supply current
BS
—
—
—
0
—
—
5
V
V
= V
= V
QBS0
HO
S
B
µA
30
4
QBS1
HO
VBSMIN Minimum required VBS voltage for proper
HO functionality
V
µA
I
Offset supply leakage current
—
—
50
V = V = 600V
B S
LK
Oscillator I/O Characteristics
Symbol Definition
Min.
Typ.
Max. Units Test Conditions
f
Oscillator frequency
—
30
—
R
T
= 32kΩ, R
=
osc
DT
6.1kΩ, C =470pF
T
kHz
—
—
R = 6.1kΩ, R
=
100
T
DT
6.1kΩ, C =470pF
T
—
—
—
—
—
—
—
—
—
—
—
—
df/dV
df/dT
d
Oscillator frequency voltage stability
Oscillator frequency temperature stability
Oscillator duty cycle
0.5
0.02
50
%/V
%/C
%
V
CCUV
+ < V
< 15V
CC
-40oC < Tj < 125oC
V
CT+
Upper C ramp voltage threshold
4.0
2.0
T
V
V
CT-
Lower C ramp voltage threshold
T
mV
SD = 5V, CS = 2V,
or Tj > TSD
V
Fault-mode C pin voltage
0
CTFLT
T
—
—
2.0
0
—
—
V
V
R pin voltage
T
Fault-mode R pin voltage
T
RT
SD = 5V, CS = 2V,
or Tj > TSD
V
RTFLT
mV
—
—
—
—
2.0
2.0
0.5
0.02
—
—
—
—
tdlo
LO output deadtime
µsec
toho
HO output deadtime
dtd/dV
dtd/dT
Deadtime voltage stability
Deadtime temperature stability
%/V
%/C
V
CCUV
+ < V
< 15V
CC
-40oC < Tj < 125oC
Preheat Characteristics
Symbol Definition
Min.
Typ.
Max. Units Test Conditions
I
CPH pin charging current
—
—
—
1.0
4.0
—
—
—
—
—
µA
V
= 0V
CPH
CPH
V
V
V
V
CPH pin lgnition mode threshold voltage
CPH pin run mode threshold voltage
CPHIGN
CPHRUN
CPHCLMP
CPHFLT
V
5.15
7.6
0
I
= 1mA
CPH pin clamp voltage
Fault-mode CPH pin voltage
—
—
CPH
mV
SD = 5V, CS = 2V,
or Tj > TSD
5
ADVANCEDINFORMATION
IR2157
Electrical Characteristics (cont.)
RPH Characteristics
Symbol Definition
Min.
Typ.
Max. Units Test Conditions
I
V
Open circuit RPH pin leakage current
Fault-mode RPH pin voltage
—
—
0.1
0
—
—
µA
mV
V
= 5V,V
SD = 5V, CS = 2V,
or Tj > TSD
= 5V
RPH
RPHLK
RPH
RPHFLT
RUN Characteristics
Symbol Definition
Min.
Typ.
Max. Units Test Conditions
I
Open circuit RUN pin leakage current
Fault-mode RUN pin voltage
—
—
0.1
0
—
—
µA
V
= 5V
RUNLK
RUN
V
mV
SD = 5V, CS = 2V,
or Tj > TSD
RUNFLT
Protection Circuitry Characteristics
Symbol Definition
Min.
Typ.
Max. Units Test Conditions
V
Rising shutdown pin threshold voltage
Shutdown pin threshold hysteresis
Over-current sense threshold voltage
Under-current sense threshold voltage
Over-current sense propogation delay
—
—
—
—
—
2.0
150
1.0
0.2
160
—
—
—
—
—
V
SDTH+
V
mV
SDHYS
V
CSTH+
V
V
CSTH-
CS
T
nsec Delay from CS to LO
or HO
V
V
Low V
Low V
/rectified line input upper threshold
/rectified line input lower threshold
—
—
—
5.15
3.0
—
—
—
DC+
BUS
V
DC-
BUS
T
Thermal shutdown junction temperature
175
oC
SD
Gate Driver Output Characteristics
Symbol Definition
Min.
Typ.
Max. Units Test Conditions
VOL
Low-level output voltage
High level output voltage
Turn-on rise time
—
—
—
—
0
100
100
150
100
I
= 0
o
mV
V
0
85
45
V
- V I = 0
O, o
OH
BIAS
t
r
f
nsec
t
Turn-off fall time
Note 4: When the IC senses an overtemperature condition (Tj > 175ºC), the IC is latched off. In order to reset this Fault
Latch, the SD pin must be cycled high and then low, or the VCC supply to the IC must be cycled below the
falling undervoltage lockout threshold (VCCUV-).
6
ADVANCEDINFORMATION
IR2157
Lead Assignments & Definitions
Lead # Symbol Description
1
V
DC bus sensing input
DC
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
V D C
C P H
R P H
R T
H O
VS
2
C
R
Preheat timing capacitor
Preheat frequency resistor & ignition capacitor
Oscillator timing resistor
Run frequency resistor
PH
PH
T
3
4
R
5
RUN
VB
6
C
Oscillator timing capacitor
Deadtime programming
Shutdown input
T
N/C
V C C
C O M
LO
7
D
T
SD
8
R U N
C T
9
CS
Current sensing input
10
11
12
13
14
15
16
LO
Low-side gate driver output
IC Power & signal ground
Logic & low-side gate driver supply
Unused
COM
V
CC
N/C
D T
V
B
V
S
HO
High-side gate driver floating supply
High voltage floating return
High-side gate driver output
S D
C S
Functional Block Diagram
3.0V
1 4
VB
HO
VS
1
VDC
S
R
Q
Q
P U L S E
L E V E L
SHIFT
FILTER
LATCH
&
1 6
1 5
5.1V
1.0uA
CPH
2
7.6V
5.1V
4.0V
T
S
Q
Q
Q
Q
4.0V
2.0V
1 2
1 0
VCC
LO
R1
R2
R
3
4
5
RPH
RT
IRT
15.6V
2.0V
1 1
COM
RUN
0.2V
Q
Q
D
CLK
R
ICT = I RT
9
CS
6
7
CT
DT
SD
Q
Q
S
R
1.0V
8
UNDER-
VOLTAGE
DETECT
OVER-
T E M P
DETECT
2.0V
7
ADVANCEDINFORMATION
IR2157
16 Lead SOIC (narrow body)
01-3064 00
16 Lead PDIP
01-3065 00
8
ADVANCEDINFORMATION
IR2157
Description of Operation & Component Selection Tips
Supply Bypassing and PC Board Layout
Rules
Connecting the IC Ground (COM) to the
Power Ground
Component selection and placement on the pc
board is extremely important when using power
control ICs VCC should be bypassed to COM as close
to the IC terminals as possible with a low ESR/ESL
capacitor, as shown in Figure 1 below.
Both the low power control circuitry and low side
gate driver output stage grounds return to this pin
within the IC. The COM pin should be connected to
the bottom terminal of the current sense resistor in
the source of the low side power MOSFET using an
individual pc board trace, as shown in Figure 2. In
addition, the ground return path of the timing
components and VCC decoupling capacitor should
be connected directly to the IC COM pin, and not via
separate traces or jumpers to other ground traces on
the board.
pin 1
CBOOT (surface mount)
DBoot (surface mount)
IR2157 pin
1
CVCC (through hole)
CVCC (surface mount)
CVCC (surface mount)
Figure 1: Supply bypassing PCB layout example
timing
components
CVCC (through hole)
RC S (through hole)
A rule of thumb for the value of this bypass capacitor
is to keep its minimum value at least 2500 times the
value of the total input capacitance (Ciss) of the
power transistors being driven. This decoupling
capacitor can be split between a higher valued
electrolytic type and a lower valued ceramic type
connected in parallel, although a good quality
electrolytic (e.g., 10mF) placed immediately adjacent
to the VCC and COM terminals will work well.
VBUS return
Figure 2: COM pin connection PCB layout example
These connection technique prevents high current
ground loops from interfering with sensitive timing
component operation, and allows the entire control
circuit to reject common-mode noise due to output
switching.
In a typical application circuit, the supply voltage to
the IC is normally derived by means of a high value
startup resistor (1/4W) from the rectified line voltage,
in combination with a charge pump from the output
of the half-bridge. With this type of supply
arrangement, the internal 15.6V zener clamp diode
from VCC to COM will determine the steady state IC
supply voltage.
9
ADVANCEDINFORMATION
IR2157
The heart of this controller is an oscillator which
resembles those found in many popular PWM voltage
regulator ICs. In its simplest form, this oscillator
consists of a timing resistor and capacitor connected
to ground. The voltage across the timing capacitor
CT is a sawtooth, where the rising portion of the ramp
is determined by the current in the RT pin, and the
falling portion of the ramp is determined by an external
deadtime resistor RDT. The oscillograph in Figure 4
illustrates the relationship between the oscillator
capacitor waveform and the gate driver outputs.
The Control Sequence & Timing
Component Selection
The IR2157 uses the following control sequence
(Figure 3) to drive rapid start fluorescent lamps.
fStart
fPH
fRun
fmin
t
5V
VCPH
2V
VRPH
2V
VRUN
Ignition
R a m p
m o d e
Preheat mode
Run mode
Figure 3: IR2157 control sequence
Figure 4
The control sequence used in the IR2157 allows
the Run Mode operating frequency of the ballast to
be higher than the ignition frequency (i.e., fstart >
fph > frun > fign). This control sequence is
recommended for lamp types where the ignition
frequency is too close to the run frequency to ensure
proper lamp striking for all production resonant LC
component tolerances (please note that it is possible
to use the IR2157 in systems where fstart > fph >
fign > frun, simply by leaving the RUN pin open).
The deadtime can be programmed by means of the
external RDT resistor, given a certain range of CT
capacitor values, using the graph shown in Figure 5.
The RT input is a voltage-controlled current source,
where the voltage is regulated to be approximately
2.0V. In order to maintain proper linearity between
the RT pin current and the CT capacitor charging
current, the value of the RT pin current should be
kept between 50µA and 500µA. The RT pin can
also be used as a feedback point for closed loop
control.
Six pins in the IC are used to control the Startup,
Preheat, Ignition Ramp, and Run modes of
operation, and to allow ballast and lamp engineers
the flexibility to optimize their designs for virtually
any lamp type.
10
ADVANCEDINFORMATION
IR2157
During the Startup Mode, the operating frequency is
determined by the parallel combination of RPH,
RSTART , and RT , combined with the values of
CSTART, CT and RDT , as shown in Figure 6. This
frequency is normally chosen to ensure that the
instantaneous voltage across the lamp during the
first few cycles of operation does not exceed the
strike potential of the lamp. As the voltage across
CSTART charges up to the RT pin voltage, the output
frequency exponentially decays to the preheat
frequency.
10
tDEAD
(usec)
CT = 220 pF
CT = 470 pF
CT = 1 nF
1
During the Preheat Mode, the operating frequency
is determined by the parallel combination of RPH
and RT , combined with the value of CT and RDT .
This frequency, along with the Preheat Time, is
normally chosen to ensure that adequate heating of
the lamp filaments occurs. Typically, a 4.5:1 ratio of
0.1
1
10
100
RDT (Kohms)
Figure 5: Deadtime versus R
DT
1.0uA
CPH
2
7.6V
CPH
5.1V
S
Q
Q
4.0V
2.0V
4.0V
R 1
R 2
RPH
RT
3
4
5
CIGN
RPH
IRT
2.0V
RT
R RUN
RUN
CSTART RSTART
ICT
= IRT
CT
DT
6
7
CT
RDT
UNDER-
VOLTAGE
DETECT
Figure 6: Oscillator section block diagram with external component connection
11
ADVANCEDINFORMATION
IR2157
The following graphs, Figures 8 and 9, illustrate the
relationship between the effective RT resistance (i.e.,
the parallel combination of resistors which programs
the CT capacitor charging current) and the operating
frequency.
the hot filament-to-cold filament resistance is desired
for maximum lamp life, as shown in Figure 7
150
FREQ
(KHz)
CT=220pF,RDT=11K
CT=470pF,RDT=6.2K
CT=1nF,RDT=3K
100
50
0
Figure 7: Lamp filament voltage during the
preheat, ignition ramp and run modes.
0
5
10
15
20
25
30
35
40
RT (K ohms)
The Preheat Time is programmed by means of the
preheat capacitor, CPH, an internal 1mA current
source, and an internal threshold on the CPH pin of
4.0V, according to the following formula:
Figure 8: fosc versus effective RT (tDEAD = 2.0 usec)
t
C
PH = 4E6 CPH
PH = 250E-9 tPH
,
or
250
200
At the end of the Preheat Time, the internal, open-
drain transistor holding the RPH pin to ground turns
off, and the voltage on this pin charges exponentially
up to the RT pin potential. During this Ignition Ramp
Mode, the output frequency exponentially decays to
a minimum value. The rate of decay of this frequency
is a function of the RPH * CPH time constant. Because
the Ignition Ramp Mode ends when the voltage on
the CPH pin reaches 5.15V, the ignition ramp is
always 1/4th as long as the preheat time.
When the CPH pin reaches 5.15V, an open-drain
transistor on the RUN pin turns on, and the external
RRUN resistor is then in parallel with the RT resistor.
The Run Mode operating frequency is therefore a
function of the parallel combination of RRUN and
RT , and this means that the operating power of the
lamp can be programmed by means of RRUN .
CT=220pF, RDT=5.6K
CT=470pF, RDT=2.7K
CT=1nF, RDT=1.2K
150
FREQ
(KHz)
100
50
0
0
5
10
15
20
25
30
35
40
RT (K ohms)
Figure 9: fosc versus effective RT (tDEAD = 1.0 usec)
12
ADVANCEDINFORMATION
IR2157
Lamp Protection & Automatic Restart Circuitry Operation
Three pins on the IR2157 are used for protection, as shown in Figure 10 below. These are VDC (dc bus
monitor), SD (unlatched shutdown), and CS (latched shutdown).
+ V BUS
3.0V
V D C
R2
1
S
R
Q
Q
5.1V
R1
C1
from oscillator
section
1.0uA
T
Q
Q
C P H
2
R
7.6V
Q2
5.1V
4.0V
Q
Q
D
0.2V
C S
R4
CLK
R
9
DT
S D
S
R
Q
Q
from lamp
lower cathode
R3
7
8
R5
C2
RCS
1.0V
UNDER-
OVER-
TEMP
DETECT
2.0V
VOLTAGE
DETECT
Figure 10: Lamp protection & automatic restart circuitry block diagram with external component connection.
Sensing the DC Bus Voltage
pump off of the output of the half-bridge). In this
case, the voltage on the VDC pin will shut the oscillator
off, thereby protecting the power transistors from
potentially hazardous hard switching. Approximately
2V of hysteresis has been designed into the internal
comparator sensing the VDC pin, in order to account
for variations in the dc bus voltage under varying
load conditions. When the dc bus recovers, the chip
restarts from the beginning of the control sequence,
as shown in timing diagram 11 below.
The first of these protection pins senses the voltage
on the DC bus by means of an external resistor
divider and an internal comparator with hysteresis.
When power is first supplied to the IC at system
startup, 3 conditions are required before oscillation
is initiated: 1.) the voltage on the VCC pin must
exceed the rising undervoltage lockout threshold
(11.5V), 2.) the voltage at the VDC pin must exceed
5.1V, and 3.) the voltage on the SD pin must be below
approximately 1.85V. If a low dc bus condition occurs
during normal operation, or if power to the ballast is
shut off, the dc bus will collapse prior to the VCC of
the chip (assuming the VCC is derived from a charge
13
ADVANCEDINFORMATION
IR2157
rectified
AC line
+VB
U
S
V
C
R
D
P
P
R
U
C
D
C
H
H
T
H O
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
Q1
R G
5
H
S
V S
V B
C B
LR
E S
V D C
L
O
B
C
B
K
E
3
R S
C B O O T
U
P P L Y
R S
N
U
R
N / C
D B O O T
D 1
C
CS
N U
B B E R
R
N
T
V
C
L
C
O
O
C
4
C R
E S
M
CV
C
D 2
CT
T
Q2
R C
R G
L
S
S
D
C S
R3
R 4
R 5
8
C 2
S
C P H
VB S return
U
15
L O
Figure 12: Lamp presence detection circuit
connection (shaded area)
15
H O - V S
2
S D
Restart
RUN mode
Low VDC
4
8
Figure 11: VDC pin fault and auto restart
CT
C P H
Lamp Presence Detection and
Automatic Restart
15
The second protection pin, SD, is used for both
unlatched shutdown and automatic restart functions.
The SD pin would normally be connected to an
external circuit which senses the presence of the
lamp (or lamps), as shown in Figure 12.
L O
15
H O - V S
When the SD pin exceeds 2.0V (approximately
150mV of hysteresis is included to increase noise
immunity), signaling either a lamp fault or lamp
removal, the oscillator is disabled, both gate driver
outputs are pulled low, and the chip is put into the
micropower mode. Since a lamp fault would normally
lead to a lamp exchange, when a new lamp is
inserted into the fixture, the SD pin would be pulled
back to near the ground potential. Under these
Restart
RUN mode
SD mode
Figure 13: SD pin fault and auto restart
conditions a reset signal would restart the chip from
the beginning of the control sequence, as shown in
the timing diagram in Figure 13.
14
ADVANCEDINFORMATION
IR2157
and under-resonance conditions, there is a negative-
going threshold of 0.2V which is enabled at the onset
of the run mode. The sensing of this 0.2V threshold
is synchronized with the falling edge of the LO output.
Thus, for a lamp removal and replacement, the ballast
automatically restarts the lamp in the proper manner,
maximizing lamp life and minimizing stress on the
power MOSFETs or IGBTs. The SD pin contains an
internal 7.5V zener diode clamp, thereby reducing
the number of external components required.
Figures 15, 16 and 17 are oscillographs of fault
conditions. Figure 15 shows a failure of the lamp to
strike, Figure 16 shows a hard switching condition
and Figure 17 shows an under-current condition.
Half-Bridge Current Sensing and
Protection
The third pin used for protection is the CS pin, which
is normally connected to a resistor in the source of
the lower power MOSFET, as shown in Figure 14.
The CS pin is used to sense fault conditions such a
failure of a lamp to strike, over-current during normal
operation, hard switching, no load, and operation
below resonance. If any one of these conditions is
sensed, the fault latch is set, the oscillator is disabled,
the gate driver outputs go low, and the chip is put
into the micropower mode. The CS pin performs its
sensing functions on a cycle-by-cycle basis in order
to maximize ballast reliability. failure-to-strike, and
For the over-current, hard switching fault conditions,
the 1V, positive-going CS threshold is enabled at
the end of the preheat time. For the under-current
Figure 15: Lamp failure to strike
rectified
AC line
+V BUS
V D C
C P H
RPH
RT
HO
V S
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
Q1
RGHS
1
/
Bridge output
2
V B
RSUPPLY
CB O O T
RSNUBBER
N/C
V C C
C O M
LO
DB O O T
D1
CSNUBBER
RUN
CT
CV C C
D2
DT
Q2
RG L S
S D
C S
R3
RC S
VBUS return
Figure 14: Half-bridge current sensing circuit
connection (shaded area)
Figure 16: Hard switching condition
15
ADVANCEDINFORMATION
IR2157
Recovery from such a fault condition is accomplished
by cycling either SD pin or the VCC pin. When a
lamp is removed, the SD pin goes high, the fault
latch is reset, and the chip is held off in an unlatched
state. Lamp replacement causes the SD pin to go
low again, reinitiating the startup sequence. The
fault latch can also be reset by the undervoltage
lockout signal, if VCC falls below the lower
undervoltage threshold.
Bootstrap Supply Considerations
Power is normally supplied to the high-side circuitry
by means of a simple charge pump from VCC, as
shown in Figure 19 below.
rectified
AC line
+V BUS
V D C
C P H
RPH
RT
HO
V S
1
2
3
4
5
6
7
8
16
15
14
13
12
11
10
9
Q1
Figure 17: Operation below resonance
RGHS
1
/
Bridge output
2
V B
RSUPPLY
CB O O T
RSNUBBER
N/C
V C C
C O M
LO
DB O O T
D1
CSNUBBER
RUN
CT
CV C C
D2
DT
Q2
RG L S
S D
C S
R3
RC S
VBUS return
Figure 19: Typical bootstrap supply connection
with VCC charge pump from half-bridge output
(shaded area)
A high voltage, fast recovery diode DBOOT (the so-
called bootstrap diode) is connected between VCC
(anode) and VB (cathode), and a capacitor CBOOT
(the so-called bootstrap capacitor) is connected
between the VB and VS pins. During half-bridge
switching, when MOSFET Q2 is on and Q1 is off, the
bootstrap capacitor CBOOT is charged from the VCC
decoupling capacitor, through the bootstrap diode
DBOOT, and through Q2. Alternately, when Q2 is off
and Q1 is on, the bootstrap diode is reverse-biased,
Figure 18: Auto restart for lamp replacement
16
ADVANCEDINFORMATION
IR2157
and the bootstrap capacitor (which ‘floats’ on the
source of the upper power MOSFET) serves as the
power supply to the upper gate driver CMOS circuitry.
Since the quiescent current in this CMOS circuitry is
very low (typically 45mA in the on-state), the majority
of the drop in the VBS voltage when Q1 is on occurs
due to the transfer of charge from the bootstrap
capacitor to the gate of the power MOSFET.
pin
1
C BOOT (surface mount)
D Boot (surface mount)
C VCC (through hole)
CVCC (surface mount)
VB should be bypassed to VS as close as possible
to the pins of the IC with a low ESR/ESL capacitor. A
PCB layout example is shown in figure 20. A rule of
thumb for the value of this capacitor is to keep its
minimum value at least 50 times the value of the total
input capacitance (Ciss) of the MOSFET or IGBT being
driven. In addition, the VS pin should be connected
directly to the high side power MOSFET source.
Figure 20: Supply bypassing PCB layout example
Characteristic Curves
0.15
100
10
1
T = -25
0.125
T = 25C
T = 75C
T = 125C
0.1
Iqcc
(mA)
0.075
Iqcc
(mA)
0.1
0.05
0.025
0
0.01
0.001
0
2
4
6
8
10
12
0
2
4
6
8
10
12
14
16
VCC (volts)
VCC (volts)
Figure 22: I
versus V
(V < V
CC
and temperature
)
CC+
QCC
CC
Figure 21: I
versus V
QCC
CC
4
30
25
20
15
10
5
T = -25
T = 25C
T = 75C
T = 125C
3.5
Iqcc
(mA)
Iqcc
(mA)
3
T = -25
T = 25C
T = 75C
T = 125C
2.5
11.5
0
12.5
13.5
14.5
14.5
15
15.5
VCC (volts)
16
16.5
VCC (volts)
Figure 24: V
versus I
and temperature
QCC
Figure 23: I
versus V
and temperature
)
CLAMP
QCC
CC
(V > V
CC
CC+
17
ADVANCEDINFORMATION
IR2157
80
70
60
50
12
11.5
11
T = -25C
T = 25C
T = 75C
T = 125C
Vccuv+
Vccuv-
Vccuv
(V)
Iqbs1
40
10.5
10
(uA)
30
20
10
0
9.5
9
0
2
4
6
8
10
12
14
16
18
20
-25
0
25
50
Temperature (C)
75
100
125
VBS (volts)
Figure 26: I
versus V
BS
Figure 25: V
and V
versus temperature
QBS1
CCUV+
CCUV-
54
53.75
53.5
210
207.5
205
T = -25C
T = 25C
T = 75C
T = 125C
53.25
202.5
200
fOSC
(KHz)
fOSC
(KHz)
53
52.75
52.5
52.25
52
197.5
195
T = -25C
T = 25C
T = 75C
T = 125C
192.5
190
11
11.5
12
12.5
13
13.5
14
14.5
15
11
11.5
12
12.5
13
VCC (volts)
13.5
14
14.5
15
VCC (volts)
Figure 27: f
versus V and temperature
Figure 28: f versus V and temperature
OSC CC
OSC
CC
(RT=330kΩ, CT=300pF)
(RT=6.2kΩ, CT=300pF)
1000
990
980
970
960
950
940
930
920
910
900
80
T = -25C
T = 25C
T = 75C
T = -25C
T = 25C
T = 75C
T = 125C
70
60
50
40
30
20
T = 125C
tDEAD
(nsec)
tfall
(nsec)
11
11.5
12
12.5
13
13.5
14
14.5
15
11
11.5
12
12.5
13
13.5
14
14.5
15
VCC (volts)
VCC (volts)
Figure 29: t
versus V and temperature
Figure 30: t
versus V and temperature
fall CC
DEAD
CC
18
ADVANCEDINFORMATION
IR2157
1.1
160
140
120
100
80
T = -25C
T = 25C
T = 75C
T = -25C
T = 25C
T = 75C
T = 125C
1.08
T = 125C
1.06
CS+
(volts)
trise
(nsec)
1.04
1.02
1
60
40
11
11.5
12
12.5
13
13.5
14
14.5
15
11
11.5
12
12.5
13
13.5
14
14.5
15
VCC (volts)
VCC (volts)
Figure 32: CS+ threshold versus V
and temperature
Figure 31: t
versus V
and temperature
CC
CC
rise
0.235
2.15
2.125
2.1
T = -25C
T = 25C
T = 75C
T = 125C
T = -25C
T = 25C
T = 75C
T = 125C
0.23
0.225
0.22
SD+
(volts)
CS-
(volts)
2.075
2.05
2.025
2
0.215
0.21
0.205
0.2
11
11.5
12
12.5
13
13.5
14
14.5
15
11
11.5
12
12.5
13
13.5
14
14.5
15
VCC (volts)
VCC (volts)
Figure 33: CS- threshold versus V
and temperature
Figure 34: SD+ threshold versus V
and temperature
CC
CC
0.25
5.4
5.35
5.3
T = -25C
T = 25C
T = 75C
T = 125C
T = -25C
T = 25C
T = 75C
T = 125C
0.225
0.2
SD
5.25
hysterisis
VDC+
(volts)
(volts)
0.175
5.2
5.15
5.1
5.05
5
0.15
0.125
0.1
11
11.5
12
12.5
13
VCC (volts)
13.5
14
14.5
15
11
11.5
12
12.5
13
13.5
14
14.5
15
VCC (volts)
Figure 35: SD hysterisis versus V and temperature
Figure 36: VDC+ threshold versus V and temperature
CC
CC
19
ADVANCEDINFORMATION
IR2157
3.3
3.25
3.2
4.15
T = -25C
T = 25C
T = 75C
T = 125C
T = -25C
T = 25C
T = 75C
4.1
T = 125C
4.05
VCPHIGN
(volts)
VDC-
3.15
(volts)
4
3.95
3.9
3.1
3.05
3
11
11.5
12
12.5
13
13.5
14
14.5
15
11
11.5
12
12.5
13
13.5
14
14.5
15
VCC (volts)
VCC (volts)
Figure 38: V
threshold versus V and
CC
temperature
CPHIGN
Figure 37: VDC- threshold versus V
and temperature
CC
5.25
5.2
1.2
1.15
1.1
T = -25C
T = 25C
T = 75C
T = 125C
5.15
1.05
1
VCPHRUN
(volts)
ICPH
(uA)
5.1
5.05
5
0.95
0.9
T = -25C
T = 25C
T = 75C
T = 125C
0.85
0.8
11
11.5
12
12.5
13
13.5
14
14.5
15
11
11.5
12
12.5
13
13.5
14
14.5
15
VCC (volts)
VCC (volts)
Figure 39: V
threshold versus V and
CC
temperature
CPHRUN
Figure 40: I
versus V
and temperature
CC
CPH
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http://www.irf.com/
Data and specifications subject to change without notice. 3/1/99
20
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