IRS2983SPBF_15 [INFINEON]

LED FLYBACK CONTROL IC;


型号：	IRS2983SPBF_15
厂家：	Infineon
描述：	LED FLYBACK CONTROL IC
文件：	总17页 (文件大小：504K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

IRS2983SPBF

LED FLYBACK CONTROL IC

Product Summary

Features

Topology

Flyback



Flyback LED Driver

Critical-conduction / Transition mode operation

Primary constant power control

Burst mode operation at light load

Over-current protection

Micropower startup (150 A)

Low quiescent current (2.5 mA)

Latch immunity and ESD protection

Open load over voltage protection

Noise immunity

I_o+& I _o-(typical)

t_r& t_f(typical)

200 mA / 400 mA

60 ns / 30 ns

Typical Applications

Package



LED Drivers

8-Lead SOIC

IRS2983SPBF

Ordering Information

Standard Pack

Base Part Number

Package Type

Complete Part Number

Form

Quantity

Tube/Bulk

IRS2983SPBF

SO8N

Tape and Reel

2500

IRS2983STRPBF

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January 15, 2015

IRS2983SPBF

Table of Contents

Page

Description

Qualification Information

Absolute Maximum Ratings

Recommended Operating Conditions

Electrical Characteristics

Functional Block Diagram

State Diagram

Input/Output Pin Equivalent Circuit Diagram

Lead Definitions

Lead Assignments

Application Information and Additional Details

Package Details

Tape and Reel Details

Part Marking Information

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January 15, 2015

IRS2983SPBF

Description

The IRS2983 is a fully integrated, fully protected SMPS control IC designed to drive Flyback converter LED drivers.

The IRS2983 features include primary side power regulation, which allows a basic converter to be implemented

without the need for an opto isolator in a Flyback LED driver with a fixed load enabling a low cost, high reliability

isolated LED driver design to be realized. The IRS2983 may also be used in converters that do include secondary

feedback through an opto isolator. Other features of the IRS2983 include a high voltage startup enabling VCC

supply to be derived initially from the high voltage DC bus until the auxiliary inductor winding is able to take over.

The IRS2983 operates in critical conduction (CrCM) or discontinuous (DCM) modes and is fully protected against

open and short circuit as well as inductor saturation. The IRS2983 may be used in single stage Flyback LED

drivers with an unsmoothed DC bus to obtain high power factor and low THD.

Typical Connection Diagram

DFB

RADJ

CSN

RSN

DVCC

QVCC

DSN

RIN

CIN

IC1

VCC

BR1

RZX1

CVCC

OUT

VDC

CVOUT

ROUT

Line

Input

COMP

COM

CCOMP

RDC

CDC

RCS

RZX2

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January 15, 2015

IRS2983SPBF

Qualification Information^†

Industrial^††

Comments: This family of ICs has passed JEDEC’s Industrial

qualification. IR’s Consumer qualification level is granted by

extension of the higher Industrial level.

Qualification Level

MSL2^†††260°C

SOIC8

Moisture Sensitivity Level

(per IPC/JEDEC J-STD-020)

Class B

Machine Model

Human Body Model

(per JEDEC standard JESD22-A115)

ESD

Class 1C

(per EIA/JEDEC standard EIA/JESD22-A114)

Class I, Level A

(per JESD78)

Yes

IC Latch-Up Test

RoHS Compliant

†

Qualification standards can be found at International Rectifier’s web site http://www.irf.com/

†† Higher qualification ratings may be available should the user have such requirements. Please contact

your International Rectifier sales representative for further information.

††† Higher MSL ratings may be available for the specific package types listed here. Please contact your

International Rectifier sales representative for further information.

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January 15, 2015

IRS2983SPBF

Absolute Maximum Ratings

Absolute maximum ratings indicate sustained limits beyond which damage to the device may occur. All voltage

parameters are absolute voltages referenced to COM, all currents are defined positive into any lead. The thermal

resistance and power dissipation ratings are measured under board mounted and still air conditions.

Symbol

V_CC

Definition

Min.

---

Max.

20.8

Units

IC Low Voltage Supply^†

V_OUT

V_CC+ 0.3

Gate Driver Output Voltage

-0.3

Maximum allowable output current (OUT) due to external

power transistor Miller effect

VCC current

IO_MAX

-800

600

I_CC

V_HV

V_COMP

V_DC

V_ZX

HV Pin Voltage

-0.3

600

COMP Pin Voltage

VDC Pin Voltage

V_CC+ 0.3

-0.3

-5

ZX Pin Voltage

I_COMP

I_ZX

COMP Pin Current

ZX Pin Current

I_CS

CS Pin Current

Package Power Dissipation @ T_A +25ºC

P_D

(8-Pin SOIC)

---

P_D= (T_JMAX-T_A)/R_JA

R_JA

Thermal Resistance, Junction to Ambient

(8-Pin SOIC)

200

ºC/W

T_J

T_S

T_L

Junction Temperature

-55

---

150

300

Storage Temperature

ºC

Lead Temperature (soldering, 10 seconds)

†

This IC contains a zener clamp structure between the chip V_CCand COM which has a nominal breakdown

voltage of 20V. This supply pin should not be driven by a DC, low impedance power source greater than the

V_CLAMPspecified in the Electrical Characteristics section.

Recommended Operating Conditions

For proper operation the device should be used within recommended conditions.

Symbol

Definition

Min.

V_CCUV+

Max.

Units

V_CC

Supply Voltage

I_CC

I_CS

I_ZX

V_CCSupply Current

CS Pin Current

-1

ZX Pin Current

V_DC

V_CS

T_J

VDC Pin Voltage

CS Pin Voltage

6.0

1.3

125

0.1

-25

Junction Temperature

ºC

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January 15, 2015

IRS2983SPBF

Electrical Characteristics

V_CC=14V +/- 0.25V, C_OUT= 1000pF,

V_COMP= V_OC= V_BUS= V_ZX= 0V, T_A=25˚C unless otherwise specified

Symbol

Definition

Min

Typ Max

Units Test Conditions

Supply Characteristics

V_CCSupply Undervoltage Positive

Going Threshold

V_CCSupply Undervoltage Negative

Going Threshold

V_CCSupply Undervoltage Lockout

Hysteresis

V_CCUV

11.5

9.5

12.5

10.5

2.0

13.5

11.5

3.0

V_CCUV

V_UVHYS

1.5

I_QCCUV

I_CC

UVLO Mode V_CCQuiescent Current

---

150

2.5

---

5.0

V_CC= 6V

A

V_CCSupply Current

Zener Clamp Voltage

V_CC

V_CLAMP

I_CC= 10mA

19.8

20.8

21.8

High Voltage Startup Characteristics

V_HVSMIN

Minimum startup voltage

30.0

---

V <

V_CCUV-

I_{HV_CHARGE}

V_CCcharge current

HV=100V~400V

High voltage start-up circuit OFF

state leakage current

I_{HVS_OFF}

---

HV=400V

A

Error Amplifier Characteristics

I_COMP

COMP Pin Error Amplifier Output

Current Sourcing

COMP Pin Error Amplifier Output

Current Sinking

Error Amplifier Output Voltage

Swing (high state)

Error Amplifier Output Voltage

Swing (low state)

---

SOURCE

A

I_COMP

SINK

V_COMPOH

13.5

2.5

V_COMPOL

A

GBD

Error Amplifier Output Voltage in

Fault Mode

Input bias current

V_COMPFLT

I_VBUS

---

-1

V_BUS=0 to 3V

Control Characteristics

V_ZX+

V_ZX-

ZX Pin Threshold Voltage (Arm)

ZX Pin Threshold Voltage (Trigger)

Power Regulation Reference

Multiplier Gain

1.40

0.52

---

1.54

0.60

1.00

2.00

1.68

0.68

---

V_PREF

K_MULT

1.90

2.10

V_CS=0.5V

V_BUS=2.5V

COMP=4.0V

CS=1.5V

t_BLANK

OC pin current-sensing blank time

160

200

264

ZX = 0

COMP = 4.0V

t_WD

Gate Drive Restart Pulse Interval

PWM Minimum ON time

136

100

167

135

198

s

t_ONMIN

t_ONMAX

ZX = 0

COMP

PWM Maximum ON Time

= 13V

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January 15, 2015

IRS2983SPBF

Electrical Characteristics (cont’d)

V_CC=14V +/- 0.25V, C_OUT= 1000pF,

V_COMP= V_OC= V_BUS= V_ZX= 0V, T_A=25˚C unless otherwise specified.

Symbol

t_OFFMIN

V_{COMPOFF_HYS}

V_DCMAX

Definition

PWM Minimum OFF Time

Min

2.7

Typ Max

Units Test Conditions

3.0

---

3.3

---

s

Cut off voltage hysteresis

Maximum voltage for multiplier input^†

---

7.0

GBD

Signal is

averaged before

entering

multiplier input.

GBD

Maximum peak voltage for multiplier

input^†

V_CSPKMAX

---

1.0

Protection Circuitry Characteristics

V_CSTH

CS Pin Over-current Sense Threshold 1.19

1.25

1.40

1.31

1.68

Cut off voltage below which gate

V_COMPOFF

1.12

V_BUS=2.6V

drive output is disabled

ZX Pin Over-voltage Comparator

Threshold

ZX Pin Over-voltage Comparator

Hysteresis

V_OVTH

4.90

5.15

200

5.40

---

V_OVHYS

---

Gate Driver Output Characteristics (OUT pin)

V_OL

I_O= 0

Low-Level Output Voltage

---

100

–

V_CCV_O

V_OH

High-Level Output Voltage

I_O= 0

t_r

t_f

Turn-On Rise Time

Turn-Off Fall Time

Source Current

Sink Current

---

110

---

I0+

I0-

200

400

---

†

Multiplier operates accurately from zero to the maximum input specified.

GBD Guaranteed by design

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January 15, 2015

IRS2983SPBF

Functional Block Diagram

STARTUP

VCC

VCLAMP

VCC

UVLO

OUT

VDC

Set

dominant

VPREF

KMULT

Restart

Timer

COMP

COM

AVERAGER

Blank Timer

VCSTH

VOVTH

Minimum

Off Time

VZX+

/VZX-

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January 15, 2015

IRS2983SPBF

State Diagram

Power Turned On

UVLO Mode

ICC = IQCCUV

HVREG = On

OUT = Low

COMP = Held Low

Watchdog

Timeout

VCC > VCCUV+

VCS < VCSTH

-VOVHYS

Fault Mode

OUT = Low

COMP = Held Low

VZX > VOVTH

Current Limit

Startup Mode

OUT = Switching

OUT = Low

VCS > VCSTH

VMULT > 1V

VCS < VCSTH

-VOVHYS

Regulating Mode

OUT = Switching

HVREG = Off

VZX > VOVTH

VCS > VCSTH

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January 15, 2015

IRS2983SPBF

Input/Output Pin Equivalent Circuit Diagrams

VCC

COMP,

ESD

VDC,

Diode

CS,

ZX,

VCLAMP

OUT

ESD

Diode

COM

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IRS2983SPBF

Lead Definitions

Symbol

Description

High Voltage Startup Input

VDC

COMP

Full Wave Voltage Input

Compensation and averaging capacitor input

PFC Zero-Crossing & Over-Voltage Detection

PFC Current Sensing Input

COM

OUT

VCC

IC Power & Signal Ground

Gate Driver Output

Logic & Low-Side Gate Driver Supply

Lead Assignments

VCC

OUT

VDC

COM

COMP

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IRS2983SPBF

This “power” is then regulated against an accurate

internal reference (VPREF) to provide regulation

of the LED current typically within +/-5% over line

voltage variation from 120VAC to 230VAC.

Application Information and Additional

Details

The IRS2983 is a switched mode controller IC

designed for use in Flyback or Buck-Boost LED

drivers. An internal high voltage regulator supplies

the IC low voltage VCC supply during startup

allowing operation directly from a DC input voltage

up to 600V.

Input voltage is sensed through an appropriately

scaled resistor divider (RIN and RDC) to provide a

voltage at VDC within the range from 0V to

VDCMAX. Input current is sensed through a shunt

resistor (RCS) connected from the source of the

Flyback MOSFET switch to the DC bus return.

This current waveform is a high frequency ramp

rising from zero at the beginning of each switching

cycle to reach a peak level at the point the

MOSFET is switched off and remaining at zero

during the off time.

Internal high voltage regulator

In order to begin operating the IRS2983 requires

the low voltage VCC supply to be raised above the

under

voltage

lockout

positive threshold

(VCCUV+) and to continue operating VCC must

be maintained above the under voltage lockout

negative threshold (VCCUV-).

The HV regulator enables the IRS2983 based LED

driver to start up very rapidly and deliver light

within 0.5s of switch on over the range of line

voltage input. When the switching converter is

running VCC is normally supplied through an

auxiliary winding. When operating with primary

regulation (see below) as steady state operation is

reached the HV regulator is deactivated.

V(t)

VOUT(t)

VCS(t)

The auxiliary winding from the Flyback or Buck-

Boost inductor/transformer provides output voltage

and zero-crossing (ZX) information as well as

supplying VCC.

Figure 1: Current sense waveform

In the event of a short circuit at the output the VCC

supply from the auxiliary winding collapses below

VCCUV- causing the IRS2983 to shut off. The

startup sequence begins again in a continuous

“hiccup” mode until the short circuit is removed

thereby preventing damage to the circuit.

In order to obtain a DC current feedback signal the

IRS2983 contains an averaging circuit that takes

the CS pin input and converts it to a DC level

proportional to the converters input current. This

signal is then multiplied with the voltage (VDC)

input to produce an internal voltage proportional to

the converter input power. Loop compensation is

performed by means of a transconductance error

amplifier using an external capacitor (CCOMP)

connected to 0V to realize an integrator that

provides a stable error voltage used to control the

converter on time. CCOMP is typically 1μF.

The output current normally increases by a small

amount as the input voltage is increased. RADJ is

a resistor in the order of Meg-Ohms that can be

added to provide a small feed forward correction

to the current sense input allowing the output

current to be fine-tuned to give tighter regulation

over a wide input voltage range.

Primary power regulation

The IRS2983 can operate using primary regulation

or using a secondary feedback loop. It is capable

of regulating the LED output current indirectly by

calculating and controlling the input power of the

converter. Since the LED load voltage is

essentially constant, the power consumed is

approximately proportional to the DC output

current. In practice there are variations in LED

forward voltage drop due to tolerance and

temperature, however perfect accuracy is not

usually necessary in such applications. For a fixed

LED load the current will be approximately

proportional to the input power. The IRS2983

senses input voltage and inductor current and

uses these quantities to estimate the input power.

At light loads if VCOMP drops below VCOMPOL

the IRS2983 operates in burst mode.

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IRS2983SPBF

Primary current limiting

where,

At very low input voltages the power regulation

loop would require a very high peak current that

may exceed the maximum rating of the inductor. In

order to prevent this from occurring, the IRS2983

also includes cycle by cycle primary current

limiting with a threshold VCSTH at the CS pin

input. Under low line or fault conditions where the

MOSFET current is abnormally high the gate drive

is switched off after the blanking time tBLANK.

Leading edge blanking is necessary to avoid false

tripping due to the fast high current switch on

transient that occurs at switch on of the MOSFET

resulting from the circuit parasitics. This is also

blanked from the averaging input that feeds the

power regulation multiplier in order to prevent

inaccuracies.

The IRS2983 normally operates in critical

conduction mode (CrCM), also known as transition

or boundary mode. The transformer auxiliary

winding provides a signal to the IRS2983 that

indicates when all of the energy stored in the

inductor has been transferred to the output. This

triggers the start of the next switching cycle. The

auxiliary winding voltage is divided down through

RZX1 and RZX2 to provide the ZX pin input signal.

N_A= Number of turns on the auxiliary winding

N_S= Number of turns on the secondary winding

VOUT = DC Output Voltage (LED voltage)

When the converter MOSFET switches off the

voltage VZX transitions high. The values of RZX1

and RZX2 must be selected so that this voltage

always exceeds the VZX+ threshold.

If the IRS2983 is used in a converter that is

required to drive loads over a range of voltage an

additional feedback circuit is needed to control the

output current. In this case the VZX voltage needs

to exceed VZX+ at the minimum load voltage. If

VZX does not exceed VZX+ the IRS2983 cannot

operate in CrCM and remains pulsing and waiting

for tWD timeout for the next cycle. When VZX

exceeds VZX+ the IRS2983 waits until the VZX

then drops below VZX- again to initiate the next

switching cycle. A capacitor may be added in

parallel with RZX2 to add some delay if needed to

minimize switching loss by switching on in the

minimum point or “valley” of the drain voltage.

The IRS2983 includes a minimum off time function

so that if the ZX pin input transitions high and low

before tOFFMIN the gate drive output will not go

high again until after this period. This prevents

false tripping by ringing at the ZX input and also

limits the converter maximum switching frequency

by entering discontinuous mode (DCM) under

conditions where the off time would otherwise be

very short. This function extends the operating

range of the converter allowing operation down to

very low duty cycles. This thereby enables

dimming designs to be implemented as well as

limiting operating frequency to prevent overheating

of the circuit inductor, MOSFET and snubber

components.

V(t)

VOUT(t)

VCSTH

VCS(t)

Figure 2: Cycle by cycle current limiting

VZX(t)

V(t)

The pulse that appears at ZX has an amplitude

proportional to the secondary output voltage and

therefore the DC output voltage:

VOUT(t)

N_A RZX 2VOUT

N_S(RZX1 RZX 2)

VZX 

[1]

Figure 3: Zero crossing detection

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January 15, 2015

IRS2983SPBF

Over voltage protection

The ZX is a multi-function input also used for output

over voltage limiting. In a Flyback or Buck-Boost

converter if the load becomes disconnected the

output voltage can become very high causing

damage to components as well as presenting an

electrical hazard. In order to protect against this the

IRS2983 senses the output voltage indirectly

through the ZX input, which is proportional to the

actual output voltage. If the ZX input voltage

exceeds VOVTH when the MOSFET switches off the

gate drive remains switched off for a tWD period

before starting the next cycle regardless of when the

ZX voltage transitions low. The IRS2983 also

discharges the COMP capacitor to zero so that the

next cycle will begin at minimum duty cycle and

ramp up slowly. This protection scheme allows the

LED load to be hot connected and disconnected

from the converter output without risk of damaging

the circuit or of high voltages appearing at the

output. Care should be taken however to avoid LED

damage due to output capacitor discharge. An NTC

thermistor at the output may be needed to limit the

current surge. The overvoltage threshold is set by

choosing the values of RZX1 and RZX2

appropriately, according to the formula:

VCOMP(t)

VZX(t)

VOUT(t)

V(t)

twd

Figure 4: Overvoltage protection

The feedback circuit is usually fed through an opto

isolator. This can be connected to the IRS2983 in

the following way:

DVCC

RVCC

QVCC

CIN

IC1

DZX

RZX1

VCC

OUT

VDC

CVCC

COMP

COM

RPFC

VOVTH  N_S(RZX1 RZX 2)

VOUT_OV



[2]

MPFC

N_A RZX 2

Secondary error

feedback

RCS

CF2

The recommended over voltage threshold is 25%

above the normal operating voltage of the LED

load.

RZX2

Operating with a secondary feedback circuit

Figure 5: Secondary feedback circuit

In applications where accurate current regulation

over a wide input voltage range or range of output

voltages is required, the IRS2983 can be used in

conjunction with a secondary sensing and

feedback circuit.

A simple output voltage feedback scheme is

shown in figure 5 to illustrate how the opto isolator

is connected to the IRS2983 to create a feedback

circuit. The VDC input is tied to COM leaving the

internal multiplier output at zero so that the COMP

output provides pull up. The opto isolator feedback

pulls down on the COMP voltage to reduce the on

time as the opto diode current is increased driven

by a secondary error amplifier circuit. The HV

startup is not disabled in this operating mode but

draws only micro current if VCC is biased above

17V. This is easily done by using a series pass

transistor with the base biased with an 18V zener

diode to supply VCC.

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January 15, 2015

IRS2983SPBF

Package Details

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January 15, 2015

IRS2983SPBF

Tape and Reel Details

LOADED TAPE FEED DIRECTION

NOTE : CONTROLLING

DIMENSION IN MM

CARRIER TAPE DIMENSION FOR 8SOICN

Metric

Imperial

Min

0.311

0.153

0.46

Code

Min

7.90

3.90

11.70

5.45

6.30

5.10

1.50

Max

8.10

4.10

12.30

5.55

6.50

5.30

n/a

Max

0.318

0.161

0.484

0.218

0.255

0.208

n/a

0.214

0.248

0.200

0.059

1.60

0.062

REEL DIMENSIONS FOR 8SOICN

Metric

Imperial

Code

Min

329.60

20.95

12.80

1.95

98.00

n/a

14.50

12.40

Max

330.25

21.45

13.20

2.45

102.00

18.40

17.10

14.40

Min

12.976

0.824

0.503

0.767

3.858

n/a

Max

13.001

0.844

0.519

0.096

4.015

0.724

0.673

0.566

0.570

0.488

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January 15, 2015

IRS2983SPBF

Part Marking Information

Part number

Date code

S2983

YWW ?

IR logo

Pin 1

Identifier

? XXXX

Lot Code

(Prod mode –

4 digit SPN code)

MARKING CODE

Lead Free Released

Non-Lead Free Released

Assembly site code

Per SCOP 200-002

The information provided in this document is believed to be accurate and reliable. However, International Rectifier assumes no

responsibility for the consequences of the use of this information. International Rectifier assumes no responsibility for any infringement

of patents or of other rights of third parties which may result from the use of this information. No license is granted by implication or

otherwise under any patent or patent rights of International Rectifier. The specifications mentioned in this document are subject to

change without notice. This document supersedes and replaces all information previously supplied.

For technical support, please contact IR’s Technical Assistance Center

http://www.irf.com/technical-info/

WORLD HEADQUARTERS:

233 Kansas St., El Segundo, California 90245

Tel: (310) 252-7105

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January 15, 2015

IRS2983SPBF_15 [INFINEON]

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