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EL5150IWZ-T7A [INTERSIL]

200MHz Amplifiers; 200MHz的放大器
EL5150IWZ-T7A
型号： EL5150IWZ-T7A
厂家： Intersil    Intersil
描述：

200MHz Amplifiers
200MHz的放大器

商用集成电路 放大器 光电二极管
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EL5150, EL5151, EL5250, EL5251, EL5451  
®
Data Sheet  
February 14, 2005  
FN7384.4  
200MHz Amplifiers  
Features  
The EL5150, EL5151, EL5250, EL5251, and EL5451 are  
200MHz bandwidth -3dB voltage mode feedback amplifiers  
with DC accuracy of 0.01%, 1mV offsets and 10kV/V open  
loop gains. These amplifiers are ideally suited for  
applications ranging from precision measurement  
instrumentation to high speed video and monitor  
applications. Capable of operating with as little as 1.4mA of  
current from a single supply ranging from 5V to 12V, dual  
supplies ranging from ±2.5V to ±5.0V, these amplifiers are  
also well suited for handheld, portable and battery-powered  
equipment.  
• 200MHz -3dB bandwidth  
• 67V/µs slew rate  
• Very high open loop gains 50kV/V  
• Low supply current = 1.4mA  
• Single supplies from 5V to 12V  
• Dual supplies from ±2.5V to ±5V  
• Fast disable on the EL5150 and EL5250  
• Low cost  
• Pb-free available (RoHS compliant)  
Single amplifiers are offered in SOT-23 packages and duals  
in a 10-pin MSOP package for applications where board  
space is critical. Quad amplifiers are available in a 14-pin SO  
package. Additionally, singles and duals are available in the  
industry-standard 8-pin SO package. All parts operate over  
the industrial temperature range of -40°C to +85°C.  
Applications  
• Imaging  
• Instrumentation  
• Video  
• Communications devices  
Ordering Information  
TAPE &  
TAPE &  
PART NUMBER  
PACKAGE  
REEL  
PKG. DWG. #  
PART NUMBER  
PACKAGE  
REEL  
PKG. DWG. #  
EL5150IS  
8-Pin SO  
-
MDP0027  
EL5151IWZ-T7A  
(See Note)  
5-Pin SOT-23 7” (250 pcs)  
(Pb-Free)  
MDP0038  
EL5150IS-T7  
EL5150IS-T13  
8-Pin SO  
8-Pin SO  
7”  
13”  
-
MDP0027  
MDP0027  
MDP0027  
EL5250IY  
10-Pin MSOP  
10-Pin MSOP  
10-Pin MSOP  
-
MDP0043  
MDP0043  
MDP0043  
EL5250IY-T7  
EL5250IY-T13  
7”  
EL5150ISZ  
(See Note)  
8-Pin SO  
(Pb-Free)  
13”  
EL5150ISZ-T7  
(See Note)  
8-Pin SO  
(Pb-Free)  
7”  
13”  
MDP0027  
MDP0027  
EL5251IS  
8-Pin SO  
8-Pin SO  
-
MDP0027  
MDP0027  
EL5150ISZ-T13  
(See Note)  
8-Pin SO  
(Pb-Free)  
EL5251IS-T7  
7”  
EL5150IW-T7  
6-Pin SOT-23  
7” (3K pcs)  
MDP0038  
MDP0038  
MDP0038  
EL5251IS-T13  
EL5251IY  
8-Pin SO  
13”  
-
MDP0027  
MDP0043  
MDP0043  
EL5150IW-T7A  
6-Pin SOT-23 7” (250 pcs)  
8-Pin MSOP  
8-Pin MSOP  
EL5150IWZ-T7  
(See Note)  
6-Pin SOT-23  
(Pb-Free)  
7” (3K pcs)  
EL5251IY-T7  
7”  
EL5150IWZ-T7A  
(See Note)  
6-Pin SOT-23 7” (250 pcs)  
(Pb-Free)  
MDP0038  
EL5251IY-T13  
8-Pin MSOP  
13”  
MDP0043  
EL5151IW-T7  
5-Pin SOT-23  
7” (3K pcs)  
MDP0038  
MDP0038  
MDP0038  
EL5451IS  
14-Pin SO  
14-Pin SO  
14-Pin SO  
-
MDP0027  
MDP0027  
MDP0027  
EL5151IW-T7A  
5-Pin SOT-23 7” (250 pcs)  
EL5451IS-T7  
EL5451IS-T13  
7”  
EL5151IWZ-T7  
(See Note)  
5-Pin SOT-23  
(Pb-Free)  
7” (3K pcs)  
13”  
NOTE: Intersil Pb-free products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination  
finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at  
Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020C.  
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.  
1
1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc.  
Copyright © Intersil Americas Inc. 2004-2005. All Rights Reserved.  
All other trademarks mentioned are the property of their respective owners.  
EL5150, EL5151, EL5250, EL5251, EL5451  
Pinouts  
EL5150  
(8-PIN SO)  
TOP VIEW  
EL5150  
(6-PIN SOT-23)  
TOP VIEW  
EL5151  
(5-PIN SOT-23)  
TOP VIEW  
NC  
IN-  
1
2
3
4
8
7
6
5
CE  
OUT  
VS-  
IN+  
1
2
3
6
5
4
VS+  
CE  
OUT  
VS-  
IN+  
1
2
3
5
4
VS+  
IN-  
VS+  
OUT  
NC  
-
+
+
-
+ -  
IN+  
VS-  
IN-  
EL5250  
(10-PIN MSOP)  
TOP VIEW  
EL5251  
(8-PIN MSOP)  
TOP VIEW  
EL5451  
(14-PIN SO)  
TOP VIEW  
INA+  
CEA  
VS-  
INA-  
OUTA  
INA-  
INA+  
VS-  
OUTA  
INA-  
1
2
3
4
5
10  
9
1
2
3
4
8
7
6
5
VS+  
1
2
3
4
5
6
7
14 OUTD  
13 IND-  
12 IND+  
11 VS-  
-
+
OUTA  
VS+  
-
+
OUTB  
INB-  
-
-
+
+
+
+
-
-
8
INA+  
VS+  
-
+
+
-
OUTB  
INB-  
CEB  
INB+  
7
INB+  
6
INB+  
INB-  
10 INC+  
9
8
INC-  
OUTB  
OUTC  
FN7384.4  
February 14, 2005  
2
EL5150, EL5151, EL5250, EL5251, EL5451  
Absolute Maximum Ratings (T = 25°C)  
A
Supply Voltage between V and GND. . . . . . . . . . . . . . . . . . . 13.2V  
S
Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 40mA  
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . .-40°C to +125°C  
Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C  
Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C  
Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to V +0.5V  
S
Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves  
Current into I +, I -, CE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5mA  
N N  
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the  
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.  
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests  
are at the specified temperature and are pulsed tests, therefore: T = T = T  
A
J
C
Electrical Specifications V + = +5V, V - = -5V, R = 150Ω, T = 25°C, unless otherwise specified.  
S
S
L
A
PARAMETER  
DESCRIPTION  
CONDITIONS  
MIN  
TYP  
MAX  
UNIT  
AC PERFORMANCE  
BW  
-3dB Bandwidth  
A
= +1, R = 500Ω  
200  
40  
MHz  
MHz  
MHz  
MHz  
V/µs  
V/µs  
ns  
V
L
A
= +2, R = 150Ω  
V
L
GBWP  
BW1  
SR  
Gain Bandwidth Product  
0.1dB Bandwidth  
Slew Rate  
A
= 500  
40  
V
A
= +1, R = 500Ω  
10  
V
L
V
V
V
= ±2.5V, A = +2  
50  
67  
O
V
= ±3.0V, A = 1, R = 500Ω  
100  
80  
O
V
L
t
0.1% Settling Time  
= -1V to +1V, A = -2  
OUT V  
S
dG  
dP  
Differential Gain Error (Note 1)  
Differential Phase Error (Note 1)  
Input Referred Voltage Noise  
Input Referred Current Noise  
A
= +2, R = 150Ω  
0.04  
0.9  
12  
%
V
L
A
= +2, R = 150Ω  
°
V
L
V
nV/√Hz  
pA/√Hz  
N
I
1.0  
N
DC PERFORMANCE  
V
Offset Voltage  
-1  
0.5  
-2  
1
mV  
OS  
T V  
Input Offset Voltage Temperature  
Coefficient  
Measured from T  
MIN  
to T  
MAX  
µV/°C  
C
OS  
A
Open Loop Gain  
15  
56  
kV/V  
VOL  
INPUT CHARACTERISTICS  
CMIR  
Common Mode Input Range  
Guaranteed by CMRR test  
-3.5  
85  
+3.5  
V
CMRR  
Common Mode Rejection Ratio  
Input Bias Current  
100  
20  
6
dB  
nA  
nA  
MΩ  
pF  
I
I
-100  
-30  
80  
+100  
30  
B
Input Offset Current  
Input Resistance  
OS  
R
170  
1
IN  
IN  
C
Input Capacitance  
OUTPUT CHARACTERISTICS  
V
Output Voltage Swing Low  
R
R
R
= 150Ω to GND  
= 500Ω to GND  
= 10Ω to GND  
±2.5  
±3.1  
±40  
±2.8  
±3.4  
±70  
V
V
OUT  
L
L
L
I
Output Current  
mA  
OUT  
FN7384.4  
February 14, 2005  
3
EL5150, EL5151, EL5250, EL5251, EL5451  
Electrical Specifications V + = +5V, V - = -5V, R = 150Ω, T = 25°C, unless otherwise specified. (Continued)  
S
S
L
A
PARAMETER  
DESCRIPTION  
CONDITIONS  
MIN  
TYP  
MAX  
UNIT  
ENABLE (SELECTED PACKAGES ONLY)  
t
t
I
I
Enable Time  
EL5150  
EL5150  
210  
620  
5
ns  
ns  
µA  
µA  
V
EN  
Disable Time  
DIS  
CE Pin Input High Current  
CE Pin Input Low Current  
CE = V +  
1
25  
+1  
IHCE  
ILCE  
S
CE = V + - 5V  
S
-1  
0
V
V
CE Input High Voltage for Powerdown  
CE Input Low Voltage for Powerdown  
Disable  
Enable  
V + -1  
S
IHCE  
ILCE  
V + -3  
S
V
SUPPLY  
I
I
I
Supply Current - Enabled (per amplifier) No load, V = 0V, CE = +5V  
IN  
1.12  
-10  
-25  
80  
1.35  
-1  
1.6  
+5  
0
mA  
µA  
µA  
dB  
SON  
Supply Current - Disabled (per amplifier)  
SOFF+  
SOFF-  
Supply Current - Disabled (per amplifier) No load, V = 0V  
IN  
-14  
110  
PSRR  
Power Supply Rejection Ratio  
DC, V = ±3.0V to ±6.0V  
S
NOTE:  
1. Standard NTSC test, AC signal amplitude = 286mV , f = 3.58MHz, V  
P-P  
is swept from 0.8V to 3.4V, R is DC coupled.  
L
OUT  
Typical Performance Curves  
100  
80  
60  
40  
20  
0
-45  
0
180  
90  
A =+1  
V
R =500Ω  
L
R =0Ω  
45  
0
-90  
F
A =+2  
V
R =150Ω  
L
90  
R =400Ω  
F
A =+5  
V
R =500Ω  
R =1.5KΩ  
L
F
135  
180  
-180  
-270  
1K  
10K  
100K  
1M  
10M  
100M  
1G  
100K  
1M  
10M  
FREQUENCY (Hz)  
100M  
1G  
FREQUENCY (Hz)  
FIGURE 1. EL5150 FREQUENCY vs OPEN LOOP  
GAIN/PHASE  
FIGURE 2. PHASE vs FREQUENCY FOR VARIOUS GAINS  
FN7384.4  
February 14, 2005  
4
EL5150, EL5151, EL5250, EL5251, EL5451  
Typical Performance Curves (Continued)  
5
3
5
3
A =+1  
V =±5V  
S
V
C =5pF  
A =+2  
L
V
R =R =402Ω  
F
G
1
1
R =1kΩ  
L
R =500Ω  
L
-1  
-3  
-5  
-1  
-3  
-5  
R =500Ω  
L
R =200Ω  
L
R =150Ω  
L
R =300Ω  
L
R =100Ω  
R =100Ω  
L
L
100K  
1M  
10M  
100M  
1G  
0.1  
1
10  
100  
FREQUENCY (Hz)  
FREQUENCY (Hz)  
FIGURE 3. EL5150 GAIN vs FREQUENCY FOR VARIOUS R  
FIGURE 4. EL5150 GAIN vs FREQUENCY FOR VARIOUS R  
L
L
L
L
L
L
4
5
A =+5  
A =+1  
V
L
V
R =1.5kΩ  
R =500Ω  
F
C =15pF  
C =5pF  
L
L
2
0
3
1
C =8.2pF  
L
R =500Ω  
L
R =400Ω  
L
C =3.9pF  
-2  
-4  
-6  
-1  
-3  
-5  
L
C =0pF  
L
R =200Ω  
L
R =100Ω  
L
100K  
1M  
10M  
100M  
100K  
1M  
10M  
FREQUENCY (Hz)  
100M 300M  
FREQUENCY (Hz)  
FIGURE 5. EL5150 GAIN vs FREQUENCY FOR VARIOUS R  
5
FIGURE 6. EL5150 GAIN vs FREQUENCY FOR VARIOUS C  
5
A =+2  
C =68pF  
A =+5  
V
V
L
R =500Ω  
R =1.5kΩ  
L
F
C =47pF  
L
C =82pF  
R =R =400Ω  
R =500Ω  
L
F
G
L
3
1
3
1
C =68pF  
L
C =22pF  
L
C =47pF  
L
-1  
-3  
-1  
-3  
-5  
C =0pF  
L
C =15pF  
L
C =0pF  
L
-5  
100K  
1M  
10M  
100M  
100K  
1M  
FREQUENCY (Hz)  
10M  
30M  
FREQUENCY (Hz)  
FIGURE 7. EL5150 GAIN vs FREQUENCY FOR VARIOUS C  
FIGURE 8. EL5150 GAIN vs FREQUENCY FOR VARIOUS C  
FN7384.4  
February 14, 2005  
5
EL5150, EL5151, EL5250, EL5251, EL5451  
Typical Performance Curves (Continued)  
5
3
4
2
A =+1  
A =+2  
V
V
C
-=4.7pF  
IN  
C =12pF  
IN  
C
-=18pF  
IN  
R =500Ω  
R =500Ω  
L
L
C =5pF  
C =5pF  
L
L
C
-=12pF  
IN  
-=8.2pF  
R =R =400Ω  
F
G
C
IN  
1
0
C
=8.2pF  
IN  
C
-=3.3pF  
IN  
-1  
-3  
-5  
-2  
-4  
C
=3.9pF  
IN  
C
-=0pF  
IN  
C
=0pF  
IN  
C
-=1pF  
IN  
-6  
100K  
100K  
1M  
10M  
FREQUENCY (Hz)  
100M 400M  
1M  
10M  
100M  
FREQUENCY (Hz)  
FIGURE 9. EL5150 GAIN vs FREQUENCY FOR VARIOUS C  
-
FIGURE 10. EL5150 GAIN vs FREQUENCY FOR VARIOUS C  
4
IN  
IN  
4
A =+5  
V
C
-=33pF  
A =+5  
V
IN  
C
-=100pF  
R =1.5kΩ  
R =1.5kΩ  
IN  
F
F
R =500Ω  
R =500Ω  
L
L
L
2
0
2
0
C =5pF  
C =5pF  
C
-=68pF  
IN  
L
R =500Ω  
L
C
-=8.2pF  
IN  
C
-=8pF  
IN  
R =300Ω  
L
-2  
-4  
-6  
-2  
-4  
-6  
C
-=3.3pF  
IN  
C
R =200Ω  
L
-=0pF  
IN  
R =100Ω  
L
R =50Ω  
L
100K  
1M  
FREQUENCY (Hz)  
10M  
40M  
100K  
1M  
10M  
30M  
FREQUENCY (Hz)  
FIGURE 11. EL5150 GAIN vs FREQUENCY FOR VARIOUS C  
-
FIGURE 12. EL5250 GAIN vs FREQUENCY FOR VARIOUS R  
IN  
L
5
4
A =+2  
R =500Ω  
L
L
V
R =R =3kΩ  
F
G
R =500Ω  
C =5pF  
L
C =5pF  
L
R =R =2kΩ  
3
1
2
0
F
G
A =+1  
V
R =R =1kΩ  
F
G
A =+2  
V
-1  
-3  
-5  
-2  
-4  
-6  
R =R =500Ω  
F
G
A =+3  
V
R =R =100Ω  
F
G
100K  
1M  
10M  
100M  
100K  
1M  
10M  
100M 300M  
FREQUENCY (Hz)  
FREQUENCY (Hz)  
FIGURE 13. EL5150 GAIN vs FREQUENCY FOR VARIOUS  
R /R  
FIGURE 14. EL5250 GAIN vs FREQUENCY FOR VARIOUS  
GAINS  
F
G
FN7384.4  
February 14, 2005  
6
EL5150, EL5151, EL5250, EL5251, EL5451  
Typical Performance Curves (Continued)  
4
2
0
20  
R =500Ω  
L
BOTH CHANNELS SHOWN  
A =+1  
V
POSITIVE SUPPLY  
L
C =5pF  
A =+1  
V
0
40  
A =+2  
V
-2  
-4  
-6  
60  
A =+3  
V
80  
100  
1K  
100K  
1M  
10M  
100M  
10K  
100K  
1M  
10M  
100M  
FREQUENCY (Hz)  
FREQUENCY RESPONSE (Hz)  
FIGURE 15. EL5250 GAIN vs FREQUENCY FOR VARIOUS  
GAINS  
FIGURE 16. PSRR vs FREQUENCY  
0
-40  
-50  
-60  
-70  
-80  
-90  
A =+1  
V
A =+2  
V
NEGATIVE SUPPLY  
R =500Ω  
L
C =5pF  
L
20  
40  
IN CHANNEL A  
OUT CHANNEL B  
60  
80  
100  
1K  
10K  
100K  
1M  
10M  
100M  
100K  
1M  
10M  
100M  
FREQUENCY RESPONSE (Hz)  
FREQUENCY (Hz)  
FIGURE 17. PSRR vs FREQUENCY  
FIGURE 18. EL5250 CROSSTALK vs FREQUENCY  
1K  
40  
50  
60  
70  
80  
90  
A =+2  
A =+2  
V
V
R =500Ω  
L
C =5pF  
L
100  
10  
IN CHANNEL B  
OUT CHANNEL A  
1
0.1  
0.001  
100K  
1M  
10M  
100M  
1K  
10K  
100K  
1M  
10M  
100M  
FREQUENCY (Hz)  
FREQUENCY (Hz)  
FIGURE 19. EL5250 CROSSTALK vs FREQUENCY  
FIGURE 20. OUTPUT IMPEDANCE  
FN7384.4  
February 14, 2005  
7
EL5150, EL5151, EL5250, EL5251, EL5451  
Typical Performance Curves (Continued)  
0
20  
2500  
1500  
500  
A =+2  
A =+1  
V
V
R =500Ω  
L
C =5pF  
L
40  
60  
-500  
80  
-1500  
100  
100  
-2500  
1K  
10K  
100K  
1M  
10M  
100M  
1M  
10M  
100M  
600M  
FREQUENCY (Hz)  
FREQUENCY (Hz)  
FIGURE 21. CMRR  
FIGURE 22. GROUP DELAY  
3
2.5  
2
100  
10  
1
A =+1  
V
R =500Ω  
L
C =5pF  
L
1.5  
1
0.5  
0
0.1  
100  
1
1.5  
2
2.5  
3
3.5  
4
4.5  
5
1K  
10K  
100K  
SUPPLY VOLTAGE (V)  
FREQUENCY (Hz)  
FIGURE 23. SUPPLY CURRENT vs SUPPLY VOLTAGE  
FIGURE 24. VOLTAGE + CURRENT NOISE vs FREQUENCY  
90  
80  
105  
100  
95  
3RD HD  
2ND HD  
70  
60  
50  
40  
30  
20  
10  
0
90  
85  
80  
A =+1  
V
R =500Ω  
L
75  
C =2.2pF  
L
FREQ=1.9MHz  
70  
2.2  
0
1
2
3
4
5
6
7
8
9
2.7  
3.2  
3.7  
4.2  
4.7  
5.2  
5.7  
6.2  
OUTPUT SWING (V  
)
SPLIT POWER SUPPLY (V)  
P-P  
FIGURE 25. DISTORTION vs OUTPUT AMPLITUDE  
FIGURE 26. SLEW RATE vs POWER SUPPLY  
FN7384.4  
February 14, 2005  
8
EL5150, EL5151, EL5250, EL5251, EL5451  
Typical Performance Curves (Continued)  
-30  
-40  
-50  
-60  
-70  
-20  
-30  
-40  
-50  
-60  
-70  
A =+5  
A =+5  
V
V
V =±5V  
V =±5V  
S
S
R =500Ω  
R =500Ω  
L
L
THD  
R =402Ω  
R =402Ω  
F
F
OUT  
V
=2V  
THD_Fin=2MHz  
P-P  
2ND HD  
3RD HD  
THD_Fin=500kHz  
0
1
2
3
4
5
7
8
0.5  
1
10  
OUTPUT VOLTAGE (V  
)
FUNDAMENTAL FREQUENCY (MHz)  
P-P  
FIGURE 27. TOTAL HARMONIC DISTORTION vs OUTPUT  
VOLTAGE  
FIGURE 28. HARMONIC DISTORTION vs FREQUENCY  
A =+1  
A =+1  
V
V
R =500Ω  
R =500Ω  
L
L
C =2.2pF  
C =2.2pF  
L
L
20%-80%  
CH3 RISE  
1.874ns  
80%-20%  
CH3 FALL  
3.106ns  
20%-80%  
CH3 RISE  
11.72ns  
80%-20%  
CH3 FALL  
15.28ns  
TIME (40ns/DIV)  
TIME (40ns/DIV)  
FIGURE 29. SMALL SIGNAL STEP RESPONSE  
FIGURE 30. LARGE SIGNAL STEP RESPONSE  
A =+2  
A =+2  
V
V
R =150Ω  
R =150Ω  
L
L
C =2.2pF  
C =2.2pF  
L
L
20%-80%  
CH3 RISE  
4.337ns  
80%-20%  
CH3 FALL  
6.229ns  
20%-80%  
CH3 RISE  
12.87ns  
80%-20%  
CH3 FALL  
15.67ns  
TIME (40ns/DIV)  
TIME (40ns/DIV)  
FIGURE 31. SMALL SIGNAL STEP RESPONSE  
FIGURE 32. LARGE SIGNAL STEP RESPONSE  
FN7384.4  
February 14, 2005  
9
EL5150, EL5151, EL5250, EL5251, EL5451  
Typical Performance Curves (Continued)  
A =+1  
R =500Ω  
V
L
R =500Ω  
SUPPLY=±5.0V, ±2.7mA  
L
CH 1  
CH 4  
CH 2  
210ns  
ENABLE  
620ns  
DISABLE  
800ns  
ENABLE  
520ns  
DISABLE  
TIME (400ns/DIV)  
TIME (1µs/DIV)  
FIGURE 33. EL5150 ENABLE/DISABLE  
FIGURE 34. EL5250 ENABLE/DISABLE  
0.06  
1.5  
0.04  
0.02  
0
1.0  
0.5  
0
-0.02  
-0.04  
-0.5  
-1.0  
0
10 20 30 40 50 60 70 80 90 100  
IRE  
0
10 20 30 40 50 60 70 80 90 100  
IRE  
FIGURE 35. DIFFERENTIAL GAIN  
FIGURE 36. DIFFERENTIAL PHASE  
4
2
-50  
-70  
A =+1  
A =+1  
V
V
R =500Ω  
R =500Ω  
L
L
C =5pF  
C =2.7pF  
L
L
0
-90  
±2.0V  
-2  
-4  
-6  
-110  
-130  
-150  
±6.0V  
100K  
1M  
10M  
100M 300M  
100K  
1M  
10M  
100M 300M  
FREQUENCY (Hz)  
FREQUENCY (Hz)  
FIGURE 37. SMALL SIGNAL FREQUENCY vs SUPPLY  
FIGURE 38. INPUT-TO-OUTPUT ISOLATION WITH PART  
DISABLED  
FN7384.4  
February 14, 2005  
10  
EL5150, EL5151, EL5250, EL5251, EL5451  
Typical Performance Curves (Continued)  
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL  
CONDUCTIVITY TEST BOARD  
JEDEC JESD51-3 LOW EFFECTIVE THERMAL  
CONDUCTIVITY TEST BOARD  
1.4  
1.2  
1
1
0.9  
0.8  
0.7  
0.6  
0.5  
0.4  
0.3  
0.2  
0.1  
0
833mW  
1.136W  
SO14  
SO14  
=120°C/W  
θ
=88°C/W  
JA  
θ
JA  
909mW  
625mW  
486mW  
SO8  
=110°C/W  
SO8  
=160°C/W  
JA  
0.8 870mW  
θ
θ
JA  
0.6  
MSOP8/10  
435mW  
391mW  
θ
=206°C/W  
JA  
MSOP8/10  
0.4  
θ
=115°C/W  
SOT23-5/6  
θ =265°C/W  
JA  
JA  
SOT23-5/6  
0.2  
0
θ
=230°C/W  
JA  
0
25  
50  
75 85 100  
125  
150  
0
25  
50  
75 85 100  
125  
150  
AMBIENT TEMPERATURE (°C)  
AMBIENT TEMPERATURE (°C)  
FIGURE 39. PACKAGE POWER DISSIPATION vs AMBIENT  
TEMPERATURE  
FIGURE 40. PACKAGE POWER DISSIPATION vs AMBIENT  
TEMPERATURE  
accordingly; for instance, if the load resistor is 150Ω, the  
output swing ranges from -3.5V to 3.5V. This response is a  
simple application of Ohms law indicating a lower value  
resistance results in greater current demands of the  
amplifier. Additionally, the load resistance affects the  
frequency response of this family as well as all operational  
amplifiers; as clearly indicated by the Gain Vs Frequency For  
Various RL curves clearly indicate. In the case of the  
frequency response reduced bandwidth with decreasing  
load resistance is a function of load resistance in conjunction  
with the output zero response of the amplifier.  
Product Description  
The EL5150, EL5151, EL5250, EL5251 and EL5451 are  
wide bandwidth, low power, low offset voltage feedback  
operational amplifiers capable of operating from a single or  
dual power supplies. This family of operational amplifiers are  
internally compensated for closed loop gain of +1 or greater.  
Connected in voltage follower mode, driving a 500Ω load  
members of this amplifier family demonstrate a -3dB  
bandwidth of about 200MHz. With the loading set to  
accommodate typical video application, 150Ω load and gain  
set to +2, bandwidth reduces to about 40MHz with a 67V/µs  
slew rate. Power down pins on the EL5151 and EL5251  
reduce the already low power demands of this amplifier  
family to 12µA typical while the amplifier is disabled.  
Choosing A Feedback Resistor  
A feedback resistor is required to achieve unity gain; simply  
short the output pin to the inverting input pin. Gains greater  
than +1 require a feedback and gain resistor to set the  
desired gain. This gets interesting because the feedback  
resistor forms a pole with the parasitic capacitance at the  
inverting input; as the feedback resistance increases the  
position of the pole shifts in the frequency domain, the  
amplifier's phase margin is reduced and the amplifier  
becomes less stable. Peaking in the frequency domain and  
ringing in the time domain are symptomatic of this shift in  
pole location. So we want to keep the feedback resistor as  
small as possible. You may want to use a large feedback  
resistor for some reason; in this case to compensate the shift  
of the pole and maintain stability a small capacitor in the few  
Pico farad range in parallel with the feedback resistor is  
recommended.  
Input, Output and Supply Voltage Range  
The EL5150 and family members have been designed to  
operate with supply voltage ranging from 5V to 12V. Supply  
voltages range from ±2.5V to ±5V for split supply operation.  
And of course split supply operation can easily be achieved  
using single supplies with by splitting off half of the single  
supply with a simple voltage divider as illustrated in the  
application circuit section.  
Input Common Mode Range  
These amplifiers have an input common mode voltage  
ranging from 3.5V above the negative supply (V - pin) to  
3.5V below the positive supply (V + pin). If the input signal is  
driven beyond this range the output signal will exhibit  
distortion.  
S
S
For the gains greater than unity it has been determined a  
feedback resistance ranging from 500Ω to 750Ω provides  
optimal response.  
Maximum Output Swing & Load Resistance  
The outputs of the EL5150 and family members exhibit  
maximum output swing ranges from -4V to 4V for V = ±5V  
S
with a load resistance of 500Ω. Naturally, as the load  
resistance becomes lower, the output swing lowers  
FN7384.4  
February 14, 2005  
11  
EL5150, EL5151, EL5250, EL5251, EL5451  
ranging from 70mA and 95mA can be expected and  
Gain Bandwidth Product  
naturally, if the output is shorted indefinitely the part can  
easily be damaged from overheating; or excessive current  
density may eventually compromise metal integrity.  
Maximum reliability is maintained if the output current is  
always held below ±40mA. This limit is set and limited by the  
design of the internal metal interconnect. Note that in  
transient applications, the part is extremely robust.  
The EL5150 and family members have a gain bandwidth  
product of 40MHz for a gain of +5. Bandwidth can be  
predicted by the following equation:  
(Gain) x (BW) = GainBandwidthProduct  
Video Performance  
For good video performance, an amplifier is required to  
maintain the same output impedance and same frequency  
response as DC levels are changed at the output; this  
characteristic is widely referred to as “diffgain-diffphase”.  
Many amplifiers have a difficult time with this especially while  
driving standard video loads of 150Ω, as the output current  
has a natural tendency to change with DC level. The dG and  
dP for these families is a respectable 0.04% and 0.9°, while  
driving 150Ω at a gain of 2. Driving high impedance loads  
would give a similar or better dG and dP performance as the  
current output demands placed on the amplifier lessen with  
increased load.  
Power Dissipation  
With the high output drive capability of these devices, it is  
possible to exceed the 125°C absolute maximum junction  
temperature under certain load current conditions.  
Therefore, it is important to calculate the maximum junction  
temperature for an application to determine if load conditions  
or package types need to be modified to assure operation of  
the amplifier in a safe operating area.  
The maximum power dissipation allowed in a package is  
determined according to:  
T
– T  
AMAX  
JMAX  
Driving Capacitive Loads  
--------------------------------------------  
PD  
=
MAX  
Θ
JA  
These devices can easily drive capacitive loads as  
demanding as 27pF in parallel with 500Ω while holding  
peaking to within 5dB of peaking at unity gain. Of course if  
less peaking is desired, a small series resistor (usually  
between 5Ω to 50Ω) can be placed in series with the output  
to eliminate most peaking; however, there will be a small  
sacrifice of gain which can be recovered by simply adjusting  
the value of the gain resistor.  
Where:  
T
= Maximum junction temperature  
= Maximum ambient temperature  
JMAX  
T
AMAX  
q
= Thermal resistance of the package  
JA  
The maximum power dissipation actually produced by an IC  
is the total quiescent supply current times the total power  
supply voltage, plus the power in the IC due to the load, or:  
Driving Cables  
Both ends of all cables must always be properly terminated;  
double termination is absolutely necessary for reflection-free  
performance. Additionally, a back-termination series resistor  
at the amplifier's output will isolate the amplifier from the  
cable and allow extensive capacitive drive. However, other  
applications may have high capacitive loads without a back-  
termination resistor. Again, a small series resistor at the  
output can help to reduce peaking.  
For sourcing:  
n
V
OUTi  
-----------------  
PD  
= V × I  
+
+
(V – V  
) ×  
MAX  
S
SMAX  
S
OUTi  
∑
R
Li  
i = 1  
For sinking:  
n
PD  
= V × I  
(V  
– V ) × I  
OUTi S LOADi  
MAX  
S
SMAX  
∑
Disable/Power-Down  
i = 1  
Devices with disable can be disabled with their output placed  
in a high impedance state. The turn off time is about 330ns  
and the turn on time is about 130ns. When disabled, the  
amplifier's supply current is reduced to 17µA typically;  
essentially eliminating power consumption. The amplifier's  
power down is controlled by standard TTL or CMOS signal  
levels at the ENABLE pin. The applied logic signal is relative  
Where:  
V = Supply voltage  
S
I
= Maximum quiescent supply current  
SMAX  
V
= Maximum output voltage of the application  
OUT  
R
= Load resistance tied to ground  
LOAD  
to V - pin. Letting the ENABLE pin float or the application of  
S
I
= Load current  
a signal that is less than 0.8V above V - enables the  
S
LOAD  
amplifier. The amplifier is disabled when the signal at  
ENABLE pin is above V + -1.5V.  
S
N = number of amplifiers (Max = 2)  
By setting the two PD equations equal to each other, we  
MAX  
Output Drive Capability  
can solve the output current and R  
to avoid the device  
LOAD  
Members of the EL5150 family do not have internal short  
circuit protection circuitry. Typically, short circuit currents  
overheat.  
FN7384.4  
February 14, 2005  
12  
EL5150, EL5151, EL5250, EL5251, EL5451  
compromised performance. Minimizing parasitic capacitance  
Power Supply Bypassing Printed Circuit Board  
Layout  
at the amplifier's inverting input pin is very important. The  
feedback resistor should be placed very close to the  
inverting input pin. Strip line design techniques are  
recommended for the signal traces.  
As with any high frequency device, a good printed circuit  
board layout is necessary for optimum performance. Lead  
lengths should be as short as possible. The power supply  
pin must be well bypassed to reduce the risk of oscillation.  
Application Circuits  
For normal single supply operation, where the V - pin is  
S
connected to the ground plane, a single 4.7µF tantalum  
capacitor in parallel with a 0.1µF ceramic capacitor from V +  
to GND will suffice. This same capacitor combination should  
be placed at each supply pin to ground if split supplies are to  
Sullen Key Low Pass Filter  
S
A common and easy to implement filter taking advantage of  
the wide bandwidth, low offset and low power demands of  
the EL5150. A derivation of the transfer function is provided  
for convenience. (see Figure 39)  
be used. In this case, the V - pin becomes the negative  
S
supply rail.  
Sullen Key High Pass Filter  
Printed Circuit Board Layout  
Again, this useful filter benefits from the characteristics of the  
EL5150. The transfer function is very similar to the low pass  
so only the results are presented.(see Figure 40)  
For good AC performance, parasitic capacitance should be  
kept to a minimum. Use of wire wound resistors should be  
avoided because of their additional series inductance. Use  
of sockets should also be avoided if possible. Sockets add  
parasitic inductance and capacitance that can result in  
RB  
K = 1+  
RA  
1
5V  
V2  
Vo = K  
V1  
R2C2s +1  
0.1µF  
Vo  
V1− Vi  
R1  
Vo − Vi  
1
K − V1  
1+  
+
= 0  
R2  
C1s  
K
H(s) =  
2
R1C1R2C2s + ((1− K)R1C1+ R1C2 + R21C2)s +1  
1
C1  
1n  
H(jw) =  
2
1− w R1C1R2C2 + jw((1− K)R1C1+ R1C2 + R2C2)  
R1  
1K  
U1A  
+
R2  
1K  
Holp = K  
4
3
1
1
V+  
V-  
wo =  
V
OUT  
1n  
R1C1R2C2  
2
V1  
C2  
-
1
R7  
11  
Q =  
1K  
R1C1  
R1C2  
R2C1  
R2C2  
R1C1  
1K  
(1− K)  
+
+
R2C2  
RB  
RA  
1K  
Holp = K  
Equations simplify if we let all  
components be equal R=C  
1
wo =  
RC  
1
0.1µF  
Q =  
3 − K  
5V  
V3  
FIGURE 41. SULLEN KEY LOW PASS FILTER  
FN7384.4  
February 14, 2005  
13  
EL5150, EL5151, EL5250, EL5251, EL5451  
5V  
V2  
0.1µF  
Holp = K  
1
R8  
wo =  
R1C1R2C2  
1K  
3
C7  
1n  
U1A  
+
C9  
1n  
4
1
Q =  
1
V+  
V-  
V
R1C1  
R1C2  
R2C1  
R2C2  
R1C1  
OUT  
1n  
(1− K)  
+
+
2
V1  
C2  
R2C2  
-
R7  
11  
1K  
1K  
RB  
RA  
1K  
K
Holp =  
wo =  
4 − K  
Equations simplify if we let  
all components be equal R=C  
2
RC  
0.1µF  
2
Q =  
4 − K  
5V  
V3  
FIGURE 42. SULLEN KEY HIGH PASS FILTER  
Differential Output Instrumentation Amplifier  
A
1
R
R
3
3
e
1
The addition of a third amplifier to the conventional three  
amplifier Instrumentation Amplifier introduces the benefits of  
differential signal realization; specifically the advantage of  
using common mode rejection to remove coupled noise and  
ground –potential errors inherent in remote transmission.  
This configuration also provides enhanced bandwidth, wider  
output swing and faster slew rate than conventional three  
amplifier solutions with only the cost of an additional  
amplifier and few resistors.  
+
-
A
3
R
e 3  
2
o
-
+
+
R
R
3
3
REF  
R
e
G
o
R
R
3
3
A
4
R
2
-
+
-
e 4  
o
A
2
R
R
3
3
-
+
e
2
e
e
= –(1 + 2R ⁄ R )(e – e )  
e
= (1 + 2R ⁄ R )(e – e )  
o4 2 G 1 2  
o3  
o
2
G
1
2
= –2(1 + 2R ⁄ R )(e – e )  
2
G
1
2
2f  
C1, 2  
A
= –2(1 + 2R ⁄ R )  
2 G  
-----------------  
Di  
BW =  
A
Di  
FN7384.4  
February 14, 2005  
14  
EL5150, EL5151, EL5250, EL5251, EL5451  
resulting in an imbalance in the bridge. A voltage variation  
Strain Gauge  
from the referenced high accuracy source is generated and  
translated to the difference amplifier through the buffer  
stage. This voltage difference as a function of the strain is  
converted into an output voltage.  
The strain gauge is an ideal application to take advantage of  
the moderate bandwidth and high accuracy of the EL5150.  
The operation of the circuit is very straight-forward. As the  
strain variable component resistor in the balanced bridge is  
subjected to increasing strain, its resistance changes  
5V  
V2  
0.1µF  
VARIABLE SUBJECT TO STRAIN  
1K  
V5  
U1A  
4
R17  
4
3
22  
22  
0V  
R15  
R15  
1K  
+
1K  
1
1K  
V+  
V-  
V
(V1+V2+V3+V4)  
OUT  
R14  
R18  
4
2
-
RL  
11  
1K  
1K  
1K  
RF  
0.1µF  
5V  
V4  
FN7384.4  
February 14, 2005  
15  
EL5150, EL5151, EL5250, EL5251, EL5451  
MSOP Package Outline Drawing  
FN7384.4  
February 14, 2005  
16  
EL5150, EL5151, EL5250, EL5251, EL5451  
SO Package Outline Drawing  
FN7384.4  
February 14, 2005  
17  
EL5150, EL5151, EL5250, EL5251, EL5451  
SOT-23 Package Outline Drawing  
NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at  
http://www.intersil.com/design/packages/index.asp  
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.  
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality  
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without  
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and  
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result  
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.  
For information regarding Intersil Corporation and its products, see www.intersil.com  
FN7384.4  
February 14, 2005  
18  

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SI9122E

 500-kHz Half-Bridge DC/DC Controller with Integrated Secondary Synchronous Rectification Drivers

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VISHAY
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