ISL55004_06 [INTERSIL]
High Supply Voltage 200MHz Unity-Gain Stable Operational Amplifier; 高电源电压200MHz的单位增益稳定运算放大器
| 型号： | ISL55004_06 |
| 厂家： | 
Intersil |
| 描述： | High Supply Voltage 200MHz Unity-Gain Stable Operational Amplifier |
| 文件： | 总12页 (文件大小：509K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
ISL55004
®
Data Sheet
July 27, 2006
FN6219.2
High Supply Voltage 200MHz Unity-Gain
Stable Operational Amplifier
Features
• 200MHz -3dB bandwidth
• Unity-gain stable
The ISL55004 is a high speed, low power, low cost
monolithic operational amplifier. The ISL55004 is unity-gain
stable and features a 300V/µs slew rate and 200MHz
bandwidth while requiring only 8.5mA of supply current per
amplifier.
• Low supply current: 8.5mA per amplifier
• Wide supply range: ±2.5V to ±15V dual-supply and 5V to
30V single-supply
The power supply operating range of the ISL55004 is from
±15V down to ±2.5V. For single-supply operation, the
ISL55004 operates from 30V down to 5V.
• High slew rate: 300V/µs
• Fast settling: 75ns to 0.1% for a 10V step
• Wide output voltage swing: -12.75V/+13.4V with
The ISL55004 also features an extremely wide output
V = ±15V, R = 1kΩ
S
L
voltage swing of -12.75V/+13.4V with V = ±15V and
S
• Enhanced replacement for EL2444
R = 1kΩ.
L
• Pb-free plus anneal available (RoHS compliant)
At a gain of +1, the ISL55004 has a -3dB bandwidth of
200MHz with a phase margin of 55°. Because of its
conventional voltage-feedback topology, the ISL55004 allow
the use of reactive or non-linear elements in its feedback
network. This versatility combined with low cost and 140mA
of output-current drive makes the ISL55004 an ideal choice
for price-sensitive applications requiring low power and high
speed.
Applications
• Video amplifiers
• Single-supply amplifiers
• Active filters/integrators
• High speed sample-and-hold
• High speed signal processing
• ADC/DAC buffers
The ISL55004 is in a 14 Ld SO (0.150”) package and
specified for operation over the full -40°C to +85°C
temperature range.
• Pulse/RF amplifiers
• Pin diode receivers
• Log amplifiers
Ordering Information
TAPE
PART
&
PKG.
DWG. #
PART NUMBER MARKING REEL
PACKAGE
• Photo multiplier amplifiers
• Difference amplifiers
ISL55004IB
55004IB
55004IB
-
14 Ld SO (0.150”) MDP0027
ISL55004IB-T7
7” 14 Ld SO (0.150”) MDP0027
13” 14 Ld SO (0.150”) MDP0027
ISL55004IB-T13 55004IB
Pinout
ISL55004
[14 LD SO (0.150”)]
TOP VIEW
ISL55004IBZ
(See Note)
55004IBZ
-
14 Ld SO (0.150”) MDP0027
(Pb-Free)
ISL55004IBZ-T7 55004IBZ
(See Note)
7” 14 Ld SO (0.150”) MDP0027
(Pb-Free)
OUT1
IN1-
1
2
3
4
5
6
7
14 OUT4
13 IN4-
12 IN4+
11 VS-
ISL55004IBZ-T13 55004IBZ
(See Note)
13” 14 Ld SO (0.150”) MDP0027
(Pb-Free)
-
-
+
+
+
+
-
-
IN1+
VS+
NOTE: Intersil Pb-free plus anneal products employ special Pb-free
material sets; molding compounds/die attach materials and 100%
matte tin plate termination finish, which are RoHS compliant and
compatible with both SnPb and Pb-free soldering operations. Intersil
Pb-free products are MSL classified at Pb-free peak reflow
temperatures that meet or exceed the Pb-free requirements of
IPC/JEDEC J STD-020.
IN2+
IN2-
10 IN3+
9
8
IN3-
OUT2
OUT3
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1
1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc.
Copyright Intersil Americas Inc. 2005-2006. All Rights Reserved
All other trademarks mentioned are the property of their respective owners.
ISL55004
Absolute Maximum Ratings (T = 25°C)
A
Supply Voltage (V ). . . . . . . . . . . . . . . . . . . . . . . . . . ±16.5V or 33V
Power Dissipation (P ) . . . . . . . . . . . . . . . . . . . . . . . . . See Curves
D
S
Input Voltage (V . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .±V
Operating Temperature Range (T ). . . . . . . . . . . . . .-40°C to +85°C
IN)
S
A
Differential Input Voltage (dV ). . . . . . . . . . . . . . . . . . . . . . . . .±10V
Operating Junction Temperature (T ) . . . . . . . . . . . . . . . . . . +150°C
J
IN
Continuous Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . 60mA
Storage Temperature (T ) . . . . . . . . . . . . . . . . . . .-65°C to +150°C
ST
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: T = T = T
A
J
C
DC Electrical Specifications
V
= ±15V, A = +1, R = 1kΩ, T = 25°C, unless otherwise specified.
S
V
L
A
PARAMETER
DESCRIPTION
Input Offset Voltage
CONDITION
MIN
TYP
1.2
MAX
UNIT
mV
µV/°C
µA
µA
nA/°C
V/V
dB
dB
V
V
V
= ±15V
5
OS
S
TCV
Average Offset Voltage Drift (Note 1)
Input Bias Current
17
OS
I
I
V
V
= ±15V
= ±15V
0.6
3.5
2
B
S
S
Input Offset Current
0.2
OS
TCI
Average Offset Current Drift (Note 1)
Open-loop Gain
0.2
OS
A
V
V
V
V
= ±15V, V
= ±10V, R = 1kΩ
12000
75
21000
100
90
VOL
S
OUT
L
PSRR
CMRR
CMIR
Power Supply Rejection Ratio
Common-mode Rejection Ratio
Common-mode Input Range
Output Voltage Swing
= ±5V to ±15V
S
= ±10V, V
= 0V
OUT
75
CM
= ±15V
13
S
V
V +, R = 1kΩ
13.25
-12.6
9.6
13.4
-12.75
10.7
-9.4
140
8.5
V
OUT
O
L
V -, R = 1kΩ
V
O
L
V +, R = 150Ω
V
O
L
V -, R = 150Ω
-8.3
80
V
O
L
I
I
Output Short Circuit Current
Supply Current (per amplifier)
Input Resistance
mA
mA
MΩ
pF
SC
V
= ±15V, no load
9.25
S
S
R
C
R
2.0
3.2
IN
Input Capacitance
A
= +1
= +1
1
IN
V
Output Resistance
A
50
mΩ
V
OUT
V
PSOR
Power Supply Operating Range
Dual supply
±2.25
4.5
±15
30
Single supply
V
NOTE:
1. Measured from T
MIN
to T .
MAX
AC Electrical Specifications
V
= ±15V, A = +1, R = 1kΩ, T = 25°C, unless otherwise specified.
S
V
L
A
PARAMETER
BW
DESCRIPTION
CONDITION
= ±15V, A = +1
MIN
TYP
200
55
MAX
UNIT
MHz
MHz
MHz
MHz
MHz
°
-3dB Bandwidth (V
= 0.4V
)
V
V
V
V
V
OUT
PP
S
S
S
S
S
V
= ±15V, A = -1
V
= ±15V, A = +2
53
V
= ±15V, A = +5
V
17
GBWP
PM
Gain Bandwidth Product
Phase Margin
= ±15V
70
R
= 1kΩ, C = 5pF
55
L
L
SR
Slew Rate (Note 1)
260
300
V/µs
FN6219.2
July 27, 2006
2
ISL55004
AC Electrical Specifications
V
= ±15V, A = +1, R = 1kΩ, T = 25°C, unless otherwise specified. (Continued)
S
V
L
A
PARAMETER
DESCRIPTION
CONDITION
MIN
TYP
9.5
MAX
UNIT
MHz
ns
FPBW
Full-power Bandwidth (Note 2)
V
V
= ±15V
S
S
t
Settling to +0.1% (A = +1)
V
= ±15V, 10V step
75
S
dG
dP
Differential Gain (Note 3)
Differential Phase
NTSC/PAL
NTSC/PAL
10kHz
0.01
0.05
12
%
°
eN
Input Noise Voltage
Input Noise Current
nV/√Hz
pA/√Hz
iN
10kHz
1.5
NOTES:
1. Slew rate is measured on rising edge.
2. For V = ±15V, V = 10V , for V = ±5V, V
= 5V . Full-power bandwidth is based on slew rate measurement using FPBW = SR/(2π *
PP
S
OUT
PP
S
OUT
V
).
PEAK
3. Video performance measured at V = ±15V, A = +2 with two times normal video level across R = 150Ω. This corresponds to standard video
S
V
L
levels across a back-terminated 75Ω load. For other values or R , see curves.
L
Typical Performance Curves
FIGURE 1. OPEN-LOOP GAIN vs FREQUENCY
4
FIGURE 2. OPEN-LOOP PHASE vs FREQUENCY
4
V
R
R
= ±15V
= 500Ω
= 500Ω
V
R
R
= ±15V
= 500Ω
= 500Ω
S
F
L
S
F
L
3
2
3
2
1
0
1
0
A
= +1
V
A
= -1
V
A
= +2
V
-1
-2
-1
-2
A
= -2
V
A
= +5
V
-3
-4
-5
-3
-4
-5
A
= -5
V
-6
100k
-6
100k
1M
10M
100M
1G
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 3. GAIN vs FREQUENCY FOR VARIOUS NON-
INVERTING GAIN SETTINGS
FIGURE 4. GAIN vs FREQUENCY FOR VARIOUS INVERTING
GAIN SETTINGS
FN6219.2
July 27, 2006
3
ISL55004
Typical Performance Curves (Continued)
FIGURE 5. PHASE vs FREQUENCY FOR VARIOUS NON-
INVERTING GAIN SETTINGS
FIGURE 6. PHASE vs FREQUENCY FOR VARIOUS
INVERTING GAIN SETTINGS
100
350
R =500Ω
A =+2
V
L
R =500Ω
F
R =500Ω
L
80
300
POSITIVE SLEW RATE
NEGATIVE SLEW RATE
C =5pF
L
60
40
20
0
250
200
150
100
0
3
6
9
12
15
0
3
6
9
12
15
SUPPLY VOLTAGES (±V)
SUPPLY VOLTAGES (±V)
FIGURE 7. GAIN BANDWIDTH PRODUCT vs SUPPLY
FIGURE 8. SLEW RATE vs SUPPLY
4
4
V
R
C
= ±15V
= 500Ω
= 5pF
= +2
S
F
L
V
R
C
= ±15V
= 0Ω
3
2
S
F
L
3
2
= 5pF
A
V
R
= 500Ω
L
A
= +1
V
1
0
R
= 1kΩ
1
0
L
R
= 1kΩ
L
-1
-2
R
= 150Ω
R = 150Ω
L
-1
-2
L
R
= 500Ω
L
R
= 50Ω
L
-3
-4
-5
-3
-4
-5
R
= 50Ω
L
-6
100k
-6
1M
10M
100M
1G
100k
1M
10M
FREQUENCY (Hz)
100M
1G
FREQUENCY (Hz)
FIGURE 9. GAIN vs FREQUENCY FOR VARIOUS R
FIGURE 10. GAIN vs FREQUENCY FOR VARIOUS R
LOAD
LOAD
(A = +1)
(A = +2)
V
V
FN6219.2
July 27, 2006
4
ISL55004
Typical Performance Curves (Continued)
4
4
V
R
R
= ±15V
= 500Ω
= 500Ω
= +2
S
F
L
V
= ±15V
S
F
L
3
2
3
2
C
= 100pF
C
= 47pF
L
C
= 68pF
L
L
R
R
A
= 0Ω
= 500Ω
= +1
C
= 27pF
A
L
V
V
1
0
1
0
C
= 39pF
L
C
= 15pF
L
C
= 22pF
C
L
C
= 5pF
L
-1
-2
-1
-2
= 5pF
L
-3
-4
-5
-3
-4
-5
C
= 0pF
L
-6
100k
-6
100k
1M
10M
100M
1G
1M
10M
FREQUENCY (Hz)
100M
1G
FREQUENCY (Hz)
FIGURE 11. GAIN vs FREQUENCY FOR VARIOUS C
FIGURE 12. GAIN vs FREQUENCY FOR VARIOUS C
LOAD
LOAD
(A = +1)
(A = +2)
V
V
4
4
V
R
C
= ±15V
V
= ±15V
S
L
L
S
L
L
R
= 500Ω
3
2
3
2
F
= 500Ω
R
C
A
= 500Ω
= 5pF
= +2
= 5pF
= +1
A
V
V
R
= 500Ω
F
1
0
1
0
R
= 100Ω
F
R
= 1kΩ
F
R
= 250Ω
F
R
= 250Ω
F
-1
-2
-1
-2
R
= 0Ω
F
R
= 100Ω
F
-3
-4
-5
-3
-4
-5
-6
100k
-6
100k
1M
10M
100M
1G
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 13. GAIN vs FREQUENCY FOR VARIOUS R
FIGURE 14. GAIN vs FREQUENCY FOR VARIOUS R
FEEDBACK
FEEDBACK
(A = +1)
(A = +2)
V
V
4
4
V
R
R
= ±15V
R
R
C
= 0Ω
S
F
L
L
F
L
L
3
2
C
= 10pF
3
2
IN
= 500Ω
= 500Ω
= 5pF
= +2
= 500Ω
C
= 6.8pF
IN
= 5pF
= +1
V = ±2.5V
S
C
A
V
A
1
0
V
C
= 4.7pF
1
0
IN
V
= ±10V
S
-1
-2
-1
-2
C
= 2.2pF
IN
V
= ±15V
S
C
= 0pF
IN
-3
-4
-5
-3
-4
-5
V
= ±5V
S
-6
100k
-6
100k
1M
10M
100M
1G
1M
10M
100M
1G
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 15. GAIN vs FREQUENCY FOR VARIOUS INVERTING
FIGURE 16. GAIN vs FREQUENCY FOR VARIOUS SUPPLY
SETTINGS
INPUT CAPACITANCE (C
)
IN
FN6219.2
July 27, 2006
5
ISL55004
Typical Performance Curves (Continued)
FIGURE 17. COMMON-MODE REJECTION RATIO (CMRR)
FIGURE 18. POWER SUPPLY REJECTION RATIO (PSRR)
-20
V =±15V
S
A =+1
-30
-40
-50
-60
-70
-80
-90
-100
V
THD
R =0Ω
F
R =500Ω
L
C =5pF
L
OUT
V
=2V
P-P
2ND HD
3RD HD
10M
500K
1M
40M
FREQUENCY (Hz)
FIGURE 19. HARMONIC DISTORTION vs FREQUENCY
(A = +1)
FIGURE 20. HARMONIC DISTORTION vs OUTPUT VOLTAGE
(A = +2)
V
V
25
20
R =500Ω
L
L
A =+1
V
C =5pF
A =+2
V
R =500Ω
F
15
10
5
0
0
3
6
9
12
15
SUPPLY VOLTAGES (±V)
FIGURE 21. OUTPUT SWING vs FREQUENCY FOR VARIOUS
GAIN SETTINGS
FIGURE 22. OUTPUT SWING vs SUPPLY VOLTAGE FOR
VARIOUS GAIN SETTINGS
FN6219.2
July 27, 2006
6
ISL55004
Typical Performance Curves (Continued)
20% to 80%
80% to 20%
20% to 80% 80% to 20%
FIGURE 23. LARGE SIGNAL RISE AND FALL TIMES
FIGURE 24. SMALL SIGNAL RISE AND FALL TIMES
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
25
20
1.2
SO14
=120°C/W
1
0.8
0.6
0.4
0.2
0
1.042W
θ
JA
15
10
A =+1
V
R =0Ω
5
0
F
R =500Ω
L
C =5pF
L
0
3
6
9
12
15
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
SUPPLY VOLTAGES (±V)
FIGURE 26. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
FIGURE 25. SUPPLY CURRENT vs SUPPLY VOLTAGE
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.8
1.6
1.420W
1.4
SO14
1.2
θ
=88°C/W
JA
1
0.8
0.6
0.4
0.2
0
0
25
50
75 85 100
125
150
AMBIENT TEMPERATURE (°C)
FIGURE 27. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
FN6219.2
July 27, 2006
7
ISL55004
the gain slightly. If the gain setting is greater than 1, the gain
Product Description
resistor R can then be chosen to make up for any gain loss
G
The ISL55004 is a wide bandwidth, low power, and low offset
voltage feedback operational amplifier. This device is
internally compensated for closed loop gain of +1 or greater.
Connected in voltage follower mode and driving a 500Ω
load, the -3dB bandwidth is around a 200MHz. Driving a
150Ω load and a gain of 2, the bandwidth is about 90MHz
while maintaining a 300V/µs slew rate.
which may be created by the additional series resistor at the
output.
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, a back-termination series resistor at the
amplifier's output will isolate the amplifier from the cable and
allow extensive capacitive drive. However, other applications
may have high capacitive loads without a back-termination
resistor. Again, a small series resistor at the output can help
to reduce peaking.
The ISL55004 is designed to operate with supply voltage
from +15V to -15V. That means for single supply application,
the supply voltage is from 0V to 30V. For split supplies
application, the supply voltage is from ±15V. The amplifier
has an input common-mode voltage range from 1.5V above
Output Drive Capability
the negative supply (V - pin) to 1.5V below the positive
S
The ISL55004 does not have internal short circuit protection
circuitry. It has a typical short circuit current of 140mA. If the
output is shorted indefinitely, the power dissipation could
easily overheat the die or the current could eventually
compromise metal integrity. Maximum reliability is
supply (V + pin). If the input signal is outside the above
S
specified range, it will cause the output signal to be distorted.
The outputs of the ISL55004 can swing from -12.75V to
+13.4V for V = ±15V. As the load resistance becomes
S
maintained if the output current never exceeds ±60mA. This
limit is set by the design of the internal metal interconnect.
Note that in transient applications, the part is robust.
lower, the output swing is lower.
Choice of Feedback Resistor and Gain Bandwidth
Product
Short circuit protection can be provided externally with a
back match resistor in series with the output placed close as
possible to the output pin. In video applications this would be
a 75Ω resistor and will provide adequate short circuit
protection to the device. Care should still be taken not to
stress the device with a short at the output.
For applications that require a gain of +1, no feedback
resistor is required. Just short the output pin to the inverting
input pin. For gains greater than +1, the feedback resistor
forms a pole with the parasitic capacitance at the inverting
input. As this pole becomes smaller, the amplifier's phase
margin is reduced. This causes ringing in the time domain
Power Dissipation
and peaking in the frequency domain. Therefore, R can't be
F
With the high output drive capability of the ISL55004, it is
possible to exceed the 150°C absolute maximum junction
temperature under certain load current conditions.
Therefore, it is important to calculate the maximum junction
temperature for an application to determine if load conditions
or package types need to be modified to assure operation of
the amplifier in a safe operating area.
very big for optimum performance. If a large value of R
must be used, a small capacitor in the few Pico Farad range
F
in parallel with R can help to reduce the ringing and
F
peaking at the expense of reducing the bandwidth. For gain
of +1, R = 0 is optimum. For the gains other than +1,
F
optimum response is obtained with R with proper selection
F
of R and R (see Figures15 and 16 for selection).
F
G
The maximum power dissipation allowed in a package is
determined according to:
Video Performance
For good video performance, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the output.
This is especially difficult when driving a standard video load
of 150Ω, because of the change in output current with DC
level. The dG and dP of this device is about 0.01% and
0.05°, while driving 150Ω at a gain of 2. Driving high
impedance loads would give a similar or better dG and dP
performance.
T
– T
AMAX
JMAX
PD
= --------------------------------------------
MAX
Θ
JA
Where:
• T
• T
= Maximum junction temperature
= Maximum ambient temperature
JMAX
AMAX
• θ = Thermal resistance of the package
JA
Driving Capacitive Loads and Cables
The maximum power dissipation actually produced by an IC
is the total quiescent supply current times the total power
supply voltage, plus the power in the IC due to the load, or:
The ISL55004 can drive 47pF loads in parallel with 500Ω
with less than 3dB of peaking at gain of +1 and as much as
100pF at a gain of +2 with under 3db of peaking. If less
peaking is desired in applications, a small series resistor
(usually between 5Ω to 50Ω) can be placed in series with the
output to eliminate most peaking. However, this will reduce
FN6219.2
July 27, 2006
8
ISL55004
Application Circuits
For sourcing:
n
V
OUTi
R
Li
Sallen Key Low Pass Filter
-----------------
) ×
OUTi
PD
= V × I
+
+
(V – V
MAX
S
SMAX
S
∑
A common and easy to implement filter taking advantage of
the wide bandwidth, low offset and low power demands of
the ISL55004. A derivation of the transfer function is
provided for convenience (See Figure 28).
i = 1
For sinking:
n
PD
= V × I
(V
– V ) × I
OUTi S LOADi
MAX
S
SMAX
∑
Sallen Key High Pass Filter
i = 1
Again this useful filter benefits from the characteristics of the
ISL55004. The transfer function is very similar to the low
pass so only the results are presented (See Figure 29).
Where:
• V = Supply voltage
S
• I
SMAX
= Maximum quiescent supply current
• V
= Maximum output voltage of the application
OUT
• R
= Load resistance tied to ground
LOAD
• I
LOAD
= Load current
• N = number of amplifiers (max = 4)
By setting the two PD equations equal to each other, we
MAX
can solve the output current and R
to avoid the device
LOAD
overheat.
Caution: For supply voltages greater then 20V, the
maximum power dissipation at 85°C ambient temperature
could be exceeded. For higher supply voltages the
maximum ambient temperature must be de-rated according
to the Package Power Dissipation curve Figure 27. The
maximum power dissipation is highly dependent upon the
thermal conductivity of the PCB. For lower thermal
conductivity boards use Figure 26.
Power Supply Bypassing Printed Circuit Board
Layout
As with any high frequency device, a good printed circuit
board layout is necessary for optimum performance. Lead
lengths should be as short as possible. The power supply
pin must be well bypassed to reduce the risk of oscillation.
For normal single supply operation, where the V - pin is
S
connected to the ground plane, a single 4.7µF tantalum
capacitor in parallel with a 0.1µF ceramic capacitor from V +
S
to GND will suffice. This same capacitor combination should
be placed at each supply pin to ground if split supplies are to
be used. In this case, the V - pin becomes the negative
S
supply rail.
Printed Circuit Board Layout
For good AC performance, parasitic capacitance should be
kept to minimum. Use of wire wound resistors should be
avoided because of their additional series inductance. Use
of sockets should also be avoided if possible. Sockets add
parasitic inductance and capacitance that can result in
compromised performance. Minimizing parasitic capacitance
at the amplifier's inverting input pin is very important. The
feedback resistor should be placed very close to the
inverting input pin. Strip line design techniques are
recommended for the signal traces.
FN6219.2
July 27, 2006
9
ISL55004
RB
RA
V
5V
K = 1+
Vo = K
2
1
C
5
V1
R2C2s +1
Vo
1nF
C
V1− Vi
R1
Vo − Vi
1
1
K − V1
1+
+
= 0
R2
1nF
C1s
R
R
2
1
K
V+
+
-
H(s) =
V
OUT
2
1kΩ
1kΩ C
2
V
R1C1R2C2s + ((1− K)R1C1+ R1C2 + R21C2)s +1
1
R
1kΩ
7
1nF
V-
1
H(jw) =
2
1− w R1C1R2C2 + jw((1− K)R1C1+ R1C2 + R2C2)
R
B
Holp = K
1kΩ
R
1kΩ
1
A
C
5
wo =
R1C1R2C2
1nF
1
Q =
R1C1
R1C2
R2C1
R2C2
R1C1
V
3
(1− K)
+
+
5V
R2C2
Holp = K
Equations simplify if we let all
components be equal R=C
1
FIGURE 28. SALLEN KEY LOW PASS FILTER
wo =
RC
1
Q =
3 − K
V
5V
2
Holp = K
1
C
5
wo =
R1C1R2C2
1
1nF
C
1
Q =
R1C1
R1C2
R2C1
R2C2
R1C1
(1− K)
+
+
1nF
R2C2
R
R
2
1
V+
+
-
V
OUT
1kΩ
1kΩ C
2
V
1
R
1kΩ
7
1nF
V-
R
K
4 − K
2
B
Holp =
wo =
1kΩ
R
1kΩ
A
C
Equations simplify if we let
5
all components be equal R=C
RC
1nF
2
Q =
V
3
4 − K
5V
FIGURE 29. SALLEN KEY HIGH PASS FILTER
FN6219.2
July 27, 2006
10
ISL55004
Differential Output Instrumentation Amplifier
e
= –(1 + 2R ⁄ R )(e – e )
e
= (1 + 2R ⁄ R )(e – e )
o4 2 G 1 2
o3
2
G
1
2
The addition of a third amplifier to the conventional three
amplifier instrumentation amplifier introduces the benefits of
differential signal realization, specifically the advantage of
using common-mode rejection to remove coupled noise and
ground potential errors inherent in remote transmission. This
configuration also provides enhanced bandwidth, wider
output swing and faster slew rate than conventional three
amplifier solutions with only the cost of an additional
amplifier and few resistors.
e
= –2(1 + 2R ⁄ R )(e – e )
2 G 1 2
o
2f
C1, 2
A
= –2(1 + 2R ⁄ R )
2 G
Di
BW = -----------------
A
Di
Strain Gauge
The strain gauge is an ideal application to take advantage of
the moderate bandwidth and high accuracy of the ISL55004.
The operation of the circuit is very straightforward. As the
strain variable component resistor in the balanced bridge is
subjected to increasing strain, its resistance changes,
resulting in an imbalance in the bridge. A voltage variation
from the referenced high accuracy source is generated and
translated to the difference amplifier through the buffer
stage. This voltage difference as a function of the strain is
converted into an output voltage.
A
1
R
R
3
3
e
1
+
-
A
3
R
e 3
2
o
-
+
+
R
R
3
3
REF
R
e
G
o
R
R
3
3
A
4
R
2
-
+
-
e 4
o
A
2
R
R
3
3
-
+
e
2
FIGURE 30. DIFFERENTIAL OUTPUT AMPLIFIER
+
V
2
5V
-
C
6
VARIABLE SUBJECT
TO STRAIN
1nF
1kΩ
16
1kΩ
+
R
R
1kΩ
1kΩ
17
18
V
0V
R
1kΩ
R
5
15
V+
V-
+
-
-
V
OUT
(V1+V2+V3+V4)
R
1kΩ
L
1kΩ
R
F
1kΩ
C
12
1nF
+
-
V
5V
4
FIGURE 31. STRAIN GAUGE
FN6219.2
July 27, 2006
11
ISL55004
Small Outline Package Family (SO)
A
D
h X 45°
(N/2)+1
N
A
PIN #1
I.D. MARK
E1
E
c
SEE DETAIL “X”
1
(N/2)
B
L1
0.010 M
C A B
e
H
C
A2
A1
GAUGE
PLANE
SEATING
PLANE
0.010
L
4° ±4°
0.004 C
b
0.010 M
C
A
B
DETAIL X
MDP0027
SMALL OUTLINE PACKAGE FAMILY (SO)
SO16
(0.150”)
SO16 (0.300”)
(SOL-16)
SO20
(SOL-20)
SO24
(SOL-24)
SO28
(SOL-28)
SYMBOL
SO-8
0.068
0.006
0.057
0.017
0.009
0.193
0.236
0.154
0.050
0.025
0.041
0.013
8
SO-14
0.068
0.006
0.057
0.017
0.009
0.341
0.236
0.154
0.050
0.025
0.041
0.013
14
TOLERANCE
MAX
NOTES
A
A1
A2
b
0.068
0.006
0.057
0.017
0.009
0.390
0.236
0.154
0.050
0.025
0.041
0.013
16
0.104
0.007
0.092
0.017
0.011
0.406
0.406
0.295
0.050
0.030
0.056
0.020
16
0.104
0.007
0.092
0.017
0.011
0.504
0.406
0.295
0.050
0.030
0.056
0.020
20
0.104
0.007
0.092
0.017
0.011
0.606
0.406
0.295
0.050
0.030
0.056
0.020
24
0.104
0.007
0.092
0.017
0.011
0.704
0.406
0.295
0.050
0.030
0.056
0.020
28
-
±0.003
±0.002
±0.003
±0.001
±0.004
±0.008
±0.004
Basic
-
-
-
c
-
D
1, 3
E
-
E1
e
2, 3
-
L
±0.009
Basic
-
L1
h
-
Reference
Reference
-
N
-
Rev. L 2/01
NOTES:
1. Plastic or metal protrusions of 0.006” maximum per side are not included.
2. Plastic interlead protrusions of 0.010” maximum per side are not included.
3. Dimensions “D” and “E1” are measured at Datum Plane “H”.
4. Dimensioning and tolerancing per ASME Y14.5M-1994
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
FN6219.2
July 27, 2006
12
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