KKA1062AN [KODENSHI]
Telecom IC, PDIP16;
| 型号： | KKA1062AN |
| 厂家： | 
KODENSHI KOREA CORP. |
| 描述： | Telecom IC, PDIP16 光电二极管 |
| 文件： | 总9页 (文件大小：360K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TECHNICAL DATA
TELEPHONE SPEECH NETWORK
WITH DIALER INT`ERFACE
KKA1062/1062A
FEATURES
PIN CONNECTION
- Low DC line voltage; operates down to 1.6V (excluding
polarity guard)
16
1
2
3
4
5
6
7
8
SLPE
LN
- Voltage regulator with adjustable static resistance
- Provides a supply for external circuits
GAS1
GAS2
OR
15 AGC
- Symmetrical high-impedance inputs (64 kΩ) for
dynamic, magnetic or piezo-electric microphones
- Asymmetrical high-impedance input (32 kΩ) for electret
microphones
REG
14
13
12
KKA1062
V
CC
- DTMF signal input with confidence tone
or
- Mute input for pulse or DTMF dialing
- KKA1062: active HIGH (MUTE)
KKA1062A
GAR
MIC-
MIC+
STAB
MUTE
DTMF
IR
- KKA1062A: active LOW (MUTE)
- Receiving amplifier for dynamic, magnetic or
piezo-electric earpieces
11
10
9
- Large gain setting range on microphone and earpiece
amplifiers
V
EE
- Line loss compensation (line current dependent) for
microphone and earpiece amplifiers
- Gain control curve adaptable to exchange supply
- DC line voltage adjustment facility
DESCRIPTION
The KKA1062 and KKA1062A are integrated circuits that perform all speech and line interface functions required in fully
electronic telephone sets. They perform electronic switching between dialing and speech. The ICs operates at line voltage down
to 1.6 V DC (with reduced performance) to facilitate the use of more telephone sets connected in parallel.
All statements and values refer to all versions unless otherwise specified. The KKA1062 (KKA1062A) is packaged in a standard
16-pin plastic DIP and special plastic DIP with internal heatsink is also available.
QUICK REFERENCE DATA
Characteristic
Symbol
Test Condition
Min
Typ
Max
Unit
Line Voltage
VLN
I line
Iline = 15mA
3.55
4.0
2.0
4.25
V
Operating Line Current
Normal Operation
Vdc
mA
mA
11
1
140
11
with Reduced Performance
Internal Supply Current
I CC
VCC = 2.8V
Iline= 15mA
Ip= 1.2mA
Ip= 0mA
0.9
1.35
mA
V
Supply Voltage for Peripherals
VCC
2.2
2.2
2.7
3.4
Voltage Gain
GV
microphone amplifier
receiving amplifier
Line loss compensation
Gain Control
44
20
52
31
dB
dB
5.8
dB
V
∆GV
Vexch
Rexch
Exchange Supply Voltage
36
60
1
Exchange Feeding bridge Resistance
0.4
kΩ
KKA1062/1062A
BLOCK DIAGRAM
VCC
13
LN
1
10
IR
5
GAR
-
4
KKA1062A
QR
+
7
+
-
MIC+
2
GAS1
6
MIC-
-
+
-
+
11
DTMF
dB
3
GAS2
(1)
12
MUTE
SUPPLY AND
REFERENCE
CONTROL
CURRENT
LOW VOLTAGE
CIRCUIT
CURRENT
REFERENCE
16
9
14
15
8
VEE
REG AGC
STAB
SLPE
(1) Pin 12 is active HIGH (MUTE) for KKA1062.
Fig.1 Block diagram for KKA1062A
KKA1062/1062A
FUNCTIONAL DESCRIPTION
At line currents below 9mA the internal reference voltage is
automatically adjusted to a lower value (typically 1.6V at 1mA). This
means that more sets can be operated in parallel with DC line voltage
(excluding the polarity guard) down to an absolute minimum voltage
of 1.6V. At line currents below 9mA the circuit has limited sending
and receiving levels. The internal reference voltage can be adjusted
by means of an external resistor (RVA). This resistor when connected
between LN and REG will decrease the internal reference voltage
and when connected between REG and SLPE will increase the
internal reference voltage.
Supplies VCC, LN, SLPE, REG and STAB
Power for the IC and its peripheral circuits is usually obtained from
the telephone line. The supply voltage is delivered from the line via a
dropping resistor and regulated by the IC. The supply voltage VCC
may also be used to supply external circuits e.g. dialing and control
circuits.
Decoupling of the supply voltage is performed by a capacitor
between VCC and VEE . The internal voltage regulator is decoupled by
a capacitor between REG and VEE.
Microphone inputs MIC+ and MIC- and gain pins
GAS1 and GAS2
The DC current flowing into the set is determined by the exchange
supply voltage Vexch , the feeding bridge resistance Rexch and the DC
resistance of the telephone
The circuit has symmetrical microphone inputs. Its input impedance
is 64 kΩ (2 x 32kΩ) and its voltage gain is typically 52 dB (when R7
= 68k?; see Fig.6).
line Rline
.
Dynamic, magnetic, piezo-electric or electret (with built-in FET
source followers) can be used.
The circuit has internal current stabilizer operating at a level
determined by a 3.6 kΩ resistor connected between STAB and VEE
(see Fig.6). When the line current (Iline) is more than 0.5mA greater
than the sum of the IC supply current (ICC) and the current drawn by
the peripheral circuitry connected to VCC (Ip) the excess current is
shunted to VEE via LN.
The gain of the microphone amplifier can be adjusted between 44 dB
and 52 dB to suit the sensitivity of the transducer in use. The gain is
proportional to the value of R7 which is connected between GAS1
and GAS2.
The regulated voltage on the line terminal (VLN) can be calculated as:
Stability is ensured by two external capacitors, C6 connected
between GAS1 and SLPE and C8 connected between GAS1 and
VEE. The value of C6 is 100pF but this may be increased to obtain a
first-order low-pass filter. The value of C8 is 10 times the value of
C6. The cut-off frequency corresponds to the time constant R7 x C6.
V
V
LN = Vref + ISLPE x R9
LN = Vref + {(Iline - ICC - 0.5 x 10-3A) - Ip} x R9
Vref is an internally generated temperature compensated reference
voltage of 3.7V and R9 is an external resistor connected between
SLPE and VEE.
Input MUTE (KKA1062A)
In normal use the value of R9 would be 20?.
When MUTE is LOW or open-circuit, the DTMF input is enable and
the microphone and receiving amplifier inputs are inhibited. The
reverse is true when MUTE is HIGH.
MUTE switching causes only negligible clicking on the line and
earpiece output. If the number of parallel sets in use causes a drop in
line current to below 6 mA the DTMF amplifier becomes active
independent to the DC level applied to the MUTE input.
Changing the value of R9 will also affect microphone gain, DTMF
gain, gain control characteristics, sidetone level, maximum output
swing on LN and the DC characteristics (especially at the lower
voltages).
Fig.2 Equivalent impedance circuit
Dual-tone multi-frequency input DTMF
When the DTMF input is enable dialing tones may be sent on to the
line. The voltage gain from DTMF to LN is typically 25.5 dB (when
R7=68kΩ) and varies with R7 in the same way as the microphone
gain. The signalling tones can be heard in the earpiece at a low level
(confidence tone).
Receiving amplifier IR, QR and GAR
The receiving amplifier has one input (IR) and a non-inverting output
(QR). The IR to QR gain is typically 31dB (when R4 = 100kΩ). It
can be adjusted between 20 and 31dB to match the sensitivity of the
transducer in use. The gain is set with the value of R4 which is
connected between GAR and QR. The overall receive gain, between
LN and QR, is calculated by subtracting the anti-sidetone network
attenuation (32dB) from the amplifier gain. Two external capacitors,
C4 and C7, ensure stability. C4 is normally 100pF and C7 is 10 times
the value of C4. The value of C4 may be increased to obtain a first-
order low-pass filter. The cut-off frequency will depend on the time
constant R4 x C4.
Under normal conditions, when ISLPE >>ICC + 0.5mA + Ip, the static
behaviour of the circuit is that of a 3.7V regulator diode with an
internal resistance equal to that of R9. In the audio frequency range
the dynamic impedance is largely determined by R1. Fig.2 show the
equivalent impedance of the circuit.
The output voltage of the receiving amplifier is specified for
continuous-wave drive. The maximum output voltage will be higher
under speech conditions where the peak to RMS ratio is higher.
Automatic gain control input AGC
KKA1062/1062A
Zbal
Zline
Automatic line loss compensation is achieved by connecting a
resistor (R6) between AGC and VEE
=
(2)
.
Zbal + R 8
Zline+ R 1
The automatic gain control varies the gain of the microphone
amplifier and the receiving amplifier in accordance with the DC line
current. The control range is 5.8 dB which corresponds to a line
length of 5 km for a
If fixed values are chosen for R1, R2, R3 and R9, then condition (1)
will always be fulfilled when
0.5mm diameter twisted-pair copper cable with a DC resistance of
176 ?/km and average attenuation of
To obtain optimum sidetone suppression, condition (2) has to be
fulfilled which results in:
R 8
1.2dB/km. Resistor R6 should be chosen in accordance with the
exchange supply voltage and its feeding bridge resistance. The ratio
of start and stop currents of the AGC curve is independent of the
value of R6. If no automatic
line-loss compensation is required the AGC pin may be left open-
circuit. The amplifiers, in this condition, will give their maximum
specified gain.
Zbal
=
x Zline = k x Zline
R 1
R 8
R 1
Where k is scale factor; k =
The scale factor k, dependent on the value of R8, is chosen to meet
the following criteria:
- compatibility with a standard capacitor from the E6 or
E12 range for Zbal
- |Zbal//R8|<<R8 fulfilling condition (a) and thus
ensuring correct
Sidetone suppression
The anti-sidetone network, R1//Zline, R2, R3, R8, R9 and Zbal
suppresses the transmitted signal in the earpiece. Maximum
compensation is obtained when the following conditions are fulfilled:
anti-sidetone bridge operation
- |Zbal + R8|>>R9 to avoid influencing the transmit gain.
R 8 x Zbal
⎛
⎞
In practise Zline varies considerably with the line type and length. The
value chosen for Zbal should therefore be for an average line thus
giving optimum setting for short or long lines.
R9 x R2 = R1 x R 3 +
(1)
⎜
⎝
⎟
⎠
R 8 + Zbal
ABSOLUTE MAXIMUM RATING
Characteristic
Symbol
Test Condition
Min
Typ
Max
Unit
Positive Continuous Line Voltage
Repetitive Line Voltage During Switch-on
or Line Interruption
VLN
VLN(R)
12
13.2
V
V
Repetitive Peak Line Voltage for a 1ms
Pulse per 5s
VLN(RM)
28
V
R9 = 20Ω; R10 = 13Ω;
see Fig.6
Line Current
Input Voltage on all other Pins
Total Power
Dissipation
Operating Ambient Temperature
Storage Temperature
Iline
VI
Ptot
140
VCC+0.7
0.58
0.67
+75
mA
V
W
R9 = 20Ω; note 1
R9 = 20Ω; note 2
-0.7
Standard DIP
DIP with heatsink
TA
Tstg
Tj
-25
-40
oC
oC
oC
+125
+125
Junction Temperature
Notes
1. Mostly dependent on the maximum required TA and on the voltage between LN and SLPE.
2. Calculated for the maximum ambient temperature specified and a maximum junction temperature of 125oC.
(Thermal Resistance RJA = 85oC/W for standard DIP and RJA = 75oC/W for special DIP with heatsink).
150
LN (mA)
130
150
I
I
LN (mA)
130
110
90
(1)
110
90
(1)
(2)
(3)
(4)
(2)
(3)
(4)
70
70
(1) TA = 45oC; Ptot = 0.94 W
(2) TA = 55oC; Ptot = 0.82 W
(3) TA = 65oC; Ptot = 0.71 W
(4) TA = 75oC; Ptot = 0.58 W
(1) TA = 45oC; Ptot = 1.07 W
(2) TA = 55oC; Ptot = 0.93 W
(3) TA = 65oC; Ptot = 0.80 W
(4) TA = 75oC; Ptot = 0.67 W
50
30
50
30
4
6
8
10
12
2
4
6
8
10
12
2
V
LN - VSLPE (V)
V
LN - VSLPE (V)
Fig.3a Safe operating area
(Standard DIP)
Fig.3b Safe operating area
(DIP with HS)
KKA1062/1062A
ELECTRICAL CHARACTERISTICS
Iline = 11mA to mA; VEE = 0V; f = 800Hz; TA = 25oC; unless otherwise specified.
Characteristic
Symbol
Test Condition
Min
Typ
Max
Unit
Voltage Drop over Circuit between LN and VEE
VLN
MIC inputs open-circuit
I
line = 1mA
1.6
1.9
4.0
5.7
V
Iline = 4mA
Iline = 15mA
3.55
4.9
4.25
6.5
I
line = 100mA
Iline = 140mA
Iline = 15mA
Iline = 15mA
RVA(LN to REG) = 68k Ω
RVA(REG to SLPE) = 39kΩ
VCC = 2.8V
7.5
Variation with Temperature
-0.3
mV/oC
V
|VLN/T
Voltage Drop over Circuit Between LN and VEE
with External Resistor RVA
VLN
3.5
4.5
Supply Current
ICC
0.9
1.35
mA
V
Supply Voltage available for Peripheral Circuitry
VCC
Iline = 15mA;
Ip = 1.2mA
Ip = 0mA
2.2
2.7
3.4
Microphone inputs MIC- and MIC+ (pins 6 and 7)
Input Impedance
Differential
Single-ended
Common mode rejection ratio
Voltage Gain MIC+ or MIC- to LN
|Zi |
between MIC- and MIC+
MIC- or MIC+ to VEE
64
32
82
52.0
0.2
kΩ
kΩ
dB
dB
dB
CMRR
Gv
50.5
53.5
Iline = 15mA; R7 = 68k Ω
f = 300 and 3400 Hz
Gain Variation with Frequency referenced to
800Hz
∆Gvf
Gain Variation with Temperature referenced to
without R6; Iline = 50mA;
TA = -25 and +75 oC
0.2
dB
∆GvT
25 oC
DTMF Input (Pin 11)
Input Impedance
Voltage Gain from DTMF to LN
Gain Variation with Frequency referenced to
800Hz
20.7
25.5
0.2
|Zi |
Gv
kΩ
dB
dB
24.3
27.0
Iline = 15mA; R7 = 68kΩ
f = 300 and 3400 Hz
∆Gvf
Gain Variation with Temperature referenced to
Iline = 50mA;
0.2
dB
∆GvT
25 oC
TA = -25 and +75 oC
Gain adjustment inputs GAS1 and GAS2 (Pins2 and 3)
Transmitting Amplifier Gain variation by
adjustment of R7 between GAS1 and GAS2
-8
0
dB
∆Gv
Sending amplifier output LN (Pin1)
Output Voltage (RMS value)
VLN(rms)
THD = 10 %
I
line = 4mA
0.8
2.3
V
V
Iline = 15mA
1.7
Receiving amplifier input IR (Pin 10)
Input Impedance
21
|Zi |
Iline = 15mA; RL = 300Ω;
kΩ
(from pin 9 to
Receiving amplifier output QR (Pin 4)
Output Impedance
4
|Zo |
Ω
Voltage Gain from IR to QR
Gv
29.5
31
32.5
dB
Iline = 15mA; RL = 300Ω;
(from pin 9 to pin 4)
f = 300 and 3400 Hz
Gain Variation with Frequency referenced to
800Hz
0.2
0.2
dB
dB
∆Gvf
∆GvT
Vo(rms)
Gain Variation with Temperature referenced to
25oC
without R6; Iline = 50mA;
TA = -25 and +75oC
Output Voltage (RMS value)
THD = 2%; sine wave drive:
KKA1062/1062A
R4 = 100 KΩ;
line = 15 mA; Ip = 0 mA
RL = 150 Ω
I
0.22
0.3
0.33
0.48
V
V
RL = 450 Ω
Output Voltage (RMS value)
Vo(rms)
15
mV
Iline = 15mA; RL = 300Ω;
(from pin 9 to pin 4)
Gain adjustment input GAR (Pin 5)
Receiving Amplifier Gain Variation by
adjustment of R4 between GAR and QR
-11
0
dB
∆Gv
Iline = 15mA; RL = 300Ω;
(from pin 9 to pin 4)
Mute input (Pin 12)
HIGH Level Input Voltage
LOW Level Input Voltage
Input Current
VIH
VIIL
Iline = 15mA
Iline = 15mA
1.5
-
VCC
0.3
15
V
V
IMUTE
8
uA
Reduction of Gain
MIC+ or MIC- to LN
TEA1062
TEA1062A
Voltage Gain from DTMF to QR
TEA1062
TEA1062A
dB
dB
∆Gv
MUTE = HIGH
MUTE = LOW
R4 = 100kΩ; RL = 300Ω
MUTE = HIGH
70
70
Gv
-17
-17
MUTE = LOW
Automatic Gain Control Input AGC (Pin 15)
Controlling the Gain from IR to QR and the
Gain from MIC+, MIC- to LN
∆Gv
R6 = 110kΩ
(between AGC and VEE
line = 70mA
)
Gain Control Range
5.8
23
61
dB
mA
mA
I
Highest Line Current for Maximum Gain
Lowest Line Current for Minimum Gain
IlineH
IlineL
Iline = 15mA
Iline = 70mA
20
65
The supply possibilities can be increased by setting the voltage drop over the circuit VLN to a higher value be resistor RVA connected between REG and
SLPE.
VCC > 2.2V; Iline = 15mA at VLN = 4V; R1 = 620Ω; R9 = 20Ω
(1) Ip = 2.1mA. Curve (1) is valid when the receiving or when MUTE = HIGH(KKA1062), MUTE = LOW(KKA1062A).
(2) Ip = 1.7mA. Curve (2) is valid when MUTE = LOW(KKA1062), MUTE = HIGH(KKA1062A) and the receiving amplifier is
driven; Vo(rms) = 150mV, RL = 150Ω.
Fig.4 Typical current Ip available from VCC for peripheral circuitry.
KKA1062/1062A
Fig. 5 Variation of gain as a function of the line current with R6 as a parameter
TABLE 1
Values of resistor R6 for optimum line-loss compensation at various values of exchange supply voltage (Vexch) and exchange bridge resistance (Rexch );
R9 = 20>.
400 Rexch (Ω)
600 Rexch (Ω)
800 Rexch (Ω)
1000 Rexch (Ω)
Vexch (V)
R6 (kΩ)
36
48
60
100
140
-
78.7
110
-
-
-
93.1
120
82
102
PINNING
Pin
Symbol
Description
1
2
LN
GAS1
GAS2
QR
Positive Line Terminal
Gain Adjustment; Transmitting Amplifier
Gain Adjustment; Transmitting Amplifier
Non-inverting Output; Receiving Amplifier
Gain Adjustment; Receiving Amplifier
Inverting Microphone Input
3
4
5
GAR
MIC-
MIC+
STAB
VEE
6
7
Non-inverting Microphone Input
Current Stabilizer
8
9
Negative Line Terminal
10
11
12
13
14
15
16
IR
Receiving Amplifier Input
DTMF
MUTE
VCC
Dual-tone Multi-Frequency Input
Mute Input (see note 1)
Positive Supply Decoupling
REG
AGC
SLPE
Voltage Regulator Decoupling
Automatic Gain Control Input
Slope (DC resistance) Adjustment
Note 1. Pin 12 is active HIGH (MUTE) for KKA1062
KKA1062/1062A
APPLICATION INFORMATION
KKA1062A
Fig. 6 Typical application of KKA1062A, with piezo-electric earpiece and DTMF dialling
KKA1062/1062A
N SUFFIX PLASTIC DIP
(MS - 001BB)
A
Dimension, mm
9
8
16
1
Symbol
MIN
18.67
6.1
MAX
19.69
7.11
B
A
B
C
D
F
5.33
0.36
1.14
0.56
F
L
1.78
C
2.54
7.62
G
H
J
SEATING
PLANE
-T-
N
M
0
°
10
°
J
G
K
H
D
2.92
7.62
0.2
3.81
8.26
0.36
K
L
M
N
0.25 (0.010) M
T
NOTES:
1. Dimensions “A”, “B” do not include mold flash or protrusions.
Maximum mold flash or protrusions 0.25 mm (0.010) per side.
0.38
D SUFFIX SOIC
(MS - 012AC)
Dimension, mm
A
16
Symbol
MIN
9.8
MAX
10
9
A
B
C
D
F
H
B
P
3.8
4
1.35
0.33
0.4
1.75
0.51
1.27
1
8
G
R x 45
C
1.27
5.72
G
H
J
-T-
SEATING
PLANE
K
M
D
J
F
0.25 (0.010) M T C
M
0
°
8
°
0.1
0.19
5.8
0.25
0.25
6.2
K
M
P
NOTES:
1. Dimensions A and B do not include mold flash or protrusion.
2. Maximum mold flash or protrusion 0.15 mm (0.006) per side
0.25
0.5
R
for A; for B 0.25 mm (0.010) per side.
‑
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