LT1613CS5#PBF [Linear]
LT1613 - 1.4MHz, Single Cell DC/DC Converter in 5-Lead SOT-23; Package: SOT; Pins: 5; Temperature Range: 0°C to 70°C;
| 型号： | LT1613CS5#PBF |
| 厂家： | 
Linear |
| 描述： | LT1613 - 1.4MHz, Single Cell DC/DC Converter in 5-Lead SOT-23; Package: SOT; Pins: 5; Temperature Range: 0°C to 70°C 转换器 |
| 文件： | 总12页 (文件大小：261K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT1613
1.4MHz, Sing le Ce ll DC/ DC
Co nve rte r in 5-Le a d SOT-23
U
DESCRIPTIO
FEATURES
■
Uses Tiny Capacitors and Inductor
Internally Compensated
Fixed Frequency 1.4MHz Operation
The LT®1613 is the industry’s first 5-lead SOT-23 current
mode DC/DC converter. Intended for small, low power
applications, it operates from an input voltage as low as
1.1V and switches at 1.4MHz, allowing the use of tiny, low
cost capacitors and inductors 2mm or less in height. Its
small size and high switching frequency enables the
complete DC/DC converter function to take up less than
0.2 square inches of PC board area. Multiple output power
supplies can now use a separate regulator for each output
voltage, replacing cumbersome quasi-regulated ap-
proaches using a single regulator and a custom trans-
former.
■
■
■
Operates with V as Low as 1.1V
IN
■
■
■
■
■
■
■
3V at 30mA from a Single Cell
5V at 200mA from 3.3V Input
15V at 60mA from Four Alkaline Cells
High Output Voltage: Up to 34V
Low Shutdown Current: <1µA
Low VCESAT Switch: 300mV at 300mA
Tiny 5-Lead SOT-23 Package
U
A constant frequency, internally compensated current
mode PWM architecture results in low, predictable output
noise that is easy to filter. The high voltage switch on the
LT1613 is rated at 36V, making the device ideal for boost
converters up to 34V as well as for Single-Ended Primary
Inductance Converter (SEPIC) and flyback designs. The
device can generate 5V at up to 200mA from a 3.3V supply
or 5V at 175mA from four alkaline cells in a SEPIC design.
APPLICATIO S
■
Digital Cameras
Pagers
Cordless Phones
Battery Backup
LCD Bias
Medical Diagnostic Equipment
Local 5V or 12V Supply
External Modems
■
■
■
■
■
■
The LT1613 is available in the 5-lead SOT-23 package.
■
, LTC and LT are registered trademarks of Linear Technology Corporation.
■
PC Cards
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TYPICAL APPLICATIO
L1
4.7µH
Efficiency Curve
D1
100
95
V
3.3V
V
OUT
5V
200mA
IN
R1
37.4k
V
SW
FB
IN
90
V
= 4.2V
= 3.5V
IN
+
+
C1
15µF
C2
22µF
85
80
75
70
65
60
55
50
LT1613
V
IN
SHDN
SHDN
GND
V
IN
= 2.8V
R2
12.1k
V
IN
= 1.5V
L1: MURATA LQH3C4R7M24 OR SUMIDA CD43-4R7
C1: AVX TAJA156M010
C2: AVX TAJB226M006
1613 TA01
D1: MBR0520
0
50 100 150 200 250 300 350 400
LOAD CURRENT (mA)
Figure 1. 3.3V to 5V 200mA DC/DC Converter
1613 TA01a
1
LT1613
W W
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ABSOLUTE MAXIMUM RATINGS
(Note 1)
PACKAGE/ORDER INFORMATION
ORDER PART NUMBER
V Voltage .............................................................. 10V
IN
SW Voltage ................................................–0.4V to 36V
LT1613CS5
TOP VIEW
FB Voltage ..................................................... V + 0.3V
IN
SW 1
GND 2
FB 3
5 V
IN
Current into FB Pin ............................................... ±1mA
SHDN Voltage .......................................................... 10V
Maximum Junction Temperature .......................... 125°C
Operating Temperature Range
Commercial ............................................. 0°C to 70°C
Extended Commercial (Note 2)........... –40°C to 85°C
Storage Temperature Range ................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec).................. 300°C
4 SHDN
S5 PART MARKING
LTED
S5 PACKAGE
5-LEAD PLASTIC SOT-23
Consult factory for Industrial and Military grade parts.
ELECTRICAL CHARACTERISTICS The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. Commercial grade 0°C to 70°C, V = 1.5V, VSHDN = V unless
IN
IN
otherwise noted. (Note 2)
PARAMETER
CONDITIONS
MIN
TYP
MAX
1.1
UNITS
V
Minimum Operating Voltage
Maximum Operating Voltage
Feedback Voltage
0.9
10
V
●
●
1.205
1.23
27
3
1.255
80
V
FB Pin Bias Current
nA
mA
Quiescent Current
V
= 1.5V
4.5
SHDN
Quiescent Current in Shutdown
V
V
SHDN
= 0V, V = 2V
= 0V, V = 5V
IN
0.01
0.01
0.5
1.0
µA
µA
SHDN
IN
Reference Line Regulation
Switching Frequency
Maximum Duty Cycle
Switch Current Limit
1.5V ≤ V ≤ 10V
0.02
1.4
0.2
1.8
%/V
MHz
%
IN
●
●
1.0
82
86
(Note 3)
550
800
300
0.01
mA
mV
µA
V
Switch V
I
SW
= 300mA
350
1
CESAT
Switch Leakage Current
SHDN Input Voltage High
SHDN Input Voltage Low
SHDN Pin Bias Current
V
SW
= 5V
1
0.3
V
V
SHDN
= 3V
25
0.01
50
0.1
µA
µA
V
SHDN
= 0V
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
Note 2: The LT1613C is guaranteed to meet performance specifications
from 0°C to 70°C. Specifications over the –40°C to 85°C operating
temperature range are assured by design, characterization and correlation
with statistical process controls.
Note 3: Current limit guaranteed by design and/or correlation to static test.
2
LT1613
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TYPICAL PERFOR A CE CHARACTERISTICS
Oscillator Frequency vs
Temperature
Switch VCESAT vs Switch Current
SHDN Pin Current vs V
SHDN
700
600
500
400
300
200
100
0
2.00
1.75
1.50
1.25
1.00
0.75
0.50
0.25
0
50
40
30
20
10
0
T
= 25°C
T
= 25°C
A
A
V
= 5V
IN
V
IN
= 1.5V
0
100 200 300 400 500 600 700
SWITCH CURRENT (mA)
–50
–25
0
25
50
75
100
0
1
2
3
4
5
TEMPERATURE (°C)
SHDN PIN VOLTAGE (V)
1613 G01
1613 G02
1613 G03
Current Limit vs Duty Cycle
Feedback Pin Voltage
1000
1.25
900
1.24
1.23
1.22
1.21
1.20
800
70°C
VOLTAGE
700
600
500
400
300
200
25°C
–40°C
10
20
30
40
50
60
70
80
–50
–25
0
25
50
75
100
DUTY CYCLE (%)
TEMPERATURE (°C)
1613 G04
1613 G05
Switching Waveforms, Circuit of Figure 1
VOUT
100mV/DIV
AC COUPLED
V
SW
5V/DIV
ISW
200mA/DIV
ILOAD = 150mA
200ns/DIV
1613 G06
3
LT1613
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U
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PIN FUNCTIONS
SW (Pin 1): Switch Pin. Connect inductor/diode here.
SHDN (Pin 4): Shutdown Pin. Tie to 1V or more to enable
Minimize trace area at this pin to keep EMI down.
device. Ground to shut down.
GND (Pin 2): Ground. Tie directly to local ground plane.
V (Pin 5): Input Supply Pin. Must be locally bypassed.
IN
FB (Pin 3): Feedback Pin. Reference voltage is 1.23V.
Connect resistive divider tap here. Minimize trace area at
FB. Set VOUT according to VOUT = 1.23V(1 + R1/R2).
W
BLOCK DIAGRAM
V
IN
V
IN
5
R5
R6
40k
40k
1
SW
V
OUT
+
–
COMPARATOR
A2
–
A1
R1
DRIVER
g
m
(EXTERNAL)
FF
S
Q3
R
Q
R
FB
C
+
RAMP
GENERATOR
Q1
Q2
x10
Σ
FB
3
C
+
–
C
R2
(EXTERNAL)
R3
30k
0.15Ω
1.4MHz
OSCILLATOR
R4
140k
SHDN
4
SHUTDOWN
2
GND
1613 • BD
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OPERATIO
The LT1613 is a current mode, internally compensated,
fixed frequency step-up switching regulator. Operation
can be best understood by referring to the Block Diagram.
Q1 and Q2 form a bandgap reference core whose loop is
closed around the output of the regulator. The voltage
drop across R5 and R6 is low enough such that Q1 and Q2
50%) exceeds the V signal, comparator A2 changes
C
state, resetting the flip flop and turning off the switch.
More power is delivered to the output as switch current is
increased. The output voltage, attenuated by external
resistor divider R1 and R2, appears at the FB pin, closing
the overall loop. Frequency compensation is provided
internally by RC and CC. Transient response can be opti-
mized by the addition of a phase lead capacitor CPL in
parallel with R1 in applications where large value or low
ESR output capacitors are used.
do not saturate, even when V is 1V. When there is no
IN
load, FB rises slightly above 1.23V, causing V (the error
C
amplifier’s output) to decrease. Comparator A2’s output
stays high, keepingswitchQ3intheoffstate. As increased
output loading causes the FB voltage to decrease, A1’s
output increases. Switch current is regulated directly on a
As the load current is decreased, the switch turns on for a
shorter period each cycle. If the load current is further
decreased, the converter will skip cycles to maintain
outputvoltageregulation. IftheFBpinvoltageis increased
significantly above 1.23V, the LT1613 will enter a low
power state where quiescent current falls to approxi-
mately 100µA.
cycle-by-cycle basis by the V node. The flip flop is set at
C
the beginning of each switch cycle, turning on the switch.
When the summation of a signal representing switch
current and a ramp generator (introduced to avoid
subharmonic oscillations at duty factors greater than
4
LT1613
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OPERATIO
C3
1µF
LAYOUT
L1A
22µH
V
IN
4V TO
7V
The LT1613 switches current at high speed, mandating
careful attention to layout for proper performance. You
will not get advertised performance with careless layouts.
Figure 2 shows recommended component placement for
a boost (step-up) converter. Follow this closely in your
PCB layout. Note the direct path of the switching loops.
Input capacitor C1 must be placed close (<5mm) to the IC
+
L1B
22µH
V
SW
FB
C1
15µF
IN
D1
LT1613
R1
100k
V
OUT
5V/150mA
SHDN
SHDN
GND
+
R2
32.4k
C2
15µF
C1, C2: AVX TAJA156M016
C3: TAIYO YUDEN JMK325BJ226MM
D1: MOTOROLA MBR0520
1613 F03
L1, L2: MURATA LQH3C220
package. As little as 10mm of wire or PC trace from C to
IN
V will cause problems such as inability to regulate or
oscillation.
Figure 3. Single-Ended Primary Inductance Converter (SEPIC)
Generates 5V from An Input Voltage Above or Below 5V
IN
The ground terminal of output capacitor C2 should tie
closetoPin2oftheLT1613.Doingthis reduces dI/dtinthe
ground copper which keeps high frequency spikes to a
minimum. The DC/DC converter ground should tie to the
PC board ground plane at one place only, to avoid intro-
ducing dI/dt in the ground plane.
L1B
C3
L1A
+
C1
V
IN
V
OUT
D1
A SEPIC (single-ended primary inductance converter)
schematic is shown in Figure 3. This converter topology
produces a regulated output voltage that spans (i.e., can
be higher or lower than) the output. Recommended com-
ponent placement for a SEPIC is shown in Figure 4.
+
1
5
4
C2
2
3
SHUTDOWN
VIAS TO
GROUND
PLANE
R2
R1
GROUND
L1
+
1613 F04
C1
V
IN
V
OUT
D1
Figure 4. Recommended Component Placement for SEPIC
+
1
2
3
5
4
C2
COMPONENT SELECTION
Inductors
SHUTDOWN
VIAS TO
GROUND
PLANE
Inductors used with the LT1613 should have a saturation
current rating (where inductance is approximately 70% of
zerocurrentinductance)ofapproximately0.5Aorgreater.
DCR of the inductors should be 0.5Ω or less. For boost
converters, inductance should be 4.7µH for input voltage
less than 3.3V and 10µH for inputs above 3.3V. When
using the device as a SEPIC, either a coupled inductor or
two separate inductors can be used. If using separate
inductors, 22µH units are recommended for input voltage
above 3.3V. Coupled inductors have a beneficial mutual
inductance, so a 10µH coupled inductor results in the
same ripple current as two 20µH uncoupled units.
R2
R1
GROUND
1613 F02
Figure 2. Recommended Component Placement for Boost
Converter. Note Direct High Current Paths Using Wide PCB
Traces. Minimize Area at Pin 3 (FB). Use Vias to Tie Local
Ground Into System Ground Plane. Use Vias at Location Shown
to Avoid Introducing Switching Currents Into Ground Plane
5
LT1613
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OPERATIO
Table 1 lists several inductors that will work with the
LT1613, although this is not an exhaustive list. There are
many magnetics vendors whose components are suitable
for use.
lower ESR will result in lower output ripple.
Ceramic capacitors can be used with the LT1613 provided
loop stability is considered. A tantalum capacitor has
some ESR and this causes an “ESR zero” in the regulator
loop. This zero is beneficial to loop stability. The internally
compensated LT1613 does not have an accessible com-
pensation node, but other circuit techniques can be em-
ployed to counteract the loss of the ESR zero, as detailed
in the next section.
Diodes
ASchottkydiodeis recommendedforusewiththeLT1613.
The Motorola MBR0520 is a very good choice. Where the
input to output voltage differential exceeds 20V, use the
MBR0530 (a 30V diode). If cost is more important than
efficiency, the1N4148canbeused, butonlyatlowcurrent
loads.
Some capacitor types appropriate for use with the LT1613
are listed in Table 2.
Capacitors
OPERATION WITH CERAMIC CAPACITORS
The input bypass capacitor must be placed physically
close to the input pin. ESR is not critical and in most cases
an inexpensive tantalum is appropriate.
Because the LT1613 is internally compensated, loop sta-
bility must be carefully considered when choosing an
output capacitor. Small, low cost tantalum capacitors
have some ESR, which aids stability. However, ceramic
capacitors are becoming more popular, having attractive
characteristics such as near-zero ESR, small size and
reasonable cost. Simply replacing a tantalum output ca-
pacitorwithaceramicunitwilldecreasethephasemargin,
in some cases to unacceptable levels. With the addition of
a phase lead capacitor (CPL) and isolating resistor (R3),
the LT1613 can be used successfully with ceramic output
capacitors as described in the following figures.
The choice of output capacitor is far more important. The
quality of this capacitor is the greatest determinant of the
output voltage ripple. The output capacitor must have
enough capacitance to satisfy the load under transient
conditions and it must shunt the switched component of
current coming through the diode. Output voltage ripple
results when this switched current passes through the
finite output impedance of the output capacitor. The
capacitor should have low impedance at the 1.4MHz
switching frequency of the LT1613. At this frequency, the
impedanceis usuallydominatedbythecapacitor’s equiva-
lent series resistance (ESR). Choosing a capacitor with
A boost converter, stepping up 2.5V to 5V, is shown in
Figure 5. Tantalum capacitors are used for the input and
output (the input capacitor is not critical and has little
Table 1. Inductor Vendors
VENDOR
PHONE
URL
PART
COMMENT
Sumida
(847) 956-0666
www.sumida.com
CLS62-22022
CD43-220
22µH Coupled
22µH
Murata
(404) 436-1300
(407) 241-7876
www.murata.com
LQH3C-220
LQH3C-100
LQH3C-4R7
22µH, 2mm Height
10µH
4.7µH
Coiltronics
www.coiltronics.com
CTX20-1
20µH Coupled, Low DCR
Table 2. Capacitor Vendors
VENDOR
Taiyo Yuden
AVX
PHONE
URL
PART
COMMENT
(408) 573-4150
(803) 448-9411
www.t-yuden.com
www.avxcorp.com
Ceramic Caps
X5R Dielectric
Ceramic Caps
Tantalum Caps
Murata
(404) 436-1300
www.murata.com
Ceramic Caps
6
LT1613
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OPERATIO
effect on loop stability, as long as minimum capacitance
requirements are met). The transient response to a load
step of 50mA to 100mA is pictured in Figure 6. Note the
“doubletrace,”duetotheESRofC2. Theloopis stableand
settles in less than 100µs. In Figure 7, C2 is replaced by a
10µF ceramic unit. Phase margin decreases drastically,
resulting in a severely underdamped response. By adding
R3 and CPL as detailed in Figure 8’s schematic, phase
margin is restored, and transient response to the same
load step is pictured in Figure 9. R3 isolates the device FB
pin from fast edges on the VOUT node due to parasitic PC
trace inductance.
Figure 10’s circuit details a 5V to 12V boost converter,
delivering up to 130mA. The transient response to a load
step of 10mA to 130mA, without CPL, is pictured in
Figure 11. Although the ringing is less than that of the
previous example, the response is still underdamped and
can be improved. After adding R3 and CPL, the improved
transient response is detailed in Figure 12.
L1
10µH
D1
V
2.5V
V
OUT
5V
IN
+
V
SW
FB
C1
15µF
R1
37.4k
IN
+
LT1613
C2
22µF
SHDN
SHDN
GND
R2
12.1k
Figure 13 shows a SEPIC design, converting a 3V to 10V
input to a 5V output. The transient response to a load step
of 20mA to 120mA, without CPL and R3, is pictured in
Figure 14. After adding these two components, the im-
proved response is shown in Figure 15.
C1: AVX TAJA156M010R
C2: AVX TAJA226M006R
D1: MOTOROLA MBR0520
L1: MURATA LQH3C100
1613 F05
Figure 5. 2.5V to 5V Boost Converter with “A”
Case Size Tantalum Input and Output Capacitors
L1
10µH
D1
V
IN
V
OUT
2.5V
5V
C
330pF
PL
+
V
SW
FB
C1
15µF
IN
VOUT
20mV/DIV
R1
37.4k
LT1613
R3
10k
C2
10µF
AC COUPLED
SHUTDOWN
SHDN
GND
R2
12.1k
100mA
LOAD CURRENT
50mA
C1: AVX TAJA156M010R
C2: TAIYO YUDEN LMK325BJ106MN
D1: MBR0520
L1: MURATA LQH3C100K04
200µs/DIV
1613 F06
1613 F08
Figure 6. 2.5V to 5V Boost Converter Transient
Response with 22µF Tantalum Output Capacitor.
Apparent Double Trace on VOUT Is Due to Switching
Frequency Ripple Current Across Capacitor ESR
Figure 8. 2.5V to 5V Boost Converter with Ceramic
Output Capacitor. CPL Added to Increase Phase Margin,
R3 Isolates FB Pin from Fast Edges
VOUT
20mV/DIV
VOUT
20mV/DIV
AC COUPLED
AC COUPLED
100mA
50mA
100mA
50mA
LOAD CURRENT
LOAD CURRENT
200µs/DIV
1613 F07
200µs/DIV
1613 F09
Figure 7. 2.5V to 5V Boost Converter with
10µF Ceramic Output Capacitor, No CPL
Figure 9. 2.5V to 5V Boost Converter with 10µF Ceramic
Output Capacitor, 330pF CPL and 10k in Series with FB Pin
7
LT1613
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OPERATIO
L1
10µH
C3
1µF
L1
22µH
D1
V
12V
130mA
OUT
V
V
IN
3V TO
10V
IN
5V
C
PL
L2
22µH
+
C
330pF
D1
V
SW
FB
PL
200pF
C1
22µF
+
IN
V
SW
FB
C1
22µF
IN
R1
107k
LT1613
R3
10k
C2
4.7µF
LT1613
R3
10k
SHUTDOWN
SHDN
V
OUT
5V
SHUTDOWN
SHDN
GND
R2
12.3k
R1
37.4k
GND
R2
12.1k
C2
10µF
C1: AVX TAJB226M010
C2: TAIYO YUDEN EMK325BJ475MN
D1: MOTOROLA MBR0520
C1: AVX TAJB226M010
C2: TAIYO YUDEN LMK325BJ106MN
C3: TAIYO YUDEN LMK212BJ105MG
D1: MOTOROLA MBR0520
1613 F10
L1: MURATA LQH3C100
1613 F13
L1, L2: MURATA LQH3C220
Figure 10. 5V to 12V Boost Converter with 4.7µF Ceramic
Output Capacitor, CPL Added to Increase Phase Margin
Figure 13. 5V Output SEPIC with Ceramic
Output Capacitor. CPL Adds Phase Margin
VOUT
100mV/DIV
AC COUPLED
V
OUT
50mV/DIV
AC COUPLED
130mA
10mA
120mA
20mA
LOAD CURRENT
LOAD CURRENT
200µs/DIV
1613 F11
200µs/DIV
1613 F14
Figure 11. 5V to 12V Boost Converter
with 4.7µF Ceramic Output Capacitor
Figure 14. 5V Output SEPIC with 10µF
Ceramic Output Capacitor. No CPL. V = 4V
IN
VOUT
VOUT
50mV/DIV
100mV/DIV
AC COUPLED
AC COUPLED
130mA
10mA
120mA
20mA
LOAD CURRENT
LOAD CURRENT
200µs/DIV
1613 F12
200µs/DIV
1613 F15
Figure 12. 5V to 12V Boost Converter with 4.7µF
Ceramic Output Capacitor and 200pF Phase-Lead
Capacitor CPL and 10k in Series with FB Pin
Figure 15. 5V Output SEPIC with 10µF Ceramic Output
Capacitor, 330pF CPL and 10k in Series with FB Pin
8
LT1613
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OPERATIO
time required to reach final value increases to 1.7ms. In
Figure 19, CS is increased to 33nF. Input current does not
exceed the steady-state current the device uses to supply
power to the 50Ω load. Start-up time increases to 4.3ms.
CS can be increased further for an even slower ramp, if
desired.
START-UP/SOFT-START
When the LT1613 SHDN pin voltage goes high, the device
rapidly increases the switch current until internal current
limit is reached. Input current stays at this level until the
output capacitor is charged to final output voltage. Switch
current can exceed 1A. Figure 16’s oscillograph details
start-up waveforms of Figure 17’s SEPIC into a 50Ω load
without any soft-start. The output voltage reaches final
value in approximately 200µs, while input current reaches
400mA. Switch current in a SEPIC is 2x the input current,
so the switch is conducting approximately 800mA peak.
VOUT
2V/DIV
IIN
200mA/DIV
Soft-start reduces the inrush current by taking more time
to reach final output voltage. A soft-start circuit consisting
of Q1, RS1, RS2 and CS1 as shown in Figure 17 can be used
to limit inrush current to a lower value. Figure 18 pictures
VOUT and input current with RS2 of 33kΩ and CS of 10nF.
Input current is limited to a peak value of 200mA as the
V
S
5V/DIV
500µs/DIV
1613 F18
Figure 18. Soft-Start Components in Figure 17’s SEPIC
Reduces Inrush Current. CSS = 10nF, RLOAD = 50Ω
VOUT
VOUT
2V/DIV
2V/DIV
IIN
IIN
200mA/DIV
200mA/DIV
V
SHDN
V
S
5V/DIV
5V/DIV
200µs/DIV
1613 F16
1ms/DIV
1613 F18
Figure 16. Start-Up Waveforms of
Figure 17’s SEPIC Into 50Ω Load
Figure 19. Increasing CS to 33nF Further
Reduces Inrush Current. RLOAD = 50Ω
C3
1µF
L1
22µH
V
IN
4V
+
C1
L2
22µH
C
330pF
D1
PL
22µF
V
SW
FB
IN
SOFT-START COMPONENTS
LT1613
R
R3
10k
S1
33k
V
OUT
V
SHDN
S
5V
R1
37.4k
Q1
2N3904
GND
R2
12.1k
R
LOAD
C
10nF/
33nF
S
R
33k
S2
C2
10µF
1613 F17
C1: AVX TAJB226M006
C2: TAIYO YUDEN LMK325BJ106MN
C3: TAIYO YUDEN LMK212BJ105MG
D1: MOTOROLA MBR0520
L1, L2: MURATA LQH3C220
Figure 17. 5V SEPIC with Soft-Start Components
9
LT1613
U
TYPICAL APPLICATIO S
4-Cell to 5V SEPIC DC/DC Converter
C3
1µF
L1
22µH
D1
6.5V TO 4V
V
5V
175mA
OUT
+
V
SW
FB
C1
15µF
IN
L2
22µH
LT1613
374k
121k
4-CELL
+
C2
22µF
SHDN
SHDN
GND
L1, L2: MURATA LQH3C220
C3: AVX 1206YG105 CERAMIC
D1: MBR0520
1613 • TA03
4-Cell to 15V/30mA DC/DC Converter
L1
10µH
D1
Efficiency
V
IN
V
OUT
15V/30mA
3.5V TO
8V
85
80
75
70
65
60
55
50
V
= 6.5V
IN
+
V
SW
FB
C1
22µF
IN
1nF
10k
R1
137k
1%
+
LT1613
V = 5V
IN
C2
4.7µF
V
= 3.6V
IN
SHDN
SHDN
GND
R2
12.1k
C1: AVX TAJB226M016
C2: AVX TAJA475M025
D1: MOTOROLA MBR0520
L1: MURATA LQH3C100
1613 TA04
0
10 20 30 40 50 60 70 80 90 100
LOAD CURRENT (mA)
1613 TA04a
3.3V to 8V/70mA, –8V/5mA, 24V/5mA TFT LCD Bias Supply Uses All Ceramic Capacitors
D2
V
OFF
–8V
5mA
1µF
D3
V
ON
24V
5mA
0.22µF
0.22µF
0.22µF: TAIYO YUDEN EMK212BJ224MG
1µF
1µF
D4
1µF: TAIYO YUDEN LMK212BJ105MG
4.7µF: TAIYO YUDEN LMK316BJ475ML
D1: MOTOROLA MBRO520
0.22µF
D2, D3, D4: BAT54S
L1: SUMIDA CDRH5D185R4
L1
D1
5.4µH
V
IN
3.3V
AV
DD
8V
70mA
V
IN
SW
274k
LT1613
C1
C2
4.7µF
4.7µF
SHDN
FB
GND
48.7k
1613 TA05
10
LT1613
U
TYPICAL APPLICATIO S
4-Cell to 5V/50mA, 12V/10mA, 15V/10mA Digital Camera Power Supply
D3
D2
D1
15V/10mA
12V/10mA
5V/50mA
C1: TAIYO YUDEN JMK316BJ106ML
C2, C3, C4: TAIYO YUDEN EMK212BJ105MG
C5: TAIYO YUDEN JMK212BJ475MG
D1: MOTOROLA MBR0520
2
5
C3
1µF
D2, D3: BAT54
T1: COILCRAFT CCI8245A
(847) 639-6400
C4
1µF
V
IN
7V TO 3.6V
T1
6
3
4
C5
4.7µF
1
C1
10µF
C2
1µF
V
SW
270pF
102k
IN
LT1613
SHDN
SHUTDOWN
FB
GND
33.2k
1613 TA07
4-Cell to 5V/50mA, 15V/10mA, –7.5V/10mA Digital Camera Power Supply
D2
15V/10mA
C1: TAIYO YUDEN JMK316BJ106ML
C2, C3, C4: TAIYO YUDEN EMK212BJ105MG
C5: TAIYO YUDEN JMK212BJ475MG
D1: MOTOROLA MBR0520
2
5
C3
1µF
D1
D2, D3: BAT54
5V/50mA
T1: COILCRAFT CCI8244A
(847) 639-6400
C5
4.7µF
V
IN
7V TO 3.6V
T1
6
3
4
C4
1µF
D3
1
–7.5V/10mA
C1
10µF
C2
1µF
V
IN
SW
270pF
LT1613
SHDN
102k
SHUTDOWN
FB
GND
33.2k
1613 TA08
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofits circuits as describedhereinwillnotinfringeonexistingpatentrights.
11
LT1613
U
TYPICAL APPLICATIONS
Li-Ion to 16V/20mA Step-Up DC/DC Converter
L1
2.2µH
D1
V
IN
2.7V
TO 4.5V
+
V
SW
FB
C1
4.7µF
IN
LT1613
165k
1%
16V
SHDN
SHDN
20mA
C2
1µF
X5R
GND
13.7k
1%
CERAMIC
C1: AVX TAJA4R7M010
C2: TAIYO YUDEN LMK212BJ105MG
D1: BAT54S DUAL DIODE
L1: MURATA LQH3C2R2
1613 TA06
U
Dimensions in inches (millimeters) unless otherwise noted.
PACKAGE DESCRIPTION
S5 Package
5-Lead Plastic SOT-23
(LTC DWG # 05-08-1633)
2.60 – 3.00
(0.102 – 0.118)
2.80 – 3.00
(0.110 – 0.118)
(NOTE 3)
1.50 – 1.75
(0.059 – 0.069)
0.00 – 0.15
(0.00 – 0.006)
0.90 – 1.45
(0.035 – 0.057)
0.35 – 0.55
(0.014 – 0.022)
0.35 – 0.50
0.90 – 1.30
0.09 – 0.20
0.95
(0.037)
REF
(0.014 – 0.020)
FIVE PLACES (NOTE 2)
(0.035 – 0.051)
(0.004 – 0.008)
(NOTE 2)
1.90
(0.074)
REF
NOTE:
S5 SOT-23 0599
1. DIMENSIONS ARE IN MILLIMETERS
2. DIMENSIONS ARE INCLUSIVE OF PLATING
3. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
4. MOLD FLASH SHALL NOT EXCEED 0.254mm
5. PACKAGE EIAJ REFERENCE IS SC-74A (EIAJ)
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
LT1307
Single Cell Micropower DC/DC
2-Cell Micropower DC/DC
3.3V/75mA From 1V; 600kHz Fixed Frequency
LT1317
3.3V/200mA From Two Cells; 600kHz Fixed Frequency
LTC1474
LT1521
Low Quiescent Current, High Efficiency Step-Down Converter 94% Efficiency, 10µA I , 9V to 5V at 250µA
Q
300mA Low Dropout Regulator with Micropower Quiescent
Current and Shutdown
500mV Dropout, 300mA Output Current, 12µA I
Q
LTC1517-5
LT1610
Micropower, Regulated Charge Pump
3-Cells to 5V at 20mA, SOT-23 Package, 6µA I
Q
1.7MHz Single Cell Micropower DC/DC Converter
Inverting 1.4MHz Switching Regulator
30µA I , MSOP Package, Internal Compensation
Q
LT1611
5V to –5V at 150mA, Low Output Noise
LT1615/LT1615-1 Micropower DC/DC Converter in 5-Lead SOT-23
20V at 12mA from 2.5V Input, Tiny SOT-23 Package
1613f LT/TP 1299 4K • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
12
LINEAR TECHNOLOGY CORPORATION 1997
●
●
(408)432-1900 FAX:(408)434-0507 www.linear-tech.com
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