LT1946 [Linear]
1.2MHz Boost DC/DC Converter with 1.5A Switch and Soft-Start; 的1.2MHz升压型DC / DC转换器与1.5A开关和软启动型号: | LT1946 |
厂家: | Linear |
描述: | 1.2MHz Boost DC/DC Converter with 1.5A Switch and Soft-Start |
文件: | 总12页 (文件大小:268K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LT1946
1.2MHz Boost
DC/DC Converter with
1.5A Switch and Soft-Start
U
FEATURES
DESCRIPTIO
TheLT®1946isafixedfrequencystep-upDC/DCconverter
containing an internal 1.5A, 36V switch. Capable of gener-
ating 8V at 430mA from a 3.3V input, the LT1946 is ideal
for large TFT-LCD panel power supplies. The LT1946
switches at 1.2MHz, allowing the use of tiny, low profile
inductors and low value ceramic capacitors. Loop com-
pensationcanbeeitherinternalorexternal, givingtheuser
flexibility in setting loop compensation and allowing opti-
mized transient response with low ESR ceramic output
capacitors.Soft-startiscontrolledwithanexternalcapaci-
tor, which determines the input current ramp rate during
start-up.
■
1.5A, 36V Internal Switch
■
1.2MHz Switching Frequency
■
Integrated Soft-Start Function
Output Voltage Up to 34V
Low VCESAT Switch: 300mV at 1.5A (Typ)
8V at 430mA from a 3.3V Input
Small 8-Lead MSOP Package
■
■
■
■
U
APPLICATIO S
■
TFT-LCD Bias Supplies
■
GPS Receivers
■
DSL Modems
Local Power Supplies
The 8-lead MSOP package and high switching frequency
ensurealowprofileoverallsolutionlessthan1.2mmhigh.
■
, LTC and LT are registered trademarks of Linear Technology Corporation.
U
TYPICAL APPLICATIO
Efficiency
L1
D1
90
85
80
75
4.7µH
V
OUT
V
IN
8V
3.3V
430mA
6
5
SW
V
R1
28.7k
IN
3
1
OFF ON
SHDN
C1
LT1946
2
2.2µF
C2
20µF
70
65
V
C
FB
R
C
SS COMP GND
49.9k
R2
5.23k
8
7
4
C
C
C
SS
60
55
50
470pF
100nF
1946 F01
C1: 2.2µF, X5R OR X7R, 6.3V
C2: 2 × 10µF, X5R OR X7R, 10V
D1: MICROSEMI UPS120 OR EQUIVALENT
L1: TDK RLF5018T-4R7M1R4
100
200
LOAD CURRENT (mA)
400
0
500
300
1946 F01b
Figure 1. 3.3V to 8V, 430mA Step-Up DC/DC Converter
sn1946 1946fs
1
LT1946
W W U W
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ABSOLUTE AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
(Note 1)
ORDER PART
VIN Voltage ............................................................. 16V
SW Voltage ............................................... –0.4V to 36V
FB Voltage ............................................................. 2.5V
SHDN Voltage ......................................................... 16V
Current Into FB Pin .............................................. ±1mA
Maximum Junction Temperature ......................... 125°C
Operating Temperature Range (Note 2) .. –40°C to 85°C
Storage Temperature Range ................ –65°C to 150°C
Lead Temperature (Soldering, 10 sec)................. 300°C
NUMBER
TOP VIEW
V
1
2
3
4
8 SS
7 COMP
C
LT1946EMS8
FB
SHDN
GND
6 V
5 SW
IN
MS8 PACKAGE
8-LEAD PLASTIC MSOP
MS8 PART MARKING
LTUG
TJMAX = 125°C, θJA = 125°C/W
(4-LAYER BOARD)
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 3V, VSHDN = VIN unless otherwise specified. (Note 2)
SYMBOL
CONDITIONS
MIN
TYP
MAX
2.6
UNITS
Minimum Operating Voltage
Maximum Operating Voltage
Feedback Voltage
2.45
V
V
16
1.230
1.220
1.250
1.270
1.270
V
V
●
●
FB Pin Bias Current
V
FB
= 1.250V (Note 3)
20
40
120
nA
µmhos
V/V
Error Amp Transconductance
Error Amp Voltage Gain
Quiescent Current
∆I = 2µA
300
3.2
0
V
V
= 2.5V, Not Switching
5
1
mA
SHDN
Quiescent Current in Shutdown
Reference Line Regulation
Switching Frequency
= 0V, V = 3V
µA
SHDN
IN
2.6V ≤ V ≤ 16V
0.01
1.2
0.05
%/V
IN
0.9
0.8
1.4
1.5
MHz
MHz
●
Switching Frequency in Foldback
Maximum Duty Cycle
V
= 0V
0.4
90
MHz
%
FB
●
●
86
Switch Current Limit
(Note 4)
= 1A
1.5
2.1
240
0.01
4
3.1
340
1
A
Switch V
I
mV
µA
µA
V
CESAT
SW
Switch Leakage Current
Soft-Start Charging Current
SHDN Input Voltage High
SHDN Input Voltage Low
SHDN Pin Bias Current
V
SW
V
SS
= 5V
= 0.5V
2.5
2.4
6
0.5
V
V
SHDN
V
SHDN
= 3V
= 0V
16
0
32
0.1
µA
µA
Note 1: Absolute Maximum Ratings are those values beyond which the life
Note 3: Current flows out of FB pin.
of a device may be impaired.
Note 4: Current limit guaranteed by design and/or correlation to static test.
Note 2: The LT1946E is guaranteed to meet performance specifications
from 0°C to 70°C. Specifications over the –40°C to 85°C operating
temperature range are assured by design, characterization and correlation
with statistical process controls.
Current limit is independent of duty cycle and is guaranteed by design.
sn1946 1946fs
2
LT1946
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TYPICAL PERFOR A CE CHARACTERISTICS
Feedback Pin Voltage
Oscillator Frequency
Current Limit
2.6
2.4
2.2
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
1400
1200
1000
800
600
400
200
0
1.28
1.27
1.26
T
= –30°C
T
T
= 100°C
= 25°C
1.25
1.24
1.23
1.22
1.21
A
A
A
1.20
–50 –25
0
25
50
75 100 125
–25
0
50
75 100 125
0.8
1.2
–50
25
0
0.2
0.4
0.6
1.0
TEMPERATURE (°C)
TEMPERATURE (°C)
FEEDBACK VOLTAGE (V)
1946 G03
1946 G01
1946 G02
Switching Waveforms
for Figure 1 Circuit
Switch Saturation Voltage
Quiescent Current
3.8
3.6
3.4
3.2
3.0
2.8
2.6
2.4
2.2
0.35
0.30
VOUT
20mV/DIV
AC COUPLED
0.25
VSW
5V/DIV
0.20
0.15
0.10
0.05
0V
ILI
0.5A/DIV
AC COUPLED
0.5µs/DIV
1946 G06
2.0
0
–50 –25
0
25
50
125
75 100
0
0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6
TEMPERATURE (°C)
SWITCH CURRENT (A)
1946 G05
1946 G04
sn1946 1946fs
3
LT1946
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PI FU CTIO S
VC (Pin 1): Error Amplifier Output Pin. Tie external com-
pensation network to this pin, or use the internal compen-
sation network by shorting the VC pin to the COMP pin.
VIN (Pin 6): Input Supply Pin. Must be locally bypassed.
COMP (Pin 7): Internal Compensation Pin. Provides an
internal compensation network. Tie directly to the VC pin
for internal compensation. Tie to GND if not used.
FB (Pin 2): Feedback Pin. Reference voltage is 1.250V.
Connect resistive divider tap here. Minimize trace area at
FB. Set VOUT according to VOUT = 1.250(1 + R1/R2).
SS (Pin 8): Soft-Start Pin. Place a soft-start capacitor
here. Upon start-up, 4µA of current charges the capacitor
to 1.5V. Use a larger capacitor for slower start-up. Leave
floating if not in use.
SHDN(Pin3):ShutdownPin.Tieto2.4Vormoretoenable
device. Ground to shut down. Do not float this pin.
GND (Pin 4): Ground. Tie directly to local ground plane.
SW (Pin 5): Switch Pin. This is the collector of the internal
NPN power switch. Minimize the metal trace area con-
nected to this pin to minimize EMI.
W
BLOCK DIAGRA
SS
8
V
COMP
C
1
7
120k
90pF
4µA
SW
5
COMPARATOR
–
+
DRIVER
R
Q
A2
Q1
S
V
IN
1.250V
REFERENCE
6
+
–
+
–
0.01Ω
A1
Σ
V
OUT
RAMP
GENERATOR
R1 (EXTERNAL)
FB
4
0.5V
+
–
GND
R2 (EXTERNAL)
÷3
1946 BD
1.2MHz
OSCILLATOR
A3
SHUTDOWN
3
2
SHDN
FB
Figure 2. Block Diagram
sn1946 1946fs
4
LT1946
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OPERATIO
The LT1946 uses a constant frequency, current mode
control scheme to provide excellent line and load regula-
tion. Please refer to Figure 2 for the following description
of the part’s operation. At the start of the oscillator cycle,
the SR latch is set, turning on the power switch Q1. The
switch current flows through the internal current sense
resistor generating a voltage. This voltage is added to a
stabilizing ramp and the resulting sum is fed into the
positive terminal of the PWM comparator A2. When this
voltageexceedsthelevelatthenegativeinputofA2,theSR
latch is reset, turning off the power switch. The level at the
negative input of A2 (VC pin) is set by the error amplifier
(A1) and is simply an amplified version of the difference
between the feedback voltage and the reference voltage of
1.250V. In this manner, the error amplifier sets the correct
peak current level to keep the output in regulation.
below a nominal value of 0.5V. This is accomplished via
comparator A3. This feature reduces the minimum duty
cycle that the part can achieve thus allowing better control
of the switch current during start-up. When the FB pin
voltage exceeds 0.5V, the oscillator returns to the normal
frequencyof1.2MHz.Asoft-startfunctionisalsoprovided
by the LT1946. When the part is brought out of shutdown,
4µA of current is sourced out of the SS pin. By connecting
an external capacitor to the SS pin, the rate of voltage rise
on the pin can be set. Typical values for the soft-start
capacitor range from 10nF to 200nF. The SS pin directly
limits the rate of rise on the VC pin, which in turn limits the
peak switch current. Current limit is not shown in Figure 2.
The switch current is constantly monitored and not al-
lowed to exceed the nominal value of 2.1A. If the switch
current reaches 2.1A, the SR latch is reset regardless of
the output of comparator A2. This current limit helps
protect the power switch as well as the external compo-
nents connected to the LT1946.
Two functions are provided to enable a very clean start-up
for the LT1946. Frequency foldback is used to reduce the
oscillator frequency by a factor of 3 when the FB pin is
W U U
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APPLICATIO S I FOR ATIO
TheinductorsshowninTable1werechosenforsmallsize.
For better efficiency, use similar valued inductors with a
larger volume.
Inductor Selection
SeveralinductorsthatworkwellwiththeLT1946arelisted
in Table 1. This table is not exclusive; there are many other
manufacturers and inductors that can be used. Consult
each manufacturer for more detailed information and for
their entire selection of related parts, as many different
sizes and shapes are available. Ferrite core inductors
shouldbeusedtoobtainthebestefficiency, ascorelosses
at 1.2MHz are much lower for ferrite cores than for the
cheaperpowdered-ironones. Chooseaninductorthatcan
handleatleast1.5Awithoutsaturating,andensurethatthe
inductor has a low DCR (copper wire resistance) to mini-
mize I2R power losses. A 4.7µH to 10µH inductor will be
the best choice for most LT1946 designs. Note that in
some applications, the current handling requirements of
the inductor can be lower, such as in the SEPIC topology
where each inductor only carries one-half of the total
switch current.
Table 1. Recommended Inductors
MAX
DCR
(µH) (mΩ)
SIZE
L × W × H
(mm)
L
PART
VENDOR
CDRH5D18-4R1
CDRH5D18-5R4
CDRH5D28-5R3
CDRH5D28-6R2
CDRH5D28-8R2
4.1
5.4
5.3
6.2
8.2
57
76
38
45
53
5.7 × 5.7 × 2
Sumida
(847) 956-0666
www.sumida.com
5.7 × 5.7 × 3
ELL6SH-4R7M
ELL6SH-5R6M
ELL6SH-6R8M
4.7
5.6
6.8
50
59
62
6.4 × 6 × 3
Panasonic
(408) 945-5660
www.panasonic.com
RLF5018T-
4R7M1R4
4.7
45
5.6 × 5.2 × 1.8 TDK
(847) 803-6100
www.tdk.com
sn1946 1946fs
5
LT1946
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APPLICATIO S I FOR ATIO
Capacitor Selection
Low ESR (equivalent series resistance) capacitors should
beusedattheoutputtominimizetheoutputripplevoltage.
Multilayer ceramic capacitors are an excellent choice, as
they have an extremely low ESR and are available in very
small packages. X5R dielectrics are preferred, followed by
X7R, as these materials retain the capacitance over wide
voltage and temperature ranges. A 4.7µF to 20µF output
capacitor is sufficient for most applications, but systems
withverylowoutputcurrentsmayneedonlya1µFor2.2µF
output capacitor. Solid tantalum or OS-CON capacitors
can be used, but they will occupy more board area than a
ceramicandwillhaveahigherESR.Alwaysuseacapacitor
with a sufficient voltage rating.
VOUT
20mV/DIV
AC COUPLED
ILI
0.5A/DIV
AC COUPLED
R
C = 7.5k
200µs/DIV
1946 F03a
Figure 3a. Transient Response Shows Excessive Ringing
VOUT
20mV/DIV
Ceramic capacitors also make a good choice for the input
decoupling capacitor, which should be placed as close as
possible to the LT1946. A 2.2µF to 4.7µF input capacitor is
sufficient for most applications. Table 2 shows a list of
several ceramic capacitor manufacturers. Consult the
manufacturers for detailed information on their entire
selection of ceramic parts.
AC COUPLED
ILI
0.5A/DIV
AC COUPLED
RC = 18k
200µs/DIV
1946 F03b
Figure 3b. Transient Response is Better
Table 2. Ceramic Capacitor Manufacturers
Taiyo Yuden
(408) 573-4150
www.t-yuden.com
AVX
(803) 448-9411
www.avxcorp.com
Murata
(714) 852-2001
www.murata.com
VOUT
20mV/DIV
AC COUPLED
Compensation—Adjustment
ILI
0.5A/DIV
To compensate the feedback loop of the LT1946, a series
resistor-capacitor network should be connected from the
COMP pin to GND. For most applications, a capacitor in
the range of 220pF to 680pF will suffice. A good starting
value for the compensation capacitor, CC, is 470pF. The
compensation resistor, RC, is usually in the range of 20k
to 100k. A good technique to compensate a new applica-
tion is to use a 100kΩ potentiometer in place of RC, and
use a 470pF capacitor for CC. By adjusting the potentiom-
eter while observing the transient response, the optimum
value for RC can be found. Figures 3a to 3c illustrate this
process for the circuit of Figure 1 with a load current
steppedfrom250mAto300mA.Figure3ashowsthetran-
sient response with RC equal to 7.5k. The phase margin is
AC COUPLED
RC = 49.9k
200µs/DIV
1946 F03b
Figure 3c. Transient Response is Well Damped
poor as evidenced by the excessive ringing in the output
voltage and inductor current. In Figure 3b, the value of RC
is increased to 18k, which results in a more damped re-
sponse. Figure 3c shows the results when RC is increased
further to 49.9k. The transient response is nicely damped
and the compensation procedure is complete. The COMP
pin provides access to an internal resistor (120k) and
capacitor (90pF). For some applications, these values will
suffice and no external RC and CC will be needed.
sn1946 1946fs
6
LT1946
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APPLICATIO S I FOR ATIO
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Compensation—Theory
–
+
Like all other current mode switching regulators, the
LT1946 needs to be compensated for stable and efficient
operation. Two feedback loops are used in the LT1946: a
fast current loop which does not require compensation,
and a slower voltage loop which does. Standard Bode plot
analysis can be used to understand and adjust the voltage
feedback loop.
g
mp
V
OUT
C
R
L
OUT
1.250V
REFERENCE
+
–
V
C
g
ma
R1
R
C
R
O
R2
1946 F04
C
C
C : COMPENSATION CAPACITOR
C
As with any feedback loop, identifying the gain and phase
contribution of the various elements in the loop is critical.
Figure 4 shows the key equivalent elements of a boost
converter. Because of the fast current control loop, the
power stage of the IC, inductor and diode have been
replaced by the equivalent transconductance amplifier
C
g
mp
: OUTPUT CAPACITOR
OUT
: TRANSCONDUCTANCE AMPLIFIER INSIDE IC
ma
g
: POWER STAGE TRANSCONDUCTANCE AMPLIFIER
R : COMPENSATION RESISTOR
C
L
O
R : OUTPUT RESISTANCE DEFINED AS V
DIVIDED BY I
LOAD(MAX)
OUT
R : OUTPUT RESISTANCE OF g
ma
R1, R2: FEEDBACK RESISTOR DIVIDER NETWORK
Figure 4. Boost Converter Equivalent Model
g
mp. gmp actsasacurrentsourcewheretheoutputcurrent
is proportional to the VC voltage. Note that the maximum
output current of gmp is finite due to the current limit in the
IC.
The Current Mode zero is a right half plane zero which can
be an issue in feedback control design, but is manageable
with proper external component selection.
From Figure 4, the DC gain, poles and zeroes can be
calculated as follows:
Using the circuit of Figure 1 as an example, the following
tableshowstheparametersusedtogeneratetheBodeplot
shown in Figure 5.
Table 3. Bode Plot Parameters
2
Output Pole: P1=
Parameter
Value
18.6
20
Units
Ω
Comment
2• π •RL •COUT
R
L
Application Specific
Application Specific
Not Adjustable
Adjustable
1
Error Amp Pole: P2 =
2• π •RO •CC
1
Error Amp Zero: Z1=
2• π •RC •CC
C
OUT
µF
R
C
R
10
MΩ
pF
O
C
C
470
49.9
8
kΩ
V
Adjustable
V
OUT
Application Specific
Application Specific
Not Adjustable
Not Adjustable
Application Specific
Not Adjustable
1.25
VOUT
DC GAIN: A =
•gma •RO •gmp •RL
V
3.3
40
V
IN
g
g
µmho
mho
µH
ma
1
ESR Zero: Z2 =
5
mp
2• π •ESR•COUT
L
5.4
1.2
V
2 •RL
f
MHz
IN
S
RHP Zero: Z3 =
2• π •VOUT2 •L
From Figure 5, the phase is 120° when the gain reaches
0dB giving a phase margin of 60°. This is more than
adequate. The crossover frequency is 25kHz, which is
aboutthreetimeslowerthanthefrequencyoftherighthalf
plane zero Z2. It is important that the crossover frequency
be at least three times lower than the frequency of the RHP
fS
3
High Frequency Pole: P3 >
zero to achieve adequate phase margin.
sn1946 1946fs
7
LT1946
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APPLICATIO S I FOR ATIO
100
Diode Selection
ASchottkydiodeisrecommendedforusewiththeLT1946.
The Microsemi UPS120 is a very good choice. Where the
input to output voltage differential exceeds 20V, use the
UPS140(a40Vdiode).Thesediodesareratedtohandlean
average forward current of 1A. For applications where the
average forward current of the diode is less than 0.5A, an
ON Semiconductor MBR0520 diode can be used
50
0
–50
Setting Output Voltage
100
1k
10k 25k 100k
FREQUENCY (Hz)
1M
To set the output voltage, select the values of R1 and R2
(see Figure 1) according to the following equation:
1946 F05a
0
VOUT
1.25V
R1= R2
– 1
A good range for R2 is from 5k to 30k.
–100
Layout Hints
60°
ThehighspeedoperationoftheLT1946demandscareful
attention to board layout. You will not get advertised
performance with careless layout. Figure 6 shows the
recommended component placement for a boost
converter.
–180
–200
100
1k
10k 25k 100k
FREQUENCY (Hz)
1M
1946 F05b
Figure 5. Bode Plot of Figure 1’s Circuit
GROUND PLANE
C
SS
C1
+
C
C
C
V
IN
R
1
8
7
6
5
R1
2
3
4
L1
LT1946
R2
SHUTDOWN
MULTIPLE
VIAs
C2
GND
V
OUT
1946 F06
Figure 6. Recommended Component Placement for Boost Converter. Note Direct High Current Paths Using Wide PC Traces. Minimize
Trace Area at Pin 1 (VC) and Pin 2 (FB). Use Multiple Vias to Tie Pin 4 Copper to Ground Plane. Use Vias at One Location Only to Avoid
Introducing Switching Currents Into the Ground Plane
sn1946 1946fs
8
LT1946
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TYPICAL APPLICATIO S
Low Profile, Triple Output TFT Supply (10V, –10V, 20V)
D2
D3
V
ON
20V
5mA
C5
0.1µF
L1
5.4µH
AV
D1
DD
V
10V
IN
3.3V TO 5V
450mA, V = 5V
IN
6
5
SW
275mA, V = 3.3V
IN
R1
V
IN
3
8
7
75k
OFF ON
SHDN
SS LT1946
COMP
2
+
C2
20µF
C3
1µF
FB
C1
4.7µF
V
GND
4
C
1
R
33.3k
R2
10.5k
C
SS
C
100nF
C
C
470pF
C6
0.1µF
C1 TO C6: X5R OR X7R
C1: 4.7µF, 6.3V
C2: 2 × 10µF, 10V
C3: 1µF, 25V
C4: 2.2µF, 10V
C5, C6: 0.1µF, 10V
D4
D5
C4
2.2µF
V
OFF
D1: MICROSEMI UPS120 OR EQUIVALENT
D2 TO D5: ZETEX BAT54S OR EQUIVALENT
L1: SUMIDA CDRH5D18-5R4
–10V
1946 TA01
10mA
Efficiency
Transient Response
90
85
80
75
AVDD
V
= 5V
IN
50mV/DIV
AC COUPLED
V
= 3.3V
IN
ILI
0.5A/DIV
70
65
60
55
50
AVDD
150mA
LOAD 100mA
V
V
LOAD = 5mA
LOAD = 10mA
ON
OFF
V
IN = 5V
100µs/DIV
1946 TA01b
100
200
400
0
500
300
AV LOAD CURRENT (mA)
DD
1946 TA01a
sn1946 1946fs
9
LT1946
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TYPICAL APPLICATIO S
12V Output Boost Converter
L1
D1
V
OUT
4.7µH
V
12V
410mA, V = 5V
IN
3.3V TO 5V
IN
IN
6
5
SW
275mA, V = 3.3V
V
IN
R1
84.5k
3
1
OFF ON
SHDN
C1
LT1946
2
4.7µF
C2
4.7µF
V
FB
C
R
C
SS COMP GND
33.3k
R2
9.76k
8
7
4
C
C
C
SS
470pF
100nF
1946 TA02
C1: 4.7µF, X5R OR X7R, 6.3V
C2: 4.7µF, X5R OR X7R, 16V
D1: MICROSEMI UPS120 OR EQUIVALENT
L1: TDK RLF5018T-4R7M1R4
Efficiency
Transient Response
90
85
80
75
V
= 5V
IN
VOUT
100mV/DIV
V
= 3.3V
AC COUPLED
IN
70
65
ILI
0.5A/DIV
60
55
50
175mA
100mA
ILOAD
V
IN = 3.3V
100µs/DIV
1946 TA02b
100
200
300
400
0
500
LOAD CURRENT (mA)
1946 TA02a
sn1946 1946fs
10
LT1946
U
PACKAGE DESCRIPTIO
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660)
0.889 ± 0.127
(.035 ± .005)
5.23
(.206)
MIN
3.2 – 3.45
(.126 – .136)
3.00 ± 0.102
(.118 ± .004)
(NOTE 3)
0.52
(.206)
REF
0.65
(.0256)
BSC
0.42 ± 0.04
(.0165 ± .0015)
TYP
8
7 6
5
RECOMMENDED SOLDER PAD LAYOUT
3.00 ± 0.102
(.118 ± .004)
NOTE 4
4.88 ± 0.1
(.192 ± .004)
DETAIL “A”
0.254
(.010)
0° – 6° TYP
GAUGE PLANE
1
2
3
4
0.53 ± 0.015
(.021 ± .006)
1.10
(.043)
MAX
0.86
(.034)
REF
DETAIL “A”
0.18
(.077)
SEATING
PLANE
0.22 – 0.38
(.009 – .015)
0.13 ± 0.05
(.005 ± .002)
0.65
(.0256)
BCS
MSOP (MS8) 1001
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
sn1946 1946fs
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
11
LT1946
U
TYPICAL APPLICATIO
Low Profile, Triple Output TFT Supply (8V, –8V, 23V)
D2
D3
D4
D5
V
ON
23V
5mA
C5
0.1µF
C6
0.1µF
C7
0.1µF
L1
5.4µH
D1
AV
8V
DD
V
IN
3.3V
375mA
6
5
V
SW
R2
28.7k
IN
SHDN
3
8
7
OFF ON
SS LT1946
COMP
2
+
C2
20µF
C4
1µF
FB
C1
4.7µF
V
GND
4
C
1
R
49.9k
R3
5.23k
C
SS
100nF
C
C
C
470pF
C8
0.1µF
C1 TO C8: X5R OR X7R
C1: 4.7µF, 6.3V
D7
D6
C3
2.2µF
C2: 2 × 10µF, 10V
C3: 2.2µF, 10V
C4: 1µF, 25V
C5, C6, C8: 0.1µF, 10V
C7: 0.1µF, 16V
V
OFF
–8V
D1: MICROSEMI UPS120 OR EQUIVALENT
D2 TO D5: ZETEX BAT54S OR EQUIVALENT
L1: SUMIDA CDRH5D18-5R4
1946 TA03
10mA
Efficiency
Start-Up Waveforms
85
80
75
AVDD
2V/DIV
VON
70
65
60
55
50
10V/DIV
VOFF
5V/DIV
V
V
LOAD = 5mA
ON
OFF
IIN
200mA/V
LOAD = 10mA
0
100
200
300
400
1ms/DIV
1946 TA04
AV LOAD CURRENT (mA)
DD
1946 TA03a
RELATED PARTS
PART NUMBER
DESCRIPTION
1.4MHz Switching Regulator in 5-Lead ThinSOTTM
Micropower Constant Off-Time DC/DC Converter in 5-Lead ThinSOT 20V at 12mA from 2.5V, ThinSOT Package
1.2MHz/2.2MHz, 1A Switching Regulator in 5-Lead ThinSOT 12V at 300mA from 5V Input, ThinSOT Package
COMMENTS
LT1613
5V at 200mA from 3.3V Input, ThinSOT Package
LT1615
LT1930/LT1930A
LT1944/LT1944-1 Dual 350mA Boost Converter
V
V
V
= 1.2V to 15V, V
= 1.2V to 15V, V
to 34V, MS10 Package
IN
IN
IN
OUT
OUT
LT1945
LT1946A
LT1947
Dual ±250mA Boost Converter
to ±34V, MS10 Package
12.7MHz, 1.5A Boost DC/DC Converter
3MHz, Dual Switching Regulator
= 2.45V to 16V, V
to 34V, MS8E Package
OUT
8V at 200mA from 3.3V Input, 10-Lead MSOP Package
Burst Mode and ThinSOT are trademarks of Linear Technology Corporation.
sn1946 1946fs
LT/TP 1002 2K • PRINTED IN USA
12 LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
●
●
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
LINEAR TECHNOLOGY CORPORATION 2001
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