LT5568EUF [Linear]
RF/Microwave Modulator/Demodulator, 700 MHz - 1050 MHz RF/MICROWAVE I/Q MODULATOR, 4 X 4 MM, PLASTIC, MO-220WGGC, QFN-16;型号: | LT5568EUF |
厂家: | Linear |
描述: | RF/Microwave Modulator/Demodulator, 700 MHz - 1050 MHz RF/MICROWAVE I/Q MODULATOR, 4 X 4 MM, PLASTIC, MO-220WGGC, QFN-16 射频 微波 |
文件: | 总16页 (文件大小:328K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LT5568
700MHz – 1050MHz High
Linearity Direct Quadrature
Modulator
U
DESCRIPTIO
FEATURES
The LT®5568 is a direct I/Q modulator designed for high
performance wireless applications, including wireless
infrastructure. It allows direct modulation of an RF signal
using differential baseband I and Q signals. It supports
PHS, GSM, EDGE, TD-SCDMA, CDMA, CDMA2000, W-
CDMA, and other systems. It may also be configured
as an image reject upconverting mixer, by applying
90° phase-shifted signals to the I and Q inputs. The I/Q
baseband inputs consist of voltage-to-current converters
that in turn drive double-balanced mixers. The outputs of
these mixers are summed and applied to an on-chip RF
transformer, which converts the differential mixer signals
to a 50Ω single-ended output. The four balanced I and Q
baseband input ports are intended for DC coupling from a
source with a common mode voltage level of about 0.5V.
The LO path consists of an LO buffer with single-ended
input, and precision quadrature generators that produce
the LO drive for the mixers. The supply voltage range is
4.5V to 5.25V.
■
Frequency Range: 700MHz to 1050MHz
■
High OIP3: +22.9dBm at 850MHz
■
Low Output Noise Floor at 5MHz Offset:
No RF: –160.3dBm/Hz
P
OUT
= 4dBm: –154dBm/Hz
■
■
3-Ch CDMA2000 ACPR: –71.4dBc at 850MHz
Integrated LO Buffer and LO Quadrature Phase
Generator
■
■
■
■
■
50Ω AC-Coupled Single-Ended LO and RF Ports
50Ω DC Interface to Baseband Inputs
Low Carrier Leakage: –43dBm at 850MHz
High Image Rejection: –46dBc at 850MHz
16-Lead 4mm × 4mm QFN Package
U
APPLICATIO S
■
Infrastructure Tx for Cellular Bands
■
Image Reject Up-Converters for Cellular Bands
■
Low-Noise Variable Phase-Shifter for 700MHz to
1050MHz Local Oscillator Signals
RFID Reader
, LTC and LT are registered trademarks of Linear Technology Corporation.
All other trademarks are the property of their respective owners.
■
U
TYPICAL APPLICATIO
CDMA2000 ACPR, AltCPR and Noise vs RF
Output Power at 850MHz for 1 and 3 Carriers
700MHz to 1050MHz Direct Conversion Transmitter Application
–50
–60
–70
–80
–90
–125
–135
–145
–155
5V
100nF
x2
DOWNLINK TEST MODEL 64 DPCH
V
1-CH.
ACPR
CC
LT5568
RF = 700MHz
TO 1050MHz
I-DAC
V-I
I-CHANNEL
3-CH. ACPR
PA
0°
EN
90°
3-CH. AltCPR
1-CH. AltCPR
1-CH. NOISE
BALUN
Q-CHANNEL
V-I
Q-DAC
3-CH. NOISE
5568 TA01
BASEBAND
GENERATOR
–165
VCO/SYNTHESIZER
–30
–25
–20
–15
–10
–5
RF OUTPUT POWER PER CARRIER (dBm)
5568 TA02
5568f
1
LT5568
W W U W
U
W
U
ABSOLUTE AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
(Note 1)
TOP VIEW
Supply Voltage.........................................................5.5V
Common Mode Level of BBPI, BBMI and
BBPQ, BBMQ .......................................................2.5V
Operating Ambient Temperature
16 15 14 13
EN
GND
LO
1
2
3
4
12 GND
11 RF
17
(Note 2) ............................................... –40°C to 85°C
Storage Temperature Range................... –65°C to 125°C
Voltage on any Pin
GND
GND
10
9
GND
5
6
7
8
Not to Exceed...................... –500mV to V + 500mV
CC
UF PACKAGE
16-LEAD (4mm × 4mm) PLASTIC QFN
= 125°C, θ = 37°C/W
T
JMAX
JA
EXPOSED PAD (PIN 17) IS GROUND, MUST BE SOLDERED TO PCB
ORDER PART NUMBER
UF PART MARKING
5568
LT5568EUF
Order Options Tape and Reel: Add #TR
Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF
Lead Free Part Marking: http://www.linear.com/leadfree/
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
VCC = 5V, EN = High, TA = 25°C, fLO = 850MHz, fRF = 852MHz, PLO = 0dBm.
BBPI, BBMI, BBPQ, BBMQ inputs 0.54VDC, Baseband Input Frequency = 2MHz, I&Q 90° shifted (upper side-band selection).
PRF, OUT = –10dBm, unless otherwise noted. (Note 3)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
RF Output (RF)
f
RF Frequency Range
RF Frequency Range
–3dB Bandwidth
–1dB Bandwidth
0.6 to 1.2
0.7 to 1.05
GHz
GHz
RF
S
S
RF Output Return Loss
RF Output Return Loss
RF Output Noise Floor
EN = High (Note 6)
EN = Low (Note 6)
–14
–12
dB
dB
22, ON
22, OFF
NFloor
No Input Signal (Note 8)
–160.3
–154
–154
dBm/Hz
dBm/Hz
dBm/Hz
P
P
= 4dBm (Note 9)
= 4dBm (Note 10)
OUT
OUT
G
G
Conversion Power Gain
Conversion Voltage Gain
Absolute Output Power
3 • LO Conversion Gain Difference
Output 1dB Compression
Output 2nd Order Intercept
Output 3rd Order Intercept
Image Rejection
P
/P
–9
–6.8
–6.8
–2.8
–23
8.3
–3
dB
dB
P
OUT IN, I&Q
20 • Log (V
/V
)
V
OUT, 50Ω IN, DIFF, I or Q
P
1V
CW Signal, I and Q
dBm
dB
OUT
P-P DIFF
G
(Note 17)
(Note 7)
3LO vs LO
OP1dB
OIP2
OIP3
IR
dBm
dBm
dBm
dBc
(Notes 13, 14)
(Notes 13, 15)
(Note 16)
63
22.9
–46
LOFT
Carrier Leakage
(LO Feedthrough)
EN = High, P = 0dBm (Note 16)
–43
–65
dBm
dBm
LO
EN = Low, P = 0dBm (Note 16)
LO
5568f
2
LT5568
ELECTRICAL CHARACTERISTICS
VCC = 5V, EN = High, TA = 25°C, fLO = 850MHz, fRF = 852MHz, PLO = 0dBm.
BBPI, BBMI, BBPQ, BBMQ inputs 0.54VDC, Baseband Input Frequency = 2MHz, I&Q 90° shifted (upper side-band selection).
PRF, OUT = –10dBm, unless otherwise noted. (Note 3)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
LO Input (LO)
f
LO Frequency Range
0.6 to 1.2
0
GHz
dBm
dB
LO
P
S
S
LO Input Power
–10
5
LO
LO Input Return Loss
EN = High (Note 6)
EN = Low (Note 6)
(Note 5) at 850MHz
(Note 5) at 850MHz
(Note 5) at 850MHz
–11.4
–2.7
12.7
11, ON
11, OFF
LO Input Return Loss
dB
NF
LO Input Referred Noise Figure
LO to RF Small Signal Gain
LO Input 3rd Order Intercept
dB
LO
G
23.8
dB
LO
IIP3
–11.5
dBm
LO
Baseband Inputs (BBPI, BBMI, BBPQ, BBMQ)
BW
Baseband Bandwidth
–3dB Bandwidth
(Note 4)
380
0.54
48
MHz
V
BB
V
DC Common Mode Voltage
Single-Ended Input Resistance
Carrier Feedthrough on BB
Input 1dB Compression Point
I/Q Absolute Gain Imbalance
I/Q Absolute Phase Imbalance
CMBB
Ω
R
(Note 4)
IN, SE
P
P
OUT
= 0 (Note 4)
–38
4.3
dBm
LO2BB
IP1dB
Differential Peak-to-Peak (Notes 7, 18)
V
P-P, DIFF
ΔG
0.07
0.45
dB
I/Q
I/Q
Δϕ
Deg
Power Supply (V
)
CC
V
Supply Voltage
4.5
80
5
5.25
165
50
V
mA
μA
μs
CC
I
I
t
t
Supply Current
EN = High
117
CC, ON
CC, OFF
ON
Supply Current, Sleep Mode
Turn-On Time
EN = 0V
EN = Low to High (Note 11)
EN = High to Low (Note 12)
0.3
1.4
Turn-Off Time
μs
OFF
Enable (EN), Low = Off, High = On
Enable
Input High Voltage
Input High Current
EN = High
EN = 5V
1.0
V
230
0
μA
Sleep
Input Low Voltage
Input Low Current
EN = Low
EN = 0V
0.5
V
μA
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
Note 10: At 5MHz offset from the CW signal frequency.
Note 11: RF power is within 10% of final value.
Note 2: Specifications over the –40°C to 85°C temperature range are
assured by design, characterization and correlation with statistical process
controls.
Note 3: Tests are performed as shown in the configuration of Figure 7.
Note 4: On each of the four baseband inputs BBPI, BBMI, BBPQ and
Note 12: RF power is at least 30dB lower than in the ON state.
Note 13: Baseband is driven by 2MHz and 2.1MHz tones. Drive level is set
in such a way that the two resulting RF tones are –10dBm each.
Note 14: IM2 measured at LO frequency + 4.1MHz.
Note 15: IM3 measured at LO frequency + 1.9MHz and LO frequency +
2.2MHz.
Note 16: Amplitude average of the characterization data set without image
or LO feedthrough nulling (unadjusted).
BBMQ.
Note 5: V(BBPI) – V(BBMI) = 1V , V(BBPQ) – V(BBMQ) = 1V
.
DC
DC
Note 6: Maximum value within –1dB bandwidth.
Note 7: An external coupling capacitor is used in the RF output line.
Note 8: At 20MHz offset from the LO signal frequency.
Note 9: At 20MHz offset from the CW signal frequency.
Note 17: The difference in conversion gain between the spurious signal at
f = 3 • LO – BB versus the conversion gain at the desired signal at f = LO +
BB for BB = 2MHz and LO = 850MHz.
Note 18: The input voltage corresponding to the output P1dB.
5568f
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LT5568
U W
VCC = 5V, EN = High, TA = 25°C, fLO = 850MHz,
LO = 0dBm. BBPI, BBMI, BBPQ, BBMQ inputs 0.54VDC, Baseband Input Frequency fBB = 2MHz, I&Q 90° shifted. fRF = fBB + fLO (upper
TYPICAL PERFOR A CE CHARACTERISTICS
P
sideband selection). PRF, OUT = –10dBm (–10dBm/tone for 2-tone measurements), unless otherwise noted. (Note 3)
RF Output Power vs LO Frequency
at 1VP-P Differential Baseband Drive
Supply Current vs Supply Voltage
Voltage Gain vs LO Frequency
140
130
120
110
100
–4
–6
0
–2
85°C
25°C
–8
–10
–12
–14
–4
–6
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
–8
–40°C
5V, 85°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
4.5V, 25°C
5.5V, 25°C
–10
4.5
5
5.5
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
LO FREQUENCY (MHz)
SUPPLY VOLTAGE (V)
LO FREQUENCY (MHz)
5568 G03
5568 G02
5568 G01
Output 1dB Compression
vs LO Frequency
Output IP3 vs LO Frequency
Output IP2 vs LO Frequency
26
24
70
65
60
55
50
10
8
f
f
= 2MHz
= 2.1MHz
BB, 1
BB, 2
f
f
f
= f
+ f
+ f
IM2 BB, 1 BB, 2 LO
= 2MHz
BB, 1
BB, 2
= 2.1MHz
22
20
18
16
6
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
4
5V, 85°C
5V, 85°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
4.5V, 25°C
5.5V, 25°C
4.5V, 25°C
5.5V, 25°C
2
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
5568 G04
5568 G06
5568 G05
LO Feedthrough to RF Output
vs LO Frequency
2 • LO Leakage to RF Output
vs 2 • LO Frequency
3 • LO Leakage to RF Output
vs 3 • LO Frequency
–40
–42
–44
–46
–48
–40
–45
–50
–55
–60
–40
–45
–50
–55
–60
–65
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
4.5V, 25°C
5.5V, 25°C
550 650 750 850 950 1050 1150 1250
LO FREQUENCY (MHz)
1.1 1.3 1.5 1.7 1.9 2.1 2.3 2.5
2 • LO FREQUENCY (GHz)
1.65 1.95 2.25 2.55 2.85 3.15 3.45 3.75
3 • LO FREQUENCY (GHz)
5568 G07
5568 G08
5568 G09
5568f
4
LT5568
U W
TYPICAL PERFOR A CE CHARACTERISTICS
VCC = 5V, EN = High, TA = 25°C, fLO = 850MHz,
LO = 0dBm. BBPI, BBMI, BBPQ, BBMQ inputs 0.54VDC, Baseband Input Frequency fBB = 2MHz, I&Q 90° shifted. fRF = fBB + fLO (upper
sideband selection). PRF, OUT = –10dBm (–10dBm/tone for 2-tone measurements), unless otherwise noted. (Note 3)
P
LO and RF Port Return Loss
vs RF Frequency
Noise Floor vs RF Frequency
Image Rejection vs LO Frequency
–160
–161
–162
–163
–164
0
–10
–20
–30
–40
–30
–35
–40
–45
–50
LO PORT, EN = LOW
f
= 850MHz
5V, –40°C
5V, 25°C
LO
(FIXED)
LO PORT, EN = HIGH,
= 0dBm
5V, 85°C
P
LO
4.5V, 25°C
5.5V, 25°C
RF PORT,
EN = LOW
5V, –40°C
5V, 25°C
LO PORT,
EN = HIGH,
5V, 85°C
P
= –10dBm
LO
RF PORT, EN = HIGH, No LO
4.5V, 25°C
5.5V, 25°C
RF PORT, EN = HIGH, P = 0dBm
LO
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
RF FREQUENCY (MHz)
RF FREQUENCY (MHz)
LO FREQUENCY (MHz)
5568 G12
5568 G10
5568 G11
Absolute I/Q Gain Imbalance
vs LO Frequency
Absolute I/Q Phase Imbalance
vs LO Frequency
Voltage Gain vs LO Power
–4
0.2
0.1
0
4
3
2
1
0
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
–6
–8
5V, 85°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
4.5V, 25°C
5.5V, 25°C
–10
–12
–14
–16
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
–20 –16 –12
–8
–4
0
4
8
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
LO INPUT POWER (dBm)
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
5568 G15
5568 G13
5568 G14
RF CW Output Power, HD2 and HD3 vs
Output IP3 vs LO Power
CW Baseband Voltage and Temperature
–10
–20
–30
–40
–50
–60
–70
–80
10
25
23
21
19
17
15
13
0
RF
–40°C
85°C
–40°C
85°C
25°C
–10
–20
–30
–40
–50
–60
25°C
25°C
HD3
–40°C
HD2
5V, –40°C
5V, 25°C
85°C
5V, 85°C
f
f
= 2MHz
= 2.1MHz
4.5V, 25°C
5.5V, 25°C
BB, 1
BB, 2
0
1
2
3
4
5
–20 –16 –12
–8
–4
0
4
8
I AND Q BASEBAND VOLTAGE (V
)
P–P, DIFF
LO INPUT POWER (dBm)
5568 G16
HD2 = MAX POWER AT f + 2 • f OR f – 2 • f
LO
BB
LO
BB
BB
HD3 = MAX POWER AT f + 3 • f OR f – 3 • f
5568 G17
LO
BB
LO
5568f
5
LT5568
U W
VCC = 5V, EN = High, TA = 25°C, fLO = 850MHz,
LO = 0dBm. BBPI, BBMI, BBPQ, BBMQ inputs 0.54VDC, Baseband Input Frequency fBB = 2MHz, I&Q 90° shifted. fRF = fBB + fLO (upper
TYPICAL PERFOR A CE CHARACTERISTICS
P
sideband selection). PRF, OUT = –10dBm (–10dBm/tone for 2-tone measurements), unless otherwise noted. (Note 3)
RF CW Output Power, HD2 and
LO Feedthrough to RF Output
vs CW Baseband Voltage
Image Rejection
HD3 vs CW Baseband Voltage
and Supply Voltage
vs CW Baseband Voltage
–10
–20
–30
–40
–50
–60
–70
–80
10
0
–36
–38
–40
–42
–44
–35
–40
–45
–50
–55
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
RF
5V, 85°C
5V, 85°C
5V
4.5V
4.5V, 25°C
5.5V, 25°C
4.5V, 25°C
5.5V, 25°C
–10
–20
–30
–40
–50
–60
HD3
5V
4.5V
HD2
5.5V
0
1
2
3
4
5
)
0
1
2
3
4
5
)
0
1
2
3
4
5
)
I AND Q BASEBAND VOLTAGE (V
P–P, DIFF
I AND Q BASEBAND VOLTAGE (V
I AND Q BASEBAND VOLTAGE (V
P–P, DIFF
P–P, DIFF
5568 G19
HD2 = MAX POWER AT f + 2 • f OR f – 2 • f
5568 G20
LO
BB
LO
BB
BB
HD3 = MAX POWER AT f + 3 • f OR f – 3 • f
LO
BB
LO
5568 G18
RF Two-Tone Power (Each Tone),
IM2 and IM3 vs Baseband Voltage
and Supply Voltage
RF Two-Tone Power (Each Tone),
IM2 and IM3 vs Baseband Voltage
and Temperature
Gain Distribution
10
0
10
0
60
50
40
30
20
10
0
–40°C
25°C
85°C
RF
RF
–40°C
25°C
85°C
4.5V
–10
–20
–30
–40
–50
–60
–70
–80
–10
–20
–30
–40
–50
–60
–70
–80
4.5V
5V, 5.5V
–40°C
5V, 5.5V
25°C
85°C
25°C
IM3
5V
IM3
4.5V
–40°C
IM2
5.5V
IM2
85°C
f
f
= 2MHz, 2.1MHz, 0°
= 2MHz, 2.1MHz, 90°
f
f
= 2MHz, 2.1MHz, 0°
= 2MHz, 2.1MHz, 90°
BBI
BBQ
BBI
BBQ
0.1
1
10
0.1
1
10
)
–8
–7
–6.5
–6
–7.5
I AND Q BASEBAND VOLTAGE (V
)
I AND Q BASEBAND VOLTAGE (V
P–P, DIFF, EACH TONE
P–P, DIFF, EACH TONE
GAIN (dB)
5568 G23
IM2 = POWER AT f + 4.1MHz
IM2 = POWER AT f + 4.1MHz
LO
LO
IM3 = MAX POWER AT f + 1.9MHz OR f + 2.2MHz
IM3 = MAX POWER AT f + 1.9MHz OR f + 2.2MHz
LO
LO
LO
LO
Noise Floor Distribution
LO Leakage Distribution
Image Rejection Distribution
60
50
40
30
20
10
0
40
30
20
10
0
50
40
30
20
10
0
f
= 870MHz
–40°C
25°C
85°C
P
= –10dBm
LO
–40°C
25°C
85°C
–40°C
25°C
85°C
V = 800mV
BB P-P,DIFF
NOISE
NO BASEBAND
APPLIED
–160.8
–160
–159.6
–159.2
–54
–46
–42
–38
–34
–160.4
–50
< –60
–52
–48
–44
–56
NOISE FLOOR (dBm/Hz)
LO LEAKAGE (dBm)
IMAGE REJECTION (dBc)
5568 G26
5568 G24
5568 G25
5568f
6
LT5568
U
U
U
PI FU CTIO S
BBPQ,BBMQ(Pins7,5):BasebandInputsfortheQ-chan-
nel, each 50Ω input impedance. Internally biased at about
0.54V. Applied voltage must stay below 2.5V.
EN (Pin 1): Enable Input. When the enable pin voltage is
higher than 1V, the IC is turned on. When the input voltage
is less than 0.5V, the IC is turned off.
V
(Pins 8, 13): Power Supply. Pins 8 and 13 are con-
GND (Pins 2, 4, 6, 9, 10, 12, 15): Ground. Pins 6, 9, 15
and 17 (exposed pad) are connected to each other inter-
nally. Pins 2 and 4 are connected to each other internally
and function as the ground return for the LO signal. Pins
10 and 12 are connected to each other internally and
function as the ground return for the on-chip RF balun.
For best RF performance, pins 2, 4, 6, 9, 10, 12, 15 and
the Exposed Pad 17 should be connected to the printed
circuit board ground plane.
CC
nected to each other internally. It is recommended to use
0.1μF capacitors for decoupling to ground on each of
these pins.
RF (Pin 11): RF Output. The RF output is an AC-coupled
single-ended output with approximately 50Ω output im-
pedance at RF frequencies. Externally applied DC voltage
should be within the range –0.5V to V + 0.5V in order
to avoid turning on ESD protection diodes.
CC
LO(Pin3):LOInput.TheLOinputisanAC-coupledsingle-
ended input with approximately 50Ω input impedance at
RF frequencies. Externally applied DC voltage should be
BBPI, BBMI (Pins 14, 16): Baseband Inputs for the
I-channel,eachwith50Ωinputimpedance.Internallybiased
at about 0.54V. Applied voltage must stay below 2.5V.
within the range –0.5V to V + 0.5V in order to avoid
CC
Exposed Pad (Pin 17): Ground. This pin must be soldered
to the printed circuit board ground plane.
turning on ESD protection diodes.
5568f
7
LT5568
W
BLOCK DIAGRA
V
CC
8
13
LT5568
BBPI 14
BBMI 16
V-I
V-I
11 RF
0°
90°
BALUN
BBPQ
BBMQ
7
5
1
EN
2
4
6
9
3
10
12
15
17
5568 BD
GND
LO
GND
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APPLICATIO S I FOR ATIO
The LT5568 consists of I and Q input differential voltage-
to-current converters, I and Q up-conversion mixers, an
RF output balun, an LO quadrature phase generator and
LO buffers.
External I and Q baseband signals are applied to the dif-
ferential baseband input pins, BBPI, BBMI, and BBPQ,
BBMQ.Thesevoltagesignalsareconvertedtocurrentsand
translated to RF frequency by means of double-balanced
up-converting mixers. The mixer outputs are combined
in an RF output balun, which also transforms the output
impedance to 50Ω. The center frequency of the resulting
RF signal is equal to the LO signal frequency. The LO input
drives a phase shifter which splits the LO signal into in-
phaseandquadratureLOsignals.TheseLOsignalsarethen
applied to on-chip buffers which drive the up-conversion
mixers. Both the LO input and RF output are single-ended,
50Ω-matched and AC coupled.
LT5568
RF
= 5V
C
V
CC
BALUN
FROM
Q
LOMI
CM
LOPI
R1A
25Ω
R1B
23Ω
R2B
23Ω
R2A
25Ω
BBPI
R3
R4
12pF
12pF
Baseband Interface
V
REF
= 540mV
BBMI
Thebasebandinputs(BBPI,BBMI),(BBPQ,BBMQ)present
adifferentialinputimpedanceofabout100Ω.Ateachofthe
fourbasebandinputs,afirst-orderlowpassfilterusing25Ω
5568 F01
GND
Figure 1. Simplified Circuit Schematic of the LT5568
(Only I-Half is Drawn)
5568f
8
LT5568
U
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APPLICATIO S I FOR ATIO
and 12pF to ground is incorporated (see Figure 1), which Thebasebandinputsshouldbedrivendifferentially;other-
limits the baseband bandwidth to approximately 330MHz wise, the even-order distortion products will degrade the
(–1dB point). The common mode voltage is about 0.54V overall linearity severely. Typically, a DAC will be the signal
and is approximately constant over temperature.
source for the LT5568. Reconstruction filters should be
placedbetweentheDACoutputandtheLT5568’sbaseband
inputs.InFigure3,anexampleinterfaceschematicshowsa
commonlyusedDACoutputinterfacefollowedbyapassive
Itisimportantthattheappliedcommonmodevoltagelevel
of the I and Q inputs is about 0.54V in order to properly
bias the LT5568. Some I/Q test generators allow setting
the common mode voltage independently. In this case, the
common mode voltage of those generators must be set
to 0.27V to match the LT5568 internal bias, because for
DC signals, there is no –6dB source-load voltage division
(see Figure 2).
th
5 order ladder filter. The DAC in this example sources
a current from 0mA to 20mA. The interface may be DC
coupled. This allows adjustment of the DAC’s differential
outputcurrenttominimizetheLOfeedthrough.Optionally,
transformer T1 can be inserted to improve the current
balance in the BBPI and BBMI pins. This will improve the
2nd order distortion performance (OIP2).
50Ω
50Ω
48Ω
The maximum single sideband CW RF output power at
850MHz using both I and Q channels with the configura-
tion shown in Figure 3 is about –3dBm. The maximum
CW output power can be increased by connecting load
resistors R5 and R6 to –5V instead of GND, and changing
their values to 550Ω. In that case, the maximum single
sideband CW RF output power at 850MHz will be about
+2dBm. In addition, the ladder filter component values
require adjustment for a higher source impedance.
0.27V
0.54V
DC
DC
+
+
+
DC
0.54V
0.54V
0.54V
DC
DC
–
–
–
50Ω
GENERATOR
GENERATOR
LT5568
5568 F02
Figure 2. DC Voltage Levels for a Generator Programmed at
0.27VDC for a 50Ω Load and the LT5568 as a Load
V
= 5V
CC
LT5568
LOPI
RF = –3dBm, MAX
BALUN
C
LOMI
CM
R1
R2
0.5V
L1A
L2A
45Ω
45Ω
BBPI
T1
1:1
0mA to 20mA
0mA to 20mA
R5, 50Ω
C1
R6, 50Ω
R3
33Ω
R4
33Ω
DAC
C2
L1B
C3
L2B
V
REF
= 500mV
15mA
GND
0.5V
BBMI
5568 F03
GND
Figure 3. LT5568 5th Order Filtered Baseband Interface with Common DAC (Only I-Channel is Shown)
5568f
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LT5568
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APPLICATIO S I FOR ATIO
Table 1. LO Port Input Impedance vs Frequency for EN = High
and PLO = 0dBm
LO Section
The internal LO input amplifier performs single-ended to
differential conversion of the LO input signal. Figure 4
shows the equivalent circuit schematic of the LO input.
Frequency
MHz
Input Impedance
S
11
Ω
Mag
Angle
95.0
500
600
47.5 + j12.1
59.4 + j8.4
0.126
0.115
0.140
0.185
0.232
0.252
0.258
0.297
37.8
V
CC
700
800
900
1000
1100
1200
66.2 – j1.14
67.2 – j13.4
61.1 – j23.9
53.3 – j26.8
48.2 – j26.1
42.0 – j27.4
–3.41
–31.7
–53.2
–68.7
–79.4
–90.0
20pF
LO
INPUT
51Ω
5568 F04
If the part is in shutdown mode, the input impedance of
the LO port will be different. The LO input impedance for
EN = Low is given in Table 2.
Table 2. LO Port Input Impedance vs Frequency for EN = Low and
PLO = 0dBm
Figure 4. Equivalent Circuit Schematic of the LO Input
Theinternal,differentialLOsignalisthensplitintoin-phase
and quadrature (90° phase shifted) signals that drive LO
buffer sections. These buffers drive the double balanced
I and Q mixers. The phase relationship between the LO
input and the internal in-phase LO and quadrature LO
signals is fixed, and is independent of start-up conditions.
The internal phase shifters are designed to deliver accu-
rate quadrature signals. For LO frequencies significantly
below 600MHz or above 1GHz, however, the quadrature
accuracy will diminish, causing the image rejection to
degrade. The LO pin input impedance is about 50Ω, and
the recommended LO input power is 0dBm. For lower
LO input power, the gain, OIP2, OIP3 and noise floor at
Frequency
MHz
Input Impedance
S
11
Ω
Mag
Angle
85.4
49.8
19.6
–6.8
–29.6
–45.5
–65.6
–79.7
500
600
700
800
900
1000
1100
1200
33.6 + j41.3
59.8 + j69.1
140 + j89.8
225 – j62.6
92.9 – j128
39.8 – j95.9
22.8 – j72.7
16.0 – j57.3
0.477
0.539
0.606
0.659
0.704
0.735
0.755
0.763
P
A
= 4dBm will degrade, especially below –5dBm and at
RF
RF Section
T = 85°C. For high LO input power (e.g., +5dBm), the LO
Afterup-conversion,theRFoutputsoftheIandQmixersare
combined. An on-chip balun performs internal differential
tosingle-endedoutputconversion,whiletransformingthe
output signal impedance to 50Ω. Table 3 shows the RF
port output impedance vs frequency.
feedthroughwillincreasewithnoimprovementinlinearity
or gain. For lower LO input power, e.g., P = –5dBm, the
LO
image rejection improves (especially around 950MHz) at
the cost of 1.5dB degradation of the noise floor at P
=
RF
4dBm.HarmonicspresentontheLOsignalcandegradethe
imagerejectionbecausetheycanintroduceasmallexcess
phase shift in the internal phase splitter. For the second (at
1.7GHz) and third harmonics (at 2.55GHz) at –20dBc, the
resulting signal at the image frequency is about –56dBc
or lower, corresponding to an excess phase shift of much
less than 1 degree. For the second and third LO harmonics
at –10dBc, the introduced signal at the image frequency is
about –47dBc. Higher harmonics than the third will have
less impact. The LO return loss typically will be better than
11dB over the 700MHz to 1.05GHz range. Table 1 shows
the LO port input impedance vs frequency.
Table 3. RF Port Output Impedance vs Frequency for EN = High
and PLO = 0dBm
Frequency
MHz
Input Impedance
S
22
Ω
Mag
Angle
164.2
141.3
117.5
90.6
–94.7
–117.0
–130.7
–141.6
500
600
700
800
900
1000
1100
1200
22.0 + j5.7
28.2 + j12.5
38.8 + j14.8
49.4 + j7.2
49.3 – j5.1
42.5 – j11.1
36.7 – j11.7
33.0 – j10.3
0.395
0.317
0.206
0.072
0.051
0.143
0.202
0.238
5568f
10
LT5568
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APPLICATIO S I FOR ATIO
The RF output S with no LO power applied is given in Note that an ESD diode is connected internally from
22
Table 4.
the RF output to ground. For strong output RF signal
levels (higher than 3dBm), this ESD diode can degrade
the linearity performance if the 50Ω termination imped-
ance is connected directly to ground. To prevent this, a
coupling capacitor can be inserted in the RF output line.
This is strongly recommended during a 1dB compression
measurement.
Table 4. RF Port Output Impedance vs Frequency for EN = High
and No LO Power Applied
Frequency
MHz
Input Impedance
S
22
Ω
Mag
Angle
164.0
500
600
22.7 + j5.6
29.7 + j11.6
40.5 + j11.6
47.3 + j2.2
44.1 – j6.7
38.2 – j9.8
34.0 – j9.4
31.5 – j7.8
0.381
0.290
0.164
0.037
0.094
0.171
0.218
0.245
142.0
700
121.9
800
139.6
Enable Interface
900
–126.9
–133.9
–143.1
–151.6
Figure 6 shows a simplified schematic of the EN pin in-
terface. The voltage necessary to turn on the LT5568 is
1V. To disable (shut down) the chip, the enable voltage
must be below 0.5V. If the EN pin is not connected, the
chip is disabled. This EN = Low condition is assured by
the 75k on-chip pull-down resistor. It is important that
1000
1100
1200
For EN = Low the S is given in Table 5.
22
Table 5. RF Port Output Impedance vs Frequency for EN = Low
the voltage at the EN pin does not exceed V by more
CC
Frequency
MHz
Input Impedance
S
22
than 0.5V. If this should occur, the supply current could
be sourced through the EN pin ESD protection diodes,
which are not designed to carry the full supply current,
and damage may result.
Ω
Mag
Angle
164.9
142.5
118.1
87.4
500
600
21.2 + j5.4
26.6 + j12.5
36.6 + j16.6
49.2 + j11.6
52.9 – j2.0
46.4 – j11.2
39.3 – j13.2
34.4 – j12.1
0.409
0.340
0.241
0.116
0.034
0.121
0.188
0.231
700
800
900
–33.1
–101.1
–120.6
–133.8
1000
1100
1200
V
CC
V
CC
EN
75k
25k
21pF
RF
OUTPUT
7nH
1pF
51Ω
5568 F06
5568 F05
Figure 6. EN Pin Interface
Figure 5. Equivalent Circuit Schematic of the RF Output
5568f
11
LT5568
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APPLICATIO S I FOR ATIO
Evaluation Board
R1 (optional) limits the EN pin current in the event that
the EN pin is pulled high while the V inputs are low. In
CC
Figure 7 shows the evaluation board schematic. A good
ground connection is required for the exposed pad. If this
is not done properly, the RF performance will degrade. Ad-
ditionally,theexposedpadprovidesheatsinkingforthepart
and minimizes the possibility of the chip overheating.
Figures 8 and 9 the silk screens and the PCB board layout
are shown.
J1
J2
BBIM
BBIP
V
CC
C2
16
BBMI GND BBPI
EN
15
14
13
100nF
R1
V
CC
100Ω
1
2
3
4
12
GND
RF
V
EN
CC
J3
11
10
9
RF
OUT
GND
LO
J4
LO
IN
LT5568
GND
GND
GND
GND
17
BBMQ GND BBPQ
V
CC
5
6
7
8
C1
100nF
J5
J6
BBQM
GND
BBQP
BOARD NUMBER: DC966A
5568 F07
Figure 7. Evaluation Circuit Schematic
Figure 8. Component Side of Evaluation Board
Figure 9. Bottom Side of Evaluation Board
5568f
12
LT5568
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APPLICATIO S I FOR ATIO
Application Measurements
ment. See Application Note 99. Consult the factory for
advice on the ACPR measurement, if needed.
TheLT5568isrecommendedforbase-stationapplications
usingvariousmodulationformats. Figure10showsatypi-
cal application. Figure 11 shows the ACPR performance
for CDMA2000 using 1- and 3-carrier modulation. Figures
12 and 13 illustrate the 1- and 3-carrier CDMA2000 RF
spectrum. To calculate ACPR, a correction is made for the
spectrum analyzer noise floor. If the output power is high,
theACPRwillbelimitedbythelinearityperformanceofthe
part. If the output power is low, the ACPR will be limited
by the noise performance of the part. In the middle, an
optimum ACPR is observed.
TheACPRperformanceissensitivetotheamplitudematch
of the BBIP and BBIM (or BBQP and BBQM) inputs. This
is because a difference in AC current amplitude will give
rise to a difference in amplitude between the even-order
harmonic products generated in the internal V-I converter.
As a result, they will not cancel out entirely. Therefore, it
is important to keep the currents in those pins exactly the
same (but of opposite sign). The current will enter the
LT5568’s common-base stage, and will flow to the mixer
upper switches. This can be seen in Figure 1 where the
internal circuit of the LT5568 is drawn. For best results,
a high ohmic source is recommended; for example, the
Because of the LT5568’s very high dynamic range, the test
equipment can limit the accuracy of the ACPR measure-
–50
–60
–70
–80
–90
–125
–135
–145
–155
5V
100nF
DOWNLINK TEST MODEL 64 DPCH
3-CH. ACPR
V
CC 8, 13
1-CH.
ACPR
L5568
14
16
x2
RF = 700MHz
TO 1050MHz
I-DAC
V-I
I-CHANNEL
11
PA
0°
1
EN
90°
BALUN
3-CH. AltCPR
1-CH. AltCPR
1-CH. NOISE
Q-CHANNEL
V-I
7
5
Q-DAC
3-CH. NOISE
BASEBAND
GENERATOR
5568 F10
3
VCO/SYNTHESIZER
2, 4, 6, 9, 10, 12, 15, 17
–165
–30
–25
–20
–15
–10
–5
RF OUTPUT POWER PER CARRIER (dBm)
5568 F11
Figure 10. 700MHz to 1050MHz Direct
Conversion Transmitter Application
Figure 11. APCR, AltCPR and Noise
CDMA2000 Modulation
–30
–30
–40
DOWNLINK TEST
DOWNLINK
TEST
MODEL 64
DPCH
–40
–50
–60
–70
–80
–90
MODEL 64 DPCH
–50
–60
–70
–80
UNCORRECTED
SPECTRUM
–90
UNCORRECTED
SPECTRUM
CORRECTED
SPECTRUM
–100
–110
–120
–130
–100
–110
–120
–130
CORRECTED
SPECTRUM
SPECTRUM ANALYSER
NOISE FLOOR
SPECTRUM ANALYSER NOISE FLOOR
846.25 847.75 849.25 850.75 852.25 853.75
844
846
848
850
852
852
856
RF FREQUENCY (MHz)
RF FREQUENCY (MHz)
5568 F13
5568 F12
Figure 12. 1-Carrier CDMA2000 Spectrum
Figure 13. 3-Carrier CDMA2000 Spectrum
5568f
13
LT5568
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APPLICATIO S I FOR ATIO
interface circuit drawn in Figure 3, modified by pulling match.Thesecondarycentertapshouldnotbeconnected,
resistors R5 and R6 to a –5V supply and adjusting their
whichallowssomevoltageswingifthereisasingle-ended
input impedance difference at the baseband pins. As a
result,bothcurrentswillbeequal.Thedisadvantageisthat
there is no DC coupling, so the LO feedthrough calibration
cannotbeperformedviatheBBconnections. Aftercalibra-
tion when the temperature changes, the LO feedthrough
and the image rejection performance will change. This is
illustrated in Figure 14. The LO feedthrough and image
rejection can also change as a function of the baseband
drive level, as is depicted in Figure 15. In Figures 16 and
17 the LO feedthrough and image rejection vs LO power
are shown.
values to 550Ω, with T1 omitted.
Another method to reduce current mismatch between
the currents flowing in the BBIP and BBIM pins (or the
BBQP and BBQM pins) is to use a 1:1 transformer with
the two windings in the DC path (T1 in Figure 3). For DC,
the transformer forms a short, and for AC, the transformer
will reduce the common mode current component, which
forcesthetwocurrentstobebettermatched. Alternatively,
atransformerwith1:2impedanceratiocanbeused, which
gives a convenient DC separation between primary and
secondary in combination with the required impedance
–40
10
CALIBRATED WITH P = –10dBm
RF
–40°C
85°C
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
P
RF
25°C
IMAGE REJECTION
–50
–60
–70
–80
–90
LOFT
IR
LO FEED-
THROUGH
–40°C
–40°C
85°C
85°C
= 5V
EN = High
= 850MHz
V
f
f
f
= 5V
CC
V
f
f
f
= 2MHz, 0°
CC
BB, 1
BB, 0
f
= f + f
LO
= 2MHz, 0°
BBQ
= 850MHz
RF BB LO
= 2MHz, 90°
BBI
P
= 0dBm
= 2MHz, 90°+ϕ
f
= f + f
LO
RF BB LO
EN = High
40
60
TEMPERATURE (°C)
P
LO
25°C
LO = 0dBm
–40 –20
0
20
80
0
1
2
3
4
5
I AND Q BASEBAND VOLTAGE (V
)
5568 F14
P-P, DIFF
5568 F15
Figure 14. LO Feedthrough and Image Rejection
vs Temperature after Calibration at 25°C
Figure 15. LO Feedthrough and Image Rejection
vs Baseband Drive Voltage after Calibration at 25°C
–42
–25
f
LO
= 850MHz
f
= 850MHz
= –10dBm
LO
RF
P
–30
–35
–40
–45
–50
–55
–44
–46
–48
–50
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
4.5V, 25°C
5.5V, 25°C
–20 –16 –12 –8
–4
0
4
8
–20 –16 –12 –8
–4
0
4
8
LO INPUT POWER (dBm)
LO INPUT POWER (dBm)
5568 G16
5568 G17
Figure 16. LO Feedthrough vs LO Power
Figure 17. Image Rejection vs LO Power
5568f
14
LT5568
U
PACKAGE DESCRIPTIO
UF Package
16-Lead Plastic QFN (4mm × 4mm)
(Reference LTC DWG # 05-08-1692)
0.72 0.05
4.35 0.05
2.90 0.05
2.15 0.05
(4 SIDES)
PACKAGE OUTLINE
0.30 0.05
0.65 BSC
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
BOTTOM VIEW—EXPOSED PAD
PIN 1 NOTCH R = 0.20 TYP
OR 0.35 × 45° CHAMFER
0.75 0.05
R = 0.115
TYP
4.00 0.10
(4 SIDES)
15
16
0.55 0.20
PIN 1
TOP MARK
(NOTE 6)
1
2
2.15 0.10
(4-SIDES)
(UF16) QFN 10-04
0.200 REF
0.30 0.05
0.65 BSC
0.00 – 0.05
NOTE:
1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGC)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON THE TOP AND BOTTOM OF PACKAGE
5568f
InformationfurnishedbyLinearTechnologyCorporationisbelievedtobeaccurateandreliable.However,
no responsibility is assumed for its use. Linear Technology Corporation makes no representation that
the interconnection of its circuits as described herein will not infringe on existing patent rights.
15
LT5568
RELATED PARTS
PART NUMBER
Infrastructure
LT5511
DESCRIPTION
COMMENTS
High Linearity Upconverting Mixer
RF Output to 3GHz, 17dBm IIP3, Integrated LO Buffer
LT5512
DC to 3GHz High Signal Level Downconverting DC to 3GHz, 17dBm IIP3, Integrated LO Buffer
Mixer
LT5514
LT5515
LT5516
Ultralow Distortion, IF Amplifier/ADC Driver
with Digitally Controlled Gain
850MHz Bandwidth, 47dBm OIP3 at 100MHz, 10.5dB to 33dB Gain Control Range
1.5GHz to 2.5GHz Direct Conversion Quadrature 20dBm IIP3, Integrated LO Quadrature Generator
Demodulator
0.8GHz to 1.5GHz Direct Conversion Quadrature 21.5dBm IIP3, Integrated LO Quadrature Generator
Demodulator
LT5517
LT5518
40MHz to 900MHz Quadrature Demodulator
21dBm IIP3, Integrated LO Quadrature Generator
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
22.8dBm OIP3 at 2GHz, –158.2dBm/Hz Noise Floor, 50Ω Single-Ended LO and RF
Ports, 4-Ch W-CDMA ACPR = –64dBc at 2.14GHz
LT5519
LT5520
LT5521
LT5522
LT5524
LT5526
LT5527
LT5528
0.7GHz to 1.4GHz High Linearity Upconverting 17.1dBm IIP3 at 1GHz, Integrated RF Output Transformer with 50Ω Matching,
Mixer Single-Ended LO and RF Ports Operation
1.3GHz to 2.3GHz High Linearity Upconverting 15.9dBm IIP3 at 1.9GHz, Integrated RF Output Transformer with 50Ω Matching,
Mixer
Single-Ended LO and RF Ports Operation
10MHz to 3700MHz High Linearity
Upconverting Mixer
24.2dBm IIP3 at 1.95GHz, NF = 12.5dB, 3.15V to 5.25V Supply, Single-Ended LO
Port Operation
600MHz to 2.7GHz High Signal Level
Downconverting Mixer
4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended RF
and LO Ports
Low Power, Low Distortion ADC Driver with
Digitally Programmable Gain
450MHz Bandwidth, 40dBm OIP3, 4.5dB to 27dB Gain Control
High Linearity, Low Power Downconverting
Mixer
3V to 5.3V Supply, 16.5dBm IIP3, 100kHz to 2GHz RF, NF = 11dB, I = 28mA,
CC
–65dBm LO-RF Leakage
400MHz to 3.7GHz High Signal Level
Downconverting Mixer
IIP3 = 23.5dBm and NF = 12.5dB at 1900MHz, 4.5V to 5.25V Supply, I = 78mA
CC
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
21.8dBm OIP3 at 2GHz, –159.3dBm/Hz Noise Floor, 50Ω, 0.5V Baseband Interface,
DC
4-Ch W-CDMA ACPR = –66dBc at 2.14GHz
RF Power Detectors
LTC®5505
RF Power Detectors with >40dB Dynamic
Range
300MHz to 3GHz, Temperature Compensated, 2.7V to 6V Supply
LTC5507
LTC5508
LTC5509
LTC5532
LT5534
100kHz to 1000MHz RF Power Detector
300MHz to 7GHz RF Power Detector
300MHz to 3GHz RF Power Detector
100kHz to 1GHz, Temperature Compensated, 2.7V to 6V Supply
44dB Dynamic Range, Temperature Compensated, SC70 Package
36dB Dynamic Range, Low Power Consumption, SC70 Package
300MHz to 7GHz Precision RF Power Detector Precision V
Offset Control, Adjustable Gain and Offset
OUT
50MHz to 3GHz Loq RF Power Detector with
60dB Dynamic Range
1dB Output Variation over Temperature, 38ns Response Time
LTC5536
Precision 600MHz to 7GHz RF Detector with
Fast Comparater
25ns Response Time, Comparator Reference Input, Latch Enable Input, –26dBm to
+12dBm Input Range
LT5537
Wide Dynamic Range Loq RF/IF Detector
Low Frequency to 800MHz, 83dB Dynamic Range, 2.7V to 5.25V Supply
High Speed ADCs
LTC2220-1
12-Bit, 185Msps ADC
Single 3.3V Supply, 910mW Consumption, 67.5dB SNR, 80dB SFDR, 775MHz Full
Power BW
LTC2249
LTC2255
14-Bit, 80Msps ADC
14-Bit, 125Msps ADC
Single 3V Supply, 222mW Consumption, 73dB SNR, 90dB SFDR
Single 3V Supply, 395mW Consumption, 72.4dB SNR, 88dB SFDR, 640MHz Full
Power BW
5568f
LT/TP 1005 500 • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
16
●
●
© LINEAR TECHNOLOGY CORPORATION 2005
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
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