LT5571EUF [Linear]
620MHz - 1100MHz High Linearity Direct Quadrature Modulator; 了620MHz - 1100MHz高线性度直接正交调制器型号: | LT5571EUF |
厂家: | Linear |
描述: | 620MHz - 1100MHz High Linearity Direct Quadrature Modulator |
文件: | 总16页 (文件大小:316K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LT5571
620MHz – 1100MHz High
Linearity Direct Quadrature
Modulator
FEATURES
DESCRIPTION
The LT®5571 is a direct I/Q modulator designed for high
performance wireless applications, including wireless
infrastructure. It allows direct modulation of an RF signal
using differential baseband I and Q signals. It supports
RFID,GSM,EDGE,CDMA,CDMA2000,andothersystems.
It may also be configured as an image reject upconvert-
ing mixer by applying 90° phase-shifted signals to the I
and Q inputs. The high impedance I/Q baseband inputs
consist of voltage-to-current converters that in turn drive
double-balanced mixers. The outputs of these mixers are
summed and applied to an on-chip RF transformer, which
converts the differential mixer signals to a 50Ω single-
ended output. The four balanced I and Q baseband input
ports are intended for DC-coupling from a source with a
common-modevoltageatabout0.5V.TheLOpathconsists
of an LO buffer with single-ended input, and precision
quadrature generators that produce the LO drive for the
mixers. The supply voltage range is 4.5V to 5.25V.
■
Direct Conversion from Baseband to RF
■
High Output: –4.2dB Conversion Gain
■
High OIP3: 21.7dBm at 900MHz
■
Low Output Noise Floor at 20MHz Offset:
No RF: –159dBm/Hz
P
OUT
= 4dBm: –153.3dBm/Hz
■
■
■
■
Low Carrier Leakage: –42dBm at 900MHz
High Image Rejection: –53dBc at 900MHz
3-Ch CDMA2000 ACPR: –70.4dBc at 900MHz
Integrated LO Buffer and LO Quadrature Phase
Generator
■
■
50Ω AC-Coupled Single-Ended LO and RF Ports
High Impedance DC Interface to Baseband Inputs
with 0.5V Common Mode Voltage
■
16-Lead QFN 4mm × 4mm Package
APPLICATIONS
■
, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.
All other trademarks are the property of their respective owners.
RFID Interrogators
■
GSM, CDMA, CDMA2000 Transmitters
■
Point-to-Point Wireless Infrastructure Tx
■
Image Reject Up-Converters for Cellular Bands
■
Low-Noise Variable Phase-Shifter for 620MHz to
1100MHz Local Oscillator Signals
TYPICAL APPLICATION
CDMA2000 ACPR, AltCPR and Noise vs RF
Output Power at 900MHz for 1 and 3 Carriers
Direct Conversion Transmitter Application
–40
–50
–60
–70
–80
–90
–110
–120
–130
–140
–150
–160
5V
DOWNLINK TEST
MODEL 64 DPCH
100nF
V
LT5571
×2
CC
RF = 620MHz
TO 1100MHz
I-DAC
3-CH ACPR
V-I
I-CH
1-CH
3-CH AltCPR
PA
ACPR
0°
EN
90°
BALUN
Q-CH
V-I
1-CH NOISE
Q-DAC
1-CH AltCPR
3-CH NOISE
BASEBAND
GENERATOR
5571 TA01a
–30
–25
–20
–15
–10
–5
0
VCO/SYNTHESIZER
RF OUTPUT POWER PER CARRIER (dBm)
5571 TA01b
5571f
1
LT5571
ABSOLUTE MAXIMUM RATINGS
PACKAGE/ORDER INFORMATION
(Note 1)
TOP VIEW
Supply Voltage.........................................................5.5V
Common-Mode Level of BBPI, BBMI and
BBPQ, BBMQ .......................................................0.6V
Operating Ambient Temperature
16 15 14 13
EN
GND
LO
1
2
3
4
12 GND
11 RF
17
(Note 2) ............................................... –40°C to 85°C
Storage Temperature Range................... –65°C to 125°C
Voltage on any Pin
GND
GND
10
9
GND
5
6
7
8
Not to Exceed...................... –500mV to V + 500mV
CC
UF PACKAGE
16-LEAD (4mm × 4mm) PLASTIC QFN
= 125°C, θ = 37°C/W
Note: The baseband input pins should not be left floating.
T
JMAX
JA
EXPOSED PAD (PIN 17) IS GND, MUST BE SOLDERED TO PCB
ORDER PART NUMBER
LT5571EUF
UF PART MARKING
5571
Order Options Tape and Reel: Add #TR
Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF
Lead Free Part Marking: http://www.linear.com/leadfree/
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
V
= 5V, EN = High, T = 25°C, f = 900MHz, f = 902MHz,
DC
CC
A
LO
RF
P
LO
= 0dBm. BBPI, BBMI, BBPQ, BBMQ CM input voltage = 0.5V , Baseband Input Frequency = 2MHz, I & Q 90° shifted (upper
sideband selection). P
= –10dBm, unless otherwise noted. (Note 3)
RF(OUT)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
RF Output (RF)
f
RF
RF Frequency Range
RF Frequency Range
–3dB Bandwidth
–1dB Bandwidth
0.62 to 1.1
0.65 to 1.04
GHz
GHz
S
S
RF Output Return Loss
RF Output Return Loss
RF Output Noise Floor
EN = High (Note 6)
EN = Low (Note 6)
12.7
11.6
dB
dB
22, ON
22, OFF
NFloor
No Input Signal (Note 8)
–159
–153.3
–152.9
dBm/Hz
dBm/Hz
dBm/Hz
P
P
= 4dBm (Note 9)
= 4dBm (Note 10)
OUT
OUT
G
Conversion Voltage Gain
Absolute Output Power
20 • Log (V
/V )
–4.2
–0.2
–25.5
8.1
dB
dBm
dB
V
OUT, 50Ω IN, DIFF, I or Q
P
1V
P-P DIFF
CW Signal, I and Q
OUT
G
3 • LO Conversion Gain Difference
Output 1dB Compression
Output 2nd Order Intercept
Output 3rd Order Intercept
Image Rejection
(Note 17)
(Note 7)
3LO vs LO
OP1dB
OIP2
OIP3
IR
dBm
dBm
dBm
dBc
(Notes 13, 14)
(Notes 13, 15)
(Note 16)
63.8
21.7
–53
LOFT
Carrier Leakage (LO Feedthrough)
EN = High, P = 0dBm (Note 16)
–42
–61
dBm
dBm
LO
EN = Low, P = 0dBm (Note 16)
LO
5571f
2
LT5571
ELECTRICAL CHARACTERISTICS
V
= 5V, EN = High, T = 25°C, f = 900MHz, f = 902MHz,
CC A LO RF
P
= 0dBm. BBPI, BBMI, BBPQ, BBMQ CM input voltage = 0.5V , Baseband Input Frequency = 2MHz, I & Q 90° shifted (upper
LO
DC
sideband selection). P
= –10dBm, unless otherwise noted. (Note 3)
RF(OUT)
LO Input (LO)
f
LO Frequency Range
0.5 to 1.2
0
GHz
dBm
dB
LO
P
S
S
LO Input Power
–10
5
LO
LO Input Return Loss
EN = High (Note 6)
EN = Low (Note 6)
at 900MHz (Note 5)
at 900MHz (Note 5)
at 900MHz (Note 5)
–10.9
–2.6
11, ON
11, OFF
LO Input Return Loss
dB
NF
LO Input Referred Noise Figure
LO to RF Small Signal Gain
LO Input 3rd Order Intercept
14.3
dB
LO
G
18.5
dB
LO
IIP3
–4.8
dBm
LO
Baseband Inputs (BBPI, BBMI, BBPQ, BBMQ)
BW
Baseband Bandwidth
–3dB Bandwidth
400
0.5
MHz
V
BB
V
CMBB
DC Common-Mode Voltage
Differential Input Resistance
Baseband Static Input Current
Carrier Feedthrough on BB
Input 1dB Compression Point
I/Q Absolute Gain Imbalance
I/Q Absolute Phase Imbalance
Externally Applied (Note 4)
0.6
R
IN
90
kΩ
µA
I
(Note 4)
–24
–42
2.9
DC, IN
P
No Baseband Signal (Note 4)
Differential Peak-to-Peak (Note 7)
dBm
LO-BB
IP1dB
V
P-P,DIFF
ΔG
0.013
0.24
dB
I/Q
I/Q
Δϕ
Deg
Power Supply (V
)
CC
V
Supply Voltage
4.5
5
5.25
120
100
V
mA
µA
µs
CC
I
I
t
t
Supply Current
EN = High
97
CC(ON)
CC(OFF)
ON
Supply Current, Shutdown Mode
Turn-On Time
EN = 0V
EN = Low to High (Note 11)
EN = High to Low (Note 12)
0.4
1.4
Turn-Off Time
µs
OFF
Enable (EN), Low = Off, High = On
Enable
Input High Voltage
Input High Current
EN = High
EN = 5V
1
V
µA
230
Shutdown
Input Low Voltage
EN = Low
0.5
V
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: Specifications over the –40°C to 85°C temperature range are
assured by design, characterization and correlation with statistical process
controls.
Note 9: At 20MHz offset from the CW signal frequency.
Note 10: At 5MHz offset from the CW signal frequency.
Note 11: RF power is within 10% of final value.
Note 12: RF power is at least 30dB lower than in the ON state.
Note 13: Baseband is driven by 2MHz and 2.1MHz tones. Drive level is set
in such a way that the two resulting RF tones are –10dBm each.
Note 14: IM2 measured at LO frequency + 4.1MHz
Note 15: IM3 measured at LO frequency + 1.9MHz and LO frequency +
2.2MHz.
Note 16: Amplitude average of the characterization data set without image
or LO feed-through nulling (unadjusted).
Note 17: The difference in conversion gain between the spurious signal at
f = 3 • LO – BB versus the conversion gain at the desired signal at f = LO +
BB for BB = 2MHz and LO = 900MHz.
Note 3: Tests are performed as shown in the configuration of Figure 7.
Note 4: At each of the four baseband inputs BBPI, BBMI, BBPQ and BBMQ.
Note 5: V(BBPI) – V(BBMI) = 1V , V(BBPQ) – V(BBMQ) = 1V
.
DC
DC
Note 6: Maximum value within –1dB bandwidth.
Note 7: An external coupling capacitor is used in the RF output line.
Note 8: At 20MHz offset from the LO signal frequency.
5571f
3
LT5571
TYPICAL PERFORMANCE CHARACTERISTICS
V
= 5V, EN = High, T = 25°C, f = 900MHz,
CC A LO
f
RF
= 902MHz, P = 0dBm. BBPI, BBMI, BBPQ, BBMQ CM input voltage = 0.5V , Baseband Input Frequency f = 2MHz, I & Q 90°
LO DC BB
shifted, without image or LO feedthrough nulling. f = f + f (upper sideband selection). P
= –10dBm (–10dBm/tone for 2-
RF
BB
LO
RF(OUT)
tone measurements), unless otherwise noted. (Note 3)
RF Output Power vs LO Frequency
at 1V Differential Baseband
P-P
Supply Current vs Supply Voltage
Voltage Gain vs LO Frequency
Drive
–2
–4
110
100
90
2
0
85°C
25°C
–6
–2
–8
–10
–12
–14
–4
–6
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
–8
–40°C
–10
–16
–12
80
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
4.50
4.75
5.00
5.25
SUPPLY VOLTAGE (V)
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
5558 G03
5571 G02
5571 G01
Output 1dB Compression vs
LO Frequency
Output IP3 vs LO Frequency
Output IP2 vs LO Frequency
26
24
75
70
65
60
55
50
45
10
f
f
= 2MHz
= 2.1MHz
f
f
f
= f
,
+ f
,
+ f
LO
BB, 1
BB, 2
IM2 BB
BB
BB
1
BB
2
,
,
= 2MHz
1
2
= 2.1MHz
8
6
22
20
18
16
14
4
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
2
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
0
12
–2
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
5571 G04
5571 G05
5571 G06
LO Feedthrough to RF Output vs
LO Frequency
2 • LO Leakage to RF Output vs
2 • LO Frequency
3 • LO Leakage to RF Output vs
3 • LO Frequency
–40
–40
–45
5V, –40°C
5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
–50
–55
–60
–65
–70
–42
–44
–46
–48
–45
–50
–55
–60
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
550 650 750 850 950 1050 1150 1250
1.65 1.95 2.25 2.55 2.85 3.15 3.5 3.75
1.1 1.3 1.5 1.7 1.9 2.1 2.3 2.5
2 • LO FREQUENCY (GHz)
LO FREQUENCY (MHz)
3 • LO FREQUENCY (GHz)
5571 G07
5571 G09
5571 G08
5571f
4
LT5571
TYPICAL PERFORMANCE CHARACTERISTICS
V
= 5V, EN = High, T = 25°C, f = 900MHz,
CC A LO
f
RF
= 902MHz, P = 0dBm. BBPI, BBMI, BBPQ, BBMQ CM input voltage = 0.5V , Baseband Input Frequency f = 2MHz, I & Q 90°
LO DC BB
shifted, without image or LO feedthrough nulling. f = f + f (upper sideband selection). P
= –10dBm (–10dBm/tone for 2-
RF
BB
LO
RF(OUT)
tone measurements), unless otherwise noted. (Note 3)
LO and RF Port Return Loss vs
Frequency
Noise Floor vs RF Frequency
Image Rejection vs LO Frequency
–157
–158
–159
–160
–161
–162
–30
–35
–40
–45
–50
–55
0
–10
–20
–30
–40
f
= 900MHz (FIXED)
LO
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
NO BASEBAND SIGNAL
LO PORT, EN = LOW
LO PORT, EN = HIGH, P = 0dBm
LO
RF PORT,
EN = LOW
RF PORT,
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
EN = HIGH,
P
= 0dBm
LO
RF PORT,
EN = HIGH,
NO LO
LO PORT,
EN = HIGH,
P
= –10dBm
LO
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
FREQUENCY (MHz)
RF FREQUENCY (MHz)
LO FREQUENCY (MHz)
5571 G10
5571 G12
5571 G11
Absolute I/Q Gain Imbalance vs
LO Frequency
Absolute I/Q Phase Imbalance vs
LO Frequency
Voltage Gain vs LO Power
0.3
0.2
0.1
0
3
–2
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
–4
–6
2
1
0
–8
–10
–12
–14
–16
–18
–20
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
550 650 750 850 950 1050 1150 1250
550 650 750 850 950 1050 1150 1250
–20 –16 –12 –8
–4
0
4
8
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
LO INPUT POWER (dBm)
5571 G14
5571 G15
5571 G13
Output IP3 vs LO Power
LO Feedthrough vs LO Power
Image Rejection vs LO Power
24
–38
–35
–40
–45
–50
–55
–60
22
20
18
16
14
12
10
–40
–42
–44
–46
–48
–50
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
5V, –40°C
5V, 25°C
5V, 85°C
4.5V, 25°C
5.5V, 25°C
f
= 2MHz
BB, 1
f
= 2.1MHz
BB, 2
–20 –16 –12 –8
–4
0
4
8
–20 –16 –12 –8
–4
0
4
8
–20 –16 –12 –8
–4
0
4
8
LO INPUT POWER (dBm)
LO INPUT POWER (dBm)
LO INPUT POWER (dBm)
5571 G16
5571 G17
5571 G18
5571f
5
LT5571
TYPICAL PERFORMANCE CHARACTERISTICS
V
= 5V, EN = High, T = 25°C, f = 900MHz,
CC A LO
f
RF
= 902MHz, P = 0dBm. BBPI, BBMI, BBPQ, BBMQ CM input voltage = 0.5V , Baseband Input Frequency f = 2MHz, I & Q 90°
LO DC BB
shifted, without image or LO feedthrough nulling. f = f + f (upper sideband selection). P
= –10dBm (–10dBm/tone for 2-
RF
BB
LO
RF(OUT)
tone measurements), unless otherwise noted. (Note 3)
RF CW Output Power, HD2 and
HD3 vs CW Baseband Voltage and
Temperature
RF CW Output Power, HD2 and
HD3 vs CW Baseband Voltage and
Supply Voltage
LO Feedthrough to RF Output vs
CW Baseband Voltage
0
–10
–20
–30
–40
–50
–60
–70
–80
20
–10
–20
–30
–40
–50
–60
–70
–80
10
–30
–35
–40
–45
RF
5V, –40°C
5V, 25°C
RF
10
0
5V, 85°C
4.5V, 25°C
5.5V, 25°C
0
–10
–20
–30
–40
–50
–60
5V
HD3
5.5V
4.5V
25°C
85°C
–40°C
–10
–20
–30
–40
–50
–60
HD3
HD2
HD2
HD2 = MAX POWER AT
+ 2 • f OR f – 2 • f
HD2 = MAX POWER AT
f
f
+ 2 • f OR f – 2 • f
LO
BB
LO
BB
BB
LO BB LO
BB
BB
HD3 = MAX POWER AT
HD3 = MAX POWER AT
f
+ 3 • f OR f – 3 • f
f
LO
+ 3 • f OR f – 3 • f
LO
BB
LO
BB
LO
0
1
2
3
4
5
)
0
1
2
3
4
5
)
0
1
2
3
4
5
I AND Q BASEBAND VOLTAGE (V
I AND Q BASEBAND VOLTAGE (V
I AND Q BASEBAND VOLTAGE (V
)
P-P, DIFF
P-P, DIFF
P-P, DIFF
5571 G21
5571 G19
5571 G20
RF Two-Tone Power (Each Tone),
IM2 and IM3 vs Baseband Voltage
and Temperature
RF Two-Tone Power (Each Tone),
IM2 and IM3 vs Baseband Voltage
and Supply Voltage
Image Rejection vs CW Baseband
Voltage
–46
–48
–50
–52
–54
–56
–58
10
0
10
0
25°C
85°C
5V
5V, –40°C
5V, 25°C
5.5V
–40°C
4.5V
5V, 85°C
RF
RF
IM3
–10
–20
–30
–40
–50
–60
–70
–80
–10
–20
–30
–40
–50
–60
–70
–80
4.5V, 25°C
5.5V, 25°C
IM3
IM2 = POWER AT
IM2 = POWER AT
f
+ 4.1MHz
f
LO
+ 4.1MHz
LO
IM3 = MAX POWER
AT f + 1.9MHz
IM3 = MAX POWER
AT f + 1.9MHz
LO
LO
OR f + 2.2MHz
OR f + 2.2MHz
LO
LO
IM2
IM2
f
f
= 2MHz, 2.1MHz, 0°
= 2MHz, 2.1MHz, 90°
f
f
= 2MHz, 2.1MHz, 0°
= 2MHz, 2.1MHz, 90°
BBI
BBQ
BBI
BBQ
0
1
2
3
4
5
0.1
1
10
0.1
1
10
I AND Q BASEBAND VOLTAGE (V
)
I AND Q BASEBAND VOLTAGE (V
)
I AND Q BASEBAND VOLTAGE (V
)
P-P,DIFF
P-P,DIFF, EACH TONE
P-P,DIFF, EACH TONE
5571 G22
5571 G23
5571 G24
Voltage Gain Distribution
Noise Floor Distribution (no RF)
LO Leakage Distribution
25
20
15
10
5
25
20
15
10
5
20
10
0
–40°C
25°C
85°C
–40°C
25°C
85°C
–40°C
25°C
85°C
V
= 400mV
V
= 400mV
BB P-P
BB
P-P
0
0
–6.5 –6 –5.5 –5 –4.5 –4 –3.5 –3 –2.5 –2
–159.9 –159.6 –159.3 –159.0 –158.7
<–50 –48 –46 –44 –42 –40 –38 –36 –34
5571 G25
5571 G26
5571 G27
GAIN (dB)
NOISE FLOOR (dBm/Hz)
LO LEAKAGE (dBm)
5571f
6
LT5571
TYPICAL PERFORMANCE CHARACTERISTICS
V
= 5V, EN = High, T = 25°C, f = 900MHz,
CC A LO
f
RF
= 902MHz, P = 0dBm. BBPI, BBMI, BBPQ, BBMQ CM input voltage = 0.5V , Baseband Input Frequency f = 2MHz, I & Q 90°
LO DC BB
shifted, without image or LO feedthrough nulling. f = f + f (upper sideband selection). P
= –10dBm (–10dBm/tone for 2-
RF
BB
LO
RF(OUT)
tone measurements), unless otherwise noted. (Note 3)
LO Feedthrough and Image
Rejection vs Temperature After
Calibration at 25°C
Image Rejection Distribution
25
–40
–50
–60
–70
–80
–90
–40°C
25°C
85°C
V
= 400mV
P-P
CALIBRATED WITH P = 0dBm
RF
BB
f
f
= 2MHz, 0°
BBQ
BBI
= 2MHz, 90° + ϕ
CAL
20
15
10
5
LO FEEDTHROUGH
IMAGE REJECTION
0
<–60 –56 –52 –48 –44 –40 –36
–40
–20
0
20
40
60
80
5571 G28
IMAGE REJECTION (dBc)
TEMPERATURE (°C)
5571 G29
PIN FUNCTIONS
EN (Pin 1): Enable Input. When the Enable pin voltage is
higher than 1V, the IC is turned on. When the Enable volt-
age is less than 0.5V or if the pin is disconnected, the IC
is turned off. The voltage on the Enable pin should never
BBPQ,BBMQ(Pins7,5):BasebandinputsfortheQ-chan-
nel with about 90kΩ differential input impedance. These
pins should be externally biased at about 0.5V. Applied
common mode voltage must stay below 0.6V.
exceed V by more than 0.5V, in order to avoid possible
CC
V (Pins8,13):PowerSupply.Pins8and13areconnected
CC
damage to the chip.
toeachotherinternally.0.1µFcapacitorsarerecommended
GND (Pins 2, 4, 6, 9, 10, 12, 15, 17): Ground. Pins 6, 9,
15 and the Exposed Pad 17 are connected to each other
internally. Pins 2 and 4 are connected to each other inter-
nally and function as the ground return for the LO signal.
Pins 10 and 12 are connected to each other internally and
functionasthegroundreturnfortheon-chipRFbalun. For
best RF performance, Pins 2, 4, 6, 9, 10, 12, 15 and the
Exposed Pad, Pin 17, should be connected to the printed
circuit board ground plane.
for decoupling to ground on each of these pins.
RF (Pin 11): RF Output. The RF output is an AC-coupled
single-ended output with approximately 50Ω output im-
pedance at RF frequencies. Externally applied DC voltage
should be within the range –0.5V to (V + 0.5V) in order
CC
to avoid turning on ESD protection diodes.
BBPI,BBMI(Pins14,16):BasebandinputsfortheI-chan-
nel with about 90kΩ differential input impedance. These
pins should be externally biased at about 0.5V. Applied
common mode voltage must stay below 0.6V.
LO(Pin3):LOInput.TheLOinputisanAC-coupledsingle-
ended input with approximately 50Ω input impedance at
RF frequencies. Externally applied DC voltage should be
within the range –0.5V to (V + 0.5V) in order to avoid
turning on ESD protection diodes.
Exposed Pad (Pin 17): Ground. The Exposed Pad must
be soldered to the PCB.
CC
5571f
7
LT5571
BLOCK DIAGRAM
V
CC
8
13
BBPI 14
BBMI 16
V-I
V-I
11 RF
0°
90°
BALUN
BBPQ
BBMQ
7
5
1
EN
2
4
6
9
3
10
12
15
17
5571 BD
GND
LO
GND
APPLICATIONS INFORMATION
The LT5571 consists of I and Q input differential voltage-
to-currentconverters,IandQup-conversionmixers,anRF
signal combiner/balun, an LO quadrature phase generator
and LO buffers.
pins should not be left floating because the internal PNP’s
base current will pull the common mode voltage higher
than the 0.6V limit. This condition may damage the part.
The PNP’s base current is about 24µA in normal opera-
tion. On the LT5571 demo board, external 50Ω resistors
to ground are added to each baseband input to prevent
this condition and to serve as a termination resistance for
the baseband connections.
External I and Q baseband signals are applied to the dif-
ferential baseband input pins, BBPI, BBMI, and BBPQ,
BBMQ.Thesevoltagesignalsareconvertedtocurrentsand
translated to RF frequency by means of double-balanced
up-converting mixers. The mixer outputs are combined
in an RF output balun, which also transforms the output
impedance to 50Ω. The center frequency of the resulting
RF signal is equal to the LO signal frequency. The LO input
drives a phase shifter which splits the LO signal into in-
phaseandquadratureLOsignals.TheseLOsignalsarethen
applied to on-chip buffers which drive the up-conversion
mixers. Both the LO input and RF output are single-ended,
50Ω-matched and AC-coupled.
It is recommended that the I/Q signals be DC-coupled to
the LT5571. An applied common mode voltage level at the
I and Q inputs of about 0.5V will maximize the LT5571’s
dynamic range. Some I/Q generators allow setting the
common mode voltage independently. For a 0.5V com-
mon mode voltage setting, the common-mode voltage of
those generators must be set to 0.5V to create the desired
0.5V bias, when an external 50Ω is present in the setup
(See Figure 2).
Thepartshouldbedrivendifferentially;otherwise,theeven-
order distortion products will degrade the overall linearity
severely. Typically, a DAC will be the signal source for the
LT5571. A reconstruction filter should be placed between
the DAC output and the LT5571’s baseband inputs.
Baseband Interface
Thebasebandinputs(BBPI,BBMI),(BBPQ,BBMQ)present
a differential input impedance of about 90kΩ. At each of
the four baseband inputs, a capacitor of 1.8pF to ground
and a PNP emitter follower is incorporated (see Figure 1),
which limits the baseband bandwidth to approximately
200MHz (–1dB point), if driven by a 50Ω source. The
circuit is optimized for a common mode voltage of 0.5V
which should be externally applied. The baseband input
In Figure 3 a typical baseband interface is shown, includ-
ing a fifth-order low-pass ladder filter. For each baseband
pin, a 0 to 1V swing is developed corresponding to a DAC
output current of 0mA to 20mA. The maximum sinusoidal
single side-band RF output power is about +5.8dBm for
5571f
8
LT5571
APPLICATIONS INFORMATION
C
LT5571
RF
V
= 5V
CC
BALUN
FROM
Q-CHANNEL
LOMI
LOPI
BBPI
1.8pF
1.8pF
V
= 0.5V
BBMI
CM
5571 F01
GND
Figure 1. Simplified Circuit Schematic of the LT5571 (Only I-Half is Drawn)
50Ω
50Ω
LT5571
0.5V
0.5005V
DC
DC
50Ω
EXTERNAL
LOAD
+
+
1V
1V
20µA
DC
DC
DC
–
–
50Ω
GENERATOR
GENERATOR
5571 F02
Figure 2. DC Voltage Levels for a Generator Programmed at 0.5V for a 50Ω Load Without and with the LT5571 as a Load
DC
C
LT5571
MAX RF
+5.8dBm
V
CC
BALUN
5V
FROM
Q-CHANNEL
LOMI
LOPI
L1A
L2A
0.5V
0.5V
0mA TO 20mA
DC BBPI
R1A
R2A
100Ω
100Ω
C1
L1B
C2
L2B
C3
DAC
1.8pF
1.8pF
R1B
100Ω
R2B
100Ω
20mA TO 0mA
BBMI
DC
GND
5571 F03
GND
Figure 3. LT5571 Baseband Interface with 5th Order Filter and 0.5V DAC (Only I Channel is Shown)
CM
5571f
9
LT5571
APPLICATIONS INFORMATION
Table 1. Typical Performance Characteristics vs V for f = 900MHz, P = 0dBm
CM
LO
OIP2 (dBm)
LO
V
(V)
0.1
0.2
0.25
0.3
0.4
0.5
0.6
I
(mA)
55.3
G (dB)
OP1dB (dBm)
OIP3 (dBm)
9.2
NFloor (dBm/Hz)
–163.6
LOFT (dBm)
–53.6
IR (dBc)
37.0
40.4
43.5
43.9
45.1
45.4
45.6
CM
CC
V
–4.5
–3.9
–3.7
–3.6
–3.5
–3.6
–3.7
–1.5
2.0
3.4
4.5
6.3
7.9
8.4
53.4
51.7
51.9
52.1
53.1
53.0
53.7
65.3
70.3
75.7
86.4
97.1
108.1
11.2
13.3
15.6
18.7
20.6
22.1
–161.8
–161.2
–160.5
–159.6
–158.7
–157.9
–50.3
–49.0
–47.7
–45.3
–43.1
–41.2
full 0V to 1V swing on each baseband input (2V
).
PEAK
50Ω, and the recommended LO input power window is
P-P,DIFF
This maximum RF output level is limited by the 0.5V
–2dBm to 2dBm. For P < –2dBm input power, the gain,
LO
maximum baseband swing possible for a 0.5V com-
OIP2,OIP3,dynamic-range(indBc/Hz)andimagerejection
DC
mon-mode voltage level (assuming no negative supply
will degrade, especially at T = 85°C.
A
bias voltage is available).
HarmonicspresentontheLOsignalcandegradetheimage
rejection,becausetheyintroduceasmallexcessphaseshift
in the internal phase splitter. For the second (at 1.8GHz)
and third harmonics (at 2.7GHz) at –20dBc level, the in-
troduced signal at the image frequency is about –61dBc
or lower, corresponding to an excess phase shift much
less than 1 degree. For the second and third harmonics at
–10dBc, still the introduced signal at the image frequency
isabout–51dBc. Higherharmonicsthanthethirdwillhave
less impact. The LO return loss typically will be better than
11dB over the 750MHz to 1GHz range. Table 2 shows the
LO port input impedance vs frequency.
It is possible to bias the LT5571 to a common mode
voltage level other than 0.5V. Table 1 shows the typical
performance for different common mode voltages.
LO Section
The internal LO input amplifier performs single-ended to
differential conversion of the LO input signal. Figure 4
shows the equivalent circuit schematic of the LO input.
The internal differential LO signal is split into in-phase and
quadrature (90° phase shifted) signals to drive LO buffer
sections. These buffers drive the double balanced I and
Q mixers. The phase relationship between the LO input
and the internal in-phase LO and quadrature LO signals
is fixed, and is independent of start-up conditions. The
phase shifters are designed to deliver accurate quadrature
signals for an LO frequency near 900MHz. For frequen-
cies significantly below 750MHz or above 1100MHz, the
quadrature accuracy will diminish, causing the image
rejection to degrade. The LO pin input impedance is about
Table 2. LO Port Input Impedance vs Frequency for EN = High
and P = 0dBm
LO
S
FREQUENCY
(MHz)
INPUT IMPEDANCE
11
(Ω)
Mag
Angle
97
40
500
600
700
800
900
1000
1100
1200
47.2 + j11.7
58.4 + j8.3
65.0 – j0.6
66.1 – j12.2
60.7 – j22.5
53.3 – j25.1
48.4 – j25.1
42.7 – j26.4
0.123
0.108
0.131
0.173
0.221
0.239
0.248
0.285
–2
–31
–53
–69
–79
–89
V
CC
20pF
LO
INPUT
The return loss S on the LO port can be improved at
11
Z
≈ 60Ω
IN
lower frequencies by adding a shunt capacitor. The input
impedance of the LO port is different if the part is in
shut-down mode. The LO input impedance for EN = Low
is given in Table 3.
5571 F04
Figure 4. Equivalent Circuit Schematic of the LO Input
5571f
10
LT5571
APPLICATIONS INFORMATION
For EN = Low the S is given in Table 6.
Table 3. LO Port Input Impedance vs Frequency for EN = Low
22
and P = 0dBm
LO
Table 6. RF Port Output Impedance vs Frequency for EN = Low
S
11
FREQUENCY
(MHz)
INPUT IMPEDANCE
S
22
FREQUENCY
(MHz)
OUTPUT IMPEDANCE
(Ω)
Mag
Angle
83
(Ω)
Mag
Angle
166
144
120
89
–38
–99
–117
–130
500
600
700
800
900
1000
1100
1200
35.6 + j42.1
65.5 + j70.1
163 + j76.3
188 – j95.2
72.9 – j114
34.3 – j83.5
21.6 – j63.3
16.4 – j50.5
0.467
0.531
0.602
0.654
0.692
0.715
0.726
0.727
500
600
700
800
900
1000
1100
1200
21.5 + j5.0
26.9 + j11.8
36.5 + j16.0
48.8 + j11.2
52.8 – j2.2
46.6 – j11.5
39.7 – j13.9
35.0 – j13.0
0.403
0.333
0.239
0.113
0.035
0.123
0.191
0.232
46
14
–13
–36
–56
–73
–86
RF Section
To improve S for lower frequencies, a series capacitor
22
can be added to the RF output. At higher frequencies, a
Afterup-conversion,theRFoutputsoftheIandQmixersare
combined. An on-chip balun performs internal differential
tosingle-endedoutputconversion,whiletransformingthe
output signal impedance to 50Ω. Table 4 shows the RF
port output impedance vs frequency.
shunt inductor can improve the S . Figure 5 shows the
22
equivalent circuit schematic of the RF output.
Note that an ESD diode is connected internally from the
RF output to ground. For strong output RF signal levels
(higher than 3dBm) this ESD diode can degrade the lin-
earity performance if an external 50Ω termination imped-
ance is connected directly to ground. To prevent this, a
coupling capacitor can be inserted in the RF output line.
This is strongly recommended during 1dB compression
measurements.
Table 4. RF Port Output Impedance vs Frequency for EN = High
and P = 0dBm
LO
S
FREQUENCY
(MHz)
OUTPUT IMPEDANCE
22
(Ω)
Mag
Angle
165
143
119
91
500
600
700
800
900
1000
1100
1200
22.2 + j5.2
28.4 + j11.7
38.8 + j14.3
49.4 + j6.8
49.4 – j5.8
42.7 – j11.7
36.9 – j12.6
33.2 – j11.3
0.390
0.311
0.202
0.068
0.058
0.149
0.207
0.241
V
CC
–92
21pF
7nH
–115
–128
–138
RF
OUTPUT
47Ω
1pF
5571 F05
The RF output S with no LO power applied is given in
22
Table 5.
Figure 5. Equivalent Circuit Schematic of the RF Output
Table 5. RF Port Output Impedance vs Frequency for EN = High
and No LO Power Applied
Enable Interface
S
22
FREQUENCY
(MHz)
OUTPUT IMPEDANCE
Figure 6 shows a simplified schematic of the EN pin inter-
face. The voltage necessary to turn on the LT5571 is 1V.
To disable (shut down) the chip, the enable voltage must
be below 0.5V. If the EN pin is not connected, the chip is
disabled. This EN = Low condition is guaranteed by the
75kΩ on-chip pull-down resistor.
(Ω)
Mag
Angle
165
143
123
145
–123
–131
–140
–148
500
600
700
800
900
1000
1100
1200
22.9 + j5.3
30.0 + j11.2
40.6 + j11.2
47.3 + j1.9
44.2 – j7.4
38.4 – j10.4
34.2 – j10.2
31.7 – j8.7
0.377
0.283
0.160
0.034
0.099
0.175
0.221
0.246
It is important that the voltage at the EN pin does not
exceed V by more than 0.5V. If this should occur, the
CC
5571f
11
LT5571
APPLICATIONS INFORMATION
V
overheating. R1 (optional) limits the EN pin current in the
CC
event that the EN pin is pulled high while the V inputs
CC
EN
are low. The application board PCB layouts are shown in
Figures 8 and 9.
75k
25k
5571 F06
Figure 6. EN Pin Interface
full chip supply current could be sourced through the EN
pin ESD protection diodes, which are not designed for this
purpose. Damage to the chip may result.
Evaluation Board
Figure 7 shows the evaluation board schematic. A good
ground connection is required for the LT5571’s Exposed
Pad. If this is not done properly, the RF performance will
degrade.Additionally,theExposedPadprovidesheatsink-
ing for the part and minimizes the possibility of the chip
J1
J2
BBIM
BBIP
R2
49.9Ω
R5
49.9Ω
Figure 8. Component Side of Evaluation Board
V
CC
C1
16 15
BBMI GND
EN
14
BBPI
13
100nF
R1
100Ω
V
CC
1
2
3
4
12
V
EN
GND
RF
CC
J3
11
10
9
RF
OUT
GND
LO
J4
LT5571
LO IN
GND
GND
GND
GND
17
BBMQ GND BBPQ
V
CC
5
6
7
8
C2
100nF
J5
J6
BBQM
R3
49.9Ω
BBQP
R4
49.9Ω
5571 F07
BOARD NUMBER: DC944A
Figure 7. Evaluation Circuit Schematic
Figure 9. Bottom Side of Evaluation Board
5571f
12
LT5571
APPLICATIONS INFORMATION
Application Measurements
The ACPR performance is sensitive to the amplitude
mismatch of the BBIP and BBIM (or BBQP and BBQM)
input voltage. This is because a difference in AC voltage
amplitudewillgiverisetoadifferenceinamplitudebetween
theeven-orderharmonicproductsgeneratedintheinternal
V-I converter. As a result, they will not cancel out entirely.
Therefore,itisimportanttokeeptheamplitudesattheBBIP
and BBIM (or BBQP and BBQM) as equal as possible.
TheLT5571isrecommendedforbase-stationapplications
using various modulation formats. Figure 10 shows a
typical application.
Figure 11 shows the ACPR performance for CDMA2000
usingoneandthreechannelmodulation.Figures12and13
illustrate the 1- and 3-channel CDMA2000 measurement.
To calculate ACPR, a correction is made for the spectrum
analyzer’s noise floor (Application Note 99).
LO feedthrough and image rejection performance may
be improved by means of a calibration procedure. LO
feedthrough is minimized by adjusting the differential DC
offsets at the I and the Q baseband inputs. Image rejection
can be improved by adjusting the amplitude and phase
difference between the I and the Q baseband inputs. The
LO feedthrough and Image Rejection can also change
as a function of the baseband drive level, as depicted in
Figure 14.
If the output power is high, the ACPR will be limited by the
linearity performance of the part. If the output power is
low, the ACPR will be limited by the noise performance of
the part. In the middle, an optimum ACPR is obtained.
BecauseoftheLT5571’sveryhighdynamic-range,thetest
equipment can limit the accuracy of the ACPR measure-
ment. Consult Design Note 375 or the factory for advice
on ACPR measurement if needed.
–40
–50
–60
–70
–80
–90
–110
–120
–130
–140
–150
–160
DOWNLINK TEST
MODEL 64 DPCH
5V
8, 13
100nF
3-CH ACPR
V
CC
LT5571
14
16
×2
RF = 620MHz
TO 1100MvHz
1-CH
I-DAC
V-I
I-CH
3-CH AltCPR
ACPR
11
PA
0°
1
EN
90°
BALUN
1-CH NOISE
Q-CH
V-I
7
5
1-CH AltCPR
3-CH NOISE
Q-DAC
BASEBAND
GENERATOR
5571 F10
–30
–25
–20
–15
–10
–5
0
3
VCO/SYNTHESIZER
2, 4, 6, 9, 10, 12, 15, 17
RF OUTPUT POWER PER CARRIER (dBm)
5571 F11
Figure 10. 620MHz to 1.1GHz Direct Conversion Transmitter Application
Figure 11. CDMA2000 ACPR, ALTCPR and Noise vs
RF Output Power at 900MHz for 1 and 3 Carriers
–30
–40
–30
–40
20
DOWNLINK
TEST MODEL
64 DPCH
DOWNLINK TEST
MODEL 64 DPCH
P
RF
10
0
–50
–50
–10
–20
–30
–40
–50
–60
–70
–80
–90
–60
–60
25°C
85°C
–40°C
SPECTRUM
ANALYSER
NOISE
UN-
CORRECTED
SPECTRUM
–70
–70
LO FT
–80
–80
UNCORRECTED
SPECTRUM
CORRECTED
SPECTRUM
FLOOR
–90
–90
IR
–100
–110
–120
–130
–100
–110
–120
–130
f
= 2MHz, 0°
BBI
CC
V
= 5V, f
= 2MHz, 90°
BBQ
EN = HIGH, f = f + f
RF BB LO
= 900MHz, P = 0dBm
CORRECTED SPECTRUM
f
LO
SPECTRUM ANALYSER NOISE FLOOR
LO
0
1
2
3
4
5
894
896
898
900
902
904
906
896.25 897.75 899.25 900.75 902.25 903.75
I AND Q BASEBAND VOLTAGE (V
)
RF FREQUENCY (MHz)
RF FREQUENCY (MHz)
P-P,DIFF
5571 F13
5571 F12
5571 F14
Figure 12. 1-Channel CDMA2000 Spectrum Figure 13. 3-Channel CDMA2000 Spectrum
Figure 14. Image Rejection and LO Feed-
Through vs Baseband Drive Voltage After
Calibration at 25°C
5571f
13
LT5571
APPLICATIONS INFORMATION
Example: RFID Application
the RFID baseband signals in the fastest mode (TARI =
6.25µs, see [1]) significantly, and at the same time achiev-
ing enough alias attenuation while using a 32MHz sampling
frequency. The resulting Alt80-CPR (the alias frequency at
897.875MHz falls outside the RF frequency range of Figure
16a) is –92dBc for TARI = 6.25µs. The SSB-ASK output
signal spectrum is plotted in Figure 16a, together with the
Dense-Interrogator Transmit mask [1] for TARI = 25µs. The
corresponding envelope representation is given in Figure
Figure 15 shows the interface between a current drive DAC
and the LT5571 for RFID applications. The SSB-ASK mode
requiresanI/Qmodulatortogeneratethedesiredspectrum.
According to [1], the LT5571 is capable of meeting the
“Dense-Interrogator” requirements with reduced supply
current. A V = 0.25V was chosen in order to save 30mA
CM
current, resulting in a modulator supply current of about
73mA. This is achieved by sourcing 5mA average DAC
DC
16b. The Alt1-CPR can be increased by using a higher V
CM
current into 50Ω resistors R1A and R1B. As anti-aliasing
filter, anRCRCfilterwaschosenusingR1A, R1B, C1A, C1B,
R2A, R2B, C2A and C2B. This results in a second-order
passive low-pass filter with –3dB cutoff at 790kHz. This
filter cutoff is chosen high enough that it will not affect
at the cost of extra supply current or a lower baseband drive
at the cost of lower RF output power. The center frequency
of the channel is chosen at 865.9MHz (“channel 2”), while
the LO frequency is chosen at 865.875MHz.
C
LT5571
RF
V
CC
BALUN
5V
FROM
Q-CHANNEL
LOMI
LOPI
R2A
250Ω
0.25V
0.25V
0.25V
0.25V
0mA TO 10mA
DC
DC BBPI
C1A
2.2nF
C2A
470pF
R1A
50Ω
DAC
1.8pF
1.8pF
GND
C1B
2.2nF
C2B
470pF
R1B
50Ω
10mA TO 0mA
BBMI
DC
R2B
250Ω
DC
5571 F15
GND
Figure 15. Recommended Baseband Interface for RFID Applications (Only I Channel is Drawn)
0.3
0.2
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
0.1
0
–0.1
–0.2
–0.3
0
50
100
150
200
250
865.4
865.6
865.8
FREQUENCY (MHz)
CH BANDWIDTH: 100kHz ALT1 UP: –71.15dBc
866.0 866.2 866.4
TIME (µs)
5571 F16b
CH SPACING: 100kHz
CH PWR: –4.85dBm
ACP UP: –33.74dBc
ACP LOW: –37.76dBc
ALT1 LOW: –64.52dBc
ALT2 UP: –72.80dBc
ALT2 LOW: –72.42dBc
5571 F16a
Figure 16a and 16b. RFID SSB-ASK Spectrum with Mask and Corresponding RF Envelope for TARI = 25µs
[1] EPC Radio Frequency Identity Protocols, Class-1 Generation-2 UHF RFID Protocol for
Communications at 860MHz – 960MHz, version 1.0.9.
5571f
14
LT5571
PACKAGE DESCRIPTION
UF Package
16-Lead Plastic QFN (4mm × 4mm)
(Reference LTC DWG # 05-08-1692)
0.72 0.05
4.35 0.05
2.90 0.05
2.15 0.05
(4 SIDES)
PACKAGE OUTLINE
0.30 0.05
0.65 BSC
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
BOTTOM VIEW—EXPOSED PAD
PIN 1 NOTCH R = 0.20 TYP
OR 0.35 × 45° CHAMFER
0.75 0.05
R = 0.115
TYP
4.00 0.10
(4 SIDES)
15
16
0.55 0.20
PIN 1
TOP MARK
(NOTE 6)
1
2
2.15 0.10
(4-SIDES)
(UF16) QFN 10-04
0.200 REF
0.30 0.05
0.65 BSC
0.00 – 0.05
NOTE:
1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGC)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON THE TOP AND BOTTOM OF PACKAGE
5571f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
15
LT5571
RELATED PARTS
PART NUMBER
Infrastructure
LT5514
DESCRIPTION
COMMENTS
Ultralow Distortion, IF Amplifier/ADC Driver
with Digitally Controlled Gain
850MHz Bandwidth, 47dBm OIP3 at 100MHz, 10.5dB to 33dB Gain Control Range
LT5515
LT5516
1.5GHz to 2.5GHz Direct Conversion Quadrature 20dBm IIP3, Integrated LO Quadrature Generator
Demodulator
0.8GHz to 1.5GHz Direct Conversion Quadrature 21.5dBm IIP3, Integrated LO Quadrature Generator
Demodulator
LT5517
LT5518
40MHz to 900MHz Quadrature Demodulator
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
21dBm IIP3, Integrated LO Quadrature Generator
22.8dBm OIP3 at 2GHz, –158.2dBm/Hz Noise Floor, 50Ω Single-Ended RF and LO
Ports, 4-Channel W-CDMA ACPR = –64dBc at 2.14GHz
LT5519
LT5520
LT5521
LT5522
LT5524
LT5525
LT5526
LT5527
LT5528
LT5558
0.7GHz to 1.4GHz High Linearity Upconverting 17.1dBm IIP3 at 1GHz, Integrated RF Output Transformer with 50Ω Matching,
Mixer Single-Ended LO and RF Ports Operation
1.3GHz to 2.3GHz High Linearity Upconverting 15.9dBm IIP3 at 1.9GHz, Integrated RF Output Transformer with 50Ω Matching,
Mixer
Single-Ended LO and RF Ports Operation
10MHz to 3700MHz High Linearity
Upconverting Mixer
24.2dBm IIP3 at 1.95GHz, NF = 12.5dB, 3.15V to 5.25V Supply, Single-Ended LO
Port Operation
600MHz to 2.7GHz High Signal Level
Downconverting Mixer
4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended RF
and LO Ports
Low Power, Low Distortion ADC Driver with
Digitally Programmable Gain
450MHz Bandwidth, 40dBm OIP3, 4.5dB to 27dB Gain Control
High Linearity, Low Power Downconverting
Mixer
Single-Ended 50Ω RF and LO Ports, 17.6dBm IIP3 at 1900MHz, I = 28mA
CC
High Linearity, Low Power Downconverting
Mixer
3V to 5.3V Supply, 16.5dBm IIP3, 100kHz to 2GHz RF, NF = 11dB, I = 28mA,
CC
–65dBm LO-RF Leakage
400MHz to 3.7GHz High Signal Level
Downconverting Mixer
IIP3 = 23.5dBm and NF = 12.5dBm at 1900MHz, 4.5V to 5.25V Supply, I = 78mA,
CC
Conversion Gain = 2dB.
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
21.8dBm OIP3 at 2GHz, –159.3dBm/Hz Noise Floor, 50Ω, 0.5V Baseband
DC
Interface, 4-Channel W-CDMA ACPR = –66dBc at 2.14GHz
600MHz to 1100MHz High Linearity Direct
Quadrature Modulator
22.4dBm OIP3 at 900MHz, –158dBm/Hz Noise Floor, 3kΩ, 2.1V Baseband
DC
Interface, 3-Ch CDMA2000 ACPR = –70.4dBc at 900MHz
LT5560
LT5568
Ultra-Low Power Active Mixer
700MHz to 1050MHz High Linearity Direct
Quadrature Modulator
10mA Supply Current, 10dBm IIP3, 10dB NF, Usable as Up- or Down-Converter.
22.9dBm OIP3 at 850MHz, –160.3dBm/Hz Noise Floor, 50Ω, 0.5V Baseband
DC
Interface, 3-Ch CDMA2000 ACPR = –71.4dBc at 850MHz
LT5572
1.5GHz to 2.5GHz High Linearity Direct
Quadrature Modulator
21.6dBm OIP3 at 2GHz, –158.6dBm/Hz Noise Floor, High-Ohmic 0.5V Baseband
DC
Interface, 4-Ch W-CDMA ACPR = –67.7dBc at 2.14GHz
RF Power Detectors
LTC®5505
LTC5507
LTC5508
LTC5509
RF Power Detectors with >40dB Dynamic Range 300MHz to 3GHz, Temperature Compensated, 2.7V to 6V Supply
100kHz to 1000MHz RF Power Detector
300MHz to 7GHz RF Power Detector
300MHz to 3GHz RF Power Detector
100kHz to 1GHz, Temperature Compensated, 2.7V to 6V Supply
44dB Dynamic Range, Temperature Compensated, SC70 Package
36dB Dynamic Range, Low Power Consumption, SC70 Package
LTC5530
LTC5531
LTC5532
300MHz to 7GHz Precision RF Power Detector Precision V
300MHz to 7GHz Precision RF Power Detector Precision V
300MHz to 7GHz Precision RF Power Detector Precision V
Offset Control, Shutdown, Adjustable Gain
Offset Control, Shutdown, Adjustable Offset
Offset Control, Adjustable Gain and Offset
OUT
OUT
OUT
LT5534
50MHz to 3GHz Log RF Power Detector with
60dB Dynamic Range
1dB Output Variation over Temperature, 38ns Response Time, Log Linear
Response
LTC5536
LT5537
Precision 600MHz to 7GHz RF Power Detector 25ns Response Time, Comparator Reference Input, Latch Enable Input,
with Fast Comparator Output
–26dBm to +12dBm Input Range
Wide Dynamic Range Log RF/IF Detector
Low Frequency to 1GHz, 83dB Log Linear Dynamic Range
5571f
LT 1206 • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
16
●
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© LINEAR TECHNOLOGY CORPORATION 2006
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
相关型号:
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LT5571EUF#TRPBF
LT5571 - 620MHz - 1100MHz High Linearity Direct Quadrature Modulator; Package: QFN; Pins: 16; Temperature Range: -40°C to 85°C
Linear
LT5572EUF#TRPBF
LT5572 - 1.5GHz to 2.5GHz High Linearity Direct Quadrature Modulator; Package: QFN; Pins: 16; Temperature Range: -40°C to 85°C
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LT5575EUF#PBF
LT5575 - 800MHz to 2.7GHz High Linearity Direct Conversion Quadrature Demodulator; Package: QFN; Pins: 16; Temperature Range: -40°C to 85°C
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