LT6210IS6#PBF_技术文档

LT6210/LT6211

Single/Dual Programmable

Supply Current, R-R Output,

Current Feedback Ampliﬁers

FEATURES

DESCRIPTION

The LT^®6210/LT6211 are single/dual current feedback

ampliﬁers with externally programmable supply current

and bandwidth ranging from 10MHz at 300μA per ampli-

ﬁer to 200MHz at 6mA per ampliﬁer. They feature a low

distortion rail-to-rail output stage, 700V/μs slew rate and

a minimum output current drive of 7±mA.

n

Programmable Supply Current and Bandwidth:

10MHz at 300μA per Ampliﬁer up to

200MHz at 6mA per Ampliﬁer

n

Rail-to-Rail Output:

0.0±V to 2.8±V on 3V Single Supply

n

High Slew Rate: 700V/μs

High Output Drive:

n

The LT6210/LT6211 operate on supplies as low as a single

3V and up to either 12V or ±6V. The I pin allows for the

optimization of quiescent current for speciﬁc bandwidth,

distortionorslewraterequirements. Regardlessofsupply

voltage, the supply current is programmable from just

300μA to 6mA per ampliﬁer with an external resistor or

current source.

±7±mA Minimum Output Current

SET

n

C-Load™ Op Amp Drives All Capacitive Loads

n

Low Distortion:

–70dB HD2 at 1MHz 2V

–7±dB HD3 at 1MHz 2V

Fast Settling:

P-P

n

20ns 0.1% Settling for 2V Step

Excellent Video Performance Into 150Ω Load:

Differential Gain of 0.20%, Differential Phase of 0.10°

Wide Supply Range:

The LT6210 is available in the low proﬁle (1mm) 6-lead

TSOT-23 package. The LT6211 is available in the 10-lead

MSOP and the 3mm × 3mm × 0.8mm DFN packages.

3V to 12V Single Supply

±1.±V to ±6V Dual Supplies

APPLICATIONS

n

Small Size:

™

n

Buffers

Low Proﬁle (1mm) 6-Lead ThinSOT ,

n

Video Amplifers

3mm × 3mm × 0.8mm DFN and 10-Lead MSOP Packages

n

Cable Drivers

Mobile Communication

Low Power/Battery Applications

L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear

Technology Corporation. C-Load is a Trademark of Linear Technology Corporation. All other

trademarks are the property of their respective owners.

n

TYPICAL APPLICATION

Small Signal Response vs Supply Current

Line Driver Conﬁguration for Various Supply Currents

9

3

I

S

= 3mA

±V

6

0

I

= 6mA

S

3

4

7±Ω

6

V

IN

+

–

CABLE

7±Ω

I

= 300μA

S

1

3

–3

–6

–9

–12

LT6210

V

OUT

±

7±Ω

R

SET

2

0

–±V

R

F

V

A

= ±±V

= 2

S

V

A

–3

I

S

R

SET

R

LOAD

T

= 2±°C

G

F

R

G

V

= 100mV

OUT

P-P

6mA

3mA

20k

±6k

1M

887Ω

1.1k

11k

887Ω

1.1k

11k

1±0Ω

1k

–6

0.1

1

10

100

1000

300μA

FREQUENCY (MHz)

6210 TA01

6210 TA01b

62101fb

1

LT6210/LT6211

ABSOLUTE MAXIMUM RATINGS

(Note 1)

+

–

Total Supply Voltage (V to V )..............................13.2V

Input Current (Note 8) .....................................±10mA

Output Current.................................................±80mA

Output Short-Circuit Duration (Note 2) ............ Indeﬁnite

Operating Temperature Range (Note 3).... –40°C to 8±°C

Speciﬁed Temperature Range (Note 4) .... –40°C to 8±°C

Junction Temperature (Note ±) ............................. 1±0°C

Junction Temperature (DD Package)..................... 1±0°C

Storage Temperature Range .................. –6±°C to 1±0°C

Storage Temperature Range

(DD Package)..................................... –6±°C to 1±0°C

Lead Temperature (Soldering, 10 sec) .................. 300°C

PIN CONFIGURATION

TOP VIEW

+

OUT A

–IN A

+IN A

1

2

3

4

±

10

9

V

TOP VIEW

+

OUT B

–IN B

+IN B

–

+

OUT A

–IN A

+IN A

1

2

3

4

±

10

9

V

+

OUT 1

–

6 V

± I

–

11

OUT B

–IN B

+IN B

8

–

+

–

+

8

V

2

SET

I

A

–

7

SET

I

A

7

6

+

–

SET

+IN 3

4 –IN

–

V

6

I

B

SET

V

I

B

SET

MS PACKAGE

10-LEAD PLASTIC MSOP

= 1±0°C, θ = 120°C/W (NOTE ±)

S6 PACKAGE

DD PACKAGE

10-LEAD (3mm s 3mm) PLASTIC DFN

6-LEAD PLASTIC TSOT-23

T

JMAX

= 1±0°C, θ = 230°C/W (NOTE ±)

JMAX

JA

T

= 1±0°C, θ = 43°C/W (NOTE ±)

JA

JMAX

–

EXPOSED PAD (PIN 11) CONNECTED TO V

(PCB CONNECTION OPTIONAL)

ORDER INFORMATION

LEAD FREE FINISH

LT6211CDD#PBF

LT6211IDD#PBF

LT6211CMS#PBF

LT6211IMS#PBF

LT6210CS6#PBF

LT6210IS6#PBF

LEAD BASED FINISH

LT6211CDD

TAPE AND REEL

LT6211CDD#TRPBF

LT6210IS6#TRPBF

LT6210CS6#TRPBF

LT6210IS6#TRPBF

LT6210CS6#TRPBF

LT6210IS6#TRPBF

TAPE AND REEL

LT6211CDD#TR

LT6210IS6#TR

PART MARKING*

LBCD

PACKAGE DESCRIPTION

SPECIFIED TEMPERATURE RANGE

–40°C to 8±°C

10-Lead (3mm × 3mm) Plastic DFN

10-Lead Plastic MSOP

LBCD

–40°C to 8±°C

LTBBN

–40°C to 8±°C

LTBBP

10-Lead Plastic MSOP

–40°C to 8±°C

LTA3

6-Lead Plastic TSOT-23

–40°C to 8±°C

LTA3

6-Lead Plastic TSOT-23

–40°C to 8±°C

PART MARKING*

LBCD

PACKAGE DESCRIPTION

10-Lead (3mm × 3mm) Plastic DFN

10-Lead Plastic MSOP

SPECIFIED TEMPERATURE RANGE

–40°C to 8±°C

LT6211IDD

LBCD

–40°C to 8±°C

LT6211CMS

LT6210CS6#TR

LTBBN

–40°C to 8±°C

LT6211IMS

LT6210IS6#TR

LTBBP

10-Lead Plastic MSOP

–40°C to 8±°C

LT6210CS6

LTC4263CDE#TR

LTC4263IDE#TR

LTA3

6-Lead Plastic TSOT-23

–40°C to 8±°C

LT6210IS6

LTA3

6-Lead Plastic TSOT-23

–40°C to 8±°C

Consult LTC Marketing for parts speciﬁed with wider operating temperature ranges. *The temperature grade is identiﬁed by a label on the shipping container.

For more information on lead free part marking, go to: http://www.linear.com/leadfree/

For more information on tape and reel speciﬁcations, go to: http://www.linear.com/tapeandreel/

62101fb

2

LT6210/LT6211

ELECTRICAL CHARACTERISTICS

(I = 6mA per Ampliﬁer) The l denotes the speciﬁcations which

S

apply over the speciﬁed operating temperature range, otherwise speciﬁcations are at T_A= 25°C. For V⁺= 5V, V^–= –5V: R_SET= 20k to

ground, A_V= +2, R_F= R_G= 887Ω, R_L= 150Ω; For V⁺= 3V, V^–= 0V: R_SET= 0Ω to V^–, A_V= +2, R_F= 887Ω, R_G= 887Ω to 1.5V,

R_L= 150Ω to 1.5V unless otherwise speciﬁed.

+

–

+

–

V = 5V, V = –5V, I = 6mA

V = 3V, V = 0V, I = 6mA

S

SYMBOL PARAMETER

CONDITIONS

MIN

TYP

MAX

MIN

TYP

MAX

UNITS

V

Input Offset Voltage

–1

±6

±9

–1

±6.±

±10

mV

OS

l

+

I

Noninverting Input Current

Inverting Input Current

Input Noise Voltage Density

–3.±

–13.±

6.±

±7

±9

–3

2.±

6.±

±6.±

±8

μA

IN

–

±39

±±±

±2±

±40

μA

IN

en

f = 1kHz, R = 887Ω,

nV/√Hz

F

R = 46.4Ω, R = 0Ω

G

S

+i

–i

Input Noise Current Density

Noninverting Input Resistance

f = 1kHz

4.±

2±

2

4.±

2±

1.7

2

pA/√Hz

MΩ

pF

n

f = 1kHz

n

+

–

l

R

V

IN

= V – 1.2V to V + 1.2V

0.±

3.8

0.3

1.8

IN

+

C

V

Noninverting Input Capacitance f = 100kHz

2

IN

l

Input Voltage Range, High

Input Voltage Range, Low

Output Voltage Swing, High

(Note 10)

4.2

–4.2

2.2

0.8

V

INH

–3.8

1.2

V

INL

R = 1k (Note 11)

4.8

4.6

2.8±

2.7±

V

OUTH

L

R = 1±0Ω (Note 11)

4.4

4.2

2.6±

2.6

L

l

R = 1±0Ω (Note 11)

L

V

Output Voltage Swing, Low

R = 1k (Note 11)

–4.9±

–4.8

0.0±

0.1

V

OUTL

L

R = 1±0Ω (Note 11)

–4.±±

–4.4

0.3

L

l

R = 1±0Ω (Note 11)

0.3±

L

+

–

CMRR

–I

Common Mode Rejection Ratio

V

= V – 1.2V to V + 1.2V

46

43

±0

46

dB

IN

+

–

Inverting Input Current

Common Mode Rejection

= V – 1.2V to V + 1.2V

0.1±

±1.±

±2

0.2

μA/V

CMRR

IN

l

PSRR

–I

Power Supply Rejection Ratio

V = ±1.±V to ±6V (Note 6)

S

60

8±

2

60

8±

2

dB

Inverting Input Current Power

Supply Rejection

V = ±1.±V to ±6V (Note 6)

S

±7

±8

±7

±8

μA/V

PSRR

l

I

S

Supply Current per Ampliﬁer

6

8.±

10

±.8

8.3

9

mA

62101fb

3

LT6210/LT6211

ELECTRICAL CHARACTERISTICS

(I = 6mA per Ampliﬁer) The l denotes the speciﬁcations which

S

apply over the speciﬁed operating temperature range, otherwise speciﬁcations are at T_A= 25°C. For V⁺= 5V, V^–= –5V: R_SET= 20k to

ground, A_V= +2, R_F= R_G= 887Ω, R_L= 150Ω; For V⁺= 3V, V^–= 0V: R_SET= 0Ω to V^–, A_V= +2, R_F= 887Ω, R_G= 887Ω to 1.5V,

R_L= 150Ω to 1.5V unless otherwise speciﬁed.

+

–

+

–

V = 5V, V = –5V, I = 6mA

V = 3V, V = 0V, I = 6mA

S

SYMBOL PARAMETER

Maximum Output Current

CONDITIONS

R = 0Ω (Notes 7, 11)

MIN

±7±

6±

TYP

MAX

MIN

±4±

6±

TYP

MAX

UNITS

mA

l

I

OUT

L

–

+

–

R

OL

Transimpedance, ΔV /ΔI

V = V – 1.2V to V + 1.2V

OUT

11±

700

1.±

11±

200

2.4

kΩ

OUT IN

SR

Slew Rate

(Note 8)

±0% V to ±0% V

±00

V/μs

ns

t

pd

Propagation Delay

,

OUT

IN

+

–

100mV , Larger of t , t

P-P

pd pd

BW

–3dB Bandwidth

Settling Time

<1dB Peaking, A = 1

200

20

120

2±

MHz

ns

V

t

s

To 0.1% of V

, V = 2V

FINAL STEP

t , t

Small-Signal Rise and Fall Time 10% to 90%, V

= 100mV

P-P

2

3.±

ns

f

r

OUT

dG

dP

Differential Gain

(Note 9)

0.20

0.10

–70

–7±

0.3±

0.20

–6±

–7±

%

Differential Phase

(Note 9)

Deg

dBc

HD2

HD3

2nd Harmonic Distortion

3rd Harmonic Distortion

f = 1MHz, V

= 2V

OUT

P-P

OUT

(I = 3mA per Ampliﬁer) The l denotes the speciﬁcations which apply over the speciﬁed operating temperature range,

S

otherwise speciﬁcations are at T_A= 25°C. For V⁺= 5V, V^–= –5V: R_SET= 56k to ground, A_V= +2, R_F= R_G= 1.1k, R_L= 150Ω; For V⁺= 3V,

V^–= 0V: R_SET= 10k to V^–, A_V= +2, R_F= 1.27k, R_G= 1.27k to 1.5V, R_L= 150Ω to 1.5V unless otherwise speciﬁed.

+

–

+

–

V = 5V, V = –5V, I = 3mA

V = 3V, V = 0V, I = 3mA

S

SYMBOL PARAMETER

CONDITIONS

MIN

TYP

MAX

MIN

TYP

MAX

UNITS

V

Input Offset Voltage

–1

±±.±

±8.±

–1.±

±±.±

±8.±

mV

OS

l

+

I

Noninverting Input Current

Inverting Input Current

Input Noise Voltage Density

–1.±

–12

7

±±

±7

–1.±

–3

7

±±

±7

μA

IN

–

±36

±±2

±1±

±20

μA

IN

en

f = 1kHz, R = 1.1k,

nV/√Hz

F

R = ±7.6Ω, R = 0Ω

G

S

+i

–i

Input Noise Current Density

Noninverting Input Resistance

f = 1kHz

1.±

1±

3

1.±

1±

2.±

2

pA/√Hz

MΩ

pF

n

f = 1kHz

n

+

–

l

R

V

IN

= V – 1.2V to V + 1.2V

0.±

3.8

1

IN

+

C

V

Noninverting Input Capacitance f = 100kHz

2

IN

l

Input Voltage Range, High

Input Voltage Range, Low

Output Voltage Swing, High

(Note 10)

4.1

–4.1

1.8

2.1

0.9

V

INH

–3.8

1.2

V

INL

R = 1k (Note 11)

4.8

4.6

2.9

2.8

V

OUTH

L

R = 1±0Ω (Note 11)

4.3

4.1

2.6

2.±±

L

l

R = 1±0Ω (Note 11)

L

V

Output Voltage Swing, Low

R = 1k (Note 11)

–4.9±

–4.8

0.0±

0.1

V

OUTL

L

R = 1±0Ω (Note 11)

–4.±±

–4.4

0.3

0.3±

L

l

R = 1±0Ω (Note 11)

L

+

–

CMRR

–I

Common Mode Rejection Ratio

V

= V – 1.2V to V + 1.2V

46

43

±0

46

dB

IN

+

–

Inverting Input Current

Common Mode Rejection

V

= V – 1.2V to V + 1.2V

0.3

±1.±

±2

0.4

μA/V

CMRR

62101fb

4

LT6210/LT6211

ELECTRICAL CHARACTERISTICS

(I = 3mA per Ampliﬁer) The l denotes the speciﬁcations which

S

apply over the speciﬁed operating temperature range, otherwise speciﬁcations are at T_A= 25°C. For V⁺= 5V, V^–= –5V: R_SET= 56k to

ground, A_V= +2, R_F= R_G= 1.1k, R_L= 150Ω; For V⁺= 3V, V^–= 0V: R_SET= 10k to V^–, A_V= +2, R_F= 1.27k, R_G= 1.27k to 1.5V,

R_L= 150Ω to 1.5V unless otherwise speciﬁed.

+

–

+

–

V = 5V, V = –5V, I = 3mA

V = 3V, V = 0V, I = 3mA

S

SYMBOL PARAMETER

PSRR Power Supply Rejection Ratio

–I

CONDITIONS

V = ±1.±V to ±6V (Note 6)

MIN

TYP

8±

MAX

MIN

TYP

8±

MAX

UNITS

l

60

dB

S

Inverting Input Current Power

Supply Rejection

V = ±1.±V to ±6V (Note 6)

S

1.±

±7

±8

1.±

±7

±8

μA/V

PSRR

I

Supply Current per Ampliﬁer

3

4.1

4.±±

3

4.1

4.4

mA

S

l

Maximum Output Current

R = 0Ω (Notes 7, 11)

±70

6±

±4±

6±

mA

kΩ

OUT

L

–

+

–

R

Transimpedance, ΔV /ΔI

V = V – 1.2V to V + 1.2V

OUT

120

600

3.1

120

1±0

4.7

OL

OUT IN

SR

Slew Rate

(Note 8)

±0% V to ±0% V

4±0

V/μs

ns

t

pd

Propagation Delay

,

OUT

IN

+

–

100mV , Larger of t , t

P-P

pd pd

BW

–3dB Bandwidth

Settling Time

<1dB Peaking, A = 1

100

20

70

2±

MHz

ns

V

t

s

To 0.1% of V

, V = 2V

FINAL STEP

t , t

f

Small-Signal Rise and Fall Time 10% to 90%, V

= 100mV

P-P

3

±.6

ns

r

OUT

dG

dP

Differential Gain

(Note 9)

0.3±

0.30

–6±

0.42

0.44

–60

–6±

%

Differential Phase

(Note 9)

Deg

dBc

HD2

HD3

2nd Harmonic Distortion

3rd Harmonic Distortion

f = 1MHz, V

= 2V

OUT

P-P

OUT

P-P

(I = 300μA per Ampliﬁer) The l denotes the speciﬁcations which apply over the speciﬁed operating temperature range,

S

otherwise speciﬁcations are at T_A= 25°C. For V⁺= 5V, V^–= –5V: R_SET= 1M to ground, A_V= +2, R_F= R_G= 11k, R_L= 1k; For V⁺= 3V,

V^–= 0V: R_SET= 270k to V^–, A_V= +2, R_F= 9.31k, R_G= 9.31k to 1.5V, R_L= 1k to 1.5V unless otherwise speciﬁed.

+

–

+

–

V = 5V, V = –5V, I = 300μA V = 3V, V = 0V, I = 300μA

S

SYMBOL PARAMETER

CONDITIONS

MIN

TYP

MAX

MIN

TYP

MAX

UNITS

V

Input Offset Voltage

–1

±4.±

±8

–1.±

±4.±

±8

mV

OS

l

+

I

Noninverting Input Current

Inverting Input Current

Input Noise Voltage Density

0.2

–3

±1

±2

0.2

±1

±1.±

μA

IN

–

±8.±

±11

–0.±

13.±

±3

±4.±

μA

IN

en

f = 1kHz, R = 13k,

13.±

nV/√Hz

F

R = 681Ω, R = 0Ω

G

S

+i

–i

Input Noise Current Density

Noninverting Input Resistance

f = 1kHz

0.7±

±

0.7±

±

pA/√Hz

MΩ

n

f = 1kHz

n

+

–

l

R

V

= V – 1.2V to V + 1.2V

1

2±

1

1±

IN

(Note 8)

+

C

V

Noninverting Input Capacitance f = 100kHz

2

pF

V

IN

l

Input Voltage Range, High

Input Voltage Range, Low

Output Voltage Swing, High

(Note 10)

3.8

4.1

1.8

2.1

0.9

2.8±

INH

–4.1

4.8±

–3.8

1.2

V

INL

R = 1k (Note 11)

L

4.7±

4.7

2.7±

2.7

V

OUTH

l

V

Output Voltage Swing, Low

R = 1k (Note 11)

L

–4.9±

–4.8±

–4.8

0.0±

0.1±

0.2

V

OUTL

62101fb

5

LT6210/LT6211

ELECTRICAL CHARACTERISTICS

(I = 300μA per Ampliﬁer) The l denotes the speciﬁcations which

S

apply over the speciﬁed operating temperature range, otherwise speciﬁcations are at T_A= 25°C. For V⁺= 5V, V^–= –5V: R_SET= 1M to

ground, A_V= +2, R_F= R_G= 11k, R_L= 1k; For V⁺= 3V, V^–= 0V: R_SET= 270k to V^–, A_V= +2, R_F= 9.31k, R_G= 9.31k to 1.5V, R_L= 1k to

1.5V unless otherwise speciﬁed.

+

–

+

–

V = 5V, V = –5V, I = 300μA V = 3V, V = 0V, I = 300μA

S

SYMBOL PARAMETER

CMRR Common Mode Rejection Ratio

CONDITIONS

MIN

TYP

MAX

MIN

TYP

MAX

UNITS

+

–

V

IN

= V – 1.2V to V + 1.2V

46

43

±0

46

dB

l

+

–

–I

Inverting Input Current

V

= V – 1.2V to V + 1.2V

0.1±

±1.±

±2

0.2

μA/V

CMRR

IN

l

Common Mode Rejection

PSRR

–I

Power Supply Rejection Ratio

V = ±1.±V to ±6V (Note 6)

60

8±

60

8±

dB

S

Inverting Input Current Power

Supply Rejection

V = ±1.±V to ±6V (Note 6)

0.4

±2.2

±4

0.4

±2.2

±4

μA/V

PSRR

S

l

I

Supply Current per Ampliﬁer

0.3

0.±2±

0.6

0.3

0.38

0.43

mA

S

l

I

Maximum Output Current

R = 0Ω (Notes 7, 11)

±30

300

120

±10

6±

mA

kΩ

OUT

L

–

+

–

R

Transimpedance, ΔV /ΔI

V = V – 1.2V to V + 1.2V

OUT

660

170

30

120

20

OL

OUT IN

SR

Slew Rate

(Note 8)

±0% V to ±0% V ,

OUT

V/μs

ns

t

pd

Propagation Delay

±0

IN

+

–

100mV , Larger of t , t

P-P

pd pd

BW

–3dB Bandwidth

Settling Time

<1dB Peaking, A = 1

10

200

40

7.±

300

±0

MHz

ns

V

t

s

To 0.1% of V

, V = 2V

FINAL STEP

t , t

Small-Signal Rise and Fall Time 10% to 90%, V

= 100mV

P-P

ns

f

r

OUT

HD2

HD3

2nd Harmonic Distortion

3rd Harmonic Distortion

f = 1MHz, V

= 2V

–40

–4±

––4±

–4±

dBc

OUT

P-P

Note 1: Stresses beyond those listed under Absolute Maximum Ratings

may cause permanent damage to the device. Exposure to any Absolute

Maximum Rating condition for extended periods may affect device

reliability and lifetime.

Note 2: As long as output current and junction temperature are kept

below the absolute maximum ratings, no damage to the part will occur.

Depending on the supply voltage, a heat sink may be required.

from increased copper area attached to the exposed pad.

T is calculated from the ambient temperature T and the power

J

A

dissipation PD according to the following formula:

T = T + (P • θ

)

JA

J

A

D

The maximum power dissipation can be calculated by:

2

P

= (V • I

) + (V /2) /R

D(MAX)

S

S(MAX)

S

LOAD

Note 6: For PSRR and –IPSRR testing, the current into the I pin is

SET

Note 3: The LT6210C/LT6211C is guaranteed functional over the operating

temperature range of –40°C to 8±°C.

constant, maintaining a consistent LT6210/LT6211 quiescent bias point.

A graph of PSRR vs Frequency is included in the Typical Performance

Note 4: The LT6210C/LT6211C is guaranteed to meet speciﬁed

performance from 0°C to 70°C. The LT6210C/LT6211C is designed,

characterized and expected to meet speciﬁed performance from –40°C and

8±°C but is not tested or QA sampled at these temperatures. The LT6210I/

LT6211I is guaranteed to meet speciﬁed performance from –40°C to 8±°C.

–

Characteristics showing +PSRR and –PSRR with R connecting I to

SET

ground.

Note 7: While the LT6210 and LT6211 circuitry is capable of signiﬁcant

output current even beyond the levels speciﬁed, sustained short-

circuit current exceeding the Absolute Maximum Rating of ±80mA may

permanently damage the device.

Note 8: This parameter is guaranteed to meet speciﬁed performance

through design and characterization. It is not production tested.

Note 9: Differential gain and phase are measured using a Tektronix

TSG120YC/NTSC signal generator and a Tektronix 1780R Video

Measurement Set. The resolution of this equipment is 0.1% and 0.1°. Five

identical ampliﬁer stages were cascaded giving an effective resolution of

0.02% and 0.02°.

Note 10: Input voltage range on ±±V dual supplies is guaranteed by

CMRR. On 3V single supply it is guaranteed by design and by correlation

to the ±±V input voltage range limits.

Note 5: The LT6210 with no metal connected to the V pin has a θ of

JA

230°C/W, however, thermal resistances vary depending upon the amount

of PC board metal attached to Pin 2 of the device. With the LT6210

2

mounted on a 2±00mm 3/32" FR-4 board covered with 2oz copper on

2

both sides and with just 20mm of copper attached to Pin 2, θ drops to

JA

160°C/W. Thermal performance can be improved even further by using a

4-layer board or by attaching more metal area to Pin 2.

2

Thermal resistance of the LT6211 in MSOP-10 is speciﬁed for a 2±00mm

3/32" FR-4 board covered with 2oz copper on both sides and with 100mm

of copper attached to Pin ±. Its performance can also be increased with

additional copper much like the LT6210.

2

To achieve the speciﬁed θ of 43°C/W for the LT6211 DFN-10, the

JA

Note 11: This parameter is tested by forcing a ±0mV differential voltage

between the inverting and noninverting inputs.

62101fb

exposed pad must be soldered to the PCB. In this package, θ will beneﬁt

JA

6

LT6210/LT6211

TYPICAL AC PERFORMANCE

I (mA) per

SMALL-SIGNAL

–3dB BW, <1dB PEAKING (MHz)

SMALL-SIGNAL

0.1dB BW (MHz)

S

V (V)

S

Ampliﬁer

R

(Ω)

A

V

R (Ω)

L

R (Ω)

F

R (Ω)

G

SET

±±

6

20k

1

1±0

1k

1200

887

—

887

698

—

200

160

140

100

80

30

20

1±

2

20k

±6k

1M

0

2

–1

1

±±

6

698

±±

3

1690

1100

1200

13.7k

11k

±±

3

2

1100

1200

—

±±

3

–1

1

±±

0.3

6

10

±±

2

1k

11k

10k

—

10

2

±±

–1

1

1k

10k

10

1.8

20

1±

2

3, 0

1±0

1k

1100

887

120

100

70

6

0

2

887

806

—

6

0

–1

1

806

3

10k

270k

1±40

1270

1200

13k

3

2

1270

1200

—

60

3

–1

1

60

0.3

7.±

7

2

1k

9.31k

10k

9.31k

10k

1.±

–1

1k

7

TYPICAL PERFORMANCE CHARACTERISTICS

Supply Current per Ampliﬁer vs

Temperature

Supply Current per Ampliﬁer vs

Temperature

Supply Current per Ampliﬁer vs

Temperature

7.±

7.0

6.±

6.0

±.±

±.0

4.±

4.00

3.7±

3.±0

3.2±

3.00

2.7±

2.±0

2.2±

2.00

400

380

360

340

320

300

280

260

240

220

200

R

L

= ∞

R = ∞

L

R

L

= ∞

V

= ±±V

S

V

= ±±V

S

V

= ±1.±V

R

SET

= 1M TO GND

S

R

SET

= 20k TO GND

–

R

= 10k TO V

SET

V

= ±1.±V

SET

S

V

= ±1.±V

SET

S

V

= ±±V

SET

–

S

–

R

= 0Ω TO V

R

= 270k TO V

R

= ±6k TO GND

±0

TEMPERATURE (°C)

100 12±

–2±

0

2±

±0

7±

12±

–±0 –2±

0

2±

7±

–±0

100

–±0

0

2±

±0

7± 100 12±

–2±

TEMPERATURE (°C)

6210 G01

6210 G02

6210 G03

62101fb

7

LT6210/LT6211

TYPICAL PERFORMANCE CHARACTERISTICS ^{(Supply Current Is Measured Per Ampliﬁer)}

Input Noise Spectral Density

(I_S= 6mA per Ampliﬁer)

Input Noise Spectral Density

(I_S= 3mA per Ampliﬁer)

Input Noise Spectral Density

(I_S= 300μA per Ampliﬁer)

100

10

1

100

10

1

100

10

1

V

S

= ±±V

= 1k

= 2±°C

V

= ±±V

= 1±0Ω

= 2±°C

V

= ±±V

S

L

S

L

R

L

R

T

R

T

= 1±0ꢀ

= 2±°C

–i

T

A

n

A

–i

n

e

n

+i

n

e

n

e

n

–i

n

+i

n

+i

n

0.1

0.001

0.1

0.001

0.01

0.1

1

10

100

0.001

0.01

0.1

1

10

100

0.01

0.1

1

10

100

FREQUENCY (kHz)

62101GO4

62101GO±

62101GO6

Input Offset Voltage vs Input

Common Mode Voltage

Input Common Mode Range vs

Temperature

Input Common Mode Range vs

Temperature

20

1±

±.0

4.±

4.0

1.±

1.0

I

R

= 300μA

= 13.7k

L

S

F

I

R

= 300μA

= 13k

L

S

F

= 1k

10

I

R

= 300μA

= 13.7k

L

S

F

0.±

±

= 1k

I

R

= 6mA

I

R

= 3mA

I

R

= 6mA

I

R

= 3mA

S

F

S

F

S

F

S

F

I

R

= 3mA

S

F

= 1200Ω

= 1690Ω

= 1±0Ω

= 1100Ω

= 1±40Ω

= 1±0Ω

0

= 1690Ω

= 1±0Ω

L

= 1±0Ω

L

–±

–4.0

–4.±

–±.0

–0.±

–1.0

–1.±

–10

–1±

–20

V

A

= ±±V

= 1

V

A

T

= ±±V

= 1

V

A

= ±1.±V

= 1

S

V

S

V

A

S

V

I

R

= 300μA

= 13.7k

= 1k

I

R

= 300μA

I

R

= 6mA

S

F

L

S

F

S

F

= 13k

= 1k

= 1200Ω

= 1±0Ω

CMRR > 48dB

TYPICAL PART

= 2±°C

CMRR >46dB

L

TYPICAL PART

±0

100 12±

±0

100 12±

–±0 –2±

0

2±

7±

–±0 –2±

0

2±

7±

–± –4 –3 –2 –1

0

1

2

3

4

±

TEMPERATURE (°C)

INPUT COMMON MODE VOLTAGE (V)

62101 G08

62101 G09

62101 G07

Output Voltage Swing vs

Temperature

Output Voltage Swing vs

Temperature

Output Voltage Swing vs I_LOAD

±.0

4.8

4.6

4.4

1.±

1.4

1.3

1.2

1.1

±.0

4.8

4.6

4.4

4.2

4.0

3.8

3.6

3.4

3.2

3.0

OUTPUT HIGH

I

= 3mA

= 6mA

OUTPUT HIGH

S

I

= 6mA

L

S

I

= 300μA

= 1k

S

L

I

= 300μA

= 1k

S

L

R

= 1k

I

= 6mA

L

R

I

= 6mA

L

S

R

= 1±0Ω

R

= 100Ω

V

= ±±V

CM

OS

S

V

= ±1.±V

S

V

= 0V

I = 300μA

S

CM

ΔV = ±0mV

–1.1

–1.2

–1.3

–1.4

–1.±

ΔV = ±0mV

OS

–4.4

–4.6

–4.8

–±.0

I

= 6mA

L

S

I

= 6mA

L

S

R

= 1±0Ω

R

= 100Ω

I

= 300μA

= 1k

S

L

I

= 300μA

I

= 6mA

= 1k

S

L

V

= ±±V

S

R

= 1k

–2±

R

L

= 0V

CM

ΔV = ±0mV

OS

OUTPUT LOW

2± ±0

TEMPERATURE (°C)

T

= 2±°C

A

–2±

0

2±

±0

7±

12±

0

7±

12±

20

LOAD CURRENT (mA)

–±0

100

–±0

100

0

10

30

40

±0

60 70

TEMPERATURE (°C)

6210 G10

6210 G11

6210 G12

62101fb

8

LT6210/LT6211

TYPICAL PERFORMANCE CHARACTERISTICS ^{(Supply Current Is Measured Per Ampliﬁer)}

Output Voltage Swing vs I_LOAD

–3.0

–3.2

–3.4

–3.6

–3.8

–4.0

–4.2

–4.4

–4.6

–4.8

–±.0

V

= ±±V

= 0V

OS

= 2±°C

V

= ±1.±V

= 0V

CM

S

CM

S

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0

–0.1

–0.3

–0.±

–0.7

–0.9

–1.1

–1.3

–1.±

ΔV = ±0mV

OS

I

= 3mA

= 6mA

S

T

T = 2±°C

A

I

= 300μA

S

I

= 300μA

S

V

= ±1.±V

S

I

= 300μA

S

= 0V

CM

I

= 3mA

= 6mA

S

I

= 3mA

= 6mA

ΔV = ±0mV

S

OS

T

= 2±°C

A

20

LOAD CURRENT (mA)

20

LOAD CURRENT (mA)

20

LOAD CURRENT (mA)

0

10

30

40

±0

60 70

0

40

±0

60 70

0

40

±0

60 70

10

30

10

30

6210 G13

6210 G14

6210 G1±

CMRR and PSRR vs Frequency

(I_S= 6mA per Ampliﬁer)

CMRR and PSRR vs Frequency

(I_S= 3mA per Ampliﬁer)

CMRR and PSRR vs Frequency

(I_S= 300μA per Ampliﬁer)

70

60

±0

40

30

20

10

0

70

60

±0

40

30

20

10

0

70

60

±0

40

30

20

10

0

V

= ±±V

= 1±0Ω

= 2±°C

V

= ±±V

= 1±0Ω

= 2±°C

V

S

= ±±V

= 1k

= 2±°C

S

L

S

L

–PSRR

+PSRR

R

–PSRR

+PSRR

R

L

T

A

+PSRR

CMRR

0.001

0.01

0.1

1

10

100

0.001

0.01

0.1

1

10

100

0.001

0.01

0.1

1

10

FREQUENCY (MHz)

6210 G18

6210 G16

6210 G17

Frequency Response vs Closed

Loop Gain (I_S= 300μA per

Ampliﬁer)

Frequency Response vs Closed

Loop Gain (I_S= 6mA per Ampliﬁer)

Frequency Response vs Closed

Loop Gain (I_S= 3mA per Ampliﬁer)

9

6

9

6

9

6

A

= 2

A

= 2

A

= 2

= R = 11k

V

R

= R = 1100Ω

R

= R = 887Ω

R

F

G

F

G

F

G

3

A

= 1

= 13.7k

V

F

R

0

A

= 1

V

A

= –1

V

R

= 1.2k

F

A

= –1

V

= ±±V

= 1±0Ω

= 2±°C

V

= ±±V

= 1±0Ω

= 2±°C

V

= ±±V

= 1±0Ω

= 2±°C

S

L

S

L

R

= R = 1200Ω

G

S

L

F

R

= R = 10k

G

–3

F

R

T

R

T

R

T

A

V

= –1

A

= 1

A

V

R

F

= R = 698Ω

G

V

= 100mV

V

= 100mV

V

= 100mV

OUT

P-P

OUT

P-P

R

= 1690Ω

OUT

P-P

1

F

–6

0.1

1

10

100

1000

0.1

1

10

100

1000

0.1

10

100

FREQUENCY (MHz)

6210 G19

6210 G20

6210 G21

62101fb

9

LT6210/LT6211

TYPICAL PERFORMANCE CHARACTERISTICS ^{(Supply Current Is Measured Per Ampliﬁer)}

2nd and 3rd Harmonic Distortion vs

Frequency (I_S= 6mA per Ampliﬁer)

2nd and 3rd Harmonic Distortion vs

Frequency (I_S= 3mA per Ampliﬁer)

2nd and 3rd Harmonic Distortion vs

Frequency (I_S= 300μA per Ampliﬁer)

0

–10

–20

–30

–40

–±0

–60

–70

–80

–90

–100

0

–10

–20

–30

–40

–±0

–60

–70

–80

–90

–100

0

–10

–20

–30

–40

–±0

–60

–70

–80

–90

–100

V

= ±±V

G

V

= ±±V

G

V

= ±±V

S

F

S

F

S

R

V

= R = 11k

R

V

= R = 887Ω

R

V

= R = 1.1k

F G

= 2V

P-P

OUT

P-P

OUT

P-P

OUT

R

= 1k

R

= 1±0Ω

R

= 1±0Ω

L

T

= 2±°C

T

= 2±°C

T

= 2±°C

A

HD2

HD3

HD2

HD3

0.01

0.1

1

10

0.01

0.1

1

10

100

0.01

0.1

1

10

100

FREQUENCY (MHz)

6210 G24

6210 G22

6210 G23

Maximum Undistorted Output

Sinusoid vs Frequency

LT6211 Channel Separation

vs Frequency

Output Impedance vs Frequency

10

9

8

7

6

±

4

3

2

1

0

120

100

80

60

40

20

0

1000

100

V

S

= ±±V

V

A

T

= ±±V

= 2

= 2±°C

S

V

A

HD2, HD3 <–40dB

A

= 2

V

T

= 2±°C

A

I

R

= 300μA

S

F

R

L

= ∞

I

R

= 6mA

S

F

= R = 11k

G

= R = 887Ω

G

= 1k

L

= 1±0Ω

R

= 1±0Ω

L

10

1

L

I

R

= 6mA

S

F

= R = 887Ω

I

R

= 300μA

G

S

F

= 1±0Ω

V

I

= ±±V

= R = 11k

L

S

G

= 6mA

= 1k

S

L

R

= R = 887Ω

F

G

T

= 2±°C

1

A

0.1

1

10

100

0.1

10

FREQUENCY (MHz)

±00

100

0.1

1

10

FREQUENCY (MHz)

100

±00

FREQUENCY (MHz)

6210 G27

6210 G26

6210 G2±

Maximum Capacitive Load vs

Output Series Resistor

Maximum Capacitive Load vs

Feedback Resistor

Overshoot vs Capacitive Load

70

60

±0

40

30

20

10

0

±0

4±

40

10000

1000

100

V

= ±±V

V

= ±±V

S

AC PEAKING < 3dB

OVERSHOOT < 10%

I

R

= 3mA

S

F

V

I

= 100mV

V

I

= 100mV

OUT

P-P

= R = 1100Ω

OUT

S

F

L

P-P

G

= 6mA

S

= 1±0Ω

L

R

T

= R

R

T

= R = 887Ω

G

L

F

G

3±

30

I

R

= 300μA

= 1±0Ω

= 2±°C

= ∞

S

F

= R = 11k

= 2±°C

G

A

= 1k

L

2±

20

1±

10

±

V

A

V

= ±±V

= 2

OUT

T = 2±°C

A

S

V

I

R

= 6mA

S

F

= R = 887Ω

= 100mV

G

P-P

= 1±0Ω

100

L

0

10

1000

10000

10

100

CAPACITIVE LOAD (pF)

1000

800 1000 1200 1400 1600 1800 2000

FEEDBACK RESISTANCE (Ω)

CAPACITIVE LOAD (pF)

6210 G30

6210 G29

6210 G28

62101fb

10

LT6210/LT6211

TYPICAL PERFORMANCE CHARACTERISTICS ^{(Supply Current Is Measured Per Ampliﬁer)}

–3dB Small-Signal Bandwidth

vs Supply Current

1MHz 2nd and 3rd Harmonic

Distortion vs Supply Current

Slew Rate vs Supply Current

1000

100

10

–30

–40

–±0

–60

–70

–80

1000

900

800

700

600

±00

400

300

200

100

0

A

V

T

= 2

OUT

= 2±°C

V

A

V

T

= ±±V

V

A

V

T

= ±±V

= 2

OUT

= 2±°C

V

S

V

S

V

= 100mV

= 2

= 2V

P-P

= 7V

A

OUT

P-P

= 2±°C

A

V

= ±±V

S

RISING

EDGE RATE

HD2

V

= ±1.±V

S

FALLING

EDGE RATE

HD3

1

10

0.1

1

0.1

1

10

0.1

1

SUPPLY CURRENT PER AMPLIFIER (mA)

10

SUPPLY CURRENT PER AMPLIFIER (mA)

62101 G33

62101 G31

62101 G32

Small-Signal Transient Response

(I_S= 6mA per Ampliﬁer)

Small-Signal Transient Response

(I_S= 3mA per Ampliﬁer)

Small-Signal Transient Response

(I_S= 300μA per Ampliﬁer)

OUTPUT

(±0mV/DIV)

OUTPUT

(±0mV/DIV)

OUTPUT

(±0mV/DIV)

62101 G34

62101 G36

62101 G3±

V

R

= ±±V

TIME (10ns/DIV)

V

R

= ±±V

V

R

= ±±V

S

TIME (10ns/DIV)

TIME (100ns/DIV)

S

= ±2±mV

= R = 1.1k

G

= ±2±mV

= R = 11k

G

IN

= R = 887Ω

F

G

F

= 20k TO GND

= 1±0Ω

= ±6k TO GND

= 1±0Ω

= 1M TO GND

= 1k

SET

L

Large-Signal Transient Response

(I_S= 6mA per Ampliﬁer)

Large-Signal Transient Response

(I_S= 3mA per Ampliﬁer)

Large-Signal Transient Response

(I_S= 300μA per Ampliﬁer)

OUTPUT

(2V/DIV)

OUTPUT

(2V/DIV)

OUTPUT

(2mV/DIV)

62101 G37

62101 G38

62101 G39

V

R

= ±±V

V

R

= ±±V

V

R

= ±±V

TIME (10ns/DIV)

TIME (100ns/DIV)

S

= ±1.7±V

= R = 1.1k

G

= ±1.7±V

= R = 11k

G

IN

= R = 887Ω

F

G

F

= 20k TO GND

= 1±0Ω

= ±6k TO GND

= 1±0Ω

= 1M TO GND

= 1k

SET

L

62101fb

11

LT6210/LT6211

APPLICATIONS INFORMATION

Setting the Quiescent Operating Current (I Pin)

Input Considerations

SET

The inputs of the LT6210/LT6211 are protected by back-

to-back diodes. If the differential input voltage exceeds

1.4V, the input current should be limited to less than the

absolute maximum ratings of ±10mA. In normal opera-

tion, the differential voltage between the inputs is small,

so the ±1.4V limit is generally not an issue. ESD diodes

protect both inputs, so although the part is not guaranteed

to function outside the common mode range, input volt-

ages that exceed a diode beyond either supply will also

require current limiting to keep the input current below

the absolute maximum of ±10mA.

The quiescent bias point of the LT6210/LT6211 is SET

with either an external resistor from the I

pin to a

SET

lower potential or by drawing a current out of the I

SET

pin. However, the I pin is not designed to function as a

SET

shutdown. TheLT6211usestwoentirelyindependentbias

networks, so while each channel can be programmed for

a different supply current, neither I

pin should be left

SET

unconnected. A simpliﬁed schematic of the internal bias-

ing structure can be seen in Figure 1. Figure 2 illustrates

the results of varying R on 3V and ±±V supplies. Note

SET

that shorting the I

pin under 3V operation results in

SET

a quiescent bias of approximately 6mA. Attempting to

bias the LT6210/LT6211 at a current level higher than

6mA by using a smaller resistor may result in instability

and decreased performance. However, internal circuitry

clamps the supply current of the part at a safe level of

approximately 1±mA in case of accidental connection of

Feedback Resistor Selection

The small-signal bandwidth of the LT6210/LT6211 is set

by the external feedback resistors and the internal junc-

tion capacitances. As a result, the bandwidth is a function

of the quiescent supply current, the supply voltage, the

valueofthefeedbackresistor, theclosed-loopgainandthe

load resistor. Refer to the Typical AC Performance table

for more information.

the I pin directly to a negative potential.

SET

+

V

6

600Ω

8k

600Ω

Layout and Passive Components

As with all high speed ampliﬁers, the LT6210/LT6211

require some attention to board layout. Low ESL/ESR

bypass capacitors should be placed directly at the positive

and negative supply (0.1μF ceramics are recommended).

For best transient performance, additional 4.7μF tantal-

ums should be added. A ground plane is recommended

and trace lengths should be minimized, especially on the

inverting input lead.

TO

BIAS

CONTROL

±

I

6210 F01

SET

Figure 1. Internal Bias Setting Circuitry

V

R

= ±±V

S

TO GND

10

SET

Capacitance on the Inverting Input

Current feedback ampliﬁers require resistive feedback

from the output to the inverting input for stable operation.

Capacitance on the inverting input will cause peaking in

the frequency response and overshoot in the transient

response. Take care to minimize the stray capacitance at

the inverting input to ground and between the output and

the inverting input. If signiﬁcant capacitance is unavoid-

able in a given application, an inverting gain conﬁguration

should be considered. When conﬁgured inverting, the

ampliﬁer inputs do not slew and the effect of parasitics

V

= 3V

SET

S

R

TO GND

1

T

= 2±°C

= ∞

A

L

R

0.1

0.01

0.1

1

10

100

1000

R

PROGRAMMING RESISTOR (kΩ)

SET

6210 F02

Figure 2. Setting R_SETto Control I_S

is greatly reduced.

62101fb

12

LT6210/LT6211

APPLICATIONS INFORMATION

Capacitive Loads

is that of the output stage. For gains less than 2 in the

noninverting mode, the overall slew rate is limited by the

input stage. The input slew rate of the LT6210/LT6211 on

The LT6210/LT6211 are stable with any capacitive load.

Although peaking and overshoot may result in the AC

transientresponse,theampliﬁer’scompensationdecreases

bandwidthwithincreasingoutputcapacitiveloadtoensure

stability. Tomaintainaresponsewithminimalpeaking, the

feedbackresistorcanbeincreasedatthecostofbandwidth

as shown in the Typical Performance Characteristics.

Alternatively, a small resistor (±Ω to 3±Ω) can be put in

series with the output to isolate the capacitive load from

theampliﬁeroutput.Thishastheadvantagethattheampli-

ﬁer bandwidth is only reduced when the capacitive load

is present. The disadvantage of this technique is that the

gain is a function of the load resistance.

±±V supplies with an R

resistor of 20k (I = 6mA) is

SET

S

approximately 600V/μs and is set by internal currents and

capacitances. The output slew rate is additionally con-

strained by the value of the feedback resistor and internal

capacitance. At a gain of 2 with 887Ω feedback and gain

resistors, ±±V supplies and the same biasing as above,

the output slew rate is typically 700V/μs. Larger feedback

resistors, lower supply voltages and lower supply current

levelswillallreduceslewrate.Inputslewratessigniﬁcantly

exceedingtheoutputslewcapabilitycanactuallydecrease

slew performance in a positive gain conﬁguration; the

cleanest transient response will be obtained from input

signals with slew rates slower than 1000V/μs.

Power Supplies

The LT6210/LT6211 will operate on single supplies from

3V to 12V and on split supplies from ±1.±V to ±6V. If split

supplies of unequal absolute value are used, input offset

voltageandinvertinginputcurrentwillshiftfromthevalues

speciﬁedintheElectricalCharacteristicstable.Inputoffset

voltage will shift 2mV and inverting input current will shift

0.±μA for each volt of supply mismatch.

Output Swing and Drive

The output stage of the LT6210/LT6211 consists of a pair

ofclass-ABbiasedcommonemittersthatenabletheoutput

to swing rail-to-rail. Since the ampliﬁers can potentially

deliveroutputcurrentswellbeyondthespeciﬁedminimum

short-circuit current, care should be taken not to short the

output of the device indeﬁnitely. Attention must be paid to

keep the junction temperature of the IC below the absolute

maximum rating of 1±0°C if the output is used to drive

low impedance loads. See Note ± for details. Additionally,

the output of the ampliﬁer has reverse-biased ESD diodes

connected to each supply. If the output is forced beyond

eithersupply,largecurrentswillﬂowthroughthesediodes.

If the current is limited to 80mA or less, no damage to

the part will occur.

Slew Rate

Unlike a traditional voltage feedback op amp, the slew rate

of a current feedback ampliﬁer is not independent of the

ampliﬁer gain conﬁguration. In a current feedback ampli-

ﬁer, both the input stage and the output stage have slew

rate limitations. In the inverting mode, and for gains of 2

or more in the noninverting mode, the signal amplitude

between the input pins is small and the overall slew rate

TYPICAL APPLICATIONS

3V Cable Driver with Active Termination

controlledoutputimpedancefromtheline-drivingampliﬁer.

Figure 3 shows the LT6210 using this “active termination”

schemeonasingle3Vsupply. TheampliﬁerisAC-coupled

andinaninvertinggainconﬁgurationtomaximizetheinput

Driving back-terminated cables on single supplies usually

results in very limited signal amplitude at the receiving

end of the cable. However, positive feedback can be used

to reduce the size of the series back termination resistor,

thereby decreasing the attenuation between the series

and shunt termination resistors while still maintaining

signal range. The gain from V to the receiving end of the

IN

cable, V , is set to –1. The effective impedance looking

OUT

into the ampliﬁer circuit from the cable is ±0Ω throughout

the usable bandwidth.

62101fb

13

LT6210/LT6211

TYPICAL APPLICATIONS

The response of the cable driver with a 1MHz sinusoid is

resistor and has a full signal 1V bandwidth of ±0MHz.

P-P

shown in Figure 4. The circuit is capable of transmitting

Smallsignal–3dBbandwidthextendsfrom1kHzto±6MHz

a 1.±V

undistorted sinusoid to the ±0Ω termination

with the selected coupling capacitors.

P-P

V

IN

1V/DIV

3V

2k

1%

1.3k

1%

2k

1%

V

A

3V

R

1±Ω

1%

1V/DIV

SER

4

3

6

+

–

2.2μF

1

249Ω

1%

LT6210

±

V

OUT

TERM

2.2μF

V

R

OUT

1V/DIV

2

A

V

IN

±0Ω

6210 F03

1±4Ω

1%

3300pF

NPO

200ns/DIV

6210 F04

Figure 4. Response of Circuit at 1MHz

Figure 3. 3V Cable Driver with Active Termination

SIMPLIFIED SCHEMATIC

+

V

6

+

V

+IN

3

–IN

4

OUT

1

OUTPUT BIAS

CONTROL

600Ω

8k

600Ω

–

V

SUPPLY

CURRENT

CONTROL

±

–

V

I

SET

2

6210 SS

PACKAGE DESCRIPTION

DD Package

10-Lead Plastic DFN (3mm × 3mm)

(Reference LTC DWG # 0±-08-1699)

R = 0.11±

TYP

6

0.38 ± 0.10

10

0.67± ±0.0±

3.±0 ±0.0±

2.1± ±0.0± (2 SIDES)

1.6± ±0.0±

3.00 ±0.10

(4 SIDES)

1.6± ± 0.10

(2 SIDES)

PIN 1

TOP MARK

(SEE NOTE 6)

PACKAGE

OUTLINE

(DD) DFN 1103

±

1

0.2± ± 0.0±

0.±0 BSC

0.7± ±0.0±

0.200 REF

0.2± ± 0.0±

0.±0

BSC

2.38 ±0.10

(2 SIDES)

2.38 ±0.0±

(2 SIDES)

0.00 – 0.0±

BOTTOM VIEW—EXPOSED PAD

RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS

NOTE:

1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-2).

CHECK THE LTC WEBSITE DATA SHEET FOR CURRENT STATUS OF VARIATION ASSIGNMENT

2. DRAWING NOT TO SCALE

4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE

MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.1±mm ON ANY SIDE

±. EXPOSED PAD SHALL BE SOLDER PLATED

6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE

TOP AND BOTTOM OF PACKAGE

3. ALL DIMENSIONS ARE IN MILLIMETERS

62101fb

14

LT6210/LT6211

PACKAGE DESCRIPTION

MS Package

10-Lead Plastic MSOP

(Reference LTC DWG # 0±-08-1661 Rev E)

3.00 ± 0.102

(.118 ± .004)

(NOTE 3)

0.889 ± 0.127

(.03± ± .00±)

0.497 ± 0.076

(.0196 ± .003)

10 9

8

7 6

REF

DETAIL “A”

0.2±4

±.23

3.00 ± 0.102

(.118 ± .004)

(NOTE 4)

3.20 – 3.4±

(.206)

4.90 ± 0.1±2

(.193 ± .006)

(.010)

(.126 – .136)

MIN

0° – 6° TYP

GAUGE PLANE

0.±0

(.0197)

BSC

0.30± ± 0.038

(.0120 ± .001±)

TYP

0.±3 ± 0.1±2

(.021 ± .006)

1

2

3

4 ±

RECOMMENDED SOLDER PAD LAYOUT

0.86

(.034)

REF

1.10

(.043)

MAX

DETAIL “A”

0.18

(.007)

SEATING

PLANE

0.17 – 0.27

(.007 – .011)

TYP

NOTE:

0.1016 ± 0.0±08

(.004 ± .002)

1. DIMENSIONS IN MILLIMETER/(INCH)

2. DRAWING NOT TO SCALE

0.±0

(.0197)

BSC

MSOP (MS) 0307 REV E

3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.

MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.1±2mm (.006") PER SIDE

4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.

INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.1±2mm (.006") PER SIDE

±. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX

S6 Package

6-Lead Plastic TSOT-23

(Reference LTC DWG # 0±-08-1636)

0.62

MAX

0.9±

REF

2.90 BSC

(NOTE 4)

1.22 REF

1.4 MIN

1.±0 – 1.7±

(NOTE 4)

2.80 BSC

3.8± MAX 2.62 REF

PIN ONE

RECOMMENDED SOLDER PAD LAYOUT

PER IPC CALCULATOR

0.30 – 0.4± TYP

± PLCS (NOTE 3)

0.9± BSC

0.80 – 0.90

0.20 BSC

DATUM ‘A’

0.01 – 0.10

1.00 MAX

0.30 – 0.±0 REF

1.90 BSC

0.09 – 0.20

(NOTE 3)

NOTE:

S± TSOT-23 0302 REV B

1. DIMENSIONS ARE IN MILLIMETERS

2. DRAWING NOT TO SCALE

3. DIMENSIONS ARE INCLUSIVE OF PLATING

4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR

±. MOLD FLASH SHALL NOT EXCEED 0.2±4mm

6. JEDEC PACKAGE REFERENCE IS MO-193

62101fb

Information furnished by Linear Technology Corporation is believed to be accurate and reliable.

However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-

tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.

15

LT6210/LT6211

TYPICAL APPLICATION

Line Driver with Power Saving Mode

of the LT6210 in this circuit increases from about 40MHz

in low power mode to over 200MHz in full speed mode,

as illustrated in Figure 6. Other AC specs also improve

signiﬁcantly at the higher current setting. The following

In applications where low distortion or high slew rate are

desirable but not necessary at all times, it may be possible

todecreasetheLT6210orLT6211’squiescentcurrentwhen

the higher power performance is not required. Figure ±

illustrates a method of setting quiescent current with a

FET switch. In the ±V dual supply case pictured, shorting

table shows harmonic distortion at 1MHz with a 2V

sinusoid at the two selected current levels.

P-P

Harmonic Distortion

the I

pin through an effective 20k to ground sets the

LOW POWER

–±3dBc

–46dBc

FULL SPEED

–68dBc

–77dBc

SET

supply current to 6mA, while the 240k resistor at the I

HD2

HD3

HD2

HD3

SET

pin with the FET turned off sets the supply current to ap-

proximately1mA.Thefeedbackresistorof4.02kisselected

to minimize peaking in low power mode. The bandwidth

3

2

R3

±V

4.02k

FULL

1

SPEED

MODE

4

0

–

6

I

= 6mA

S

1

–1

–2

–3

–4

–±

–6

V

LT6210

±

OUT

V

LOW POWER

MODE

IN

3

R

LOAD

2

+

1±0Ω

I

= 1mA

S

–±V

HS/LP

R2

22k

R1

240k

T

= 2±°C

OUT

A

V

= 100mV

P-P

2N7002

0

1

10

100

1000

6210 F0±

FREQUENCY (MHz)

6210 F06

Figure 5. Line Driver with Low Power Mode

Figure 6. Frequency Response for Full

Speed and Low Power Mode

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62101fb

LT 0809 REV B • PRINTED IN USA

LinearTechnology Corporation

1630 McCarthy Blvd., Milpitas, CA 9±03±-7417

16

●

(408) 432-1900 FAX: (408) 434-0±07 www.linear.com


型号：	LT6210IS6#PBF
厂家：	Linear
描述：	LT6210 - Single Programmable Supply Current, R-R Output, Current Feedback Amplifiers; Package: SOT; Pins: 6; Temperature Range: -40°C to 85°C 放大器光电二极管商用集成电路
文件：	总16页 (文件大小：276K)
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LT6210IS6#PBF [Linear]

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