LTC1090AMJ [Linear]
Single Chip 10-Bit Data Acquisition System; 单芯片10位数据采集系统型号: | LTC1090AMJ |
厂家: | Linear |
描述: | Single Chip 10-Bit Data Acquisition System |
文件: | 总28页 (文件大小:343K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LTC1090
Single Chip 10-Bit Data
Acquisition System
U
FEATURES
DESCRIPTIO
The LTC®1090 is a data acquisition component which
contains a serial I/O successive approximation A/D con-
verter. It uses LTCMOSTM switched capacitor technology
to perform either 10-bit unipolar, or 9-bit plus sign bipolar
A/D conversions. The 8-channel input multiplexer can be
configured for either single ended or differential inputs (or
combinations thereof). An on-chip sample and hold is
included for all single ended input channels.
■
Software Programmable Features:
Unipolar/Bipolar Conversions
4 Differential/8 Single Ended Inputs
MSB or LSB First Data Sequence
Variable Data Word Length
■
Built-In Sample and Hold
Single Supply 5V, 10V or ±5V Operation
Direct 4 Wire Interface to Most MPU Serial Ports and
All MPU Parallel Ports
30kHz Maximum Throughput Rate
■
■
The serial I/O is designed to be compatible with industry
standard full duplex serial interfaces. It allows either
MSB or LSB first data and automatically provides 2’s
complement output coding in the bipolar mode. The
output data word can be programmed for a length of 8, 10,
12 or 16 bits. This allows easy interface to shift registers
and a variety of processors.
■
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KEY SPECIFICATIO S
■
Resolution: 10 Bits
■
Total Unadjusted Error (LTC1090A): ±1/2LSB Max
■
Conversion Time: 22µs
The LTC1090A is specified with total unadjusted error
(including the effects of offset, linearity and gain errors)
less than ±0.5LSB.
■
Supply Current: 2.5mA Max, 1.0mA Typ
, LTC and LT are registered trademarks of Linear Technology Corporation.
LTCMOS is a trademark of Linear Technology Corp.
TheLTC1090isspecifiedwithoffsetandlinearitylessthan
±0.5LSB but with a gain error limit of ±2LSB for
applications where gain is adjustable or less critical.
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TYPICAL APPLICATIO
FOR 8051 CODE SEE
APPLICATIONS INFORMATION
SECTION
LTC1090
MPU
(e.g., 8051)
Linearity Plot
DIFFERENTIAL
INPUT
1.0
5V
BIPOLAR INPUT
0.5
0.0
5V
–5V
D
P1.1
P1.2
P1.3
P1.4
OUT
D
IN
T
SCLK
CS
–0.5
–1.0
UNIPOLAR
INPUTS
SERIAL DATA
LINK
0
512
1024
OUTPUT CODE
LTC1090 • TA02
(+)
(–)
– UNIPOLAR
INPUT
LTC1090 • TA01
–5V
1090fc
1
LTC1090
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ABSOLUTE AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
(Notes 1 and 2)
TOP VIEW
ORDER PART
Supply Voltage (VCC) to GND or V– ................................ 12V
Negative Supply Voltage (V–) ..................... –6V to GND
Voltage:
1
2
V
CC
20
19
18
17
16
15
14
13
12
11
CH0
CH1
NUMBER
ACLK
SCLK
3
CH2
LTC1090ACN
LTC1090CN
LTC1090CSW
Analog and Reference
4
D
IN
CH3
Inputs .................................... (V–) –0.3V to VCC 0.3V
Digital Inputs ......................................... –0.3V to 12V
Digital Outputs ..............................– 0.3V to VCC 0.3V
Power Dissipation.............................................. 500mW
Operating Temperature Range
5
D
OUT
CH4
6
CS
CH5
+
7
REF
CH6
–
8
REF
CH7
–
9
V
COM
DGND
10
AGND
LTC1090AC/LTC1090C........................–40°C to 85°C
LTC1090AM/LTC1090M (OBSOLETE) ......–55°C to 125°C
Storage Temperature Range ................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec).................. 300°C
SW PACKAGE
20-LEAD PLASTIC SO WIDE
N PACKAGE
20-LEAD PDIP
T
T
= 150°C, θ = 70°C/W
JA
JMAX
JMAX
= 110°C, θ = 90°C/W
JA
LTC1090AMJ
LTC1090MJ
LTC1090ACJ
LTC1090CJ
J PACKAGE
20-LEAD CERDIP
T
= 150°C θ = 70° C/W
JMAX
JA
OBSOLETE PACKAGE
Consider the SW or N Package for Alternate Source
LTC1090 • POI01
Consult LTC Marketing for parts specified with wider operating temperature
ranges.
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RECO E DED OPERATI G CO DITIO S
LTC1090/LTC1090A
SYMBOL PARAMETER
CONDITIONS
MIN
MAX
UNITS
V
–
V
V
Positive Supply Voltage
Negative Supply Voltage
Shift Clock Frequency
A/D Clock Frequency
V = 0V
4.5
–5.5
0
10
CC
–
V
V
V
= 5V
= 5V
= 5V
0
V
CC
CC
CC
f
f
1.0
MHz
MHz
SCLK
ACLK
25°C
85°C
125°C
0.01
0.05
0.25
2.0
2.0
2.0
t
Total Cycle Time
See Operating Sequence
10 SCLK +
48 ACLK
Cycles
CYC
↓
t
t
t
Hold Time, CS Low After Last SCLK
V
V
V
= 5V
= 5V
= 5V
0
ns
ns
hCS
hDI
CC
CC
CC
↑
Hold Time, D After SCLK
150
IN
↓
Setup Time CS Before Clocking in First Address Bit (Note 9)
2 ACLK Cycles
suCS
1µs
↑
t
t
t
t
Setup Time, D Stable Before SCLK
V
V
V
V
= 5V
= 5V
= 5V
= 5V
400
127
200
44
ns
ns
ns
suDI
IN
CC
CC
CC
CC
ACLK High Time
WHACLK
WLACLK
WHCS
ACLK Low Time
CS High Time During Conversion
ACLK
Cycles
1090fc
2
LTC1090
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CO VERTER A D ULTIPLEXER CHARACTERISTICS
The ■ denotes specifications which
apply over the full operating temperature range, otherwise specifications are TA = 25°C. (Note 3)
LTC1090A
LTC1090
TYP
PARAMETER
Offset Error
CONDITIONS
(Note 4)
MIN
TYP
MAX
±0.5
±0.5
±1.0
±1.0
MIN
MAX
±0.5
±0.5
±2.0
UNITS
LSB
■
■
■
■
Linearity Error
Gain Error
(Notes 4 and 5)
(Note 4)
LSB
LSB
Total Unadjusted Error
V
= 5.000V
LSB
REF
(Notes 4 and 6)
Reference Input Resistance
Analog and REF Input Range
10
10
kΩ
V
–
(Note 7)
(V ) – 0.05V to V 0.05V
CC
On Channel Leakage Current
(Note 8)
On Channel = 5V
Off Channel = 0V
■
■
■
■
1
–1
–1
1
1
–1
–1
1
µA
On Channel = 0V
Off Channel = 5V
µA
µA
µA
Off Channel Leakage Current
(Note 8)
On Channel = 5V
Off Channel = 0V
On Channel = 0V
Off Channel = 5V
AC ELECTRICAL CHARACTERISTICS
The ■ denotes specifications which apply over the full operating
temperature range, otherwise specification are TA = 25°C. (Note 3)
LTC1090/LTC1090A
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
↓
t
t
t
t
t
t
t
t
t
Delay Time From CS to D
Analog Input Sample Time
Conversion Time
Data Valid
(Note 9)
2
ACLK Cycles
ACC
SMPL
CONV
dDO
dis
OUT
See Operating Sequence
See Operating Sequence
See Test Circuits
See Test Circuits
See Test Circuits
5
SCLK Cycles
44
ACLK Cycles
↓
Delay Time, SCLK to D
Data Valid
■
■
■
250
300
400
50
450
ns
ns
ns
ns
ns
ns
ns
OUT
↑
Delay Time, CS to D
Hi-Z
140
150
OUT
↓
Delay Time, 2nd CLK to D
Enabled
ns
en
OUT
↓
Time Output Data Remains Valid After SCLK
hDO
f
D
OUT
D
OUT
Fall Time
See Test Circuits
See Test Circuits
■
■
90
60
300
300
ns
ns
Rise Time
r
C
Input Capacitance
Analog Inputs
On Channel
Off Channel
65
5
5
pF
pF
pF
IN
Digital Inputs
1090fc
3
LTC1090
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DIGITAL A DDCELECTRICALCHARACTERISTICS
The ■ denotes specifications which apply
over the full operating temperature range, otherwise specification are TA = 25°C. (Note 3)
LTC1090/LTC1090A
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
V
V
High Level lnput Voltage
Low Level Input Voltage
High Level lnput Current
Low Level Input Current
High Level Output Voltage
V
V
V
V
= 5.25V
= 4.75V
■
■
■
■
2.0
IH
IL
CC
CC
IN
0.8
2.5
V
I
I
= V
µA
µA
IH
IL
CC
= 0V
–2.5
IN
V
V
V
= 4.75V, l = 10µA
= 4.75V, l = 360µA
4.7
4.0
V
V
OH
CC
CC
O
O
■
■
2.4
V
Low Level Output Voltage
Hi-Z Output Leakage
V
= 4.75V, l = 1.6mA
0.4
V
OL
CC
O
I
V
V
= V , CS High
■
■
3
–3
µA
µA
OZ
OUT
OUT
CC
= 0V, CS High
I
I
I
I
I
Output Source Current
Output Sink Current
Positive Supply Current
Reference Current
V
V
= 0V
–10
10
mA
mA
mA
mA
µA
SOURCE
SINK
CC
OUT
OUT
= V
CC
+
CS High, REF Open
= 5V
■
■
■
1.0
0.5
1
2.5
1.0
50
V
REF
–
REF
–
Negative Supply Current
CS High, V = –5V
–
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
below V or one diode drop above V . Be careful during testing at low
CC
V
levels (4.5V), as high level reference or analog inputs (5V) can cause
CC
Note 2: All voltage values are with respect to ground with DGND, AGND
this input diode to conduct, especially at elevated temperatures, and cause
errors for inputs near full-scale. This spec allows 50mV forward bias of
either diode. This means that as long as the reference or analog input does
not exceed the supply voltage by more than 50mV, the output code will be
correct. To achieve an absolute 0V to 5V input voltage range will therefore
require a minimum supply voltage of 4.950V over initial tolerance,
temperature variations and loading.
–
and REF wired together (unless otherwise noted).
–
Note 3: V = 5V, V + = 5V, V – = 0V, V = 0V for unipolar mode and
CC
REF
REF
–5V for bipolar mode, ACLK = 2.0MHz, SCLK = 0.5MHz unless otherwise
specified.
Note 4: These specs apply for both unipolar and bipolar modes. In bipolar
mode, one LSB is equal to the bipolar input span (2V ) divided by 1024.
REF
For example, when V = 5V, 1LSB (bipolar) = 2(5V)/1024 = 9.77mV.
Note 5: Linearity error is specified between the actual end points of the
A/D transfer curve.
Note 6: Total unadjusted error includes offset, gain, linearity, multiplexer
and hold step errors.
Note 7: Two on-chip diodes are tied to each reference and analog input
which will conduct for reference or analog input voltages one diode drop
REF
Note 8: Channel leakage current is measured after the channel selection.
Note 9: To minimize errors caused by noise at the chip select input, the
internal circuitry waits for two ACLK falling edges after a chip select falling
edge is detected before responding to control input signals. Therefore, no
attempt should be made to clock an address in or data out until the
minimum chip select setup time has elapsed.
1090fc
4
LTC1090
TEST CIRCUITS
On and Off Channel Leakage Current
Voltage Waveforms for DOUT Delay Time, tdDO
SCLK
0.8V
5V
I
t
ON
dDO
2.4V
0.4V
ON CHANNELS
A
D
OUT
I
OFF
A
Voltage Waveforms for DOUT Rise and Fall Times, tr, tf
OFF
CHANNELS
POLARITY
2.4V
D
OUT
0.4V
LTC1090 • TC01
t
t
f
r
LTC1090 • TC02
Voltage Waveforms for ten and tdis
1
2
ACLK
2.0V
CS
D
OUT
90%
2.4V
0.4V
WAVEFORM 1
(SEE NOTE 1)
t
t
dis
en
D
OUT
WAVEFORM 2
(SEE NOTE 2)
10%
NOTE 1: WAVEFORM 1 IS FOR AN OUTPUT WITH INTERNAL CONDITIONS SUCH THAT THE OUTPUT
IS HIGH UNLESS DISABLED BY THE OUTPUT CONTROL
NOTE 2: WAVEFORM 2 IS FOR AN OUTPUT WITH INTERNAL CONDITIONS SUCH THAT THE OUTPUT
IS LOW UNLESS DISABLED BY THE OUTPUT CONTROL
LTC1090 • TC03
Load Circuit for tdis and ten
Load Circuit for tdDO, tr, and tf
1.4V
TEST
POINT
5V WAVEFORM 2
3k
3k
100pF
D
OUT
D
TEST POINT
100pF
OUT
WAVEFORM 1
LTC1090 • TC04
LTC1090 • TC05
1090fc
5
LTC1090
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PI FU CTIO S
#
PIN
FUNCTION
DESCRIPTION
1-8
9
CH0 to CH7
COM
Analog Inputs
Common
The analog inputs must be free of noise with respect to AGND.
The common pin defines the zero reference point for all single ended inputs. It must be free
of noise and is usually tied to the analog ground plane.
10
11
12
13,14
15
16
17
18
19
DGND
AGND
DigitalGround
This is the ground for the internal logic. Tie to the ground plane.
AGND should be tied directly to the analog ground plane.
Tie V to most negative potential in the circuit. (Ground in single supply applications.)
The reference inputs must be kept free of noise with respect to AGND.
A logic low on this input enables data transfer.
The A/D conversion result is shifted out of this output.
The A/D configuration word is shifted into this input.
This clock synchronizes the serial data transfer.
This clock controls the A/D conversion process.
This supply must be kept free of noise and ripple by bypassing directly to the analog ground
plane.
Analog Ground
Negative Supply
Reference Inputs
Chip Select Input
Digital Data Output
Data Input
Shift Clock
A/D Conversion Clock
Positive Supply
–
–
V
–
+
REF , REF
CS
D
OUT
D
IN
SCLK
ACLK
20
V
CC
W
BLOCK DIAGRA
20
18
V
SCLK
CC
OUTPUT
16
INPUT SHIFT
REGISTER
17
SHIFT
D
D
OUT
IN
REGISTER
1
2
3
4
5
6
7
8
9
SAMPLE
AND HOLD
CH0
CH1
CH2
CH3
CH4
CH5
CH6
CH7
COM
COMP
10-BIT
SAR
ANALOG
INPUT
MUX
10-BIT
CAPACITIVE
DAC
19
15
ACLK
10
11
AGND
12
13
–
14
+
CONTROL
AND
TIMING
–
DGND
V
REF
REF
CS
LTC1090 • BD01
1090fc
6
LTC1090
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TYPICAL PERFOR A CE CHARACTERISTICS
Supply Current vs Supply Voltage
Supply Current vs Temperature
Reference Current vs Temperature
6
5
4
3
2
1
0
1.4
1.2
1.0
0.8
0.6
0.5
0.4
0.3
+
V
= 5V
REF OPEN
REF
ACLK = 2MHz
CS = V
= 25°C
CC
T
A
0.6
0.4
0.2
0.2
0.1
0
+
REF OPEN
ACLK = 2MHz
CS = 5V
V
= 5V
CC
4
6
7
8
9
10
50
100 125
50
100 125
5
–50 –25
0
25
75
–50 –25
0
25
75
SUPPLY VOLTAGE, V (V)
AMBIENT TEMPERATURE, T (°C)
AMBIENT TEMPERATURE, T (°C)
CC
A
A
LTC1090 • TPC01
LTC1090 • TPC02
LTC1090 • TPC03
Unadjusted Offset Error vs
Reference Voltage
Linearity Error vs Reference
Voltage
Change in Gain Error vs
Reference Voltage
1.25
1.0
1.25
1.0
10
9
8
7
6
5
4
3
2
1
0
V
= 5V
V
= 5V
V
= 5V
CC
CC
CC
0.75
0.5
0.75
0.5
V
= 1mV
OS
0.25
0
0.25
0
V
= 0.5mV
OS
0
1
2
3
4
5
0
1
2
3
4
5
0.2
1.0
5.0
REFERENCE VOLTAGE, V
(V)
REFERENCE VOLTAGE, V
(V)
REF
REFERENCE VOLTAGE, V
(V)
REF
REF
LTC1090 • TPC04
LTC1090 • TPC05
LTC1090 • TPC06
Change in Gain Error vs Supply
Voltage
Offset Error vs Supply Voltage
Linearity Error vs Supply Voltage
1.25
1.0
1.25
1.0
0.5
0.25
0
V
= 4V
V
= 4V
V
= 4V
REF
REF
REF
ACLK = 2MHz
= 1.25mV AT V = 5V
ACLK = 2MHz
ACLK = 2MHz
V
OS
CC
0.75
0.5
0.75
0.5
–0.25
–0.5
0.25
0
0.25
0
4
6
7
8
9
10
4
6
7
8
9
10
4
6
7
8
9
10
5
5
5
SUPPLY VOLTAGE, V (V)
SUPPLY VOLTAGE, V (V)
SUPPLY VOLTAGE, V (V)
CC
CC
CC
LTC1090 • TPC07
LTC1090 • TPC08
LTC1090 • TPC09
1090fc
7
LTC1090
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Change in Offset Error
vs Temperature
Change in Gain Error
vs Temperature
Change in Linearity Error
vs Temperature
0.6
0.5
0.4
0.3
0.6
0.5
0.4
0.3
0.6
0.5
0.4
0.3
V
V
= 5V
= 5V
V
V
= 5V
= 5V
CC
V
V
= 5V
= 5V
CC
CC
REF
REF
REF
ACLK = 2MHz
ACLK = 2MHz
ACLK = 2MHz
0.2
0.1
0
0.2
0.1
0
0.2
0.1
0
50
100 125
–50 –25
0
25
75
50
100 125
–50 –25
0
25
75
50
100 125
–50 –25
0
25
75
AMBIENT TEMPERATURE, T (°C)
AMBIENT TEMPERATURE, T (°C)
AMBIENT TEMPERATURE, T (°C)
A
A
A
LTC1090 • TPC11
LTC1090 • TPC10
LTC1090 • TPC12
Maximum Conversion Clock Rate
vs Temperature
Maximum Conversion Clock Rate
vs Supply Voltage
Maximum Conversion Clock Rate
vs Reference Voltage
7
6
5
4
3
2
1
0
5
6
5
4
3
V
= 5V
= 25°C
V
= 4V
= 25°C
CC
REF
T
T
A
A
4
3
2
1
0
2
1
0
V
V
= 5V
CC
= 5V
REF
8
10
0
1
2
3
4
5
4
5
6
7
9
50
100 125
–50 –25
0
25
75
REFERENCE VOLTAGE, V
(V)
SUPPLY VOLTAGE, V (V)
CC
AMBIENT TEMPERATURE, T (°C)
REF
A
LTC1090 • TPC14
LTC1090 • TPC15
LTC1090 • TPC13
Maximum Filter Resistor vs Cycle
Time
Sample-and-Hold Acquisition
Time vs Source Resistance
Maximum Conversion Clock Rate
vs Source Resistance
10
5
4
3
2
1
0
100k
V
V
T
= 5V
REF
CC
V
V
T
= 5V
= 5V
= 25°C
R
CC
FILTER
= 5V
V
+
_
IN
REF
= 25°C
A
C
≥ 1µF
A
FILTER
10k
1k
0 TO 5V INPUT STEP
1
V
+
–
INPUT
IN
+
R
IN
SOURCE
V
+
_
INPUT
–
100
R
SOURCE
0.1
100
10
1k
10k
10
100
1k
(Ω)
10k
10
100
CYCLE TIME, t
1000
10k
+
R
(Ω)
(µs)
SOURCE
CYC
–
R
SOURCE
LTC1090 • TPC18
LTC1090 • TPC16
LTC1090 • TPC17
**MAXIMUM RFILTER REPRESENTS THE FILTER RESISTOR VALVE AT WHICH A 0.1LSB SHIFT
CHANGE IN FULL SCALE ERROR FROM ITS VALUE AT R = 0 IS FIRST DETECTED.
*MAXIMUM ACLK FREQUENCY REPRESENTS THE ACLK FREQUENCY AT WHICH A 0.1LSB
SHIFT IN THE ERROR AT ANY CODE TRANSITION FROM ITS 2MHz VALVE IS FIRST DETECTED.
FILTER
1090fc
8
LTC1090
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TYPICAL PERFOR A CE CHARACTERISTICS
Digital Input Logic Threshold vs
Supply Voltage
Input Channel Leakage Current
vs Temperature
Noise Error vs Reference Voltage
2.0
1.75
1.5
1000
900
800
700
600
500
400
300
200
100
4
3
2
1
LTC1090 NOISE = 200µV PEAK-TO-PEAK
T
= 25°C
A
GUARANTEED
1.25
1.0
0.75
0.5
ON CHANNEL
OFF CHANNELS
0.25
0
0.2
1
5
–50
0
25
50
75 100 125
–25
4
5
6
7
8
9
10
REFERENCE VOLTAGE, V
(V)
SUPPLY VOLTAGE, V (V)
AMBIENT TEMPERATURE, T (°C)
REF
CC
A
LTC1090 • TPC21
LTC1090 • TPC20
LTC1090 • TPC19
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APPLICATIO S I FOR ATIO
The LTC1090 is a data acquisition component which
contains the following functional blocks:
DIGITAL CONSIDERATIONS
1. Serial Interface
1. 10-bit successive approximation capacitive
A/D converter
The LTC1090 communicates with microprocessors and
other external circuitry via a synchronous, full duplex,
four wire serial interface (see Operating Sequence). The
shift clock (SCLK) synchronizes the data transfer with
each bit being transmitted on the falling SCLK edge
and captured on the rising SCLK edge in both transmit-
ting and receiving systems. The data is transmitted and
received simultaneously (full duplex).
2. Analog multiplexer (MUX)
3. Sample and hold (S/H)
4. Synchronous, full duplex serial interface
5. Control and timing logic
Operating Sequence
(Example: Differential Inputs (CH3 to CH2), Bipolar, MSB First and 10-Bit Word Length)
t
CYC
1
5
8
10
SCLK
CS
DON’T CARE
t
t
CONV
SMPL
SGL/
DIFF
D
ODD/
SIGN
IN
MSBF
DON’T CARE
SEL1 SEL0 UNI
WL1 WL0
D
OUT
B9
(SB)
B8
B7
B6 B5
B4 B3
B2
B1
B0
SHIFT CONFIGURATION
WORD IN
SHIFT A/D RESULT OUT AND
NEW CONFIGURATION WORD IN
LTC1090 • AI01
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LTC1090
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APPLICATIO S I FOR ATIO
Datatransferisinitiatedbyafallingchipselect(CS)signal.
After the falling CS is recognized, an 8-bit input word
is shiftedintotheDIN inputwhichconfigurestheLTC1090
for the next conversion. Simultaneously, the result of the
previous conversion is output on the DOUT line. At the end
of the data exchange the requested conversion begins and
CS should be brought high. After tCONV, the conversion is
complete and the results will be available on the next data
transfer cycle. As shown below, the result of a conversion
is delayed by one CS cycle from the input word requesting
it.
Multiplexer (MLIX) Address
The first four bits of the input word assign the MUX
configuration for the requested conversion. For a given
channel selection, the converter will measure the voltage
between the two channels indicated by the + and – signs
in the selected row of Table 1. Note that in differential
mode (SGL/DIFF = O) measurements are limited to four
adjacent input pairs with either polarity. In single ended
mode, all input channels are measured with respect to
COM. Figure 1 shows some examples of multiplexer
assignments.
Table 1. Multiplexer Channel Selection
D
D
D
D
Word 1
Word 0
D
D
Word 2
Word 1
D
D
Word 3
Word 2
OUT
IN
IN
IN
IN
MUX ADDRESS
SGL/ ODD SELECT
DIFFERENTIAL CHANNEL SELECTION
OUT
OUT
OUT
t
t
CONV
A/D
CONV
A/D
Data
Transfer
Data
Transfer
DIFF SIGN
1
0
0
1
1
0
0
1
1
0
0
1
0
1
0
1
0
1
0
1
2
3
4
5
6
+
–
7
–
+
Conversion
Conversion
LTC1090 • AI02
0
0
0
0
0
0
0
0
0
0
0
0
1
1
1
1
+
–
+
–
2. Input Data Word
+
–
The LTC1090 8-bit input data word is clocked into the DIN
input on the first eight rising SCLK edges after chip select
is recognized. Further inputs on the DIN pin are then
ignored until the next CS cycle. The eight bits of the input
word are defined as follows:
–
+
–
+
–
+
Unipolar/
Bipolar
Word Length
Data Input (D ) Word:
IN
MUX ADDRESS
SGL/ ODD/ SELECT
SINGLE ENDED CHANNEL SELECTION
SGL/
DIFF
ODD/
SIGN
SELECT
1
SELECT
0
UNI
MSBF
WL1
WL0
DIFF SIGN
1
0
0
1
1
0
0
1
1
0
0
1
0
1
0
1
0
1
0
1
2
3
4
5
6
7 COM
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
+
–
–
–
–
–
–
–
MUX Address
MSB First/
LSB First
+
LTC1090• AI03
+
+
+
+
+
+
–
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APPLICATIO S I FOR ATIO
4 Differential
8 Single Ended
Combinations of Differential and Single Ended
CHANNEL
CHANNEL
0,1
CHANNEL
+
+
+
+
+
+
+
+
0
1
2
3
4
5
6
7
+( – )
–( + )
+
–
0,1
+( – )
–( + )
–
2,3
4,5
6,7
2,3
+
+( – )
–( + )
4
5
6
7
+
+
+
+( – )
–( + )
+
COM ( – )
COM (
)
–
LTC1090 • AI04B
LTC1090 • AI04C
LTC1090 • AI04A
Changing the MUX Assignment “On the Fly”
+
–
–
4,5
6,7
5,4
+
+
–
+
+
6
7
COM (UNUSED)
COM (
)
–
1ST CONVERSION
2ND CONVERSION
LTC1090 • AI04E
LTC1090 • AI04D
Figure 1. Examples of Multiplexer Options on the LTC1090
Unipolar/Bipolar (UNI)
input voltage. When UNI is a logical zero, a bipolar conver-
sion will result. The input span and code assignment for
each conversion type are shown in the figures below.
The fifth input bit (UNI) determines whether the conver-
sion will be unipolar or bipolar. When UNI is a logical one,
a unipolar conversion will be performed on the selected
Unipolar Transfer Curve (UNI = 1)
1 1 1 1 1 1 1 1 1 1
1 1 1 1 1 1 1 1 1 0
0 0 0 0 0 0 0 0 0 1
0 0 0 0 0 0 0 0 0 0
V
IN
V
– 2LSB
V
REF
OV 1LSB
REF
LTC1090 • AI05
V
– 1LSB
REF
Bipolar Transfer Curve (UNI = 0)
0 1 1 1 1 1 1 1 1 1
0 1 1 1 1 1 1 1 1 0
–V +1LSB
REF
0 0 0 0 0 0 0 0 0 1
0 0 0 0 0 0 0 0 0 0
1LSB
–V
REF
V
IN
V
– 2LSB
V
1 1 1 1 1 1 1 1 1 1
1 1 1 1 1 1 1 1 1 0
REF
REF
–1LSB
V
– 1LSB
REF
–2LSB
1 0 0 0 0 0 0 0 0 1
1 0 0 0 0 0 0 0 0 0
LTC1090 • AI06
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Unipolar Output Code (UNI = 1)
control the length of the present, not the next, DOUT word.
WL1andWL0arenever“don’tcares”andmustbesetfor
the correct DOUT word length even when a “dummy” DIN
wordissent. Onanytransfercycle, thewordlengthshould
be made equal to the number of SCLK cycles sent by the
MPU.
INPUT VOLTAGE
(V = 5V)
OUTPUT CODE
INPUT VOLTAGE
REF
1111111111
V
V
– 1LSB
4.9951V
REF
REF
1111111110
– 2LSB
4.9902V
•
•
•
•
•
•
•
•
•
WL1
WL0
OUTPUT WORD LENGTH
0000000001
0000000000
1LSB
0V
0.0049V
0V
0
0
1
1
0
1
0
1
8 Bits
10 Bits
12 Bits
16 Bits
Bipolar Output Code (UNI = 0)
INPUT VOLTAGE
OUTPUT CODE
INPUT VOLTAGE
(V
REF
= 5V)
Figure 2 shows how the data output (DOUT) timing can be
controlled with word length selection and MSB/LSB first
format selection.
0111111111
V
V
– 1LSB
4.9902V
REF
REF
0111111110
– 2LSB
4.9805V
•
•
•
•
•
•
•
•
•
3. Deglitcher
0000000001
0000000000
1111111111
1111111110
•
1LSB
0.0098V
0V
0V
A deglitching circuit has been added to the Chip Select
input of the LTC1090 to minimize the effects of errors
causedbynoiseonthatinput.Thiscircuitignoreschanges
in state on the CS input that are shorter in duration than 1
ACLK cycle. After a change of state on the CS input, the
LTC1090 waits for two falling edges of the ACLK before
recognizing a valid chip select. One indication of CS low
recognition is the DOUT line becoming active (leaving the
Hi-Z state). Note that the deglitching applies to both the
rising and falling CS edges.
–1LSB
–0.0098V
–2LSB
–0.0195V
•
•
•
•
•
•
•
•
1000000001
1000000000
– (V ) + 1LSB
–4.9902V
–5.000V
REF
– (V
)
REF
MSB First/LSB First Format (MSBF)
The output data of the LTC1090 is programmed for MSB
first or LSB first sequence using the MSBF bit. For MSB
first output data the input word clocked to the LTC1090
should always contain a logical one in the sixth bit location
(MSBF bit). Likewise for LSB first output data, the input
wordclockedtotheLTC1090shouldalwayscontainazero
in the MSBF bit location. The MSBF bit in a given DIN word
will control the order of the next DOUT word. The MSBF bit
affects only the order of the output data word. The order
of the input word is unaffected by this bit.
ACLK
CS
HIGH Z
D
VALID OUTPUT
OUT
LOW CS RECOGNIZED
INTERNALLY
MSBF
OUTPUT FORMAT
LSB First
0
1
ACLK
CS
MSB First
Word Length (WL1, WL0)
The last two bits of the input word (WL1 and WL0) program
the output data word length of the LTC1090. Word lengths
of 8, 10, 12 or 16 bits can be selected according to the
following table. The WL1 and WL0 bits in a given DIN word
HIGH Z
D
OUT
HIGH CS RECOGNIZED
INTERNALLY
LTC1090 • AI07
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LTC1090
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U
8-Bit Word Length
t
t
CONV
SMPL
CS
SCLK
1
8
(SB)
D
THE LAST TWO BITS
ARE TRUNCATED
OUT
B9 B8 B7
B6 B5
B3 B4
B4
B5
B3 B2
MSB FIRST
D
OUT
LSB FIRST
B0 B1 B2
B6 B7
LTC1090 • AI08A
10-Bit Word Length
t
t
SMPL
CONV
CS
SCLK
10
1
(SB)
D
OUT
MSB FIRST
B9 B8 B7
B6 B5
B4
B5
B3 B2 B1 B0
(SB)
B9
D
OUT
LSB FIRST
B0 B1 B2
B3 B4
B6 B7
B8
LTC1090 • AI08B
12-Bit Word Length
t
t
CONV
SMPL
CS
SCLK
10
12
1
(SB)
FILL
ZEROES
D
OUT
MSB FIRST
B9 B8 B7
B6 B5
B4
B5
B3 B2 B1 B0
(SB)
B9
D
OUT
B0 B1 B2
B3 B4
B6 B7
B8
*
*
LSB FIRST
LTC1090 • AI08C
16-Bit Word Length
t
t
CONV
SMPL
CS
SCLK
16
1
10
(SB)
FILL
ZEROES
D
OUT
MSB FIRST
B9 B8 B7
B6 B5
B3 B4
B4
B5
B3 B2 B1 B0
(SB)
B9
D
OUT
LSB FIRST
B0 B1 B2
B6 B7
B8
*
*
*
*
*
*
*IN UNIPOLAR MODE, THESE BITS ARE FILLED WITH ZEROES.
IN BIPOLAR MODE, THE SIGN BIT IS EXTENDED INTO THESE LOCATIONS
LTC1090 • AI08D
Figure 2. Data Output (DOUT) Timing with Different Word Lengths
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4. CS Low During Conversion
In the normal mode of operation, CS is brought high
during the conversion time (see Figure 3). The serial port
ignores any SCLK activity while CS is high. The LTC1090
will also operate with CS low during the conversion. In this
mode, SCLK must remain low during the conversion as
shown in Figure 4. After the conversion is complete, the
D
OUT line will become active with the first output bit. Then
the data transfer can begin as normal.
5. Microprocessor Interfaces
The LTC1090 can interface directly (without external hard-
ware) to most popular microprocessor (MPU) synchronous
t
SHIFT
MUX
ADDRESS
IN
SMPL
SAMPLE
ANALOG
INPUT
SHIFT RESULT OUT
AND NEW ADDRESS IN
40 TO 44 ACLK CYCLES
CS
SCLK
SEL SEL
SEL
1
SGL/
DIFF
SGL/
DIFF
ODD/
SIGN
ODD/
SIGN
SEL
0
D
UNI MSBF WL1 WL0
UNI MSBF WL1 WL0
DON’T CARE
IN
1
0
D
OUT
B9
B8
B7
B6 B5
B4 B3
B2
B1
B0
B9
B8
B7
B6 B5
B4 B3
B2
B1
B0
LTC1090 • AI09
Figure 3. CS High During Conversion
t
SHIFT
MUX
ADDRESS
IN
SMPL
SAMPLE
ANALOG
INPUT
SHIFT RESULT OUT
AND NEW ADDRESS IN
40 TO 44 ACLK CYCLES
CS
SCLK
D
SCLK MUST REMAIN LOW
DON’T CARE
SEL SEL
SEL
1
SGL/
DIFF
SGL/
DIFF
ODD/
SIGN
ODD/
SIGN
SEL
0
UNI MSBF WL1 WL0
UNI MSBF WL1 WL0
IN
1
0
D
OUT
B9
B8
B7
B6 B5
B4 B3
B2
B1
B0
B9
B8
B7
B6 B5
B4 B3
B2
B1
B0
LTC1090 • AI10
Figure 4. CS Low During Conversion
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U
serial formats (see Table 2). If an MPU without a serial
interfaceisused,then4oftheMPU’sparallelportlinescan
be programmed to form the serial link to the LTC1090.
Included here are three serial interface examples and one
example showing a parallel port programmed to form the
serial interface.
National MICROWIRE (COP420)
The COP420 transfers data MSB first and in 4-bit incre-
ments (nibbles). This is easily accommodated by setting
the LTC1090 to MSB first format and 12-bit word length.
The data output word is then received by the COP420 in
three 4-bit blocks with the final two unused bits filled with
zeroes by the LTC1090.
Table 2. Microprocessors with Hardware Serial Interfaces
Compatible with the LTC1090**
PART NUMBER
Motorola
TYPE OF INTERFACE
Hardware and Software Interface to National Semiconductor
COP420 Processor
MC6805S2, S3
MC68HC11
MC68HC05
SPI
SPI
SPI
LTC1090
CS
COP420
GO
SK
SO
SCLK
RCA
ANALOG
INPUTS
CDP68HC05
Hitachi
SPI
D
IN
D
SI
OUT
HD6305
HD63705
HD6301
HD63701
HD6303
SCI Synchronous
SCI Synchronous
SCI Synchronous
SCI Synchronous
SCI Synchronous
D
OUT
from LTC1090 stored in COP420 RAM
MSB*
National Semiconductor
COP400 Family
COP800 Family
NS8050U
MICROWIRE†
MICROWIRE/PLUS
MICROWIRE/PLUS
MICROWIRE/PLUS
B9 B8 B7 B6
Location A
first 4 bits
†
HPC16000 Family
second 4 bits
third 4 bits
Location A + 1
Location A + 2
B5 B4 B3 B2
Texas Instruments
LSB
TMS7002
TMS7042
TMS70C02
TMS70C42
TMS32011*
TMS32020*
Serial Port
Serial Port
Serial Port
Serial Port
Serial Port
Serial Port
B1 B0 B0 B0
LTC1090 • AI11
*B9 is MSB in unipolar or sign bit in bipolar
*Requires external hardware
MNEMONIC
DESCRIPTION
**Contact LTC Marketing for interface information for processors not on
this list
MICROWIRE and MlCROWIRE/PLUS are trademarks of National
LEI
SC
Enable SlO
Set Carry flag
G0 is set to (CS goes low)
Load first 4 bits of D to ACC
Swap ACC with SIO reg. Starts SK Clk
Load 2nd 4 bits of D to ACC
Timing
Swap first 4 bits from A/D with ACC. SK continues.
Put first 4 bits in RAM (location A)
Timing
Swap 2nd 4 bits from A/D with ACC. SK continues.
Put 2nd 4 bits in RAM (location A + 1)
Clear Carry
†
OGI
LDD
XAS
LDD
NOP
XAS
XIS
NOP
XAS
XIS
RC
NOP
XAS
XIS
OGI
LEI
Semiconductor Corp.
IN
Serial Port Microprocessors
IN
Most synchronous serial formats contain a shift clock
(SCLK)andtwodatalines,onefortransmittingandonefor
receiving. In most cases data bits are transmitted on the
falling edge of the clock (SCLK) and captured on the rising
edge. However, serial port formats vary among MPU
manufacturers as to the smallest number of bits that can
be sent in one group (e.g., 4-bit, 8-bit or 16-bit transfers).
They also vary as to the order in which the bits are
transmitted (LSB or MSB first). The following examples
showhowtheLTC1090accommodatesthesedifferences.
Timing
Swap 3rd 4 bits from A/D with ACC. SK off
Put 3rd 4 bits in RAM (location A + 2)
G0 is set to 1 (CS goes high)
Disable SlO
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Motorola SPI (MC68HC05C4)
Hitachi Synchronous SCI (HD63705)
The MC68HC05C4 transfers data MSB first and in 8-bit
increments. Programming the LTC1090 for MSB first
format and 16-bit word length allows the 10-bit data
output to be received by the MPU as two 8-bit bytes with
the final 6 unused bits filled with zeroes by the LTC1090.
The HD63705 transfers serial data in 8-bit increments,
LSB first. To accommodate this, the LTC1090 is
programmed for 16-bit word length and LSB first format.
The 10-bit output data is received by the processor as two
8-bit bytes, LSB first. The LTC1090 fills the final 6 unused
bits (after the MSB) with zeroes in unipolar mode and with
the sign bit in bipolar mode.
Hardware and Software Interface to Motorola MC68HC05C4
Processor
Hardware and Software Interface to Hitachi HD63705 Processor
LTC1090
CS
MC68HCO5C4
CO
LTC1090
CS
HD63705
C0
SCK
SCLK
ANALOG
INPUTS
D
MOSI
CK
IN
SCLK
ANALOG
INPUTS
D
D
T
X
MISO
OUT
IN
D
R
X
OUT
D
OUT
from LTC1090 stored in MC68HCO5C4 RAM
MSB*
D
OUT
from LTC1090 stored in HD63705 RAM
LSB
B9 B8 B7 B6 B5 B4 B3 B2
LSB
Location A
byte 1
B7 B6 B5 B4 B3 B2 B1 B0
Sign
Location A
byte 1
Location A + 1
B1 B0
0
0
0
0
0
0
byte 2
Location A + 1
B9 B9 B9 B9 B9 B9 B9 B8 byte 2
LTC1090 • AI12
*B9 is MSB in unipolar or sign bit in bipolar
Bipolar
LSB
MNEMONIC
DESCRIPTION
C0 is cleared (CS goes Low)
B7 B6 B5 B4 B3 B2 B1 B0
MSB
Location A
byte 1
byte 2
BCLR n
LDA
STA
↑
NOP
↓
LDA
LDA
STA
STA
↑
NOP
↓
BSET n
LDA
LDA
STA
Load D for LTC1090 into ACC
IN
0
0 0
0
0
0 B9 B8
Location A + 1
Load D from ACC to SPI data reg. Start SCK
IN
Unipolar
LTC1090 • AI13
8 NOPs for timing
MNEMONIC
DESCRIPTION
Load contents of SPI status reg. into ACC
Load LTC1090 D
Load LTC1090 D
from SPI data reg. into ACC (byte 1)
into RAM (location A)
OUT
LDA
BCLR n
STA
Load D word for LTC1090 into ACC from RAM
C0 cleared (CS goes low)
Load D word for LTC1090 into SCI data reg. from ACC
and start clocking data (LSB first)
IN
OUT
Start next SPl cycle
IN
6 NOPs for timing
↑
NOP
↓
6 NOPs for timing
C0 is set (CS goes high)
Load contents of SPI status reg. into ACC
LDA
Load contents of SCI data reg. into ACC (byte 1)
Start next SCI cycle
Load LTC1090 D
Load LTC1090 D
from SPI data reg. into ACC (byte 2)
into RAM (location A + 1)
OUT
OUT
STA
Load LTC1090 D
word into RAM (Location A)
OUT
NOP
BSET n
LDA
Timing
C0 set (CS goes high)
Load contents of SCI data reg. into ACC (byte 2)
Load LTC1090 D word into RAM (Location A + 1)
STA
OUT
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16
LTC1090
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8051 Code
DESCRIPTION
Parallel Port Microprocessors
MNEMONIC
When interfacing the LTC1090 to an MPU which has a
parallel port, the serial signals are created on the port with
software. Three MPU port lines are programmed to create
the CS, SCLK and DIN signals for the LTC1090. A fourth
port line reads the DOUT line. An example is made of the
Intel 8051/8052/80C252 family.
MOV PI,#02H
Initialize port 1 (bit 1 is made
an input)
SCLK goes low
CS goes high
D word for the LTC1090 is
placed in ACC.
CS goes low
Load counter
CLR P1.3
SETB P1.4
CONTINUE: MOV A,#0DH
IN
CLR P1.4
MOV R4,#08
NOP
MOV C, P1.1
RLC A
MOV P1.2, C
SETB P1.3
CLR P1.3
DJNZ R4, LOOP
MOV R2, A
MOV C, P1.1
CLR A
RLC A
SETB P1.3
CLR P1.3
MOV C, P1.1
RRC A
RRC A
Intel 8051
Delay for deglitcher
Read data bit into carry
Rotate data bit into ACC
LOOP:
To interface to the 8051, the LTC1090 is programmed for
MSB first format and 10-bit word length. The 8051 gener-
ates CS, SCLK and DIN on three port lines and reads DOUT
on the fourth.
Output D bit to LTC1090
IN
SCLK goes high
SCLK goes low
Next bit
Store MSBs in R2
Read data bit into carry
CIear ACC
Rotate data bit into ACC
SCLK goes high
SCLK goes low
Read data bit into carry
Rotate right into ACC
Rotate right into ACC
Store LSBs in R3
SCLK goes high
SCLK goes low
Hardware and Software Interface to Intel 8051 Processor
LTC1090
8051
D
P1.1
OUT
D
P1.2
P1.3
IN
ANALOG
INPUTS
SCLK
CS
P1.4
ALE
MOV R3, A
SETB P1.3
CLR P1.3
ACLK
SETB P1.4
MOV R5,#07H
DJNZ R5, DELAY
CS goes high
Load counter
Delay for LTC1090 to perform
conversion
Repeat program
D
from LTC1090 stored in 8051 RAM
OUT
DELAY:
MSB*
AJMP CONTINUE
R2
R3
B9 B8 B7 B6 B5 B4 B3 B2
LSB
B1 B0
0
0
0
0
0
0
*B9 is MSB in unipolar or sign bit in bipolar
2
1 0
OUTPUT PORT
SERIAL DATA
3-WIRE SERIAL
3
INTERFACE TO OTHER
PERIPHERALS OR LTC1090s
3
3
3
MPU
CS
CS
CS
LTC1090
LTC1090
LTC1090
8 CHANNELS
8 CHANNELS
8 CHANNELS
LTC1090 • AI14
Figure 5. Several LTC1090’s Sharing One 3-Wire Serial Interface
1090fc
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6. Sharing the Serial Interface
V
CC
4.7µF TANTALUM
The LTC1090 can share the same 3-wire serial interface
withotherperipheralcomponentsorotherLTC1090s(see
Figure 5). In this case, the CS signals decide which
LTC1090 is being addressed by the MPU.
1
20
ANALOG CONSIDERATIONS
1. Grounding
The LTC1090 should be used with an analog ground plane
and single point grounding techniques.
Pin11(AGND)shouldbetieddirectlytothisgroundplane.
Pin 10 (DGND) can also be tied directly to this ground
plane because minimal digital noise is generated within
the chip itself.
V –
ANALOG
GROUND
PLANE
10
11
Pin 20 (VCC) should be bypassed to the ground plane with
a 4.7µF tantalum with leads as short as possible. Pin 12
(V–) should be bypassed with a 0.1µF ceramic disk. For
single supply applications, V– can be tied to the ground
plane.
0.1µF CERAMIC DISK
LTC1090 • AI15
Figure 6. Example Ground Plane for the LTC1090
Itisalsorecommendedthatpin13(REF–)andpin9(COM)
be tied directly to the ground plane. All analog inputs
should be referenced directly to the single point ground.
Digital inputs and outputs should be shielded from and/or
routed away from the reference and analog circuitry.
Figure6showsanexampleofanidealgroundplanedesign
for a two sided board. Of course this much ground plane
will not always be possible, but users should strive to get
as close to this ideal as possible.
HORIZONTAL: 10µs/DIV
Figure 7. Poor VCC Bypassing. Noise and Ripple
can Cause A/D Errors
2. Bypassing
For good performance, VCC must be free of noise and
ripple. Any changes in the VCC voltage with respect to
analog ground during a conversion cycle can induce
errorsornoiseintheoutputcode. VCC noiseandripplecan
bekeptbelow1mVbybypassingtheVCC pindirectlytothe
analog ground plane with a 4.7µF tantalum with leads as
shortaspossible. Figures7and8showtheeffectsofgood
and poor VCC bypassing.
HORIZONTAL: 10µs/DIV
Figure 8. Good VCC Bypassing Keeps Noise and Ripple
on VCC Below 1mV
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18
LTC1090
W U U
APPLICATIO S I FOR ATIO
U
“+” Input Settling
3. Analog Inputs
This input capacitor is switched onto the “+” input during
the sample phase (tSMPL, see Figure 10). The sample
phasestartsatthe4thSCLKcycleandlastsuntilthefalling
edge of the last SCLK (the 8th, 10th, 12th or 16th SCLK
cycle depending on the selected word length). The voltage
on the “+” input must settle completely within this sample
time. Minimizing RSOURCE+ and C1 will improve the input
settling time. If large “+” input source resistance must be
used, the sample time can be increased by using a slower
SCLK frequency or selecting a longer word length. With
the minimum possible sample time of 4µs, RSOURCE+ < 2k
and C1 < 20pF will provide adequate settling.
Because of the capacitive redistribution A/D conversion
techniques used, the analog inputs of the LTC1090 have
capacitive switching input current spikes. These current
spikes settle quickly and do not cause a problem.
However, if large source resistances are used or if slow
settling op amps drive the inputs, care must be taken to
insure that the transients caused by the current spikes
settle completely before the conversion begins.
Source Resistance
The analog inputs of the LTC1090 look like a 60pF capaci-
tor (CIN) in series with a 500Ω resistor (RON) as shown in
Figure 9. CIN gets switched between the selected “+” and
“–” inputs once during each conversion cycle. Large
external source resistors and capacitances will slow the
settling of the inputs. It is important that the overall RC
time constants be short enough to allow the analog inputs
to completely settle within the allowed time.
“–” Input Settling
Attheendofthesamplephasetheinputcapacitor switches
to the “–” input and the conversion starts (see Figure 10).
During the conversion, the “+” input voltage is effectively
“held” by the sample and hold and will not affect the
conversion result. However, it is critical that the “–” input
voltage be free of noise and settle completely during the
first four ACLK cycles of the conversion time. Minimizing
“
+
”
+
INPUT
R
SOURCE
+
V
IN
4TH SCLK
= 500Ω
R
C1
ON
–
RSOURCE and C2 will improve settling time. If large
“
–
”
–
C
= 60pF
INPUT
“–”inputsourceresistancemustbeused,thetimeallowed
for settling can be extended by using a slower ACLK
R
IN
SOURCE
LAST SCLK
LTC1090
–
V
IN
C2
–
frequency. At the maximum ACLK rate of 2MHz, RSOURCE
< 1kΩ and C2 < 20pF will provide adequate settling.
LTC1090 • AI16
Figure 9. Analog Input Equivalent Circuit
SAMPLE
“ + ” INPUT MUST
SETTLE DURING THIS TIME
HOLD
MUX ADDRESS
SHIFTED IN
t
SMPL
CS
SCLK
ACLK
LAST SCLK (8TH, 10TH, 12TH OR 16TH DEPENDING ON WORK LENGTH)
1
2
3
4
1
2
3
4
1ST BIT
TEST
“ – ” INPUT MUST SETTLE
DURING THIS TIME
“ + ” INPUT
“ – ” INPUT
LTC1090 • AI17
Figure 10. “+” and “–” Input Settling Windows
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19
LTC1090
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APPLICATIO S I FOR ATIO
Input Op Amps
When driving the analog inputs with an op amp it is
important that the op amp settle within the allowed time
(see Figure 10). Again, the “+” and “–” input sampling
times can be extended as described above to accommo-
date slower op amps. Most op amps including the LT1006
and LT1013 single supply op amps can be made to settle
well even with the minimum settling windows of 4µs (“+”
input) and 2µs (“–” input) which occur at the maximum
clock rates (ACLK = 2MHz and SCLK = 1MHz). Figures 11
and 12 show examples of adequate and poor op amp
settling.
eliminated by increasing the cycle time as shown in the
typical curve of Maximum Filter Resistor vs Cycle Time.
I
DC
R
FILTER
V
“ + ”
IN
LTC1090
C
FILTER
–
“
”
LTC1090 • AI18
Figure 13. RC Input Filtering
Input Leakage Current
Input leakage currents can also create errors if the source
resistancegetstoolarge.Forinstance,themaximuminput
leakage specification of 1µA (at 125°C) flowing through a
source resistance of 1kΩ will cause a voltage drop of 1mV
or 0.2LSB. This error will be much reduced at lower
temperatures because leakage drops rapidly (see typical
curve of Input Channel Leakage Current vs Temperature).
HORIZONTAL: 1µs/DIV
Figure 11. Adequate Settling of Op Amp Driving Analog Input
Noise Coupling into Inputs
High source resistance input signals (>500Ω) are more
sensitivetocouplingfromexternalsources.Itispreferable
to use channels near the center of the package (i.e., CH2 to
CH7) for signals which have the highest output resistance
because they are essentially shielded by the pins on the
package ends (DGND and CH0). Grounding any unused
inputs (especially the end pin, CH0) will also reduce
outside coupling into high source resistances.
HORIZONTAL: 20µs/DIV
Figure 12. Poor Op Amp Settling can Cause A/D Errors
RC Input Filtering
It is possible to filter the inputs with an RC network as
shown in Figure 13. For large values of CF (e.g., 1µF), the
capacitive input switching currents are averaged into a net
DC current. Therefore, a filter should be chosen with a
small resistor and large capacitor to prevent DC drops
across the resistor. The magnitude of the DC current is
approximatelylDC =60pFxVIN/tCYC andisroughlypropor-
tional to VIN. When running at the minimum cycle time of
33µs, theinputcurrentequals9µAatVIN =5V. Inthiscase,
afilterresistorof50Ωwillcause0.1LSBoffull-scaleerror.
If a larger filter resistor must be used, errors can be
4. Sample-and-Hold
Single Ended Inputs
The LTC1090 provides a built-in sample and hold (S&H)
function for all signals acquired in the single ended mode
(COM pin grounded). This sample and hold allows the
LTC1090 to convert rapidly varying signals (see typical
curveofS&HAcquisitionTimevsSourceResistance). The
input voltage is sampled during the tSMPL time as shown
in Figure 10. The sampling interval begins after the fourth
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20
LTC1090
W U U
APPLICATIO S I FOR ATIO
U
MUX address bit is shifted in and continues during the When driving the reference inputs, three things should be
remainder of the data transfer. On the falling edge of the kept in mind:
final SCLK, the S&H goes into hold mode and the conver-
1. The source resistance (ROUT) driving the reference
sion begins. The voltage will be held on either the 8th,
inputs should be low (less than 1Ω) to prevent DC
10th, 12th or 16th falling edge of the SCLK depending on
the word length selected.
(IREF).
drops caused by the 1mA maximum reference current
Differential Inputs
2. Transients on the reference inputs caused by the
capacitive switching currents must settle completely
during each bit test (each 4 ACLK cycles). Figures 15
and 16 show examples of both adequate and poor
settling. Using a slower ACLK will allow more time for
the reference to settle. However, even at the maximum
ACLK rate of 2MHz most references and op amps can
be made to settle within the 2µs bit time.
With differential inputs or when the COM pin is not tied to
ground, the A/D no longer converts just a single voltage
but rather the difference between two voltages. In these
cases,thevoltageontheselected“+” inputisstillsampled
and held and therefore may be rapidly time varying just as
in single ended mode. However, the voltage on the se-
lected “–” input must remain constant and be free of noise
and ripple throughout the conversion time. Otherwise, the 3. It is recommended that the REF– input be tied directly
differencing operation may not be performed accurately.
The conversion time is 44 ACLK cycles. Therefore, a
change in the “–” input voltage during this interval can
“–” input this error would be:
totheanaloggroundplane.IfREF– isbiasedatavoltage
other than ground, the voltage must not change during
a conversion cycle. This voltage must also be free of
noise and ripple with respect to analog ground.
VERROR (MAX) = VPEAK x 2 x π x f(“–”) x 44/fACLK
+
REF
Where f(“–”) is the frequency of the “–” input voltage,
VPEAK is its peak amplitude and fACLK is the frequency of
theACLK. InmostcasesVERROR willnotbesignificant. For
a 60Hz signal on the “–” input to generate a 1/4LSB error
(1.25mV) with the converter running at ACLK = 2MHz, its
peak value would have to be 150mV.
14
EVERY 4 ACLK CYCLES
R
R
OUT
ON
10k
TYP
V
–
REF
REF
13
5pF – 30pF
LTC1090
LTC1090 • AI19
Figure 14. Reference Input Equivalent Circuit
5. Reference Inputs
The voltage between the reference inputs of the LTC1090
defines the voltage span of the A/D converter. The refer-
ence inputs look primarily like a 10kΩ resistor but will
have transient capacitive switching currents due to the
switched capacitor conversion technique (see Figure 14).
During each bit test of the conversion (every 4 ACLK
cycles), a capacitive current spike will be generated on the
reference pins by the A/D. These current spikes settle
quickly and do not cause a problem. However, if slow
settling circuitry is used to drive the reference inputs, care
must be taken to insure that transients caused by these
current spikes settle completely during each bit test of the
conversion.
HORIZONTAL: 1µs/DIV
Figure 15. Adequate Reference Settling
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21
LTC1090
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APPLICATIO S I FOR ATIO
voltage. The offset (which is typically a fixed voltage)
becomes a larger fraction of an LSB as the size of the LSB
is reduced. The typical curve of Unadjusted Offset Error vs
Reference Voltage shows how offset in LSBs is related to
reference voltage for a typical value of VOS. For example,
a VOS of 0.5mV which is 0.1LSB with a 5V reference
becomes 0.5LSB with a 1V reference and 2.5LSBs with a
0.2V reference. If this offset is unacceptable, it can be
corrected digitally by the receiving system or by offsetting
the “–” input to the LTC1090.
HORIZONTAL: 1µs/DIV
Figure 16. Poor Reference Settling Can Cause A/D Errors
6. Reduced Reference Operation
Noise with Reduced VREF
The effective resolution of the LTC1090 can be increased
by reducing the input span of the converter. The LTC1090
exhibits good linearity and gain over a wide range of
reference voltages (see typical curves of Linearity and
Gain Error vs Reference Voltage). However, care must be
taken when operating at low values of VREF because of the
reduced LSB step size and the resulting higher accuracy
requirementplacedontheconverter.Thefollowingfactors
must be considered when operating at low VREF values:
The total input referred noise of the LTC1090 can be
reduced to approximately 200µV peak-to-peak using a
ground plane, good bypassing, good layout techniques
and minimizing noise on the reference inputs. This noise
isinsignificantwitha5Vreferencebutwillbecomealarger
fraction of an LSB as the size of the LSB is reduced. The
typical curve of Noise Error vs Reference Voltage shows
the LSB contribution of this 200µV of noise.
1. Conversion speed (ACLK frequency)
For operation with a 5V reference, the 200µV noise is only
0.04LSB peak-to-peak. In this case, the LTC1090 noise
will contribute virtually no uncertainty to the output code.
However, for reduced references, the noise may become
asignificantfractionofanLSBandcauseundesirablejitter
in the output code. For example, with a 1V reference, this
same 200µV noise is 0.2LSB peak-to-peak. This will
reduce the range of input voltages over which a stable
output code can be achieved by 0.2LSB. If the reference is
further reduced to 200mV, the 200µV noise becomes
equal to one LSB and a stable code may be difficult to
achieve.Inthiscaseaveragingreadingsmaybenecessary.
2. Offset
3. Noise
Conversion Speed with Reduced VREF
With reduced reference voltages, the LSB step size is
reducedandtheLTC1090internalcomparatoroverdriveis
reduced. With less overdrive, more time is required to
perform a conversion. Therefore, the maximum ACLK
frequency should be reduced when low values of VREF are
used. This is shown in the typical curve of Maximum
Conversion Clock Rate vs Reference Voltage.
This noise data was taken in a very clean setup. Any setup
induced noise (noise or ripple on VCC, VREF, VIN or V–) will
add to the internal noise. The lower the reference voltage
to be used, the more critical it becomes to have a clean,
noise-free setup.
Offset with Reduced VREF
The offset of the LTC1090 has a larger effect on the output
code when the A/D is operated with reduced reference
1090fc
22
LTC1090
U
TYPICAL APPLICATIO
A “Quick Look” Circuit for the LTC1090
SNEAK-A-BITTM
The LTC1090’s unique ability to software select the polar-
ity of the differential inputs and the output word length is
used to achieve one more bit of resolution. Using the
circuit below with two conversions and some software, a
2’s complement 10-bit + sign word is returned to memory
inside the MPU. The MC68HC05C4 was chosen as an
example; however, any processor could be used.
Users can get a quick look at the function and timing of the
LTC1090 by using the following simple circuit. REF+ and
DIN are tied to VCC selecting a 5V input span, CH7 as a
single ended input, unipolar mode, MSB first format and
16-bit word length. ACLK and SCLK are tied together and
driven by an external clock. CS is driven at 1/64 the clock
rate by the CD4520 and DOUT outputs the data. All other
pins are tied to a ground plane. The output data from the
Two 10-bit unipolar conversions are performed: the first
over a 0 to 5V span and the second over a 0 to –5V span
(by reversing the polarity of the inputs). The sign of the
input is determined by which of the two spans contained
it.Thentheresultingnumber(rangingfrom–1023to1023
decimal) is converted to 2’s complement notation and
stored in RAM.
D
OUT pin can be viewed on an oscilloscope which is set up
to trigger on the falling edge of CS.
A “Quick Look” Circuit for the LTC1090
5V
4.7µF
f/64
CH0
CH1
CH2
CH3
CH4
CH5
CH6
CH7
COM
DGND
V
CC
Scope Trace of LTC1090 “Quick Look” Circuit
V
DD
ACLK
SCLK
CLK
EN
0.1
Showing A/D Output of 0101010101 (155HEX
)
f
RESET
D
Q1
Q4
Q3
IN
D
Q2
OUT
CS
+
LTC1090
LTC1090
Q3
Q2
Q1
REF
REF
V
Q4
CS
V
–
–
IN
RESET
EN
V
CLK
SS
D
AGND
OUT
CLOCK IN
1MHz MAX
MSB
(B9)
LSB
(B0)
DEGLITCHER
TIME
FILLS
ZERO
TO OSCILLOSCOPE
LTC1090 • TA03
SNEAK-A-BIT Circuit
10µF
LT1021-5
9V
2MHz
CLOCK
CH0
CH1
CH2
CH3
CH4
CH5
CH6
CH7
COM
V
CC
ACLK
SCLK
MC68HC05C4
OTHER CHANNELS
OR SNEAK-A-BIT
INPUTS
SCK
D
MOSI
MISO
CO
IN
D
OUT
LTC1090
CS
V
IN
–5V TO 5V
+
REF
–
REF
–
V
DGND
AGND
0.1µF
–5V
LTC1090 • TA04
SNEAK-A-BIT is a trademark of Linear Technology Corp.
1090fc
23
LTC1090
U
TYPICAL APPLICATIO
Sneak-A-Bit Code for the LTC1090 Using the MC68HC05C4
SNEAK-A-BIT
V
IN
MNEMONIC
DESCRIPTION
5V
5V
V
( + ) CH6
( – ) CH7
IN
READ–/+: LDA #$3F
Load D word for LTC1090 into ACC
IN
1ST CONVERSION
1024 STEPS
JSR TRANSFER Read LTC1090 routine
LDA $60
STA $71
LDA $61
Load MSBs from LTC1090 into ACC
Store MSBs in $71
Load LSBs from LTC1090 into ACC
Store LSBs in $72
SOFTWARE
1ST CONVERSION
2047 STEPS
0V
0V
0V
STA $72
2ND CONVERSION
1024 STEPS
RTS
Return
V
( – ) CH6
( + ) CH7
IN
READ+/–: LDA #$7F
Load D word for LTC1090 into ACC
IN
JSR TRANSFER Read LTC1090 routine
LDA $60
STA $73
–5V
–5V
Load MSBs from LTC1090 into ACC
Store MSBs in $73
2ND CONVERSION
LDA $61
STA $74
Load LSBs from LTC1090 into ACC
Store LSBs in $74
SNEAK-A-BIT Code
RTS
Return
TRANSFER:BCLR 0, $02
STA $0C
LOOP 1: TST $0B
BPL LOOP 1
LDA $0C
STA $0C
STA $60
LOOP 2: TST $0B
BPL LOOP 2
BSET 0, $02
LDA $0C
CS goes low
D
from LTC1090 in MC68HC05C4 RAM
Sign
OUT
Load D into SPI. Start transfer
IN
Test status of SPlF
Loop to previous instruction if not done
Load contents of SPI data reg into ACC
Start next cycle
Store MSBs in $60
Test status of SPlF
Loop to previous instruction if not done
CS goes high
Load contents of SPI data reg into ACC
Location $77
B10 B9 B8 B7 B6 B5 B4 B3
LSB
B2 B1 B0
filled with 0s
Location $87
D
words for LTC1090
IN
MSBF
STA $61
RTS
CHK SIGN: LDA $73
Store LSBs in $61
Return
MUX Addr.
(ODD/SIGN)
UNI
Word
Length
Load MSBs of +/–read into ACC
Or ACC (MSBs) with LSBs of +/–read
If result is 0 goto minus
Clear carry
Rotate right $73 through carry
Rotate right $74 through carry
Load MSBs of +/–read into ACC
Store MSBs in RAM location $77
Load LSBs of +/–read into ACC
Store LSBs in RAM location $87
Goto end of routine
ORA $74
BEQ MINUS
CLC
ROR $73
ROR $74
LDA $73
STA $77
LDA $74
STA $87
D
D
D
1
2
3
0
0
0
0
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
IN
IN
IN
1
0
1
1
LTC1090 • TA05
BRA END
CLC
Sneak-A-Bit Code for the LTC1090 Using the MC68HC05C4
MINUS:
Clear carry
ROR $71
ROR $72
COM $71
COM $72
LDA $72
ADD #$01
STA $72
CLRA
ADC $71
STA $71
STA $77
LDA $72
STA $87
RTS
Shift MSBs of – /+ read right
Shift LSBs of – /+ read right
1’s complement of MSBs
1’s complement of LSBs
Load LSBs into ACC
Add 1 to LSBs
Store ACC in $72
Clear ACC
Add with carry to MSBs. Result in ACC
Store ACC in $71
Store MSBs in RAM location $77
Load LSBs in ACC
Store LSBs in RAM location $87
MNEMONIC
DESCRIPTION
LDA #$50
Configuration data for SPCR
Load configuration data into $0A
Configuration data for port C DDR
Load configuration data into port C DDR
Make sure CS is high
STA
LDA #$FF
STA $06
BSET 0, $02
$0A
JSR
READ–/+
Dummy read configures LTC1090 for next
read
JSR
JSR
JSR
READ+/–
READ–/+
CHK SIGN
Read CH6 with respect to CH7
Read CH7 with respect to CH6
Determines which reading has valid data,
converts to 2’s complement and stores in
RAM
END:
Return
1090fc
24
LTC1090
U
PACKAGE DESCRIPTIO
J Package
20-Lead CERDIP (Narrow .300 Inch, Hermetic)
(Reference LTC DWG # 05-08-1110)
1.060
(26.924)
MAX
CORNER LEADS OPTION
(4 PLCS)
20
19
18
17
16
15
14
13
12
11
10
0.023 – 0.045
(0.584 – 1.143)
HALF LEAD
OPTION
0.025
(0.635)
RAD TYP
0.220 – 0.310
(5.588 – 7.874)
0.045 – 0.068
(1.143 – 1.727)
FULL LEAD
OPTION
1
2
3
4
5
6
7
8
9
0.005
(0.127)
MIN
0.200
(5.080)
MAX
0.300 BSC
(0.762 BSC)
0.015 – 0.060
(0.381 – 1.524)
0.008 – 0.018
(0.203 – 0.457)
0° – 15°
0.125
(3.175)
MIN
0.045 – 0.065
(1.143 – 1.651)
0.100
(2.54)
BSC
NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE
OR TIN PLATE LEADS
0.014 – 0.026
J20 1298
(0.356 – 0.660)
OBSOLETE PACKAGE
1090fc
25
LTC1090
U
PACKAGE DESCRIPTIO
N Package
20-Lead PDIP (Narrow .300 Inch)
(Reference LTC DWG # 05-08-1510)
1.040*
(26.416)
MAX
20
19
18
17
16
15
14
13
12
11
10
0.255 ± 0.015*
(6.477 ± 0.381)
3
4
5
6
7
8
9
1
2
0.300 – 0.325
0.045 – 0.065
0.130 ± 0.005
(7.620 – 8.255)
(1.143 – 1.651)
(3.302 ± 0.127)
0.020
(0.508)
MIN
0.065
(1.651)
TYP
0.009 – 0.015
(0.229 – 0.381)
+0.035
0.325
0.005
(0.127)
MIN
0.100
(2.54)
BSC
–0.015
0.125
(3.175)
MIN
0.018 ± 0.003
(0.457 ± 0.076)
+0.889
8.255
(
)
–0.381
*THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS.
MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.010 INCH (0.254mm)
N20 1098
1090fc
26
LTC1090
U
PACKAGE DESCRIPTIO
SW Package
20-Lead Plastic Small Outline (Wide .300 Inch)
(Reference LTC DWG # 05-08-1620)
0.496 – 0.512*
(12.598 – 13.005)
19 18
16
14 13 12 11
20
17
15
0.394 – 0.419
(10.007 – 10.643)
NOTE 1
0.291 – 0.299**
(7.391 – 7.595)
2
3
5
7
8
9
10
1
4
6
0.037 – 0.045
(0.940 – 1.143)
0.093 – 0.104
(2.362 – 2.642)
0.010 – 0.029
(0.254 – 0.737)
× 45°
0° – 8° TYP
0.050
(1.270)
BSC
0.004 – 0.012
0.009 – 0.013
(0.102 – 0.305)
NOTE 1
0.016 – 0.050
(0.406 – 1.270)
(0.229 – 0.330)
0.014 – 0.019
S20 (WIDE) 1098
(0.356 – 0.482)
TYP
NOTE:
1. PIN 1 IDENT, NOTCH ON TOP AND CAVITIES ON THE BOTTOM OF PACKAGES ARE THE MANUFACTURING OPTIONS.
THE PART MAY BE SUPPLIED WITH OR WITHOUT ANY OF THE OPTIONS
*DIMENSION DOES NOT INCLUDE MOLD FLASH. MOLD FLASH SHALL NOT EXCEED 0.006" (0.152mm) PER SIDE
**DIMENSION DOES NOT INCLUDE INTERLEAD FLASH. INTERLEAD FLASH SHALL NOT EXCEED 0.010" (0.254mm) PER SIDE
1090fc
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
27
LTC1090
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
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ON
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LTC1852/LTC1853
LTC2404/LTC2408
LTC2424/LTC2428
LowPower, SmallSize
5V, Programmable MUX and Sequencer
3V or 5V, Programmable MUX and Sequencer
4ppm INL, 10ppm Total Unadjusted Error, 200µA
1.2ppm Noise, 8ppm INL, Pin Compatible with LTC2404/LTC2408
No Latency ∆Σ is a trademark of Linear Technology Corporation.
1090fc
LW/TP 0902 1K REV C • PRINTED IN USA
28 LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
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(408) 432-1900 FAX: (408) 434-0507 www.linear.com
LINEAR TECHNOLOGY CORPORATION 1990
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