LTC1403CMSE [Linear]
Serial 12-Bit/14-Bit, 2.8Msps Sampling ADCs with Shutdown; 串行12位/ 14位, 2.8Msps采样ADC ,带有关断![LTC1403CMSE](http://pdffile.icpdf.com/pdf1/p00082/img/icpdf/LTC1403_434069_icpdf.jpg)
型号: | LTC1403CMSE |
厂家: | ![]() |
描述: | Serial 12-Bit/14-Bit, 2.8Msps Sampling ADCs with Shutdown |
文件: | 总20页 (文件大小:324K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
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LTC1403/LTC1403A
Serial 12-Bit/14-Bit, 2.8Msps
Sampling ADCs with Shutdown
U
FEATURES
DESCRIPTIO
The LTC®1403/LTC1403A are 12-bit/14-bit, 2.8Msps se-
rial ADCs with differential inputs. The devices draw only
4.7mA from a single 3V supply and come in a tiny 10-lead
MS package. A Sleep shutdown feature lowers power
consumption to 10µW. The combination of speed, low
power and tiny package makes the LTC1403/LTC1403A
suitable for high speed, portable applications.
■
2.8Msps Conversion Rate
■
Low Power Dissipation: 14mW
■
3V Single Supply Operation
■
2.5V Internal Bandgap Reference can be Overdriven
■
3-Wire Serial Interface
■
Sleep (10µW) Shutdown Mode
■
Nap (3mW) Shutdown Mode
■
80dB Common Mode Rejection
The 80dB common mode rejection allows users to elimi-
nategroundloopsandcommonmodenoisebymeasuring
signals differentially from the source.
■
0V to 2.5V Unipolar Input Range
■
Tiny 10-Lead MS Package
U
The devices convert 0V to 2.5V unipolar inputs differen-
tially. The absolute voltage swing for +AIN and –AIN
extends from ground to the supply voltage.
APPLICATIO S
■
Communications
Data Acquisition Systems
■
The serial interface sends out the conversion results
during the 16 clock cycles following CONV↑ for compat-
ibility with standard serial interfaces. If two additional
clock cycles for acquisition time are allowed after the data
stream in between conversions, the full sampling rate of
2.8Msps can be achieved with a 50.4MHz clock.
■
Uninterrupted Power Supplies
■
Multiphase Motor Control
■
Multiplexed Data Acquisition
, LTC and LT are registered trademarks of Linear Technology Corporation.
W
BLOCK DIAGRA
2nd, 3rd and SFDR
10µF 3V
vs Input Frequency
–44
7
V
–50
–56
LTC1403A
DD
+
–
THREE-
STATE
SERIAL
OUTPUT
PORT
A
A
THD
2nd, SFDR
IN
1
2
+
–62
14-BIT ADC
SDO
S & H
8
–68
–74
IN
–
3rd
–80
–86
14
V
REF
3
4
10
9
CONV
SCK
–92
2.5V
REFERENCE
TIMING
LOGIC
10µF
–98
GND
5
–104
0.1
1
10
100
1403A TA01
6
11
EXPOSED PAD
FREQUENCY (MHz)
1403A TA02
1403af
1
LTC1403/LTC1403A
W W U W
U W
U
ABSOLUTE AXI U RATI GS
(Notes 1, 2)
PACKAGE/ORDER I FOR ATIO
Supply Voltage (VDD)................................................. 4V
Analog Input Voltage
ORDER PART
NUMBER
(Note 3) ....................................–0.3V to (VDD + 0.3V)
Digital Input Voltage ................... – 0.3V to (VDD + 0.3V)
Digital Output Voltage.................. –0.3V to (VDD + 0.3V)
Power Dissipation.............................................. 100mW
Operation Temperature Range
LTC1403C/LTC1403AC............................ 0°C to 70°C
LTC1403I/LTC1403AI ......................... –40°C to 85°C
Storage Temperature Range ................. –65°C to 150°C
Lead Temperature (Soldering, 10 sec).................. 300°C
TOP VIEW
LTC1403CMSE
LTC1403IMSE
LTC1403ACMSE
LTC1403AIMSE
+
–
A
A
1
2
3
4
5
10 CONV
IN
IN
9
8
7
6
SCK
SDO
DD
GND
V
11
REF
GND
GND
V
MSE PACKAGE
10-LEAD PLASTIC MSOP
MSE PART MARKING
TJMAX = 125°C, θJA = 150°C/ W
EXPOSED PAD IS GND (PIN 11)
MUST BE SOLDERED TO PCB
LTBDN
LTBDP
LTADF
LTAFD
Consult LTC Marketing for parts specified with wider operating temperature ranges.
U
CO VERTER CHARACTERISTICS
The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. With internal reference. VDD = 3V
LTC1403
TYP MAX
LTC1403A
TYP MAX
PARAMETER
CONDITIONS
MIN
12
MIN
14
UNITS
Bits
Resolution (No Missing Codes)
Integral Linearity Error
Offset Error
●
●
●
●
(Notes 4, 5, 18)
(Notes 4, 18)
(Note 4, 18)
–2
±0.25
±1
2
–4
±0.5
±2
4
LSB
–10
–30
10
30
–20
–60
20
60
LSB
Gain Error
±5
±10
LSB
Gain Tempco
Internal Reference (Note 4)
External Reference
±15
±1
±15
±1
ppm/°C
ppm/°C
U
U
A ALOG I PUT
The ● denotes the specifications which apply over the full operating temperature range,
otherwise specifications are at TA = 25°C. VDD = 3V
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
V
Analog Differential Input Range (Notes 3, 9)
2.7V ≤ V ≤ 3.3V
●
0 to 2.5
V
V
IN
DD
Analog Common Mode + Differential
Input Range (Note 10)
0 to V
CM
DD
I
Analog Input Leakage Current
●
●
1
µA
pF
ns
ns
ps
IN
C
Analog Input Capacitance
13
IN
t
t
t
Sample-and-Hold Acquisition Time
Sample-and-Hold Aperture Delay Time
Sample-and-Hold Aperture Delay Time Jitter
Analog Input Common Mode Rejection Ratio
(Note 6)
39
ACQ
AP
1
0.3
JITTER
CMRR
f
f
= 1MHz, V = 0V to 3V
= 100MHz, V = 0V to 3V
–60
–15
dB
dB
IN
IN
IN
IN
1403af
2
LTC1403/LTC1403A
U W
DY A IC ACCURACY
The ● denotes the specifications which apply over the full operating temperature range,
otherwise specifications are at TA = 25°C. VDD = 3V
LTC1403
TYP MAX
LTC1403A
TYP MAX
SYMBOL PARAMETER
CONDITIONS
MIN
MIN
UNITS
SINAD
Signal-to-Noise Plus
Distortion Ratio
100kHz Input Signal
1.4MHz Input Signal
100kHz Input Signal, External V = 3.3V,
70.5
70.5
72
73.5
73.5
76.3
dB
dB
dB
●
●
68
70
REF
V
DD
≥ 3.3V
750kHz Input Signal, External V = 3.3V,
72
76.3
dB
REF
V
DD
≥ 3.3V
THD
SFDR
IMD
Total Harmonic
Distortion
100kHz First 5 Harmonics
1.4MHz First 5 Harmonics
–87
–83
–90
–86
dB
dB
–76
–78
Spurious Free
Dynamic Range
100kHz Input Signal
1.4MHz Input Signal
–87
–83
–90
–86
dB
dB
+
Intermodulation
Distortion
1.25V to 2.5V 1.25MHz into A , 0V to 1.25V,
–82
–82
dB
IN
–
1.2MHz into A
IN
Code-to-Code
V
REF
= 2.5V (Note 18)
0.25
1
LSB
RMS
Transition Noise
Full Power Bandwidth
V
= 2.5V , SDO = 11585LSB (Note 15)
50
5
50
5
MHz
MHz
IN
P-P
P-P
Full Linear Bandwidth S/(N + D) ≥ 68dB
U U
U
I TER AL REFERE CE CHARACTERISTICS The ● denotes the specifications which apply over the
full operating temperature range, otherwise specifications are at TA = 25°C. VDD = 3V
PARAMETER
CONDITIONS
= 0
MIN
TYP
2.5
15
MAX
UNITS
V
V
V
V
V
V
Output Voltage
Output Tempco
Line Regulation
Output Resistance
Settling Time
I
OUT
REF
REF
REF
REF
REF
ppm/°C
µV/V
Ω
V
= 2.7V to 3.6V, V = 2.5V
600
0.2
2
DD
REF
Load Current = 0.5mA
ms
U
U
The ● denotes the specifications which apply over the
DIGITAL I PUTS A D DIGITAL OUTPUTS
full operating temperature range, otherwise specifications are at TA = 25°C. VDD = 3V
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
V
High Level Input Voltage
Low Level Input Voltage
Digital Input Current
V
V
V
= 3.3V
= 2.7V
●
●
●
2.4
V
V
IH
IL
DD
DD
IN
0.6
I
= 0V to V
±10
µA
pF
V
IN
DD
C
V
V
Digital Input Capacitance
High Level Output Voltage
Low Level Output Voltage
5
IN
V
= 3V, I = –200µA
OUT
●
2.5
2.9
OH
OL
DD
V
V
= 2.7V, I
= 2.7V, I
= 160µA
= 1.6mA
0.05
0.10
V
V
DD
DD
OUT
OUT
●
●
0.4
I
Hi-Z Output Leakage D
V
= 0V to V
DD
±10
µA
pF
OZ
OUT
OUT
C
Hi-Z Output Capacitance D
1
OZ
OUT
I
I
Output Short-Circuit Source Current
Output Short-Circuit Sink Current
V
V
= 0V, V = 3V
20
15
mA
mA
SOURCE
SINK
OUT
OUT
DD
= V = 3V
DD
1403af
3
LTC1403/LTC1403A
W U
POWER REQUIRE E TS
The ● denotes the specifications which apply over the full operating temperature
range, otherwise specifications are at TA = 25°C. (Note 17)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
Supply Voltage
2.7
3.6
V
DD
I
Positive Supply Voltage
Active Mode
Nap Mode
Sleep Mode (LTC1403)
Sleep Mode (LTC1403A)
●
●
4.7
1.1
2
7
mA
mA
µA
DD
1.5
15
10
2
µA
P
Power Dissipation
Active Mode with SCK in Fixed State (Hi or Lo)
12
mW
D
W U
TI I G CHARACTERISTICS
The ● denotes the specifications which apply over the full operating temperature
range, otherwise specifications are at TA = 25°C. VDD = 3V
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
f
Maximum Sampling Frequency per Channel
(Conversion Rate)
●
2.8
MHz
SAMPLE(MAX)
t
t
t
t
t
t
t
t
t
t
t
t
t
t
Minimum Sampling Period (Conversion + Acquisiton Period)
Clock Period
●
●
357
ns
THROUGHPUT
(Note 16)
19.8
16
2
10000
ns
SCK
Conversion Time
(Note 6)
18
SCLK cycles
CONV
Minimum Positive or Negative SCLK Pulse Width
CONV to SCK Setup Time
(Note 6)
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ms
1
(Notes 6, 10)
(Note 6)
3
2
Nearest SCK Edge Before CONV
0
3
Minimum Positive or Negative CONV Pulse Width
SCK to Sample Mode
(Note 6)
4
4
(Note 6)
4
5
CONV to Hold Mode
(Notes 6, 11)
(Notes 6, 7, 13)
(Notes 6, 12)
(Notes 6, 12)
(Notes 6, 12)
(Notes 6, 14)
1.2
45
8
6
16th SCK↑ to CONV↑ Interval (Affects Acquisition Period)
Minimum Delay from SCK to Valid Bits 0 Through 13
SCK to Hi-Z at SDO
7
8
6
9
Previous SDO Bit Remains Valid After SCK
2
10
12
V
Settling Time After Sleep-to-Wake Transition
2
REF
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
cycle later. It is best for CONV to rise half a clock before SCK, when
running the clock at rated speed.
Note 2: All voltage values are with respect to GND.
Note 3: When these pins are taken below GND or above V , they will be
clamped by internal diodes. This product can handle input currents greater
Note 11: Not the same as aperture delay. Aperture delay is smaller (1ns)
because the 2.2ns delay through the sample-and-hold is subtracted from
the CONV to Hold mode delay.
DD
than 100mA below GND or greater than V without latchup.
Note 12: The rising edge of SCK is guaranteed to catch the data coming
out into a storage latch.
Note 13: The time period for acquiring the input signal is started by the
DD
Note 4: Offset and full-scale specifications are measured for a single-
+
–
ended A input with A grounded and using the internal 2.5V reference.
IN
IN
16th rising clock and it is ended by the rising edge of convert.
Note 14: The internal reference settles in 2ms after it wakes up from Sleep
mode with one or more cycles at SCK and a 10µF capacitive load.
Note 5: Integral linearity is tested with an external 2.55V reference and is
defined as the deviation of a code from the straight line passing through
the actual endpoints of a transfer curve. The deviation is measured from
the center of quantization band.
Note 15: The full power bandwidth is the frequency where the output code
Note 6: Guaranteed by design, not subject to test.
Note 7: Recommended operating conditions.
swing drops to 3dB with a 2.5V input sine wave.
Note 16: Maximum clock period guarantees analog performance during
conversion. Output data can be read without an arbitrarily long clock.
P-P
Note 8: The analog input range is defined for the voltage difference
+
–
between A and A
.
Note 17: V = 3V, f
= 2.8Msps.
SAMPLE
IN
IN
DD
+
–
Note 9: The absolute voltage at A and A must be within this range.
Note 18: The LTC1403A is measured and specified with 14-bit Resolution
(1LSB = 152µV) and the LTC1403 is measured and specified with 12-bit
Resolution (1LSB = 610µV).
IN
IN
Note 10: If less than 3ns is allowed, the output data will appear one clock
1403af
4
LTC1403/LTC1403A
U W
TYPICAL PERFOR A CE CHARACTERISTICS
TA = 25°C, VDD = 3V (LTC1403A)
ENOBs and SINAD
vs Input Frequency
THD, 2nd and 3rd vs Input
Frequency
SFDR vs Input Frequency
–44
–50
–56
–62
104
98
92
86
80
74
68
62
56
50
44
12.0
11.5
11.0
10.5
10.0
9.5
74
71
68
65
62
59
56
53
50
THD
2nd
–68
–74
3rd
–80
–86
9.0
–92
8.5
–98
–104
8.0
0.1
1
10
100
0.1
1
10
100
0.1
1
10
100
FREQUENCY (MHz)
FREQUENCY (MHz)
FREQUENCY (MHz)
1403A G02
1403A G17
1403A G01
98kHz Sine Wave 4096 Point
FFT Plot
1.3MHz Sine Wave 4096 Point
FFT Plot
SNR vs Input Frequency
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
–120
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
–120
74
71
68
65
62
59
56
53
50
2.8Msps
2.8Msps
0
350k
700k
1.05M
1.4M
0
350k
700k
1.05M
1.4M
0.1
1
10
100
FREQUENCY (Hz)
FREQUENCY (Hz)
FREQUENCY (MHz)
1403A G03
1403A G04
1403A G05
1.4MHz Input Summed with
1.56MHz Input IMD 4096 Point
FFT Plot
Differential Linearity
vs Output Code
Integral Linearity
vs Output Code
4
3
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
–110
–120
1.0
0.8
2.8Msps
0.6
2
0.4
1
0.2
0
0
–0.2
–0.4
–0.6
–0.8
–1.0
–1
–2
–3
–4
0
4096
8192
12288
16383
0
350k
700k
1.05M
1.4M
0
4096
8192
12288
16383
OUTPUT CODE
FREQUENCY (Hz)
OUTPUT CODE
1403A G14
1403A G06
1403A G13
1403af
5
LTC1403/LTC1403A
U W
TA = 25°C, VDD = 3V (LTC1403A)
TYPICAL PERFOR A CE CHARACTERISTICS
Differential and Integral Linearity
vs Conversion Rate
SINAD vs Conversion Rate
80
79
78
77
76
75
74
73
72
71
70
5
4
18 CLOCKS PER CONVERSION
EXTERNAL V
= 3.3V f ~f /3
IN
MAX INL
REF
S
3
2
MAX DNL
EXTERNAL V
= 3.3V f ~f /40
IN
REF
S
1
0
–1
–2
–3
–4
–5
MIN DNL
MIN INL
INTERNAL V
= 2.5V f ~f /40
IN
REF
S
INTERNAL V
= 2.5V f ~f /3
IN
REF
S
2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0
CONVERSION RATE (Msps)
2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 4.0
CONVERSION RATE (Msps)
1403A G16
1403A G15
TA = 25°C, VDD = 3V (LTC1403 and LTC1403A)
2.5VP-P Power Bandwidth
CMRR vs Frequency
PSRR vs Frequency
0
–20
12
–25
–30
–35
–40
–45
–50
–55
–60
–65
6
0
–40
–6
–12
–18
–60
–80
–24
–30
–36
–100
–120
–70
100
10k
100k 1M
10M 100M
1k
1M
10M
100M
1G
1
10
100
1k
10k 100k
1M
FREQUENCY (Hz)
FREQUENCY (Hz)
FREQUENCY (Hz)
1403A G07
1403A G09
1403A G08
Reference Voltage vs Load
Current
VDD Supply Current vs
Conversion Rate
Reference Voltage vs VDD
2.4902
2.4900
2.4898
2.4896
2.4894
2.4892
2.4890
2.4902
2.4900
2.4898
2.4896
2.4894
2.4892
2.4890
6.0
5.5
5.0
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
0
0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0
LOAD CURRENT (mA)
2.6
2.8
3.0
3.2
(V)
3.4
3.6
0
0.4 0.8 1.2 1.6 2.0 2.4 2.8 3.2 3.6 4.0
CONVERSION RATE (Msps)
V
DD
1403A G10
1403A G11
1403A G12
1403af
6
LTC1403/LTC1403A
U
U
U
PI FU CTIO S
+
+
AIN (Pin 1): Noninverting Analog Input. AIN operates
fully differentially with respect to AIN– with a 0V to 2.5V
differential swing and a 0V to VDD common mode swing.
10µF tantalum in parallel with 0.1µF ceramic). Keep in
mindthatinternalanalogcurrentsanddigitaloutputsignal
currents flow through this pin. Care should be taken to
place the 0.1µF bypass capacitor as close to Pins 6 and 7
as possible.
–
–
AIN (Pin 2): Inverting Analog Input. AIN operates fully
+
differentially with respect to AIN with a –2.5V to 0V
differential swing and a 0V to VDD common mode swing.
SDO (Pin 8): Three-State Serial Data Output. Each of
output data words represents the difference between
AIN+ and AIN– analog inputs at the start of the previous
conversion.
VREF (Pin 3): 2.5V Internal Reference. Bypass to GND and
to a solid analog ground plane with a 10µF ceramic
capacitor (or 10µF tantalum in parallel with 0.1µF ce-
ramic). Can be overdriven by an external reference be-
tween 2.55V and VDD.
SCK (Pin 9): External Clock Input. Advances the conver-
sion process and sequences the output data on the rising
edge. Responds to TTL (≤3V) and 3V CMOS levels. One
or more pulses wake from sleep.
GND (Pins 5, 6, 11): Ground and Exposed Pad. These
ground pins and the exposed pad must be tied directly to
the solid ground plane under the part. Keep in mind that
analog signal currents and digital output signal currents
flow through these pins.
CONV (Pin 10): Convert Start. Holds the analog input
signal and starts the conversion on the rising edge.
Responds to TTL (≤3V) and 3V CMOS levels. Two pulses
with SCK in fixed high or fixed low state start Nap mode.
Four or more pulses with SCK in fixed high or fixed low
state start Sleep mode.
VDD (Pin 7): 3V Positive Supply. This single power pin
supplies3Vtotheentirechip.BypasstoGNDandtoasolid
analog ground plane with a 10µF ceramic capacitor (or
W
BLOCK DIAGRA
10µF 3V
7
V
LTC1403A
DD
+
–
THREE-
STATE
SERIAL
OUTPUT
PORT
A
A
IN
1
2
+
14-BIT ADC
SDO
S & H
8
IN
–
14
V
REF
3
4
10
9
CONV
SCK
2.5V
REFERENCE
TIMING
LOGIC
10µF
GND
5
1403A BD
6
11
EXPOSED PAD
1403af
7
LTC1403/LTC1403A
W U
W
TI I G DIAGRA
LTC1403 Timing Diagram
t
2
t
7
t
3
t
1
16
17
1
2
3
4
5
6
7
8
9
10
11
12
13
15
t
16
17
18
1
14
SCK
t
4
5
CONV
t
6
t
ACQ
INTERNAL
S/H STATUS
SAMPLE
HOLD
SAMPLE
HOLD
t
t
9
t
8
t
8
10
SDO REPRESENTS THE ANALOG INPUT FROM THE PREVIOUS CONVERSION
Hi-Z
Hi-Z
SDO
D11 D10 D9 D8 D7 D6 D5 D4 D3 D2 D1
D0
X
X
1403A TD01
14-BIT DATA WORD
CONV
t
t
THROUGHPUT
*BITS MARKED "X" AFTER D0 SHOULD BE IGNORED.
LTC1403A Timing Diagram
t
2
t
7
t
t
1
3
16
17
1
2
3
4
5
6
7
8
9
10
11
12
13
15
t
16
17
18
1
14
SCK
t
4
5
CONV
t
6
t
ACQ
INTERNAL
S/H STATUS
SAMPLE
HOLD
SAMPLE
HOLD
t
t
t
8
t
8
9
10
SDO REPRESENTS THE ANALOG INPUT FROM THE PREVIOUS CONVERSION
Hi-Z
Hi-Z
SDO
D13 D12 D11 D10 D9 D8 D7 D6 D5 D4 D3
D2
D1
D0
1403A TD01b
14-BIT DATA WORD
CONV
t
t
THROUGHPUT
Nap Mode and Sleep Mode Waveforms
SLK
t
1
t
1
CONV
NAP
SLEEP
t
12
V
1403A TD02
REF
NOTE: NAP AND SLEEP ARE INTERNAL SIGNALS
SCK to SDO Delay
SCK
SCK
V
V
IH
IH
t
10
8
t
t
9
V
V
90%
10%
OH
OL
SDO
SDO
1403A TD03
1403af
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LTC1403/LTC1403A
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APPLICATIO S I FOR ATIO
DRIVING THE ANALOG INPUT
detailed information is available in the Linear Technology
Databooks and on the LinearViewTM CD-ROM.)
The differential analog inputs of the LTC1403/LTC1403A are
easy to drive. The inputs may be driven differentially or as a
single-ended input (i.e., the AIN– input is grounded). Both
differential analog inputs, AIN+ with AIN–, are sampled at the
same instant. Any unwanted signal that is common to both
inputsofeachinputpairwillbereducedbythecommonmode
rejectionofthesample-and-holdcircuit.Theinputsdrawonly
one small current spike while charging the sample-and-hold
capacitors at the end of conversion. During conversion, the
analoginputsdrawonlyasmallleakagecurrent. Ifthesource
impedance of the driving circuit is low, then the LTC1403/
LTC1403A inputs can be driven directly. As source imped-
ance increases, so will acquisition time. For minimum acqui-
sition time with high source impedance, a buffer amplifier
must be used. The main requirement is that the amplifier
driving the analog input(s) must settle after the small current
spikebeforethenextconversionstarts(settlingtimemustbe
39ns for full throughput rate). Also keep in mind while
choosing an input amplifier, the amount of noise and har-
monic distortion added by the amplifier.
LTC®1566-1: Low Noise 2.3MHz Continuous Time Low-
Pass Filter.
LT1630:Dual30MHzRail-to-RailVoltageFBAmplifier.2.7V
to ±15V supplies. Very high AVOL, 500µV offset and 520ns
settling to 0.5LSB for a 4V swing. THD and noise are –93dB
to40kHzandbelow1LSBto320kHz(AV =1,2VP-P into1kΩ,
VS =5V), makingthepartexcellentforACapplications(to1/
3 Nyquist) where rail-to-rail performance is desired. Quad
version is available as LT1631.
LT1632:Dual45MHzRail-to-RailVoltageFBAmplifier.2.7V
to ±15V supplies. Very high AVOL, 1.5mV offset and 400ns
settling to 0.5LSB for a 4V swing. It is suitable for applica-
tions with a single 5V supply. THD and noise are
–93dB to 40kHz and below 1LSB to 800kHz (AV = 1,
2VP-P into 1kΩ, VS = 5V), making the part excellent for AC
applications where rail-to-rail performance is desired.Quad
version is available as LT1633.
LT1813: Dual 100MHz 750V/µs 3mA Voltage Feedback
Amplifier. 5V to ±5V supplies. Distortion is –86dB to 100kHz
and –77dB to 1MHz with ±5V supplies (2VP-P into 500Ω).
Excellent part for fast AC applications with ±5V supplies.
CHOOSING AN INPUT AMPLIFIER
Choosing an input amplifier is easy if a few requirements are
taken into consideration. First, to limit the magnitude of the
voltage spike seen by the amplifier from charging the sam-
pling capacitor, choose an amplifier that has a low output
impedance(<100Ω)attheclosed-loopbandwidthfrequency.
For example, if an amplifier is used in a gain of 1 and has a
unity-gain bandwidth of 50MHz, then the output impedance
at 50MHz must be less than 100Ω. The second requirement
is that the closed-loop bandwidth must be greater than
40MHz to ensure adequate small-signal settling for full
throughput rate. If slower op amps are used, more time for
settling can be provided by increasing the time between
conversions. The best choice for an op amp to drive the
LTC1403/LTC1403A will depend on the application. Gener-
ally, applications fall into two categories: AC applications
where dynamic specifications are most critical and time
domainapplicationswhereDCaccuracyandsettlingtimeare
most critical. The following list is a summary of the op amps
that are suitable for driving the LTC1403/LTC1403A. (More
LT1801: 80MHz GBWP, –75dBc at 500kHz, 2mA/Amplifier,
8.5nV/√Hz.
LT1806/LT1807:325MHzGBWP,–80dBcDistortionat5MHz,
Unity-GainStable,R-RInandOut,10mA/Amplifier,3.5nV/√Hz.
LT1810: 180MHz GBWP, –90dBc Distortion at 5MHz,
Unity-GainStable,R-RInandOut,15mA/Amplifier,16nV/√Hz.
LT1818/LT1819:400MHz,2500V/µs,9mA,Single/DualVolt-
age Mode Operational Amplifier.
LT6200: 165MHz GBWP, –85dBc Distortion at 1MHz, Unity-
Gain Stable, R-R In and Out, 15mA/Amplifier,
0.95nV/√Hz.
LT6203: 100MHz GBWP, –80dBc Distortion at 1MHz,
Unity-Gain Stable, R-R In and Out, 3mA/Amplifier,
1.9nV/√Hz.
LT6600-10: Amplifier/Filter Differential In/Out with 10MHz
Cutoff.
LinearView is a trademark of Linear Technology Corporation.
1403af
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51Ω
1
+
A
A
V
IN
47pF
3
3V
V
REF
REF
2
–
IN
LTC1403/
LTC1403A
REF
LTC1403/
LTC1403A
10µF
3
11
GND
10µF
11
1403A F02
GND
1403A F01
Figure 1. RC Input Filter
Figure 2
INPUT FILTERING AND SOURCE IMPEDANCE
INPUT RANGE
The noise and the distortion of the input amplifier and
other circuitry must be considered since they will add to
the LTC1403/LTC1403A noise and distortion. The small-
signalbandwidthofthesample-and-holdcircuitis50MHz.
Any noise or distortion products that are present at the
analog inputs will be summed over this entire bandwidth.
Noisy input circuitry should be filtered prior to the analog
inputs to minimize noise. A simple 1-pole RC filter is
sufficient for many applications. For example, Figure 1
shows a 47pF capacitor from AIN+ to ground and a 51Ω
source resistor to limit the input bandwidth to 47MHz. The
47pF capacitor also acts as a charge reservoir for the input
sample-and-hold and isolates the ADC input from sam-
pling-glitchsensitivecircuitry.Highqualitycapacitorsand
resistors should be used since these components can add
distortion. NPO and silvermica type dielectric capacitors
have excellent linearity. Carbon surface mount resistors
can generate distortion from self heating and from dam-
age that may occur during soldering. Metal film surface
mount resistors are much less susceptible to both prob-
lems. When high amplitude unwanted signals are close in
frequency to the desired signal frequency, a multiple pole
filter is required. High external source resistance, com-
bined with the 13pF of input capacitance, will reduce the
rated 50MHz bandwidth and increase acquisition time
beyond 39ns.
The analog inputs of the LTC1403/LTC1403A may be
driven fully differentially with a single supply. Each input
may swing up to 3VP-P individually. In the conversion
range, the noninverting input of each channel is always up
to 2.5V more positive than the inverting input of each
channel. The 0V to 2.5V range is also ideally suited for
single-ended input use with single supply applications.
The common mode range of the inputs extend from
ground to the supply voltage VDD. If the difference be-
tween the AIN+ and AIN– inputs exceeds 2.5V, the output
code will stay fixed at all ones and if this difference goes
below 0V, the ouput code will stay fixed at all zeros.
INTERNAL REFERENCE
TheLTC1403/LTC1403Ahasanon-chip,temperaturecom-
pensated, bandgap reference that is factory trimmed near
2.5V to obtain 2.5V input span. The reference amplifier
output VREF, (Pin 3) must be bypassed with a capacitor to
ground. The reference amplifier is stable with capacitors
of 1µF or greater. For the best noise performance, a 10µF
ceramicora10µFtantaluminparallelwitha0.1µFceramic
is recommended. The VREF pin can be overdriven with an
external reference as shown in Figure 2. The voltage of the
external reference must be higher than the 2.5V of the
class A pull-up output of the internal reference. The
recommended range for an external reference is 2.55V to
VDD. Anexternalreferenceat2.55VwillseeaDCquiescent
load of 0.75mA and as much as 3mA during conversion.
1403af
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LTC1403/LTC1403A Transfer
Characteristic
CMRR vs Frequency
0
111...111
111...110
111...101
–20
–40
–60
–80
000...010
000...001
000...000
–100
–120
100
10k
100k 1M
10M 100M
1k
0
FS – 1LSB
FREQUENCY (Hz)
INPUT VOLTAGE (V)
1403A F03
1403A F05
Figure 3
Figure 4
INPUT SPAN VERSUS REFERENCE VOLTAGE
the inputs. The common mode rejection holds up at
extremelyhighfrequencies,seeFigure3.Theonlyrequire-
ment is that both inputs not go below ground or exceed
VDD. Integral nonlinearity errors (INL) and differential
nonlinearity errors (DNL) are largely independent of the
common mode voltage. However, the offset error will
vary. The change in offset error is typically less than 0.1%
of the common mode voltage.
The differential input range has a unipolar voltage span
that equals the difference between the voltage at the
referencebufferoutputVREF atPin3, andthevoltageatthe
ground (Exposed Pad Ground). The differential input
range of the ADC is 0V to 2.5V when using the internal
reference. The internal ADC is referenced to these two
nodes. This relationship also holds true with an external
reference.
Figure 4 shows the ideal input/output characteristics for
the LTC1403/LTC1403A. The code transitions occur mid-
way between successive integer LSB values (i.e., 0.5LSB,
1.5LSB, 2.5LSB, FS – 1.5LSB). The output code is natural
binarywith1LSB=2.5V/16384=153µVfortheLTC1403A,
and 1LSB = 2.5V/4096 = 610µV for the LTC1403. The
LTC1403A has 1LSB RMS of random white noise.
DIFFERENTIAL INPUTS
The LTC1403/LTC1403A has a unique differential sample-
and-hold circuit that allows inputs from ground to VDD.
The ADC will always convert the unipolar difference of
AIN+ – AIN–, independent of the common mode voltage at
1403af
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optimumperformance, a10µFsurfacemountAVXcapaci-
tor with a 0.1µF ceramic is recommended for the VDD and
VREF pins. Alternatively, 10µF ceramic chip capacitors
such as Murata GRM235Y5V106Z016 may be used. The
capacitorsmustbelocatedasclosetothepinsaspossible.
The traces connecting the pins and the bypass capacitors
must be kept short and should be made as wide as
possible.
Figure5showstherecommendedsystemgroundconnec-
tions. All analog circuitry grounds should be terminated at
the LTC1403/LTC1403A GND (Pins 4, 5, 6 and exposed
pad). The ground return from the LTC1403/LTC1403A
(Pins 4, 5, 6 and exposed pad) to the power supply should
belowimpedancefornoisefreeoperation.Digitalcircuitry
groundsmustbeconnectedtothedigitalsupplycommon.
In applications where the ADC data outputs and control
signals are connected to a continuously active micropro-
cessor bus, it is possible to get errors in the conversion
results. These errors are due to feedthrough from the
microprocessor to the successive approximation com-
parator. The problem can be eliminated by forcing the
microprocessor into a Wait state during conversion or by
using three-state buffers to isolate the ADC data bus.
Figure 5. Recommended Layout
Board Layout and Bypassing
POWER-DOWN MODES
Wire wrap boards are not recommended for high resolu-
tion and/or high speed A/D converters. To obtain the best
performance from the LTC1403/LTC1403A, a printed cir-
cuit board with ground plane is required. Layout for the
printed circuit board should ensure that digital and analog
signal lines are separated as much as possible. In particu-
lar, care should be taken not to run any digital track
alongside an analog signal track. If optimum phase match
between the inputs is desired, the length of the two input
wires should be kept matched.
Upon power-up, the LTC1403/LTC1403A is initialized to
the active state and is ready for conversion. The Nap and
Sleep mode waveforms show the power-down modes for
the LTC1403/LTC1403A. The SCK and CONV inputs con-
trol the power-down modes (see Timing Diagrams). Two
rising edges at CONV, without any intervening rising
edges at SCK, put the LTC1403/LTC1403A. in Nap mode
and the power drain drops from 14mW to 6mW. The
internal reference remains powered in Nap mode. One or
morerisingedgesatSCKwakeuptheLTC1403/LTC1403A
for service very quickly, and CONV can start an accurate
conversion within a clock cycle. Four rising edges at
High quality tantalum and ceramic bypass capacitors
should be used at the VDD and VREF pins as shown in the
Block Diagram on the first page of this data sheet. For
1403af
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LTC1403/LTC1403A
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APPLICATIO S I FOR ATIO
CONV, without any intervening rising edges at SCK, put
the LTC1403/LTC1403A in Sleep mode and the power
drain drops from 16mW to 10µW. One or more rising
edges at SCK wake up the LTC1403/LTC1403A for opera-
tion. The internal reference (VREF ) takes 2ms to slew and
settle with a 10µF load. Note that, using sleep mode more
frequentlythanevery2ms, compromisesthesettledaccu-
racyoftheinternalreference. Notethat, forslowerconver-
sion rates, the Nap and Sleep modes can be used for
substantial reductions in power consumption.
sync input of the processor serial port. It is good practice
to drive the LTC1403/LTC1403A CONV input first to avoid
digital noise interference during the sample-to-hold tran-
sition triggered by CONV at the start of conversion. It is
also good practice to keep the width of the low portion of
the CONV signal greater than 15ns to avoid introducing
glitches in the front end of the ADC just before the sample-
and-hold goes into hold mode at the rising edge of CONV.
Minimizing Jitter on the CONV Input
Inhighspeedapplicationswherehighamplitudesinewaves
above 100kHz are sampled, the CONV signal must have as
little jitter as possible (10ps or less). The square wave
output of a common crystal clock module usually meets
this requirement easily. The challenge is to generate a
CONV signal from this crystal clock without jitter corrup-
tion from other digital circuits in the system. A clock
divider and any gates in the signal path from the crystal
clock to the CONV input should not share the same
integratedcircuitwithotherpartsofthesystem. Asshown
intheinterfacecircuitexamples, theSCKandCONVinputs
should be driven first, with digital buffers used to drive the
serial port interface. Also note that the master clock in the
DSP may already be corrupted with jitter, even if it comes
directly from the DSP crystal. Another problem with high
speed processor clocks is that they often use a low cost,
low speed crystal (i.e., 10MHz) to generate a fast, but
jittery, phase-locked-loop system clock (i.e., 40MHz). The
jitter in these PLL-generated high speed clocks can be
several nanoseconds. Note that if you choose to use the
frame sync signal generated by the DSP port, this signal
will have the same jitter of the DSP’s master clock.
DIGITAL INTERFACE
The LTC1403/LTC1403A has a 3-wire SPI (Serial Protocol
Interface) interface. The SCK and CONV inputs and SDO
output implement this interface. The SCK and CONV
inputs accept swings from 3V logic and are TTL compat-
ible, if the logic swing does not exceed VDD. A detailed
description of the three serial port signals follows:
Conversion Start Input (CONV)
The rising edge of CONV starts a conversion, but subse-
quent rising edges at CONV are ignored by the LTC1403/
LTC1403A until the following 16 SCK rising edges have
occurred. It is necessary to have a minimum of 16 rising
edges of the clock input SCK between rising edges of
CONV. But to obtain maximum conversion speed, it is
necessary to allow two more clock periods between con-
versions to allow 39ns of acquisition time for the internal
ADC sample-and-hold circuit. With 16 clock periods per
conversion, the maximum conversion rate is limited to
2.8Msps to allow 39ns for acquisition time. In either case,
the output data stream comes out within the first 16 clock
periods to ensure compatibility with processor serial
ports. The duty cycle of CONV can be arbitrarily chosen to
be used as a frame sync signal for the processor serial
port. A simple approach to generate CONV is to create a
pulsethatisoneSCKwidetodrivetheLTC1403/LTC1403A
and then buffer this signal with the appropriate number of
inverters to ensure the correct delay driving the frame
Serial Clock Input (SCK)
The rising edge of SCK advances the conversion process
and also udpates each bit in the SDO data stream. After
CONVrises,thethirdrisingedgeofSCKstartsclockingout
the 12/14 data bits with the MSB sent first. A simple
approach is to generate SCK to drive the LTC1403/
1403af
13
LTC1403/LTC1403A
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APPLICATIO S I FOR ATIO
LTC1403A first and then buffer this signal with the appro-
priate number of inverters to drive the serial clock input of
the processor serial port. Use the falling edge of the clock
to latch data from the Serial Data Output (SDO) into your
processor serial port. The 14-bit Serial Data will be re-
ceived right justified, in a 16-bit word with 16 or more
clocks per frame sync. It is good practice to drive the
LTC1403/LTC1403A SCK input first to avoid digital noise
interference during the internal bit comparison decision
by the internal high speed comparator. Unlike the CONV
input, the SCK input is not sensitive to jitter because the
input signal is already sampled and held constant.
HARDWARE INTERFACE TO TMS320C54x
The LTC1403/LTC1403A is a serial output ADC whose
interface has been designed for high speed buffered serial
ports in fast digital signal processors (DSPs). Figure 6
shows an example of this interface using a TMS320C54X.
The buffered serial port in the TMS320C54x has direct
accesstoa2kBsegmentofmemory. TheADC’sserialdata
can be collected in two alternating 1kB segments, in real
time, at the full 2.8Msps conversion rate of the LTC1403/
LTC1403A.TheDSPassemblycodesetsframesyncmode
at the BFSR pin to accept an external positive going pulse
and the serial clock at the BCLKR pin to accept an external
positive edge clock. Buffers near the LTC1403/LTC1403A
may be added to drive long tracks to the DSP to prevent
corruption of the signal to LTC1403/LTC1403A. This con-
figuration is adequate to traverse a typical system board,
but source resistors at the buffer outputs and termination
resistors at the DSP, may be needed to match the charac-
teristic impedance of very long transmission lines. If you
need to terminate the SDO transmission line, buffer it first
with one or two 74ACTxx gates. The TTL threshold inputs
of the DSP port respond properly to the 3V swing from the
SDO pin.
Serial Data Output (SDO)
Upon power-up, the SDO output is automatically reset to
the high impedance state. The SDO output remains in high
impedance until a new conversion is started. SDO sends
out 12/14 bits in the output data stream beginning at the
thirdrisingedgeofSCKaftertherisingedgeofCONV.SDO
is always in high impedance mode when it is not sending
out data bits. Please note the delay specification from SCK
to a valid SDO. SDO is always guaranteed to be valid by the
next rising edge of SCK. The 16-bit output data stream is
compatible with the 16-bit or 32-bit serial port of most
processors.
3V
7
5V
V
V
CC
DD
10
9
CONV
SCK
BFSR
BCLKR
BDR
B13 B12
8
6
SDO
GND
LTC1403/
LTC1403A
TMS320C54x
CONV
CLK
3-WIRE SERIAL
INTERFACELINK
1403A F09
0V TO 3V LOGIC SWING
Figure 6. DSP Serial Interface to TMS320C54x
1403af
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; 01-08-01 ******************************************************************
; Files: 014SI.ASM -> 1403A Sine wave collection with Serial Port interface
;
;
bvectors.asm
s2k14ini.asm
buffered mode to avoid standard mode bug.
2k buffer size.
; first element at 1024, last element at 1023, two middles at 2047 and 0000
; unipolar mode
; Works 16 or 64 clock frames.
; negative edge BCLKR
; negative BFSR pulse
; -0 data shifted
; 1' cable from counter to CONV at DUT
; 2' cable from counter to CLK at DUT
; ***************************************************************************
.width
160
.length 110
.title "sineb0 BSP in auto buffer mode"
.mmregs
.setsect ".text",
0x500,0
;Set address of executable
.setsect "vectors", 0x180,0
.setsect "buffer", 0x800,0
.setsect "result", 0x1800,0
.text
;Set address of incoming 1403 data
;Set address of BSP buffer for clearing
;Set address of result for clearing
;.text marks start of code
start:
;this label seems necessary
;Make sure /PWRDWN is low at J1-9
;to turn off AC01 adc
tim=#0fh
prd=#0fh
tcr = #10h
tspc = #0h
pmst = #01a0h
sp = #0700h
dp = #0
; stop timer
; stop TDM serial port to AC01
; set up iptr. Processor Mode STatus register
; init stack pointer.
; data page
ar2 = #1800h
ar3 = #0800h
ar4 = #0h
; pointer to computed receive buffer.
; pointer to Buffered Serial Port receive buffer
; reset record counter
call sineinit
; Double clutch the initialization to insure a proper
sinepeek:
call sineinit
; reset. The external frame sync must occur 2.5 clocks
; or more after the port comes out of reset.
wait
;
goto
wait
----------------Buffered Receive Interrupt Routine ------------------
breceive:
ifr = #10h
TC = bitf(@BSPCE,#4000h) ; check which half (bspce(bit14)) of buffer
if (NTC) goto bufull ; if this still the first half get next half
; clear interrupt flags
bspce = #(2023h + 08000h); turn on halt for second half (bspce(bit15))
return_enable
;
--------------mask and shift input data ----------------------------
bufull:
b = *ar3+ << -0
b = #03FFFh & b
; load acc b with BSP buffer and shift right -0
; mask out the TRISTATE bits with #03FFFh
;
*ar2+ = data(#0bh)
; store B to out buffer and advance AR2 pointer
TC = (@ar2 == #02000h) ; output buffer is 2k starting at 1800h
if (TC) goto start
goto bufull
; restart if out buffer is at 1fffh
1403af
15
LTC1403/LTC1403A
;
-------------------dummy bsend return------------------------
bsend
return_enable
;this is also a dummy return to define bsend
;in vector table file BVECTORS.ASM
;
----------------------- end ISR ----------------------------
.copy "c:\dskplus\1403\s2k14ini.asm"
;initialize buffered serial port
.space 16*32 ;clear a chunk at the end to mark the end
;======================================================================
;
;
;
VECTORS
;======================================================================
.sect "vectors" ;The vectors start here
.copy "c:\dskplus\1403\bvectors.asm" ;get BSP vectors
.sect "buffer"
.space 16*0x800
.sect "result"
.space 16*0x800
;Set address of BSP buffer for clearing
;Set address of result for clearing
.end
**********************************************************************
(C) COPYRIGHT TEXAS INSTRUMENTS, INC. 1996
**********************************************************************
*
*
*
*
*
*
*
*
* File: s2k14ini.ASM BSP initialization code for the 'C54x DSKplus
*
*
*
for use with 1403A in standard mode
BSPC and SPC are the same in the 'C542
BSPCE and SPCE seem the same in the 'C542
**********************************************************************
.title "Buffered Serial Port Initialization Routine"
ON
.set 1
OFF
YES
.set !ON
.set 1
NO
.set !YES
.set 2
.set 1
.set 3
.set 0
BIT_8
BIT_10
BIT_12
BIT_16
GO
.set 0x80
**********************************************************************
* This is an example of how to initialize the Buffered Serial Port (BSP).
* The BSP is initialized to require an external CLK and FSX for
* operation. The data format is 16-bits, burst mode, with autobuffering
* enabled.
*
*****************************************************************************************************
*LTC1403 timing from LCC28 socket board with 10MHz crystal.
*10MHz, divided from 40MHz, forced to CLKIN by 1403 board.
*Horizontal scale is 25ns/chr or 100ns period at BCLKR
*Timing measured at DSP pins. Jxx pin labels for jumper cable.
*
*
*
*
*BFSR Pin J1-20 ~~\____/~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~\____/~~~~~~~~~~~*
*BCLKR Pin J1-14 _/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~\_/~*
*BDR
Pin J1-26 _---_---_---<B13-B12-B11-B10-B09-B08-B07-B06-B05-B04-B03-B02-B01-B00>---_---<B13-B12*
*CLKIN Pin J5-09 ~~~~~\_______/~~~~~~~\_______/~~~~~~~\_______/~~~~~~~\_______/~~~~~~~\_______/~~~~~*
*C542 read
*
0
B13 B12 B11 B10 B09 B08 B07 B06 B05 B04 B03 B02 B01 B00
0
0
B13 B12*
*
1403af
16
LTC1403/LTC1403A
* negative edge BCLKR
* negative BFSR pulse
* no data shifted
* 1' cable from counter to CONV at DUT
* 2' cable from counter to CLK at DUT
*No right shift is needed to right justify the input data in the main program
*the two msbs should also be masked
*
*
*****************************************************************************************************
*
Loopback
Format
IntSync
IntCLK
BurstMode
CLKDIV
PCM_Mode
FS_polarity
CLK_polarity
Frame_ignore
XMTautobuf
RCVautobuf
XMThalt
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
.set
NO
BIT_16
NO
NO
YES
3
NO
YES
NO
!YES
NO
YES
NO
;(digital looback mode?)
;(Data format? 16,12,10,8)
;(internal Frame syncs generated?) TXM bit
;(internal clks generated?) MCM bit
;(if BurstMode=NO, then Continuous) FSM bit
;(3=default value, 1/4 CLOCKOUT)
;(Turn on PCM mode?)
;(change polarity)YES=^^^\_/^^^, NO=___/^\___
;(change polarity)for BCLKR YES=_/^, NO=~\_
;(inverted !YES -ignores frame)
;(transmit autobuffering)
DLB bit
FO bit
;(receive autobuffering)
;(transmit buff halt if XMT buff is full)
;(receive buff halt if RCV buff is full)
;(address of transmit buffer)
;(length of transmit buffer)
;(address of receive buffer)
RCVhalt
NO
XMTbufAddr
XMTbufSize
RCVbufAddr
RCVbufSize
*
0x800
0x000
0x800
0x800
;(length of receive buffer)works up to 800
* See notes in the 'C54x CPU and Peripherals Reference Guide on setting up
* valid buffer start and length values. Page 9-44
*
*
**********************************************************************
.eval ((Loopback >> 1)|((Format & 2)<<1)|(BurstMode <<3)|(IntCLK <<4)|(IntSync <<5)) ,SPCval
.eval ((CLKDIV)|(FS_polarity <<5)|(CLK_polarity<<6)|((Format & 1)<<7)|(Frame_ignore<<8)|(PCM_Mode<<9)), SPCEval
.eval (SPCEval|(XMTautobuf<<10)|(XMThalt<<12)|(RCVautobuf<<13)|(RCVhalt<<15)), SPCEval
sineinit:
bspc = #SPCval
ifr = #10h
; places buffered serial port in reset
; clear interrupt flags
imr = #210h
; Enable HPINT,enable BRINT0
intm = 0
; all unmasked interrupts are enabled.
; programs BSPCE and ABU
bspce = #SPCEval
axr = #XMTbufAddr
bkx = #XMTbufSize
arr = #RCVbufAddr
bkr = #RCVbufSize
bspc = #(SPCval | GO)
return
; initializes transmit buffer start address
; initializes transmit buffer size
; initializes receive buffer start address
; initializes receive buffer size
; bring buffered serial port out of reset
;for transmit and receive because GO=0xC0
; ***************************************************************************
; File: BVECTORS.ASM -> Vector Table for the 'C54x DSKplus 10.Jul.96
;
;
BSP vectors and Debugger vectors
TDM vectors just return
; ***************************************************************************
; The vectors in this table can be configured for processing external and
; internal software interrupts. The DSKplus debugger uses four interrupt
; vectors. These are RESET, TRAP2, INT2, and HPIINT.
;
;
*
DO NOT MODIFY THESE FOUR VECTORS IF YOU PLAN TO USE THE DEBUGGER
*
1403af
17
LTC1403/LTC1403A
U
W U U
APPLICATIO S I FOR ATIO
; All other vector locations are free to use. When programming always be sure
; the HPIINT bit is unmasked (IMR=200h) to allow the communications kernel and
; host PC interact. INT2 should normally be masked (IMR(bit 2) = 0) so that the
; DSP will not interrupt itself during a HINT. HINT is tied to INT2 externally.
;
;
;
.title "Vector Table"
.mmregs
reset
nmi
goto #80h
nop
nop
;00; RESET * DO NOT MODIFY IF USING DEBUGGER *
;04; non-maskable external interrupt
return_enable
nop
nop
nop
trap2
int0
goto #88h
nop
nop
.space 52*16
;08; trap2 * DO NOT MODIFY IF USING DEBUGGER *
;0C-3F: vectors for software interrupts 18-30
;40; external interrupt int0
return_enable
nop
nop
nop
int1
return_enable
nop
nop
nop
return_enable
nop
nop
nop
return_enable
nop
nop
nop
goto breceive
nop
nop
nop
;44; external interrupt int1
;48; external interrupt int2
;4C; internal timer interrupt
;50; BSP receive interrupt
;54; BSP transmit interrupt
;58; TDM receive interrupt
int2
tint
brint
bxint
trint
goto bsend
nop
nop
nop
return_enable
nop
nop
nop
txint
int3
return_enable
nop
nop
;5C; TDM transmit interrupt
;60; external interrupt int3
return_enable
nop
nop
nop
hpiint
dgoto #0e4h
nop
nop
;64; HPIint * DO NOT MODIFY IF USING DEBUGGER *
;68-7F; reserved area
.space 24*16
1403af
18
LTC1403/LTC1403A
U
PACKAGE DESCRIPTIO
MSE Package
10-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1663)
BOTTOM VIEW OF
EXPOSED PAD OPTION
2.06 ± 0.102
2.794 ± 0.102
(.110 ± .004)
0.889 ± 0.127
(.035 ± .005)
(.081 ± .004)
1
1.83 ± 0.102
(.072 ± .004)
5.23
(.206)
MIN
2.083 ± 0.102 3.20 – 3.45
(.082 ± .004) (.126 – .136)
10
0.50
(.0197)
BSC
0.305 ± 0.038
(.0120 ± .0015)
TYP
3.00 ± 0.102
(.118 ± .004)
(NOTE 3)
0.497 ± 0.076
(.0196 ± .003)
REF
10 9
8
7 6
RECOMMENDED SOLDER PAD LAYOUT
3.00 ± 0.102
(.118 ± .004)
(NOTE 4)
4.90 ± 0.152
(.193 ± .006)
DETAIL “A”
0.254
(.010)
0° – 6° TYP
1
2
3
4 5
GAUGE PLANE
0.53 ± 0.152
(.021 ± .006)
0.86
(.034)
REF
1.10
(.043)
MAX
DETAIL “A”
0.18
(.007)
SEATING
PLANE
0.17 – 0.27
(.007 – .011)
TYP
0.127 ± 0.076
(.005 ± .003)
MSOP (MSE) 0603
0.50
(.0197)
BSC
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
1403af
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
19
LTC1403/LTC1403A
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
ADCs
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16-Bit, 500ksps Parallel ADC
16-Bit, 333ksps Parallel ADC
16-Bit, 250ksps Serial ADC
14-Bit, 2.5Msps Parallel ADC
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±5V Supply, ±2.5V Span, 90dB SINAD
±5V Supply, ±2.5V Span, 90dB SINAD
5V, Configurable Bipolar/Unipolar Inputs
5V, Selectable Spans, 80dB SINAD
±5V Supply, ±2.5V Span, 78dB SINAD
LTC1604
LTC1609
LTC1411
LCT1414
LTC1407/LTC1407A
LTC1420
12-/14-Bit, 3Msps Simultaneous Sampling ADC 3V, 2-Channel Differential, 14mW, MSOP Package
12-Bit, 10Msps Parallel ADC
12-Bit, 5Msps Parallel ADC
12-Bit, 3Msps Parallel ADC
12-Bit, 2.2Msps Serial ADC
16-Bit, 250ksps Serial ADC
5V, Selectable Spans, 72dB SINAD
LTC1405
5V, Selectable Spans, 115mW
LTC1412
±5V Supply, ±2.5V Span, 72dB SINAD
5V or ±5V Supply, 4.096V or ±2.5V Span
5V Supply, 1 and 2 Channel, 4.3mW, MSOP Package
LTC1402
LTC1864/LTC1865
DACs
LTC1666/LTC1667/LTC1668 12-/14-/16-Bit, 50Msps DACs
87dB SFDR, 20ns Settling Time
LTC1592
16-Bit, Serial SoftSpanTM
I
DAC
±1LSB INL/DNL, Software Selectable Spans
OUT
References
LT1790-2.5
LT1461-2.5
LT1460-2.5
Micropower Series Reference in SOT-23
Precision Voltage Reference
0.05% Initial Accuracy, 10ppm Drift
0.04% Initial Accuracy, 3ppm Drift
0.1% Initial Accuracy, 10ppm Drift
Micropower Series Voltage Reference
SoftSpan is a trademark of Linear Technology Corporation.
1403af
LT/TP 1203 1K • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
20
●
●
LINEAR TECHNOLOGY CORPORATION 2002
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
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