LTC2217IUP-TRPBF [Linear]
16-Bit, 105Msps Low Noise ADC; 16位,105Msps低噪声ADC型号: | LTC2217IUP-TRPBF |
厂家: | Linear |
描述: | 16-Bit, 105Msps Low Noise ADC |
文件: | 总32页 (文件大小:1276K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LTC2217
16-Bit, 105Msps
Low Noise ADC
FEATURES
DESCRIPTION
■
Sample Rate: 105Msps
TheLTC®2217isa105Mspssampling16-bitA/Dconverter
designedfordigitizinghighfrequency,widedynamicrange
signals with input frequencies up to 400MHz. The input
■
81.3dBFS Noise Floor
■
100dB SFDR
■
SFDR >90dB at 70MHz
range of the ADC is fixed at 2.75V
.
P-P
■
85fs
Jitter
RMS
The LTC2217 is perfect for demanding communications
applications,withACperformancethatincludes81.3dBFS
Noise Floor and 100dB spurious free dynamic range
■
■
■
■
■
■
■
■
■
■
2.75V Input Range
P-P
400MHz Full Power Bandwidth S/H
Optional Internal Dither
(SFDR). Ultra low jitter of 85fs
allows undersampling
RMS
Optional Data Output Randomizer
LVDS or CMOS Outputs
Single 3.3V Supply
Power Dissipation: 1.19W
Clock Duty Cycle Stabilizer
Pin Compatible with LTC2208
64-Pin (9mm × 9mm) QFN Package
ofhighinputfrequencieswhilemaintainingexcellentnoise
performance.MaximumDCspecificationsinclude 3.5LSB
INL, 1LSB DNL (no missing codes).
The digital output can be either differential LVDS or
single-ended CMOS. There are two format options for the
CMOS outputs: a single bus running at the full data rate or
demultiplexed buses running at half data rate. A separate
output power supply allows the CMOS output swing to
range from 0.5V to 3.6V.
APPLICATIONS
■
Telecommunications
+
–
The ENC and ENC inputs may be driven differentially
or single-ended with a sine wave, PECL, LVDS, TTL or
CMOS inputs. An optional clock duty cycle stabilizer al-
lows high performance at full speed with a wide range of
clock duty cycles.
■
Receivers
■
Cellular Base Stations
■
Spectrum Analysis
■
Imaging Systems
■
ATE
, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.
All other trademarks are the property of their respective owners. Patents Pending.
TYPICAL APPLICATION
3.3V
SENSE
64k Point FFT,
FIN = 4.9MHz, –1dBFS
OV
DD
1.575V
COMMON MODE
BIAS VOLTAGE
INTERNAL ADC
REFERENCE
GENERATOR
V
0.5V TO 3.6V
1μF
CM
0
–10
2.2μF
–20
–30
–40
–50
–60
–70
–80
OF
CLKOUT
D15
+
AIN
+
16-BIT
PIPELINED
ADC CORE
OUTPUT
DRIVERS
CORRECTION
LOGIC AND
SHIFT REGISTER
CMOS
OR
LVDS
ANALOG
INPUT
S/H
AMP
•
•
•
–
–
AIN
D0
–90
OGND
–100
–110
–120
–130
CLOCK/DUTY
CYCLE
CONTROL
3.3V
1μF
V
DD
1μF
1μF
GND
2217 TA01
0
10
20
30
40
50
FREQUENCY (MHz)
+
–
ENC
ENC
SHDN DITH MODE LVDS RAND
ADC CONTROL INPUTS
2217 TA01b
2217f
1
LTC2217
ABSOLUTE MAXIMUM RATINGS
PIN CONFIGURATION
OVDD = VDD (Notes 1 and 2)
TOP VIEW
Supply Voltage (V )...................................–0.3V to 4V
DD
Digital Output Ground Voltage (OGND)........–0.3V to 1V
Analog Input Voltage (Note 3) ..... –0.3V to (V + 0.3V)
DD
+
SENSE 1
GND 2
48 D11 /DA6
Digital Input Voltage .................... –0.3V to (V + 0.3V)
DD
–
47 D11 /DA5
+
V
3
46 D10 /DA4
Digital Output Voltage................–0.3V to (OV + 0.3V)
CM
GND 4
DD
–
45 D10 /DA3
+
V
V
5
6
44 D9 /DA2
43 D9 /DA1
42 D8 /DA0
41 D8 /CLKOUTA
40 CLKOUT /CLKOUTB
39 CLKOUT /OFB
38 D7 /DB15
37 D7 /DB14
36 D6 /DB13
35 D6 /DB12
34 D5 /DB11
33 D5 /DB10
Power Dissipation............................................ 2000mW
DD
–
DD
+
GND 7
Operating Temperature Range
+
–
AIN
AIN
8
9
65
–
+
LTC2217C ................................................ 0°C to 70°C
LTC2217I .............................................–40°C to 85°C
Storage Temperature Range ..................–65°C to 150°C
–
GND 10
GND 11
+
+
–
ENC 12
–
+
ENC 13
–
GND 14
+
Digital Output Supply Voltage (OV )..........–0.3V to 4V
V
DD
V
DD
15
16
DD
–
T
= 150°C, θ = 20°C/W
JA
JMAX
EXPOSED PAD (PIN 65) IS GND, MUST BE SOLDERED TO PCB
ORDER INFORMATION
LEAD FREE FINISH
TAPE AND REEL
PART MARKING
PACKAGE DESCRIPTION
64-Lead (9mm × 9mm) Plastic QFN
64-Lead (9mm × 9mm) Plastic QFN
TEMPERATURE RANGE
0°C to 70°C
–40°C to 85°C
LTC2217CUP#PBF
LTC2217IUP#PBF
LTC2217CUP#TRPBF
LTC2217IUP#TRPBF
LTC2217UP
LTC2217UP
LEAD BASED FINISH
TAPE AND REEL
PART MARKING
PACKAGE DESCRIPTION
TEMPERATURE RANGE
LTC2217CUP
LTC2217IUP
LTC2217CUP#TR
LTC2217IUP#TR
LTC2217UP
LTC2217UP
64-Lead (9mm × 9mm) Plastic QFN
64-Lead (9mm × 9mm) Plastic QFN
0°C to 70°C
–40°C to 85°C
Consult LTC Marketing for parts specified with wider operating temperature ranges.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
CONVERTER CHARACTERISTICS The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. (Note 4)
PARAMETER
CONDITIONS
MIN
TYP
MAX
3.5
4
UNITS
LSB
Integral Linearity Error
Integral Linearity Error
Differential Linearity Error
Offset Error
Differential Analog Input (Note 5) T = 25°C
1.3
A
●
●
●
Differential Analog Input (Note 5)
Differential Analog Input
(Note 6)
1.3
LSB
0.18/–0.22
1
LSB
1.3
4
6
mV
Offset Drift
μV/°C
%FS
●
Gain Error
External Reference
0.3
1
ppm/°C
ppm/°C
Full-Scale Drift
Internal Reference
External Reference
–65
12
Transition Noise
External Reference
2
LSB
RMS
2217f
2
LTC2217
ANALOG INPUT The ● denotes the specifications which apply over the full operating temperature range, otherwise
specifications are at TA = 25°C. (Note 4)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
2.75
MAX
UNITS
+
–
V
IN
3.135V ≤ V ≤ 3.465V
V
Analog Input Range (A
–
A
)
IN
DD
P-P
IN
●
●
●
V
I
Analog Input Common Mode
Differential Input (Note 7)
1.2
–1
–3
1.575
1.8
1
V
μA
μA
μA
μA
IN, CM
+
–
Analog Input Leakage Current
SENSE Input Leakage Current
0V ≤ A
,
A
≤ V
IN DD
IN
IN
I
I
I
0V ≤ SENSE ≤ V
3
SENSE
MODE
LVDS
DD
MODE Pin Pull-Down Current to GND
LVDS Pin Pull-Down Current to GND
Analog Input Capacitance
10
10
+
–
C
Sample Mode ENC < ENC
9.1
1.8
pF
pF
IN
+
–
Hold Mode ENC > ENC
t
t
Sample-and-Hold
0.35
ns
fs RMS
dB
AP
Acquisition Delay Time
Sample-and-Hold
Aperture Jitter
85
JITTER
+
–
CMRR
Analog Input
Common Mode Rejection Ratio
1.2V < (A = A ) <1.8V
80
IN
IN
BW-3dB
Full Power Bandwidth
R < 25Ω
S
400
MHz
DYNAMIC ACCURACY The ● denotes the specifications which apply over the full operating temperature range,
otherwise specifications are at TA = 25°C. AIN = –1dBFS with 2.75V range unless otherwise noted. (Note 4)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
SNR
Signal-to-Noise Ratio
5MHz Input
81.2
dBFS
15MHz Input, T = 25°C
80.4
80.1
81.1
80.7
dBFS
dBFS
A
●
●
15MHz Input
30MHz Input, T = 25°C
81.1
dBFS
A
70MHz Input, T = 25°C
79.6
79.3
80.4
80.1
dBFS
dBFS
A
70MHz Input
140MHz Input
5MHz Input
78.8
100
dBFS
dBc
SFDR
SFDR
Spurious Free
Dynamic Range
2nd or 3rd Harmonic
15MHz Input, T = 25°C
88
87
100
99
dBc
dBc
A
●
●
15MHz Input
30MHz Input
95
dBc
70MHz Input, T = 25°C
85
83
92
88
dBc
dBc
A
70MHz Input
140MHz Input
5MHz Input
85
105
105
105
103
95
dBc
dBc
dBc
dBc
dBc
dBc
Spurious Free Dynamic Range
4th Harmonic or Higher
●
●
15MHz Input
30MHz Input
70MHz Input
140MHz Input
93
93
2217f
3
LTC2217
DYNAMIC ACCURACY The ● denotes the specifications which apply over the full operating temperature range,
otherwise specifications are at TA = 25°C. AIN = –1dBFS with 2.75V range unless otherwise noted. (Note 4)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
S/(N+D)
Signal-to-Noise
5MHz Input
81.2
dBFS
Plus Distortion Ratio
15MHz Input, T = 25°C
15MHz Input
79.9
79.7
81
80.6
dBFS
dBFS
A
●
●
30MHz Input
81.1
dBFS
70MHz Input, T = 25°C
78.7
78.2
80
79.5
dBFS
dBFS
A
70MHz Input
140MHz Input
5MHz Input
78.8
105
105
105
105
100
115
115
115
115
110
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
SFDR
SFDR
IMD
Spurious Free Dynamic Range
at –25dBFS
Dither “OFF”
15MHz Input
30MHz Input
70MHz Input
140MHz Input
5MHz Input
Spurious Free Dynamic Range
at –25dBFS
Dither “ON”
●
15MHz Input
30MHz Input
70MHz Input
140MHz Input
100
Intermodulation Distortion
f
IN1
f
IN1
= 14MHz, f = 21MHz, –7dBFS
= 67MHz, f = 74MHz, –7dBFS
100
90
dBc
dBc
IN2
IN2
COMMON MODE BIAS CHARACTERISTICS The ● denotes the specifications which apply over the
full operating temperature range, otherwise specifications are at TA = 25°C. (Note 4)
PARAMETER
CONDITIONS
MIN
TYP
1.575
60
MAX
UNITS
V
V
CM
V
CM
V
CM
V
CM
Output Voltage
Output Tempco
Line Regulation
Output Resistance
I
I
= 0
= 0
1.475
1.675
OUT
OUT
ppm/°C
3.135V ≤ V ≤ 3.465V
2.4
mV/V
DD
Ω
| I
| ≤ 0.8mA
1.1
OUT
2217f
4
LTC2217
DIGITAL INPUTS AND DIGITAL OUTPUTS The ● denotes the specifications which apply over the
full operating temperature range, otherwise specifications are at TA = 25°C. (Note 4)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
+
–
Encode Inputs (ENC , ENC )
●
V
V
Differential Input Voltage
(Note 7)
0.2
1.2
V
ID
Common Mode Input Voltage
Internally Set
Externally Set (Note 7)
1.6
V
V
ICM
3
R
Input Resistance
Input Capacitance
(See Figure 2)
(Note 7)
6
3
k
Ω
IN
C
IN
pF
Logic Inputs
●
●
●
V
V
High Level Input Voltage
Low Level Input Voltage
Digital Input Current
V
V
V
= 3.3V
= 3.3V
2
V
V
IH
IL
DD
DD
IN
0.8
10
I
IN
= 0V to V
μA
pF
DD
C
Digital Input Capacitance
(Note 7)
1.5
IN
LOGIC OUTPUTS (CMOS MODE)
OV = 3.3V
DD
V
High Level Output Voltage
V
V
= 3.3V
= 3.3V
I = –10μA
I = –200μA
O
3.299
3.29
V
V
OH
DD
DD
O
●
●
3.1
V
Low Level Output Voltage
I = 160μA
0.01
0.10
V
V
OL
O
I = 1.6mA
O
0.4
I
I
Output Source Current
Output Sink Current
V
V
= 0V
–50
50
mA
mA
SOURCE
OUT
OUT
= 3.3V
SINK
OV = 2.5V
DD
V
V
High Level Output Voltage
Low Level Output Voltage
V
V
= 3.3V
= 3.3V
I = –200μA
2.49
0.1
V
V
OH
OL
DD
DD
O
I = 1.60mA
O
OV = 1.8V
DD
V
V
High Level Output Voltage
Low Level Output Voltage
V
V
= 3.3V
= 3.3V
I = –200μA
1.79
0.1
V
V
OH
OL
DD
DD
O
I = 1.60mA
O
LOGIC OUTPUTS (LVDS MODE)
STANDARD LVDS
●
●
V
V
Differential Output Voltage
100Ω Differential Load
247
350
1.2
454
mV
V
OD
OS
Output Common Mode Voltage 100Ω Differential Load
1.125
1.375
Low Power LVDS
●
●
V
Differential Output Voltage
100Ω Differential Load
125
175
1.2
250
mV
V
OD
OS
V
Output Common Mode Voltage 100Ω Differential Load
1.125
1.375
2217f
5
LTC2217
POWER REQUIREMENTS The ● denotes the specifications which apply over the full operating temperature
range, otherwise specifications are at TA = 25°C. AIN = –1dBFS unless otherwise noted. (Note 4)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
3.3
17
MAX
UNITS
V
●
V
P
Analog Supply Voltage
Shutdown Power
(Note 8)
3.135
3.465
DD
SHDN = V
(Note 8)
mW
SHDN
DD
Standard LVDS Output Mode
●
●
●
●
OV
Output Supply Voltage
Analog Supply Current
Output Supply Current
Power Dissipation
3
3
3.3
365
75
3.6
430
90
V
mA
DD
I
I
VDD
OVDD
mA
P
1450
1716
mW
DIS
Low Power LVDS Output Mode
●
●
●
●
OV
Output Supply Voltage
Analog Supply Current
Output Supply Current
Power Dissipation
(Note 8)
(Note 8)
3.3
363
42
3.6
430
50
V
mA
DD
I
I
VDD
OVDD
mA
P
1335
1584
mW
DIS
CMOS Output Mode
OV
●
●
●
Output Supply Voltage
Analog Supply Current
Power Dissipation
0.5
3.6
430
V
mA
DD
I
360
VDD
P
DIS
1190
1420
mW
TIMING CHARACTERISTICS The ● denotes the specifications which apply over the full operating temperature
range, otherwise specifications are at TA = 25°C. (Note 4)
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
●
f
Sampling Frequency
ENC Low Time
(Note 8)
1
105
MHz
S
L
●
●
t
Duty Cycle Stabilizer Off (Note 7)
Duty Cycle Stabilizer On (Note 7)
4.52
3.1
4.762
4.762
500
500
ns
ns
●
●
t
ENC High Time
Duty Cycle Stabilizer Off (Note 7)
Duty Cycle Stabilizer On (Note 7)
4.52
3.1
4.762
4.762
500
500
ns
ns
H
LVDS Output Mode (Standard and Low Power)
●
●
●
t
t
t
t
t
ENC to DATA Delay
ENC to CLKOUT Delay
DATA to CLKOUT Skew
Output Rise Time
Output Fall Time
(Note 7)
(Note 7)
1.3
1.3
2.5
2.5
0
3.8
3.8
0.6
ns
ns
D
C
(t -t ) (Note 7)
C D
–0.6
ns
SKEW
RISE
FALL
0.5
0.5
7
ns
ns
Data Latency
Data Latency
Cycles
CMOS Output Mode
●
●
●
t
t
t
ENC to DATA Delay
ENC to CLKOUT Delay
DATA to CLKOUT Skew
Data Latency
(Note 7)
(Note 7)
1.3
1.3
2.7
2.7
0
4
4
ns
ns
ns
D
C
(t -t ) (Note 7)
C D
–0.6
0.6
SKEW
Data Latency
Full Rate CMOS
Demuxed
7
7
Cycles
Cycles
2217f
6
LTC2217
ELECTRICAL CHARACTERISTICS
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 5: Integral nonlinearity is defined as the deviation of a code from a “best
fit straight line” to the transfer curve. The deviation is measured from the
center of the quantization band.
Note 6: Offset error is the offset voltage measured from –1/2LSB when the
output code flickers between 0000 0000 0000 0000 and 1111 1111 1111
1111 in 2’s complement output mode.
Note 2: All voltage values are with respect to GND, with GND and OGND
shorted (unless otherwise noted).
Note 3: When these pin voltages are taken below GND or above V , they
will be clamped by internal diodes. This product can handle input currents
Note 7: Guaranteed by design, not subject to test.
Note 8: Recommended operating conditions.
DD
of greater than 100mA below GND or above V without latchup.
DD
+
Note 4: V = 3.3V, f
= 105MHz, LVDS outputs, differential ENC /
DD
SAMPLE
–
ENC = 2V sine wave with 1.6V common mode, input range = 2.75V
P-P
P-P
with differential drive, unless otherwise specified.
TIMING DIAGRAM
LVDS Output Mode Timing
All Outputs are Differential and Have LVDS Levels
t
AP
N + 1
N + 4
ANALOG
INPUT
N + 3
N
N + 2
t
H
t
L
–
ENC
+
ENC
t
D
N – 7
N – 6
N – 5
N – 4
N – 3
D0-D15, OF
t
C
+
CLKOUT
2217 TD01
–
CLKOUT
2217f
7
LTC2217
TIMING DIAGRAMS
Full-Rate CMOS Output Mode Timing
All Outputs are Single-Ended and Have CMOS Levels
t
AP
N + 1
N + 4
ANALOG
INPUT
N + 3
N
N + 2
t
H
t
L
–
ENC
+
ENC
t
D
N – 7
N – 6
N – 5
N – 4
N – 3
DA0-DA15, OFA
t
C
CLKOUTA
CLKOUTB
HIGH IMPEDANCE
DB0-DB15, OFB
2217 TD02
Demultiplexed CMOS Output Mode Timing
All Outputs are Single-Ended and Have CMOS Levels
t
AP
N + 1
N + 4
ANALOG
INPUT
N + 3
N
N + 2
t
H
t
L
–
ENC
+
ENC
t
t
D
D
N – 8
N – 6
N – 4
DA0-DA15, OFA
DB0-DB15, OFB
N – 7
N – 5
N – 3
t
C
CLKOUTA
CLKOUTB
2217 TD03
2217f
8
LTC2217
TYPICAL PERFORMANCE CHARACTERISTICS
Integral Nonlinearity (INL) vs
Output Code - Dither “Off“
Integral Nonlinearity (INL) vs
Output Code - Dither “On“
Differential Nonlinearity (DNL) vs
Output Code
2.0
1.5
2.0
1.5
1.0
0.8
0.6
1.0
1.0
0.4
0.5
0.5
0.2
0.0
0.0
0.0
–0.2
–0.4
–0.6
–0.8
–1.0
–0.5
–1.0
–1.5
–2.0
–0.5
–1.0
–1.5
–2.0
0
16384
32768
49152
65536
0
16384
32768
49152
65536
0
16384
32768
49152
65536
OUTPUT CODE
OUTPUT CODE
OUTPUT CODE
2217 G03
2217 G01
2217 G02
64k Point FFT, fIN = 4.9MHz,
–1dBFS
64k Point FFT, fIN = 15.1MHz,
–1dBFS
AC Grounded Input Histogram
14000
12000
10000
8000
6000
4000
2000
0
0
–10
–20
–30
–40
–50
–60
–70
–80
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
32736
32745
32754
0
10
20
30
40
50
0
10
20
30
40
50
OUTPUT CODE
FREQUENCY (MHz)
FREQUENCY (MHz)
2217 G06
2217 G04
2217 G05
64k Point 2-Tone FFT,
fIN = 14.25MHz and 21.5MHz,
–7dBFS
64k Point FFT, fIN = 15.1MHz,
–20dBFS, Dither “Off”
64k Point FFT, fIN = 15.1MHz,
–20dBFS, Dither “On”
0
–10
0
–10
0
–10
–20
–20
–20
–30
–30
–30
–40
–40
–40
–50
–50
–50
–60
–60
–60
–70
–70
–70
–80
–80
–80
–90
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
–100
–110
–120
–130
0
10
20
30
40
50
0
10
20
30
40
50
0
10
20
30
40
50
FREQUENCY (MHz)
FREQUENCY (MHz)
FREQUENCY (MHz)
2217 G07
2217 G08
2217 G09
2217f
9
LTC2217
TYPICAL PERFORMANCE CHARACTERISTICS
64k Point 2-Tone FFT,
fIN = 14.25MHz and 21.5MHz,
–25dBFS, Dither “On”
SFDR vs Input Level,
fIN = 15.2MHz, Dither “Off”
SFDR vs Input Level,
fIN = 15.2MHz, Dither “On”
0
–10
–20
–30
–40
140
130
120
110
100
90
140
130
120
110
100
90
–50
–60
–70
80
80
–80
–90
–100
–110
–120
–130
70
70
60
60
50
50
40
40
30
30
0
10
20
30
40
50
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
FREQUENCY (MHz)
2217 G10
2217 G12
2217 G11
64k Point FFT, fIN = 30.1MHz,
–20dBFS, Dither “On”
64k Point FFT, fIN = 28.7MHz,
–1dBFS
SNR vs Input Level, fIN = 15.2MHz
82
81
80
79
78
0
–10
–20
–30
–40
–50
–60
–70
–80
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
0
10
20
30
40
50
0
10
20
30
40
50
FREQUENCY (MHz)
FREQUENCY (MHz)
2217 G13
2217 G14
2217 G15
64k Point FFT, fIN = 70.1MHz,
–20dBFS, Dither “Off”
64k Point FFT, fIN = 70.1MHz,
–10dBFS, Dither “Off”
64k Point FFT, fIN = 70.2MHz,
–1dBFS
0
–10
0
–10
0
–10
–20
–20
–20
–30
–30
–30
–40
–40
–40
–50
–50
–50
–60
–60
–60
–70
–70
–70
–80
–80
–80
–90
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
–100
–110
–120
–130
0
10
20
30
40
50
0
10
20
30
40
50
0
10
20
30
40
50
FREQUENCY (MHz)
FREQUENCY (MHz)
FREQUENCY (MHz)
2217 G16
2217 G17
2217 G18
2217f
10
LTC2217
TYPICAL PERFORMANCE CHARACTERISTICS
64k Point FFT, fIN = 70.1MHz,
–20dBFS, Dither “On”
SFDR vs Input Level,
fIN = 70.5MHz, Dither “Off”
SFDR vs Input Level,
fIN = 70.5MHz, Dither “On”
0
–10
–20
–30
–40
140
130
120
110
100
90
140
130
120
110
100
90
–50
–60
–70
80
80
–80
–90
–100
–110
–120
–130
70
70
60
60
50
50
40
40
30
30
0
10
20
30
40
50
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
FREQUENCY (MHz)
2217 G21
2217 G19
2217 G20
64k Point 2-Tone FFT,
fIN = 67.2MHz and 74.4MHz,
–15dBFS, Dither “On”
64k Point 2-Tone FFT,
fIN = 67.2MHz and 74.4MHz,
–7dBFS
SNR vs Input Level, FIN = 70.5MHz
82
81
80
79
78
0
–10
–20
–30
–40
–50
–60
–70
–80
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
0
10
20
30
40
50
0
10
20
30
40
50
FREQUENCY (MHz)
FREQUENCY (MHz)
2217 G24
2217 G22
2217 G23
64k Point 2-Tone FFT,
fIN = 67.2MHz and 74.4MHz,
–25dBFS, Dither “On”
64k Point FFT, fIN = 140.5MHz,
–1dBFS
64k Point FFT, fIN = 140.1MHz,
–20dBFS, Dither “On”
0
–10
0
–10
0
–10
–20
–20
–20
–30
–30
–30
–40
–40
–40
–50
–50
–50
–60
–60
–60
–70
–70
–70
–80
–80
–80
–90
–90
–90
–100
–110
–120
–130
–100
–110
–120
–130
–100
–110
–120
–130
0
10
20
30
40
50
0
10
20
30
40
50
0
10
20
30
40
50
FREQUENCY (MHz)
FREQUENCY (MHz)
FREQUENCY (MHz)
2217 G25
2217 G26
2217 G27
2217f
11
LTC2217
TYPICAL PERFORMANCE CHARACTERISTICS
SFDR vs Input Level,
fIN = 140.5MHz, Dither “Off”
SFDR vs Input Level,
fIN = 140.5MHz, Dither “On”
SNR vs Input Level,
fIN = 140.5MHz
140
130
120
110
100
90
140
130
120
110
100
90
82
81
80
79
78
80
80
70
70
60
60
50
50
40
40
30
30
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
2217 G30
0
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
–80 –70 –60 –50 –40 –30 –20 –10
INPUT LEVEL (dBFS)
0
2217 G28
2217 G29
SFDR (HD2 and HD3) vs
Input Frequency
SNR and SFDR vs Sample Rate,
fIN = 5.2MHz
SNR vs Input Frequency
110
105
100
95
82
81
80
79
78
77
76
110
105
100
95
LIMIT
SFDR
HD2
90
90
HD3
SFDR
85
85
SNR
80
80
75
75
70
70
0
40
80
120
160
0
50
100
150
200
250
0
50
100
150
200
250
INPUT FREQUENCY (MHz)
INPUT FREQUENCY (MHz)
SAMPLE RATE (MSPS)
2217 G31
2217 G32
2217 G33
SNR and SFDR vs Supply
Voltage (VDD), fIN = 5.1MHz
IVDD vs Sample Rate and Supply
Voltage, fIN = 5MHz, –1dBFS
SNR and SFDR vs Clock Duty
Cycle, fIN = 5.2MHz
110
105
100
95
110
100
90
450
425
400
375
350
325
300
LOWER LIMIT
V
= 3.3V
DD
SFDR
UPPER LIMIT
90
V
= 3.135V
V
= 3.465V
DD
80
DD
85
SNR
80
SFDR DCS OFF
SNR DCS OFF
SFDR DCS ON
SNR DCS ON
70
75
70
2.8
60
3.0
3.2
3.4
3.6
0
50
100
150
200
30
40
50
60
70
SUPPLY VOLTAGE (V)
SAMPLE RATE (Msps)
DUTY CYCLE (%)
2217 G34
2217 G35
2217 G36
2217f
12
LTC2217
TYPICAL PERFORMANCE CHARACTERISTICS
Normalized Full Scale vs
Temperature, Internal Reference,
5 Units
Input Offset Voltage vs
Temperature, Internal Reference,
5 Units
1.005
1.004
1.003
1.002
1.001
1
5
4
3
2
1
0
0.999
0.998
0.997
0.996
0.995
–1
–2
–3
–4
–5
–40
–20
0
20
40
60
80
–40
–20
0
20
40
60
80
TEMPERATURE (°C)
TEMPERATURE (°C)
2217 G37
2217 G38
Normalized Full Scale vs
Temperature, External Reference,
5 Units
Input Offset Voltage vs
Temperature, External Reference,
5 Units
1.005
1.004
1.003
1.002
1.001
1
5
4
3
2
1
0
0.999
0.998
0.997
0.996
0.995
–1
–2
–3
–4
–5
–40
–20
0
20
40
60
80
–40
–20
0
20
40
60
80
TEMPERATURE (°C)
TEMPERATURE (°C)
2217 G39
2217 G40
SFDR vs Analog Input Common
Mode Voltage, 5MHz and 70MHz,
–1dBFS
Mid-Scale Settling After Wake
Up from Shutdown or Starting
Encode Clock
Full-Scale Settling After Wake
Up from Shutdown or Starting
Encode Clock
110
105
100
95
0.5
0.4
0.5
0.4
WAKE-UP
WAKE-UP
0.3
0.3
5MHz
0.2
0.2
90
0.1
0.1
85
0.0
0.0
CLOCK START
CLOCK START
80
–0.1
–0.2
–0.3
–0.4
–0.5
–0.1
–0.2
–0.3
–0.4
–0.5
70MHz
75
70
65
60
0.5 0.75
1
1.25 1.5
1.75
2
0
400
800
1200
1600
2000
0
300
600
900
1200
1500
ANALOG INPUT COMMON MODE VOLTAGE (V)
TIME AFTER WAKE-UP OR CLOCK START (μs)
TIME AFTER WAKE-UP OR CLOCK START (μs)
2217 G41
2217 G42
2217 G43
2217f
13
LTC2217
PIN FUNCTIONS
For CMOS Mode. Full Rate or Demultiplexed
CLKOUTB(Pin40):DataValidOutput.CLKOUTBwilltoggle
at the sample rate in full rate CMOS mode or at 1/2 the
sample rate in demultiplexed mode. Latch the data on the
falling edge of CLKOUTB.
SENSE (Pin 1): Reference Mode Select and External
Reference Input. Tie SENSE to V to select the internal
DD
2.5V bandgap reference. An external reference of 2.5V or
1.25V may be used; both reference values will set a full
scale ADC range of 2.75V.
CLKOUTA (Pin 41): Inverted Data Valid Output. CLKOUTA
will toggle at the sample rate in full rate CMOS mode or
at 1/2 the sample rate in demultiplexed mode. Latch the
data on the rising edge of CLKOUTA.
GND (Pins 2, 4, 7, 10, 11, 14, 18): ADC Power Ground.
V
(Pin3):1.575VOutput.Optimumvoltageforinputcom-
CM
DA0-DA15(Pins42-48and51-59):DigitalOutputs,ABus.
DA15 is the MSB. Output bus for full rate CMOS mode
and demultiplexed mode.
mon mode. Must be bypassed to ground with a minimum
of 2.2μF. Ceramic chip capacitors are recommended.
V
(Pins 5, 6, 15, 16, 17): 3.3V Analog Supply Pin.
DD
OFA (Pin 60): Over/Under Flow Digital Output for the A
Bus. OFA is high when an over or under flow has occurred
on the A bus.
Bypass to GND with 1μF ceramic chip capacitors.
+
A
A
(Pin 8): Positive Differential Analog Input.
(Pin 9): Negative Differential Analog Input.
IN
IN
–
LVDS (Pin 61): Data Output Mode Select Pin. Connecting
+
LVDSto0VselectsfullrateCMOSmode.ConnectingLVDS
ENC (Pin 12): Positive Differential Encode Input. The
+
to1/3V selectsdemultiplexedCMOSmode. Connecting
sampled analog input is held on the rising edge of ENC .
DD
LVDS to 2/3V selects Low Power LVDS mode. Connect-
Internally biased to 1.6V through a 6.2kΩ resistor. Output
DD
+
ing LVDS to V selects Standard LVDS mode.
data can be latched on the rising edge of ENC .
DD
–
MODE (Pin 62): Output Format and Clock Duty Cycle
Stabilizer Selection Pin. Connecting MODE to 0V selects
offset binary output format and disables the clock duty
ENC (Pin 13): Negative Differential Encode Input. The
–
sampled analog input is held on the falling edge of ENC .
Internally biased to 1.6V through a 6.2kΩ resistor. By-
pass to ground with a 0.1μF capacitor for a single-ended
Encode signal.
cyclestabilizer.ConnectingMODEto1/3V selects offset
DD
binary output format and enables the clock duty cycle sta-
bilizer.ConnectingMODEto2/3V selects2’scomplement
DD
SHDN (Pin 19): Power Shutdown Pin. SHDN = low results
in normal operation. SHDN = high results in powered
down analog circuitry and the digital outputs are placed
in a high impedance state.
output format and enables the clock duty cycle stabilizer.
Connecting MODE to V selects 2’s complement output
DD
format and disables the clock duty cycle stabilizer.
RAND (Pin 63): Digital Output Randomization Selection
Pin. RAND low results in normal operation. RAND high
selects D1-D15 to be EXCLUSIVE-ORed with D0 (the
LSB). The output can be decoded by again applying an
XOR operation between the LSB and all other bits. This
mode of operation reduces the effects of digital output
interference.
DITH (Pin 20): Internal Dither Enable Pin. DITH = low
disables internal dither. DITH = high enables internal
dither. Refer to Internal Dither section of this data sheet
for details on dither operation.
DB0-DB15(Pins21-30and33-38):DigitalOutputs,BBus.
DB15istheMSB. Activeindemultiplexedmode. TheBbus
is in high impedance state in full rate CMOS mode.
NC(Pin64):NotConnectedInternally.Forpincompatibility
OGND (Pins 31 and 50): Output Driver Ground.
with the LTC2208 this pin should be connected to GND or
V
DD
as required. Otherwise no connection.
OV (Pins 32 and 49): Positive Supply for the Output
DD
Drivers. Bypass to ground with 1μF capacitor.
GND (Exposed Pad): ADC Power Ground. The exposed
pad on the bottom of the package must be soldered to
ground.
OFB(Pin39):Over/UnderFlowDigitalOutputfortheBBus.
OFBishighwhenanoverorunderflowhasoccurredonthe
B bus. At high impedance state in full rate CMOS mode.
2217f
14
LTC2217
PIN FUNCTIONS
For LVDS Mode. STANDARD or LOW POWER
OGND (Pins 31 and 50): Output Driver Ground.
SENSE (Pin 1): Reference Mode Select and External
OV (Pins 32 and 49): Positive Supply for the Output
DD
Reference Input. Tie SENSE to V to select the internal
Drivers. Bypass to ground with 0.1μF capacitor.
DD
2.5V bandgap reference. An external reference of 2.5V or
1.25V may be used; both reference values will set a full
scale ADC range of 2.75V.
–
+
CLKOUT /CLKOUT (Pins 39 and 40): LVDS Data Valid
+
0utput. Latch data on the rising edge of CLKOUT , falling
edge of CLKOUT .
–
GND (Pins 2, 4, 7, 10, 11, 14, 18): ADC Power Ground.
–
+
OF /OF (Pins59and60):Over/UnderFlowDigitalOutput
OF is high when an over or under flow has occurred.
V
CM
(Pin 3): 1.575V Output. Optimum voltage for input
common mode. Must be bypassed to ground with a
minimum of 2.2μF. Ceramic chip capacitors are recom-
mended.
LVDS (Pin 61): Data Output Mode Select Pin. Connecting
LVDSto0VselectsfullrateCMOSmode.ConnectingLVDS
to1/3V selectsdemultiplexedCMOSmode. Connecting
DD
V
DD
(Pins 5, 6, 15, 16, 17): 3.3V Analog Supply Pin.
LVDS to 2/3V selects Low Power LVDS mode. Connect-
DD
Bypass to GND with 1μF ceramic chip capacitors.
ing LVDS to V selects Standard LVDS mode.
DD
+
A
A
(Pin 8): Positive Differential Analog Input.
(Pin 9): Negative Differential Analog Input.
MODE (Pin 62): Output Format and Clock Duty Cycle
Stabilizer Selection Pin. Connecting MODE to 0V selects
offset binary output format and disables the clock duty
IN
IN
–
+
ENC (Pin 12): Positive Differential Encode Input. The
cyclestabilizer.ConnectingMODEto1/3V selectsoffset
DD
+
sampled analog input is held on the rising edge of ENC .
binary output format and enables the clock duty cycle sta-
Internally biased to 1.6V through a 6.2kΩ resistor. Output
bilizer.ConnectingMODEto2/3V selects2’scomplement
DD
+
data can be latched on the rising edge of ENC .
output format and enables the clock duty cycle stabilizer.
–
Connecting MODE to V selects 2’s complement output
DD
ENC (Pin 13): Negative Differential Encode Input. The
sampled analog input is held on the falling edge of ENC .
–
format and disables the clock duty cycle stabilizer.
Internally biased to 1.6V through a 6.2kΩ resistor. By-
pass to ground with a 0.1μF capacitor for a single-ended
Encode signal.
RAND(Pin63):DigitalOutputRandomizationSelectionPin.
RAND low results in normal operation. RAND high selects
D1-D15 to be EXCLUSIVE-ORed with D0 (the LSB). The
outputcanbedecodedbyagainapplyinganXORoperation
between the LSB and all other bits. The mode of operation
reduces the effects of digital output interference.
SHDN (Pin 19): Power Shutdown Pin. SHDN = low results
in normal operation. SHDN = high results in powered
down analog circuitry and the digital outputs are set in
high impedance state.
NC (Pin 64): Not Connected Internally. For pin compat-
ibility with the LTC2208 this pin should be connected to
DITH (Pin 20): Internal Dither Enable Pin. DITH = low
disablesinternaldither.DITH=highenablesinternaldither.
Refer to Internal Dither section of the data sheet for details
on dither operation.
GND or V as required. Otherwise no connection.
DD
GND (Exposed Pad Pin 65): ADC Power Ground. The
exposed pad on the bottom of the package must be sol-
dered to ground.
–
+
–
+
D0 /D0 to D15 /D15 (Pins 21-30, 33-38, 41-48 and
51-58): LVDS Digital Outputs. All LVDS outputs require
differential100ΩterminationresistorsattheLVDSreceiver.
+
–
D15 /D15 is the MSB.
2217f
15
LTC2217
BLOCK DIAGRAM
+
A
A
IN
IN
V
DD
INPUT
S/H
FIRST PIPELINED
ADC STAGE
SECOND PIPELINED
ADC STAGE
THIRD PIPELINED
ADC STAGE
FOURTH PIPELINED
ADC STAGE
FIFTH PIPELINED
ADC STAGE
–
GND
DITHER
SIGNAL
GENERATOR
CORRECTION LOGIC
AND
SHIFT REGISTER
ADC CLOCKS
RANGE
SELECT
OV
DD
CLKOUT+
CLKOUT–
+
SENSE
OF
DIFFERENTIAL
INPUT
LOW JITTER
CLOCK
DRIVER
–
OF
ADC
REFERENCE
+
–
PGA
CONTROL
LOGIC
D15
D15
OUTPUT
DRIVERS
•
•
•
V
CM
BUFFER
+
D0
–
D0
VOLTAGE
REFERENCE
2217 F01
OGND
+
–
ENC
ENC
SHDN RAND M0DE LVDS DITH
Figure 1. Functional Block Diagram
2217f
16
LTC2217
OPERATION
DYNAMIC PERFORMANCE
by the presence of another sinusoidal input at a different
frequency.
Signal-to-Noise Plus Distortion Ratio
If two pure sine waves of frequencies fa and fb are applied
totheADCinput,nonlinearitiesintheADCtransferfunction
can create distortion products at the sum and difference
frequencies of mfa nfb, where m and n = 0, 1, 2, 3, etc.
For example, the 3rd order IMD terms include (2fa + fb),
(fa + 2fb), (2fa - fb) and (fa - 2fb). The 3rd order IMD is
defined as the ratio of the RMS value of either input tone
to the RMS value of the largest 3rd order IMD product.
The signal-to-noise plus distortion ratio [S/(N+D)] is the
ratiobetweentheRMSamplitudeofthefundamentalinput
frequency and the RMS amplitude of all other frequency
components at the ADC output. The output is band lim-
ited to frequencies above DC to below half the sampling
frequency (Nyquist Frequency).
Signal-to-Noise Ratio
Spurious Free Dynamic Range (SFDR)
The signal-to-noise (SNR) is the ratio between the RMS
amplitudeofthefundamentalinputfrequencyandtheRMS
amplitude of all other frequency components, except the
first five harmonics.
The ratio of the RMS input signal amplitude to the RMS
value of the peak spurious spectral component expressed
in dBc. SFDR may also be calculated relative to full scale
and expressed in dBFS.
Total Harmonic Distortion
Full Power Bandwidth
Total harmonic distortion is the ratio of the RMS sum of
all harmonics of the input signal to the fundamental itself.
The out-of-band harmonics alias into the frequency band
between DC and half the sampling frequency (Nyquist
Frequency). THD is expressed as:
The Full Power bandwidth is that input frequency at which
theamplitudeofthereconstructedfundamentalisreduced
by 3dB from a full scale input signal.
Aperture Delay Time
⎛
⎞
2
2
2
2
V + V + V +…V
N
+
–
(
)
2
3
4
ThetimefromwhenarisingENC equalstheENC voltage
to the instant that the input signal is held by the sample-
and-hold circuit.
⎜
⎜
⎟
⎟
THD= –20Log
V1
⎜
⎝
⎟
⎠
Aperture Delay Jitter
where V is the RMS amplitude of the fundamental fre-
1
quencyandV throughV aretheamplitudesofthesecond
2
N
The variation in the aperture delay time from conversion
to conversion. This random variation will result in noise
whensamplinganACinput.Thesignal-to-noiseratioterm
due to the jitter alone will be:
through nth harmonics.
Intermodulation Distortion
If the ADC input signal consists of more than one spectral
component, the ADC transfer function nonlinearity can
produce intermodulation distortion (IMD) in addition to
THD. IMD is the change in one sinusoidal input caused
SNR
= –20log (2π • f • t
)
JITTER
IN JITTER
ThisformulastatesSNRduetojitteraloneatanyamplitude
in terms of dBc.
2217f
17
LTC2217
APPLICATIONS INFORMATION
CONVERTER OPERATION
SAMPLE/HOLD OPERATION AND INPUT DRIVE
Sample/Hold Operation
TheLTC2217isaCMOSpipelinedmultistepconverterwith
a low noise front-end. As shown in Figure 1, the converter
has five pipelined ADC stages; a sampled analog input
will result in a digitized value seven cycles later (see the
TimingDiagramsection).Theanaloginputisdifferentialfor
improvedcommonmodenoiseimmunityandtomaximize
the input range. Additionally, the differential input drive
will reduce even order harmonics of the sample and hold
circuit. The encode input is also differential for improved
common mode noise immunity.
Figure2showsanequivalentcircuitfortheLTC2217CMOS
differentialsampleandhold. Thedifferentialanaloginputs
are sampled directly onto sampling capacitors (C
through NMOS transitors. The capacitors shown attached
)
SAMPLE
to each input (C
) are the summation of all other
PARASITIC
capacitance associated with each input.
During the sample phase when ENC is low, the NMOS
transistors connect the analog inputs to the sampling
capacitors and they charge to, and track the differential
input voltage. When ENC transitions from low to high, the
sampled input voltage is held on the sampling capacitors.
During the hold phase when ENC is high, the sampling
capacitors are disconnected from the input and the held
voltage is passed to the ADC core for processing. As ENC
transitions for high to low, the inputs are reconnected to
the sampling capacitors to acquire a new sample. Since
the sampling capacitors still hold the previous sample,
a charging glitch proportional to the change in voltage
between samples will be seen at this time. If the change
between the last sample and the new sample is small,
the charging glitch seen at the input will be small. If the
The LTC2217 has two phases of operation, determined
+
+
–
–
by the state of the differential ENC /ENC input pins. For
–
brevity, the text will refer to ENC greater than ENC as
+
ENC high and ENC less than ENC as ENC low.
Each pipelined stage shown in Figure 1 contains an ADC,
a reconstruction DAC and an interstage amplifier. In
operation, the ADC quantizes the input to the stage and
the quantized value is subtracted from the input by the
DAC to produce a residue. The residue is amplified and
output by the residue amplifier. Successive stages oper-
ate out of phase so that when odd stages are outputting
their residue, the even stages are acquiring that residue
and vice versa.
When ENC is low, the analog input is sampled differen-
tially directly onto the input sample-and-hold capacitors,
inside the “input S/H” shown in the block diagram. At the
instant that ENC transitions from low to high, the voltage
on the sample capacitors is held. While ENC is high, the
held input voltage is buffered by the S/H amplifier which
drivesthefirstpipelinedADCstage.Thefirststageacquires
the output of the S/H amplifier during the high phase of
ENC. When ENC goes back low, the first stage produces
its residue which is acquired by the second stage. At
the same time, the input S/H goes back to acquiring the
analog input. When ENC goes high, the second stage
produces its residue which is acquired by the third stage.
An identical process is repeated for the third and fourth
stages, resulting in a fourth stage residue that is sent to
the fifth stage for final evaluation.
LTC2217
V
DD
C
C
SAMPLE
7.3pF
R
R
R
20Ω
PARASITIC
3Ω
ON
+
A
IN
C
1.8pF
PARASITIC
V
DD
SAMPLE
7.3pF
R
ON
PARASITIC
3Ω
20Ω
–
A
IN
C
1.8pF
PARASITIC
V
DD
1.6V
6k
+
–
ENC
ENC
Each ADC stage following the first has additional range to
accommodate flash and amplifier offset errors. Results
from all of the ADC stages are digitally delayed such that
the results can be properly combined in the correction
logic before being sent to the output buffer.
6k
1.6V
2217 F02
Figure 2. Equivalent Input Circuit
2217f
18
LTC2217
APPLICATIONS INFORMATION
input change is large, such as the change seen with input
frequencies near Nyquist, then a larger charging glitch
will be seen.
has a very broadband S/H circuit, DC to 400MHz; it can
be used in a wide range of applications; therefore, it is not
possible to provide a single recommended RC filter.
Figures3and4showtwoexamplesofinputRCfilteringfor
two ranges of input frequencies. In general it is desirable
to make the capacitors as large as can be tolerated—this
will help suppress random noise as well as noise coupled
fromthedigitalcircuitry.TheLTC2217doesnotrequireany
input filter to achieve data sheet specifications; however,
no filtering will put more stringent noise requirements on
the input drive circuitry.
Common Mode Bias
TheADCsample-and-holdcircuitrequiresdifferentialdrive
toachievespecifiedperformance.Eachinputshouldswing
0.6875V for the 2.75V range, around a common mode
voltage of 1.575V. The V output pin (Pin 3) is designed
to provide the common mode bias level. V can be tied
CM
CM
directly to the center tap of a transformer to set the DC
input level or as a reference level to an op amp differential
driver circuit. The V pin must be bypassed to ground
CM
Transformer Coupled Circuits
close to the ADC with 2.2μF or greater.
Figure 3 shows the LTC2217 being driven by an RF trans-
former with a center-tapped secondary. The secondary
Input Drive Impedance
center tap is DC biased with V , setting the ADC input
CM
Aswithallhighperformance,highspeedADCsthedynamic
performanceoftheLTC2217canbeinfluencedbytheinput
drivecircuitry,particularlythesecondandthirdharmonics.
SourceimpedanceandinputreactancecaninfluenceSFDR.
At the falling edge of ENC the sample and hold circuit will
connectthesamplingcapacitortotheinputpinandstartthe
samplingperiod.ThesamplingperiodendswhenENCrises,
holding the sampled input on the sampling capacitor. Ide-
ally,theinputcircuitryshouldbefastenoughtofullycharge
the sampling capacitor during the sampling period
signal at its optimum DC level. Figure 3 shows a 1:1 turns
ratiotransformer.Otherturnsratioscanbeused;however,
astheturnsratioincreasessodoestheimpedanceseenby
the ADC. Source impedance greater than 50Ω can reduce
the input bandwidth and increase high frequency distor-
tion. A disadvantage of using a transformer is the loss of
lowfrequencyresponse.MostsmallRFtransformershave
poor performance at frequencies below 1MHz.
Center-tapped transformers provide a convenient means
of DC biasing the secondary; however, they often show
poor balance at high input frequencies, resulting in large
2nd order harmonics.
1/(2 • f ); however, this is not always possible and
ENCODE
the incomplete settling may degrade the SFDR. The sam-
pling glitch has been designed to be as linear as possible
to minimize the effects of incomplete settling.
V
CM
For the best performance it is recommended to have a
source impedance of 100Ω or less for each input. The
source impedance should be matched for the differential
inputs. Poor matching will result in higher even order
harmonics, especially the second.
2.2μF
5Ω
10Ω
+
5Ω
A
A
IN
IN
T1
8.2pF
LTC2217
35Ω
35Ω
8.2pF
0.1μF
10Ω
INPUT DRIVE CIRCUITS
Input Filtering
–
5Ω
8.2pF
T1 = MA/COM ETC1-1T
RESISTORS, CAPACITORS
ARE 0402 PACKAGE SIZE
EXCEPT 2.2μF
2217 F03
A first-order RC low-pass filter at the input of the ADC can
servetwofunctions:limitthenoisefrominputcircuitryand
provide isolation from ADC S/H switching. The LTC2217
Figure 3. Single-Ended to Differential Conversion
Using a Transformer. Recommended for Input
Frequencies from 5MHz to 100MHz
2217f
19
LTC2217
APPLICATIONS INFORMATION
Figure 4 shows transformer coupling using a transmis-
sion line balun transformer. This type of transformer has
much better high-frequency response and balance than
fluxcoupledcenter-taptransformers.Couplingcapacitors
are added at the ground and input primary terminals to
allow the secondary terminals to be biased at 1.575V.
V
CM
2.2μF
HIGH SPEED
DIFFERENTIAL
AMPLIFIER
+
–
25Ω
25Ω
A
IN
IN
LTC2217
ANALOG
INPUT
+
+
12pF
CM
–
–
A
V
CM
12pF
AMPLIFIER = LTC6600-20,
LTC1993, ETC.
2217 F05
2.2μF
5Ω
5Ω
0.1μF
0.1μF
+
–
10Ω
A
A
IN
IN
Figure 5. DC Coupled Input with Differential Amplifier
ANALOG
INPUT
LTC2217
0.1μF
25Ω
25Ω
4.7pF
reference, tie the SENSE pin to V . To use an external
DD
T1
1:1
reference, simply apply either a 1.25V or 2.5V reference
4.7pF
10Ω
5Ω
voltage to the SENSE input pin. Both 1.25V and 2.5V ap-
4.7pF
pliedtoSENSEwillresultinafullscalerangeof2.75V .A
T1 = MA/COM ETC1-1-13
P-P
2217 F04
RESISTORS, CAPACITORS
ARE 0402 PACKAGE SIZE
EXCEPT 2.2μF
1.575V output, V , is provided for a common mode bias
CM
for input drive circuitry. An external bypass capacitor is
requiredfortheV output.Thisprovidesahighfrequency
Figure 4. Using a Transmission Line Balun Transformer.
Recommended for Input Frequencies from 100MHz to 250MHz
CM
low impedance path to ground for internal and external
circuitry. This is also the compensation capacitor for the
reference; which will not be stable without this capacitor.
The minimum value required for stability is 2.2μF.
Direct Coupled Circuits
Figure 5 demonstrates the use of a differential amplifier to
convert a single ended input signal into a differential input
signal. The advantage of this method is that it provides
low frequency input response; however, the limited gain
bandwidth of any op amp or closed-loop amplifier will de-
gradetheADCSFDRathighinputfrequencies.Additionally,
wideband op amps or differential amplifiers tend to have
high noise. As a result, the SNR will be degraded unless
the noise bandwidth is limited prior to the ADC input.
RANGE
SELECT
AND GAIN
CONTROL
TIE TO V TO USE
DD
INTERNAL
ADC
REFERENCE
INTERNAL 2.5V
REFERENCE
OR INPUT AN
EXTERNAL 2.5V
REFERENCE
SENSE
PGA
OR INPUT AN
EXTERNAL 1.25V
REFERENCE
2.5V
BANDGAP
REFERENCE
Reference Operation
V
CM
Figure6showstheLTC2217referencecircuitryconsisting
of a 2.5V bandgap reference, a programmable gain ampli-
fier and control circuit. The LTC2217 has three modes of
reference operation: Internal Reference, 1.25V external
reference or 2.5V external reference. To use the internal
1.575V
BUFFER
2.2μF
2217 F06
Figure 6. Reference Circuit
2217f
20
LTC2217
APPLICATIONS INFORMATION
3. If the ADC is clocked with a fixed-frequency sinusoidal
signal, filter the encode signal to reduce wideband
noise.
The internal programmable gain amplifier provides the
internal reference voltage for the ADC. This amplifier has
very stringent settling requirements and therefore is not
accessible for external use.
4. Balance the capacitance and series resistance at both
encode inputs such that any coupled noise will appear
at both inputs as common mode noise.
TheSENSEpincanbedriven 5%aroundthenominal2.5V
or 1.25V external reference inputs. This adjustment range
can be used to trim the ADC gain error or other system
gain errors. When selecting the internal reference, the
The encode inputs have a common mode range of 1.2V
to V . Each input may be driven from ground to V for
DD
DD
SENSE pin should be tied to V as close to the converter
DD
single-ended drive.
as possible. If the sense pin is driven externally it should
be bypassed to ground as close to the device as possible
with 1μF ceramic capacitor.
LTC2217
V
DD
TO INTERNAL
ADC CLOCK
DRIVERS
V
CM
1.575V
1.6V
6k
2.2μF
V
DD
LTC2217
SENSE
6
2
+
3.3V
1μF
LTC1461-2.5
4
ENC
2.2μF
1.6V
6k
V
DD
2217 F07
–
ENC
Figure 7. A 2.75V Range ADC with
an External 2.5V Reference
Driving the Encode Inputs
2217 F08a
The noise performance of the LTC2217 can depend on
the encode signal quality as much as on the analog input.
The encode inputs are intended to be driven differentially,
primarily for noise immunity from common mode noise
sources. Each input is biased through a 6k resistor to a
1.6V bias. The bias resistors set the DC operating point
fortransformercoupleddrivecircuitsandcansetthelogic
threshold for single-ended drive circuits.
Figure 8a. Equivalent Encode Input Circuit
0.1μF
+
T1
ENC
50Ω
50Ω
100Ω
8.2pF
LTC2217
0.1μF
–
0.1μF
ENC
Any noise present on the encode signal will result in ad-
ditional aperture jitter that will be RMS summed with the
inherent ADC aperture jitter.
2217 F08b
T1 = MA/COM ETC1-1-13
RESISTORS AND CAPACITORS
ARE 0402 PACKAGE SIZE
In applications where jitter is critical (high input frequen-
cies), take the following into consideration:
Figure 8b. Balun-Driven Encode
1. Differential drive should be used.
2. Use as large an amplitude possible. If using trans-
former coupling, use a higher turns ratio to increase the
amplitude.
2217f
21
LTC2217
APPLICATIONS INFORMATION
+
The lower limit of the LTC2217 sample rate is determined
by droop affecting the sample and hold circuits. The
pipelined architecture of this ADC relies on storing analog
signals on small valued capacitors. Junction leakage will
dischargethecapacitors.Thespecifiedminimumoperating
frequency for the LTC2217 is 1Msps.
ENC
V
= 1.6V
THRESHOLD
–
LTC2217
1.6V
ENC
0.1μF
2217 F09
Figure 9. Single-Ended ENC Drive,
Not Recommended for Low Jitter
DIGITAL OUTPUTS
3.3V
Digital Output Modes
3.3V
MC100LVELT22
D0
The LTC2217 can operate in four digital output modes:
standard LVDS, low power LVDS, full rate CMOS, and
demultiplexed CMOS. The LVDS pin selects the mode of
operation. This pin has a four level logic input, centered at
130Ω
Q0
130Ω
ENC
+
–
LTC2217
ENC
Q0
0,1/3VDD,2/3V andVDD.Anexternalresistordividercan
DD
83Ω
83Ω
be used to set the 1/3VDD and 2/3VDD logic levels. Table 1
shows the logic states for the LVDS pin.
2217 F10
Table 1. LVDS Pin Function
LVDS
Figure 10. ENC Drive Using a CMOS to PECL Translator
DIGITAL OUTPUT MODE
Full-Rate CMOS
Demultiplexed CMOS
Low Power LVDS
LVDS
0V(GND)
Maximum and Minimum Encode Rates
1/3V
2/3V
DD
DD
The maximum encode rate for the LTC2217 is 105Msps.
For the ADC to operate properly the encode signal should
have a 50% ( 5%) duty cycle. Each half cycle must have
at least 4.5ns for the ADC internal circuitry to have enough
settlingtimeforproperoperation.Achievingaprecise50%
duty cycle is easy with differential sinusoidal drive using
a transformer or using symmetric differential logic such
as PECL or LVDS. When using a single-ended ENCODE
signal asymmetric rise and fall times can result in duty
cycles that are far from 50%.
V
DD
Digital Output Buffers (CMOS Modes)
Figure 11 shows an equivalent circuit for a single output
buffer in CMOS Mode, Full-Rate or Demultiplexed. Each
buffer is powered by OVDD and OGND, isolated from the
ADCpowerandground.TheadditionalN-channeltransistor
intheoutputdriverallowsoperationdowntolowvoltages.
The internal resistor in series with the output makes the
output appear as 50Ω to external circuitry and eliminates
the need for external damping resistors.
An optional clock duty cycle stabilizer can be used if the
input clock does not have a 50% duty cycle. This circuit
usestherisingedgeofENCpintosampletheanaloginput.
The falling edge of ENC is ignored and an internal falling
edge is generated by a phase-locked loop. The input clock
duty cycle can vary from 30% to 70% and the clock duty
cycle stabilizer will maintain a constant 50% internal duty
cycle. If the clock is turned off for a long period of time,
the duty cycle stabilizer circuit will require one hundred
clock cycles for the PLL to lock onto the input clock. To
use the clock duty cycle stabilizer, the MODE pin must be
As with all high speed/high resolution converters, the
digital output loading can affect the performance. The
digital outputs of the LTC2217 should drive a minimum
capacitive load to avoid possible interaction between the
digital outputs and sensitive input circuitry. The output
should be buffered with a device such as a ALVCH16373
CMOS latch. For full speed operation the capacitive load
should be kept under 10pF. A resistor in series with the
connected to 1/3V or 2/3V using external resistors.
DD
DD
2217f
22
LTC2217
APPLICATIONS INFORMATION
output may be used, but is not required since the ADC
has a series resistor of 43Ω on-chip.
+
–
resistor, even if the signal is not used (such as OF /OF or
+
–
CLKOUT /CLKOUT ). To minimize noise the PC board
traces for each LVDS output pair should be routed close
together. TominimizeclockskewallLVDSPCboardtraces
should have about the same length.
Lower OV voltages will also help reduce interference
DD
from the digital outputs.
In Low Power LVDS Mode 1.75mA is steered between
the differential outputs, resulting in 175mV at the LVDS
receiver’s 100Ω termination resistor. The output com-
mon mode voltage is 1.20V, the same as standard LVDS
Mode.
LTC2217
OV
DD
0.5V
TO 3.6V
V
V
DD
DD
0.1μF
OV
DD
DATA
FROM
LATCH
PREDRIVER
LOGIC
43Ω
TYPICAL
DATA
OUTPUT
Data Format
The LTC2217 parallel digital output can be selected for
offset binary or 2’s complement format. The format is
selected with the MODE pin. This pin has a four level
OGND
2217 F11
logic input, centered at 0, 1/3V , 2/3V and V . An
DD
DD
DD
external resistor divider can be user to set the 1/3V
Figure 11. Equivalent Circuit for a Digital Output Buffer
DD
and 2/3V logic levels. Table 2 shows the logic states
DD
for the MODE pin.
Digital Output Buffers (LVDS Modes)
Table 2. MODE Pin Function
CLOCK DUTY
Figure 12 shows an equivalent circuit for an LVDS output
+
–
pair. A 3.5mA current is steered from OUT to OUT or
vice versa, which creates a 350mV differential voltage
acrossthe100ΩterminationresistorattheLVDSreceiver.
A feedback loop regulates the common mode output volt-
age to 1.20V. For proper operation each LVDS output pair
must be terminated with an external 100Ω termination
MODE
OUTPUT FORMAT
CYCLE STABILIZER
0(GND)
Offset Binary
Off
On
On
Off
1/3V
2/3V
Offset Binary
DD
DD
2’s Complement
2’s Complement
V
DD
LTC2217
OV
DD
3.3V
3.5mA
0.1μF
V
DD
V
DD
OV
DD
43Ω
43Ω
DATA
FROM
LATCH
10k
10k
PREDRIVER
LOGIC
LVDS
RECEIVER
OV
DD
100Ω
+
–
1.20V
OGND
2217 F12
Figure 12. Equivalent Output Buffer in LVDS Mode
2217f
23
LTC2217
APPLICATIONS INFORMATION
Overflow Bit
LSB and all other bits. The LSB, OF and CLKOUT output
are not affected. The output Randomizer function is active
when the RAND pin is high.
An overflow output bit (OF) indicates when the converter
is over-ranged or under-ranged. In CMOS mode, a logic
high on the OFA pin indicates an overflow or underflow on
the A data bus, while a logic high on the OFB pin indicates
an overflow on the B data bus. In LVDS mode, a differ-
ential logic high on OF /OF pins indicates an overflow
or underflow.
LTC2217
CLKOUT
CLKOUT
OF
+
–
OF
Output Clock
D15
The ADC has a delayed version of the encode input avail-
able as a digital output, CLKOUT. The CLKOUT pin can
be used to synchronize the converter data to the digital
system. This is necessary when using a sinusoidal en-
code. In both CMOS modes, A bus data will be updated
as CLKOUTA falls and CLKOUTB rises. In demultiplexed
CMOS mode the B bus data will be updated as CLKOUTA
falls and CLKOUTB rises.
D15 ⊕ D0
D14 ⊕ D0
D14
•
•
•
D2
D1
D2 ⊕ D0
D1 ⊕ D0
In Full Rate CMOS Mode, only the A data bus is active;
data may be latched on the rising edge of CLKOUTA or
the falling edge of CLKOUTB.
RAND = HIGH,
SCRAMBLE
ENABLED
RAND
D0
In demultiplexed CMOS mode CLKOUTA and CLKOUTB
will toggle at 1/2 the frequency of the encode signal. Both
the A bus and the B bus may be latched on the rising edge
of CLKOUTA or the falling edge of CLKOUTB.
D0
2217 F13
Figure 13. Functional Equivalent of Digital Output Randomizer
Digital Output Randomizer
Output Driver Power
Interference from the ADC digital outputs is sometimes
unavoidable. Interference from the digital outputs may be
fromcapacitiveorinductivecoupling, orcouplingthrough
the ground plane. Even a tiny coupling factor can result in
discernible unwanted tones in the ADC output spectrum.
By randomizing the digital output before it is transmitted
offchip,theseunwantedtonescanberandomized,trading
a slight increase in the noise floor for a large reduction in
unwanted tone amplitude.
Separate output power and ground pins allow the output
drivers to be isolated from the analog circuitry. The power
supply for the digital output buffers, OV , should be tied
DD
to the same power supply as for the logic being driven.
For example, if the converter is driving a DSP powered
by a 1.8V supply, then OV should be tied to that same
DD
1.8V supply. In CMOS mode OV can be powered with
DD
any logic voltage up to the 3.6V. OGND can be powered
with any voltage from ground up to 1V and must be less
The digital output is “Randomized” by applying an exclu-
sive-ORlogicoperationbetweentheLSBandallotherdata
output bits. To decode, the reverse operation is applied;
that is, an exclusive-OR operation is applied between the
than OV . The logic outputs will swing between OGND
DD
and OV . In LVDS Mode, OV should be connected to
DD
DD
a 3.3V supply and OGND should be connected to GND.
2217f
24
LTC2217
APPLICATIONS INFORMATION
Internal Dither
PC BOARD
FPGA
The LTC2217 is a 16-bit ADC with a very linear transfer
function;however,atlowinputlevelsevenslightimperfec-
tions in the transfer function will result in unwanted tones.
Small errors in the transfer function are usually a result
of ADC element mismatches. An optional internal dither
mode can be enabled to randomize the input location on
the ADC transfer curve, resulting in improved SFDR for
low signal levels.
CLKOUT
OF
D15 ⊕ D0
D15
D14 ⊕ D0
As shown in Figure 15, the output of the sample-and-hold
amplifier is summed with the output of a dither DAC. The
dither DAC is driven by a long sequence pseudo-random
numbergenerator;therandomnumberfedtotheditherDAC
is also subtracted from the ADC result. If the dither DAC
is precisely calibrated to the ADC, very little of the dither
signalwillbeseenattheoutput.Thedithersignalthatdoes
leak through will appear as white noise. The dither DAC is
calibrated to result in typically less than 0.5dB elevation
in the noise floor of the ADC as compared to the noise
floor with dither off, when a suitable input termination is
provided (see Demo Board schematic DC996B).
D14
•
•
•
LTC2217
D2 ⊕ D0
D1 ⊕ D0
D2
D1
D0
D0
2217 F14
Figure 14. Descrambling a Scrambled Digital Output
LTC2217
CLKOUT
OF
+
D15
AIN
16-BIT
PIPELINED
ADC CORE
•
•
•
DIGITAL
SUMMATION
ANALOG
INPUT
OUTPUT
DRIVERS
S/H
AMP
–
AIN
D0
CLOCK/DUTY
CYCLE
CONTROL
MULTIBIT DEEP
PSEUDO-RANDOM
NUMBER
PRECISION
DAC
GENERATOR
2217 F15
+
–
ENC
ENC
DITH
DITHER ENABLE
HIGH = DITHER ON
LOW = DITHER OFF
Figure 15. Functional Equivalent Block Diagram of Internal Dither Circuit
2217f
25
LTC2217
APPLICATIONS INFORMATION
Grounding and Bypassing
connecting the pins and bypass capacitors must be kept
short and should be made as wide as possible.
The LTC2217 requires a printed circuit board with a
clean unbroken ground plane; a multilayer board with an
internal ground plane is recommended. The pinout of the
LTC2217 has been optimized for a flowthrough layout so
that the interaction between inputs and digital outputs is
minimized. Layout for the printed circuit board should
ensure that digital and analog signal lines are separated
as much as possible. In particular, care should be taken
not to run any digital track alongside an analog signal
track or underneath the ADC.
The LTC2217 differential inputs should run parallel and
close to each other. The input traces should be as short
as possible to minimize capacitance and to minimize
noise pickup.
Heat Transfer
Most of the heat generated by the LTC2217 is transferred
from the die through the bottom-side exposed pad. For
good electrical and thermal performance, the exposed
pad must be soldered to a large grounded pad on the PC
board. It is critical that the exposed pad and all ground
pins are connected to a ground plane of sufficient area
with as many vias as possible.
High quality ceramic bypass capacitors should be used
at the V
V
, and OV pins. Bypass capacitors must
DD, CM DD
be located as close to the pins as possible. The traces
2217f
26
LTC2217
APPLICATIONS INFORMATION
Layer 1 Component Side
Layer 2 GND Plane
2217f
27
LTC2217
APPLICATIONS INFORMATION
Layer 3 GND
Layer 4 GND
2217f
28
LTC2217
APPLICATIONS INFORMATION
Layer 5 GND
Layer 6 Bottom Side
2217f
29
LTC2217
APPLICATIONS INFORMATION
V C 5
V C 4
V C 3
V C 2
V C 1
V E 5
V E 4
V E 3
V E 2
V E 1
V C 5
V C 4
V C 3
V C 2
V C 1
V E 5
V E 4
V E 3
V E 2
V E 1
4 8
4 7
2 6
2 5
1 2
3 7
3 6
2 3
4 8
4 7
2 6
2 5
1 2
3 7
3 6
2 3
2
1
2
1
6 5
O V D D 4 9
O G N D 5 0
O V D D 3 2
3 2
4 9
5 0
5 1
5 2
5 3
5 4
5 5
5 6
5 7
5 8
5 9
6 0
6 1
6 2
6 3
6 4
O G N D 3 1
3 1
D 4 +
3 0
D 1 2 –
D 1 2 +
D 1 3 –
D 1 3 +
D 1 4 –
D 1 4 +
D 1 5 –
D 1 5 +
D 4 –
2 9
D 3 +
2 7
D 3 –
2 7
D 2 +
2 6
D 2 –
2 5
D 1 +
2 4
D 1 –
2 3
O F –
O F +
L V D S
D 0 +
2 2
D 0 –
2 1
D I T H
2 0
S H D N
M O D E
R A N D
1 9
G N D 1 8
1 8
V D D 1 7
N C
1 7
•
•
2217f
30
LTC2217
PACKAGE DESCRIPTION
UP Package
64-Lead Plastic QFN (9mm × 9mm)
(Reference LTC DWG # 05-08-1705)
0.70 0.05
7.15 0.05
7.50 REF
8.10 0.05 9.50 0.05
(4 SIDES)
7.15 0.05
PACKAGE OUTLINE
0.25 0.05
0.50 BSC
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
APPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED
0.75 0.05
R = 0.10
TYP
R = 0.115
TYP
9 .00 0.10
(4 SIDES)
63 64
0.40 0.10
PIN 1 TOP MARK
(SEE NOTE 5)
1
2
PIN 1
CHAMFER
C = 0.35
7.15 0.10
7.50 REF
(4-SIDES)
7.15 0.10
(UP64) QFN 0406 REV C
0.200 REF
0.25 0.05
0.50 BSC
BOTTOM VIEW—EXPOSED PAD
0.00 – 0.05
NOTE:
1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION WNJR-5
2. ALL DIMENSIONS ARE IN MILLIMETERS
3. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.20mm ON ANY SIDE, IF PRESENT
4. EXPOSED PAD SHALL BE SOLDER PLATED
5. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE
6. DRAWING NOT TO SCALE
2217f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
31
LTC2217
RELATED PARTS
PART NUMBER DESCRIPTION
COMMENTS
LTC1749
LTC1750
LT1993
12-Bit, 80Msps Wideband ADC
Up to 500MHz IF Undersampling, 87dB SFDR
Up to 500MHz IF Undersampling, 90dB SFDR
600MHz BW, 75dBc Distortion at 70MHz
150mW, 81.6dB SNR, 100dB SFDR
14-Bit, 80Msps Wideband ADC
High Speed Differential Op Amp
16-Bit, 10Msps ADC
16-Bit, 25Msps ADC
16-Bit, 40Msps ADC
16-Bit, 65Msps ADC
16-Bit, 80Msps ADC
16-Bit, 105Msps ADC
16-Bit, 130Msps ADC
16-Bit, 160Msps ADC
16-Bit, 65Msps ADC
16-Bit, 80Msps ADC
12-Bit, 170Msps ADC
12-Bit, 185Msps ADC
14-Bit, 65Msps ADC
10-Bit, 105Msps ADC
10-Bit, 125Msps ADC
12-Bit, 105Msps ADC
12-Bit, 125Msps ADC
14-Bit, 105Msps ADC
14-Bit, 125Msps ADC
Dual 14-Bit, 80Msps ADC
LTC2202
LTC2203
LTC2204
LTC2205
LTC2206
LTC2207
LTC2208
LTC2209
LTC2215
LTC2216
LTC2220
LTC2220-1
LTC2249
LTC2250
LTC2251
LTC2252
LTC2253
LTC2254
LTC2255
LTC2299
LT5512
230mW, 81.6dB SNR, 100dB SFDR
470mW, 79dB SNR, 100dB SFDR
530mW, 79dB SNR, 100dB SFDR
725mW, 77.9dB SNR, 100dB SFDR
900mW, 77.9dB SNR, 100dB SFDR
1250mW, 77.7dB SNR, 100dB SFDR
1450mW, 77.1dB SNR, 100dB SFDR
700mW, 81.5dB SNR, 100dB SFDR
970mW, 81.3dB SNR, 100dB SFDR
890mW, 67.5dB SNR, 9mm × 9mm QFN Package
910mW, 67.5dB SNR, 9mm × 9mm QFN Package
230mW, 73dB SNR, 5mm × 5mm QFN Package
320mW, 61.6dB SNR, 5mm × 5mm QFN Package
395mW, 61.6dB SNR, 5mm × 5mm QFN Package
320mW, 70.2dB SNR, 5mm × 5mm QFN Package
395mW, 70.2dB SNR, 5mm × 5mm QFN Package
320mW, 72.5dB SNR, 5mm × 5mm QFN Package
395mW, 72.4dB SNR, 5mm × 5mm QFN Package
445mW, 73dB SNR, 9mm × 9mm QFN Package
DC to 3GHz, 21dBm IIP3, Integrated LO Buffer
DC-3GHz High Signal Level
Downconverting Mixer
LT5514
LT5522
Ultralow Distortion IF Amplifier/ADC 450MHz 1dB BW, 47dB OIP3, Digital Gain Control 10.5dB to 33dB in 1.5dB/Step
Driver with Digitally Controlled Gain
600MHz to 2.7GHz High Linearity
Downconverting Mixer
4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended RF and LO Ports
2217f
LT 0108 • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
32
●
●
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
© LINEAR TECHNOLOGY CORPORATION 2007
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