LTC3252EDE [Linear]
Dual, Low Noise, Inductorless Step-Down DC/DC Converter; 双通道,低噪声,无电感器降压型DC / DC转换器型号: | LTC3252EDE |
厂家: | Linear |
描述: | Dual, Low Noise, Inductorless Step-Down DC/DC Converter |
文件: | 总12页 (文件大小:288K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LTC3252
Dual, Low Noise,
Inductorless Step-Down
DC/DC Converter
U
FEATURES
DESCRIPTIO
The LTC®3252 is a switched capacitor step-down DC/DC
converter that produces two adjustable regulated outputs
from a single 2.7V to 5.5V input. The part uses switched
capacitor fractional conversion to achieve a typical effi-
ciency increase of 50% over that of a linear regulator. No
inductors are required.
■
2.7V to 5.5V Input Voltage Range
■
No Inductors
■
Typical Efficiency 50% Higher than LDOs
■
Spread Spectrum Operation
Low Input and Output Noise
■
■
Shutdown Disconnects Load from VIN
■
Dual Adjustable Independent Outputs
A unique constant frequency, spread spectrum architec-
ture provides a very low noise regulated output as well as
low noise at the input. The part also has Burst Mode®
operationtoprovidehighefficiencyatlowoutputcurrents,
as well as ultralow current shutdown.
(Range: 0.9V to 1.6V)
■
Output Current: 250mA Each Output
■
Low Operating Current: IIN = 60µA Typ
(35µA with One Output Enabled)
■
Low Shutdown Current: IIN = 0.01µA Typ
■
■
■
Low operating currents (60µA with both outputs enabled,
35µA with one output enabled) and low external parts
count make the LTC3252 ideally suited for space-con-
strained battery-powered applications. The part is short-
circuit and overtemperature protected and is available in a
tiny 4mm × 3mm 12-pin DFN package.
Soft-Start Limits Inrush Current at Turn On
Short Circuit and Over Temperature Protected
Available in 4mm × 3mm 12-Pin DFN Package
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APPLICATIO S
■
Handheld Electronic Devices
, LTC and LT are registered trademarks of Linear Technology Corporation.
Burst Mode is a registered trademark of Linear Technology Corporation.
■
Cellular Phones
■
Low Voltage Logic Supplies
■
DSP Power Supplies
■
3.3V to 1.5V Conversion
U
TYPICAL APPLICATIO
1.5V and 1.2V Output Voltages with Shutdown
1.5V/1.2V Efficiency vs Input Voltage
100
I
I
(1.5V) = 100mA
(1.2V) = 100mA
2
11
3
5
1
OUT
OUT
V
= 1.5V
OUT
OUT
90
80
70
60
50
40
30
20
10
0
EN1
EN2
OUT1
FB1
OFF ON
OFF ON
I
≤ 250mA
470k
510k
LTC3252-1.5V
1-CELL
Li-ION
OR 3-CELL
NiMH
V
4.7µF
IN
4
6
4.7µF
+
–
+
–
LTC3252-1.2V
C1
C1
C2
C2
LTC3252
1µF
1µF
LDO-1.5V
LDO-1.2V
10
8
9
V
= 1.2V
≤ 250mA
OUT
OUT2
FB2
I
OUT
261k
510k
7
12
4.7µF
GND
2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5
(V)
3252 TA01
V
IN
3252 TA01a
3252f
1
LTC3252
W W U W
U
W
U
ABSOLUTE AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
(Notes 1, 6)
ORDER PART
TOP VIEW
VIN to GND................................................–0.3V to 6.0V
EN1, EN2, FB1, FB2 to GND .......... –0.3V to (VIN + 0.3V)
IOUT1, IOUT2 (Note 3)........................................... 400mA
Operating Ambient Temperature Range
(Note 2) .................................................. –40°C to 85°C
Storage Temperature Range ................. –65°C to 125°C
Lead Temperature (Soldering, 10 sec).................. 300°C
NUMBER
FB1
EN1
1
2
3
4
5
6
12 FB2
11 EN2
LTC3252EDE
+
V
10 C2
IN
+
C1
9
8
7
OUT2
–
OUT1
C2
GND
–
DE PART
MARKING
C1
DE PACKAGE
12-LEAD (4mm × 3mm) PLASTIC DFN
3252
EXPOSED PAD IS GROUND
(MUST BE SOLDERED TO PCB)
TJMAX = 125°C, θJA = 40°C/W, θJC = 4.3°C/W
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 3.6V, VOUT1 = VOUT2 = 1.5V, C1 = C2 = 1µF, Cin = COUT1 = COUT2
4.7µF (all capacitors ceramic) unless otherwise noted.
=
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
Min Operating Voltage
Max Operating Voltage
(Note 4)
●
●
●
2.7
V
V
IN
5.5
I
Operating Current,
Both Outputs Enabled
I
= 0mA, V
= V , V
= V ,
60
35
100
µA
VIN
OUT
EN1
IN EN2
IN
2.7V ≤ V ≤ 5.5V
IN
Operating Current,
I
= 0mA, V
= 0, V
= V or V
= V ,
●
60
µA
OUT
EN1
EN2
IN
EN1
IN
One Output Enabled
V
= 0, 2.7V ≤ V ≤ 5.5V
EN2
IN
Shutdown Current
V
= 0V, V = 0V, 2.7V ≤ V ≤ 5.5V
●
●
●
●
●
0.01
0.8
1
µA
V
M0
M1
IN
V
, V
Feedback Voltage
I
= 0mA, 2.7V ≤ V ≤ 5.5V
0.78
250
250
–50
0.82
FB1 FB2
OUT
IN
I
I
I
Output Current
V
V
V
= V
= V
mA
mA
nA
OUT1
OUT2
FB
EN1
EN2
FB1
IN
IN
Output Current
FB1, FB2 Input Current
Output Ripple (OUT1 or OUT2)
Spread Spectrum Frequency Range
= V = 0.85V
50
FB2
V
I
= 250mA
10
mV
P-P
RIPPLE
OUT
f
f
Switching Frequency
Switching Frequency
●
●
0.8
1.2
1.0
1.6
MHz
MHz
MIN
2.0
MAX
V
V
EN1, EN2 Input High Voltage
EN1, EN2 Input Low Voltage
EN1, EN2 Input High Current
EN1, EN2 Input Low Current
Turn On Time
2.7V ≤ V ≤ 5.5V
●
●
●
●
0.8
0.8
V
V
IH
IL
IN
2.7V ≤ V ≤ 5.5V
0.4
1
IN
I
I
t
EN1 = V , EN2 = V
IN
–1
–1
µA
IH
IN
EN1 = 0V, EN2 = 0V
= 3Ω
1
µA
IL
R
0.8
0.08
0.2
1
ms
ON
OUT
OUT1, OUT2 Load Regulation (Referred to FB pin)
Line Regulation
mV/mA
%/V
Ω
0 ≤ I
≤ 250mA or 0 ≤ I
≤ 250mA
OUT2
OUT1
R
Open Loop Output Impedance,
(OUT1 or OUT2)
V
= 3.0V, I
= 200mA, V = 0.74V (Note 5)
●
1.4
OL
IN
OUT
FB
3252f
2
LTC3252
ELECTRICAL CHARACTERISTICS
Note 1: Absolute Maximum Ratings are those values beyond which the life
Note 4: Minimum operating voltage required for regulation is:
> 2 • (V + R • I
of a device may be impaired.
V
)
OL OUT
IN
OUT(MIN)
Note 2: The LTC3252EDE is guaranteed to meet specified performance
from 0°C to 70°C. Specifications over the –40°C and 85°C operating
temperature range are assured by design characterization and correlation
with statistical process control.
Note 5: Output not in regulation; R = (V /2 – V )/I .
OUT OUT
OL
IN
Note 6: This IC includes overtemperature protection that is intended to
protect the device during momentary overload conditions. Junction
temperature will exceed 125°C when overtemperature protection is active.
Continuous operation above the specified maximum operating junction
temperature may impair device reliability.
Note 3: Based on long-term current density limitations.
U W
TYPICAL PERFOR A CE CHARACTERISTICS
No Load Supply Current vs Supply
Voltage (One Output Enabled)
No Load Supply Current vs Supply
Voltage (Both Outputs Enabled)
FB Voltage vs Load Current
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
0.82
0.81
0.80
0.79
0.78
0.77
0.76
V
IN
= 3.6V
25°C
85°C
25°C
85°C
25°C
–40°C
–40°C
–45°C
85°C
2.7
3.7
4.2
(V)
4.7
5.2
2.7
3.7
4.2
(V)
4.7
5.2
0
50
100
I
OUT
150
(mA)
200
250
3.2
3.2
V
V
IN
IN
3252 G01
3252 G02
3252 G03
EN1/EN2 Input Threshold Voltage
vs Supply Voltage
1.5V Output Voltage vs Supply
Voltage
1.5V Output Efficiency vs Output
Current
1.2
1.1
1.0
0.9
0.8
0.7
0.6
0.5
0.4
1.60
1.58
1.56
1.54
1.52
1.50
1.48
1.46
1.44
1.42
1.40
100
80
60
40
20
0
T
= 25°C
A
T
= 25°C
A
25°C
I
= 50mA
OUT
–40°C
I
= 0mA
OUT
V
V
V
V
V
= 3.1V
= 3.3V
= 3.6V
= 4V
IN
IN
IN
IN
IN
I
= 250mA
85°C
OUT
= 5V
2.7
3.7
4.2
(V)
4.7
5.2
3
3.5
4
4.5
5
5.5
0.1
1
10
(mA)
100
1000
3.2
V
V
IN
(V)
I
OUT
IN
3252 G04
3252 G05
3252 G06
3252f
3
LTC3252
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Oscillator Max/Min Frequency vs
Supply Voltage
1.2V Output Voltage vs Supply
Voltage
1.2V Efficiency vs Load Current
2.0
1.9
1.8
1.7
1.6
1.5
1.4
1.3
1.2
1.1
1.0
0.9
0.8
1.30
1.28
1.26
1.24
1.22
1.20
1.18
1.16
1.14
1.12
1.10
100
80
60
40
20
0
T
= 25°C
A
T
= 25°C
A
25°C MAX
–40°C MAX
I
I
I
= 0mA
OUT
OUT
OUT
85°C MAX
= 50mA
= 250mA
V
V
V
V
= 2.8V
= 3.1V
= 3.5V
= 4.5V
IN
IN
IN
IN
25°C MIN
–40°C MIN
85°C MIN
2.7
3.7
4.2
(V)
4.7
5.2
2.7
3.7
4.2
(V)
4.7
5.2
0.1
1
10
(mA)
100
1000
3.2
3.2
V
V
IN
I
OUT
IN
3252 G07
3252 G08
3252 G09
Output Current Transient
Response
Line Transient Response
4.5V
3.5V
250mA
20mA
V
IN
I
OUT
V
OUT
20mV/DIV
AC
V
OUT
10mV/DIV
AC
3252 G12
3252 G11
V
I
= 1.5V
= 150mA
V
V
= 3.6V
OUT
OUT
IN
OUT
= 1.5V
U
U
U
PI FU CTIO S
FB1 (Pin 1): Feedback Input Pin 1. An output divider C1+ (Pin 4): Flying Capacitor 1 Positive Terminal (C1).
should be connected from OUT1 to FB1 to program the
output voltage.
OUT1 (Pin 5): Regulated Output Voltage 1. OUT1 is
disconnected from VIN when in shutdown. Bypass OUT1
EN1 (Pin 2): Input Enable Pin 1. When EN1 is high, OUT1 with a low ESR ceramic capacitor to GND (CO1). See
is enabled. When EN1 is low OUT1 is shut down.
Output Capacitor Selection section for size requirements.
VIN (Pin 3): Input Supply Voltage. Operating VIN may be C1– (Pin 6): Flying Capacitor 1 Negative Terminal (C1).
between 2.7V and 5.5V. Bypass VIN with a ≥ 4.7µF (1µF
min) low ESR ceramic capacitor to GND (CIN).
performance.
GND (Pin 7): Ground. Connect to a ground plane for best
3252f
4
LTC3252
U
U
U
PI FU CTIO S
C2– (Pin 8): Flying Capacitor 2 Negative Terminal (C2).
EN2 (Pin 11): Input Enable Pin 2. When EN2 is high, OUT2
is enabled. When EN2 is low OUT2 is shut down.
OUT2 (Pin 9): Regulated Output Voltage 2. OUT2 is
disconnected from VIN when in shutdown. Bypass OUT2
with a low ESR ceramic capacitor to GND (CO2). See
Output Capacitor Selection section for size requirements.
FB2 (Pin 12): Feedback Input Pin 2. An output divider
should be connected from OUT2 to FB2 to program the
output voltage.
C2+ (Pin 10): Flying Capacitor 2 Positive Terminal (C2).
W
W
SI PLIFIED BLOCK DIGRAM
EN1
2
EN2
11
SWITCH
CONTROL
SPREAD SPECTRUM
OSCILLATOR
OVERTEMPERATURE
CHARGE
PUMP 1
V
IN
3
+
4
5
6
C1
OUT1
–
C1
1
FB1
–
+
BURST
DETECT
CIRCUIT
CHARGE
PUMP 2
+
10 C2
9
8
OUT2
–
C2
12 FB2
–
+
7
GND
3252 SBD
3252f
5
LTC3252
U
OPERATIO
(Refer to Simplified Block Diagram)
TheLTC3252hastwoswitchedcapacitorchargepumpsto
step down VIN to two regulated output voltages. The two
charge pumps operate 180° out of phase to reduce input
ripple. Regulation is achieved by sensing each output
voltage through an external resistor divider and modulat-
ing the charge pump output current based on the error
signal. A 2-phase nonoverlapping clock activates the two
chargepumpsrunningthemoutofphasefromeachother.
On the first phase of the clock current is transferred from
VIN,throughtheexternalflyingcapacitor1,toOUT1viathe
switches of charge pump 1. Not only is current being
delivered to OUT1 on the first phase, but the flying capaci-
tor is also being charged up. On the second phase of the
clock, flying capacitor 1 is connected from OUT1 to
ground, transferring the charge stored during the first
phase of the clock to OUT1 via the switches of charge
pump 1. Charge pump 2 operates in the same manner to
supply current to OUT2, but with the phases of the clock
reversed relative to charge pump 1. Using this method of
switching, only half of the output current for each output
is delivered from VIN, thus achieving a 50% increase in
efficiency over a conventional LDO. A spread spectrum
oscillator, which utilizes random switching frequencies
between 1MHz and 1.6MHz, sets the rate of charging and
discharging of the flying capacitors. This architecture
achievesextremelylowoutputnoise.Inputnoiseissignifi-
cantly reduced compared to conventional charge pumps.
Theoutputsalsohavealowcurrentburstmodetoimprove
efficiency even at light loads.
Short-Circuit/Thermal Protection
The LTC3252 has built-in short-circuit current limiting as
well as over temperature protection. During short-circuit
conditions, internal circuitry automatically limits each
output to approximately 500mA of current. If fault condi-
tions (such as shorted outputs) cause excessive self
heating on chip such that the junction temperature ex-
ceeds approximately 160°C, the thermal shutdown cir-
cuitry will disable the charge pumps. The IC resumes
operation once the junction temperature drops back to
approximately155°C. TheLTC3252willcycleinandoutof
thermal shutdown without latchup or damage until the
overstress condition is removed. Long term overstress
(IOUT1 or IOUT2 > 400mA, and/or TJ > 125°C) should be
avoided as it can degrade the performance or shorten the
life of the part.
Soft-Start
To prevent excessive current flow at VIN during start-up,
the LTC3252 has built-in soft-start circuitry on each out-
put. When an output is enabled, the soft-start circuitry
increases the amount of current available from the output
linearly over a period of approximately 500µs. The soft-
start circuitry is disabled shortly after the output achieves
regulation.
Spread Spectrum Operation
Switchingregulatorscanbeparticularlytroublesomewhere
electromagnetic interference (EMI) is concerned. Switch-
ingregulatorsoperateonacycle-by-cyclebasistotransfer
power to an output. In most cases, the frequency of
operation is either fixed or is a constant based on the
output load. This method of conversion creates large
componentsofnoiseatthefrequencyofoperation(funda-
mental) and multiples of the operating frequency (har-
monics).
In shutdown mode all circuitry is turned off and the
LTC3252 draws only leakage current from the VIN supply.
Furthermore, OUT1 and OUT2 are disconnected from VIN.
The EN1 and EN2 pins are CMOS inputs with threshold
voltages of approximately 0.8V to allow regulator control
with low voltage logic levels. The LTC3252 is in shutdown
when a logic low is applied to both enable pins. Since the
mode pins are high impedance CMOS inputs, they should
neverbeallowedtofloat. Alwaysdrivetheenablepinswith
valid logic levels.
3252f
6
LTC3252
U
OPERATIO
(Refer to Simplified Block Diagram)
Unlikeconventionalbuckconverters,theLTC3252’sinter-
nal oscillator is designed to produce a clock pulse whose
period is random on a cycle-by-cycle basis but fixed
between1MHzand1.6MHz.Thishasthebenefitofspread-
ing the switching noise over a range of frequencies, thus
significantly reducing the peak noise. Figures 1 and 2
show how the spread spectrum feature of the LTC3252
significantly reduces the peak harmonic noise and virtu-
ally elliminates harmonics compared to a conventional
buck converter.
threshold (30mA typ). When this occurs, the part shuts
down the internal oscillator and goes into a low current
operating state. The LTC3252 will remain in the low
current operating state until either output has dropped
enough to require another burst of current. The LTC3252
resumes continuous operation when the load on one or
both outputs exceeds the internally set threshold. Unlike
traditional charge pumps where the burst current is highly
dependant on many factors (i.e., supply, switch strength,
capacitor selection, etc.), the LTC3252’s burst current is
set by the burst threshold and hysteresis. This means that
the output ripple voltage in Burst Mode operation is
relatively consistent and is typically about 12mV with a
4.7µFoutputcapacitorona1.5Voutput.Theripplevoltage
amplitude is a direct function of the output capacitor size.
BurstModeoperationripplevoltagedoesincreaseslightly
at lower output voltages due to the increase in loop gain.
Userscancounteractoutputvoltagerippleincreasethrough
the use of a slightly larger output capacitor. See Recom-
mended Output Capacitance guidelines of Figure 3.
Spread spectrum operation is always enabled but is most
effective when the LTC3252’s outputs are out of Burst
Mode operation and the oscillator is running continuously
(see the Low Current Burst Mode Operation section).
Low Current Burst Mode Operation
Toimproveefficiencyatlowoutputcurrents,aBurstMode
operation function is included in the LTC3252. An output
current sense is used to detect when the required output
current of both outputs drop below an internally set
Figure 1. Conventional Buck Input Noise
Figure 2. LTC3252 Input Noise
3252f
7
LTC3252
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OPERATIO
(Refer to Simplified Block Diagram)
Output Capacitor Selection
tance required for good transient response (see the Ce-
ramic Capacitor Selection Guidelines section).
The style and value of capacitors used with the LTC3252
determineseveralimportantparameterssuchasregulator
control loop stability, output ripple and charge pump
strength.
Likewise excessive ESR on the output capacitor will tend
to degrade the loop stability of the LTC3252. The closed
loop output impedance of the LTC3252 is approximately:
The switching nature of the LTC3252 minimizes output
noise significantly but not completely. What small ripple
that exists at an output is controlled by the value of output
capacitordirectly. Increasingthesizeoftheoutputcapaci-
tor will proportionately reduce the output ripple. The ESR
(equivalentseriesresistance)oftheoutputcapacitorplays
the dominant role in output noise. When the LTC3252
switches between clock phases there is a period where all
switches are turned off. This “blanking period” shows up
asaspikeattheoutputandisadirectfunctionoftheoutput
current times the ESR value. To reduce output noise and
ripple, it is suggested that a low ESR (<0.08Ω) ceramic
capacitor be used for the output capacitor. Tantalum and
aluminum capacitors are not recommended because of
their high ESR.
VOUT
RO = 0.08Ω •
0.8V
For example, with the output programmed to 1.5V, the RO
is 0.15Ω, which produces a 38mV output change for a
250mA load current step. For stability and good load
transient response it is important for the output capacitor
to have 0.1Ω or less of ESR. Ceramic capacitors typically
have exceptional ESR and combined with a tight board
layout should yield excellent stability and load transient
performance.
Furtheroutputnoisereductioncanbeachievedbyfiltering
the LTC3252 outputs through a very small series inductor
as shown in Figure 4. A 10nH inductor will reject the fast
output transients caused by the blanking period, thereby
presenting a nearly constant output voltage. For economy
the 10nH inductor can be fabricated on the PC board with
about 1cm (0.4") of PC board trace.
Both the style and value of the output capacitors can
significantly affect the stability of the LTC3252. As shown
in the Simplified Block Diagram, the LTC3252 uses a
control loop to adjust the strength of each charge pump to
match the current required at the output. The error signal
of each loop is stored directly on each output capacitor.
Thus the output capacitors also serve to form the domi-
nant pole in each control loop. Figure 3 is a graph of the
recommended output capacitance, and minimum capaci-
10nH
V
OUT
LTC3252
GND
OUT
4.7µF
0.47µF
3252 F04
Figure 4. 10nH Inductor Used for
Additional Output Noise Reduction
8
VIN Capacitor Selection
RECOMMENDED
CAPACITANCE
7
6
5
4
3
2
Thelownoise,dualphasearchitectureusedbytheLTC3252
makes input noise filtering much less demanding than
conventional charge pump regulators. The LTC3252 input
current will transition between IOUT1/2 and IOUT2/2 for
each half cycle of the oscillator. The blanking period
described in the VOUT section also effects the input. For
this reason it is recommended that a low ESR 4.7µF (1µF
min) or greater ceramic capacitor be used for CIN (see the
Ceramic Capacitor Selection Guidelines section). Alumi-
num and tantalum capacitors can be used but are not
MINIMUM
CAPACITANCE
0.9
1
1.1 1.2 1.3 1.4 1.5 1.6
V
(V)
OUT
3252 F03
Figure 3. Output Capacitance vs Output Voltage
recommended because of their high ESR.
3252f
8
LTC3252
U
OPERATIO
(Refer to Simplified Block Diagram)
Further input noise reduction can be achieved by filtering
the input through a very small series inductor as shown in
Figure 5. A 10nH inductor will reject the fast input tran-
sients caused by the blanking period, thereby presenting
anearlyconstantloadtotheinputsupply.Foreconomythe
10nH inductor can be fabricated on the PC board with
about 1cm (0.4") of PC board trace.
discussing the specified capacitance value. For example,
over rated voltage and temperature conditions, a 4.7µF,
10V, Y5V ceramic capacitor in a 0805 case may not
provide any more capacitance than a 1µF, 10V, X7R
available in the same 0805 case. In fact, over bias and
temperature range, the 1µF, 10V, X7R will provide more
capacitance than the 4.7µF, 10V, Y5V. The capacitor
manufacturer’s data sheet should be consulted to deter-
mine what value of capacitor is needed to ensure mini-
mum capacitance values are met over operating
temperature and bias voltage.
10nH
V
IN
V
IN
SUPPLY
4.7µF
LTC3252
GND
Below is a list of ceramic capacitor manufacturers and
how to contact them:
3252 F05
Figure 5. 10nH Inductor Used for
Additional Input Noise Reduction
AVX
Kemet
www.avxcorp.com
www.kemet.com
www.murata.com
www.t-yuden.com
www.vishay.com
Flying Capacitor Selection
Murata
Taiyo Yuden
Vishay
Warning: A polarized capacitor such as tantalum or alumi-
num should never be used for the flying capacitors since
their voltages can reverse upon start-up of the LTC3252.
Ceramic capacitors should always be used for the flying
capacitors.
Layout Considerations
Duetothehighswitchingfrequencyandtransientcurrents
produced by the LTC3252 careful board layout is neces-
sary for optimal performance. A true ground plane and
short connections to all capacitors will improve perfor-
mance and ensure proper regulation under all conditions.
Figure 7 shows the suggested layout configuration. Note
the exposed paddle of the package is ground (GND) and
must be soldered to the PCB ground.
The flying capacitors control the strength of the charge
pump. In order to achieve the rated output current it is
necessary for the flying capacitor to have at least 0.4µF of
capacitance over operating temperature with a 2V bias
(seetheCeramicCapacitorSelectionGuidelines).If100mA
or less of current is required from an output then its asso-
ciatedflyingcapacitorminimumcanbereducedto0.15µF.
Ceramic Capacitor Selection Guidelines
The flying capacitor pins C1+, C1–, C2+ and C2– will have
very high edge rate wave forms. The large dv/dt on these
pins can couple energy capacitively to adjacent printed
circuit board runs. Magnetic fields can also be generated
if the flying capacitors are not close to the LTC3252 (i.e.,
the loop area is large). To decouple capacitive energy
transfer, a Faraday shield may be used. This is a grounded
PC trace between the sensitive node and the LTC3252
pins. For a high quality AC ground, it should be returned to
a solid ground plane that extends all the way to the
LTC3252. Keep the FB traces away from or shielded from
the flying capacitor traces or degraded performance could
result.
Capacitors of different materials lose their capacitance
withhighertemperatureandvoltageatdifferentrates. For
example, a ceramic capacitor made of X7R material will
retainmostofitscapacitancefrom–40°Cto85°Cwhereas
a Z5U or Y5V style capacitor will lose considerable
capacitance over that range (60% to 80% loss typical).
Z5U and Y5V capacitors may also have a very strong
voltage coefficient causing them to lose an additional
60% or more of their capacitance when the rated voltage
is applied. Therefore, when comparing different capaci-
tors it is often more appropriate to compare the amount
of achievable capacitance for a given case size rather than
3252f
9
LTC3252
U
OPERATIO
(Refer to Simplified Block Diagram)
Thermal Management
IOUT1 = 150mA and OUT1 regulating at 1.5V the measured
efficiency is 80.6% which is in close agreement with the
theoretical 83.3% calculation.
To reduce the maximum junction temperature, a good
thermal connection to the PC board is recommended.
Soldering the exposed paddle of the IC to the PCB and
maintaining a solid ground plane under the device on one
or more layers of the PC board, the thermal resistance of
the package can be as small as 40°C/W. By applying the
suggested thermal management techniques the IC junc-
tion temperature should never exceed 125°C even under
worst case operating conditions.
Programming the LTC3252 Output Voltages (FB1 and
FB2 Pin)
EachoutputoftheLTC3252isprogrammedtoanarbitrary
voltageviaanexternalresistivedivider.Figure7showsthe
required voltage divider connection. The voltage divider
ratio is given by the expression:
RA OUT
RB 0.8V
Power Efficiency
=
−1
The power efficiency (η) of the LTC3252 is approximately
50% higher than a conventional linear regulator. This
occurs because the input current for a 2-to-1 step-down
charge pump is approximately half the output current. For
an ideal 2-to-1 step-down charge pump the power effi-
ciency is given by:
Typical values for total voltage divider resistance can
range from several kΩs up to 1MΩ.
The user may want to consider load regulation when
setting the desired output voltage. The closed loop output
impedance of the LTC3252 is approximately:
POUT
P
IN
VOUT •IOUT 2VOUT
OUT
RO = 0.08Ω •
0.8V
η ≡
=
=
1
V
IN
V • IOUT
IN
2
For a 1.5V output, RO is 0.15Ω, which produces a 38mV
output change for a 250mA load current step. Thus, the
user may want to target an unloaded output voltage
slightly higher than desired to compensate for the output
load conditions. The output may be programmed for
regulation voltages of 0.9V to 1.6V.
TheswitchinglossesandquiescentcurrentoftheLTC3252
are designed to minimize efficiency loss over the entire
output current range, causing only a couple % error from
the theoretical efficiency. For example with VIN = 3.6V,
R
R
R '
B
R '
A
A
B
Since the LTC3252 employs a 2-to-1 charge pump archi-
tecture, it is not possible to achieve output voltages
greater than half the available input voltage. The minimum
VIN supply required for regulation can be determined by
the following equation:
1
EN2
EN1
V
IN
LTC3252
C2
C
IN
VIN (MIN) ≤ 2 • (VOUT (MIN) + IOUT • ROL)
C1
OUT1
OUT1
OUT2
FB2
OUT2
R
OUT1
0.8V
R ' OUT2
A
A
B
R
R
R '
A
A
LTC3252
=
– 1
=
– 1
OUT1
OUT2
R
R '
B
0.8V
C
C
O2
O1
C
O1
FB1
C
O2
R '
B
B
GND
GND
GND
(CONNECT DIRECTLY TO GROUND PLANE)
3252 F06
3252 F07
Figure 6. Suggested Layout for the LTC3252
Figure 7. Programming the LTC3252
3252f
10
LTC3252
U
TYPICAL APPLICATIO
Li-Ion to 1.5V/1.2V Outputs
3
2
5
11
9
V
EN2
OFF ON
IN
OUT2
1.5V
EN1
OUT2
OFF ON
1µF
OUT1
1.2V
250mA
10
+
OUT1
C2
470k
510k
1µF
LTC3252
250mA
4
6
1
8
+
–
261k
C1
C2
4.7µF
12
7
–
C1
FB2
4.7µF
FB1
GND
Li-ION
510k
4.7µF
3252 TA02
U
PACKAGE DESCRIPTIO
DE/UE Package
12-Lead Plastic DFN (4mm × 3mm)
(Reference LTC DWG # 05-08-1695)
0.58 ±0.05
3.40 ±0.05
2.24 ±0.05 (2 SIDES)
1.70 ±0.05
PACKAGE OUTLINE
0.25 ± 0.05
0.50
BSC
3.30 ±0.05
(2 SIDES)
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
0.38 ± 0.10
4.00 ±0.10
(2 SIDES)
R = 0.115
TYP
7
12
R = 0.20
TYP
3.00 ±0.10 1.70 ± 0.10
(2 SIDES)
(2 SIDES)
PIN 1
TOP MARK
PIN 1
NOTCH
(UE12/DE12) DFN 0802
6
0.25 ± 0.05
1
0.75 ±0.05
0.200 REF
0.50
BSC
3.30 ±0.10
(2 SIDES)
0.00 – 0.05
BOTTOM VIEW—EXPOSED PAD
NOTE:
1. DRAWING PROPOSED TO BE A VARIATION OF VERSION
(WGED) IN JEDEC PACKAGE OUTLINE M0-229
2. ALL DIMENSIONS ARE IN MILLIMETERS
3. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
4. EXPOSED PAD SHALL BE SOLDER PLATED
3252f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
11
LTC3252
U
TYPICAL APPLICATIO S
Fixed 3.3VIN to 1.5VOUT at 300mA
3-Cell NiMH with Digitally Selectable 1.2V/1.5V Output
OFF ON
3
2
5
11
9
3
2
5
11
9
V
EN2
EN2
IN
V
EN2
3.3V
IN
I
OUT
OUT
250mA
EN1
EN1
OUT2
4.7µF
1µF
1.5V
EN1
OUT2
10
+
300mA
10
OUT1
C2
261k
+
OUT1
C2
470k
510k
1µF
LTC3252
4
6
1
8
4.7µF
+
–
1µF
LTC3252
4
6
1
8
C1
C2
+
–
C1
C2
1µF
4.7µF
3-CELL
NiMH
12
7
–
10µF
C1
FB2
12
7
–
C1
FB2
FB1
GND
EN1 EN2 OUT
FB1
GND
412k
100k
OFF
OFF
ON
OFF
ON
OFF 1.5V
0V
1.2V
3252 TA03
ON
ON
1.5V
3252 TA04
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
LTC1514
50mA, 650kHz, Step-Up/Down Charge Pump
with Low Battery Comparator
V
= 2.7V to 10V, V
= 10µA, S8
= 3V or 5V, Regulated Output, I = 60µA,
Q
IN
OUT
I
SHDN
LTC1515
50mA, 650kHz, Step-Up/Down Charge Pump
with Power-On Reset
V
= 2.7V to 10V, V
= <1µA, S8
= 3.3V or 5V, Regulated Output, I = 60µA,
Q
IN
OUT
I
SHDN
LT1776
500mA (I ), 200kHz, High Efficiency
Step-Down DC/DC Converter
90% Efficiency, V = 7.4V to 40V, V Min = 1.24V,
OUT
OUT
IN
I = 3.2mA, I
= 30µA, N8, S8
Q
SHDN
LTC1911-1.5
LTC1911-1.8
LTC3250-1.5
LTC3251
250mA, 1.5MHz, High Efficiency
Step-Down Charge Pump
75% Efficiency, V = 2.7V to 5.5V, V
= 1.5V, Regulated Output,
= 1.8V, Regulated Output,
= 1.5V, Regulated Output,
IN
OUT
OUT
OUT
I = 180µA, I
= 10µA, MS8
Q
SHDN
250mA, 1.5MHz, High Efficiency
Step-Down Charge Pump
75% Efficiency, V = 2.7V to 5.5V, V
IN
I = 180µA, I
= 10µA, MS8
Q
SHDN
250mA, 1.5MHz, High Efficiency
Step-Down Charge Pump
85% Efficiency, V = 3.1V to 5.5V, V
IN
I = 35µA, I
= <1µA, ThinSOT
Q
SHDN
500mA, Spread Spectrum, High Efficiency
Step-Down Charge Pump
Up to 85% Efficiency, V = 2.7V to 5.5V, V
= 0.9V to 1.6V,
IN
OUT
I = 8µA, I
Q
= <1µA, MS10
SHDN
LTC3404
600mA (I ), 1.4MHz, Synchronous
Step-Down DC/DC Converter
95% Efficiency, V = 2.7V to 6V, V
Min = 0.8V,
Min = 0.8V,
OUT
IN
OUT
OUT
I = 10µA, I
= <1µA, MS8
Q
SHDN
LTC3405/LTC3405A 300mA (I ), 1.5MHz, Synchronous
95% Efficiency, V = 2.7V to 6V, V
IN
OUT
Step-Down DC/DC Converter
I = 20µA, I
= <1µA, ThinSOT
Q
SHDN
LTC3406/LTC3406B 600mA (I ), 1.5MHz, Synchronous
95% Efficiency, V = 2.5V to 5.5V, V
Min = 0.6V,
Min = 0.8V,
Min = 0.8V,
Min = 2.5V,
OUT
IN
OUT
OUT
OUT
OUT
Step-Down DC/DC Converter
I = 20µA, I
= <1µA, ThinSOT
Q
SHDN
LTC3411
LTC3412
LTC3440
1.25A (I ), 4MHz, Synchronous Step-Down 95% Efficiency, V = 2.5V to 5.5V, V
DC/DC Converter
OUT
IN
I = 60µA, I
= <1µA, MS10
Q
SHDN
2.5A (I ), 4MHz, Synchronous Step-Down
95% Efficiency, V = 2.5V to 5.5V, V
IN
OUT
DC/DC Converter
I = 60µA, I
= <1µA, TSSOP-16E
Q
SHDN
600mA (I ), 2MHz, Synchronous
95% Efficiency, V = 2.5V to 5.5V, V
IN
OUT
Buck-Boost DC/DC Converter
I = <25µA, I
= 1µA, MS10
Q
SHDN
3252f
LT/TP 0503 1K • PRINTED IN USA
12 LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
●
●
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
LINEAR TECHNOLOGY CORPORATION 2003
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