LTC6101CCS5 [Linear]
High Voltage, High-Side Current Sense Amplifier in SOT-23; 高电压,高边电流检测放大器采用SOT -23型号: | LTC6101CCS5 |
厂家: | Linear |
描述: | High Voltage, High-Side Current Sense Amplifier in SOT-23 |
文件: | 总20页 (文件大小:330K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LTC6101/LTC6101HV
High Voltage,
High-Side Current Sense
Amplifier in SOT-23
U
FEATURES
DESCRIPTIO
TheLTC®6101/LTC6101HVareversatile, highvoltage, high
side current sense amplifiers. Design flexibility is provided
by the excellent device characteristics; 300µV Max offset
and only 375µA (typical at 60V) of current consumption.
The LTC6101 operates on supplies from 4V to 60V and
LTC6101HV operates on supplies from 5V to 100V.
■
Supply Range:
5V to 100V, 105V Absolute Maximum (LTC6101HV)
4V to 60V, 70V Absolute Maximum (LTC6101)
Low Offset Voltage: 300µV Max
Fast Response: 1µs Response Time (0V to 2.5V on
a 5V Output Step)
■
■
■
■
■
Gain Configurable with 2 Resistors
Low Input Bias Current: 170nA Max
PSRR: 110dB Min
The LTC6101 monitors current via the voltage across an
external sense resistor (shunt resistor). Internal circuitry
convertsinputvoltagetooutputcurrent,allowingforasmall
sense signal on a high common mode voltage to be trans-
lated into a ground referenced signal. Low DC offset allows
the use of a small shunt resistor and large gain-setting
resistors. As a result, power loss in the shunt is reduced.
4V to 60V (LTC6101)
5V to 100V (LTC6101HV)
■
■
■
Output Current: 1mA Max
Low Supply Current: 250µA, VS = 14V
Low Profile (1mm) SOT-23 (ThinSOTTM) Package
The wide operating supply range and high accuracy make
the LTC6101 ideal for a large array of applications from
automotive to industrial and power management. A maxi-
mum input sense voltage of 500mV allows a wide range of
currents to be monitored. The fast response makes the
LTC6101 the perfect choice for load current warnings and
shutoff protection control. With very low supply current,
the LTC6101 is suitable for power sensitive applications.
U
APPLICATIO S
■
Current Shunt Measurement
Battery Monitoring
■
■
Remote Sensing
■
Power Management
, LTC and LT are registered trademarks of Linear Technology Corporation.
ThinSOT is a trademark of Linear Technology Corporation.
All other trademarks are the property of their respective owners.
The LTC6101 is available in 5-lead SOT-23 and 8-lead
MSOP packages.
U
TYPICAL APPLICATIO
16-Bit Resolution Unidirectional Output into LTC2433 ADC
Step Response
I
V
LOAD
SENSE
+
–
–
V
SENSE
R
IN
100Ω
5V TO 105V
∆V
SENSE
– = 100mV
4
2
3
5
5.5V
5V
L
O
A
D
+
–
T
= 25°C
1µF
5V
A
V
+ = 12V
R
R
V
= 100
= 5k
SENSE
IN
OUT
V
OUT
+ = V+
V
OUT
1
LTC6101HV
I
= 100µA
OUT
LTC2433-1
TO µP
R
OUT
4.99k
0.5V
0V
I
= 0
OUT
500ns/DIV
6101 TA01
6101 TA01b
R
R
OUT
V
OUT
=
• V
SENSE
= 49.9V
SENSE
IN
6101fa
1
LTC6101/LTC6101HV
W W U W
ABSOLUTE AXI U RATI GS
(Note 1)
Total Supply Voltage (V+ to V–)
LTC6101I/LTC6101HVI ...................... –40°C to 85°C
LTC6101H/LTC6101HVH ................. –40°C to 125°C
Specified Temperature Range (Note 2)
LTC6101C/LTC6101HVC ......................... 0°C to 70°C
LTC6101I/LTC6101HVI ...................... –40°C to 85°C
LTC6101H/LTC6101HVH ................. –40°C to 125°C
Storage Temperature Range ................ –65°C to 150°C
Lead Temperature (Soldering, 10 sec)................. 300°C
LTC6101............................................................. 70V
LTC6101HV ...................................................... 105V
Minimum Input Voltage (–IN Pin) ................... (V+ – 4V)
Maximum Output Voltage (Out Pin)........................... 9V
Input Current ..................................................... ±10mA
Output Short-Circuit Duration (to V–) ............. Indefinite
Operating Temperature Range
LTC6101C/LTC6101HVC .................... –40°C to 85°C
U
W
U
PACKAGE/ORDER I FOR ATIO
TOP VIEW
+
TOP VIEW
–IN
NC
NC
1
2
3
4
8 +IN
7 V
OUT 1
–
5 V
+
V
2
6 NC
–
–IN 3
4 +IN
5 V
OUT
MS8 PACKAGE
8-LEAD PLASTIC MSOP
TJMAX = 150°C, θJA = 300°C/ W
S5 PACKAGE
5-LEAD PLASTIC TSOT-23
TJMAX = 150°C, θJA = 250°C/ W
ORDER PART NUMBER
MS8 PART MARKING*
ORDER PART NUMBER
S5 PART MARKING*
LTC6101ACMS8
LTC6101AIMS8
LTC6101AHMS8
LTC6101HVACMS8
LTC6101HVAIMS8
LTC6101HVAHMS8
LTBSB
LTBSB
LTBSB
LTBSX
LTBSX
LTBSX
LTC6101BCS5
LTC6101CCS5
LTC6101BIS5
LTBND
LTBND
LTBND
LTBND
LTBND
LTBND
LTBSZ
LTBSZ
LTBSZ
LTBSZ
LTBSZ
LTBSZ
LTC6101CIS5
LTC6101BHS5
LTC6101CHS5
LTC6101HVBCS5
LTC6101HVCCS5
LTC6101HVBIS5
LTC6101HVCIS5
LTC6101HVBHS5
LTC6101HVCHS5
Order Options Tape and Reel: Add #TR
Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF
Lead Free Part Marketing: http://www.linear.com/leadfree/
Consult LTC Marketing for parts specified with wider operating temperature ranges.
*The temperature grades and parametric grades are identified by a label on the shipping container.
6101fa
2
LTC6101/LTC6101HV
ELECTRICAL CHARACTERISTICS
(LTC6101) The
●
denotes the specifications which apply over the full
+
+
operating temperature range, otherwise specifications are at T = 25°C, R = 100Ω, R
= 10k, V
= V (see Figure 1 for
SENSE
A
IN
OUT
details), 4V ≤ V ≤ 60V unless otherwise noted.
S
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
V
Supply Voltage Range
Input Offset Voltage
●
4
60
V
S
V
V
V
= 5mV, Gain = 100, LTC6101A
= 5mV, Gain = 100, LTC6101AC, LTC6101AI
= 5mV, Gain = 100, LTC6101AH
±85
±300
±450
±535
µV
µV
µV
OS
SENSE
SENSE
SENSE
●
●
V
= 5mV, Gain = 100, LTC6101B
= 5mV, Gain = 100, LTC6101C
±150
±400
±450
±810
µV
µV
SENSE
●
V
±1500
±2500
µV
µV
SENSE
●
∆V /∆T
Input Offset Voltage Drift
Input Bias Current
V
V
V
= 5mV, LTC6101A
= 5mV, LTC6101B
= 5mV, LTC6101C
●
●
●
±1
±3
µV/°C
µV/°C
µV/°C
OS
SENSE
SENSE
SENSE
±10
I
I
R
= 1M
100
170
245
nA
nA
B
IN
●
●
●
Input Offset Current
R
= 1M
±2
±15
nA
OS
IN
V
Input Sense Voltage Full Scale
Power Supply Rejection Ratio
V
within Specification, R = 1k
500
mV
SENSE(MAX)
OS
IN
PSRR
V = 6V to 60V, V
= 5mV, Gain = 100
= 5mV, Gain = 100
= 88mV
118
115
140
133
dB
dB
S
SENSE
●
●
V = 4V to 60V, V
110
105
dB
dB
S
SENSE
V
V
Maximum Output Voltage
Minimum Output Voltage
12V ≤ V ≤ 60V, V
V = 6V, V
V = 4V, V
●
●
●
8
3
1
V
V
V
OUT
S
SENSE
= 330mV, R = 1k, R
= 10k
= 2k
S
SENSE
IN
OUT
OUT
= 550mV, R = 1k, R
S
SENSE
IN
V
V
V
= 0V, Gain = 100, LTC6101A
= 0V, Gain = 100, LTC6101AC, LTC6101AI
= 0V, Gain = 100, LTC6101AH
0
30
45
53.5
mV
mV
mV
OUT (0)
SENSE
SENSE
SENSE
●
●
V
= 0V, Gain = 100, LTC6101B
= 0V, Gain = 100, LTC6101C
0
0
45
81
mV
mV
SENSE
●
●
V
150
250
mV
mV
SENSE
I
t
Maximum Output Current
6V ≤ V ≤ 60V, R
= 2k, V = 110mV, Gain = 20
SENSE
●
●
1
0.5
mA
mA
OUT
r
S
OUT
V = 4V, V
= 550mV, Gain = 2, R = 2k
S
SENSE
OUT
Input Step Response
(to 2.5V on a 5V Output Step)
∆V
S
= 100mV Transient, 6V ≤ V ≤ 60V, Gain = 50
1
1.5
µs
µs
SENSE
V = 4V
S
BW
Signal Bandwidth
Supply Current
I
I
= 200µA, R = 100, R = 5k
OUT
140
200
kHz
kHz
OUT
OUT
IN
= 1mA, R = 100, R
= 5k
IN
OUT
I
V = 4V, I
= 0, R = 1M
220
240
250
375
450
475
µA
µA
S
S
OUT
IN
●
●
●
V = 6V, I
= 0, R = 1M
475
525
µA
µA
S
OUT
IN
V = 12V, I
= 0, R = 1M
500
590
µA
µA
S
OUT
IN
V = 60V, I
LTC6101I, LTC6101C
LTC6101H
= 0, R = 1M
640
690
720
µA
µA
µA
S
OUT
IN
●
●
6101fa
3
LTC6101/LTC6101HV
ELECTRICAL CHARACTERISTICS
(LTC6101HV) The
●
denotes the specifications which apply over the full
+
+
operating temperature range, otherwise specifications are at T = 25°C, R = 100Ω, R
= 10k, V
= V (see Figure 1 for
SENSE
A
IN
OUT
details), 5V ≤ V ≤ 100V unless otherwise noted.
S
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
V
V
Supply Voltage Range
Input Offset Voltage
●
5
100
V
S
V
SENSE
V
SENSE
V
SENSE
= 5mV, Gain = 100, LTC6101HVA
= 5mV, Gain = 100, LTC6101HVAC, LTC6101HVAI
= 5mV, Gain = 100, LTC6101HVAH
±85
±300
±450
±535
µV
µV
µV
OS
●
●
V
= 5mV, Gain = 100, LTC6101HVB
±150
±400
±450
±810
µV
µV
SENSE
●
V
= 5mV, Gain = 100, LTC6101HVC
±1500
±2500
µV
µV
SENSE
●
∆V /∆T
Input Offset Voltage Drift
Input Bias Current
V
V
V
= 5mV, LTC6101HVA
= 5mV, LTC6101HVB
= 5mV, LTC6101HVC
●
●
●
±1
±3
µV/°C
µV/°C
µV/°C
OS
SENSE
SENSE
SENSE
±10
I
I
R
= 1M
100
170
245
nA
nA
B
IN
●
●
●
Input Offset Current
R
= 1M
±2
±15
nA
OS
IN
V
Input Sense Voltage Full Scale
Power Supply Rejection Ratio
V
within Specification, R = 1k
500
mV
SENSE(MAX)
OS
IN
PSRR
V = 6V to 100V, V
= 5mV, Gain = 100
= 5mV, Gain = 100
= 88mV
118
115
140
133
dB
dB
S
SENSE
●
V = 5V to 100V, V
110
105
dB
dB
S
SENSE
●
V
V
Maximum Output Voltage
Minimum Output Voltage
12V ≤ V ≤ 100V, V
5V, V
●
●
8
3
V
V
OUT
S
SENSE
= 330mV, R = 1k, R
= 10k
SENSE
IN
OUT
V
V
V
= 0V, Gain = 100, LTC6101HVA
= 0V, Gain = 100, LTC6101HVAC, LTC6101HVAI
= 0V, Gain = 100, LTC6101HVAH
0
30
45
53.5
mV
mV
mV
OUT (0)
SENSE
SENSE
SENSE
●
●
V
= 0V, Gain = 100, LTC6101HVB
0
0
45
81
mV
mV
SENSE
●
V
= 0V, Gain = 100, LTC6101HVC
150
250
mV
mV
SENSE
●
●
I
t
Maximum Output Current
5V ≤ V ≤ 100V, R
= 2k, V = 110mV, Gain = 20
SENSE
1
mA
OUT
r
S
OUT
Input Step Response
(to 2.5V on a 5V Output Step)
∆V
S
= 100mV Transient, 6V ≤ V ≤ 100V, Gain = 50
1
1.5
µs
µs
SENSE
V = 5V
S
BW
Signal Bandwidth
Supply Current
I
I
= 200µA, R = 100, R = 5k
OUT
140
200
kHz
kHz
OUT
OUT
IN
= 1mA, R = 100, R
= 5k
IN
OUT
I
V = 5V, I
= 0, R = 1M
200
220
230
350
450
475
µA
µA
S
S
OUT
IN
●
●
●
V = 6V, I
= 0, R = 1M
475
525
µA
µA
S
OUT
IN
V = 12V, I
= 0, R = 1M
500
590
µA
µA
S
OUT
IN
V = 60V, I
LTC6101HVI, LTC6101HVC
LTC6101HVH
= 0, R = 1M
640
690
720
µA
µA
µA
S
OUT
IN
●
●
V = 100V, I
LTC6101HVI, LTC6101HVC
LTC6101HVH
= 0, R = 1M
350
640
690
720
µA
µA
µA
S
OUT
IN
●
●
6101fa
4
LTC6101/LTC6101HV
ELECTRICAL CHARACTERISTICS
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
Note 2: The LTC6101C/LTC6101HVC are guaranteed to meet specified
performance from 0°C to 70°C. The LTC6101C/LTC6101HVC are designed,
characterized and expected to meet specified performance from –40°C to
85°C but are not tested or QA sampled at these temperatures. LTC6101I/
LTC6101HVI are guaranteed to meet specified performance from –40°C to
85°C. The LTC6101H/LTC6101HVH are guaranteed to meet specified
performance from –40°C to 125°C.
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Input V vs Temperature
Input V vs Supply Voltage
Input Sense Range
OS
OS
40
20
800
600
2.5
2
REPRESENTATIVE
T
= 25°C
T
= 0°C
T
= –40°C
A
A
A
UNITS
T
A
= 0°C
0
400
T
T
= 70°C
T
T
= –40°C
= 45°C
–20
–40
–60
–80
–100
–120
–140
A
A
A
200
1.5
1
0
A
= 125°C
–200
–400
–600
–800
–1000
T
= 85°C
A
T
T
= 85°C
A
R
R
V
= 100
= 5k
IN
OUT
IN
0.5
0
R
R
V
= 100
= 5k
A GRADE
B GRADE
C GRADE
IN
OUT
IN
R
R
= 3k
OUT
= 5mV
IN
LTC6101
LTC6101HV
= 125°C
A
= 3k
= 5mV
4
11 18 25 32 39 46 53 60
(V)
–40 –20
0
20 40 60 80 100 120
4 10 20 30 40 50 60 70 80 90 100
V
V
(V)
SUPPLY
TEMPERATURE (°C)
SUPPLY
6101 G02
6101 G05
6101 G01
LTC6101: V
Maximum vs
LTC6101HV: V
Temperature
Maximum vs
LTC6101: I
Maximum vs
OUT
OUT
OUT
Temperature
Temperature
12
10
8
12
10
8
7
6
5
4
3
2
1
0
V
S
= 60V
V
S
= 100V
S
S
V
= 12V
S
V
= 12V
V
= 12V
V
= 60V
S
V
V
V
= 6V
= 5V
= 4V
S
S
S
6
6
V
V
= 6V
= 4V
S
V
V
= 6V
= 4V
S
S
4
4
S
2
2
0
0
–40 –20
0
20 40 60 80 100 120
TEMPERATURE (°C)
6101 G06
–40 –20
0
20 40 60 80 100 120
TEMPERATURE (°C)
6101 G20
–40 –20
0
20 40 60 80 100 120
TEMPERATURE (°C)
6101 G07
6101fa
5
LTC6101/LTC6101HV
U W
TYPICAL PERFOR A CE CHARACTERISTICS
LTC6101HV: I
Temperature
Maximum vs
Output Error Due to Input Offset vs
Input Voltage
OUT
Gain vs Frequency
100
10
1
7
6
5
4
3
2
1
0
40
35
30
25
20
15
10
5
T
= 25°C
A
GAIN =10
I
= 1mA
OUT
V
S
= 12V
S
T
R
R
= 25°C
A
= 100
IN
= 4.99k
OUT
V
= 100V
V
V
= 6V
= 5V
I
= 200µA
S
S
OUT
C GRADE
0.1
B GRADE
A GRADE
0
V
= 4V
S
–5
–10
0.01
–40 –20
0
20 40 60 80 100 120
TEMPERATURE (°C)
6101 G21
1k
10k
100k
1M
0
0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5
FREQUENCY (Hz)
INPUT VOLTAGE (V)
6101 G09
6101 G08
Input Bias Current vs
Temperature
LTC6101: Supply Current vs
Supply Voltage
LTC6101HV: Supply Current vs
Supply Voltage
160
140
120
100
80
600
500
400
300
200
100
0
450
400
350
300
250
200
150
100
50
70°C
85°C
125°C
70°C
85°C
V
= 6V TO 100V
S
125°C
V
= 4V
S
25°C
0°C
25°C
60
–40°C
0°C
40
–40°C
V
= 0
= 1M
V
= 0
IN
IN
IN
IN
20
R
R
= 1M
0
0
–40 –20
0
20 40 60 80 100 120
TEMPERATURE (°C)
0
10 20 30 40 50 60 70 80 90 100
0
4
8 12 16 20 24 28 32 36 40 44 48 52 56 60
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
6101 G10
6101 G22
6101 G11
Step Response 0mV to 10mV
Step Response 10mV to 20mV
–
–
V+-10mV
SENSE
V
V
SENSE
V+
V+-10mV
V+-20mV
0.5V
1V
T
= 25°C
A
T
= 25°C
V+ = 12V
A
V+ = 12V
R
R
V
= 100
IN
R
R
V
= 100
IN
= 5k
OUT
= 5k
+ = V+
OUT
SENSE
+ = V+
SENSE
0V
0.5V
V
OUT
V
OUT
TIME (10µs/DIV)
TIME (10µs/DIV)
6101 G12
6101 G13
6101fa
6
LTC6101/LTC6101HV
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Step Response Rising Edge
Step Response 100mV
Step Response 100mV
–
–
–
V
V
SENSE
SENSE
V
SENSE
V+
V+
∆V
– =100mV
V+-100mV
V+-100mV
T
= 25°C
SENSE
A
V+ = 12V
= 2200pF
C
= 10pF
LOAD
C
5V
5V
LOAD
5.5V
5V
T
= 25°C
A
R
R
V
= 100
V+ = 12V
IN
= 5k
OUT
R
R
V
= 100
+ = V+
IN
T
= 25°C
A
SENSE
V+ = 12V
= 5k
OUT
+ = V+
C
= 1000pF
LOAD
SENSE
R
R
V
= 100
= 5k
SENSE
IN
OUT
V
OUT
+ = V+
I
= 100µA
OUT
0V
0V
0.5V
0V
I
= 0
V
V
OUT
OUT
OUT
TIME (10µs/DIV)
TIME (100µs/DIV)
TIME (500ns/DIV)
6101 G14
6101 G15
6101 G16
Step Response Falling Edge
PSRR vs Frequency
160
LTC6101,
+
∆V
– =100mV
140
120
100
80
SENSE
V
= 4V
V
OUT
5.5V
5V
T
= 25°C
A
V+ = 12V
LTC6101,
LTC6101HV,
R
R
V
= 100
IN
+
V
= 12V
= 5k
OUT
+ = V+
SENSE
60
R
R
= 100
IN
= 10k
= 5pF
OUT
OUT
40
I
= 100µ
OUT
C
GAIN = 100
LTC6101HV,
+
20
I
= 100µA
= 50mVp
V = 5V
OUTDC
INAC
0.5V
0V
I
= 0
OUT
V
0
0.1
1
10 100 1k
10k 100k 1M
TIME (500ns/DIV)
FREQUENCY (Hz)
6101 G19
6101 G17
6101fa
7
LTC6101/LTC6101HV
U
U
U
PI FU CTIO S
OUT (Pin 1): Current Output. OUT (Pin 1) will source a
current that is proportional to the sense voltage into an
external resistor.
V– (Pin 2): Negative Supply (or Ground for Single-Supply
Operation).
IN– (Pin 3): The internal sense amplifier will drive IN– (Pin
3) to the same potential as IN+ (Pin 4). A resistor (RIN) tied
from V+ to IN– sets the output current IOUT = VSENSE/RIN.
VSENSE isthevoltagedevelopedacrosstheexternalRSENSE
(Figure 1).
IN+ (Pin 4): Must be tied to the system load end of the
sense resistor, either directly or through a resistor.
V+ (Pin 5): Positive Supply Pin. Supply current is drawn
through this pin. The circuit may be configured so that
the LTC6101 supply current is or is not monitored along
with the system load current. To monitor only system
load current, connect V+ to the more positive side of the
sense resistor. To monitor the total current, including the
LTC6101 current, connect V+ to the more negative side of
the sense resistor.
W
BLOCK DIAGRA
I
LOAD
V
SENSE
+
–
R
V
BATTERY
SENSE
R
IN
5
+
10V
V
L
O
A
D
–
+
5k
5k
–
+
IN
IN
3
4
I
10V
OUT
R
R
OUT
OUT
V
OUT
= V x
SENSE
1
–
IN
V
LTC6101/LTC6101HV
R
OUT
2
6101 BD
Figure 1. LTC6101/LTC6101HV Block Diagram and Typical Connection
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APPLICATIO S I FOR ATIO
The LTC6101 high side current sense amplifier (Figure 1)
provides accurate monitoring of current through a user-
selected sense resistor. The sense voltage is amplified by
a user-selected gain and level shifted from the positive
power supply to a ground-referred output. The output
signal is analog and may be used as is or processed with
an output filter.
RIN, between IN– and V+ forces a potential across RIN that
is the same as the sense voltage across RSENSE. A corre-
sponding current, VSENSE/RIN, will flow through RIN. The
high impedance inputs of the sense amplifier will not
conduct this input current, so it will flow through an
internal MOSFET to the output pin.
The output current can be transformed into a voltage by
adding a resistor from OUT to V–. The output voltage is
Theory of Operation
then VO = V– + IOUT • ROUT
.
An internal sense amplifier loop forces IN– to have the
same potential as IN+. Connecting an external resistor,
6101fa
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LTC6101/LTC6101HV
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APPLICATIO S I FOR ATIO
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Useful Gain Configurations
Peak dissipation is 200mW. If a 5mΩ sense resistor is
employed, then the effective current error is 30mA, while
the peak sense voltage is reduced to 10mV at 2A, dissipat-
ing only 20mW.
Gain
20
R
R
V
at V
= 5V
I
at V
= 5V
IN
OUT
SENSE
OUT
OUT
OUT
499
200
100
10k
10k
10k
250mV
100mV
50mV
500µA
500µA
500µA
50
The low offset and corresponding large dynamic range of
the LTC6101 make it more flexible than other solutions in
this respect. The 150µV typical offset gives 60dB of
dynamicrangeforasensevoltagethatislimitedto150mV
max, and over 70dB of dynamic range if the rated input
maximum of 500mV is allowed.
100
Selection of External Current Sense Resistor
The external sense resistor, RSENSE, has a significant
effect on the function of a current sensing system and
must be chosen with care.
Sense Resistor Connection
First, the power dissipation in the resistor should be
considered. The system load current will cause both heat
and voltage loss in RSENSE. As a result, the sense resistor
should be as small as possible while still providing the
input dynamic range required by the measurement. Note
that input dynamic range is the difference between the
maximuminputsignalandtheminimumaccuratelyrepro-
duced signal, and is limited primarily by input DC offset of
the internal amplifier of the LTC6101. In addition, RSENSE
must be small enough that VSENSE does not exceed the
maximum input voltage specified by the LTC6101, even
under peak load conditions. As an example, an application
may require that the maximum sense voltage be 100mV.
If this application is expected to draw 2A at peak load,
RSENSE should be no more than 50mΩ.
Kelvin connection of the IN– and IN+ inputs to the sense
resistor should be used in all but the lowest power appli-
cations. Solder connections and PC board interconnec-
tions that carry high current can cause significant error in
measurementduetotheirrelativelylargeresistances. One
10mm x 10mm square trace of one-ounce copper is
approximately 0.5mΩ. A 1mV error can be caused by as
little as 2A flowing through this small interconnect. This
willcausea1%errorina100mVsignal.A10Aloadcurrent
inthesameinterconnectwillcausea5%errorforthesame
100mVsignal. Byisolatingthesensetracesfromthehigh-
current paths, this error can be reduced by orders of
magnitude. A sense resistor with integrated Kelvin sense
terminals will give the best results. Figure 2 illustrates the
recommended method.
Once the maximum RSENSE value is determined, the mini-
mum sense resistor value will be set by the resolution or
dynamic range required. The minimum signal that can be
accurately represented by this sense amp is limited by the
input offset. As an example, the LTC6101B has a typical
input offset of 150µV. If the minimum current is 20mA, a
sense resistor of 7.5mΩ will set VSENSE to 150µV. This is
the same value as the input offset. A larger sense resistor
will reduce the error due to offset by increasing the sense
voltage for a given load current.
+
V
R
IN
R
SENSE
4
2
3
5
–
+
LOAD
Choosing a 50mΩ RSENSE will maximize the dynamic
range and provide a system that has 100mV across the
sense resistor at peak load (2A), while input offset causes
an error equivalent to only 3mA of load current.
1
V
OUT
LTC6101
R
OUT
6101 F02
Figure 2. Kelvin Input Connection Preserves
Accuracy Despite Large Load Current
6101fa
9
LTC6101/LTC6101HV
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APPLICATIO S I FOR ATIO
Selection of External Input Resistor, RIN
currentmeasurementaccuracybylimitingtheresult,while
increasing the low current measurement resolution.
The external input resistor, RIN, controls the transcon-
ductance of the current sense circuit. Since IOUT = VSENSE
/
+
V
RIN, transconductance gm = 1/RIN. For example, if RIN =
100, then IOUT = VSENSE/100 or IOUT = 1mA for VSENSE
100mV.
=
R
D
SENSE
SENSE
6101 F03a
RIN shouldbechosentoallowtherequiredresolutionwhile
limitingtheoutputcurrent.Atlowsupplyvoltage,IOUT may
be as much as 1mA. By setting RIN such that the largest
expected sense voltage gives IOUT = 1mA, then the maxi-
mum output dynamic range is available. Output dynamic
range is limited by both the maximum allowed output
current and the maximum allowed output voltage, as well
as the minimum practical output signal. If less dynamic
range is required, then RIN can be increased accordingly,
reducing the max output current and power dissipation.
If low sense currents must be resolved accurately in a
systemthathasverywidedynamicrange,asmallerRINthan
the max current spec allows may be used if the max
current is limited in another way, such as with a Schottky
diode across RSENSE (Figure 3a). This will reduce the high
LOAD
Figure 3a. Shunt Diode Limits Maximum Input Voltage to Allow
Better Low Input Resolution Without Overranging
This approach can be helpful in cases where occasional
large burst currents may be ignored. It can also be used in
a multirange configuration where a low current circuit is
added to a high current circuit (Figure 3b). Note that a
comparator (LTC1540) is used to select the range, and
transistor M1 limits the voltage across RSENSE LO
.
Care should be taken when designing the board layout for
RIN, especially for small RIN values. All trace and intercon-
nect impedances will increase the effective RIN value,
causingagainerror. Inaddition, internaldeviceresistance
will add approximately 0.2Ω to RIN.
V
LOGIC
CMPZ4697
10k
(3.3V TO 5V)
7
3
4
M1
+
–
Si4465
V
IN
R
SENSE HI
10m
I
LOAD
8
Q1
CMPT5551
5
6
V
OUT
40.2k
R
SENSE LO
100m
301
301
301
301
4.7k
1.74M
LTC1540
4
2
3
5
4
3
5
2
1
HIGH
RANGE
INDICATOR
(I > 1.2A)
+
+
–
–
2
V
IN
619k
LOAD
1
1
HIGH CURRENT RANGE OUT
250mV/A
LTC6101
LTC6101
7.5k
V
LOGIC
BAT54C
LOW CURRENT RANGE OUT
2.5V/A
R
5
(
V
+5V
)
≤ V ≤ 60V
LOGIC
IN
7.5k
6101 F03b
0 ≤ I
≤ 10A
LOAD
Figure 3b. Dual LTC6101s Allow High-Low Current Ranging
6101fa
10
LTC6101/LTC6101HV
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APPLICATIO S I FOR ATIO
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Output Error, EOUT, Due to the Amplifier DC Offset
Voltage, VOS
Selection of External Output Resistor, ROUT
The output resistor, ROUT, determines how the output
currentisconvertedtovoltage. VOUT issimplyIOUT •ROUT
EOUT(VOS) = VOS • (ROUT/RIN)
.
The DC offset voltage of the amplifier adds directly to the
value of the sense voltage, VSENSE. This is the dominant
error of the system and it limits the available dynamic
range.Theparagraph“SelectionofExternalCurrentSense
Resistor” provides details.
In choosing an output resistor, the max output voltage
must first be considered. If the circuit that is driven by the
output does not limit the output voltage, then ROUT must
be chosen such that the max output voltage does not
exceed the LTC6101 max output voltage rating. If the
followingcircuitisabufferorADCwithlimitedinputrange,
then ROUT must be chosen so that IOUT(MAX) • ROUT is less
than the allowed maximum input range of this circuit.
Output Error, EOUT, Due to the Bias Currents,
IB(+) and IB(–)
The bias current IB(+) flows into the positive input of the
internal op amp. IB(–) flows into the negative input.
In addition, the output impedance is determined by ROUT
.
If the circuit to be driven has high enough input imped-
ance, then almost any useful output impedance will be
acceptable. However, ifthedrivencircuithasrelativelylow
input impedance, or draws spikes of current, such as an
ADC might do, then a lower ROUT value may be required in
order to preserve the accuracy of the output. As an
example, if the input impedance of the driven circuit is 100
times ROUT, then the accuracy of VOUT will be reduced by
1% since:
EOUT(IBIAS) = ROUT((IB(+) • (RSENSE/RIN) – IB(–))
Since IB(+) ≈ IB(–) = IBIAS, if RSENSE << RIN then,
EOUT(IBIAS) ≈ –ROUT • IBIAS
For instance if IBIAS is 100nA and ROUT is 1kΩ, the output
error is 0.1mV.
Note that in applications where RSENSE ≈ RIN, IB(+) causes
a voltage offset in RSENSE that cancels the error due to
ROUT •R
ROUT + R
IN(DRIVEN)
IB(–) and EOUT(IBIAS) ≈ 0. In applications where RSENSE
<
VOUT = IOUT
•
RIN, the bias current error can be similarly reduced if an
external resistor RIN(+) = (RIN – RSENSE) is connected as
shown in Figure 4 below. Under both conditions:
IN(DRIVEN)
100
101
= IOUT •ROUT
•
= 0.99•IOUT •ROUT
EOUT(IBIAS) = ± ROUT • IOS; IOS = IB(+) – IB(–)
Error Sources
+
V
The current sense system uses an amplifier and resistors
to apply gain and level shift the result. The output is then
dependent on the characteristics of the amplifier, such as
gain and input offset, as well as resistor matching.
–
R
IN
R
SENSE
+
R
IN
4
2
3
5
–
+
Ideally, the circuit output is:
LOAD
R
R
VOUT = VSENSE
•
OUT ;VSENSE = RSENSE •ISENSE
IN
In this case, the only error is due to resistor mismatch,
which provides an error in gain only. However, offset
voltage, bias current and finite gain in the amplifier cause
additional errors:
1
V
OUT
LTC6101
R
OUT
6101 F04
+
–
R
=
R
– R
IN
IN SENSE
Figure 4. Second Input R Minimizes
Error Due to Input Bias Current
6101fa
11
LTC6101/LTC6101HV
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APPLICATIO S I FOR ATIO
If the offset current, IOS, of the LTC6101 amplifier is 2nA,
the 100 microvolt error above is reduced to 2 microvolts.
AddingRIN+ asdescribedwillmaximizethedynamicrange
of the circuit. For less sensitive designs, RIN is not
necessary.
PQ = IDD • V+
The total power dissipated is the output dissipation plus
the quiescent dissipation:
+
PTOTAL = POUT + PQ
At maximum supply and maximum output current, the
total power dissipation can exceed 100mW. This will
cause significant heating of the LTC6101 die. In order to
prevent damage to the LTC6101, the maximum expected
dissipation in each application should be calculated. This
number can be multiplied by the θJA value listed in the
package section on page 2 to find the maximum expected
die temperature. This must not be allowed to exceed
150°C, or performance may be degraded.
Example:
If an ISENSE range = (1A to 1mA) and (VOUT SENSE
3V/1A
/I
) =
Then, from the Electrical Characteristics of the LTC6101,
RSENSE ≈ VSENSE (max) / ISENSE (max) = 500mV/1A =
500mΩ
Gain = ROUT/RIN = VOUT(max) / VSENSE (max) = 3V/500mV
= 6
Asanexample,ifanLTC6101intheS5packageistoberun
at 55V ±5V supply with 1mA output current at 80°C:
If the maximum output current, IOUT, is limited to 1mA,
ROUT equals 3V/1mA≈3.01kΩ(1%value)andRIN=3kΩ/
6 ≈ 499Ω (1% value).
PQ(MAX) = IDD(MAX) • V+(MAX) = 41.4mW
POUT(MAX) = IOUT • V+(MAX) = 60mW
TRISE = θJA • PTOTAL(MAX)
The output error due to DC offset is ±900µVolts (typ) and
the error due to offset current, IOS is 3k x 2nA = ±6µVolts
(typical), provided RIN+ = RIN
.
–
TMAX = TAMBIENT + TRISE
Themaximumoutputerrorcanthereforereach±906µVolts
or 0.03% (–70dB) of the output full scale. Considering the
system input 60dB dynamic range (ISENSE = 1mA to 1A),
the70dBperformanceoftheLTC6101makesthisapplica-
tion feasible.
TMAX must be < 150°C
PTOTAL(MAX) ≈ 96mW and the max die temp
will be 104°C
If this same circuit must run at 125°C, the max die
temp will increase to 150°C. (Note that supply current,
and therefore PQ, is proportional to temperature. Refer to
Typical Performance Characteristics section.) In this con-
dition, the maximum output current should be reduced to
avoid device damage. Note that the MSOP package has a
larger θJA than the S5, so additional care must be taken
when operating the LTC6101A/LTC6101HVA at high tem-
peratures and high output currents.
Output Error, EOUT, Due to the Finite DC Open Loop
Gain, AOL, of the LTC6101 Amplifier
This errors is inconsequential as the AOL of the LTC6101
is very large.
Output Current Limitations Due to Power Dissipation
The LTC6101 can deliver up to 1mA continuous current to
the output pin. This current flows through RIN and enters
the current sense amp via the IN(–) pin. The power
dissipated in the LTC6101 due to the output signal is:
The LTC6101HV can be used at voltages up to 105V. This
additional voltage requires that more power be dissipated
for a given level of current. This will further limit the
allowed output current at high ambient temperatures.
POUT = (V–IN – VOUT) • IOUT
Since V–IN ≈ V+, POUT ≈ (V+ – VOUT) • IOUT
ItisimportanttonotethattheLTC6101hasbeendesigned
to provide at least 1mA to the output when required, and
can deliver more depending on the conditions. Care must
Thereisalsopowerdissipatedduetothequiescentsupply
current:
6101fa
12
LTC6101/LTC6101HV
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APPLICATIO S I FOR ATIO
U
allow a wide VSENSE range, it also allows the input refer-
ence to be separate from the positive supply (Figure 5).
Note that the difference between VBATT and V+ must be no
more than the common mode range listed in the Electrical
Characteristics table. If the maximum VSENSE is less than
500mV,theLTC6101maymonitoritsownsupplycurrent,
as well as that of the load (Figure 6).
be taken to limit the maximum output current by proper
choice of sense resistor and, if input fault conditions exist,
external clamps.
Output Filtering
Theoutputvoltage,VOUT,issimplyIOUT•ZOUT.Thismakes
filtering straightforward. Any circuit may be used which
generates the required ZOUT to get the desired filter
response. For example, a capacitor in parallel with ROUT
will give a low pass response. This will reduce unwanted
noise from the output, and may also be useful as a charge
reservoir to keep the output steady while driving a switch-
ing circuit such as a mux or ADC. This output capacitor in
parallel with an output resistor will create a pole in the
output response at:
V
BATTERY
R
IN
R
SENSE
4
2
3
5
–
+
+
V
LOAD
1
f–3dB
=
1
2 • π •ROUT •COUT
V
OUT
LTC6101
R
OUT
Useful Equations
6101 F05
+
Figure 5. V Powered Separately from
Input Voltage: VSENSE = ISENSE •RSENSE
Load Supply (V
)
BATT
VOUT
VSENSE
ROUT
RIN
Voltage Gain:
Current Gain:
=
+
V
IOUT
ISENSE
RSENSE
RIN
R
IN
=
R
SENSE
4
2
3
5
–
+
IOUT
VSENSE RIN
1
Transconductance:
=
LOAD
VOUT
ISENSE
ROUT
RIN
Transimpedance:
= RSENSE
•
1
V
LTC6101
OUT
R
OUT
Input Common Mode Range
6101 F06
The inputs of the LTC6101 can function from 1.5V below
the positive supply to 0.5V above it. Not only does this
Figure 6. LTC6101 Supply Current
Monitored with Load
6101fa
13
LTC6101/LTC6101HV
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APPLICATIO S I FOR ATIO
Reverse Supply Protection
If the output current is very low and an input transient
occurs, there may be an increased delay before the output
voltage begins changing. This can be improved by in-
creasingtheminimumoutputcurrent,eitherbyincreasing
RSENSE or decreasing RIN. The effect of increased output
current is illustrated in the step response curves in the
Typical Performance Characteristics section of this
datasheet. Note that the curves are labeled with respect to
the initial output currents.
Some applications may be tested with reverse-polarity
supplies due to an expectation of this type of fault during
operation. The LTC6101 is not protected internally from
external reversal of supply polarity. To prevent damage
that may occur during this condition, a Schottky diode
should be added in series with V– (Figure 7). This will limit
the reverse current through the LTC6101. Note that this
diodewilllimitthelowvoltageperformanceoftheLTC6101
byeffectivelyreducingthesupplyvoltagetothepartbyVD.
The speed is also affected by the external circuit. In this
case, if the input changes very quickly, the internal ampli-
fier will slew the gate of the internal output FET (Figure 1)
in order to maintain the internal loop. This results in
current flowing through RIN and the internal FET. This
current slew rate will be determined by the amplifier and
FETcharacteristicsaswellastheinputresistor, RIN. Using
asmallerRIN willallowtheoutputcurrenttoincreasemore
quickly, decreasing the response time at the output. This
will also have the effect of increasing the maximum output
current. Using a larger ROUT will decrease the response
time, since VOUT = IOUT • ROUT. Reducing RIN and increas-
ing ROUT will both have the effect of increasing the voltage
gain of the circuit.
Inaddition,iftheoutputoftheLTC6101iswiredtoadevice
that will effectively short it to high voltage (such as
throughanESDprotectionclamp)duringareversesupply
condition, the LTC6101’s output should be connected
through a resistor or Schottky diode (Figure 8).
Response Time
TheLTC6101isdesignedtoexhibitfastresponsetoinputs
for the purpose of circuit protection or signal transmis-
sion. This response time will be affected by the external
circuit in two ways, delay and speed.
R
SENSE
R
SENSE
R1
100
R1
V
BATT
4
2
3
5
100
L
O
A
D
+
–
4
2
3
5
L
O
A
D
+
–
V
BATT
1
R3
1k
LTC6101
D1
1
LTC6101
D1
ADC
R2
4.99k
R2
4.99k
6101 F07
6101 F08
Figure 7. Schottky Prevents Damage During Supply Reversal
Figure 8. Additional Resistor R3 Protects
Output During Supply Reversal
6101fa
14
LTC6101/LTC6101HV
U
TYPICAL APPLICATIO S
Bidirectional Current Sense Circuit with Separate Charge/Discharge Output
I
I
CHARGE
DISCHARGE
R
SENSE
CHARGER
R
IN C
R
IN D
100
100
R
R
IN C
100
IN D
100
4
2
3
5
3
5
4
2
V
BATT
+
+
–
–
L
O
A
D
1
1
LTC6101
LTC6101
+
OUT D
–
+
R
R
OUT C
4.99k
OUT D
4.99k
V
V
OUT C
–
6101 TA02
R
R
OUT D
DISCHARGING: V
CHARGING: V
= I
• R
WHEN I
≥ 0
DISCHARGE
OUT D DISCHARGE
SENSE
R
(
)
IN D
OUT C
= I
• R
WHEN I
≥ 0
CHARGE
OUT C CHARGE
SENSE
(
)
R
IN C
LTC6101 Monitors Its Own Supply Current
High-Side-Input Transimpedance Amplifier
V
S
I
R
SENSE
LOAD
CMPZ4697*
(10V)
LASER MONITOR
PHOTODIODE
i
PD
I
R1
100
SUPPLY
4.75k
4.75k
10k
4
2
3
5
L
O
A
D
4
3
5
+
–
+
–
2
V
BATT
1
LTC6101
+
–
R2
4.99k
1
V
OUT
LTC6101
V
O
6101 TA03
R
L
V
= I • R
L
6101 TA04
O
PD
V
OUT
= 49.9 • R
(
I
+ I
)
SENSE LOAD SUPPLY
*V SETS PHOTODIODE BIAS
Z
V
+ 4 ≤ V ≤ V + 60
S Z
Z
6101fa
15
LTC6101/LTC6101HV
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TYPICAL APPLICATIO S
16-Bit Resolution Unidirectional Output into LTC2433 ADC
I
V
LOAD
SENSE
+
–
R
IN
4V TO 60V
100Ω
4
2
3
5
L
O
A
D
+
–
1µF
5V
2
1
+
V
REF
OUT
1
V
4
5
CC
9
8
7
+
LTC6101
IN
SCK
SDD
LTC2433-1
TO µP
R
OUT
4.99k
–
IN
C
C
–
F
REF GND
O
3
6
10
R
R
OUT
6101 TA06
V
=
• V
= 49.9V
SENSE
ADC FULL-SCALE = 2.5V
OUT
SENSE
IN
Intelligent High-Side Switch with Current Monitor
10µF
63V
V
LOGIC
14V
47k
5
100Ω
3
1%
FAULT
8
6
3
4
1
4
2
R
S
LT1910
1
LTC6101
2
V
O
OFF ON
100Ω
4.99k
1µF
5
SUB85N06-5
V
= 49.9 • R • I
S L
L
O
A
D
O
I
L
FOR R = 5mΩ,
S
V
O
= 2.5V AT I = 10A (FULL SCALE)
L
6101 TA07
6101fa
16
LTC6101/LTC6101HV
U
TYPICAL APPLICATIO S
48V Supply Current Monitor with Isolated Output with 105V Survivability
I
V
SENSE
SENSE
–
+
V
LOAD
S
R
SENSE
R
IN
3
5
4
2
–
+
–
V
LTC6101HV
V
LOGIC
R
OUT
V
OUT
ANY OPTOISOLATOR
–
V
N = OPTOISOLATOR CURRENT GAIN
R
SENSE
V
= V
I
•
• N • R
OUT
OUT
LOGIC – SENSE
6101 TA08
R
IN
Simple 500V Current Monitor
DANGER! Lethal Potentials Present — Use Caution
I
V
SENSE
500V
SENSE
SENSE
+
–
R
R
IN
100Ω
4
3
L
O
A
D
DANGER!!
HIGH VOLTAGE!!
+
–
2
5
1
62V
CMZ59448
LTC6101
M1
V
M2
OUT
R
OUT
M1 AND M2 ARE FQD3P50 TM
2M
4.99k
R
OUT
V
=
• V
= 49.9 V
SENSE SENSE
OUT
R
IN
6101 TA09
6101fa
17
LTC6101/LTC6101HV
U
PACKAGE DESCRIPTIO
MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660)
0.889 ± 0.127
(.035 ± .005)
5.23
(.206)
MIN
3.20 – 3.45
(.126 – .136)
3.00 ± 0.102
(.118 ± .004)
(NOTE 3)
0.52
(.0205)
REF
0.65
(.0256)
BSC
0.42 ± 0.038
(.0165 ± .0015)
TYP
8
7 6 5
RECOMMENDED SOLDER PAD LAYOUT
3.00 ± 0.102
(.118 ± .004)
(NOTE 4)
4.90 ± 0.152
(.193 ± .006)
DETAIL “A”
0.254
(.010)
0° – 6° TYP
GAUGE PLANE
1
2
3
4
0.53 ± 0.152
(.021 ± .006)
1.10
(.043)
MAX
0.86
(.034)
REF
DETAIL “A”
0.18
(.007)
SEATING
PLANE
0.22 – 0.38
0.127 ± 0.076
(.009 – .015)
(.005 ± .003)
0.65
(.0256)
BSC
TYP
MSOP (MS8) 0204
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
6101fa
18
LTC6101/LTC6101HV
U
PACKAGE DESCRIPTIO
S5 Package
5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635)
0.62
MAX
0.95
REF
2.90 BSC
(NOTE 4)
1.22 REF
1.50 – 1.75
(NOTE 4)
2.80 BSC
1.4 MIN
3.85 MAX 2.62 REF
PIN ONE
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
0.30 – 0.45 TYP
5 PLCS (NOTE 3)
0.95 BSC
0.80 – 0.90
0.20 BSC
DATUM ‘A’
0.01 – 0.10
1.00 MAX
0.30 – 0.50 REF
1.90 BSC
0.09 – 0.20
(NOTE 3)
NOTE:
S5 TSOT-23 0302
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
6101fa
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
19
LTC6101/LTC6101HV
U
TYPICAL APPLICATIO
Bidirectional Current Sense Circuit with Combined Charge/Discharge Output
I
I
CHARGE
DISCHARGE
R
SENSE
CHARGER
R
IN C
R
IN D
R
IN D
R
IN C
4
2
3
5
3
5
4
2
V
BATT
+
+
–
–
L
O
A
D
1
1
LTC6101
LTC6101
+
OUT
V
R
OUT
–
6101 TA05
R
R
OUT
IN D
DISCHARGING: V
CHARGING: V
= I
• R
WHEN I
≥ 0
DISCHARGE
OUT DISCHARGE
SENSE
(
)
R
R
OUT
IN C
= I
• R
WHEN I
≥ 0
CHARGE
OUT CHARGE
SENSE
(
)
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
Extends 44V above V , 55µA Supply Current,
LT1636
Rail-to-Rail Input/Output, Micropower Op Amp
V
CM
EE
Shutdown Function
LT1637/LT1638/
LT1639
Single/Dual/Quad, Rail-to-Rail, Micropower Op Amp
V
Extends 44V above V , 0.4V/µs Slew Rate, >1MHz
CM EE
Bandwidth, <250µA Supply Current per Amplifier
LT1787/LT1787HV Precision, Bidirectional, High Side Current Sense Amplifier
2.7V to 60V Operation, 75µV Offset, 60µA Current Draw
±200V Transient Protection, Drives Three Optoisolators for Status
±250V Common Mode, Micropower, Pin Selectable Gain = 1, 10
2.7V to ±18V, Micropower, Pin Selectable Gain = –13 to 14
3µV Offset, 30nV/°C Drift, Input Extends Down to V–
LTC1921
LT1990
LT1991
Dual –48V Supply and Fuse Monitor
High Voltage, Gain Selectable Difference Amplifier
Precision, Gain Selectable Difference Amplifier
LTC2050/LTC2051/ Single/Dual/Quad Zero-Drift Op Amp
LTC2052
LTC4150
Coulomb Counter/Battery Gas Gauge
Indicates Charge Quantity and Polarity
Over-The-Top is a trademark of Linear Technology Corporation.
6101fa
LT/TP 0805 500 REV A • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
20
●
●
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
© LINEAR TECHNOLOGY CORPORATION 2005
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