MAX4410EUD [MAXIM]
80mW, DirectDrive Stereo Headphone Driver with Shutdown; 用80mW的关机， DirectDrive立体声耳机驱动器
| 型号： | MAX4410EUD |
| 厂家： | 
MAXIM INTEGRATED PRODUCTS |
| 描述： | 80mW, DirectDrive Stereo Headphone Driver with Shutdown |
| 文件： | 总20页 (文件大小：861K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
19-2386; Rev 2; 10/02
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
General Description
Features
The MAX4410 stereo headphone driver is designed for
portable equipment where board space is at a
premium. The MAX4410 uses a unique, patented,
DirectDrive architecture to produce a ground-refer-
enced output from a single supply, eliminating the need
for large DC-blocking capacitors, saving cost, board
space, and component height.
ꢀ No Bulky DC-Blocking Capacitors Required
ꢀ Ground-Referenced Outputs Eliminate DC-Bias
Voltages on Headphone Ground Pin
ꢀ No Degradation of Low-Frequency Response Due
to Output Capacitors
ꢀ 80mW Per Channel into 16Ω
The MAX4410 delivers up to 80mW per channel into a
16Ω load and has low 0.003% THD + N. A high power-
supply rejection ratio (90dB at 1kHz) allows this device to
operate from noisy digital supplies without an additional
linear regulator. The MAX4410 includes 8kV ESD pro-
tection on the headphone outputs. Comprehensive click-
and-pop circuitry suppresses audible clicks and pops on
startup and shutdown. Independent left/right, low-power
shutdown controls make it possible to optimize power
savings in mixed mode, mono/stereo applications.
ꢀ Low 0.003% THD + N
ꢀ High PSRR (90dB at 1kHz)
ꢀ Integrated Click-and-Pop Suppression
ꢀ 1.8V to 3.6V Single-Supply Operation
ꢀ Low Quiescent Current
ꢀ Independent Left/Right, Low-Power
Shutdown Controls
ꢀ Short-Circuit and Thermal Overload Protection
The MAX4410 operates from a single 1.8V to 3.6V supply,
consumes only 7mA of supply current, has short-circuit
and thermal overload protection, and is specified over the
extended -40°C to +85°C temperature range. The
MAX4410 is available in a tiny (2mm x 2mm x 0.6mm),
16-bump chip-scale package (UCSP™) and a 14-pin
TSSOP package.
ꢀ
8kV ESD-Protected Amplifier Outputs
ꢀ Available in Space-Saving Packages
16-Bump UCSP (2mm x 2mm x 0.6mm)
14-Pin TSSOP
Ordering Information
PIN/BUMP-
PACKAGE
PART
TEMP RANGE
Applications
Notebooks
Cellular Phones
PDAs
MP3 Players
Web Pads
Portable Audio Equipment
MAX4410EBE-T*
MAX4410EUD
-40°C to +85°C
-40°C to +85°C
16 UCSP-16
14 TSSOP
*Future product—contact factory for availability.
Functional Diagram
MAX4410
LEFT
AUDIO
INPUT
SHDNL
SHDNR
RIGHT
AUDIO
INPUT
UCSP is a trademark of Maxim Integrated Products, Inc.
Pin Configurations and Typical Application Circuit appear
at end of data sheet.
________________________________________________________________ Maxim Integrated Products
1
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
ABSOLUTE MAXIMUM RATINGS
PGND to SGND .....................................................-0.3V to +0.3V
Continuous Power Dissipation (T = +70°C)
A
PV
to SV
SS
and SV
-0.3V to +0.3V
14-Pin TSSOP (derate 9.1mW/°C above +70°C) ..........727mW
16-Bump UCSP (derate 15.2mW/°C above +70°C)....1212mW
Junction Temperature......................................................+150°C
Operating Temperature Range ...........................-40°C to +85°C
Storage Temperature Range.............................-65°C to +150°C
Bump Temperature (soldering) (Note 1)
Infrared (15s) ...............................................................+220°C
Vapor Phase (60s) .......................................................+215°C
Lead Temperature (soldering, 10s) .................................+300°C
DD
DD .................................................................
PV to SV .........................................................-0.3V to +0.3V
SS
PV
to PGND or SGND.........................-0.3V to +4V
DD
DD
SS
PV and SV to PGND or SGND ..........................-4V to +0.3V
SS
IN_ to SGND..........................................................-0.3V to +0.3V
SHDN_ to SGND........................(SGND - 0.3V) to (SV
OUT_ to SGND ............................(SV - 0.3V) to (SV
C1P to PGND.............................(PGND - 0.3V) to (PV
+ 0.3V)
+ 0.3V)
+ 0.3V)
DD
DD
DD
SS
C1N to PGND.............................(PV - 0.3V) to (PGND + 0.3V)
SS
Output Short Circuit to GND or V ...........................Continuous
DD
Note 1: This device is constructed using a unique set of packaging techniques that impose a limit on the thermal profile the device
can be exposed to during board-level solder attach and rework. This limit permits only the use of the solder profiles recom-
mended in the industry-standard specification, JEDEC 020A, paragraph 7.6, Table 3 for IR/VPR and convection reflow.
Preheating is required. Hand or wave soldering is not allowed.
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
(PV
= SV
= 3V, PGND = SGND = 0, SHDNL = SHDNR = SV , C1 = C2 = 2.2µF, R = R = 10kΩ, R = ∞, T = T
to T
,
MAX
DD
DD
DD
IN
F
L
A
MIN
unless otherwise noted. Typical values are at T = +25°C.) (Note 2)
A
PARAMETER
SYMBOL
CONDITIONS
Guaranteed by PSRR test
MIN
TYP
MAX
UNITS
Supply Voltage Range
V
1.8
3.6
V
DD
One channel enabled
Two channels enabled
SHDNL = SHDNR = GND
4
7
6
Quiescent Supply Current
Shutdown Supply Current
I
mA
µA
DD
11.5
10
I
SHDN
0.7 x
V
V
IH
IL
SV
DD
SHDN_ Thresholds
V
0.3 x
SV
DD
SHDN_ Input Leakage Current
SHDN_ to Full Operation
CHARGE PUMP
-1
+1
µA
µs
t
f
175
320
0.5
SON
OSC
Oscillator Frequency
AMPLIFIERS
272
368
kHz
Input Offset Voltage
Input Bias Current
V
Input AC-coupled, R = 32Ω
2.4
mV
nA
OS
L
I
-100
75
+100
BIAS
1.8V ≤ V
≤ 3.6V
DC
90
90
55
65
80
DD
Power-Supply Rejection Ratio
Output Power
PSRR
dB
f
f
= 1kHz
RIPPLE
RIPPLE
200mV
ripple
P-P
= 20kHz
R = 32Ω
L
P
THD + N = 1%
mW
OUT
R = 16Ω
L
40
2
_______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
ELECTRICAL CHARACTERISTICS (continued)
(PV
= SV
= 3V, PGND = SGND = 0, SHDNL = SHDNR = SV , C1 = C2 = 2.2µF, R = R = 10kΩ, R = ∞, T = T
to T
,
DD
DD
DD
IN
F
L
A
MIN
MAX
unless otherwise noted. Typical values are at T = +25°C.) (Note 2)
A
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
R = 32Ω,
L
0.003
P
= 25mW
OUT
Total Harmonic Distortion Plus
Noise
THD + N
f
= 1kHz
%
IN
R = 16Ω,
L
0.003
P
= 50mW
OUT
Signal-to-Noise Ratio
Slew Rate
SNR
SR
R = 32Ω, P
= 20mW, f = 1kHz
95
0.8
300
70
dB
V/µs
pF
L
OUT
IN
Maximum Capacitive Load
Crosstalk
C
No sustained oscillations
R = 16Ω, P = 1.6mW, f = 10kHz
L
dB
°C
L
OUT
IN
Thermal Shutdown Threshold
Thermal Shutdown Hysteresis
ESD Protection
140
15
°C
Human body model (OUTR, OUTL)
8
kV
Note 2: All specifications are 100% tested at T = +25°C; temperature limits are guaranteed by design.
A
Typical Operating Characteristics
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
TOTAL HARMONIC DISTORTION PLUS
TOTAL HARMONIC DISTORTION PLUS
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
NOISE vs. FREQUENCY
NOISE vs. FREQUENCY
MAX4410 toc01
MAX4410 toc02
1
0.1
1
0.1
1
V
A
= 3V
V
A
= 3V
DD
DD
V
A
= 3V
DD
V
R = 32Ω
= -1V/V
= -2V/V
V
V
= -1V/V
R = 16Ω
R = 16Ω
L
L
L
0.1
P
= 10mW
OUT
P
= 5mW
OUT
0.01
0.001
P
= 25mW
OUT
P
= 25mW
OUT
P
= 10mW
OUT
P
= 50mW
OUT
10k
0.01
0.001
0.01
0.001
P
= 10mW
100
OUT
P
= 25mW
OUT
1k
P
= 50mW
OUT
1k
0.0001
10
1k
FREQUENCY (Hz)
100k
10
100
10k
100k
10
100
10k
100k
FREQUENCY (Hz)
FREQUENCY (Hz)
_______________________________________________________________________________________
3
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
TOTAL HARMONIC DISTORTION PLUS
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
NOISE vs. FREQUENCY
MAX4410 toc05
1
0.1
1
0.1
1
0.1
V
A
L
= 1.8V
V
A
= 1.8V
DD
V
R = 16Ω
L
V
A
= 3V
DD
DD
= -1V/V
= -2V/V
= -2V/V
V
V
R = 16Ω
R = 32Ω
L
P
OUT
= 5mW
P
= 5mW
OUT
P
= 5mW
OUT
P
= 10mW
OUT
P
= 10mW
P
OUT
0.01
0.001
0.01
0.001
0.01
0.001
P
= 10mW
100
OUT
P
= 20mW
= 20mW
OUT
P
= 25mW
OUT
OUT
10
100
1k
FREQUENCY (Hz)
10k
100k
10
100
1k
FREQUENCY (Hz)
10k
100k
10
1k
FREQUENCY (Hz)
10k
100k
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. FREQUENCY
1
0.1
1
100
10
1
V
A
= 1.8V
V
A
= 3V
DD
V
V
A
= 1.8V
DD
DD
= -2V/V
= -1V/V
= -1V/V
V
V
R = 32Ω
R = 16Ω
R = 32Ω
L
L
L
f
= 20Hz
IN
0.1
0.01
P
= 20mW
OUT
OUTPUTS
180° OUT OF
PHASE
P
= 5mW
OUT
OUTPUTS IN
PHASE
P
= 10mW
OUT
0.1
0.01
0.001
P
= 5mW
OUT
P
= 10mW
OUT
100
0.01
ONE
CHANNEL
P
= 20mW
OUT
1k
0.001
0.001
10
10k
100k
10
100
1k
FREQUENCY (Hz)
10k
100k
0
50
100
150
200
FREQUENCY (Hz)
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
10
1
100
100
10
1
V
A
= 3V
V
A
= 3V
V
A
= 3V
DD
V
DD
DD
= -2V/V
= -1V/V
= -1V/V
V
V
R = 16Ω
= 20Hz
R = 16Ω
= 1kHz
R = 16Ω
L
10
1
L
L
f
IN
f
f
IN
= 10kHz
IN
OUTPUTS
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
180° OUT OF
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
PHASE
OUTPUTS IN
PHASE
0.1
0.1
0.1
0.01
ONE
CHANNEL
0.01
0.01
ONE
CHANNEL
ONE
CHANNEL
0.001
0.001
0.001
0
50
100
150
200
0
50
100
150
200
0
50
100
150
200
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
4
_______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
10
1
100
10
1
100
10
OUTPUTS IN
PHASE
= -1V/V
V
L
V
A
= 3V
V
A
= 3V
V
A
= 3V
DD
DD
DD
= -2V/V
= -2V/V
V
V
R = 16Ω
= 1kHz
R = 16Ω
= 10kHz
R = 32Ω
L
L
f
IN
f
f = 20Hz
IN
IN
1
ONE
CHANNEL
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
0.1
OUTPUTS
180° OUT OF
PHASE
0.1
0.1
OUTPUTS
180° OUT OF
PHASE
0.01
0.001
0.0001
0.01
0.01
ONE
CHANNEL
ONE
CHANNEL
0.001
0.001
0
50
100
150
200
0
50
100
150
200
0
25
50
75
100
125
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
10
1
100
10
1
100
10
1
V
A
= 3V
V
A
= 3V
DD
V
A
= 3V
DD
OUTPUTS IN
PHASE
DD
OUTPUTS IN
PHASE
OUTPUTS IN
PHASE
= -1V/V
= -1V/V
V
= -1V/V
V
V
R = 32Ω
= 20Hz
R = 32Ω
= 1kHz
L
R = 32Ω
= 10kHz
L
L
f
IN
f
IN
f
IN
OUTPUTS
180° OUT OF
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.1
0.1
ONE
CHANNEL
ONE
CHANNEL
ONE
CHANNEL
0.01
0.01
0.01
0.001
0.001
0.001
0
25
50
75
100
125
0
25
50
75
100
125
0
25
50
75
100
125
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
10
1
100
10
1
100
10
1
V
A
= 3V
OUTPUTS IN
PHASE
V
A
= 3V
V
A
= 1.8V
DD
V
R = 16Ω
L
DD
DD
OUTPUTS IN
PHASE
OUTPUTS IN
PHASE
= -2V/V
= -2V/V
= -1V/V
V
V
R = 32Ω
= 1kHz
R = 32Ω
= 10kHz
L
L
f
IN
f
IN
f = 20Hz
IN
OUTPUTS
OUTPUTS
180° OUT OF
OUTPUTS
180° OUT OF
PHASE
ONE
CHANNEL
0.1
180° OUT OF
0.1
0.1
PHASE
PHASE
ONE
CHANNEL
0.01
0.01
0.01
ONE
CHANNEL
0.001
0.001
0.001
0
25
50
75
100
125
0
25
50
75
100
125
0
10
20
30
40
50
60
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
_______________________________________________________________________________________
5
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
10
1
100
10
1
100
10
1
V
A
= 1.8V
V
A
= 1.8V
OUTPUTS IN
PHASE
V
A
= 1.8V
DD
V
R = 16Ω
L
DD
DD
= -1V/V
= -1V/V
= -2V/V
V
V
R = 16Ω
= 10kHz
R = 16Ω
= 1kHz
L
L
f
f
IN
f = 20Hz
IN
IN
OUTPUTS IN
PHASE
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.1
0.1
ONE
CHANNEL
ONE
CHANNEL
0.01
0.01
0.01
ONE
CHANNEL
0.001
0.001
0.001
0
10
20
30
40
50
60
0
10
20
30
40
50
60
0
10
20
30
40
50
60
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
10
1
100
10
1
100
10
1
V
A
= 1.8V
V
A
= 1.8V
V
A
= 1.8V
DD
V
R = 32Ω
L
DD
DD
= -2V/V
= -2V/V
= -1V/V
V
V
R = 16Ω
= 1kHz
R = 16Ω
= 10kHz
L
L
f
IN
f
f = 20Hz
IN
IN
OUTPUTS IN
PHASE
OUTPUTS IN
PHASE
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.1
0.1
ONE
CHANNEL
0.01
0.01
0.01
ONE
ONE
CHANNEL
CHANNEL
0.001
0.001
0.001
0
10
20
30
40
50
60
0
10
20
30
40
50
60
0
10
20
30
40
50
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
100
10
1
100
10
1
100
10
1
V
A
= 1.8V
V
A
= 1.8V
V
A
= 1.8V
DD
V
R = 32Ω
L
DD
DD
= -2V/V
= -1V/V
= -1V/V
V
V
R = 32Ω
= 20Hz
R = 32Ω
= 1kHz
L
L
f
f
IN
f
= 10kHz
IN
IN
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.1
0.1
ONE
CHANNEL
0.01
0.01
0.01
ONE
CHANNEL
ONE
CHANNEL
0.001
0.001
0.001
0
10
20
30
40
50
0
10
20
30
40
50
0
10
20
30
40
50
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
6
_______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
TOTAL HARMONIC DISTORTION PLUS
NOISE vs. OUTPUT POWER
0
100
10
1
100
10
1
V
R
= 3V
DD
= 16Ω
V
A
= 1.8V
V
A
= 1.8V
DD
DD
= -2V/V
= -2V/V
L
V
V
R = 32Ω
= 10kHz
-20
R = 32Ω
= 1kHz
L
L
f
f
IN
IN
OUTPUTS IN
PHASE
-40
-60
OUTPUTS
180° OUT OF
PHASE
OUTPUTS IN
PHASE
OUTPUTS
180° OUT OF
PHASE
0.1
0.1
ONE
CHANNEL
-80
ONE
CHANNEL
0.01
0.01
0.001
-100
0.001
0.01
0.1
1
10
100
0
10
20
30
40
50
0
10
20
30
40
50
FREQUENCY (kHz)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
POWER-SUPPLY REJECTION RATIO
vs. FREQUENCY
0
0
0
V
= 3V
V
= 1.8V
V
= 1.8V
DD
DD
= 32Ω
DD
= 16Ω
R
R
L
R = 32Ω
L
L
-20
-20
-40
-60
-20
-40
-60
-40
-60
-80
-80
-80
-100
-100
-100
0.01
0.1
1
10
100
0.01
0.1
1
10
100
0.01
0.1
1
10
100
FREQUENCY (kHz)
FREQUENCY (kHz)
FREQUENCY (kHz)
CROSSTALK vs. FREQUENCY
OUTPUT POWER vs. SUPPLY VOLTAGE
OUTPUT POWER vs. SUPPLY VOLTAGE
0
-20
200
180
160
140
120
100
80
300
V
P
= 3V
f
= 1kHz
f
= 1kHz
IN
L
DD
IN
= 1.6mW
INPUTS 180°
OUT OF PHASE
R
L
= 16Ω
R
= 16Ω
OUT
250
200
150
100
50
INPUTS 180°
OUT OF PHASE
R = 16Ω
THD + N = 1%
THD + N = 10%
L
-40
-60
60
LEFT TO RIGHT
RIGHT TO LEFT
INPUTS
IN PHASE
INPUTS
IN PHASE
-80
40
20
-100
0
0
0.01
0.1
1
10
100
1.8
2.1
2.4
2.7
3.0
3.3
3.6
1.8
2.1
2.4
2.7
3.0
3.3
3.6
FREQUENCY (Hz)
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
_______________________________________________________________________________________
7
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
OUTPUT POWER vs. SUPPLY VOLTAGE
OUTPUT POWER vs. SUPPLY VOLTAGE
OUTPUT POWER vs. LOAD RESISTANCE
140
180
160
140
120
100
80
160
140
120
100
80
f
= 1kHz
f
= 1kHz
IN
L
IN
V
IN
= 3V
DD
= 1kHz
R
L
= 32Ω
R
= 32Ω
120
100
f
INPUTS 180°
THD + N = 10%
INPUTS 180°
OUT OF PHASE
THD + N = 1%
THD + N = 1%
OUT OF PHASE
80
60
40
20
0
INPUTS 180°
OUT OF PHASE
INPUTS
IN PHASE
60
60
40
20
0
INPUTS
IN PHASE
40
20
0
INPUTS
IN PHASE
1.8
2.1
2.4
2.7
3.0
3.3
3.6
1.8
2.1
2.4
2.7
3.0
3.3
3.6
10
100
1k
10k
100k
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
LOAD RESISTANCE (Ω)
OUTPUT POWER vs. LOAD RESISTANCE
OUTPUT POWER vs. LOAD RESISTANCE
OUTPUT POWER vs. LOAD RESISTANCE
45
40
35
30
25
20
15
10
5
70
60
50
40
30
20
10
0
250
200
150
V
IN
= 3V
V
= 1.8V
= 1kHz
V
= 1.8V
f = 1kHz
IN
DD
= 1kHz
DD
DD
f
f
IN
INPUTS 180°
OUT OF PHASE
INPUTS 180°
OUT OF PHASE
THD + N = 10%
THD + N = 1%
THD + N = 10%
INPUTS IN
PHASE
INPUTS IN
PHASE
INPUTS 180°
OUT OF PHASE
100
50
0
INPUTS
IN PHASE
0
10
100
1k
10k
100k
10
100
1k
10k
100k
10
100
1k
10k
100k
LOAD RESISTANCE (Ω)
LOAD RESISTANCE (Ω)
LOAD RESISTANCE (Ω)
POWER DISSIPATION
vs. OUTPUT POWER
POWER DISSIPATION
vs. OUTPUT POWER
POWER DISSIPATION
vs. OUTPUT POWER
180
160
140
120
100
400
350
300
250
200
150
100
50
INPUTS
IN PHASE
INPUTS
IN PHASE
INPUTS
IN PHASE
f
= 1kHz
= 16Ω
= 1.8V
f
= 1kHz
= 16Ω
= 3V
IN
L
DD
OUT
IN
L
DD
OUT
R
V
R
V
140
120
100
80
P
= P
+ P
P
= P
+ P
OUTR
OUTL OUTR
OUTL
INPUTS 180°
OUT OF PHASE
INPUTS 180°
OUT OF PHASE
80
60
40
20
0
INPUTS 180°
OUT OF PHASE
60
40
20
0
f
= 1kHz
= 32Ω
IN
R
L
V
P
= 3V
DD
OUT
= P
+ P
OUTR
OUTL
0
0
40
80
120
160
200
0
10
20
30
40
50
60
0
40
80
120
160
200
OUTPUT POWER (mW)
OUTPUT POWER (mW)
OUTPUT POWER (mW)
8
_______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
POWER DISSIPATION
vs. OUTPUT POWER
GAIN AND PHASE vs. FREQUENCY
70
60
50
80
60
40
20
0
INPUTS
IN PHASE
GAIN
INPUTS 180°
-20
-40
-60
-80
-100
-120
-140
-160
-180
40
30
20
10
0
OUT OF PHASE
PHASE
f
= 1kHz
= 32Ω
= 1.8V
IN
L
DD
R
V
V
A
= 3V
DD
= 1000V/V
V
R
P
= P
+ P
OUT
OUTL OUTR
= 16Ω
L
0
10
20
30
40
50
60
100
10k
100k
1M
10M
1k
OUTPUT POWER (mW)
FREQUENCY (Hz)
CHARGE-PUMP OUTPUT RESISTANCE
vs. SUPPLY VOLTAGE
GAIN FLATNESS vs. FREQUENCY
10
10
V
PVSS
NO LOAD
= GND
IN_
0
-10
-20
I
= 10mA
8
6
4
2
0
-30
-40
-50
V
A
L
= 3V
DD
= -1V/V
V
R = 16Ω
100
10
1k
10k 100k 1M
10M
1.8
2.1
2.4
2.7
3.0
3.3
3.6
FREQUENCY (Hz)
SUPPLY VOLTAGE (V)
OUTPUT POWER vs. CHARGE-PUMP
CAPACITANCE AND LOAD RESISTANCE
OUTPUT SPECTRUM vs. FREQUENCY
90
80
70
60
50
0
-20
C1 = C2 = 2.2µF
C1 = C2 = 1µF
V
IN
R
A
= 1V
P-P
IN
f
= 1kHz
= 32Ω
= -1V/V
L
V
-40
C1 = C2 = 0.68µF
C1 = C2 = 0.47µF
-60
40
30
20
10
0
-80
f
= 1kHz
IN
-100
-120
THD + N = 1%
INPUTS IN PHASE
10
20
30
40
50
0.1
1
10
100
LOAD RESISTANCE (Ω)
FREQUENCY (kHz)
_______________________________________________________________________________________
9
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Operating Characteristics (continued)
(C1 = C2 = 2.2µF, THD + N measurement bandwidth = 22Hz to 22kHz, T = +25°C, unless otherwise noted.)
A
SHUTDOWN SUPPLY CURRENT
vs. SUPPLY VOLTAGE
SUPPLY CURRENT vs. SUPPLY VOLTAGE
10
10
SHDNL = SHDNR = GND
8
6
4
2
0
8
6
4
2
0
0
0.9
1.8
2.7
3.6
0
0.9
1.8
2.7
3.6
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
POWER-UP/DOWN WAVEFORM
EXITING SHUTDOWN
MAX4410 toc58
MAX4410 toc57
3V
0V
2V/div
V
DD
SHDNR
OUTR
OUT_
10mV/div
20dB/div
-100dB
500mV/div
OUT_FFT
200ms/div
FFT: 25Hz/div
200µs/div
f
= 1kHz
IN
R = 32Ω
IN_
R = 32Ω
SHDNL = GND
L
L
V
= GND
10 ______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Pin Description
PIN
BUMP
NAME
FUNCTION
TSSOP
UCSP
1
B2
SHDNL
Active-Low, Left-Channel Shutdown. Connect to V for normal operation.
DD
Charge-Pump Power Supply. Powers charge-pump inverter, charge-pump logic, and
oscillator.
2
A3
PV
DD
3
4
A4
B4
C4
D4
D3
D2
D1
C1
C2
B1
A1
A2
C1P
PGND
C1N
Flying Capacitor Positive Terminal
Power Ground. Connect to SGND.
Flying Capacitor Negative Terminal
Charge-Pump Output
5
6
PV
SS
SS
7
SV
Amplifier Negative Power Supply. Connect to PV
.
SS
8
OUTL
SV
Left-Channel Output
9
Amplifier Positive Power Supply. Connect to PV
.
DD
DD
10
11
12
13
14
INL
Left-Channel Audio Input
OUTR
SHDNR
INR
Right-Channel Output
Active-Low, Right-Channel Shutdown. Connect to V
Right-Channel Audio Input
for normal operation.
DD
SGND
Signal Ground. Connect to PGND.
______________________________________________________________________________________ 11
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Detailed Description
The MAX4410 stereo headphone driver features Maxim’s
patented DirectDrive architecture, eliminating the large
output-coupling capacitors required by traditional single-
supply headphone drivers. The device consists of two
80mW Class AB headphone drivers, undervoltage lock-
out (UVLO)/shutdown control, charge-pump, and com-
prehensive click-and-pop suppression circuitry (see
Typical Application Circuit). The charge pump inverts the
V
DD
V
/2
V
DD
OUT
positive supply (PV ), creating a negative supply
DD
(PV ). The headphone drivers operate from these bipo-
SS
GND
lar supplies with their outputs biased about GND (Figure
1). The drivers have almost twice the supply range com-
pared to other 3V single-supply drivers, increasing the
available output power. The benefit of this GND bias is
that the driver outputs do not have a DC component typi-
CONVENTIONAL DRIVER-BIASING SCHEME
cally V /2. Thus, the large DC-blocking capacitors are
DD
+V
DD
unnecessary, improving frequency response while con-
serving board space and system cost.
Each channel has independent left/right, active-low
shutdown controls, making it possible to optimize
power savings in mixed-mode, mono/stereo operation.
The device features an undervoltage lockout that pre-
vents operation from an insufficient power supply and
click-and-pop suppression that eliminates audible tran-
sients on startup and shutdown. Additionally, the
MAX4410 features thermal overload and short-circuit
protection and can withstand 8kV ESD strikes on the
output pins.
V
GND
-V
OUT
DD
DirectDrive BIASING SCHEME
Figure 1. Traditional Driver Output Waveform vs. MAX4410
Output Waveform
DirectDrive
Traditional single-supply headphone drivers have their
outputs biased about a nominal DC voltage (typically
half the supply) for maximum dynamic range. Large
coupling capacitors are needed to block this DC bias
from the headphone. Without these capacitors, a signif-
icant amount of DC current flows to the headphone,
resulting in unnecessary power dissipation and possi-
ble damage to both headphone and headphone driver.
details of the possible capacitor sizes. There is a low
DC voltage on the driver outputs due to amplifier offset.
However, the offset of the MAX4410 is typically 0.5mV,
which, when combined with a 32Ω load, results in less
than 16µA of DC current flow to the headphones.
Previous attempts to eliminate the output-coupling capac-
itors involved biasing the headphone return (sleeve) to
the DC-bias voltage of the headphone amplifiers. This
method raises some issues:
Maxim’s patented DirectDrive architecture uses a
charge pump to create an internal negative supply volt-
age. This allows the outputs of the MAX4410 to be
biased about GND, almost doubling dynamic range
while operating from a single supply. With no DC com-
ponent, there is no need for the large DC-blocking
capacitors. Instead of two large (220µF, typ) tantalum
capacitors, the MAX4410 charge pump requires two
small ceramic capacitors, conserving board space,
reducing cost, and improving the frequency response
of the headphone driver. See the Output Power vs.
Charge-Pump Capacitance and Load Resistance
graph in the Typical Operating Characteristics for
1) When combining a microphone and headphone on
a single connector, the microphone bias scheme
typically requires a 0V reference.
2) The sleeve is typically grounded to the chassis.
Using this biasing approach, the sleeve must be
isolated from system ground, complicating product
design.
3) During an ESD strike, the driver’s ESD structures
are the only path to system ground. Thus, the driver
must be able to withstand the full ESD strike.
12 ______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
4) When using the headphone jack as a line out to other
equipment, the bias voltage on the sleeve may con-
flict with the ground potential from other equipment,
resulting in possible damage to the drivers.
Charge Pump
The MAX4410 features a low-noise charge pump. The
320kHz switching frequency is well beyond the audio
range, and thus does not interfere with the audio sig-
nals. The switch drivers feature a controlled switching
speed that minimizes noise generated by turn-on and
turn-off transients. By limiting the switching speed of the
switches, the di/dt noise caused by the parasitic bond
wire and trace inductance is minimized. Although not
typically required, additional high-frequency noise atten-
uation can be achieved by increasing the size of C2
(see Typical Application Circuit).
Low-Frequency Response
In addition to the cost and size disadvantages of the DC-
blocking capacitors required by conventional head-
phone amplifiers, these capacitors limit the amplifier’s
low-frequency response and can distort the audio signal.
1) The impedance of the headphone load and the DC-
blocking capacitor form a highpass filter with the
-3dB point set by:
LF ROLL OFF (16Ω LOAD)
1
f
=
−3dB
0
2πR C
L
OUT
-3
-5
330µF
where R is the headphone impedance and C
is
220µF
100µF
L
OUT
-10
-15
the DC-blocking capacitor value. The highpass filter
is required by conventional single-ended, single
power-supply headphone drivers to block the midrail
DC bias component of the audio signal from the
headphones. The drawback to the filter is that it can
attenuate low-frequency signals. Larger values of
-3dB CORNER FOR
100µF IS 100Hz
33µF
-20
-25
-30
C
OUT
reduce this effect but result in physically larg-
er, more expensive capacitors. Figure 2 shows the
relationship between the size of C and the result-
ing low-frequency attenuation. Note that the -3dB
point for a 16Ω headphone with a 100µF blocking
capacitor is 100Hz, well within the normal audio
band, resulting in low-frequency attenuation of the
reproduced signal.
-35
OUT
10
100
FREQUENCY (Hz)
1k
Figure 2. Low-Frequency Attenuation for Common DC-Blocking
Capacitor Values
2) The voltage coefficient of the DC-blocking capacitor
contributes distortion to the reproduced audio signal
as the capacitance value varies as a function of the
voltage change across the capacitor. At low fre-
quencies, the reactance of the capacitor dominates
at frequencies below the -3dB point and the voltage
coefficient appears as frequency-dependent distor-
tion. Figure 3 shows the THD + N introduced by two
different capacitor dielectric types. Note that below
100Hz, THD + N increases rapidly.
ADDITIONAL THD + N DUE
TO DC-BLOCKING CAPACITORS
10
1
0.1
TANTALUM
0.01
The combination of low-frequency attenuation and fre-
quency-dependent distortion compromises audio
reproduction in portable audio equipment that empha-
sizes low-frequency effects such as multimedia lap-
tops, as well as MP3, CD, and DVD players. By
eliminating the DC-blocking capacitors through
DirectDrive technology, these capacitor-related defi-
ciencies are eliminated.
0.001
ALUM/ELEC
0.0001
10
100
1k
10k
100k
FREQUENCY (Hz)
Figure 3. Distortion Contributed by DC-Blocking Capacitors
______________________________________________________________________________________ 13
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
°C/W as specified in the Absolute Maximum Ratings
Shutdown
The MAX4410 features two shutdown controls allowing
either channel to be shut down or muted independently.
SHDNL controls the left channel while SHDNR controls
the right channel. Driving either SHDN_ low disables the
respective channel, sets the driver output impedance to
about 1kΩ, and reduces the supply current to less than
10µA. When both SHDN_ inputs are driven low, the
charge pump is also disabled, further reducing supply
current draw to 6µA. The charge pump is enabled once
either SHDN_ input is driven high.
section. For example, θ
of the TSSOP package is
JA
+109.9°C/W.
The MAX4410 has two sources of power dissipation,
the charge pump and the two drivers. If the power dis-
sipation for a given application exceeds the maximum
allowed for a given package, either reduce V
,
DD
increase load impedance, decrease the ambient tem-
perature, or add heat sinking to the device. Large out-
put, supply, and ground traces improve the maximum
power dissipation in the package.
Click-and-Pop Suppression
In traditional single-supply audio drivers, the output-
coupling capacitor is a major contributor of audible
clicks and pops. Upon startup, the driver charges the
coupling capacitor to its bias voltage, typically half the
supply. Likewise, on shutdown the capacitor is dis-
charged to GND. This results in a DC shift across the
capacitor, which in turn, appears as an audible transient
at the speaker. Since the MAX4410 does not require
output-coupling capacitors, this does not arise.
Thermal overload protection limits total power dissipa-
tion in the MAX4410. When the junction temperature
exceeds +140°C, the thermal protection circuitry dis-
ables the amplifier output stage. The amplifiers are
enabled once the junction temperature cools by 15°C.
This results in a pulsing output under continuous ther-
mal overload conditions.
Output Power
The device has been specified for the worst-case sce-
nario— when both inputs are in phase. Under this con-
dition, the drivers simultaneously draw current from the
charge pump, leading to a slight loss in headroom of
Additionally, the MAX4410 features extensive click-and-
pop suppression that eliminates any audible transient
sources internal to the device. The Power-Up/Down
Waveform in the Typical Operating Characteristics
shows that there are minimal spectral components in the
audible range at the output upon startup or shutdown.
V
. In typical stereo audio applications, the left and
SS
right signals have differences in both magnitude and
phase, subsequently leading to an increase in the max-
imum attainable output power. Figure 4 shows the two
extreme cases for in and out of phase. In reality, the
available power lies between these extremes.
In most applications, the output of the preamplifier dri-
ving the MAX4410 has a DC bias of typically half the
supply. At startup, the input-coupling capacitor is
charged to the preamplifier’s DC-bias voltage through
the R of the MAX4410, resulting in a DC shift across
F
TOTAL HARMONIC DISTORTION PLUS
the capacitor and an audible click/pop. Delaying the
NOISE vs. OUTPUT POWER
rise of the MAX4410’s SHDN_ signals 4 to 5 time con-
100
V
A
= 3V
DD
stants (200ms to 300ms) based on R and C relative
IN
IN
= -1V/V
V
to the start of the preamplifier eliminates this click/pop
caused by the input filter.
R = 16Ω
= 10kHz
10
1
L
f
IN
Applications Information
OUTPUTS IN
PHASE
Power Dissipation
Under normal operating conditions, linear power ampli-
fiers can dissipate a significant amount of power. The
maximum power dissipation for each package is given
in the Absolute Maximum Ratings section under
Continuous Power Dissipation or can be calculated by
the following equation:
OUTPUTS
180° OUT OF
PHASE
0.1
0.01
ONE
CHANNEL
0.001
0
50
100
150
200
OUTPUT POWER (mW)
T
− T
A
J(MAX)
P
=
DISSPKG(MAX)
θ
JA
Figure 4. Output Power vs. Supply Voltage with Inputs In/Out
of Phase
where T
is +150°C, T is the ambient tempera-
A
J(MAX)
ture, and θ is the reciprocal of the derating factor in
JA
14 ______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
an optimum DC level. Assuming zero-source impedance,
the -3dB point of the highpass filter is given by:
Powering Other Circuits from a
Negative Supply
An additional benefit of the MAX4410 is the internally
1
f
=
generated, negative supply voltage (-V ). This voltage
DD
−3dB
2πR C
IN IN
is used by the MAX4410 to provide the ground-refer-
enced output level. It can, however, also be used to
power other devices within a design. Current draw from
Choose R according to the Gain-Setting Resistors sec-
IN
tion. Choose the C such that f
lowest frequency of interest. Setting f
is well below the
-3dB
IN
this negative supply (PV ) should be limited to 5mA,
SS
exceeding this will affect the operation of the head-
phone driver. The negative supply voltage appears on
the PV pin. A typical application is a negative supply
SS
to adjust the contrast of LCD modules.
too high affects
-3dB
the low-frequency response of the amplifier. Use capaci-
tors whose dielectrics have low-voltage coefficients,
such as tantalum or aluminum electrolytic. Capacitors
with high-voltage coefficients, such as ceramics, may
result in increased distortion at low frequencies.
When considering the use of PV in this manner, note
SS
Other considerations when designing the input filter
include the constraints of the overall system and the
actual frequency band of interest. Although high-fidelity
audio calls for a flat-gain response between 20Hz and
20kHz, portable voice-reproduction devices such as
cellular phones and two-way radios need only concen-
trate on the frequency range of the spoken human voice
(typically 300Hz to 3.5kHz). In addition, speakers used
in portable devices typically have a poor response
below 150Hz. Taking these two factors into considera-
tion, the input filter may not need to be designed for a
20Hz to 20kHz response, saving both board space and
cost due to the use of smaller capacitors.
that the charge-pump voltage at PV is roughly pro-
SS
portional to -V
and is not a regulated voltage. The
DD
charge-pump output impedance plot appears in the
Typical Operating Characteristics.
Component Selection
Gain-Setting Resistors
External feedback components set the gain of the
MAX4410. Resistors R and R (see Typical Application
F
IN
Circuit) set the gain of each amplifier as follows:
R
F
A
= −
V
R
IN
Charge-Pump Capacitor Selection
Use capacitors with an ESR less than 100mΩ for opti-
mum performance. Low-ESR ceramic capacitors mini-
mize the output resistance of the charge pump. For
best performance over the extended temperature
range, select capacitors with an X7R dielectric. Table 1
lists suggested manufacturers.
To minimize V , set R equal to 10kΩ. Values other
OS
F
OS
than 10kΩ increase V
due to the input bias current,
which in turn increases the amount of DC current flow
to the speaker.
Compensation Capacitor
The stability of the MAX4410 is affected by the value of
the feedback resistor (R ). The combination of R and
F
F
the input and parasitic trace capacitance introduces an
additional pole. Adding a capacitor in parallel with R
compensates for this pole. Under typical conditions
with proper layout, the device is stable without the
additional capacitor.
Flying Capacitor (C1)
The value of the flying capacitor (C1) affects the load
regulation and output resistance of the charge pump. A
C1 value that is too small degrades the device’s ability
to provide sufficient current drive, which leads to a loss
of output voltage. Increasing the value of C1 improves
load regulation and reduces the charge-pump output
resistance to an extent. See the Output Power vs.
Charge-Pump Capacitance and Load Resistance
graph in the Typical Operating Characteristics. Above
2.2µF, the on-resistance of the switches and the ESR of
C1 and C2 dominate.
F
Input Filtering
The input capacitor (C ), in conjunction with R forms a
IN
IN,
highpass filter that removes the DC bias from an incom-
ing signal (see Typical Application Circuit). The AC-cou-
pling capacitor allows the amplifier to bias the signal to
Table 1. Suggested Capacitor Manufacturers
SUPPLIER
Taiyo Yuden
TDK
PHONE
FAX
WEBSITE
www.t-yuden.com
www.component.tdk.com
800-348-2496
847-803-6100
847-925-0899
847-390-4405
Note: Please indicate you are using the MAX4410 when contacting these component suppliers.
______________________________________________________________________________________ 15
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Output Capacitor (C2)
Layout and Grounding
Proper layout and grounding are essential for optimum
performance. Connect PGND and SGND together at a
single point on the PC board. Connect all components
associated with the charge pump (C2 and C3) to the
The output capacitor value and ESR directly affect the
ripple at PV . Increasing the value of C2 reduces out-
SS
put ripple. Likewise, decreasing the ESR of C2
reduces both ripple and output resistance. Lower
capacitance values can be used in systems with low
maximum output power levels. See the Output Power
vs. Charge-Pump Capacitance and Load Resistance
graph in the Typical Operating Characteristics.
PGND plane. Connect PV
and SV
together at the
DD
DD
and SV
device. Connect PV
together at the
SS
SS
device. Bypassing of both supplies is accomplished
by charge-pump capacitors C2 and C3 (see Typical
Application Circuit). Place capacitors C2 and C3 as
close to the device as possible. Route PGND and all
traces that carry switching transients away from SGND
and the traces and components in the audio signal
path. Refer to the layout example in the MAX4410 EV
kit datasheet.
Power-Supply Bypass Capacitor
The power-supply bypass capacitor (C3) lowers the out-
put impedance of the power supply, and reduces the
impact of the MAX4410’s charge-pump switching tran-
sients. Bypass PV with C3, the same value as C1, and
DD
place it physically close to the PV
and PGND pins
DD
When using the MAX4410 in a UCSP package, make
sure the traces to OUTR (bump C2) are wide enough
to handle the maximum expected current flow. Multiple
traces may be necessary.
(refer to the MAX4410 EV kit for a suggested layout).
Adding Volume Control
The addition of a digital potentiometer provides simple
volume control. Figure 5 shows the MAX4410 with the
MAX5408 dual log taper digital potentiometer used as
an input attenuator. Connect the high terminal of the
MAX5408 to the audio input, the low terminal to ground
UCSP Considerations
For general UCSP information and PC layout consider-
ations, refer to the Maxim Application Note: Wafer-
Level Ultra Chip-Scale Package.
and the wiper to C . Setting the wiper to the top posi-
IN
tion passes the audio signal unattenuated. Setting the
wiper to the lowest position fully attenuates the input.
R
F
5
6
H0
L0
LEFT AUDIO
INPUT
C
IN
R
IN
10
W0A
7
8
INL
OUTL
MAX4410
MAX5408
RIGHT AUDIO
INPUT
H1
L1
12
C
IN
R
IN
13
11
10
W1A
INR
OUTR
11
R
F
Figure 5. MAX4410 and MAX5408 Volume Control Circuit
16 ______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Typical Application Circuit
C
IN
1µF
R
R
F
IN
10kΩ
1.8V to 3.6V
10kΩ
LEFT
CHANNEL
AUDIO IN
C3
2.2µF
9
(D1)
1
(B2)
12
(B1)
10
(C1)
2
(A3)
INL
PV
DD
SV
DD
SHDNL
SHDNR
SV
DD
8
(D2)
OUTL
SGND
HEADPHONE
JACK
UVLO/
SHUTDOWN
CONTROL
3
(A4)
C1P
SV
SS
CHARGE
PUMP
CLICK-AND-POP
SUPPRESSION
C1
2.2µF
5
(C4) C1N
SV
DD
SGND
11
(C2)
MAX4410
OUTR
SV
SS
PV
SV
7
SS
6
PGND
4
SGND
INR
SS
14
(A2)
13
(A1)
(D4)
C2
2.2µF
(D3) (B4)
C
IN
1µF
R
F
10kΩ
R
IN
10kΩ
RIGHT
CHANNEL
AUDIO IN
( ) DENOTE BUMPS FOR UCSP.
______________________________________________________________________________________ 17
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Pin Configurations
TOP VIEW
(BUMP SIDE
DOWN)
MAX4410
TOP VIEW
1
2
3
4
A
B
C
D
SHDNL
PV
1
2
3
4
5
6
7
14 SGND
13 INR
INR
SGND
SHDNL
OUTR
PV
C1P
DD
DD
C1P
PGND
C1N
12 SHDNR
11 OUTR
10 INL
PGND
C1N
SHDNR
INL
MAX4410
PV
SS
SV
SS
9
8
SV
DD
OUTL
SV
DD
OUTL
SV
SS
PV
SS
TSSOP
UCSP (B16-2)
Chip Information
TRANSISTOR COUNT: 4295
PROCESS: BiCMOS
18 ______________________________________________________________________________________
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information,
go to www.maxim-ic.com/packages.)
______________________________________________________________________________________ 19
80mW, DirectDrive Stereo Headphone Driver
with Shutdown
Package Information (continued)
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information,
go to www.maxim-ic.com/packages.)
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
20 ____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600
© 2002 Maxim Integrated Products
Printed USA
is a registered trademark of Maxim Integrated Products.
相关型号：
MAX4411BETP+T
Audio Amplifier, 0.08W, 2 Channel(s), 1 Func, BICMOS, 4 X 4 MM, 0.80 MM HEIGHT, QFN-20
MAXIM
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