AT9933LG-GVAO [MICROCHIP]
Switching Controller, PDSO8;
| 型号： | AT9933LG-GVAO |
| 厂家： | 
MICROCHIP |
| 描述： | Switching Controller, PDSO8 开关 光电二极管 |
| 文件： | 总16页 (文件大小：760K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
AT9933
Hysteretic Boost-Buck (Ćuk) LED Driver IC
Features
General Description
• Constant Current LED Driver
• Steps Input Voltage Up or Down
• Low Electromagnetic Interference (EMI)
• Variable Frequency Operation
• Internal 75V Linear Regulator
• Input and Output Current Sensing
• Input Current Limit
The AT9933 is a variable frequency PWM controller IC,
designed to control an LED lamp driver using a
low-noise boost-buck (Ćuk) topology. It uses
patent-pending Hysteretic Current-mode control to
regulate both the input and the output currents. This
enables superior input surge immunity without the
necessity for complex loop compensation. Input
current control enables current limiting during Startup,
Input Undervoltage and Output Overload conditions.
The AT9933 provides a low-frequency PWM dimming
input that can accept an external control signal with a
duty cycle of 0%–100% and a high dimming ratio.
• Enable and Pulse-width Modulation (PWM)
Dimming
• Ambient Temperature Rating of up to 125°C
This AT9933-based LED driver is ideal for LED lamps.
The part is rated for up to 125°C ambient temperatures.
Applications
• LED Lighting Applications
Package Type
8-lead SOIC
(Top View)
VIN 1
8 REF
7 CS2
CS1 2
GND 3
6 VDD
5 PWMD
GATE 4
See Table 2-1 for pin information.
2016 Microchip Technology Inc.
DS20005597A-page 1
AT9933
Functional Block Diagram
VIN
Regulator
VDD
7.5V
Input Comparator
CS1
100mV
GATE
0mV
CS2
REF
Output Comparator
1.25V
PWMD
GND
AT9933
DS20005597A-page 2
2016 Microchip Technology Inc.
AT9933
Typical Application Circuit
C1
D2 (optional)
L2
L1
-
VO
+
VDC
RD
CD
D3
D1
Q1
RCS1
RCS2
C2
RS1
VIN
VDD
RS2
GATE
CS1
PWMD
CS2
RREF1
RREF2
GND
REF
C3
AT9933
2016 Microchip Technology Inc.
DS20005597A-page 3
AT9933
1.0
ELECTRICAL CHARACTERISTICS
Absolute Maximum Ratings†
VIN to GND ................................................................................................................................................–0.5V to +75V
CS1, CS2, PWMD and GATE to GND ............................................................................................. –0.3V to VDD +0.3V
VDD(MAX) .................................................................................................................................................................+12V
Operating Temperature Range............................................................................................................. –40°C to +125°C
Junction Temperature.......................................................................................................................................... +150°C
Storage Temperature Range ............................................................................................................... –65°C to +150°C
Continuous Power Dissipation (TA = +25°C):
8-lead SOIC ............................................................................................................................................ 700 mW
† Notice: Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the
device. This is a stress rating only, and functional operation of the device at those or any other conditions above those
indicated in the operational sections of this specification is not intended. Exposure to maximum rating conditions for
extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
Electrical Specifications: Specifications are at TA = 25°C, VIN = Open and VDD = 7.5V unless otherwise noted.
Parameter
Sym.
Min.
Typ. Max. Unit
Conditions
INPUT
DC input voltage
(Note 1 and Note 2)
Input DC Supply Voltage Range
VINDC
IINSD
Note 3
—
75
1
V
PWMD connected to GND,
VIN = 12V (Note 2)
Shutdown Mode Supply Current
—
0.5
mA
INTERNAL REGULATOR
VIN = 8V–75V, IDD(EXT) = 0,
500 pF capacitor at GATE,
PWMD = GND (Note 1)
Internally Regulated Voltage
VDD
7
7.5
9
V
VDD Undervoltage Lockout
Threshold
UVLO
6.35
—
6.7
7.05
—
V
VDD rising (Note 1)
V
DD Undervoltage Lock-out
∆UVLO
500
mV
Hysteresis
REFERENCE
REF Pin Voltage
0°C < TA < +85°C
REF bypassed with a 0.1 µF
capacitor to GND, IREF = 0,
PWMD = 5V
1.212
1.187
1.25 1.288
1.25 1.312
VREF
V
REF Pin Voltage
–40°C < TA < +125°C
REF bypassed with a 0.1 µF capac-
mV itor to GND, IREF = 0,
VDD = 7V–9V, PWMD = 5V
Line Regulation of Reference
Voltage
VREFLINE
0
–0.01
0
—
—
—
20
500
10
REF bypassed with a 0.1 µF capac-
µA itor to GND, IREF = 0, VDD = 7V–9V,
PWMD = 5V
Reference Output Current Range
IREF
REF bypassed with a 0.1 µF capac-
mV itor to GND, IREF = 0 µA–500 µA,
PWMD = 5V
Load Regulation of Reference
Voltage
VREFLOAD
PWM DIMMING
PWMD Input Low Voltage
PWMD Input High Voltage
VPWMD(LO)
VPWMD(HI)
—
2
—
—
0.8
—
V
V
VDD = 7V–9V (Note 1)
VDD = 7V–9V (Note 1)
Note 1: Specifications apply over the full operating ambient temperature range of –40ºC < TA < +125ºC.
2: Also limited by package power dissipation limit, whichever is lower
3: Depends on the current drawn by the part. See Section 4.0 “Application Information”
DS20005597A-page 4
2016 Microchip Technology Inc.
AT9933
ELECTRICAL CHARACTERISTICS (CONTINUED)
Electrical Specifications: Specifications are at TA = 25°C, VIN = Open and VDD = 7.5V unless otherwise noted.
Parameter
Sym.
Min.
Typ. Max. Unit
Conditions
PWMD Pull-down Resistance
GATE DRIVER
RPWMD
50
100
150
kΩ VPWMD = 5V
GATE Short Circuit Current
GATE Sinking Current
GATE Output Rise Time
GATE Output Fall Time
ISOURCE
ISINK
0.165
0.165
—
—
—
30
30
—
—
50
50
A
A
VGATE = 0V
VGATE = VDD
TRISE
TFALL
ns
ns
CGATE = 500 pF
CGATE = 500 pF
—
INPUT CURRENT SENSE COMPARATOR
CS2 = 200 mV, CS1 increasing,
GATE goes LOW to HIGH (Note 1)
Voltage required to turn on GATE VTURNON1
85
–15
—
100
0
115
15
mV
mV
ns
VTURN-
CS2 = 200 mV, CS1 decreasing,
GATE goes HIGH to LOW (Note 1)
Voltage required to turn off GATE
OFF1
CS2 = 200 mV,
CS1 = 50 mV to +200 mV step
Delay to Output (Turn-on)
Delay to Output (Turn-off)
TD1,ON
150
150
250
250
CS2 = 200 mV,
CS1 = 50 mV to –100 mV step
TD1,OFF
—
ns
OUTPUT CURRENT SENSE COMPARATOR
CS1 = 200 mV, CS2 increasing,
GATE goes LOW to HIGH (Note 1)
Voltage required to turn on GATE VTURNON2
85
–15
—
100
0
115
15
mV
mV
ns
VTURN-
CS1 = 200 mV, CS2 decreasing,
GATE goes HIGH to LOW (Note 1)
Voltage required to turn off GATE
OFF2
CS1 = 200 mV,
CS2 = 50 mV to +200 mV step
Delay to Output (Turn-on)
Delay to Output (Turn-off)
TD2,ON
150
150
250
250
CS1 = 200 mV,
CS2 = 50 mV to –100 mV step
TD2,OFF
—
ns
Note 1: Specifications apply over the full operating ambient temperature range of –40ºC < TA < +125ºC.
2: Also limited by package power dissipation limit, whichever is lower
3: Depends on the current drawn by the part. See Section 4.0 “Application Information”
TEMPERATURE SPECIFICATIONS
Parameter
Sym.
Min.
Typ.
Max. Unit
Conditions
TEMPERATURE RANGE
Operating Temperature
Junction Temperature
Storage Temperature
TA
TJ
TS
–40
—
—
—
—
+125
+150
+150
°C
°C
°C
–65
PACKAGE THERMAL RESISTANCE
8-lead SOIC
JA
—
+101
—
°C/W Note 1
Note 1: Mounted on a FR-4 board, 25 mm x 25 mm x 1.57 mm
2016 Microchip Technology Inc.
DS20005597A-page 5
AT9933
2.0
PIN DESCRIPTION
The details on the pins of AT9933 are listed on
Table 2-1. Refer to Package Type for the location of
the pins.
TABLE 2-1:
PIN FUNCTION TABLE
Pin Number Pin Name
Description
1
2
VIN
This pin is the input of an 8V–75V voltage regulator.
This pin is used to sense the input and output currents of the boost-buck converter. It is
a non-inverting input of the internal comparator.
CS1
This is the ground return for all the internal circuitry. This pin must be electrically
connected to the ground of the power train.
3
4
5
6
7
8
GND
GATE
PWMD
VDD
This pin is the output gate driver for an external N-channel power Metal-oxide
Semiconductor Field-effect Transistor (MOSFET).
When this pin is left open or pulled to GND, the gate driver is disabled. Pulling the pin to
a voltage greater than 2V will enable the gate driver output.
This is a power supply pin for all internal circuits. It must be bypassed to GND with a
low-ESR capacitor greater than 0.1 µF.
This pin is used to sense the input and output currents of the boost-buck converter. It is
a non-inverting input of the internal comparator.
CS2
This pin provides accurate reference voltage. It must be bypassed with a
0.01 µF–0.1 µF capacitor to GND.
REF
DS20005597A-page 6
2016 Microchip Technology Inc.
AT9933
the VDD is greater than the undervoltage lockout. Thus,
under certain conditions, the converter will be able to
start at VIN voltages of less than 8V. The start/stop
voltages at the VIN pin can be determined using the
maximum voltage drop across the linear regulator as a
function of the current drawn. The data for ambient
temperatures 25ºC and 125ºC are shown in Figure 3-1
below:
3.0
3.1
DETAILED DESCRIPTION
Power Topology
The AT9933 is optimized to drive a Continuous
Conduction Mode (CCM) boost-buck DC/DC converter
topology commonly referred to as Ćuk converter.
(Refer to Typical Application Circuit.) This power
converter topology offers numerous advantages useful
for driving high-brightness light-emitting diodes (HB
LED). These advantages include step-up or step-down
voltage conversion ratio and low input and output
current ripple. The output load is decoupled from the
input voltage with a capacitor, making the driver
inherently failure-safe for the output load.
3.5
3.0
2.5
2.0
125OC
1.5
1.0
25OC
The AT9933 offers a simple and effective control
technique for a boost-buck LED driver. It uses two
Hysteretic mode controllers—one for the input and one
for the output. The outputs of these two hysteretic
comparators are ANDED and used to drive the external
FET. This control scheme gives accurate current
control and constant output current in the presence of
input voltage transients without the need for
complicated loop design.
0.5
0
0
1
2
3
4
5
6
7
IIN (mA)
FIGURE 3-1:
Maximum Voltage Drop vs.
Input Current.
Assume an ambient temperature of 125°C. Provided
that the IC is driving a 15 nC gate charge FET at
300 kHz, the total input current is estimated to be
5.5 mA (using Equation 3-1). At this input current, the
maximum voltage drop from Figure 3-1 can be
approximately estimated to be VDROP = 2.7V. However,
before the IC starts switching, the current drawn will be
1 mA. At this current level, the voltage drop is
approximately VDROP1 = 0.5V. Thus, the start/stop VIN
voltages can be computed as shown in Equation 3-2
and Equation 3-3:
3.2
Input Voltage Regulator
The AT9933 can be powered directly from its VIN pin
that can withstand a maximum voltage of up to 75V.
When a voltage is applied to the VIN pin, the AT9933
seeks to regulate a constant 7.5V (typical) at the VDD
pin. The regulator also has a built-in undervoltage
lockout which shuts off the IC when the voltage at the
VDD pin falls below the UVLO threshold.
The VDD pin must be bypassed by a low-ESR capacitor
(≥0.1 μF) to provide a low-impedance path for the high
frequency current of the output gate driver.
EQUATION 3-2:
VIN – START = UVLOMAX + VDROP1
The input current drawn from the VIN pin is the sum of
the 1 mA current drawn by the internal circuit and the
current drawn by the gate driver, which in turn depends
on the switching frequency and the gate charge of the
external FET. Refer to Equation 3-1.
= 6.95V + 0.5V
= 7.45V
EQUATION 3-3:
VIN – STOP = UVLOMAX – UVLO + VDROP
= 6.95V – 0.5V + 2.7V
EQUATION 3-1:
IIN = 1mA + QG fS
= 9.15V
In the above equation, fS is the switching frequency,
and QG is the gate charge of the external FET which
can be obtained from the data sheet of the FET.
Note:
Since the gate driver draws too much cur-
rent in this situation, VIN-START is less than
VIN-STOP. The control IC will oscillate
between on and off if the input voltage is
between the start and stop voltages. In
these circumstances, it is recommended
that the input voltage be kept higher than
VIN-STOP. The IC will operate normally if
the input voltage is kept higher than 9.2V.
3.3
Minimum Input Voltage at VIN Pin
The minimum input voltage at which the converter will
start and stop depends on the minimum voltage drop
required for the linear regulator. The internal linear
regulator will control the voltage at the VDD pin when
VIN is between 8V and 75V. However, when the VIN is
less than 8V, the converter will still function as long as
2016 Microchip Technology Inc.
DS20005597A-page 7
AT9933
In case of input transients that reduce the input voltage
below 8V (e.g. Cold Crank condition in an automotive
system), the VIN pin of the AT9933 can be connected to
the MOSFET drain through a switching diode using a
small (1 nF) capacitor between VIN and GND as long as
the drain voltage does not exceed 75V. Since the drain
of the FET is at a voltage equal to the sum of the input
and output voltages, the IC will still be operational when
the input goes below 8V. Therefore, a larger capacitor
is needed at the VDD pin to supply power to the IC when
the MOSFET is switched on.
each time, ensuring a quick response time for the
output current. The recommended PWM dimming
frequency range is from 100 Hz to a few kilohertz.
The flying capacitor in the Ćuk converter (C1) is initially
charged to the input voltage VDC (through diodes D1
and D2). When the circuit is turned on and reaches
Steady state, the voltage across C1 will be VDC+VO. In
the absence of diode D2, when the circuit is turned off,
capacitor C1 will discharge through the LEDs and the
input voltage source VDC. Thus, during PWM dimming,
if capacitor C1 has to be charged and discharged each
cycle, the transient response of the circuit will be
limited. By adding diode D2, the voltage across
capacitor C1 is held at VDC+VO even when the circuit
is turned off, enabling the circuit to return quickly to its
Steady state (and bypassing the start-up stage) upon
being enabled.
In this case, VDD UVLO cannot be relied upon to turn off
the IC at low input voltages when input current levels
can get too large. In such cases, the input current limit
must be chosen to ensure that the input current is set
to a safe level.
3.4
Reference
An internally trimmed voltage reference of 1.25V is
provided at the REF pin. The reference can supply a
maximum output current of 500 µA to drive external
resistor dividers.
This reference can be used to set the current
thresholds of the two comparators as shown in the
Typical Application Circuit section.
3.5
Current Comparators
The AT9933 features two identical comparators with a
built-in 100 mV hysteresis. When the GATE is low, the
inverting terminal is connected to 100 mV, but when the
GATE is high, it is connected to GND. One comparator
is used for the input current control and the other for the
output current control.
The input side hysteretic controller is in operation
during Start-up, Overload and Input Undervoltage
conditions. This ensures that the input current never
exceeds the designed value. During normal operation,
the input current is less than the programmed current.
Therefore, the output of the input side comparator will
be high. The output of the AND gate will then be
dictated by the output current controller.
The output side hysteretic comparator controls the
external MOSFET during Steady state operation of the
circuit. This comparator turns the MOSFET on and off
based on the LED current.
3.6
PWM Dimming
PWM Dimming can be achieved by applying a
TTL-compatible square wave signal to the PWM pin.
When the PWMD pin is pulled high, the gate driver is
enabled and the circuit operates normally. When the
PWMD pin is left open or connected to GND, the gate
driver is disabled and the external MOSFET turns off.
The signal at the PWMD pin inhibits the driver only and
the IC need not go through the entire start-up cycle
DS20005597A-page 8
2016 Microchip Technology Inc.
AT9933
4.4
Design Example
4.0
4.1
APPLICATION INFORMATION
Overvoltage Protection
The choice of the resistor dividers to set the input and
output current levels is illustrated by means of the
design example given below.
Overvoltage protection can be added by splitting the
output side resistor RS2 into two components and
adding a Zener diode D3. (Refer to Figure 4-1 below.)
When there is an Open LED condition, the diode D3 will
clamp the output voltage and the Zener diode current
The parameters of the power circuit are:
VIN MIN = 9.01V
VIN MAX = 16V
will be regulated by the sum of RS2A and RCS2
.
VO = 28V
IO = 0.35A
fS MIN = 300kHz
4.2
Damping Circuit
The Ćuk converter is inherently unstable when the
output current is being controlled. An uncontrolled input
current will lead to an undamped oscillation between L1
and C1, causing excessively high voltages across
capacitor C1. To prevent these oscillations, a damping
circuit consisting of RD and CD is applied across the
capacitor C1. This damping circuit will stabilize the
circuit and help in the proper operation of the converter.
Using these parameters, the values of the power stage
inductors and capacitor can be computed. (See figures
below.) Refer to Application Note AN-H51 for more
details.
L1 = 82H
L2 = 150H
C1 = 0.22F
4.3
Design and Operation of the
Boost-buck Converter
The input and output currents for this design are:
For details on the design for a boost-buck converter
using the AT9933 and the calculation of the damping
components, refer to Application Notes AN-H51 and
AN-H58.
IIN MAX = 1.6A
IIN = 0.21A
IO = 350mA
IO = 87.5mA
C1
D2 (optional)
L2
L1
-
RD
CD
CO
VDC
VO
D1
Q1
+
RCS2
RCS1
RS2A
D3
C2
RS1
VIN
VDD
RS2B
GATE PWMD
CS1
CS2
REF
RREF2
GND
RREF1
C3
AT9933
FIGURE 4-1:
Design Example Circuit.
2016 Microchip Technology Inc.
DS20005597A-page 9
AT9933
Using IO = 350 mA and ꢀIO = 87.5 mA in Equation 4-1
and Equation 4-2, RCS2 = 1.78Ω and
4.5
Current Limits
The current sense resistor RCS2, combined with the
other resistors RS2 and RREF2, determines the output
current limits.
RS2/RREF2 = 0.5625.
Before the design of the output side is complete,
overvoltage protection has to be included in the design.
For this application, choose a 33V Zener diode. This is
the voltage at which the output will clamp in case of an
Open LED condition. For a 350 mW diode, the
maximum current rating at 33V works out to about
10 mA. Using a 2.5 mA current level during Open LED
conditions, and assuming the same RS2/RREF2 ratio,
the Zener current limiting resistor can be determined as
illustrated in Equation 4-6.
The resistors can be chosen using Equation 4-1 and
Equation 4-2.
EQUATION 4-1:
RS
------------
I RCS = 1.2V
– 0.05V
RREF
Where I is the current (either IO or IIN) and ꢀI is the
peak-to-peak ripple in the current (either ꢀIO or
ꢀIIN).
EQUATION 4-6:
RCS + RS2A = 120
EQUATION 4-2:
RS
------------
I RCS = 0.1V
+ 0.1V
Choose the following values for the resistors:
RREF
RCS2 = 1.65Ω, 1/4W, 1%
RREF2 = 10 kΩ, 1/8W, 1%
RS2A = 100Ω, 1/8W, 1%
RS2B = 5.23 kΩ, 1/8W, 1%
Where I is the current (either IO or IIN) and ꢀI is the
peak-to-peak ripple in the current (either ꢀIO or
ꢀIIN).
For the input side, the current level used in the
equations should be larger than the maximum input
current, so that it does not interfere with the normal
operation of the circuit. The peak input current can be
computed as shown in Equation 4-3.
The current sense resistor needs to be at least a 1/4W,
1% resistor.
Similarly, using IIN = 2.1A and ꢀIIN = 0.3 x IIN = 0.63 in
Equation 4-1 and Equation 4-2, the following values
can be determined:
EQUATION 4-3:
IIN
RS1
----------
IIN PK = IIN MAX
= 1.706A
+
---------------
= 0.442
2
RREF1
RCS1 = 0.228
PRCS1 = I2IN LIM R
= 1W
CS1
Assuming a 30% peak-to-peak ripple when the
converter is in Input Current Limit mode, the minimum
value of the input current is calculated as seen in
Equation 4-4.
Choose the following values for the resistors:
RCS1 = parallel combination of three 0.68Ω, 1/2W, 5%
EQUATION 4-4:
resistors
RREF1 = 10kΩ, 1/8W, 1%
RS1 = 4.42kΩ, 1/8W, 1%
ILIM MIN = 0.85 IIN LIM
Setting
ILIM MIN = 1.05 IIN PK
The current level to limit the converter can then be
computed. See equation Equation 4-5.
EQUATION 4-5:
1.05
0.85
---------
IIN LIM
=
IIN PK
= 2.1A
DS20005597A-page 10
2016 Microchip Technology Inc.
AT9933
5.0
5.1
PACKAGING INFORMATION
Package Marking Information
Example
8-lead SOIC
XXXXXXXX
AT9933LG
e3
YYWW
e3
1645
NNN
222
Legend: XX...X Product Code or Customer-specific information
Y
Year code (last digit of calendar year)
YY
WW
NNN
Year code (last 2 digits of calendar year)
Week code (week of January 1 is week ‘01’)
Alphanumeric traceability code
Pb-free JEDEC® designator for Matte Tin (Sn)
This package is Pb-free. The Pb-free JEDEC designator ( )
e
3
*
e
3
can be found on the outer packaging for this package.
Note: In the event the full Microchip part number cannot be marked on one line, it will
be carried over to the next line, thus limiting the number of available
characters for product code or customer-specific information. Package may or
not include the corporate logo.
2016 Microchip Technology Inc.
DS20005597A-page 11
AT9933
Note: For the most current package drawings, see the Microchip Packaging Specification at www.microchip.com/packaging.
DS20005597A-page 12
2016 Microchip Technology Inc.
AT9933
APPENDIX A: REVISION HISTORY
Revision A (October 2016)
• Converted Supertex Doc# DSFP-AT9933 to
Microchip DS20005597A
• Changed the quantity of the 8-lead SOIC package
from 3000/Reel to 3300/Reel
• Made minor text changes throughout the docu-
ment
2016 Microchip Technology Inc.
DS20005597A-page 13
AT9933
PRODUCT IDENTIFICATION SYSTEM
To order or obtain information, e.g., on pricing or delivery, contact your local Microchip representative or sales office.
Example:
XX
PART NO.
Device
-
X
-
X
a)
AT9933LG-G:
Hysteretic Boost-buck (Ćuk) LED
Driver IC, 8-lead SOICPackage,
3300/Reel
Package
Options
Environmental
Media Type
Device:
AT9933
LG
=
=
=
=
Hysteretic Boost-Buck (Ćuk) LED Driver IC
8-lead SOIC
Package:
Environmental:
Media Type:
G
Lead (Pb)-free/RoHS-compliant Package
3300/Reel for an LG Package
(blank)
DS20005597A-page 14
2016 Microchip Technology Inc.
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INCLUDING BUT NOT LIMITED TO ITS CONDITION,
QUALITY, PERFORMANCE, MERCHANTABILITY OR
FITNESS FOR PURPOSE. Microchip disclaims all liability
arising from this information and its use. Use of Microchip
devices in life support and/or safety applications is entirely at
the buyer’s risk, and the buyer agrees to defend, indemnify and
hold harmless Microchip from any and all damages, claims,
suits, or expenses resulting from such use. No licenses are
conveyed, implicitly or otherwise, under any Microchip
intellectual property rights unless otherwise stated.
Trademarks
The Microchip name and logo, the Microchip logo, AnyRate,
dsPIC, FlashFlex, flexPWR, Heldo, JukeBlox, KeeLoq,
KeeLoq logo, Kleer, LANCheck, LINK MD, MediaLB, MOST,
MOST logo, MPLAB, OptoLyzer, PIC, PICSTART, PIC32 logo,
RightTouch, SpyNIC, SST, SST Logo, SuperFlash and UNI/O
are registered trademarks of Microchip Technology
Incorporated in the U.S.A. and other countries.
ClockWorks, The Embedded Control Solutions Company,
ETHERSYNCH, Hyper Speed Control, HyperLight Load,
IntelliMOS, mTouch, Precision Edge, and QUIET-WIRE are
registered trademarks of Microchip Technology Incorporated
in the U.S.A.
Analog-for-the-Digital Age, Any Capacitor, AnyIn, AnyOut,
BodyCom, chipKIT, chipKIT logo, CodeGuard, dsPICDEM,
dsPICDEM.net, Dynamic Average Matching, DAM, ECAN,
EtherGREEN, In-Circuit Serial Programming, ICSP, Inter-Chip
Connectivity, JitterBlocker, KleerNet, KleerNet logo, MiWi,
motorBench, MPASM, MPF, MPLAB Certified logo, MPLIB,
MPLINK, MultiTRAK, NetDetach, Omniscient Code
Generation, PICDEM, PICDEM.net, PICkit, PICtail,
PureSilicon, RightTouch logo, REAL ICE, Ripple Blocker,
Serial Quad I/O, SQI, SuperSwitcher, SuperSwitcher II, Total
Endurance, TSHARC, USBCheck, VariSense, ViewSpan,
WiperLock, Wireless DNA, and ZENA are trademarks of
Microchip Technology Incorporated in the U.S.A. and other
countries.
SQTP is a service mark of Microchip Technology Incorporated
in the U.S.A.
Microchip received ISO/TS-16949:2009 certification for its worldwide
headquarters, design and wafer fabrication facilities in Chandler and
Tempe, Arizona; Gresham, Oregon and design centers in California
and India. The Company’s quality system processes and procedures
are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping
devices, Serial EEPROMs, microperipherals, nonvolatile memory and
analog products. In addition, Microchip’s quality system for the design
and manufacture of development systems is ISO 9001:2000 certified.
Silicon Storage Technology is a registered trademark of
Microchip Technology Inc. in other countries.
GestIC is a registered trademarks of Microchip Technology
Germany II GmbH & Co. KG, a subsidiary of Microchip
Technology Inc., in other countries.
All other trademarks mentioned herein are property of their
respective companies.
QUALITYꢀMANAGEMENTꢀꢀSYSTEMꢀ
CERTIFIEDꢀBYꢀDNVꢀ
© 2016, Microchip Technology Incorporated, Printed in the
U.S.A., All Rights Reserved.
ISBN: 978-1-5224-0995-3
== ISO/TSꢀ16949ꢀ==ꢀ
2016 Microchip Technology Inc.
DS20005597A-page 15
Worldwide Sales and Service
AMERICAS
ASIA/PACIFIC
ASIA/PACIFIC
EUROPE
Corporate Office
2355 West Chandler Blvd.
Chandler, AZ 85224-6199
Tel: 480-792-7200
Fax: 480-792-7277
Technical Support:
http://www.microchip.com/
support
Asia Pacific Office
China - Xiamen
Tel: 86-592-2388138
Fax: 86-592-2388130
Austria - Wels
Tel: 43-7242-2244-39
Fax: 43-7242-2244-393
Suites 3707-14, 37th Floor
Tower 6, The Gateway
Harbour City, Kowloon
China - Zhuhai
Tel: 86-756-3210040
Fax: 86-756-3210049
Denmark - Copenhagen
Tel: 45-4450-2828
Fax: 45-4485-2829
Hong Kong
Tel: 852-2943-5100
Fax: 852-2401-3431
India - Bangalore
Tel: 91-80-3090-4444
Fax: 91-80-3090-4123
France - Paris
Tel: 33-1-69-53-63-20
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Australia - Sydney
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Web Address:
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Germany - Dusseldorf
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Atlanta
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Tel: 678-957-9614
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China - Beijing
Tel: 86-10-8569-7000
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Germany - Karlsruhe
Tel: 49-721-625370
India - Pune
Tel: 91-20-3019-1500
China - Chengdu
Tel: 86-28-8665-5511
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Germany - Munich
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Austin, TX
Tel: 512-257-3370
Japan - Osaka
Tel: 81-6-6152-7160
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Boston
China - Chongqing
Tel: 86-23-8980-9588
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Italy - Milan
Tel: 39-0331-742611
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Westborough, MA
Tel: 774-760-0087
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Japan - Tokyo
Tel: 81-3-6880- 3770
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China - Dongguan
Tel: 86-769-8702-9880
Italy - Venice
Tel: 39-049-7625286
Chicago
Itasca, IL
Tel: 630-285-0071
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Korea - Daegu
Tel: 82-53-744-4301
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China - Guangzhou
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Netherlands - Drunen
Tel: 31-416-690399
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China - Hangzhou
Tel: 86-571-8792-8115
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Korea - Seoul
Cleveland
Tel: 82-2-554-7200
Fax: 82-2-558-5932 or
82-2-558-5934
Poland - Warsaw
Tel: 48-22-3325737
Independence, OH
Tel: 216-447-0464
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China - Hong Kong SAR
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Spain - Madrid
Tel: 34-91-708-08-90
Fax: 34-91-708-08-91
Malaysia - Kuala Lumpur
Tel: 60-3-6201-9857
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Dallas
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Fax: 972-818-2924
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Tel: 86-25-8473-2460
Fax: 86-25-8473-2470
Sweden - Stockholm
Tel: 46-8-5090-4654
Malaysia - Penang
Tel: 60-4-227-8870
Fax: 60-4-227-4068
Detroit
Novi, MI
Tel: 248-848-4000
UK - Wokingham
Tel: 44-118-921-5800
Fax: 44-118-921-5820
China - Qingdao
Tel: 86-532-8502-7355
Fax: 86-532-8502-7205
Philippines - Manila
Tel: 63-2-634-9065
Fax: 63-2-634-9069
Houston, TX
Tel: 281-894-5983
China - Shanghai
Tel: 86-21-5407-5533
Fax: 86-21-5407-5066
Singapore
Tel: 65-6334-8870
Fax: 65-6334-8850
Indianapolis
Noblesville, IN
Tel: 317-773-8323
Fax: 317-773-5453
China - Shenyang
Tel: 86-24-2334-2829
Fax: 86-24-2334-2393
Taiwan - Hsin Chu
Tel: 886-3-5778-366
Fax: 886-3-5770-955
Los Angeles
China - Shenzhen
Tel: 86-755-8864-2200
Fax: 86-755-8203-1760
Mission Viejo, CA
Tel: 949-462-9523
Fax: 949-462-9608
Taiwan - Kaohsiung
Tel: 886-7-213-7828
China - Wuhan
Tel: 86-27-5980-5300
Fax: 86-27-5980-5118
Taiwan - Taipei
Tel: 886-2-2508-8600
Fax: 886-2-2508-0102
New York, NY
Tel: 631-435-6000
San Jose, CA
Tel: 408-735-9110
China - Xian
Tel: 86-29-8833-7252
Fax: 86-29-8833-7256
Thailand - Bangkok
Tel: 66-2-694-1351
Fax: 66-2-694-1350
Canada - Toronto
Tel: 905-695-1980
Fax: 905-695-2078
06/23/16
DS20005597A-page 16
2016 Microchip Technology Inc.
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