MRFIC1502R2 [MOTOROLA]
RF/MICROWAVE DOWN CONVERTER, PLASTIC, LQFP-48;型号: | MRFIC1502R2 |
厂家: | MOTOROLA |
描述: | RF/MICROWAVE DOWN CONVERTER, PLASTIC, LQFP-48 射频 微波 |
文件: | 总8页 (文件大小:137K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
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by MRFIC1502/D
SEMICONDUCTOR TECHNICAL DATA
The MRFIC Line
This integrated circuit is intended for GPS receiver applications. The dual
conversion design is implemented in Motorola’s low–cost high performance
MOSAIC 3 silicon bipolar process and is packaged in a low–cost surface mount
TQFP–48 package. In addition to the mixers, a VCO, a PLL and a loop filter are
integrated on–chip. Output IF is nominally 9.5 MHz.
1.575 GHz GPS
DOWNCONVERTER
•
•
•
•
•
65 dB Minimum Conversion Gain
5 Volts Operation
50 mA Typical Current Consumption
Low–Cost, Low Profile Plastic LQFP Package
Order MRFIC1502R2 for Tape and Reel.
R2 Suffix = 1,500 Units per 16 mm, 13 inch Reel.
•
Device Marking = M1502
CASE 932–02
(LQFP–48)
TO FROM
BPF BPF
GND GND GND GND RF IN GND
V
GND
41
GND GND
38 37
CC1
48
47
46
45
44
43
42
40
39
TQFP–48
1
2
36 GND
GND
35
34
33
32
31
38 MHz TRAP
38 MHz TRAP
VCO VT
3
4
GND
V
CC5
BYPASS CAP
IF OUT
VCO
ACTIVE
FILTER
5
GND
40
6
V
CC2
VCO CE
GND
2
30 GND
7
GAIN CONTROL
8
29
28
27
26
25
SF CAP1
GND
LOOP
FILTER
V
CC3
9
PHASE
DETECTOR
GND
GND
GND
10
11
12
SF CAP2
GND
GND
20
21
22
23
24
13
14
15
16
17
18
19
GND
C2A C2B
C1
CA
CB DCX0
V
CC4
GND CLK GND GND
OUT
Pin Connections and Functional Block Diagram
Motorola, Inc. 2001
Rev 1
MAXIMUM RATINGS
Rating
Symbol
Limit
+6.0
Unit
Vdc
mA
°C
DC Supply Voltage
V
DD
DC Supply Current
I
60
DD
Operating Ambient Temperature
Storage Temperature Range
T
A
– 40 to +100
– 65 to +150
+260
T
stg
°C
Lead Soldering Temperature Range (10 seconds)
—
°C
ELECTRICAL CHARACTERISTICS (T = 25°C, and V
= 5 V, Tested in Circuit shown in Figure 1 unless otherwise noted)
A
CC
Min
4.75
—
Typ
—
Max
5.25
60
Unit
Vdc
mA
dB
Characteristic
Supply Voltage
Supply Current
—
L–Band Gain (Measured from L–Band Input to 47 MHz Output)
—
20
45
—
IF Gain (Measured from 47 MHz Input to 9.5 MHz Output with Gain
Control at Maximum)
—
—
dB
Conversion Gain (Measured from L–Band Input to 9.5 MHz Output with
Gain Control at Maximum)
65
—
—
dB
Gain Control (Externally Adjustable 0 to 5.0 V, Maximum at 0 V)
Noise Figure (Double Sideband)
—
—
—
—
—
—
—
—
—
—
—
—
400
40
9.5
2:1
2:1
2:1
2000
–7
—
—
dB
dB
L–Band Input VSWR (Measured into 50 Ω; 1575.42 ± 5.0 MHz)
First IF Output VSWR (Measured into 50 Ω; 47.74 ± 5.0 MHz)
Second IF Output VSWR (Measured into 50 Ω; 9.5 ± 5.0 MHz)
Input Impedance @ 1st IF 47.7 ± 5 MHz (For Reference Only)
Output 1.0 dB Compression Point
—
—
—
—
—
—
—
Ω
—
dBm
dBm
dBm
dBm
dBm
dBm
mVpp
First LO (Measured at the First IF Output)
–20
–45
–50
–25
–45
—
—
All Other Harmonics (Measured at the First IF Output)
38.1915 MHz Leakage at First IF Output
—
—
Second LO (Measured at the Second IF Output)
All Other Harmonics (Measured at Second IF Output)
Reference Oscillator Input
—
—
4500
Clock Output
Frequency
2Xf
ref
—
2Xf
ref
Amplitude
Low
HIgh
—
2.0
0.8
—
V
V
(Clock Amplitude Measured with the Output Loaded in 15 pF and 40 kΩ)
Duty Cycle
45
1.2
—
55
3.0
—
%
V
VCO Lock Voltage
—
0.16
15
Phase Detector Gain
VCO Modulation Sensitivity
V/Radian
MHz/V
—
—
MRFIC1502
2
MOTOROLA WIRELESS SEMICONDUCTOR
SOLUTIONS DEVICE DATA
L7
C22
C21
L6
C23
L8
V
CC
L9
C34
R3
C24
RF
INPUT
L10
C19
C20
C18
41
40
39
38
48
47
46
45
44
43
42
37
TQFP–48
36
35
1
2
3
CR1
C31
C17
L3
C14
R1
34
33
32
31
30
29
28
27
26
25
V
CC
4
C16
L1
C36
C13
C12
C15
ACTIVE
FILTER
5
VCO
40
IF OUTPUT
C10
V
CC
6
L5
C35
C11
2
7
8
GAIN CONTROL
C3
C2
V
CC
LOOP
FILTER
9
PHASE
DETECTOR
L4
C8
C9
10
11
12
20
21
22
23
24
13
14
15
16
17
18
19
C5
C6
C7
C1
C36
C37
C4
L1
DXCO
V
CC
CLOCK
OUTPUT
C1, C8, C10, C12, C13, C15,
C19, C20, C37
C4, C5
C6, C7, C31
C2, C3
C14
C16, C18, C36
C17
C24
C35
CR1
68 pF, ATC
1.0 pF, ATC*
2.7 pF, MA45233–123, MACOM
2.2 µH, 1008CS–222XKBC, COILCRAFT
10,000 pF
5600 pF
1000 pF
1.0 µF
3.9 pF, ATC
27 pF, ATC
15 pF, ATC
5.6 pF, ATC
47 pF, ATC
120 pF, ATC
L1, L4, L5, L10
L3
L6
L7
L8
L9
R1
R3
2.2 nH, LL2012–F2N2S, TOKO
2.2 µH
220 nH
0.56 µH
0.27 µH
10 kΩ
C21
C9, C11, C34, C36
C22, C23
220 Ω
* See Application Information on following pages for importance of emitter capacitance
Figure 1. Test Circuit Configuration
MOTOROLA WIRELESS SEMICONDUCTOR
SOLUTIONS DEVICE DATA
MRFIC1502
3
Table 1. Port Impedance Derived from Circuit Characterization
Z
in
Ohms
f
(MHz)
Pin Number
Pin Name
RF IN
R
jX
–16.09
11.3
44
40
39
32
1575.42
47.74
47.74
9.5
38.3
54.45
43
TO BPF
FROM BPF
IF OUT
1.5
560
–850
Z
in
represents the input impedance of the pin.
APPLICATION INFORMATION
Design Philosophy
The MRFIC1502 design is a standard dual downconver-
sion configuration with an integrated fixed frequency phase–
locked loop to generate the two local oscillators and the
buffer to generate the sampling clock for a digital correlator
and decimator. The active device for the L–band VCO is also
integrated on the chip. This chip is designed in the third gen-
eration of Motorola’s Oxide Self Aligned Integrated Circuits
(MOSAIC 3) silicon bipolar process.
This filtering is primarily to reduce the amount of LO leakage
into the final IF amplifier and is achieved using a single 3.9
pF capacitor across the differential ports. The value of the
capacitor determines the high frequency of the low pass
structure.
The supply pin for the IF circuits is pin 33. This supply pin
should be isolated from the other chip supplies in order to re-
duce the amount of coupling. The recommended capacitors
are a 47 pF and a 0.01 µF, in parallel to bypass the supply to
ground and should be placed physically as close to the pin as
possible.
Circuit Considerations
The RF input to the MRFIC1502 is internally matched to 50
ohms. Therefore, only AC coupling is required on the input.
The output of the amplifier is fed directly into the first mixer.
This mixer is an active Gilbert Cell configuration. The output
of the mixer is brought off–chip for filtering of the unwanted
The output of the second IF amplifier is 50 ohms with a
bandwidth of ±5.0 MHz. This signal must be filtered before
being digitized in order to limit the noise entering the A/D
converter.
mixer products. The amplifier and mixer have their own V
CC
supply (pin 42) in order to reduce the amount of coupling to
the other circuits. There are two bypass capacitors on this
pin, one for the high frequency components and one for the
lower frequency components. These two capacitors should
be placed physically as close to the bias pin as possible to
reduce the inductance in the path. The capacitors should
also be grounded as close to the ground of the IC as pos-
sible, preferably through a ground plane.
The output impedance of the first mixer is 50 ohms, while
the input impedance to the first IF amplifier is 1 kΩ. There is
a trap (zero) designed in at the second LO frequency to limit
the amount of LO leakage into the high gain first IF amplifier.
The first IF amplifier is a variable gain amplifier with 25 dB
of gain and 40 dB of gain control. The gain control pin can be
grounded to provide the maximum gain out of the amplifier. If
the baseband design utilizes a multi–bit A/D converter in the
digital signal processing chip, this amplifier could be used to
control the input to the A/D converter. The amplifier has an
external bypassing capacitor. This capacitor should be on
the order of 0.01 µF, and again should be located near the
package pin.
VCO Resonator Design
The design and layout of the circuits around the voltage
controlled oscillator (VCO) are the most sensitive of the en-
tire layout. The active device and biasing resistors are inte-
grated on the MRFIC1502. The external circuits consist of
the power supply decoupling, the capacitors for the inte-
grated supply superfilter, the resonator and frequency adjust-
ing elements, and the bypassing capacitor on the emitter of
the active device.
The VCO supply is isolated from the rest of the PLL circuits
in order to reduce the amount of noise that could cause fre-
quency/phase noise in the VCO. The supply should be fil-
tered using a 22 µH inductor in series and a 27 pF and 0.01
µF in parallel. The 27 pF capacitor should be series resonant
at least as high as the VCO frequency to get the most L–
band bypassing as possible. The on–chip supply filter re-
quires two capacitors off–chip to filter the supply. The
capacitors on the input (pin 8) and output (pin 10) of the filter
are 1.0 µF, and the output also has a high frequency bypass
capacitor in parallel. The input capacitor should not be smaller
than a 1.0 µF to insure stability of the supply filter.
The second mixer design is also a Gilbert Cell
configuration. The interface between the mixer and the
second IF amplifier is differential in order to increase noise
immunity. This differential interface is also brought off–chip
so that some additional filtering could be added in parallel
between the output of the mixer and input to the amplifier.
The VCO design is a standard negative resistance cell
with a buffer amplifier. The resonating structure is connected
to the base of the active device and consists of a coupling
capacitor, a hyper–abrupt varactor diode, and a wire wound
chip inductor. With the values shown on the application
MRFIC1502
4
MOTOROLA WIRELESS SEMICONDUCTOR
SOLUTIONS DEVICE DATA
circuit, the VCO is centered at 1527.7 MHz, and the gain of
the VCO is approximately 20 MHz/Volt.
discrete components around the loop filter and VCO is very
critical to the performance of the phase–locked loop. Care
should be taken in routing the VCO control voltage line from
the output of the loop filter to the varactor diode.
The output of the divide by 40 is buffered by a clock trans-
lator that converts the low level sine wave into a TTL level
square wave. The loading on the buffer is high so the peak
currents can reach as high as 50 mA with the maximum load
of 1.0 kΩ in parallel with 40 pF on the output. Therefore, the
The above performance is heavily dependent on the ca-
pacitive structure that is used as the emitter bypass on pin 6.
The total capacitance should be 1.0 pF; that can be achieved
using either a discrete element or a microstrip open circuited
stub. The evaluation circuit shown uses a 1.0 pF capacitor.
Phase–locked Loop Design
The VCO signal at 1527.68 MHz is divided by 40 to get the
second LO frequency of 38.19 MHz. In addition to providing
the LO to the second mixer, the 38 MHz signal is output
through a translator and is used as the sampling clock for the
digital correlator and decimator circuits. There is an addition-
al divide by two so the signal used by the phase detector is at
19.096 MHz. The reference input to the phase detector (pin 18)
has an input sensitivity of 400 mVpp minimum and 2.5 Vpp
maximum.
translator has a dedicated V
supply, pin 28, which requires
CC
external bypassing and isolation. The recommended bypas-
sing uses two capacitors in parallel, a 47 pF and a 0.01 µF
capacitor.
Conclusion
The MRFIC1502 offers a highly integrated downconverter
solution for GPS receivers. For more detailed applications in-
formation on GPS system design refer to application note
AN1610, “Using Motorola’s MRFIC1502 in Global Position-
ing System Receivers.”
The loop filter design is the standard op–amp loop filter,
resulting in a type 2 second order loop. The layout of the
MOTOROLA WIRELESS SEMICONDUCTOR
SOLUTIONS DEVICE DATA
MRFIC1502
5
PACKAGE DIMENSIONS
PLASTIC PACKAGE
CASE 932–03
(LQFP–48)
ISSUE F
4X
NOTES:
0.200 AB T–U Z
1. DIMENSIONING AND TOLERANCING PER ASME
Y14.5M, 1994.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DATUM PLANE AB IS LOCATED AT BOTTOM OF
LEAD AND IS COINCIDENT WITH THE LEAD
WHERE THE LEAD EXITS THE PLASTIC BODY AT
THE BOTTOM OF THE PARTING LINE.
4. DATUMS T, U, AND Z TO BE DETERMINED AT
DATUM PLANE AB.
DETAIL Y
P
9
A
A1
48
37
5. DIMENSIONS S AND V TO BE DETERMINED AT
SEATING PLANE AC.
1
36
6. DIMENSIONS A AND B DO NOT INCLUDE MOLD
PROTRUSION. ALLOWABLE PROTRUSION IS
0.250 PER SIDE. DIMENSIONS A AND B DO
INCLUDE MOLD MISMATCH AND ARE
DETERMINED AT DATUM PLANE AB.
7. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. DAMBAR PROTRUSION SHALL
NOT CAUSE THE D DIMENSION TO EXCEED
0.350.
T
U
B
V
AE
AE
B1
V1
8. MINIMUM SOLDER PLATE THICKNESS SHALL BE
0.0076.
12
25
9. EXACT SHAPE OF EACH CORNER IS OPTIONAL.
MILLIMETERS
13
24
DIM MIN
MAX
7.000 BSC
3.500 BSC
Z
A
A1
B
B1
C
D
E
F
G
H
J
K
L
M
N
P
S1
7.000 BSC
3.500 BSC
T, U, Z
1.400 1.600
0.170 0.270
1.350 1.450
0.170 0.230
0.500 BSC
0.050 0.150
0.090 0.200
0.500 0.700
S
DETAIL Y
4X
0.200 AC T–U Z
0
7
0.080 AC
12 REF
G
AB
AC
0.090 0.160
0.250 BSC
0.150 0.250
9.000 BSC
4.500 BSC
9.000 BSC
4.500 BSC
0.200 REF
R
S
S1
V
V1
W
AA
AD
1.000 REF
M
BASE METAL
TOP & BOTTOM
R
N
J
E
C
F
D
M
0.080
AC T–U Z
SECTION AE–AE
W
H
L
K
DETAIL AD
AA
MRFIC1502
6
MOTOROLA WIRELESS SEMICONDUCTOR
SOLUTIONS DEVICE DATA
NOTES
MOTOROLA WIRELESS SEMICONDUCTOR
SOLUTIONS DEVICE DATA
MRFIC1502
7
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or
guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the
applicationor use of any product or circuit, and specifically disclaims any and all liability, includingwithoutlimitationconsequentialorincidental
damages. “Typical” parameters which may be provided in Motorola data sheets and/or specifications can and do vary in differentapplications
and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application
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HOME PAGE: http://www.motorola.com/semiconductors/
◊
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