LMP8645 [NSC]
Precision High Voltage Current Sense Amplifier; 精密高电压电流检测放大器
| 型号： | LMP8645 |
| 厂家： | 
National Semiconductor |
| 描述： | Precision High Voltage Current Sense Amplifier |
| 文件： | 总16页 (文件大小：397K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
July 1, 2010
LMP8645/LMP8645HV
Precision High Voltage Current Sense Amplifier
General Description
Features
The LMP8645 and the LMP8645HV are precision current
sense amplifiers that detect small differential voltages across
a sense resistor in the presence of high input common mode
voltages with a supply voltage range from 2.7V to 12V.
Typical values, TA = 25°C
High common-mode voltage range
■
LMP8645
LMP8645HV
Supply voltage range
-2V to 42V
-2V to 76V
2.7V to 12V
—
—
The LMP8645 accepts input signals with common mode volt-
age range from -2V to 42V, while the LMP8645HV accepts
input signal with common mode voltage range from -2V to
76V. The LMP8645 and LMP8645HV have adjustable gain
for applications where supply current and high common mode
voltage are the determining factors. The gain is configured
with a single resistor, providing a high level of flexibility, the
accuracy could be as low as 2% (max) including the gain set-
ting resistor. The output is buffered in order to provide low
output impedance. This high side current sense amplifier is
ideal for sensing and monitoring currents in DC or battery
powered systems, excellent AC and DC specifications over
temperature, and keeps errors in the current sense loop to a
minimum. The LMP8645 is an ideal choice for industrial, au-
tomotive and consumer applications, and it is available in
TSOT-6 package.
■
■
■
■
■
■
■
■
■
■
Gain configurable with a single resistor
Max variable gain accuracy (with external resistor) 2.0%
Transconductance
Low offset voltage
Input bias
PSRR
CMRR
Temperature range
6-Pin TSOT Package
200 μA/V
1 mV
12 μA
90 dB
95 dB
−40°C to 125°C
Applications
High-side current sense
■
■
■
■
■
■
Vehicle current measurement
Motor controls
Battery monitoring
Remote sensing
Power management
Typical Application
30071632
LMP™ is a trademark of National Semiconductor Corporation.
© 2010 National Semiconductor Corporation
300716
www.national.com
LMP8645
Voltage at RG pin
-6V to 60V
13.2V
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Voltage at OUT pin
V- to V+
Storage Temperature Range
Junction Temperature (Note 3)
For soldering specifications,
-65°C to 150°C
150°C
ESD Tolerance (Note 2)
Human Body Model
see product folder at www.national.com and
www.national.com/ms/MS/MS-SOLDERING.pdf
For input pins +IN, -IN
For all other pins
Machine Model
±5000V
±2000V
200V
Operating Ratings (Note 1)
Charge device model
Supply Voltage (VS = V+ - V−)
Differential voltage +IN- (-IN)
Voltage at pins +IN, -IN
LMP8645HV
1250V
13.2V
6V
Supply Voltage (VS = V+ - V−)
Temperature Range (Note 3)
Package Thermal Resistance(Note 3)
TSOT-6
2.7V to 12V
-40°C to 125°C
96°C/W
-6V to 80V
2.7V Electrical Characteristics (Note 4)
Unless otherwise specified, all limits guaranteed for at TA = 25°C, VS=V+ – V-, V+ = 2.7V, V− = 0V, −2V < VCM < 76V, RG= 25kΩ,
RL = 10 MΩ. Boldface limits apply at the temperature extremes.
Min
Typ
Max
Symbol
VOS
Parameter
Condition
Units
(Note 6) (Note 5) (Note 6)
Input Offset Voltage
VCM = 2.1V
-1
-1.7
1
1.7
mV
TCVOS
Input Offset Voltage Drift(Note 7, VCM = 2.1V
Note 9)
7
μV/°C
μA
IB
Input Bias Current(Note 10)
Input Voltage Noise (Note 9)
VCM = 2.1V
12
20
eni
120
f > 10 kHz, RG = 5 kΩ
VCM = 12V, RG = 5 kΩ
nV/
mV
VSENSE(MAX) Max Input Sense Voltage (Note 9)
600
Gain AV
Gm
Adjustable Gain Setting (Note 9) VCM = 12V
1
100
V/V
µA/V
%
Transconductance
Accuracy
VCM = 2.1V
VCM = 2.1V
200
-2
2
-3.4
3.4
Gm drift(Note 9)
−40°C to 125°C, VCM=2.1V
VCM = 2.1V, 2.7V < V+ < 12V
140
ppm /°C
dB
PSRR
CMRR
Power Supply Rejection Ratio
Common Mode Rejection Ratio
90
95
LMP8645HV 2.1V < VCM < 76V
LMP8645 2.1V < VCM< 42V
dB
-2V <VCM < 2V
60
BW
−3 dB Bandwidth (Note 9)
990
260
135
0.5
RG = 10 kΩ,, CG = 4 pF VSENSE = 400 mV,
CL = 30 pF ,RL= 1MΩ
RG = 25 kΩ, CG = 4 pF, VSENSE = 200 mV,
CL = 30 pF, RL = 1MΩ
kHz
Rg = 50kΩ, CG = 4 pF, VSENSE = 100 mV,
CL = 30 pF, RL = 1MΩ
SR
IS
Slew Rate(Note 8, Note 9)
VCM =5V, CG = 4 pF, VSENSE from 25 mV
to 175 mV, CL = 30 pF, RL = 1MΩ
VCM = 2.1V
V/µs
uA
Supply Current
380
525
710
VCM = −2V
2000
2500
2700
VOUT
Maximum Output Voltage
Minimum Output Voltage
1.2
V
VCM = 2.1V, Rg= 500 kΩ
VCM = 2.1V
20
mV
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2
Min
Typ
Max
Symbol
IOUT
Parameter
Condition
Units
(Note 6) (Note 5) (Note 6)
Output current (Note 9)
5
Sourcing, VOUT= 600mV, Rg = 150kΩ
Sinking, VOUT= 600mV, Rg = 150kΩ
mA
pF
5
CLOAD
Max Output Capacitance Load
30
(Note 9)
5V Electrical Characteristics (Note 4)
Unless otherwise specified, all limits guaranteed for at TA = 25°C, VS=V+-V-, V+ = 5V, V− = 0V, −2V < VCM < 76V, Rg= 25kΩ, RL =
10 MΩ. Boldface limits apply at the temperature extremes.
Min
Typ
Max
Symbol
VOS
Parameter
Condition
Units
(Note 6) (Note 5) (Note 6)
Input Offset Voltage
VCM = 2.1V
-1
-1.7
1
1.7
mV
TCVOS
Input Offset Voltage Drift(Note 7, VCM = 2.1V
Note 9)
7
μV/°C
μA
IB
Input Bias Current(Note 10)
Input Voltage Noise (Note 9)
VCM = 2.1V
12.5
120
22
eni
f > 10 kHz, RG = 5 kΩ
VCM = 12V, RG = 5 kΩ
nV/
mV
VSENSE(MAX) Max Input Sense Voltage (Note 9)
600
Gain AV
Gm
Adjustable Gain Setting (Note 9) VCM = 12V
1
100
V/V
µA/V
%
Transconductance
Accuracy
VCM = 2.1V
VCM = 2.1V
200
-2
2
-3.4
3.4
Gm drift (Note 9)
−40°C to 125°C, VCM= 2.1V
VCM = 2.1V, , 2.7V < V+ < 12V
140
ppm /°C
dB
PSRR
CMRR
Power Supply Rejection Ratio
Common Mode Rejection Ratio
90
95
LMP8645HV 2.1V <VCM < 76V
LMP8645 2.1V <VCM< 42V
dB
-2V < VCM < 2V
60
BW
−3 dB Bandwidth (Note 9)
850
260
140
0.5
RG= 10 kΩ, CG = 4 pF VSENSE = 400 mV,
CL = 30 pF, RL = 1MΩ
RG= 25 kΩ, CG = 4 pF, VSENSE = 300 mV,
CL = 30 pF, RL = 1MΩ
kHz
RG= 50 kΩ, CG = 4 pF, VSENSE = 300mV,
CL = 30 pF, RL = 1MΩ
SR
IS
Slew Rate(Note 8, Note 9)
VCM = 5V, CG = 4 pF, VSENSE from 100 mV
to 500 mV, CL = 30 pF, RL= 1MΩ
VCM = 2.1V
V/µs
uA
Supply Current
450
610
780
VCM = −2V
2100
2800
3030
VOUT
Maximum Output Voltage
Minimum Output Voltage
Output current (Note 9)
3.3
V
VCM =5V, Rg= 500 kΩ
VCM =2.1V
22
mV
IOUT
5
5
Sourcing, VOUT= 1.65V, Rg= 150kΩ
Sinking, VOUT= 1.65V, Rg= 150kΩ
mA
pF
CLOAD
Max Output Capacitance Load
30
(Note 9)
3
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12V Electrical Characteristics (Note 4)
Unless otherwise specified, all limits guaranteed for at TA = 25°C, VS=V+-V-, V+ = 12V, V− = 0V, −2V < VCM < 76V, Rg= 25kΩ, RL
= 10 MΩ. Boldface limits apply at the temperature extremes.
Min
Typ
Max
Symbol
VOS
Parameter
Condition
Units
(Note 6) (Note 5) (Note 6)
Input Offset Voltage
VCM = 2.1V
-1
-1.7
1
1.7
mV
TCVOS
Input Offset Voltage Drift(Note 7, VCM = 2.1V
Note 9)
7
μV/°C
μA
IB
Input Bias Current(Note 10)
Input Voltage Noise (Note 9)
VCM = 2.1V
13
23
eni
120
f > 10 kHz, RG = 5 kΩ
VCM =12V, RG = 5 kΩ
nV/
mV
VSENSE(MAX) Max Input Sense Voltage(Note 9)
600
Gain AV
Gm
Adjustable Gain Setting (Note 9) VCM = 12V
1
100
V/V
µA/V
%
Transconductance
Accuracy
VCM = 2.1V
VCM = 2.1V
200
-2
2
-3.4
3.4
Gm drift (Note 9)
−40°C to 125°C, VCM =2.1V
VCM =2.1V, 2.7V <V+ < 12V
140
ppm /°C
dB
PSRR
CMRR
Power Supply Rejection Ratio
Common Mode Rejection Ratio
90
95
LMP8645HV 2.1V <VCM < 76V
LMP8645 2.1V <VCM< 42V
dB
–2V <VCM < 2V
60
BW
−3 dB Bandwidth (Note 9)
860
260
140
0.6
RG = 10 kΩ, CG = 4 pF VSENSE = 400 mV,
CL = 30 pF, RL= 1MΩ
RG = 25 kΩ, CG = 4 pF, VSENSE = 400 mV,
CL = 30 pF, RL= 1MΩ
kHz
RG = 50 kΩ, CG = 4 pF, VSENSE =400 mV,
CL = 30 pF, RL= 1MΩ
SR
IS
Slew Rate(Note 8, Note 9)
VCM = 5V, CG = 4 pF, VSENSE from 100 mV
to 500 mV, CL = 30 pF, RL=1MΩ
VCM = 2.1V
V/µs
uA
Supply Current
555
765
920
VCM = −2V
2200
2900
3110
VOUT
Maximum Output Voltage
Minimum Output Voltage
Output current (Note 9)
10.2
V
VCM = 12V, RG= 500kΩ
VCM = 2.1V
24
mV
mA
IOUT
5
5
Sourcing, VOUT= 5.25V, Rg= 150kΩ
Sinking, VOUT= 5.25V, Rg= 150kΩ
CLOAD
Max Output Capacitance Load
30
pF
(Note 9)
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device
is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics
Tables.
Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC) Field-
Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
Note 3: The maximum power dissipation must be derated at elevated temperatures and is dictated by TJ(MAX), θJA, and the ambient temperature, TA. The maximum
allowable power dissipation PDMAX = (TJ(MAX) - TA)/ θJA or the number given in Absolute Maximum Ratings, whichever is lower.
Note 4: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating
of the device such that TJ = TA. No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self-heating where TJ
TA.
>
Note 5: Typical values represent the most likely parametric norm at the time of characterization. Actual typical values may vary over time and will also depend
on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material.
Note 6: All limits are guaranteed by testing, design, or statistical analysis.
Note 7: Offset voltage temperature drift is determined by dividing the change in VOS at the temperature extremes by the total temperature change.
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4
Note 8: The number specified is the average of rising and falling slew rates and measured at 90% to 10%.
Note 9: This parameter is guaranteed by design and/or characterization and is not tested in production.
Note 10: Positive Bias Current corresponds to current flowing into the device.
5
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Block Diagram
30071630
Connection Diagram
6-Pin TSOT
30071602
Top View
Pin Descriptions
Pin
Name
VOUT
V-
Description
1
2
3
4
5
6
Single Ended Output
Negative Supply Voltage
Positive Input
+IN
-IN
Negative Input
RG
External Gain Resistor
Positive Supply Voltage
V+
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6
Ordering Information
Package
Part Number
Package Marking
Transport Media
NSC Drawing
LMP8645MK
LMP8645MKE
LMP8645MKX
LMP8645HVMK
LMP8645HVMKE
LMP8645HVMKX
1k Units Tape and Reel
250 Units Tape and Reel
3k Units Tape and Reel
1k Units Tape and Reel
250 Units Tape and Reel
3k Units Tape and Reel
AJ6A
6-Pin TSOT
MK06A
AK6A
7
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Typical Performance Characteristics Unless otherwise specified: TA = 25°C, VS=V+-V-, VSENSE= +IN -
(-IN), RL = 10 MΩ.
Supply Curent vs. Supply Voltage
AC PSRR vs. Frequency
Gain vs. Frequency
Supply current vs. VCM
AC CMRR vs. Frequency
CMRR vs. VCM
30071625
30071626
30071613
30071612
30071614
30071624
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Output voltage vs. VSENSE
Output voltage vs. VSENSE (ZOOM close to 0V)
30071617
30071616
Large Step response
Small Step response
30071618
30071619
Settling time (rise)
Settling time (fall)
30071621
30071620
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Common mode step response (rise)
Common mode step response (fall)
30071622
30071615
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10
value that provides a full-scale shunt voltage range of 100 mV
to 200 mV.
Application Information
GENERAL
SELECTION OF THE GAIN RESISTOR
The LMP8645 and LMP8645HV are single supply high side
current sense amplifiers with variable gain selected through
an external resistor and a common mode voltage range of -2V
to 42V or -2V to 76V depending on the grade.
In the LMP8645 and LMP8645HV the gain is selected through
an external resistor connected to the RG pin. Moreover the
gain resistor RGAIN determines the voltage of the output buffer
which is related to the supply voltage and to the common
mode voltage of the input signal. The gain resistor must be
chosen such that the max output voltage does not exceed the
LMP8645 max output voltage rating for a given common
mode voltage.
The sense voltage is amplified by a user-selected gain and
level shifted from the positive power supply to a ground-re-
ferred output.
THEORY OF OPERATION
The following equations explain how to select the gain resistor
for various range of the input common mode voltage.
As seen from the picture below, the current flowing through
RS develops a voltage drop equal to VSENSE across RS. The
high impedance inputs of the amplifier doesn’t conduct this
current and the high open loop gain of the sense amplifier
forces its non-inverting input to the same voltage as the in-
verting input. In this way the voltage drop across RIN matches
VSENSE. A current proportional to IS according to the following
relation:
Case 1 −2V < VCM ≤ 1.8V
The max voltage at the RG pin is given by the following in-
equality VRG=Vsense*RGAIN *Gm ≤ min(1.3V; Vout_max)
where Vout_max is the maximum allowable output voltage
according to the Electrical Tables.All the gain resistors
(RGAIN) which respect the previous inequality are allowed. The
graphical representation in Figure 2 helps in the selection; all
the combinations (VSENSE, RGAIN) below the curve are al-
lowed.
IS′ = VSENSE/RIN = RS*IS/RIN , where RIN = 1/Gm
flows entirely in the external gain resistor developing a voltage
drop equal to
VG = IS′ *RGAIN = (VSENSE/RIN) *RGAIN = ((RS*IS)/RIN)*RGAIN
This voltage is buffered and showed at the output with a very
low impedance allowing a very easy interface of the LMP8645
with other ICs (ADC, μC…).
VOUT = (RS*IS)*G, where G = RGAIN/RIN
30071604
FIGURE 2. Allowed Gains for CASE 1
As a consequence once selected the gain (RGAIN) the
VSENSE range is fixed too. For example if an application re-
quired a Gain of 10, RG will be 50 kΩ and VSENSE will be in the
range 10 mV to 100 mV.
Case 2 1.8V < VCM ≤ VS
In this case the max voltage at the RG pin is related to the
common mode voltage and VSENSE. So all the RGAIN resistors
which respect the following inequalities are allowed:
30071603
FIGURE 1. Current monitor
VR ≤ min (Vout_max; (VCM - Vsense-250mV))
G
where
SELECTION OF THE SHUNT RESISTOR
VRG = VSENSE*RGAIN*Gm and Vout_max is the maximum
allowable output voltage according to the Electrical Tables.
The accuracy of the current measurement strictly depends on
the value of the shunt resistor RS. Its value depends on the
application and it is a compromise between small-signal ac-
curacy and maximum permissible voltage loss in the mea-
surement section. High values of RS provide better accuracy
at lower currents by minimizing the effects of offset, while low
values of RS minimize voltage loss in the supply section. For
most applications, best performance is obtained with an RS
The graphical representation in Figure 3 helps in the selec-
tion; all the combinations (VSENSE, RGAIN) below the curves for
given VCM and supply voltage are allowed.
11
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the voltage source doesn't have a low impedance an error in
the amplitude's measurement will occur. In this case a buffer
is needed to drive the ADC. The LMP8645 has an internal
output buffer able to drive a capacitance load up to 30 pF or
the input stage of an ADC. If required an external low pass
RC filter can be added at the output of the LMP8645 to reduce
the noise and the bandwidth of the current sense. Any other
filter solution which implies a capacitance connected to the
RG pin is not suggested due to the high impedance of that pin.
30071605
FIGURE 3. Allowed Gains for CASE 2
Also in this case once selected the RGAIN (Gain) the VSENSE
range is fixed too.
Case 3 VCM ≥ VS
The max voltage at the RG pin is Vout_max, it means that
VOUT = VSENSE * RGAIN/RIN ≤ Vout_max where Vout_max is
the maximum allowable output voltage according to the Elec-
trical Tables.So all the RGAIN resistors which respect the
previous inequality are allowed. The graphical representation
in helps in the selection; all the combinations (VSENSE
RGAIN) below the curves are allowed.
,
30071631
FIGURE 5. LMP8645 to ADC interface
SENSING CURRENT IN LED DRIVER APPLICATIONS
The LMP8645 is the right choice in the applications which re-
quires high side current sense, such as High Brightness LED
for automotive where the LED's cathode has to be connected
to the case (ground) of the car. In this case the classical low
side current sense with a shunt resistor connected between
the LED's cathode and the case doesn't guarantee the ground
connection. In Figure 6, the LMP8645 monitors the current for
the LM3406 a constant current buck regulator. The LMP8645
is supplied by the internal LDO of the LM3406 thorough the
pin VCC, the current which flows in the LED is programmed
according the following formula: IF= VCS/(RS*Gain), where
Gain = RGAIN*Gm and VCS=200 mV. In this application the
current which flows in the HB LED is in the range between
350 mA and 1A, so in order to reduce the power dissipation
on the shunt resistor and have a good accuracy, the RS should
be in the range between 50 mΩ and 200 mΩ. In the table
below two examples are analyzed.
30071606
FIGURE 4. Allowed Gains for CASE 3
IF=350mA
40kΩ
IF=1A
Also in this case once selected the RGAIN (Gain) the VSENSE
range is fixed too.
RGAIN
RS
36kΩ
77mΩ
27mΩ
27mW
From the cases showed above a good way to maximize the
output voltage swing of the LMP8645 is to select the max al-
lowable Rgain according to the previous equations. For a
fixed supply voltage and Vsense as the common mode volt-
age increases, the max allowable Rgain increases too.
Dissipated Power 9.5mW
Total Accuracy
≊5%
≊5%
DRIVING ADC
The input stage of an Analog to Digital converter can be mod-
eled with a resistor and a capacitance versus ground. So if
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12
30071608
FIGURE 6. High Side Current Sensing in Driving HP/HB LED
13
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Physical Dimensions inches (millimeters) unless otherwise noted
TSOT-6
NS Package Number MK06A
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14
Notes
15
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Notes
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