935316769518 [NXP]
Switching Regulator;型号: | 935316769518 |
厂家: | NXP |
描述: | Switching Regulator 开关 |
文件: | 总24页 (文件大小:1252K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Document Number: MC34670
Rev. 3.0, 12/2006
escale Semiconductor
Advance Information
IEEE 802.3af PD With Current
Mode Switching Regulator
34670
The 34670 combines a Power Interface Port for IEEE 802.3af
Powered Devices (PD) and a high performance current mode
switching regulator. It allows a designer to build PDs with a minimum
of external components by means of integrating the required IEEE
802.3af functions and all functions necessary to build a high
efficiency DC/DC converter.
POWER OVER ETHERNET
On the PD side the 34670 fully supports the IEEE802.3af standard
and provides complete signature and power classification functions.
It controls inrush current limiting and incorporates adjustable
undervoltage lockout. The switching regulator provides excellent line
and load regulation. It drives an external Power MOSFET with sense
resistor.
EG SUFFIX (PB-FREE)
98ASB42343B
20-PIN SOICW
Features
• Integrated IEEE 802.3af Compliant Interface
• Signature Detection and Classification Functionality
• Integrated Isolation Switch
• Programmable Inrush Current Limiting Control
• Adjustable Undervoltage Lockout
• Input Voltage Range up to 80 V
• Current Mode Control
ORDERING INFORMATION
Temperature
Device
Package
Range (T )
A
MCZ34670EG/R2
-40°C to 85°C
20 SOICW
• Adjustable Oscillator
• Leading Edge Blanking
• Internal Slope Compensation Circuitry
• Input Overvoltage Protection
• 50% Duty Cycle Limitation
• Pb-Free Packaging Designated by Suffix Code EG
RJ-45
PSE HUB OR SWITCH
ETHERNET APPLIANCE (PD)
TX
RX
PHY
PHY
RX
TX
HOST
CONTROLLER
PSE POWER
CONTROLLER
HOST
PROCESSOR
CAT 5
CABLE
SWITCH
-48V
GND
48 V POWER
SUPPLY
34670
PD POWER
CONTROLLER
ISOLATION SWITCH
-48V
DC/DC
Figure 1. 34670 Simplified Application Diagram
* This document contains certain information on a new product.
Specifications and information herein are subject to change without notice.
© Freescale Semiconductor, Inc., 2006. All rights reserved.
RNAL BLOCK DIAGRAM
INTERNAL BLOCK DIAGRAM
FREQ
HIGH VOLTAGE
REGULATOR
VPWR
VDD
2.5V
8V
INTERNAL
SUPPLY
5.7V
0.8R
R
S
R
R
POR
OSC
Q
GATE
SS
RCLA
EN
3.5V
UV or UVLO
UNDERVOLTAGE
UV or UVLO
5µA
LOCKOUT
+
OVERVOLTAGE
DETECTION
0.3V
S
R
CONTROL LOGIC
Q
4.5V
5k
Ω
PWM
COMPARATOR
0.6 - 2.6V
CS
BLANK
0.4V
1.4V
0.6V
+
3
CURRENT
LIMITATION
ILIM
SLOPE
COMP
GATE
DRIVE
COMP
FB
UVLO
TEMP
SENSOR
1.2V
REG
DETECT
R
SENSE
+
250mV
VIN
VOUT
RESET
Figure 2. 34670 Simplified Internal Block Diagram
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
2
PIN CONNECTIONS
PIN CONNECTIONS
1
VPWR
20
19
18
17
16
15
14
VDD
2
3
GATE
VPWR
RCLA
UVLO
TEST1
TEST2
FREQ
CS
FB
4
5
COMP
SS
6
7
RESET
8
13
12
11
ILIM
VIN
VIN
VOUT
VOUT
VOUT
9
10
Figure 3. 34670 Pin Connections
Table 1. 34670 Pin Definitions
Pin Number
Pin Name
Formal Name
Definition
This is the most positive power supply input. The load connects between this pin
and the VOUT pin.
1, 2
VPWR
Positive Supply
Voltage Input
Connect a resistor between RCLA and VIN to select the class of the PD.
3
4
RCLA
UVLO
Classification Resistor
Undervoltage Lookout
Used to adjust the undervoltage lookout threshold voltage, connected to VIN to use
the default threshold voltage.
Connect to VIN in application mode.
5
6
7
TEST1
TEST2
FREQ
Test pins
Adjusts the internal oscillator frequency by connecting a resistor between FREQ
Frequency Adjustment
Inrush Current Limit
and VIN
.
Used to adjust the inrush current limit of the isolation switch, add a resistor
8
ILIM
between ILIM and VIN
.
This is the most negative power supply input.
9
10
VIN
VIN
Negative Supply Voltage
This pin is the drain of the internal Power MOSFET (high current path).
This pin is the drain of the internal Power MOSFET (low current path).
This is an active-low RESET output signal. This pin is referenced to VOUT
11, 12
13
VOUT
VOUT
RESET
Output Voltage
Output Voltage
.
14
RESET Output
(active low)
Connect an external capacitor to SS. The internal current source charges the
capacitor and generates a soft-start ramp.
15
16
17
18
19
20
SS
COMP
FB
Soft Start Input
Compensation Pin
Feedback Input
Current Sense
COMP is the output of the error amplifier and is available for feedback
compensation. COMP is pulled-up by an internal 5.0 kΩ resistor to 5.0 V.
This is the inverting input of the error amplifier. In non-isolated applications it’s
connected to the secondary output through a resistor divider.
The current sense pin CS senses a voltage that is proportional to the current
through the sense resistor.
CS
GATE drives the gate of the external power MOSFET. GATE sources and sinks
up to 1.0 A.
GATE
VDD
Gate Driver Output
VDD Output
VDD mainly supplies the gate of the external power MOSFET. Connect a capacitor
from VDD to VOUT
.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
3
CTRICAL CHARACTERISTICS
MAXIMUM RATINGS
ELECTRICAL CHARACTERISTICS
MAXIMUM RATINGS
Table 2. Maximum Ratings
All voltages are with respect to VIN unless otherwise noted. Exceeding these ratings may cause a malfunction or permanent
damage to the device.
Ratings
Symbol
Value
Unit
ELECTRICAL RATINGS
Power Supply Voltage
Supply Current
V
-0.3 to 80
18
V
mA
V
PWR
I
PWR
VOUT Pins Voltage
UVLO Voltage
V
-0.3 to (V
+ 0.3)
OUT
PWR
V
-0.3 to 10
V
UVLO
RCLA
RCLA Voltage
V
-0.3 to 5.0
-0.3 to 5.0
-0.3 to 5.0
V
ILIM Voltage
V
V
ILIM
FREQ Voltage
VFREQ
V
With respect to:
(2)
(3)
VOUT
VIN
FB, COMP Voltage
VFB, VCOMP
-0.3 to 5.0
-0.3 to 5.0
-0.3 to 16
-0.3 to 80
-0.3 to 80
-0.3 to 80
-0.3 to 80
-0.3 to 80
-0.3 to 80
V
V
V
V
V
V
SS Voltage
SS
VDD Voltage
V
DD
GATE Voltage
CS Voltage
V
-0.3 to (V
+ 0.3)
DD
GATE
V
-0.3 to 5.0
CS
RESET Voltage
V
-0.3 to 15
RESET
ESD Voltage (1)
Human Body Model
Machine Model
V
V
ESD1
±2000
±200
V
ESD2
Output Clamp Energy
E
12
mJ
CL
NotesNotes
1. ESD1 testing is performed in accordance with the Human Body Model (C
= 100 pF, R
= 1500 Ω). ESD2 testing is performed in
ZAP
ZAP
accordance with the Machine Model (C
2. Measured value relative to VOUT
= 200 pF, R
= 0 Ω).
ZAP
ZAP
3. Measured value relative to V
IN
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
4
ELECTRICAL CHARACTERISTICS
MAXIMUM RATINGS
Table 2. Maximum Ratings (continued)
All voltages are with respect to VIN unless otherwise noted. Exceeding these ratings may cause a malfunction or permanent
damage to the device.
Ratings
Symbol
Value
Unit
THERMAL RATINGS
Operating Temperature
Ambient (4)
°C
-40 to 85
120
T
A
Junction (8), (9)
T
J
Storage Temperature
TSTG
-65 to 150
800
°C
Power Dissipation (T = 25 °C) (7)
P
D
mW
°C/W
A
Thermal Resistance
Rθ
JA
103
47
Junction to Ambient
20LD SOIC W/B Package (9)
RθJB
(6)
Peak Package Reflow Temperature During Reflow (5)
Thermal Shutdown Temperature
Thermal Shutdown Recovery Temperature
NotesNotes
,
TPPRT
Note 6
180
°C
°C
°C
T
T
SHUT
150
HYST
4. The limiting factor is junction temperature; taking into account the power dissipation, thermal resistance, and heat sinking.
5. Pin soldering temperature limit is for 10 seconds maximum duration. Not designed for immersion soldering. Exceeding these limits may
cause malfunction or permanent damage to the device.
6. Freescale’s Package Reflow capability meets Pb-free requirements for JEDEC standard J-STD-020C. For Peak Package Reflow
Temperature and Moisture Sensitivity Levels (MSL),
Go to www.freescale.com, search by part number [e.g. remove prefixes/suffixes and enter the core ID to view all orderable parts. (i.e.
MC33xxxD enter 33xxx), and review parametrics.
7. Maximum power dissipation at indicated ambient temperature in free air with no heatsink used.
8. For T = 85°C and P = 700 mW and R = 47°C/W.
θJB
A
D
9. Measured with 4 layers 2s2p JEDEC std. PCB.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
5
CTRICAL CHARACTERISTICS
STATIC ELECTRICAL CHARACTERISTICS
STATIC ELECTRICAL CHARACTERISTICS
Table 3. Static Electrical Characteristics
Characteristics noted under conditions 30 V ≤ VPWR ≤ 60 V, -40°C ≤ TA ≤ 85°C, VIN = 0 V unless otherwise noted. Typical
values noted reflect the approximate parameter means at TA = 25°C under nominal conditions unless otherwise noted.
Characteristic
Symbol
Min
Typ
Max
Unit
SIGNATURE DETECTION
Input Offset Current (1.4 V ≤ V
≤ 9.5 V)
I
—
—
—
10
—
µA
kΩ
PORT
OFFSET
Differential Input Resistance (1.4 V ≤ V
≤ 9.5 V)
R
600
PORT
DIFF
CLASSIFICATION
Classification Current (13.5 V ≤ V
≤ 20 V)
I
mA
PORT
CLASS
Class 0: R
Class 1: R
Class 2: R
Class 3: R
Class 4: R
= 4.42 kΩ
= 475 Ω
= 261 Ω
= 169 Ω
= 113 Ω
0
—
—
—
—
—
4.0
12
20
30
44
CLASS
CLASS
CLASS
CLASS
CLASS
9.0
17
26
36
Classification Current Limit
I
—
—
50
mA
V
CLASS(LIM)
RCLA Reference Voltage (13.5 V ≤ V
≤ 20 V)
V
4.0
4.5
5.0
PORT
RCLA
INRUSH CURRENT LIMITATION (37 V ≤ V
≤ 60 V) (RLIM)
PORT
Input Inrush Current, ILIM connected to VIN
I
I
—
—
350
mA
INRUSH
INRUSH
Input Inrush Current, ILIM connected via resistor R
to VIN
ILIM
R
R
R
= 12.1 kΩ
= 42.2 kΩ
= 191 kΩ
130
70
180
110
65
250
165
100
ILIM
ILIM
ILIM
30
NORMAL OPERATION (VPWR, UVLO)
Supply Voltage
V
—
—
—
4.5
—
60
7.3
40
V
mA
V
PWR
Supply Current (10)
I
PWR
Default Turn-On Voltage (UVLO = VIN
Default Turn-Off Voltage (UVLO = VIN
UVLO Hysteresis when set internally
External UVLO Programming Range
UVLO Reference Voltage
)
)
V
—
UVLO(ON)
V
30
6.0
25
1.96
—
—
—
V
UVLO(OFF)
V
—
—
V
HYST(INT)
V
—
50
V
UVLO(PR)
V
2.0
15
—
2.04
—
V
UVLO(REF)
UVLO Hysteresis when set externally
UVLO Bias Current
V
%
µA
HYST(EXT)
I
—
1.0
UVLO(B)
ISOLATION SWITCH (ILIM)
On-Resistance (V
= 48 V, I
= 350 mA) (11)
PORT
R
—
—
—
500
700
mΩ
PORT
DS(ON)
Isolation Switch Current Limit in Normal Operation Mode
I
380
mA
LIM
Notes
10. GATE pin open, PWM controller running.
11. Measured across VIN and VOUT
.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
6
ELECTRICAL CHARACTERISTICS
STATIC ELECTRICAL CHARACTERISTICS
Table 3. Static Electrical Characteristics(continued)
Characteristics noted under conditions 30 V ≤ VPWR ≤ 60 V, -40°C ≤ TA ≤ 85°C, VIN = 0 V unless otherwise noted. Typical
values noted reflect the approximate parameter means at TA = 25°C under nominal conditions unless otherwise noted.
Characteristic
PWM COMPARATOR (COMP)
Symbol
Min
Typ
Max
Unit
COMP Control Voltage Range
COMP Input Bias Current
V
1.3
—
—
—
4.0
1.8
V
COMP
I
mA
COMP(B)
HIGH VOLTAGE REGULATOR
Regulator Output Voltage
VDD
8.0
9.0
10
—
V
V
REG
Regulator Turn-Off Voltage (12)
V
VDD
Reg
REG(OFF)
+0.5
Regulator Current Limitation (13)
Regulator Continuous Current
GATE DRIVER (UVLO)
Gate Driver UVLO, Rising
Gate Driver UVLO, Falling
CURRENT LIMIT (CS)
CS Threshold Voltage
CS Bias Current
I
7.0
—
—
15
mA
mA
REGLIM
I
—
5.0
REGDC
V
VDD-0.5
—
—
—
—
V
V
GATE(R)
V
6.5
GATE(F)
V
320
—
400
—
480
30
mV
CS
I
µA
CS(B)
ERROR AMPLIFIER
Reference Voltage
V
1.164
1.2
1.236
V
REF
OVERVOLTAGE SHUTDOWN
OVLO Threshold, Rising
OVLO Threshold, Falling
OVLO Hysteresis
V
66
63
—
—
—
72
69
—
V
V
V
OV(R)
V
OV(F)
V
3.0
OV(HYS)
SOFT-START (SS)
SS Output Voltage
V
—
3.25
—
2.0
5.0
2.0
—
V
µA
mA
V
SS
SS Source Current
I
6.75
2.25
SS(OUT)
SS Sink Current
I
SS(IN)
Shutdown Threshold Voltages
V
0.48
0.24
0.6
0.3
0.72
0.40
SS(R)
V
SS(F)
THERMAL SHUTDOWN
Thermal Shutdown Temperature
Thermal Hysteresis
T
150
—
165
30
180
—
°C
°C
SHUTDOWN
T
HYS
Notes
12. An external voltage has to be applied.
13. Thermal limitations of the device might derate usable current range.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
7
CTRICAL CHARACTERISTICS
DYNAMIC ELECTRICAL CHARACTERISTICS
DYNAMIC ELECTRICAL CHARACTERISTICS
Table 4. Dynamic Electrical Characteristics
Characteristics noted under conditions 30 V ≤ VPWR ≤ 60 V, -40°C ≤ TA ≤ 85°C, VIN = 0 V unless otherwise noted. Typical
values noted reflect the approximate parameter means at TA = 25°C under nominal conditions unless otherwise noted.
Characteristic
Symbol
Min
Typ
Max
Unit
NORMAL OPERATION
Turn-On Filter Time
Turn-Off Filter Time
PWM COMPARATOR
t
—
—
200
200
—
—
µs
µs
FILT(ON)
t
FILT(OFF)
Slope Compensation Ramp as a Function of Switching Frequency
mV/µs
f
f
f
= 100 kHz
= 250 kHz
= 400 kHz
m
—
—
—
10
25
40
—
—
—
PWM
PWM
PWM
100
m
250
m
400
Duty Cycle Limit (14)
GATE DRIVER
D
—
—
48
%
MAX
Rise Time (10% - 90%), C
Fall Time (90% - 10%), C
= 2.0 nF, VDD
= 9.0 V
REG
t
—
—
—
—
50
30
ns
ns
Load
R
= 2.0 nF, VDD
= 9.0 V
REG
t
Load
F
CURRENT LIMIT
Blanking Time (14)
PWM OSCILLATOR
t
40
50
60
ns
BLANK
Default Clock Frequency (FREQ connected to VIN
Oscillator Frequency Adjusting Resistor Range
)
f
175
121
320
80
225
—
325
499
480
120
kHz
kΩ
PWM
R
FREQ
Oscillator Frequency Range, R
Oscillator Frequency Range, R
ERROR AMPLIFIER
= 121 kΩ
= 499 kΩ
fRANGE
fRANGE
—
kHz
kHz
FREQ
—
FREQ
Gain Bandwidth (14)
GBW
1.0
—
—
—
—
MHz
dB
DC Open Loop Gain
A
80
VOL
RESET OUTPUT
RESET Output Low Voltage (I
= 20 mA)
V
—
—
—
0.8
—
V
RESET, SINK
RESET,LOW
tRESET
RESET Output Filter Time
20
µs
Notes
14. Guaranteed by design. Not production tested.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
8
ELECTRICAL CHARACTERISTICS
TYPICAL SWITCHING WAVEFORMS
TYPICAL SWITCHING WAVEFORMS
w/o snubber
w/ snubber
w/ snubber
w/o snubber
Figure 4. Drain Voltage of Switching MOSFET
Figure 6. Secondary Voltage before Diode
Figure 5. Secondary and Output Voltage
Figure 7. Gate Voltage and Voltage at CS pin
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
9
CTRICAL CHARACTERISTICS
ELECTRICAL PERFORMANCE CURVES
ELECTRICAL PERFORMANCE CURVES
MC34670 Efficiency Plot: Vo = 5V, w/o bias winding, Coilcraft
DA2142-AL
90.00
85.00
80.00
75.00
70.00
65.00
60.00
55.00
50.00
57V
48V
36V
0.40 0.60 0.80 1.00 1.20 1.40 1.60 1.80 2.00
IO [A]
MC34670 Efficiency Plot: Vo = 5V, w/ bias winding, Coilcraft
DA2362-AL
90.00
85.00
80.00
75.00
70.00
65.00
60.00
55.00
50.00
57V
48V
36V
0.40 0.60 0.80 1.00 1.20 1.40 1.60 1.80 2.00
IO [A]
Figure 8. Efficiency Plot
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
10
FUNCTIONAL DESCRIPTION
INTRODUCTION
FUNCTIONAL DESCRIPTION
INTRODUCTION
The 34670 combines a Power Interface Port for IEEE
802.3af Powered Devices (PD) and a high performance
current mode switching regulator. It allows a designer to build
PDs with a minimum of external components by means of
integrating the required IEEE 802.3af functions and all
functions necessary to build a high efficiency DC/DC
converter. Thus 34670 gives the system designer a device
that drastically reduces cost and board space.
The 34670 also offers an input overvoltage detection to
protect the external switching MOSFET by disabling the gate
driver in case of input line overvoltage.
The switching regulator provides excellent line and load
regulation. It drives an external power MOSFET with sense
resistor. The switching frequency is adjustable between
100 kHz and 400 kHz. The output voltage feedback
information can be accomplished by an optocoupler, if
isolation is required.
On the PD side the 34670 fully supports the IEEE802.3af
standard and provides complete signature detection and
power classification functions. It controls inrush current
limiting and incorporates an adjustable undervoltage lockout.
The 34670 includes thermal protection circuitry to protect the
device in case of high power dissipation.
An internal logic control block manages the sequencing of
signature detection, classification and proper turn on and turn
off of the DC/DC converter.
FUNCTIONAL PIN DESCRIPTION
POSITIVE SUPPLY VOLTAGE INPUT (VPWR)
RESET OUTPUT (RESET)
This is the most positive power supply input. The load
connects between this pin and the VOUT pin.
This is an active-low RESET output signal. This pin is
referenced to VOUT
.
CLASSIFICATION RESISTOR (RCLA)
SOFT START INPUT (SS)
Connect a resistor between RCLA and VIN to select the
class of the PD.
Connect an external capacitor to SS. The internal current
source charges the capacitor and generates a soft-start
ramp.
UNDERVOLTAGE LOOKOUT (UVLO)
COMPENSATION PIN (COMP)
Used to adjust the undervoltage lookout threshold voltage,
connected to VIN to use the default threshold voltage.
COMP is the output of the error amplifier and is available
for feedback compensation. COMP is pulled-up by an
internal 5.0 kΩ resistor to 5.0 V.
TEST PINS (TEST1, TEST2)
Connect to VIN in application mode.
FEEDBACK INPUT (FB)
This is the inverting input of the error amplifier. In non-
isolated applications it’s connected to the secondary output
through a resistor divider.
FREQUENCY ADJUSTMENT (FREQ)
Adjusts the internal oscillator frequency by connecting a
resistor between FREQ and VIN.
CURRENT SENSE (CS)
INRUSH CURRENT LIMIT (ILIM)
The current sense pin CS senses a voltage that is
proportional to the current through the sense resistor.
Used to adjust the inrush current limit of the isolation
switch, add a resistor between ILIM and VIN.
GATE DRIVER OUTPUT (GATE)
NEGATIVE SUPPLY VOLTAGE (VIN)
GATE drives the gate of the external power MOSFET.
GATE sources and sinks up to 1.0 A.
This is the most negative power supply input.
OUTPUT VOLTAGE (VOUT)
VDD OUTPUT (VDD)
This pin is the drain of the internal Power MOSFET (high
current path and low current path).
VDD mainly supplies the gate of the external power
MOSFET. Connect a capacitor from VDD to VOUT
.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
11
CTIONAL DEVICE OPERATION
OPERATIONAL MODES
FUNCTIONAL DEVICE OPERATION
OPERATIONAL MODES
POWER DEVICES (PD) INTERFACE
The PD interface of the 34670 has been designed to
comply with the requirements of the IEEE standard 802.3af.
The device operates in three different modes, depending on
the input voltage.
I
PD OPERATING MODES
The IEEE 802.3af standard defines three operating modes
in general. These modes are summarized in Table 5.
I2
I1
Table 5. PD Operating Modes
Operating Mode
Voltage at PD Input Connector
Signature Resistor Detection
Classification
2.7 V - 10.1 V
14.5 V - 20.5 V
37 V - 57 V
Normal Operation Mode
V
V1
V2
SIGNATURE RESISTOR DETECTION
A PD shall present a valid detection signature at the PD
input connector to get properly detected as a power over LAN
enabled pin. Valid and non-valid detection signature regions
are separated by guard bands. See Figure 9 for valid and
non-valid signature regions.
V
– V
2
1
dR = --------------------
– I
I
2
1
Figure 10. dR Measurement
It can be seen in Figure 11, that a signature resistor of
25 kΩ as defined in IEEE 802.3af and two diodes in series
would lead to an effective resistance out of the valid region
specified in Figure 9. At low voltages the effective resistance
is above the maximum allowed value of 26.25 kΩ, as
illustrated in Figure 11. Therefore one has to adjust the
signature resistor RSIG (R1 and R2, see UVLO Adjustment
on page 13) to a value below 25 kΩ to stay within the valid
region.
valid region
non-valid region
non-valid region
Signature [kΩ]
12
23.75 26.25
45
Figure 9. Signature Resistance Guard Bands
The effective resistance across the input pins is calculated
by two subsequent voltage-current measurements made
during the detection process by the PSE.
VALID PD DETECTION SIGNATURE
CHARACTERISTICS
During signature detection phase the Power Sourcing
Equipment (PSE) applies a voltage in the range 2.7 V -
10.1 V on the PI connector and looks for the 25 kΩ signature
resistor. Since the PD circuitry includes bridge rectifiers, the
PD has to compensate for the voltage drop across the diodes
and the diodes serial resistance. The effective signature
resistance dR is obtained by the V-I-Slope measurement of
the PSE (Figure 10).
Figure 11. dR at Low Input Voltages
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
12
FUNCTIONAL DEVICE OPERATION
OPERATIONAL MODES
CLASSIFICATION
CLASSIFICATION SIGNATURE LOAD CURRENT
A PD may optionally be classified by the PSE. The intent
of classification is to provide a method for more efficient
power allocation through the PSE. The PD classification
allows the PSE to identify four different (power) classes
depending on the required power that the PD will draw during
normal operation. The classes and the corresponding
maximum power drawn by the PD is shown in Table 6.
The implementation for the classification circuitry is shown
in Figure 12.
+VPORT
34670
VPWR
Table 6. PD Classes
Maximum Power
Vref
+
-
Class
Usage
EN
[W]
0
1
2
3
4
Default
Optional
Optional
Optional
Reserved
0.44 - 12.95
0.44 - 3.84
3.84 - 6.49
6.49 - 12.95
—
RCLA
ICLASS
VIN
RCLASS
-VPORT
PD CLASSES
Figure 12. Classification Circuitry
During classification probing by the PSE, the PD applies
the appropriate load current onto the line. The PSE measures
the load current and can determine the classification as
described in Table 7.
A constant voltage is applied at pin RCLA and depending
on the resistor RCLASS, a current from +VPORT to -VPORT is
flowing with the following relation:
VRCLA
ICLASS = --------------------
RCLASS
.
Table 7. PD Class vs. Classification Current
ICLASS is the classification current that is measured by the
PSE. The values for the RCLASS resistor corresponding to the
appropriate class are listed in Table 8.
Classification Current [mA]
Class
Condition
Min
Max
Table 8. PD Class vs. Classification Resistor RCLASS
14.5 - 20.5 Volts
measured at PD
input connector
0
1
2
3
4
0
4
RCLASS [Ω]
4.42k
475
Class
Classification Current [mA]
9
12
20
30
44
0
1
2
3
4
2.0
10.5
18.5
28
17
26
36
261
169
40
113
UVLO ADJUSTMENT
The 34670 has default UVLO settings that corresponds to
the IEEE 802.3af standard. Nevertheless the user can adjust
the UVLO by an external resistor divider as sketched in
Figure 13. Since the UVLO resistor divider replaces the
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
13
CTIONAL DEVICE OPERATION
OPERATIONAL MODES
signature resistor, the total resistance of R1+R2 must equal
25 kΩ.
R
= R
– R
SIG
1
2
VUVLO(OFF) = VUVLO(ON) ⋅ 0.85
+VPORT
The typical turn-off voltage VUVLO(OFF) is 85% of the turn
VPWR
on voltage VUVLO(ON)
.
RCLA
INRUSH CURRENT LIMITATION
The 34670 has been designed to interface also with legacy
PoE-PSEs which do not meet the inrush current requirement
of the IEEE 802.3af specification. By setting the initial inrush
current limit to a low level, a PD using the 34670 minimizes
the current drawn from the PSE during start-up. The
maximum inrush current level can be set by connecting a
resistor from ILIM to VIN as illustrated in Figure 15.
R1
UVLO
R2
ILIM
VIN
-VPORT
+VPORT
Figure 13. UVLO Adjustment by External
Resistor Divider
VPWR
To use the default settings for UVLO, the pin UVLO must
be connected to VIN. In this case, a valid signature resistor
has to be placed between -VPORT and +VPORT. This
configuration can be seen in Figure 14.
RCLASS
RCLA
RSIG
25kΩ
+VPORT
UVLO
RILIM
ILIM
VPWR
VIN
RCLA
-VPORT
RSIG
25kΩ
Figure 15. Inrush Current Limitation by External
Resistor RILIM
UVLO
ILIM
The following table shows the selectable current limits and
the corresponding resistor value that has to be connected
between pins ILIM and VIN:
VIN
-VPORT
Table 9. Inrush Current Limit vs. RILIM
Figure 14. Default UVLO Settings
Inrush Current Limit [mA]
R
Value [kΩ]
ILIM
To calculate the values for R1 and R2 the following
equations should be used:
180
110
65
12.1
42.2
191
R
+ R = R
SIG
1
2
VUVLO(REF)
---------------------------------
VUVLO(ON)
R
=
⋅ R
SIG
2
After powering up, the 34670 switches to the high level
current limit, thereby allowing the PD to consume up to
12.95 W if a 802.3af PSE is present.
where VUVLO(ON) is the desired turn-on voltage threshold and
UVLO(ref) the UVLO reference voltage.
V
PULSE WITH MODULATOR CONTROLLER
diode reverse recovery current of the power circuit. The
leading-edge blanking of the CS signal prevents the PWM
comparator from premature termination of the on cycle.
CURRENT-MODE CONTROL OPERATION
The 34670 offers current-mode control operation with
leading-edge blanking. The current-limit comparator monitors
the CS pin at all times and provides cycle-by-cycle current
limit.
The 34670 limits the duty cycle to 50%. This is
advantageous for applications which are not allowed to
exceed an on-time of 50 % of the switching period TS. Beside
the duty-cycle limit, slope compensation is provided to
stabilize the inner current loop and avoid oscillations for
The CS signal contains a leading-edge spike that is the
result of the MOSFET gate charge current, capacitive and
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
14
FUNCTIONAL DEVICE OPERATION
OPERATIONAL MODES
converters running in continuos conduction mode (CCM).
The value of the slope compensation depends on the
switching frequency. See Table 10.
T1
NP
NS
Table 10. Slope Compensation Values
Switching Frequency [kHz]
Slope Compensation [mV/µs]
100
250
400
10
25
50
RV
ISOLATED OPTOCOUPLER FEEDBACK
Isolated voltage feedback can be accomplished by using
an optocoupler and a shunt regulator (see Figure 19). The
output voltage accuracy is a function of the accuracy of the
shunt regulator and feedback resistor divider tolerance,
therefore the feedback resistors should have an appropriate
accuracy.
R1
R2
Since the error amplifier function is implemented on the
secondary side by the optocoupler and a 3-pin adjustable
shunt regulator, the internal error amplifier of the 34670 is not
used. The FB pin is connected to VOUT, thus disabling the
internal open-drain error amplifier.
TLV431
Figure 16. Isolated Optocoupler Feedback
The bias voltage for the optocoupler is accomplished
through the internal 5.0 kΩ pull-up resistor between COMP
and an internal 5.0 V reference.
ISOLATED PRIMARY CONTROL FEEDBACK
Another option to accomplish isolated feedback is the use
of a tertiary winding (see Figure 21). The advantage of this
solution without optocoupler and shunt regulator is clearly the
cost effectiveness. Nevertheless the line and load regulation
is worse than with optocoupler feedback.
When a TL431 or TLV431 shunt regulator is used for
output voltage regulation, the output voltage is set by the ratio
of resistors R1 and R2, see Figure 16 for details. The output
voltage is given by the following equation:
When isolated primary feedback is used, the loop
compensation components are connected between pins
COMP and FB.
R
⎛
⎞
⎟
⎠
1
V
= V
⋅ 1 + -------
⎜
O
REF
R
⎝
2
where VREF = 1.24 V for the TLV431 (VREF = 2.5 V for the
TL431).
INTERNAL REGULATORS
The internal high voltage regulator of the 34670 regulates
from the input voltage across VPWR and VIN down to the
VDD voltage. During start-up the high voltage regulator
provides the necessary voltage for the internal gate driver to
commence switching. If the external MOSFET gate drive
pulls less than 3.0 mA under all circumstances, an auxiliary
transformer winding that usually provides the bias voltage for
the chip and the gate driver is not required.
In cases where the external MOSFET gate drive pulls
more than 5.0 mA, an auxiliary winding is needed to reduce
the power dissipation in the internal high voltage LDO. See
Figure 18 for an application drawing. It is recommended to
add a 0.1 µF ceramic capacitor in parallel with the existing
load capacitor. This reduces noise at the VDD pin caused by
the auxiliary winding.
The high voltage regulator is disabled when the VDD pin is
forced by an external voltage above the VDD regulation point.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
15
CTIONAL DEVICE OPERATION
OPERATIONAL MODES
This reduces power dissipation in the device and improves
overall efficiency.
When the overvoltage protection is triggered
(VPWR > VOV(R)), the gate driver is immediately disabled. At
the same time, the slow discharge of CSS is initiated. While
the soft-start capacitor is discharging, the gate driver remains
disabled. Once VSS = 0.3 V and the overvoltage
(VPWR < VOV(F)) condition disappears, operation resumes
through a regular soft-start.
12
VREG(OFF)
10
VGATE(R)
CURRENT-SENSE COMPARATOR
8
The current-sense (CS) comparators and its associated
circuitry limits the peak current through the MOSFET. Current
is sensed at CS pin as a voltage across the sense resistor
VGATE(F)
6
4
2
RCS between the source of the MOSFET and VOUT
.
The CS input has two voltage trip levels, a 600mV high
limit and a 400 mV low limit. When the voltage on CS
produced by a current through the current sense resistor
exceeds the high limit threshold, the current ON-cycle is
immediately terminated and the GATE output is pulled low.
t
GATE enable
If the low limit threshold is exceeded for longer than 50 ns
(typical blanking time), the current ON-cycle is also
terminated. The blanking time ensures a false termination of
the switching cycle caused by the leading-edge spike on the
sense waveform.
HVReg enable
Figure 17. VDD and MOSFET Driver Output Behavior
A load capacitor connected to VDD ensures a proper
filtering of the VDD voltage. The minimum capacitance value
for this load capacitor should be at least 10 µF. An electrolytic
type capacitor is sufficient.
The current-sense resistor RCS is selected according to
the following equation:
400mV
R
= ----------------------------------------
CS
I
LIM(primary)
Please refer to application note A/N3279 for further
information about the size of the capacitor.
where ILIM(primary) is the maximum peak primary-side
current.
If VDD falls below the UVLO threshold, the voltage
regulator is disabled and the MOSFET driver output (GATE)
is held low.
In case of an overcurrent in the external MOSFET the
current switching cycle is terminated and GATE is pulled low.
The soft-start capacitor CSS is discharged and after removal
of the faulty condition the PWM is re-started through a regular
soft start.
PWM CONTROLLER UVLO, SOFT-START, AND
SHUTDOWN FUNCTION
The soft-start function provided by the 34670 allows the
output voltage to ramp up in a controlled way, thus
eliminating output voltage overshoot.
PWM OSCILLATOR
A default 250 kHz oscillator sets the switching frequency
of the PWM controller. The frequency of the oscillator can be
adjusted between 100 kHz and 400 kHz by an optional
external resistor RFREQ connected from the FREQ pin of the
integrated circuit to VIN.
While the PWM controller is in undervoltage lockout, the
capacitor CSS connected to the SS pin is fully discharged.
After coming out of undervoltage lockout, an internal current
source starts charging the capacitor CSS to initiate soft-start.
When VSS has reached 0.6 V, the gate driver is enabled and
PWM operation begins. The duty cycle during soft-start is
primarily controlled by the internal sawtooth voltage and the
voltage at the SS pin. If the voltage at the SS pin is above
2.6 V, the regular PWM control through pins CS, COMP, and
FB takes over and soft-start is finished.
The appropriate switching frequency fPWM can be
calculated as shown below:
47920
f
[kHz] = ----------------------------------- + 4
PWM
R
[kΩ]
FREQ
where fPWM is the PWM switching frequency and RFREQ is the
frequency adjusting resistor.
The following equation calculates the total soft-start time:
t
[ms] = 0.4 ⋅ C
[nF]
To use the default frequency of 250 kHz the FREQ pin can
be connected to VIN or can be left open.
SS
SS
OVERVOLTAGE SHUTDOWN
RESET OUTPUT
The 34670 includes an overvoltage protection (OVP)
feature that turns off the external MOSFET when the input
voltage exceeds the overvoltage threshold.
The RESET pin is an open drain output. The reset control
circuit supervises the FB voltage and recognizes if the output
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
16
FUNCTIONAL DEVICE OPERATION
OPERATIONAL MODES
voltage is out of regulation. In this case the RESET pin is
pulled low.
N-CHANNEL MOSFET GATE DRIVER
GATE drives an N-channel MOSFET. GATE sources and
sinks large transient currents up to 1.0 A to charge and
discharge the MOSFET gate. The GATE output is supplied
by the internal generated VDD voltage, which is internally set
to approximately 9.0 V.
The RESET output can only be used in non-isolated
applications.
There is a 20 µs delay filter preventing erroneous RESET
output pulses. During soft-start, RESET is held low. RESET
is released when the PWM controller is in regulation.
For Power-over-Ethernet applications, the used MOSFET
must be able to withstand a DC level of ~60 V plus the
reflected voltage at the primary side of the transformer. This
requires a MOSFET rated at 150 V or 200 V.
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
17
CAL APPLICATIONS
TYPICAL APPLICATIONS
Please refer to application note AN3279 for further information of PD design and layout recommendations.
T1
NAUX
+VPORT
VOUT = 5V@2A
3
NP
NS
34670
RX
VPWR
RCLA
6
1
RESET
VDD
TX
RV
CDD 0.1
F
2
CPORT
M1
R1
R2
GATE
CS
RCLASS
CIN
UVLO
ILIM
RCS
4
5
VIN SS
FREQ COMP FB VOUT
-VPORT
CSS
7
8
Figure 18. Isolated Flyback Converter with Bias Winding
+VPORT
VOUT = 5V@2A
D1
T1
RX+
3
NP
NS
34670
RX
TX
RX-
TX+
VPWR
RESET
RCLA
VDD
6
1
TX-
RV
2
CDD
CPORT
M1
R1
R2
GATE
CS
RCLASS
CIN
UVLO
ILIM
RCS
4
5
VIN SS
FREQ COMP FB VOUT
SPARE+
SPARE-
-VPORT
CSS
7
8
Figure 19. Isolated Flyback Converter without Bias Winding
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
18
TYPICAL APPLICATIONS
T1
+VPORT
NR
NP
3
NS
34670
RX
TX
VPWR
RCLA
6
1
RESET
VDD
RV
2
CDD
CPORT
M1
R1
R2
GATE
CS
RCLASS
CIN
UVLO
ILIM
RCS
4
5
Rv1
Rv2
VIN SS
FREQ COMP FB VOUT
-VPORT
CSS
7
8
Figure 20. Isolated Forward Converter
T1
CAUX
NAUX
+VPORT
VOUT = 5V@2A
3
NP
NS
34670
RX
TX
VPWR
RESET
RCLA
VDD
6
1
2
CDD
CPORT
M1
R1
GATE
RCLASS
CIN
UVLO
ILIM
CS
R2
RCS
4
5
VIN SS
FREQ COMP FB VOUT
-VPORT
C2
CSS
R2
7
8
C1
Figure 21. Isolated Flyback with Primary Control
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
19
CAL APPLICATIONS
+VPORT
VOUT = 5V@2A
T1
3
D1
NP
NS
CO
34670
RX
VPWR
RCLA
6
RESET
VDD
1
TX
2
CDD
CPORT
M1
R3
R4
GATE
CS
RCLASS
CIN
UVLO
ILIM
RCS
4
5
VIN SS
FREQ COMP FB VOUT
R1
Rb
-VPORT
C2
CSS
R2
7
8
C1
Figure 22. Non-Isolated Flyback Converter
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
20
REFERENCE DOCUMENTS
REFERENCE DOCUMENTS
Table 11. Reference Documents
Title
LIterature Order Number
Publication Date
IEEE Std 802.3af™-2003
IEEE Std 802.3af™-2003
AN3279
18 June 2003
MC34670 Usage and Configuration
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
21
KAGING
PACKAGE DIMENSIONS
PACKAGING
PACKAGE DIMENSIONS
For the most current package revision, visit www.freescale.com and perform a keyword search using the “98A” listed below.
EG SUFFIX (PB-FREE)
20-PIN
PLASTIC PACKAGE
98ASB42343B
ISSUE J
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
22
REVISION HISTORY
REVISION HISTORY
Revision
Date
8/2006
Description of Changes
• Initial release
1.0
2.0
• Change to UVLO Hysteresis when set internally on page 6, Regulator Current Limitation
(13) on page 7, OVLO Threshold, Rising on page 7, OVLO Threshold, Falling on page 7,
Shutdown Threshold Voltages on page 7, and Default Clock Frequency (FREQ
connected to VIN) on page 8
9/2006
• Changed Data Sheet category to “Advanced Information*”
• Typ and Max change to RCLA Reference Voltage (13.5 V ≤ VPORT ≤ 20 V) on page 6
• Deleted Oscillator Frequency Adjusting Resistor Range in Static Electrical
Characteristics
12/2006
3.0
• Split Oscillator Frequent Range into two parameters, Oscillator Frequency Range,
RFREQ = 121 kΩ on page 8 and Oscillator Frequency Range, RFREQ = 499 kΩ on page 8
• Added note to Duty Cycle Limit (14) on page 8, Blanking Time (14) on page 8, and Gain
Bandwidth (14) on page 8
• Changed nomenclature for Peak Package Reflow Temperature During Reflow (5) (6)
on
,
page 5
• Changed name and value for Thermal Shutdown Recovery Temperature on page 5
34670
Analog Integrated Circuit Device Data
Freescale Semiconductor
23
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© Freescale Semiconductor, Inc., 2006. All rights reserved.
MC34670
Rev. 3.0
12/2006
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