SA5230D-T [NXP]
IC OP-AMP, 4000 uV OFFSET-MAX, 0.6 MHz BAND WIDTH, PDSO8, PLASTIC, SO-8, Operational Amplifier;型号: | SA5230D-T |
厂家: | NXP |
描述: | IC OP-AMP, 4000 uV OFFSET-MAX, 0.6 MHz BAND WIDTH, PDSO8, PLASTIC, SO-8, Operational Amplifier 放大器 光电二极管 |
文件: | 总16页 (文件大小:142K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
INTEGRATED CIRCUITS
NE5230/SA5230
Low voltage operational amplifier
Product data
2001 Aug 03
Supersedes data of 1994 Aug 31
File under Integrated Circuits, IC11 Handbook
Philips
Semiconductors
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
DESCRIPTION
PIN CONFIGURATION
The NE5230 is a very low voltage operational amplifier that can
perform with a voltage supply as low as 1.8 V or as high as 15 V.
In addition, split or single supplies can be used, and the output will
swing to ground when applying the latter. There is a bias adjusting
pin which controls the supply current required by the device and
thereby controls its power consumption. If the part is operated at
±0.9 V supply voltages, the current required is only 110 µA when the
current control pin is left open. Even with this low power
consumption, the device obtains a typical unity gain bandwidth of
180 kHz. When the bias adjusting pin is connected to the negative
supply, the unity gain bandwidth is typically 600 kHz while the supply
current is increased to 600 µA. In this mode, the part will supply full
power output beyond the audio range.
N, D Packages
1
8
7
6
5
NC
V
NC
2
–IN
CC
–
+
3
4
+IN
OUTPUT
V
EE
BIAS ADJ.
SP00250
Figure 1. Pin Configuration
The NE5230 also has a unique input stage that allows the
common-mode input range to go above the positive and below the
negative supply voltages by 250 mV. This provides for the largest
possible input voltages for low voltage applications. The part is also
internally-compensated to reduce external component count.
APPLICATIONS
• Portable precision instruments
• Remote transducer amplifier
• Portable audio equipment
The NE5230 has a low input bias current of typically ±40 nA, and a
large open-loop gain of 125 dB. These two specifications are
beneficial when using the device in transducer applications. The
large open-loop gain gives very accurate signal processing because
of the large “excess” loop gain in a closed-loop system.
• Rail-to-rail comparators
• Half-wave rectification without diodes
The output stage is a class AB type that can swing to within 100 mV
of the supply voltages for the largest dynamic range that is needed
in many applications. The NE5230 is ideal for portable audio
equipment and remote transducers because of its low power
consumption, unity gain bandwidth, and 30 nV/√Hz noise
specification.
• Remote temperature transducer with 4 to 20 mA output
transmission
FEATURES
• Works down to 1.8 V supply voltages
• Adjustable supply current
• Low noise
• Common-mode includes both rails
• V
within 100 mV of both rails
OUT
ORDERING INFORMATION
DESCRIPTION
TEMPERATURE RANGE
0 °C to +70 °C
ORDER CODE
NE5230D
DWG #
SOT96-1
SOT97-1
SOT96-1
SOT97-1
8-Pin Plastic Small Outline (SO) Package
8-Pin Plastic Dual In-Line Package (DIP)
8-Pin Plastic Small Outline (SO) Package
8-Pin Plastic Dual In-Line Package (DIP)
0 °C to +70 °C
NE5230N
–40 °C to +85 °C
–40 °C to +85 °C
SA5230D
SA5230N
2
2001 Aug 03
853-0942 26836
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
ABSOLUTE MAXIMUM RATINGS
SYMBOL
PARAMETER
RATING
18
UNIT
V
V
V
V
Single supply voltage
Dual supply voltage
CC
±9
V
S
1
Input voltage
±9 (18)
V
IN
1
Differential input voltage
±V
S
V
V
V
P
Common-mode voltage (positive)
Common-mode voltage (negative)
V
+0.5
–0.5
V
CM
CM
D
CC
V
V
EE
2
Power dissipation
500
150
mW
°C
s
2
T
j
Operating junction temperature
2, 3
80Output short-circuit duration to either power supply pin
Storage temperature
Indefinite
–65 to 150
230
T
stg
°C
°C
T
sld
Lead soldering temperature (10sec max)
NOTES:
1. Can exceed the supply voltages when V ≤ ±7.5 V (15 V).
S
2. The maximum operating junction temperature is 150 °C. At elevated temperatures, devices must be derated according to the package
thermal resistance and device mounting conditions. Derate above 25 °C at the following rates:
N package at 9.5 mW/°C
D package at 6.25 mW/°C
3. Momentary shorts to either supply are permitted in accordance to transient thermal impedance limitations determined by the package and
device mounting conditions.
RECOMMENDED OPERATING CONDITIONS
PARAMETER
RATING
1.8 to 15
UNIT
Single supply voltage
V
V
V
V
Dual supply voltage
±0.9 to ±7.5
Common-mode voltage (positive)
Common-mode voltage (negative)
V
CC
+0.25
V
EE
–0.25
Temperature
NE grade
SA grade
0 to +70
–40 to +85
°C
°C
3
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
DC AND AC ELECTRICAL CHARACTERISTICS
Unless otherwise specified, ±0.9V ≤ V ≤ +7.5 V or equivalent single supply, R =10 kΩ, full input common-mode range, over full operating
S
L
temperature range.
NE5230/SA5230
SYMBOL
PARAMETER
TEST CONDITIONS
BIAS
UNIT
Min
Typ
0.4
3
Max
T
= 25 °C
= 25 °C
Any
Any
3
amb
V
V
Offset voltage
mV
OS
T
4
amb
Drift
Any
2
5
µV/°C
OS
T
= 25 °C
= 25 °C
High
Low
High
Low
High
Low
High
Low
High
Low
High
Low
Low
High
Low
High
Low
High
Low
High
Any
3
50
amb
T
amb
3
30
I
I
I
I
Offset current
nA
nA/°C
nA
OS
100
60
0.5
0.3
40
1.4
1.4
150
60
Drift
OS
B
T
amb
= 25 °C
= 25 °C
T
amb
20
Bias current
Drift
200
150
4
2
nA/°C
µA
B
2
4
T
amb
= 25 °C
= 25 °C
110
600
160
750
250
800
550
1.6
600
1.7
T
amb
V
V
= ±0.9 V
= ±7.5 V
S
I
S
Supply current
T
amb
= 25 °C
= 25 °C
320
1.1
T
amb
µA
S
–
+
V
≤ 6 mV, T
= 25 °C
V –0.25
V +0.25
OS
amb
V
Common-mode input range
Common-mode rejection ratio
V
CM
–
+
Any
V
V
R = 10 kΩ; V
= ±7.5 V;
S
CM
Any
85
95
T
amb
= 25 °C
CMRR
PSRR
V
S
= ±7.5 V
dB
R
= 10 kΩ; V
= ±7.5 V
Any
High
Low
High
Low
Any
80
90
85
75
80
4
S
CM
T
= 25 °C
= 25 °C
105
95
amb
T
amb
Power supply rejection ratio
dB
source
V = ±7.5 V
S
10
15
5
sink
source
sink
V
S
V
S
V
S
= ±7.5 V
= ±7.5 V
= ±7.5 V
Any
5
Any
1
Any
2
6
I
L
Load current
mA
source
sink
V
S
V
S
V
S
V
S
= ±0.9 V; T
= 25 °C
= 25 °C
= 25 °C
= 25 °C
High
High
High
High
High
Low
High
Low
4
6
amb
= ±0.9 V; T
5
7
amb
source
sink
= ±7.5 V; T
16
32
2000
750
amb
= ±7.5 V; T
amb
R = 10 kΩ; T
L
= 25 °C
= 25 °C
amb
120
60
V/mV
V/mV
amb
R = 10 kΩ; T
L
A
VOL
Large-signal open-loop gain
V = ±7.5 V
S
100
50
4
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
DC AND AC ELECTRICAL CHARACTERISTICS (Continued)
NE5230/SA5230
UNIT
SYMBOL
PARAMETER
Output voltage swing
Slew rate
TEST CONDITIONS
BIAS
Min
750
Typ
800
800
Max
T
= 25 °C +SW
= 25 °C –SW
+SW
Any
Any
Any
Any
Any
Any
Any
Any
High
Low
High
Low
Any
High
Low
High
Low
amb
T
amb
750
V
V
= ±0.9 V
= ±7.5 V
mV
S
700
–SW
700
V
OUT
T
= 25 °C +SW
= 25 °C –SW
+SW
7.30
–7.32
7.25
–7.30
7.35
–7.35
7.30
–7.35
0.25
0.09
0.6
amb
T
amb
S
V
–SW
T
= 25 °C
= 25 °C
amb
SR
V/µs
T
amb
C = 100 pF; T
= 25 °C
= 25 °C
= 25 °C
L
amb
BW
Inverting unity gain bandwidth
Phase margin
MHz
Deg.
µs
C = 100 pF; T
0.25
70
L
amb
θ
C = 100 pF; T
L amb
M
C = 100 pF, 0.1%
L
2
t
S
Settling time
C = 100 pF, 0.1%
L
5
R
R
= 0 Ω; f = 1 kHz
= 0 Ω; f = 1 kHz
30
S
S
V
INN
Input noise
nV/√Hz
60
V = ±7.5 V
S
High
High
0.003
0.002
A = 1; V = 500 mV; f = 1 kHz
V
IN
THD
Total Harmonic Distortion
%
V
S
= ±0.9 V
A = 1, V = 500 mV; f = 1 kHz
V
IN
5
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
The input stage was designed to overcome two important problems
for rail-to-rail capability. As the common-mode voltage moves from
the range where only the NPN pair was operating to where both of
the input pairs were operating, the effective transconductance would
change by a factor of two. Frequency compensation for the ranges
where one input pair was operating would, of course, not be optimal
for the range where both pairs were operating. Secondly, fast
changes in the common-mode voltage would abruptly saturate and
restore the emitter current sources, causing transient distortion.
These problems were overcome by assuring that only the input
transistor pair which is able to function properly is active. The NPN
THEORY OF OPERATION
Input Stage
Operational amplifiers which are able to function at minimum supply
voltages should have input and output stage swings capable of
reaching both supply voltages within a few millivolts in order to
achieve ease of quiescent biasing and to have maximum
input/output signal handling capability. The input stage of the
NE5230 has a common-mode voltage range that not only includes
the entire supply voltage range, but also allows either supply to be
exceeded by 250 mV without increasing the input offset voltage by
more than 6 mV. This is unequalled by any other operational
amplifier today.
pair is normally activated by the current source I through Q5 and
B1
the current mirror Q6 and Q7, assuming the PNP pair is
non-conducting. When the common-mode input voltage passes
In order to accomplish the feat of rail-to-rail input common-mode
range, two emitter-coupled differential pairs are placed in parallel so
that the common-mode voltage of one can reach the positive supply
rail and the other can reach the negative supply rail. The simplified
schematic of Figure 2 shows how the complementary
below the reference voltage, V = 0.8 V at the base of Q5, the
B1
emitter current is gradually steered toward the PNP pair, away from
the NPN pair. The transfer of the emitter currents between the
complementary input pairs occurs in a voltage range of about
120 mV around the reference voltage V . In this way the sum of the
B1
emitter-coupler transistors are configured to form the basic input
stage cell. Common-mode input signal voltages in the range from
emitter currents for each of the NPN and PNP transistor pairs is kept
constant; this ensures that the transconductance of the parallel
combination will be constant, since the transconductance of bipolar
transistors is proportional to their emitter currents.
0.8V above V to V are handled completely by the NPN pair, Q3
EE
CC
and Q4, while common-mode input signal voltages in the range of
to 0.8 V above V are processed only by the PNP pair, Q1 and
V
EE
EE
An essential requirement of this kind of input stage is to minimize
the changes in input offset voltage between that of the NPN and
PNP transistor pair which occurs when the input common-mode
Q2. The intermediate range of input voltages requires that both the
NPN and PNP pairs are operating. The collector currents of the
input transistors are summed by the current combiner circuit
composed of transistors Q8 through Q11 into one output current.
Transistor Q8 is connected as a diode to ensure that the outputs of
Q2 and Q4 are properly subtracted from those of Q1 and Q3.
voltage crosses the internal reference voltage, V . Careful circuit
B1
layout with a cross-coupled quad for each input pair has yielded a
typical input offset voltage of less than 0.3 mV and a change in the
input offset voltage of less than 0.1 mV.
V
CC
R11
R10
+
V
b2
V
Q11
Q10
I
b1
Q4
Q3
Q2
Q1
V
V
IN+
IN–
I
OUT
Q9
Q8
Q5
+
V
Q7
b1
Q6
R8
R9
V
V
EE
SL00251
Figure 2. Input Stage
6
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
diodes D1 and D2 are proportional to the logarithm of the square of
Output Stage
the reference current I . When the diode characteristics and
B1
Processing output voltage swings that nominally reach to less than
100 mV of either supply voltage can only be achieved by a pair of
complementary common-emitter connected transistors. Normally,
such a configuration causes complex feed-forward signal paths that
develop by combining biasing and driving which can be found in
previous low supply voltage designs. The unique output stage of the
NE5230 separates the functions of driving and biasing, as shown in
the simplified schematic of Figure 3, and has the advantage of a
shorter signal path which leads to increasing the effective
bandwidth.
temperatures of the pairs Q1, D1 and Q3, Q2 are equal, the relation
I
× I = I × I is satisfied.
ON B1 B1
OP
Separating the functions of biasing and driving prevents the driving
signals from becoming delayed by the biasing circuit. The output
Darlington transistors are directly accessible for in-phase driving
signals on the bases of Q5 and Q2. This is very important for simple
high-frequency compensation. The output transistors can be
high-frequency compensated by Miller capacitors CM1A and CM1B
connected from the collectors to the bases of the output Darlington
transistors.
This output stage consists of two parts: the Darlington output
transistors and the class AB control regulator. The output transistor
Q3 connected with the Darlington transistors Q4 and Q5 can source
up to 10 mA to an output load. The output of NPN Darlington
connected transistors Q1 and Q2 together are able to sink an output
current of 10 mA. Accurate and efficient class AB control is
necessary to insure that none of the output transistors are ever
completely cut off. This is accomplished by the differential amplifier
(formed by Q8 and Q9) which controls the biasing of the output
transistors. The differential amplifier compares the summed voltages
across two diodes, D1 and D2, at the base of Q8 with the summed
voltages across the base-emitter diodes of the output transistors Q1
and Q3. The base-emitter voltage of Q3 is converted into a current
by Q6 and R6 and reconverted into a voltage across the
A general-purpose op amp of this type must have enough open-loop
gain for applications when the output is driving a low resistance
load. The NE5230 accomplishes this by inserting an intermediate
common-emitter stage between the input and output stages. The
three stages provide a very large gain, but the op amp now has
three natural dominant poles — one at the output of each
common-emitter stage. Frequency compensation is implemented
with a simple scheme of nested, pole-splitting Miller integrators. The
Miller capacitors CM1A and CM1B are the first part of the nested
structure, and provide compensation for the output and intermediate
stages. A second pair of Miller integrators provide pole-splitting
compensation for the pole from the input stage and the pole
resulting from the compensated combination of poles from the
intermediate and output stages. The result is a stable,
base-emitter diode of Q7 and R7. The summed voltage across the
base-emitter diodes of the output transistors Q3 and Q1 is
proportional to the logarithm of the product of the push and pull
internally-compensated op amp with a phase margin of 70 degrees.
currents I and I , respectively. The combined voltages across
OP
ON
V
CC
R6
I
I
I
b3
b1
b2
Q3
Q6
Q5
V
b5
I
OP
Q4
CM1B
CM1A
V
OUT
Q2
V
b2
I
ON
Q8
Q9
R7
D1
Q7
Q1
I
b4
I
b5
D2
V
EE
SL00252
Figure 3. Output Stage
7
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
between 250 kHz at low bias to 600 kHz at high bias current. The
slew rate range is 0.08 V/µs at low bias and 0.25 V/µs at high bias.
THERMAL CONSIDERATIONS
When using the NE5230, the internal power dissipation capabilities
of each package should be considered. Philips Semiconductors
does not recommend operation at die temperatures above 110 °C in
the SO package because of its inherently smaller package mass.
Die temperatures of 150 °C can be tolerated in all the other
packages. With this in mind, the following equation can be used to
estimate the die temperature:
800
700
600
500
400
300
T = T
+ (P × θ )
JA
(1)
j
amb
D
Where
Tamb 5 AmbientTemperature
Tj + Die Temperature
200
PD 5 Power Dissipation
+ (ICC x VCC
)
100
100
qJA 5 Packagethermalresistance
500
600700
200
300
400
+ 270oCńW for SO8 in PC
UNITY GAIN BANDWIDTH (kHz)
board mounting
a. Unity Gain Bandwidth vs Power Supply Current for
V
= ±0.9V
See the packaging section for information regarding other methods
of mounting.
CC
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0.0
θ
= 100 °C/W for the plastic DIP.
V
= 15V
T
= 25°C
JA
CC
CC
CC
A
V
V
= 12V
= 9V
The maximum supply voltage for the part is 15 V and the typical
supply current is 1.1 mA (1.6 mA max). For operation at supply
V
V
= 6V
= 3V
CC
CC
voltages other than the maximum, see the data sheet for I versus
CC
V
CC
curves. The supply current is somewhat proportional to
temperature and varies no more than 100 µA between 25 °C and
either temperature extreme.
V
V
= 2V
CC
CC
= 1.8V
Operation at higher junction temperatures than that recommended is
possible but will result in lower MTBF (Mean Time Between
Failures). This should be considered before operating beyond
recommended die temperature because of the overall reliability
degradation.
0
1
2
3
4
5
10
10
10
10
10
(Ω)
10
R
ADJ
b. I Current vs Bias Current Adjusting Resistor for
CC
Several Supply Voltages
SL00253
DESIGN TECHNIQUES AND APPLICATIONS
The NE5230 is a very user-friendly amplifier for an engineer to
design into any type of system. The supply current adjust pin (Pin 5)
can be left open or tied through a pot or fixed resistor to the most
negative supply (i.e., ground for single supply or to the negative
supply for split supplies). The minimum supply current is achieved
by leaving this pin open. In this state it will also decrease the
bandwidth and slew rate. When tied directly to the most negative
Figure 4.
The full output power bandwidth range for V equals 2 V, is above
40 kHz for the maximum bias current setting and greater than
10 kHz at the minimum bias current setting.
CC
If extremely low signal distortion (<0.05%) is required at low supply
voltages, exclude the common-mode crossover point (V ) from the
common-mode signal range. This can be accomplished by proper
bias selection or by using an inverting amplifier configuration.
B1
supply, the device has full bandwidth, slew rate and I . The
CC
programming of the current-control pin depends on the trade-offs
which can be made in the designer’s application. The graph in
Figure 4 will help by showing bandwidth versus I . As can be seen,
Most single supply designs necessitate that the inputs to the op amp
CC
the supply current can be varied anywhere over the range of 100 µA
to 600 µA for a supply voltage of 1.8 V. An external resistor can be
inserted between the current control pin and the most negative
supply. The resistor can be selected between 1 Ω to 100 kΩ to
provide any required supply current over the indicated range. In
addition, a small varying voltage on the bias current control pin could
be used for such exotic things as changing the gain-bandwidth for
voltage controlled low pass filters or amplitude modulation.
Furthermore, control over the slew rate and the rise time of the
amplifier can be obtained in the same manner. This control over the
slew rate also changes the settling time and overshoot in pulse
response applications. The settling time to 0.1% changes from 5 µs
at low bias to 2 µs at high bias. The supply current control can also
be utilized for wave-shaping applications such as for pulse or
triangular waveforms. The gain-bandwidth can be varied from
be biased between V and ground. This is to assure that the input
CC
signal swing is within the working common-mode range of the
amplifier. This leads to another helpful and unique property of the
NE5230 that other CMOS and bipolar low voltage parts cannot
achieve. It is the simple fact that the input common-mode voltage
can go beyond either the positive or negative supply voltages. This
benefit is made very clear in a non-inverting voltage-follower
configuration. This is shown in Figure 5 where the input sine wave
allows an undistorted output sine wave which will swing less than
100mV of either supply voltage. Many competitive parts will show
severe clipping caused by input common-mode limitations. The
NE5230 in this configuration offers more freedom for quiescent
biasing of the inputs close to the positive supply rail where similar op
amps would not allow signal processing.
8
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
the line when no current is flowing, but also can power the
V+
transducer at the remote location. Usually the transducer itself is
not equipped to provide for the current transmission. The unique
features of the NE5230 can provide high output current capability
coupled with low power consumption. It can be remotely connected
to the transducer to create a current loop with minimal external
components. The circuit for this is shown in Figure 6. Here, the part
is configured as a voltage-to-current, or transconductance amplifier.
This is a novel circuit that takes advantage of the NE5230’s large
open-loop gain. In AC applications, the load current will decrease
as the open-loop gain rolls off in magnitude. The low offset voltage
and current sinking capabilities of the NE5230 must also be
considered in this application.
V+
+
–
V–
V–
V+
V
I
CC
OUT
3
2
+
–
REMOTE
POWER
SUPPLY
7
+
–
V
NE5230
6
NE5230
5
4
V
EE
T
R
A
N
S
D
U
C
E
R
V–
V+
R
L
V
IN
R
C
OTHER
PARTS
NOTES:
1. I
= V
OUT
IN/RC
V
V–
* 1.8V * V
For R = 1Ω
SL00254
C
REMOTE
INMAX
2. R
≈
L MAX
I
V
I
OUT
IN
OUT
Figure 5. In a Non-Inverting Voltage-Follower Configuration,
the NE5230 will Give Full Rail-to-Rail Swing. Other Low Voltage
Amplifiers will not Because they are Limited by their Input
Common-Mode Range and Output Swing Capability.
4mA
4mV
20mA
20mV
a. The NE5230 as a Remote Transducer Transconductance
Amp With 4-20mA Current Transmission Output Capability
There are not as many considerations when designing with the
NE5230 as with other devices. Since the NE5230 is
+
internally-compensated and has a unity gain-bandwidth of 600 kHz,
board layout is not so stringent as for very high frequency devices
such as the NE5205. The output capability of the NE5230 allows it
to drive relatively high capacitive loads and small resistive loads.
The power supply pins should be decoupled with a low-pass RC
network as close to the supply pins as possible to eliminate 60 Hz
and other external power line noise, although the power supply
rejection ratio (PSRR) for the part is very high. The pinout for the
NE5230 is the same as the standard single op amp pinout with the
exception of the bias current adjusting pin.
R
C
V
IN
V
CC
–
3
2
+
–
7
+
–
V
CC
6
NE5230
5
4
V
EE
+ I
OUT
R
L
REMOTE TRANSDUCER WITH CURRENT
TRANSMISSION
b. The Same Type of Circuit as Figure 5a, but for Sourcing
Current to the Load
There are many ways to transmit information along two wires, but
current transmission is the most beneficial when the sensing of
remote signals is the aim. It is further enhanced in the form of 4 to
20 mA information which is used in many control-type systems.
This method of transmission provides immunity from line voltage
drops, large load resistance variations, and voltage noise pickup.
The zero reference of 4mA not only can show if there is a break in
SL00255
Figure 6.
9
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
The NE5230 circuit shown in Figure 6 is a pseudo transistor
configuration. The inverting input is equivalent to the “base,” the
long line is used which causes high line resistance, a current
repeater could be inserted into the line. The same configuration of
Figure 6 can be used with exception of a resistor across the input
and line ground to convert the current back to voltage. Again, the
current sensing resistor will set up the transconductance and the
part will receive power from the line.
point where V and the non-inverting input meet is the “emitter,”
EE
and the connection after the output diode meets the V pin is the
CC
collector. The output diode is essential to keep the output from
saturating in this configuration. From here it can be seen that the
base and emitter form a voltage-follower and the voltage present at
R
must equal the input voltage present at the inverting input. Also,
C
the emitter and collector form a current-follower and the current
flowing through R is equivalent to the current through R and the
amplifier. This sets up the current loop. Therefore, the following
equation can be formulated for the working current transmission line.
The load current is:
TEMPERATURE TRANSDUCER
C
L
A variation on the previous circuit makes use of the supply current
control pin. The voltage present at this pin is proportional to absolute
temperature (PTAT) because it is produced by the amplifier bias
current through an internal resistor divider in a PTAT cell. If the
control pin is connected to the input pin, the NE5230 itself can be
used as a temperature transducer. If the center tap of a resistive pot
is connected to the control pin with one side to ground and the other
to the inverting input, the voltage can be changed to give different
temperature versus output current conditions (see Figure 7). For
additional control, the output current is still proportional to the input
voltage differential divided by the current sense resistor.
I = V /R
C
(2)
L
IN
and proportional to the input voltage for a set R . Also, the current is
C
constant no matter what load resistance is used while within the
operating bandwidth range of the op amp. When the NE5230’s
supply voltage falls past a certain point, the current cannot remain
constant. This is the “voltage compliance” and is very good for this
application because of the near rail output voltage. The equation
that determines the voltage compliance as well as the largest
possible load resistor for the NE5230 is as follows:
When using the NE5230 as a temperature transducer, the thermal
considerations in the previous section must be kept in mind.
R
= [V
)-V
- V
]/I
L
(3)
L max
remote supply
CC min
IN max
Where V
is the worst-case power supply voltage
CC min
V
I
CC
5
OUT
(approximately 1.8 V) that will still keep the part operational. As an
example, when using a 15 V remote power supply, a current sensing
resistor of 1 Ω, and an input voltage (V ) of 20 mV, the output
3
2
+
–
REMOTE
POWER
SUPPLY
7
+
V
6
IN
NE5230
current (I ) is 20 mA. Furthermore, a load resistance of zero to
L
approximately 650 Ω can be inserted in the loop without any change
in current when the bias current-control pin is tied to the negative
supply pin. The voltage drop across the load and line resistance will
not affect the NE5230 because it will operate down to 1.8 V. With a
15 V remote supply, the voltage available at the amplifier is still
enough to power it with the maximum 20 mA output into the 650 Ω
load.
–
4
V
EE
10
R
L
200
R
C
What this means is that several instruments, such as a chart
recorder, a meter, or a controller, as well as a long cable, can be
connected in series on the loop and still obtain accurate readings if
the total resistance does not exceed 650 Ω. Furthermore, any
variation of resistance in this range will not change the output
current.
NOTES:
1. I
= V
OUT
IN/RC
V
* 1.8V * V
REMOTE
INMAX
2. R
≈
L MAX
For R = 1Ω
C
I
Any voltage output type transducer can be used, but one that does
not need external DC voltage or current excitation to limit the
maximum possible load resistance is preferable. Even this problem
can be surmounted if the supply power needed by the transducer is
compatible with the NE5230. The power goes up the line to the
transducer and amplifier while the transducer signal is sent back via
the current output of the NE5230 transconductance configuration.
OUT
I
V
OUT
IN
4mA
4mV
20mA
20mV
SL00256
Figure 7. NE5230 Remote Temperature Transducer Utilizing
4–20 mA Current Transmission. This Application Shows the
use of the Accessibility of the PTAT Cell in the Device to Make
the Part, Itself, a Transducer
The voltage range on the input can be changed for transducers that
produce a large output by simply increasing the current sense
resistor to get the corresponding 4 to 20 mA output current. If a very
10
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
because the waveform forces the amplifier to swing the output
beyond either ground or the positive supply rail, depending on the
biasing, and, also, the output cannot disengage during this half
cycle. During the other half cycle, however, the amplifier achieves a
half-wave that can have a peak equal to the total supply voltage.
The photographs in Figure 9 show the effect of the different biasing
schemes, as well as the wide bandwidth (it works over the full audio
range), that the NE5230 can achieve in this configuration.
HALF-WAVE RECTIFIER WITH RAIL-TO-GROUND
OUTPUT SWING
Since the NE5230 input common-mode range includes both positive
and negative supply rails and the output can also swing to either
supply, achieving half-wave rectifier functions in either direction
becomes a simple task. All that is needed are two external resistors;
there is no need for diodes or matched resistors. Moreover, it can
have either positive- or negative-going outputs, depending on the
way the bias is arranged. This can be seen in Figure 8. Circuit (a) is
biased to ground, while circuit (b) is biased to the positive supply.
This rather unusual biasing does not cause any problems with the
NE5230 because of the unique internal saturation detectors
incorporated into the part to keep the PNP and NPN output
transistors out of “hard” saturation. It is therefore relatively quick to
recover from a saturated output condition. Furthermore, the device
does not have parasitic current draw when the output is biased to
either rail. This makes it possible to bias the NE5230 into
“saturation” and obtain half-wave rectification with good recovery.
The simplicity of biasing and the rail-to-ground half-sine wave swing
are unique to this device. The circuit gain can be changed by the
standard op amp gain equations for an inverting configuration.
By adding another NE5230 in an inverting summer configuration at
the output of the half-wave rectifier, a full-wave can be realized. The
values for the input and feedback resistors must be chosen so that
each peak will have equal amplitudes. A table for calculating values
is included in Figure 10. The summing network combines the input
signal at the half-wave and adds it to double the half-wave’s output,
resulting in the full-wave. The output waveform can be referenced to
the supply or ground, depending on the half-wave configuration.
Again, no diodes are needed to achieve the rectification.
This circuit could be used in conjunction with the remote transducer
to convert a received AC output signal into a DC level at the
full-wave output for meters or chart recorders that need DC levels.
It can be seen in these configurations that the op amp cannot
respond to one-half of the incoming waveform. It cannot respond
10
V
CC
10
2
V
IN
7
–
+
6
V
OUT
V
5
CC
3
4
O
t
a. Rail-to-Ground Output Swing Referenced to Ground
V
CC
3
7
+
6
V
OUT
10
5
2
–
4
V
V
CC
IN
10
V
CC
t
b. Negative-Going Output Referenced to V
CC
SL00257
Figure 8. Half-Wave Rectifier With Positive-Going Output Swings
11
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
500mV/Div 200µS/Div
Biased to Ground
500mV/Div 20µS/Div
Biased to Ground
500mV/Div 20µS/Div
Biased to Positive Rail
SL00258
Figure 9. Performance Waveforms for the Circuits in Figure 8.
Good response is shown at 1 and 10 kHz for both circuits under full swing with a 2 V supply.
12
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
500mV
500mV
520µs
INPUT
HALF-WAVE
OUTPUT
FULL-WAVE
OUTPUT
+V
IN
a
500mV
b
–V
IN
R3
R5
3
+
V
CC
7
7
R4
6
2
A
+V
+V
–V
1
–
+
IN
IN
5
a
b
R1
a
6
2
4
+V
–
A
B
2
FULL-WAVE
5
b
3
V
4
EE
IN
R2
+V
V
B
EE
0
2a
NOTES:
R2 = 2 R1
–2V
IN
HALF-WAVE
R4 = R5 = R3
+V will vary output reference.
B
For single supply operation V
can be grounded on A2.
SL00259
EE
Figure 10. Adding an Inverting Summer to the Input and Output of the Half-Wave will Result in Full-Wave
CONCLUSION
REFERENCES
The NE5230 is a versatile op amp in its own right. The part was
designed to give low voltage and low power operation without the
limitations of previously available amplifiers that had a multitude of
problems. The previous application examples are unique to this
amplifier and save the user money by excluding various passive
components that would have been needed if not for the NE5230’s
special input and output stages.
Johan H. Huijsing, Multi-stage Amplifier with Capacitive Nesting for
Frequency Compensation, U.S. Patent Application Serial
No. 602.234, filed April 19, 1984.
Bob Blauschild, Differential Amplifier with Rail-to-Rail Capability,
U.S. Patent Application Serial No. 525.181, filed August 23, 1983.
Operational Amplifiers - Characteristics and Applications,
Robert G. Irvine, Prentice-Hall, Inc., Englewood Cliffs, NJ 07632, 1981.
The NE5230 has a combination of novel specifications which allows
the designer to implement it easily into existing low-supply voltage
designs and to enhance their performance. It also offers the
engineer the freedom to achieve greater amplifier system design
goals. The low input referenced noise voltage eases the restrictions
on designs where S/N ratios are important. The wide full-power
bandwidth and output load handling capability allow it to fit into
portable audio applications. The truly ample open-loop gain and low
power consumption easily lend themselves to the requirements of
remote transducer applications. The low, untrimmed typical offset
voltage and low offset currents help to reduce errors in signal
processing designs. The amplifier is well isolated from changes on
the supply lines by its typical power supply rejection ratio of 105 dB.
Transducer Interface Handbook - A Guide to Analog Signal
Conditioning, Edited by Daniel H. Sheingold, Analog Devices, Inc.,
Norwood, MA 02062, 1981.
13
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
SO8: plastic small outline package; 8 leads; body width 3.9 mm
SOT96-1
14
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
DIP8: plastic dual in-line package; 8 leads (300 mil)
SOT97-1
15
2001 Aug 03
Philips Semiconductors
Product data
Low voltage operational amplifier
NE5230/SA5230
Data sheet status
Product
status
Definitions
[1]
Data sheet status
[2]
Objective data
Development
This data sheet contains data from the objective specification for product development.
Philips Semiconductors reserves the right to change the specification in any manner without notice.
Preliminary data
Product data
Qualification
Production
This data sheet contains data from the preliminary specification. Supplementary data will be
published at a later date. Philips Semiconductors reserves the right to change the specification
without notice, in order to improve the design and supply the best possible product.
This data sheet contains data from the product specification. Philips Semiconductors reserves the
right to make changes at any time in order to improve the design, manufacturing and supply.
Changes will be communicated according to the Customer Product/Process Change Notification
(CPCN) procedure SNW-SQ-650A.
[1] Please consult the most recently issued data sheet before initiating or completing a design.
[2] The product status of the device(s) described in this data sheet may have changed since this data sheet was published. The latest information is available on the Internet at URL
http://www.semiconductors.philips.com.
Definitions
Short-form specification — The data in a short-form specification is extracted from a full data sheet with the same type number and title. For
detailed information see the relevant data sheet or data handbook.
Limiting values definition — Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 60134). Stress above one
or more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation of the device at these or
at any other conditions above those given in the Characteristics sections of the specification is not implied. Exposure to limiting values for extended
periods may affect device reliability.
Application information — Applications that are described herein for any of these products are for illustrative purposes only. Philips
Semiconductors make no representation or warranty that such applications will be suitable for the specified use without further testing or
modification.
Disclaimers
Life support — These products are not designed for use in life support appliances, devices or systems where malfunction of these products can
reasonably be expected to result in personal injury. Philips Semiconductors customers using or selling these products for use in such applications
do so at their own risk and agree to fully indemnify Philips Semiconductors for any damages resulting from such application.
Righttomakechanges—PhilipsSemiconductorsreservestherighttomakechanges, withoutnotice, intheproducts, includingcircuits,standard
cells, and/or software, described or contained herein in order to improve design and/or performance. Philips Semiconductors assumes no
responsibility or liability for the use of any of these products, conveys no license or title under any patent, copyright, or mask work right to these
products, and makes no representations or warranties that these products are free from patent, copyright, or mask work right infringement, unless
otherwise specified.
Koninklijke Philips Electronics N.V. 2001
Contact information
All rights reserved. Printed in U.S.A.
For additional information please visit
http://www.semiconductors.philips.com.
Fax: +31 40 27 24825
Date of release: 12-01
9397 750 09239
For sales offices addresses send e-mail to:
sales.addresses@www.semiconductors.philips.com.
Document order number:
Philips
Semiconductors
相关型号:
SA5232D,118
IC DUAL OP-AMP, 5000 uV OFFSET-MAX, PDSO8, 3.90 MM, PLASTIC, SO-8, Operational Amplifier
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