FAN53602UC123X [ONSEMI]
1.2A Synchronous Buck Regulator;型号: | FAN53602UC123X |
厂家: | ONSEMI |
描述: | 1.2A Synchronous Buck Regulator 开关 |
文件: | 总10页 (文件大小:1121K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Synchronous Buck
Regulator 6ꢀMHz, 1.2ꢀA
FAN53602
DESCRIPTION
The FAN53602 is a 6 MHz, step−down switching voltage regulator
that delivers a fixed output from an input voltage supply of 2.3 V to
5.5 V. Using a proprietary architecture with synchronous rectification,
the FAN53602 is capable of delivering a constant load of 1.2 A.
The regulator operates at a nominal fixed frequency of 6 MHz,
which reduces the value of the external components to as low as
470 nH for the output inductor and 4.7 ꢀ F for the output capacitor.
In addition, the Pulse Width Modulation (PWM) modulator can be
synchronized to an external frequency source.
At moderate and light loads, Pulse Frequency Modulation (PFM) is
used to operate the device in Power−Save Mode with a typical
quiescent current of 24 ꢀ A. Even with such a low quiescent current,
the part exhibits excellent transient response during large load swings.
At higher loads, the system automatically switches to fixed−frequency
control, operating at 6 MHz. In Shutdown Mode, the supply current
drops below 1 ꢀ A, reducing power consumption. For applications that
require minimum ripple or fixed frequency, PFM Mode can be
disabled using the MODE pin.
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WLCSP6 1.16x0.86x0.586
CASE 567QE
MARKING DIAGRAM
12KK
XYZ
The FAN53602 is available in 6−bump, 0.4 mm pitch, Wafer−Level
Chip−Scale Package (WLCSP).
12
KK
X
Y
Z
= Alphanumeric Device Marking
= Lot Run Code
= Alphabetical Year Code
= 2 Weeks Date Code
= Assembly Plant Code
Features
• 1.2 A Output Current Capability
• 24 ꢀ A Typical Quiescent Current
• 6 MHz Fixed−Frequency Operation
• Best−in−Class Load Transient Response
• Best−in−Class Efficiency
ORDERING INFORMATION
See detailed ordering and shipping information on page 2 of
this data sheet.
• 2.3 V to 5.5 V Input Voltage Range
• Low Ripple Light−Load PFM Mode
• Forced PWM and External Clock Synchronization
• Internal Soft−Start
• Input Under−Voltage Lockout (UVLO)
• Thermal Shutdown and Overload Protection
• 6−Bump WLCSP, 0.4 mm Pitch
VIN
EN
MODE
L1
470nH
FB
A1 A2
B1 B2
C1 C2
C
IN
SW
2.2 ꢀ F
GND
4.7 ꢀ F
C
OUT
Application
Figure 1. Typical Application
®
• 3G, 4G, WiFi , WiMAXt, and WiBrot Data Cards
• Tablets
• DSC, DVC
• Netbooks
© Semiconductor Components Industries, LLC, 2016
1
Publication Order Number:
FAN53602/D
October, 2019 − Rev. 2
FAN53602
Table 1. ORDERING INFORMATION
†
Part Number
Output Voltage
Package
Temperature Range
Packing Method
3000 / Tape & Reel
Device Marking
FAN53602UC123X
1.233 V
WLCSP − 6, 0.4 mm
−40 to 85°C
TZ
Pitch
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
PIN CONFIGURATION
VIN
EN
A2
B2
C2
MODE
SW
A1 MODE
A1
B1
VIN
EN
A2
B2
SW
FB
B1
C1
C2 GND
FB
C1
GND
Figure 2. Bumps Facing Down
Figure 3. Bumps Facing Up
Table 2. PIN DEFINITIONS
Pin #
Name
Description
A1
MODE
MODE. Logic 1 on this pin forces the IC to stay in PWM Mode. A logic 0 allows the IC to
automatically switch to PFM during light loads. The regulator also synchronizes its switching
frequency to four times the frequency provided on this pin. Do not leave this pin floating.
B1
C1
C2
B2
SW
FB
Switching Node. Connect to output inductor.
Feedback / VOUT. Connect to output voltage.
GND
EN
Ground. Power and IC ground. All signals are referenced to this pin.
Enable. The device is in Shutdown Mode when voltage to this pin is < 0.4 V and enabled
when > 1.2 V. Do not leave this pin floating.
A2
VIN
Input Voltage. Connect to input power source.
Table 3. ABSOLUTE MAXIMUM RATINGS
Symbol
Parameter
Min.
−0.3
−0.3
−0.3
−0.3
Max.
Unit
V
IN
Input Voltage
7.0
V
V
V
Voltage on SW Pin
EN and Mode Pin Voltage
Other Pins
V
IN
V
IN
V
IN
+ 0.3 (Note 1)
+ 0.3 (Note 1)
+ 0.3 (Note 1)
SW
V
CTRL
V
V
ESD
Electrostatic Discharge
Protection Level
kV
Human Body Model per JESD22−A114
Charged Device Model per JESD22−C101
2.0
1.5
T
Junction Temperature
Storage Temperature
−40
−65
+150
+150
+260
°C
°C
°C
J
T
STG
T
L
Lead Soldering Temperature, 10 Seconds
Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality
should not be assumed, damage may occur and reliability may be affected.
1. Lesser of 7 V or V + 0.3 V.
IN
Table 4. THERMAL PROPERTIES
Symbol
Parameter
Typ.
Unit
θ
JAn
Junction−to−Ambient Thermal Resistance
125
°C/W
NOTE: Junction−to−ambient thermal resistance is a function of application and board layout. This data is measured with four−layer 2s2p
boards without vias in accordance to JEDEC standard JESD51. Special attention must be paid to not exceed junction temperature
T
at a given ambient temperature T .
J(max)
A
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2
FAN53602
Table 5. RECOMMENDED OPERATING CONDITIONS
Symbol
Parameter
Supply Voltage Range
Min.
2.3
Typ.
Max.
Unit
V
CC
5.5
V
I
Output Current
1200
mA
nH
ꢀ F
ꢀ H
°C
°C
OUT
L
Inductor
470
2.2
4.7
C
Input Capacitor
IN
C
Output Capacitor
1.6
−40
−40
12.0
+85
OUT
T
A
Operating Ambient Temperature
Operating Junction Temperature
T
J
+125
Functional operation above the stresses listed in the Recommended Operating Ranges is not implied. Extended exposure to stresses beyond
the Recommended Operating Ranges limits may affect device reliability.
Table 6. ELECTRICAL CHARACTERISTICS ( Note 2) Minimum and Maximum Values are at V = V = 2.3 V to
IN
EN
5.5 V, V
= 0 V (AUTO Mode), T = −40°C to +85°C, circuit of Figure 1, unless otherwise noted. Typical values are at T = 25°C,
MODE
A
A
V
IN
= V = 3.6 V.
EN
Symbol
Parameter
Condition
Power Supplies
Min.
Typ.
Max.
Unit
I
Quiescent Current
No Load, Not Switching
PWM Mode
24
8
50
ꢀ A
mA
ꢀ A
V
Q
I
Shutdown Supply Current
EN = GND, V = 3.6 V,
0.25
2.15
200
1.00
2.27
(SD)
IN
V
Under−Voltage Lockout Threshold
Under−Voltage Lockout Hysteresis
Rising VIN
UVLO
V
mV
UVHYST
Logic Inputs: EN and MODE Pins
V
Enable HIGH−Level Input Voltage
Enable Low−Level Input Voltage
Logic Input Hysteresis Voltage
Enable Input Leakage Current
1.2
V
V
IH
V
IL
LHYST
0.4
V
100
mV
ꢀ A
I
IN
Pin to VIN or GND
0.01
1.00
Switching and Synchronization
f
Switching Frequency (Note 3)
VIN = 3.6 V, T = 25°C, PWM Mode,
5.4
1.3
6.0
1.5
6.6
1.7
MHz
MHz
SW
A
IOUT = 10 mA
f
MODE Synchronization Range (Note 3)
Square Wave at MODE Input
SYNC
Regulation
Vo
Output Voltage Accuracy
VIN = 3.6 V, IOUT = 0 mA, PWM
AUTO Mode, IOUT = 0 to 1.2 A
1.202
1.171
1.233
1.233
180
1.264
1.281
300
V
V
t
SS
Soft−Start
VIN = 4.5 V, From EN Rising
Edge to 95% VOUT
ꢀ
s
Output Driver
R
PMOS On Resistance
NMOS On Resistance
PMOS Peak Current Limit
Thermal Shutdown
VIN = V = 3.6 V
175
165
1.95
150
15
m
ꢁ
ꢁ
DS(on)
GS
VIN = V = 3.6 V
m
GS
I
VIN = 3.6 V, T = 25°C
1.70
2.20
A
LIM(OL)
A
T
T
°C
°C
TSD
HYS
Thermal Shutdown Hysteresis
Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product
performance may not be indicated by the Electrical Characteristics if operated under different conditions.
2. The Electrical Characteristics table reflects open−loop data. Refer to the Operation Description and Typical Characteristics Sections for
closed−loop data.
3. Limited by the effect of t
minimum (see Operation Description section).
OFF
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3
FAN53602
TYPICAL PERFORMANCE CHARACTERISTIC
Unless otherwise noted, V = V = 3.6 V, V
= 0 V (AUTO Mode), V = 1.233 V, , T = 25°C
OUT A
IN
EN
MODE
Figure 5. Efficiency vs. Load Current
and Temperature
Figure 4. Efficiency vs. Load Current
and Input Voltage
Figure 7. VOUT Accuracy vs. Load Current
and Temperature
Figure 6. VOUT Accuracy vs. Load Current
and Input Voltage
Figure 9. Output Ripple vs. Load Current
and Input Voltage
Figure 8. Switching Frequency vs. Load Current
and Input Volatage
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FAN53602
TYPICAL PERFORMANCE CHARACTERISTIC (continued)
Unless otherwise noted, V = V = 3.6 V, V
= 0 V (AUTO Mode), V = 1.233 V, , T = 25°C
OUT A
IN
EN
MODE
Figure 11. Quiescent Current vs. Input Volatage
and Temperature, FPWM Mode
Figure 10. Quiescent Current vs. Input Voltage
and Temperature
Figure 12. Load Transient, 10 mA ꢀ 200 mA in 1 ms
Figure 13. Load Transient, 150 mA ꢀ 1200 mA in 1 ms
Figure 14. Line Transient, 3.3 V ꢀ 3.9 V in 10 ms,
Figure 15. Startup, 800 mA Load
1200 mA Load
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FAN53602
OPERATION DESCRIPTION
To prevent shut down during soft−start, the following
condition must be met:
The FAN53602 is a 6 MHz, step−down switching voltage
regulator that delivers a fixed output from an input voltage
supply of 2.3 V to 5.5 V. Using a proprietary architecture
with synchronous rectification, the FAN53602 is capable
of delivering a constant 1.2 A load current.
I
DISP ) ILOAD t IMAX(DC)
(eq. 2)
Where I
is the maximum load current the IC is
MAX(DC)
guaranteed to support.
The regulator operates at a nominal fixed frequency of
6 MHz, which reduces the value of the external components
to as low as 470 nH for the output inductor and 4.7 ꢀ F for
the output capacitor. In addition, the PWM modulator can be
synchronized to an external frequency source.
Startup into Large COUT
Multiple soft−start cycles are required for no−load startup
if COUT is greater than 15 ꢀ F. Large COUT requires light
initial load to ensure the FAN53602 starts appropriately.
The IC shuts down for 1.3 ms when IDISP exceeds ILIMIT
for more than 200 ꢀ s of current limit. The IC then begins
a new soft−start cycle. Since COUT retains its charge when
the IC is off, the IC reaches regulation after multiple
soft−start attempts.
Control Scheme
The FAN53602 uses
a
proprietary, non−linear,
fixed−frequency PWM modulator to deliver a fast load
transient response, while maintaining a constant switching
frequency over a wide range of operating conditions.
The regulator performance is independent of the output
capacitor ESR, allowing for the use of ceramic output
capacitors. Although this type of operation normally results
in a switching frequency that varies with input voltage
and load current, an internal frequency loop holds
the switching frequency constant over a large range of input
voltages and load currents.
For very light loads, the FAN53602 operates
in Discontinuous Current Mode (DCM) single−pulse PFM
Mode, which produces low output ripple compared
with other PFM architectures. Transition between PWM
and PFM is seamless, allowing for a smooth transition
between DCM and CCM.
MODE Pin
Logic 1 on this pin forces the IC to stay in PWM Mode.
A logic 0 allows the IC to automatically switch to PFM
during light loads. If the MODE pin is toggled with
a frequency between 1.3 MHz and 1.7 MHz, the converter
synchronizes its switching frequency to four times
the frequency on the MODE pin.
The MODE pin is internally buffered with a Schmitt
trigger, which allows the MODE pin to be driven with slow
rise and fall times. An asymmetric duty cycle for frequency
synchronization is also permitted as long as the minimum
time below V
or above V
is 100 ns.
IL(MAX)
IH(MAX)
Current Limit, Fault Shutdown and Restart
Combined with exceptional transient response
characteristics, the very low quiescent current
of the controller maintains high efficiency; even at very
light loads, while preserving fast transient response for
applications requiring tight output regulation.
A heavy load or short circuit on the output causes
the current in the inductor to increase until a maximum
current threshold is reached in the high−side switch. Upon
reaching this point, the high−side switch turns off,
preventing high currents from causing damage.
The regulator continues to limit the current cycle−by−cycle.
After 16 cycles of current limit, the regulator triggers
an over−current fault, causing the regulator to shut down
for about 1.3 ms before attempting a restart.
If the fault is caused by short circuit, the soft−start circuit
attempts to restart and produces an over−current fault after
about 200 ꢀ s, which results in a duty cycle of less than 15%,
limiting power dissipation.
Enable and Soft−Start
When EN is LOW, all circuits are off and the IC draws
~250 nA of current. When EN is HIGH and VIN is above its
UVLO threshold, the regulator begins a soft−start cycle.
The output ramp during soft−start is a fixed slew rate of
50 mV/ꢀ s from VOUT = 0 to 1 V, then 12.5 mV/ꢀ s until
the output reaches its setpoint. Regardless of the state of
the MODE pin, PFM Mode is enabled to prevent current
from being discharged from COUT if soft−start begins when
COUT is charged.
The current−limit fault response protects the IC in
the event of an over−current condition present during
soft−start. As a result, the IC may fail to start if heavy load
is applied during startup and/or if excessive COUT is used.
The current required to charge COUT during soft−start
commonly referred to as “displacement current” is given as:
The closed−loop peak−current limit is not the same as the
open−loop tested current limit, ILIM(OL), in the Electrical
Characteristics table. This is primarily due to the effect of
propagation delays of the IC current limit comparator.
Under−Voltage Lockout (UVLO)
When EN is HIGH, the under−voltage lockout keeps
the part from operating until the input supply voltage rises
high enough to properly operate. This ensures no
misbehavior of the regulator during startup or shutdown.
dV
dt
I
DISP + COUT @
(eq. 1)
dV
Where
refers to the soft−start slew rate.
dt
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FAN53602
Thermal Shutdown (TSD)
The transition between PFM and PWM operation is
determined by the point at which the inductor valley current
crosses zero. The regulator DC current when the inductor
When the die temperature increases, due to a high load
condition and/or a high ambient temperature; the output
switching is disabled until the die temperature falls
sufficiently. The junction temperature at which the thermal
shutdown activates is nominally 150°C with a 15°C
hysteresis.
current crosses zero, I , is:
DCM
ꢂ I
2
IDCM
+
(eq. 7)
The FAN53602 is optimized for operation with
L = 470 nH, but is stable with inductances up to 1 ꢀ H
(nominal). The inductor should be rated to maintain at least
Minimum Off−Time Effect on Switching Frequency
t
is 40 ns. This imposes constraints on
VOUT
OFF(MIN)
80% of its value at I
.
LIM(PK)
Efficiency is affected by the inductor DCR and inductance
value. Decreasing the inductor value for a given physical
size typically decreases the DCR; but because ꢂI increases,
the RMS current increases, as do the core and skin effect
losses.
the maximum
that the FAN53602 can provide or the
VIN
maximum output voltage it can provide at low VIN while
maintaining a fixed switching frequency in PWM Mode.
When VIN is LOW, fixed switching is maintained as long as:
V
VIN
OUT v 1 * tOFF(MIN) @ fSW [ 0.7
ꢂ I2
2
+ Ǹ
IRMS
IOUT(DC)
)
(eq. 8)
12
The switching frequency drops when the regulator cannot
provide sufficient duty cycle at 6 MHz to maintain
regulation.
The increased RMS current produces higher losses
through the R
of the IC MOSFETs, as well as the
DS(ON)
inductor DCR.
The calculation for switching frequency is given by:
Increasing the inductor value produces lower RMS
currents, but degrades transient response. For a given
physical inductor size, increased inductance usually results
in an inductor with lower saturation current and higher DCR.
Table 7 shows the effects of inductance higher or lower
than the recommended 1 ꢀ H on regulator performance.
1
ǒ
, 6 MHzǓ
f
SW + min
(eq. 3)
tSW(MAX)
Where:
V
OUT ) IOUT @ ROFF
+ 40 ns @ ǒ1 )
Ǔ
tSW(MAX)
V
IN * IOUT @ RON * VOUT
Output Capacitor
(eq. 4)
Table 8 suggests 0402 capacitors. 0603 capacitors may
further improve performance in that the effective
capacitance is higher. This improves transient response
and output ripple.
Where:
R
OFF + RDSON_N ) DCRL
ON + RDSON_P ) DCRL
Increasing C
has no effect on loop stability and can
R
OUT
therefore be increased to reduce output voltage ripple or to
improve transient response. Output voltage ripple, ꢂV
is:
,
OUT
APPLICATIONS INFORMATION
Selecting the Inductor
The output inductor must meet both the required
inductance and the energy−handling capability of
the application. The inductor value affects average current
limit, the PWM−to−PFM transition point, output voltage
ripple, and efficiency.
f
SW @ COUT @ ESR2
1
ꢂ I ƪ
ƫ
ꢂ
V
+
)
O
U
T
L
(
)
2 @ D @ 1 * D
8 @ fSW @ COUT
(eq. 9)
Input Capacitor
The 2.2 ꢀ F ceramic input capacitor should be placed as
close as possible between the VIN pin and GND to minimize
the parasitic inductance. If a long wire is used to bring power
to the IC, additional “bulk” capacitance (electrolytic or
The ripple current (ꢂI) of the regulator is:
VOUT
VIN
V
IN * VOUT
L @ fSW
@ ǒ
Ǔ
ꢂ
I
[
(eq. 5)
The maximum average load current, I
,
tantalum) should be placed between C and the power
MAX(LOAD)
, by the ripple
IN
is related to the peak current limit, I
current, given by:
source lead to reduce the ringing that can occur between
LIM(PK)
the inductance of the power source leads and C .
IN
The effective capacitance value decreases as VIN
increases due to DC bias effects.
ꢂ I
2
I
MAX(LOAD) + ILIM(PK)
*
(eq. 6)
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7
FAN53602
Table 7. EFFECTS OF CHANGES IN INDUCTOR VALUE (FROM 470 nH RECOMMENDED VALUE) ON REGULATOR
PERFORMANCE
Inductor Value
Increase
I
DV
Transient Response
Degraded
MAX(LOAD)
OUT
Increase
Decrease
Increase
Decrease
Decrease
Improved
Table 8. RECOMMENDED PASSIVE COMPONENTS AND THEIR VARIATION DUE TO DC BIAS
Component
Description
Vendor
Min.
Typ.
Max.
L1
0.47 ꢀ H/5.3 A/26 m
ꢁ
Murata DFE201610E−R47M
470 nH
ꢃ ꢄ ꢅ x 1.6 1.0 mm
C
2.2 ꢀ F, 6.3 V, X5R, 0402
4.7 ꢀ F, X5R, 0402
Murata or Equivalent GRM155R60J225ME15
GRM188R60J225KE19D
1.0 ꢀ F
1.6 ꢀ F
2.2 ꢀ F
4.7 ꢀ F
IN
C
Murata or Equivalent GRM155R60G475M
GRM155R60E475ME760
OUT
PCB LAYOUT GUIDELINES
There are only three external components: the inductor
and the input and output capacitors. For any buck switcher
IC, including the FAN53602, it is important to place
a low−ESR input capacitor very close to the IC, as shown
in Figure 16. The input capacitor ensures good input
decoupling, which helps reduce noise appearing
at the output terminals and ensures that the control sections
of the IC do not behave erratically due to excessive noise.
This reduces switching cycle jitter and ensures good overall
performance. It is important to place the common GND
of CIN and COUT as close as possible to the C2 terminal.
There is some flexibility in moving the inductor further
away from the IC; in that case, VOUT should be considered
at the COUT terminal.
Figure 16. PCB Layout Guidance
PRODUCT−SPECIFIC DIMENSIONS
D
E
X
Y
1.160 0.030
0.860 0.030
0.230
0.180
Wi−Fi is a registered trademark of the Wi−Fi Alliance.
WiMAX is a trademark of WiMAX Forum.
WiBro is a trademark and brand of Telecommunications Technology Association.
All brand names and product names appearing in this document are registered trademarks or trademarks of their respective holders.
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8
MECHANICAL CASE OUTLINE
PACKAGE DIMENSIONS
WLCSP6 1.16x0.86x0.586
CASE 567QE
ISSUE O
DATE 31 OCT 2016
Electronic versions are uncontrolled except when accessed directly from the Document Repository.
Printed versions are uncontrolled except when stamped “CONTROLLED COPY” in red.
DOCUMENT NUMBER:
DESCRIPTION:
98AON13324G
WLCSP6 1.16x0.86x0.586
PAGE 1 OF 1
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Multi-Output Power-Supply ControllerWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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SI9130CG-T1-E3
Pin-Programmable Dual Controller - Portable PCsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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SI9130LG-T1-E3
Pin-Programmable Dual Controller - Portable PCsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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VISHAY
SI9130_11
Pin-Programmable Dual Controller - Portable PCsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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VISHAY
SI9137
Multi-Output, Sequence Selectable Power-Supply Controller for Mobile ApplicationsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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VISHAY
SI9137DB
Multi-Output, Sequence Selectable Power-Supply Controller for Mobile ApplicationsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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VISHAY
SI9137LG
Multi-Output, Sequence Selectable Power-Supply Controller for Mobile ApplicationsWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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VISHAY
SI9122E
500-kHz Half-Bridge DC/DC Controller with Integrated Secondary Synchronous Rectification DriversWarning: Undefined variable $rtag in /www/wwwroot/website_ic37/www.icpdf.com/pdf/pdf/index.php on line 217
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VISHAY
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