MC44604PG_技术文档

MC44604

High Safety Pulsed Mode

Standby GreenLinet

PWM Controller

The MC44604 is an enhanced high performance controller that is

specifically designed for off−line and dc−to−dc converter applications.

Its high current totem pole output is ideally suited for driving a power

MOSFET.

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The MC44604 is an evolution of the MC44603A. Like the

MC44603A, the MC44604 has been optimized to operate with

universal ac mains voltage from 80 V to 280 V. It also offers enhanced

safety and reliable power management thanks to its protection features

(foldback, overvoltage detection, soft−start, accurate demagnetization

detection).

In addition, the MC44604 offers a new efficient way to reduce the

standby operating power by means of a so−called pulsed mode

standby operation of the converter, significantly reducing the

converter consumption in standby mode.

16

1

PDIP−16

P SUFFIX

CASE 648

MARKING DIAGRAM

Current Mode Controller

• Operation Up to 250 kHz Output Switching Frequency

• Inherent Feed Forward Compensation

• Latching PWM for Cycle−by−Cycle Current Limiting

• Oscillator with Precise Frequency Control

16

MC44604P

AWLYYWWG

1

High Flexibility

• Externally Programmable Reference Current

• Secondary or Primary Sensing

• High Current Totem Pole Output

• Undervoltage Lockout with Hysteresis

A

= Assembly Location

WL = Wafer Lot

YY = Year

WW = Work Week

G

= Pb−Free Package

Safety/Protection Features

PIN CONNECTIONS

• Overvoltage Protection Facility Against Open Loop

• Protection Against Short Circuit on Oscillator Pin

• Fully Programmable Foldback

V

R

ref

CC

1

2

3

4

5

6

7

8

16

15

14

13

12

11

10

9

V

Standby Management

Error Amp Input

C

• Soft−Start Feature

Output

GND

• Accurate Maximum Duty Cycle Setting

• Demagnetization (Zero Current Detection) Protection

• Internally Trimmed Reference

Error Amp Output

Foldback Input

Clamp Error Amp Input

Overvoltage

Protection

Soft−Start/D

max

Voltage Mode

/

GreenLinet Controllert

Current Sense Input

C

T

• Low Startup and Operating Current

• Pulsed Mode Standby for Low Standby Losses

• Low dV/dT for Low EMI

Demagnetization

Detection Input

Standby

Current Set

(Top View)

Features

ORDERING INFORMATION

• Pb−Free Package is Available*

Device

Package

Shipping

MC44604P

PDIP−16

25 Units / Rail

*For additional information on our Pb−Free strategy and soldering details, please

download the ON Semiconductor Soldering and Mounting Techniques

Reference Manual, SOLDERRM/D.

MC44604PG

PDIP−16

(Pb−Free)

©

Semiconductor Components Industries, LLC, 2005

1

Publication Order Number:

October, 2005 − Rev. 5

MC44604/D

MC44604

Block Diagram

R

V

ref

cc

1

16

I

V

enable

ref

CC

V

demag out

Demagnetization

Management

Demagnetization

Detection

UVLO1

UVLO2

18 V

8

Supply

Initialization

Block

Reference Block

V

Clamp Error

2

3

4

V

stby

C

stby

12

Ampllifier Input

V

osc prot

i

ref

Dis(stby)

V

OSC

4.7 V

Buffer

OUTPUT

GND

V

ref

Oscillator

Set

PWM

Latch

Q

C

T

10

Dis(stby−latched)

V

Reset

Thermal

Shutdown

Standby

Management

stby

ref

15

Standby

Management

I

V

ref

Dis(stby)

V

CC

V

ref

V

+

−

cs

Overvoltage

Protection

(OVP)

Error

AMP

Voltage

Feedback

Input

6

Overvoltage

Management

Current

Sense

14

i

ref

E/A Output 13

Dmax &

Soft−Start

Control

V

enable

UVLO2

CC

UVLO1

Dis(stby−latched)

Standby (lpk)max

Programmation

V

enable

V

CC

stby

Foldback

5

V

stby

MC44604

8

7

11

Foldback

Input

Standby

Current

Set

Current

Sense

Input

Soft−Start

(Css)/Dmax

Voltage Mode

Control

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2

MC44604

MAXIMUM RATINGS

Rating

Pin #

Symbol

(I + I )

Value

30

Unit

mA

V

Total Power Supply and Zener Current

CC

Z

Output Supply Voltage with Respect to Ground

2

1

V

18

C

V

CC

Output Current (Note 1)

− Source

− Sink

3

mA

I

−750

750

O(Source)

I

O(Sink)

Output Energy (Capacitive Load per Cycle)

Soft−Start

W

5.0

mJ

V

11

12

V

−0.3 to 2.2

−0.3 to 4.5

SS

Clamp Error Amp Input

V

CLEA

Foldback Input, Stand−by Management

−0.3 to V + 0.3

V

CC

Overvoltage Protection, Current Sense Input, R , Error Amp Input,

V

in

−0.3 to 5.5

V

ref

Error Amp Output, C , Stand−by Current Set

T

Demagnetization Detection Input Current

− Source

− Sink

8

mA

I

−4.0

10

demag−ib (Source)

I

demag−ib (Sink)

Error Amplifier Output Sink Current

13

I

20

E/A (Sink)

Power Dissipation and Thermal Characteristics

Maximum Power Dissipation at T = 85°C

P

0.6

W

A

D

Thermal Resistance, Junction−to−Air

Operating Junction Temperature

Operating Ambient Temperature

R

100

°C/W

q

JA

T

150

°C

J

T

−25 to +85

A

Maximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit

values (not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied,

damage may occur and reliability may be affected.

1. Maximum package power dissipation must be observed.

ELECTRICAL CHARACTERISTICS (V and V = 12 V [Note 2], R = 10 kW, C = 820 pF, for typical values T = 25°C,

CC

C

ref

T

A

for min/max values T = −25° to +85°C [Note 3], unless otherwise noted.)

A

Characteristic

OUTPUT SECTION (Note 4)

Pin #

Symbol

Min

Typ

Max

Unit

Output Voltage (Note 5)

3

V

Low Level Drop Voltage (I

(I

= 100 mA)

= 500 mA)

V

−

1.0

1.4

1.2

2.0

Sink

OL

High Level Drop Voltage(I

(I

= 200 mA)

= 500 mA)

V

−

1.5

2.0

2.7

Source

OH

Output Voltage During Initialization Phase

3

V

OL

V

= 0 to 1.0 V, I

= 1.0 to 5.0 V, I

= 5.0 to 13 V, I

= 10 mA

Sink

−

0.1

1.0

CC

= 100 mA

Sink

= 1.0 mA

Output Voltage Rising Edge Slew−Rate (C = 1.0 nF, T = 25°C)

3

dVo/dT

−

300

−

V/ms

L

J

Output Voltage Falling Edge Slew−Rate (C = 1.0 nF, T = 25°C)

−300

L

J

ERROR AMPLIFIER SECTION

Voltage Feedback Input (V

= 2.5 V)

14

V

2.4

−2.0

65

2.5

−0.6

70

2.6

−

V

mA

E/A out

FB

Input Bias Current (V = 2.5 V)

I

FB−ib

FB

Open Loop Voltage Gain (V

Unity Gain Bandwidth

= 2.0 V to 4.0 V)

A

VOL

−

dB

E/A out

BW

MHz

T = 25°C

−

5.5

J

T

= −25° to +85°C

A

Voltage Feedback Input Line Regulation (V = 10 V to 15 V)

14

V

−10

−

10

mV

CC

FBline−reg

2. Adjust V above the startup threshold before setting to 12 V.

CC

3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

4. No output signal when the Error Amplifier is in Low State, i.e., V = 2.7 V.

FB

5. V must be greater than 5.0 V.

C

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3

MC44604

ELECTRICAL CHARACTERISTICS (V and V = 12 V [Note 6], R = 10 kW, C = 820 pF, for typical values T = 25°C,

CC

C

ref

T

A

for min/max values T = −25° to +85°C [Note 7], unless otherwise noted.)

A

Characteristic

ERROR AMPLIFIER SECTION (continued)

Output Current

Pin #

Symbol

Min

Typ

Max

Unit

13

mA

Sink (V

= 1.5 V, V = 2.7 V)

I

Sink

E/A out

FB

T

A

= −25° to +85°C

2.0

12

−

Source (V

= 5.0 V, V = 2.3 V)

I

Source

E/A out

FB

T

A

= −25° to +85°C

−2.0

−0.2

Output Voltage Swing

V

High State (I

Low State (I

= 0.5 mA, V = 2.3 V)

V

OH

V

OL

5.5

−

6.5

1.0

7.5

1.1

E/A out (source)

FB

= 0.33 mA, V = 2.7 V)

E/A out (sink)

FB

REFERENCE SECTION

Reference Output Voltage (V = 10 V to 15 V)

16

V

2.4

−500

−40

2.5

−

2.6

−100

40

V

CC

ref

Reference Current Range (I = V /R , R = 5.0 k to 25 kW)

I

mA

mV

ref

ref ref

ref

Reference Voltage Over I Range

DV

−

ref

OSCILLATOR SECTION

Frequency

F

kHz

OSC

T

A

= 0° to +70°C

= −25° to +85°C

40.5

40

46

−

48.5

49

A

Frequency Change with Voltage (V = 10 V to 15 V)

DF

/DV

/DT

−

0.05

2.0

−

%/V

%/°C

V

CC

OSC

Frequency Change with Temperature (T = −25° to +85°C)

DF

A

OSC

Oscillator Voltage Swing (Peak−to−Peak)

10

V

I

−

OSC(P−P)

Ratio Charge Current/Reference Current (T = −25° to +85°C)

/I

0.35

78

0.43

82

−

A

charge ref

Fixed Maximum Duty Cycle = I

/(I

+ I

charge

)

D

80

%

discharge discharge

UNDERVOLTAGE LOCKOUT SECTION

Startup Threshold

1

V

13.6

14.5

15.4

V

stup−th

Disable Voltage After Threshold Turn−On

V

disable1

T

A

= 0° to +70°C

= −25° to +85°C

8.6

8.3

9.0

−

9.4

9.6

A

Disable Voltage After Threshold Turn−On

1

V

7.0

1.8

7.5

2.0

8.0

2.2

V

disable2

Delta V During Standby (V

−V

disable2

)

V

stup−th

CC

stup−th

(T = −25°C to 85°C)

A

−V

disable2

DEMAGNETIZATION DETECTION SECTION

Demagnetization Detect Input

8

Demagnetization Comparator Threshold (V

Propagation Delay (Input to Output, Low to High)

Decreasing)

V

50

−

−0.5

65

0.25

−

80

−

mV

ms

mA

pin8

demag−th

−

Input Bias Current (V

= 65 mV)

I

demag

demag−lb

Negative Clamp Level (I

= −2.0 mA)

C

−

−0.38

0.72

−

V

demag

L(neg)

Positive Clamp Level (I

= +2.0 mA)

demag

L(pos)

SOFT−START SECTION

Ratio Charge Current/I

I

/I

ss(ch) ref

−

ref

T

A

= 0° to +70°C

= −25° to +85°C

0.37

0.36

0.4

−

0.43

0.44

A

Discharge Current (V

Clamp Level

= 1.0 V)

11

I

1.5

2.2

5.0

2.4

−

mA

V

soft−start

discharge

V

2.6

ss(CL)

Duty Cycle (R

Duty Cycle (V

= 12 kW)

D

36

−

42

−

49

0

%

soft−start

soft−start (pin11)

soft−start 12k

D

soft−start

= 0.1 V)

6. Adjust V above the startup threshold before setting to 12 V.

CC

7. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

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4

MC44604

ELECTRICAL CHARACTERISTICS (V and V = 12 V [Note 8], R = 10 kW, C = 820 pF, for typical values T = 25°C,

CC

C

ref

T

A

for min/max values T = −25° to +85°C [Note 9], unless otherwise noted.)

A

Characteristic

CURRENT SENSE SECTION

Maximum Current Sense Input Threshold

(V = 2.3 V and V

Pin #

Symbol

Min

Typ

Max

Unit

7

V

0.93

−10

0.96

−2.0

1.00

−

V

cs−th

= 1.2 V)

foldback (pin6)

Feedback (pin14)

Input Bias Current

I

mA

cs−ib

Propagation Delay (Note 10)

in Normal Mode

in Standby Mode

t

−

120

200

ns

CS−NM

t

CS−stby

OVERVOLTAGE SECTION

Protection Threshold Level on V

6

V

2.42

1.0

2.5

−

2.58

3.0

V

ms

V

OVP

OVP−th

Propagation Delay (V

Protection Level on V

> 2.58 V to V Low)

out

OVP

CC

CC prot

T

A

= 0° to +70°C

= −25° to +85°C

16.1

15.9

17

−

17.9

18.1

A

Input Resistance

−

kW

T

A

= 0° to +70°C

= −25° to +85°C

1.5

1.4

2.0

−

3.0

3.4

A

FOLDBACK SECTION (Note 11)

Current Sense Voltage Threshold (V

= 0.9 V)

5

V

0.84

−6.0

0.88

−2.0

0.89

−

V

foldback (pin5)

cs−th

Foldback Input Bias Current (V

= 0 V)

I

mA

foldback (pin5)

foldback−lb

CLAMP ERROR AMPLIFIER INPUT

Clamp Level (@ l = 30 mA)

12

15

Vcl

4.5

4.7

4.9

V

STANDBY PULSED MODE SECTION

Standby Initialization Current Ratio (S1 closed)

Minimum Initialization Current Pulse Width (Note 12)

Standby On Detection Current Ratio

I

/I

126

−

140

−

154

1.0

−

ms

−

init ref

T

init

15

I

/I

0.34

18

0.38

20.5

−

0.42

23

det ref

Standby Regulation Current Ratio

I

/I

−

reg ref

Standby Bias Current (S1 and S2 open;

I

−1.0

2.0

mA

stby−ib

0 V t V

t V

) (Note 13)

stup−th

pin15

STANDBY CURRENT SET

Peak Standby Current Setting Ratio

9

7

−

T

A

= 0° to +70°C

I

/I

0.37

0.36

0.4

0.43

0.44

pk−stby ref

T

A

= −25° to +85°C

−

Standby Current Sense Threshold Ratio (Note 14)

V

/V

2.4

2.6

2.9

−

pin9 cs−st

TOTAL DEVICE

Power Supply Current

Startup (Note 13)

I

mA

CC

−

16

0.3

20

0.45

24

Operating T = −25° to +85°C (Note 9)

A

Power Supply Zener Voltage (I = 25 mA)

V

18.5

−

V

CC

Z

Thermal Shutdown

−

155

°C

8. Adjust V above the startup threshold before setting to 12 V.

CC

9. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

10.Current Sense Input to Output at V of MOS transistor = 3.0 V.

TH

11. This function can be inhibited by connecting pin 5 to V

.

CC

12.This is the minimum time during which the pin 15 current must be higher than I to enable the detection of the transition normal to standby mode.

init

13.Tested using V = 6.0 V, 9.0 V, 13.5 V, the MC44604 being off.

CC

14.Tested using V

= 0.2 V, 0.4 V, 0.6 V, 0.8 V, 1.0 V.

pin9

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5

MC44604

120

115

110

105

100

95

115

110

105

100

95

90

85

80

−50

80

−50

−25

0

25

50

75

100

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 1. Propagation Delay Current Sense

Input vs. Temperature

Figure 2. Propagation Delay Current Sense

Input in Standby vs. Temperature

3.2

3.1

3.0

2.5

2.0

3.0

2.9

2.8

1.5

1.0

−50

−25

0

25

50

75

100

−50

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 3. Current Sense Gain vs. Temperature

Figure 4. Propagation Delay Current

(V_ovp> 2.58 V to V_outLow) vs. Temperature

2.20

2.15

2.10

80

75

70

65

60

2.05

2.00

1.95

1.90

1.85

1.80

55

50

−50

−25

0

25

50

75

100

−50

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 5. Delta V_CCDuring Standby

Figure 6. Demag Comparator Threshold vs.

Temperature

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6

MC44604

160

70

60

0.890

0.885

0.880

0.875

0.870

0.865

0.860

0.855

0.850

0.845

0.840

V

= 0.9 V

pin5

50

40

30

− 60

20

10

0

−10

−20

−40

10000

1

10

100

1000

−50

−25

0

25

50

75

100

F, FREQUENCY (kHz)

T , AMBIENT TEMPERATURE (°C)

A

Figure 7. Error Amplifier Gain and Phase vs.

Frequency

Figure 8. Current Sense Voltage Threshold

vs. Temperature

0.42

0.41

0.40

0.39

0.38

49000

48000

47000

46000

45000

44000

43000

0.37

0.36

42000

41000

40000

0.35

0.34

−50

−25

0

25

50

75

100

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 9. Oscillator Frequency vs. Temperature

Figure 10. Standby On Detection Current Ratio

vs. Temperature

2.9

156

151

146

2.8

2.7

141

136

131

126

2.6

2.5

2.4

0

0.5

V

1

1.5

2

2.5

−50

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

, STANDBY CURRENT SET (V)

A

pin9

Figure 11. Standby Initialization Current Ratio vs.

Temperature

Figure 12. Standby Current Sense

Threshold Ratio

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7

MC44604

23.0

22.5

22.0

21.5

21.0

20.5

20.0

19.5

19.0

0.44

0.43

0.42

0.41

0.40

0.39

0.38

0.37

0.36

18.5

18.0

−50

−25

0

25

50

75

100

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 13. Peak Standby Current Setting Ratio

vs. Temperature

Figure 14. Standby Regulation Current Ratio

vs. Temperature

1.2

1.0

0.8

0.6

0.4

0.2

0

1.8

1.6

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0

100

200

300

400

500

0

100

I , OUTPUT SOURCE CURRENT (mA)

source

200

300

400

500

I

, SINK OUTPUT CURRENT (mA)

sink

Figure 15. Sink Output Saturation Voltage vs.

Sink Current

Figure 16. Source Output Saturation Voltage vs.

Source Current

0.45

24

20

16

12

0.40

0.35

0.30

0.25

0.20

0.15

0.10

0.05

8

4

0

2

4

6

8

10

12

14

0

2

4

6

8

10

12

14

16

V

, SUPPLY VOLTAGE (V)

CC

V , SUPPLY VOLTAGE (V)

CC

Figure 17. Startup Current vs. V_CC

Figure 18. Supply Current vs. Supply Voltage

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8

MC44604

15.5

14.5

13.5

12.5

18.0

V

, STARTUP THRESHOLD VOLTAGE

stup

17.5

17.0

11.5

10.5

9.5

V

, UVLO1

disable1

16.5

16.0

8.5

V

, UVLO2

disable2

7.5

6.5

−50

−25

0

25

50

75

100

−50

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 19. Startup Threshold, UVLO1, UVLO2

Voltage vs. Temperature

Figure 20. Protection Level on V_CCvs.

Temperature

2.60

2.55

2.50

4.90

4.85

4.80

4.75

4.70

4.65

4.60

4.55

4.50

2.45

2.40

−50

−25

0

25

50

75

100

−50

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 21. Clamp Error Amplifier Input vs.

Temperature

Figure 22. Reference Voltage vs. Temperature

22.0

21.5

21.0

20.5

20.0

19.5

18.0

−50

−25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

Figure 23. Power Supply Zener Voltage vs.

Temperature

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9

MC44604

1

Name

Pin Description

This pin is the positive supply of the IC.

V

CC

C

2

The output high state, V , is set by the voltage applied to this pin. With a separate

OH

connection to the power source, it gives the possibility to set by means of an external

resistor the output source current at a different value than the sink current.

3

Output

The output current capability is suited for driving a power MOSFET. A Bipolar

transistor can also be driven for low power applications. The maximum on−time of the

duty cycle can last up to 80% of the switching period.

4

5

GND

The ground pin is a single return typically connected back to the power source, it is

used as control and power ground.

Foldback Input

The foldback function ensures an overload protection. Feeding the foldback input with

a portion of the V voltage (1.0 V max) establishes on the system control loop a

CC

foldback characteristic allowing a smoother startup and a sharper overload protection.

The foldback action performs an active current sense clamping reduction. Above

1.0 V the foldback input is no more active.

6

7

Overvoltage Protection

Current Sense Input

When the overvoltage protection pin receives a voltage greater than 17 V the device

gets disabled and requires a complete restart sequence. The overvoltage level is

programmable.

A voltage proportional to the current flowing into the power switch is connected to this

input. The PWM latch uses this information to terminate the conduction of the output

buffer when operating in current mode. A maximum level of 1.0 V allows to limit the

inductor current either in current or voltage mode of operation.

8

Demagnetization Detection

A voltage delivered by an auxiliary transformer winding provides to the

demagnetization pin an indication of the magnetization state of the flyback energy

reservoir. A zero voltage detection corresponds to a complete core demagnetization.

The demagnetization detection ensures a discontinuous mode of operation. This

function can be inhibited by connecting Pin 8 to GND.

9

Standby Current Set

Using an external resistor connected to this pin, the standby burst mode peak current

can be adjusted.

10

C

T

The normal mode oscillator frequency is programmed by the capacitor C choice

T

together with the R resistance value. C , connected between pin 10 and GND,

ref

T

generates the oscillator sawtooth.

11

12

Soft−Start/D

/Voltage−Mode

A capacitor or a resistor or a voltage source connected to this pin can temporary or

permanently control the effective switching duty−cycle. This pin can be used as a

voltage mode control input. By connecting pin 11 to Ground, the MC44604 can be

shut down.

max

Clamp Error Amplifier Input

In normal mode, the current drawn from this pin, is used by the Error Amplifier to

perform the regulation. A 4.7 V zener diode clamps the voltage of this pin.

13

14

E/A Out

The error amplifier output is made available for loop compensation.

Voltage Feedback

This is the inverting input of the Error Amplifier. It uses a voltage that is built up using

the current drawn from the pin 12.

15

Standby Management

This block is designed to detect the standby mode. It particularly determines if the

circuit must work in standby or in normal mode at each startup. For that, it uses an

information given by an external arrangement consisting of an opto−coupler. In

standby mode, this block makes the circuit work in the standby configuration, and the

current injected in the pin 15 is used to perform the regulation. In normal mode, this

pin is internally connected to the pin 12.

16

R

REF

The R

values fixes the internal reference current which is used to perform the

REF

precise oscillator waveform. The current range goes from 100 mA up to 500 mA.

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10

MC44604

Operating Description Schematics

V

CC

stup−th

V

disable1

disable2

V

ref

UVLO1

V

Pin 11

(Soft−Start)

Output

(Pin 3)

I

CC

17 mA

0.3 mA

Figure 24. Switching Off Behavior

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11

MC44604

Operating Description Schematics

Loop Failure

No−Take Over

V

Restart

Startup

ms

>2.0

CC

CC prot

V

stup−th

Normal Mode

V

disable1

disable2

V

ref

UVLO1

V

Pin 11

(Soft−Start)

V

OVP Out

Output

I

CC

17 mA

0.3 mA

Figure 25. Starting Behavior and Overvoltage

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12

MC44604

Operating Description Schematics

V

ref

V

+ 1.6 V

CSS

Internal Clamp

External Clamp

Soft−Start

V

3.6 V

CT

V

low 1.6 V

CT

V

OSC

Output

(Pin 3)

Figure 26. Soft−Start and D_max

V

demag in

Output

(Pin 3)

V

demag out

V

demag out

Demagnetization

Management

V

Oscillator

demag in

Output

Buffer

Figure 27. Demagnetization

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13

MC44604

Error Amplifier

Current Sense Comparator and PWM Latch

A fully compensated Error Amplifier with access to the

inverting input and output is provided. It features a typical

DC voltage gain of 70 dB. The non−inverting input is

internally biased at 2.5 V and is not pinned out. The

converter output voltage is typically divided down and

monitored by the inverting input. The maximum input bias

current with the inverting input at 2.5 V is −2.0 mA. This can

cause an output voltage error that is equal to the product of

the input bias current and the equivalent input divider source

resistance.

The Error Amp Output (Pin 13) is provided for external

loop compensation. The output voltage is offset by two

diodes drops ([ 1.4 V) and divided by three before it

connects to the inverting input of the Current Sense

Comparator. This guarantees that no drive pulses appear at

the Source Output (Pin 3) when Pin 13 is at its lowest state

The MC44604 can operate as a current mode controller

and/or as a voltage mode controller. In current mode

operation, the MC44604 uses the current sense comparator,

where the output switch conduction is initiated by the

oscillator and terminated when the peak inductor current

reaches the threshold level established by the Error

Amplifier output (Pin 13). Thus the error signal controls the

peak inductor current on a cycle−by−cycle basis. The

Current Sense Comparator PWM Latch configuration used

ensures that only a single pulse appears at the Source Output

during the appropriate oscillator cycle.

The inductor current is converted to a voltage by inserting

the ground referenced sense resistor R in series with the

S

power switch Q1.

In normal mode, this voltage is monitored by the Current

Sense Input (Pin 7) and compared to a level derived from the

Error Amp output. The peak inductor current under normal

operating conditions is controlled by the voltage at Pin 13

where:

(V ). This occurs when the power supply is operating and

OL

the load is removed, or at the beginning of a soft−start

interval. The Error Amp minimum feedback resistance is

limited by the amplifier’s minimum source current (0.2 mA)

V

* 1·4 V

(pin13)

and the required output voltage (V ) to reach the current

OH

I

[

pk

3 R

sense comparator’s 1.0 V clamp level:

S

The Current Sense Comparator threshold is internally

clamped to 1.0 V. Therefore the maximum peak switch

current is:

3·0(1·0 V) ) 1·4 V

R

[

+ 22 kΩ

f (min)

0·2 mA

1·0 V

+

I

[

pk(max)

1.0 mA

R

Compensation

13

S

Error

Amplifier

R

FB

R

f

V

in

2R

2.5 V

14

C

1

V

C

R

Voltage

Feedback

Input

14

UVLO

Current

Sense

Comparator

V

OSCPROT

R

2

Q1

V

Foldback

Input

demag out

5

+

3

1.0 V

R

1

V

OSC

R

S

3

(from Oscillator)

Thermal

Protection

4.7 W

R

Q

Pin 12

PWM

Latch

R

2

GND

4

Substrate

MC44604

Current

Sense

Current Sense

Comparator

R

Figure 28. Error Amplifier Compensation

7

R

S

C

In a preferred embodiment, the feedback signal (current)

is drawn from the pin 12 that is connected to the pin 15 in

normal mode (Note 1). Using a resistor connected on pin 12,

this current generates a voltage that is the input signal of the

error amplifier arrangement.

Figure 29. Output Totem Pole

Oscillator

The oscillator is a very accurate sawtooth generator.

Note 1. The error amplifier is not used in the standby mode

regulation.

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14

MC44604

The Sawtooth Generation

order to perfectly compensate the (0.4 I ) current source

ref

In the steady state, the oscillator voltage varies between

about 1.6 V and 3.6 V.

Indeed, the sawtooth is obtained by charging and

that permanently supplies C .

T

On−time is only allowed during the oscillator capacitor

charge. So, the maximum duty cycle is 80%. (Note 1)

The demagnetization condition is taken into account by a

discharging an external capacitor C (Pin 10), using two

T

distinct current sources = I

and I

. In fact, C

discharge T

second latch (L ). (Refer to demagnetization § for further

charge

osc

is permanently connected to the charging current source

(0.4 I ) and so, the discharge current source has to be

details.)

ref

Oscillator Frequency

The oscillator frequency can be deducted using the

following equations:

higher than the charge one to be able to decrease the C

T

voltage. This condition is performed, its value being

(2 I ).

ref

.

Two comparators are used to generate the sawtooth. They

T

+ C

charge

discharge

T ^{• DVń I}charge

compare the C voltage to the oscillator valley and peak

T

values. The comparison to the low value enables to detect the

end of the discharge phase while the comparison to the high

value determines when the charge cycle must be stopped. A

T ^{• DVń I}discharge

T

where:

T

latch (L

) memorizes the oscillator state.

DISCH

is the oscillator charge time

charge

DV is the oscillator peak to peak value

V

ref

I

is the oscillator charge current

is the oscillator discharge time

discharge

charge

0.4 I

REF

and

T

C

VOS PROT

V

osc prot

I

is the oscillator discharge current

discharge

1 V

V

osc

So, as:

C < 1.6 V

T

f

= 1 /(T

+ T

) if the REGUL

discharge

C

osc

charge

OSC LOW

arrangement is not activated, the following equation can

be obtained:

DISCHARGE

1.6 V

S

Q

R

Q

L

OSC

0·395

C

OSC HIGH

f

X

DISCH

S

R

osc

10

R

• C

ref

T

V

C

T

demag out

Demagnetization Block (Note 2)

To enable the output, the L latch complementary output

3.6 V

C

OSC REGUL

osc

must be low. Now, this latch reset is activated by the L

DISCH

0

1

output during the discharge phase. So, to restart, the L has

osc

to be set (refer to Figure 30). To perform this, the

demagnetization signal must be low.

In a fly−back, a good means to detect the demagnetization

1

0

consists in using the V

voltage is:

winding voltage. Indeed this

CC

I

REGUL

I

DISCHARGE

−

negative during the on−time,

positive during the off−time,

equal to zero for the dead−time with generally a

ringing (refer to Figure 31).

MC44604

Figure 30. Oscillator

That is why, the MC44604 demagnetization detection

consists of a comparator that can compare the V winding

voltage to a reference that is typically equal to 65 mV.

CC

Now, in addition to the charge and discharge cycles, a

third state can exist. This phase can be produced when at the

end of the discharge phase, the oscillator has to wait for a

demagnetization pulse before re−starting. During this

Note 1. The output is disabled by the signal V_{osc prot}when V_CT

is lower than 1 V. (Refer to Figure 29 and Figure 30.)

delay, the C voltage must remain equal to the oscillator

T

valley value (X1.6 V). So, a third regulated current source

Note 2. The demagnetization detection can be inhibited by

connecting pin 8 to the ground.

I

controlled by C

, is connected to C in

OSC REGUL T

REGUL

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15

MC44604

Output

Control

V

ref

0.4 I

ref

0.75 V

Pin 11

Zero Current

Detection

V

Output

Buffer

Pin 8

D

Z

2.4 V

D

max

65 mV

V

OSC

Soft−Start

Capacitor

Oscillator

MC44604

−0.33 V

On−Time Off−Time Dead−Time

Figure 33. D_maxand Soft−Start Block Diagram

Figure 31. Demagnetization Detection

Maximum Duty Cycle and Soft−Start Control

A diode D has been incorporated to clamp the positive

applied voltages while an active clamping system limits the

negative voltages to typically −0.33 V. This negative clamp

level is sufficient to avoid the substrate diode switching on.

In addition to the comparator, a latch system has been

incorporated in order to keep the demagnetization block

output level low as soon as a voltage lower than 65 mV is

detected and as long as a new restart is produced (high level

on the output) (refer to Figure 33). This process avoids that

any ringing on the signal used on the pin 8, disrupts the

demagnetization detection. Finally, this method results in a

very accurate demagnetization detection.

As explained in the paragraph “oscillator”, the duty cycle

cannot be more than 80%. Now, using the D

and

max

soft−start control, this duty cycle can be limited to a lower

value. Indeed as depicted in Figure 34, the pin 11 voltage is

compared to the oscillator sawtooth, so that the MC44604

output should be disabled as soon as the pin 11 level

becomes lower than the oscillator voltage (refer to Figure 27

and to Figure 25).

Pin 11

Voltage

V

CT

(Pin 10)

For a higher safety, the demagnetization block output is

also directly connected to the output, disabling it during the

demagnetization phase (refer to Figure 29).

D

max

Figure 34. Maximum Duty Cycle Control

Output

Oscillator

Now, using the internal current source (0,4 I ), the pin 11

voltage can easily be fixed by connecting a resistor to this

pin.

If a capacitor is connected to pin 11 (without any resistor

or in parallel to a resistor for instance), the pin 11 voltage

increases from 0 to its maximum value progressively (refer

to Figure 26).

ref

Buffer

R

Q

Demag

S

V

CC

Negative Active

Clamping System

V

demag out

Thus, the allowed maximum duty cycle grows for a delay

depending on the capacitor value (and the resistor value

when a resistor is connected).

So, this pin can be used to limit the duty cycle during the

startup phase and thus, to perform a soft−start.

Pin 8

65 mV

C DEM

D

Figure 32. Demagnetization Block

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16

MC44604

Pin 11

RI

V

grows up till it reaches its maximum value (normally,

= 1 V).

C

C // R

CS

R Connected to

V

RI

V

Z

Pin 11

CS max

I = 0.4 I

Then if the output load keeps on increasing, the system is

not able to supply enough energy to maintain the output

regulation. Consequently, the decreasing output can be used

to apply a voltage that diminishes to a value lower than 1 V,

to pin 5, in order to limit the maximum peak current. In this

way, the well known foldback characteristic is obtained

(refer to Figure 36).

ref

τ = RC

Figure 35. Different Possible Uses of Pin 11

In any case (particularly if no external component is

connected to pin 11), an internal zener diode (D , refer to

Figure 34) is able to clamp the pin 11 voltage to a value V

that is higher than the oscillator value and so, that results in

no max duty cycle limitation.

Z

The foldback action can be inhibited by connecting the pin

Z

5 to V

.

CC

Overvoltage Protection

The overvoltage arrangement consists of a comparator

As soon as V

is detected, a signal UVLO1 is

disable1

that compares the pin 6 voltage to V (2,5 V) (refer to

generated until the V voltage falls down to V

ref

CC

disable2

Figure 37).

(refer to the undervoltage lockout section paragraph).

During the delay between the disable 1 and the disable 2,

using a transistor controlled by UVLO1, the pin 11 voltage

is made equal to zero in order to make the max duty cycle and

soft−start arrangement ready to work for the next restart.

In standby mode, this block is inhibited in order not to

interfere with the Standby Current Set.

V

ref

V

CC

In

Delay

Out

τ

5.0 ms

T

2.5 V

0

V

Pin 6

Protection

OVP

Enable

11.6 K

V

OVP out

The MC44604 can ensure a high converter reliability

thanks to the protection it offers.

τ

In

Out

Delay

2 K

C

OVLO

2.0 ms

2.5 V

(V

Demagnetization Detection (Refer to Demag §)

(If V

= 1.0,

OVP out

)

ref

Foldback

the Output is Disabled)

As depicted in Figure 28, the foldback input (pin 5)

enables to reduce the maximum V value that would be

CS

Figure 37. Overvoltage Protection

equal to 1 typically, if there was no foldback action. Finally,

the foldback arrangement is a programmable peak current

limitation.

If no external component is connected to pin 6, the

comparator non inverting input voltage is nearly equal to:

I

2 kΩ

V

pk max

out

ǒ

Ǔ

_•V

CC

11, 6 kΩ ) 2 kΩ

V

O

So, the comparator output is high when:

Nominal

2 kΩ

ǒ

Ǔ_•

w 17 V

V

w 2, 5 V

CC

11, 6 kΩ ) 2 kΩ

New Startup

Sequence Initiated

V

CC

V

CC

disable2

A delay latch (2 ms) is incorporated in order to only take

into account the overvoltages that last at least 2 ms.

V

I

out

If this condition is achieved, V

the delay latch

Overload

OVPout

output becomes high and as this level is brought back to the

input through an OR gate, V remains high (and so,

OVPout

Figure 36. Foldback Characteristic

the IC output is disabled) until V is disabled.

ref

Consequently when an overvoltage longer than 2 ms is

detected, the output is disabled until a new circuit restart.

It could be used as a soft−start (by connecting to pin 5, a

gradually increasing voltage) but in fact, it has been

designed to provide the system with an effective overload

protection.

Indeed, as the output load gradually increases, the

required converter peak current becomes higher and so,

The V

is connected when once the circuit has

CC

started−up in order to limit the circuit startup consumption

(T is switched on when once V has been generated).

ref

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17

MC44604

The overvoltage section is enabled 5 ms after the regulator

Thus, finally in normal mode, the upper V limit that

cc

has started to allow the reference V to stabilize.

enables the output to be active, is 9.4 V (maximum value of

ref

By connecting external resistors to pin 6, the threshold

V

disable1

) and so the minimum hysteresis is 4.2 V.

V

CC

level can be changed.

[(V

)

= 13.6 V].

stup−th min

The large hysteresis and the low startup current of the

MC44604 make it ideally suited for off−line converter

applications where efficient bootstrap startup techniques are

required.

R

ref

Pin 16

V

ref enable

V

CC

Standby Management

(Pin 1)

C

STARTUP

The MC44604 has been designed to detect the transitions

between the standby and normal mode and to manage each

mode in an optimal way.

In standby, the device monitors a pulsed mode that enables

to drastically reduce the power consumption.

Reference Block:

Voltage and Current

Sources Generator

1

0

1

0

(V , I , ...)

ref ref

V

STARTUP

14.5 V

disable

7.5 V or

12.5 V

Pulsed Mode

UVLO1

(to SOFT−START)

The MC44604 standby is preferably associated to a

flyback configuration as depicted in Figure 39.

C

UVLO1

V

disable1

MC44604

9.0 V

Input

Voltage

Figure 38. V_CCManagement

1 = Standby

0 = Normal

Mode

0

L

p

V

CC

Undervoltage Lockout Section

1

As depicted in Figure 39, an undervoltage lockout has

been incorporated to guarantee that the IC is fully functional

before allowing operation of the system.

mP

V

MC44604

stby

Indeed, the V is connected to the non inverting input of

CC

Regulator

a comparator that has an upper threshold equal to 14,5 V

(V

) and a lower one equal to 7.5 V (V

) in

stup−th

disable2

normal mode and 14.5 V and 12.5 V in Standby mode

(typical values) (Note 1).

This hysteresis comparator enables or disables the

reference block that generates the voltage and current

sources required by the system.

Figure 39. Standby Flyback Configuration

In effect, by this means, all the output regulation levels are

divided by the ratio:

This block particularly, produces V (pin 16 voltage)

ref

and I that is determined by the resistor R connected

ref

V

between pin 16 and the ground:

HV

V

stby

ref

I

+

where V + 2.5 V (typically)

ref

R

ref

where V

level, V

is the normal mode high voltage regulation

is the standby mP supply voltage.

HV

In addition to this, V is compared to a second threshold

CC

stby

level that is nearly equal to 9 V (V

) so that in normal

For instance, in the case of TV or monitors applications,

disable1

mode, a signal UVLO1 is generated to reset the maximum

duty cycle and soft−start block and so, to disable the output

stage (refer to Max. Duty Cycle and Soft−Start §) as soon as

the output levels (except the mP supply voltage, V ) are

drastically reduced by a ratio in the range of 10.

Consequently, as the output voltages are reduced, the

losses due to the output leakage consumption, are practically

eliminated, without having to disconnect the loads.

stby

V

CC

becomes lower than V

. In this way, the circuit is

disable1

reset and made ready for a next startup, before the reference

block is disabled (refer to Figure 26). In standby, UVLO1 is

not active (there is no need to discharge the soft−start

capacitor as the soft−start pin is maintained short circuited).

Startup Operations

The choice of the right configuration (normal or standby)

is performed at each startup.

Note 1. In standby the difference between V_disable2and

V_stup−this decreased not to have too low pulsed mode

frequencies.

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18

MC44604

Standby Management

The standby operation consists of two main phases:

That is why, as explained in the transitions §, at each

change of mode, the MC44604 is first turned off so that a

new startup should be performed.

−

the off phase during which the MC44604 is off.

During this sequence, the circuit V is being charged

and no energy is transferred to the output.

the active phase during which the MC44604 is on. At

this moment, some power can be drawn from the

mains.

cc

V

gets higher than V

Startup

cc

stup−th

During the active phase, the power conversion is

controlled so that:

YES

NO

I

15 > I

*

det

−

the normal mode regulation means (error amplifier)

and the soft−start are inhibited

−

the V undervoltage lockout (V

) level is

cc

disable2

STANDBY

NORMAL MODE

increased from 9 V up to 12.5 V. This limitation of the

hysteresis enables to increase the pulsed mode

frequency

the peak inductor current is forced to be constant and

equal to the level programmable by the external

− The pin 15 is con-

nected to pin 12 to pro-

vide the E/A input with a

feedback

− the standby block is in-

hibited

− Pin 15 and pin 12 are kept

disconnected and so, the

E/A input receives no feed-

back (the regulation is per-

V

cc

−

formed by comparing I

pin15

to I

− refer to standby

reg

resistor R

connected to the pin 9 so that:

Ipmax

regulation w)

− the soft−start is inhibited

and its capacitor is dis-

charged

− the lpmax limitation block

is activated (clamp of the

peak current)

0, 4 I R

ref

lpmax

I

+

pmax

2, 6 R

S

where: I

is the standby inductor peak current, R is

S

the current sense resistor.

pmax

−

the level

V

is

disable2

−

when the pin 15 current gets higher than the threshold

* this test is performed

during the first 5 ms of

circuit operation

increased (refer to under-

voltage lockout section)

I

(20.5 I ), this operating mode stops and the

reg

ref

circuit output is latched off.

So, in fact, the active phase is split into two distinct

sequences and finally three phases can be defined (refer to

Figure 32):

Figure 40. Startup Operation

At each startup, the circuit detects if it must work in

standby or in normal mode configuration.

To do that, the circuit compares the current I

so that, if:

−

the off phase: the MC44604 is off and the V

cc

capacitor is being charged. When the V gets higher

cc

to I

pin15

det

than V

, the circuit turns on and the switching

stup−th

sequence starts

the switching phase: the circuit is on and forces a

constant peak inductor current. This sequence lasts

−

I

> I : Standby mode

pin15

det

−

< I : Normal mode

pin15

det

According to the detected mode, the circuit configuration

is set (refer to Figure 40).

This detection phase takes place during the first 5 ms of

circuit operation in order to have the internal signals well

stabilized before the decision is taken.

until I

gets higher than I

pin15

reg

the latched phase: the circuit is on but the output is

disabled. This sequence lasts until the standby V

cc

undervoltage lockout voltage (12.5 V) is reached. A

new off phase is then initialized.

V

CC

stby

Opto Coupler

R

init

Pin 15

R

reg

R

det

TL431

Z

C

mP

T

MC44604

Figure 41. Standby Pin 15 Arrangement

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19

MC44604

detect a sequence during which I_pin15lower than I_reg

before being able to latch gets higher than V_z).

V

(14.5 V)

stup

V

CC

Transitions Between Normal Mode and Standby Mode

(Refer to Figure 43)

The MC44604 detects a transition by comparing the pin

15 current to:

Stby V

disable 2

(12.5 V)

V

stby

mP supply

voltage

−

I

(transition standby to normal mode)

(transition normal mode to standby)

det

init

V

pin 15

Each transition detection results in the circuit turning off,

so that the device can work in the new mode after the

following restart.

I

zener

• transition normal mode to standby:

This transition is detected by comparing the I

I

reg

det

I

pin 15

current

pin15

to the threshold current (I ).

init

output

I

is high enough so that the opto coupler current used

init

for the regulation, never exceeds this value.

time

The output is latched off

until the next re−start

The arrangement in Figure 41 is well adapted to this mode

of operation. The mP initializes the standby mode by turning

on the switch T. This results in the C capacitor charge that

produces a peak current in the primary side of the opto

Figure 42. Standby Regulation

As a consequence, V

varies between a peak value

coupler. C and R must be dimensioned so that the opto

stby

init

(obtained at the end of the switching phase) and a valley

level (reached at the end of the off phase).

coupler primary side generates a pin 15 current higher than

I

during more than 1 ms.

init

The level of the peak value is controlled by forcing a

• transition standby to normal mode:

current higher than I in pin 15 when this level has reached

reg

If the circuit detects that (I

< I ) during standby

pin15

det

the desired value.

The arrangement in Figure 41 allows to obtain this

operation. A zener diode Z is connected so that a current

operation, the circuit is turned off. So, if the normal mode is

maintained at the following startup, the circuit will restart in

a normal mode configuration.

limited by R , is drawn by this device, when the mP supply

reg

The arrangement in Figure 41 allows to perform this

detection. When the mP detects the end of the standby, it

turns off the switch T and the opto coupler stops supplying

current to the circuit.

voltage gets higher than V . By this way, the current injected

in the pin 15 increases and when this current is detected as

z

higher than I , the output gets disabled until the next

reg

startup (Note 1).

Practically, the pin 15 current can be expressed as follows

(when the zener is activated):

14.5 V

....

(

)

V

CC

12.5 V

Normal

Mode

V

* V * V

z

opto

Normal

Mode

stby

I

+ CTR

Standby Burst Mode

pin15

R

reg

Standby

Normal

Mode

where: CTR is the opto coupler gain, V

is opto coupler

time

opto

voltage drop.

The transition stand−by to normal mode occurs while

So, as the Vstby peak value is obtained when (I

), it can be calculated using the following equation:

=

pin15

the circuit is off (V charge phase)

CC

I

reg

R

I

14.5 V

reg

....

)

V

(

CC

V

+ V ) V

)

12.5 V

Normal

Mode

z

opto

stby pk

CTR

Normal

Mode

Practically, R is chosen very low (in the range of 10 W,

Standby Burst Mode

reg

low resistance just to limit the current when V

gets

stby pk

Standby

Normal

Mode

higher than V ):

z

time

V

^ V ) V

z

opto

stby pk

The transition stand−by to normal mode occurs while

the circuit is on (working phase)

Note 1. If the pin 15 current is higher than I_regat startup, the

output is just shutdown but not latched. The circuit must

Figure 43. Transitions Between Modes

http://onsemi.com

20

MC44604

Application Schematic

185 Vac

to

270 Vac

RFI

Filter

CS

1nF11kV

1 W 15 W

C4....C7

1 nF/1000 V

RS

4.7 MW

220 pF

120/0.5 A

D1 ... D4

1N4007

C1

100 mF

MR856

22 kW

(5W)

100 pF

0.1 mF

47 k 120 pF

1 mH

1N4148

R2

100 nF

68 KW

(2W)

C2

100 mF

1N4937

MCR22−6

1 kW

V

CC

1N4148

28V/1A

R4

27 kW

C16

47 nF

220 pF

R19

10 kW

100 pF

Laux

8

7

6

5

4

3

2

1

9

1N4148

1.2 k

1 kW

MR856

100 mF

MR856

10

11

12

13

14

15

16

0.1 mF

1 nF

C9 1 nF

Lp

R9 180 kW

R8 15 kW

220 pF

C10 1mF

C14

4.7 nF

15V/1A

R6

150 W

R15

1 kW

22 kW

MR852

1000 mF

C11

1mF

C18

2.2 nF

0.1 mF

8V/1A

0.1 mF

R26 20 W

MTP6N60E

R16

R11 100 W

22

220 pF

MR856

kW

R13

1 kW

(5W)

BC237B

MR852

R14

0.47 W

(1W)

R19

10 kW

C13

100 nF

4700 mF

V

CC

MOC8104

117.5 kW

100 nF

4.7 kW

4.7 k

220 kW

8.2 k 22 W

270 W

TL431

47 W

12 V

BC237B

2.5 kW

m P

4.7 kW

BC237B

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21

MC44604

PACKAGE DIMENSIONS

PDIP−16

P SUFFIX

CASE 648−08

ISSUE T

NOTES:

−A−

1. DIMENSIONING AND TOLERANCING PER

ANSI Y14.5M, 1982.

2. CONTROLLING DIMENSION: INCH.

3. DIMENSION L TO CENTER OF LEADS

WHEN FORMED PARALLEL.

4. DIMENSION B DOES NOT INCLUDE

MOLD FLASH.

16

1

9

8

B

S

5. ROUNDED CORNERS OPTIONAL.

INCHES

DIM MIN MAX

0.740 0.770 18.80 19.55

MILLIMETERS

F

C

L

MIN MAX

A

B

C

D

F

0.250 0.270

0.145 0.175

0.015 0.021

6.35

3.69

0.39

1.02

6.85

4.44

0.53

1.77

SEATING

PLANE

−T−

0.040

0.70

G

H

J

K

L

0.100 BSC

2.54 BSC

1.27 BSC

K

M

H

0.050 BSC

0.008 0.015

0.110 0.130

0.295 0.305

J

0.21

2.80

7.50

0.38

3.30

7.74

G

D 16 PL

M

0.25 (0.010)

T A

M

S

0

10

0

0.51

10

_

1.01

_

0.020 0.040

GreenLine is a trademark of Motorola, Inc.

ON Semiconductor and

are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice

to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability

arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.

“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All

operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights

nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications

intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should

Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,

and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death

associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal

Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.

PUBLICATION ORDERING INFORMATION

LITERATURE FULFILLMENT:

N. American Technical Support: 800−282−9855 Toll Free

USA/Canada

ON Semiconductor Website: http://onsemi.com

Order Literature: http://www.onsemi.com/litorder

Literature Distribution Center for ON Semiconductor

P.O. Box 61312, Phoenix, Arizona 85082−1312 USA

Phone: 480−829−7710 or 800−344−3860 Toll Free USA/Canada

Fax: 480−829−7709 or 800−344−3867 Toll Free USA/Canada

Email: orderlit@onsemi.com

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2−9−1 Kamimeguro, Meguro−ku, Tokyo, Japan 153−0051

Phone: 81−3−5773−3850

For additional information, please contact your

local Sales Representative.

MC44604/D

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22


型号：	MC44604PG
厂家：	ONSEMI
描述：	High Safety Pulsed Mode Standby GreenLine TM PWM Controller 高安全性脉冲模式待机GREENLINE TM PWM控制器脉冲控制器
文件：	总22页 (文件大小：189K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

MC44604PG [ONSEMI]

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