NCP5393 [ONSEMI]
2/3/4-Phase Controller for CPU Applications; 2/3/ 4相位控制器的CPU应用型号: | NCP5393 |
厂家: | ONSEMI |
描述: | 2/3/4-Phase Controller for CPU Applications |
文件: | 总21页 (文件大小:490K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
NCP5393
2/3/4-Phase Controller for
CPU Applications
The NCP5393 controls up to four V
phases and one V
DDNB
DD
phase to provide a buck regulator solution for current and
next-generation AMD processors. The NCP5393 incorporates
differential voltage sensing, differential phase current sensing,
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optional load-line voltage positioning, and programmable V and
V
DD
offsets to provide accurately regulated power parallel- and
DDNB
MARKING
DIAGRAM
serial-VID AMD processors. Dual-edge multiphase modulation
provides the fastest initial response to dynamic load events. This
reduces system cost by requiring less bulk and ceramic output
capacitance to meet transient regulation specifications.
1
High performance operational error amplifiers are provided to
regulators. Dynamic
NCP5393
AWLYYWWG
simplify compensation of the V and V
DD
DDNB
1
48
Reference Injection further simplifies loop compensation by
eliminating the need to compromise between response to load
transients and response to VID code changes.
QFN48, 7x7
CASE 485AJ
A
= Assembly Location
= Wafer Lot
= Year
Features
WL
YY
WW
G
•ꢀMeets AMD's Parallel, Serial (SVI) and Hybrid VR Specifications
= Work Week
= Pb-Free Package
•ꢀUp to Four V Phases
DD
•ꢀSingle-Phase V
Controller
DDNB
•ꢀDual-Edge PWM for Fastest Initial Response to Transient Loading
•ꢀHigh Performance Operational Error Amplifiers
•ꢀInternal Soft Start and Slew Rate Limiting
ORDERING INFORMATION
†
Device
NCP5393MNR2G
Package
Shipping
•ꢀDynamic Reference Injection (Patent #US07057381)
•ꢀDAC Range from 12.5 mV to 1.55 V
QFN48
(Pb-Free)
2500 / Tape & Reel
•ꢀ$0.5% DAC Accuracy fro 0.8 V to 1.55 V
†For information on tape and reel specifications,
including part orientation and tape sizes, please
refer to our Tape and Reel Packaging Specifications
Brochure, BRD8011/D.
•ꢀV and V Offset Ranges 0 mV - 800 mV
DD
DD
•ꢀTrue Differential Remote Voltage Sense Amplifiers
•ꢀPhase-to-Phase I Current Balancing
DD
•ꢀDifferential Current Sense Amplifiers for Each Phase of Each Output
•ꢀ“Lossless” Inductor Current Sensing for V and V
Outputs
DD
DDNB
•ꢀSupports Load Lines (Droop) for V and V
Outputs
DD
DDNB
•ꢀOscillator Range of 100 kHz - 1 MHz
•ꢀTracking Over Voltage Protection
•ꢀOutput Inductor DCR-Based Over Current Protection for V and
DD
V
DDNB
Outputs
•ꢀGuaranteed Startup into Precharged Loads
•ꢀTemperature Range: 0°C to 70°C
•ꢀThis is a Pb-Free Device*
Applications
•ꢀDesktop Processors
•ꢀServer Processors
•ꢀHigh-End Notebook PCs
*For additional information on our Pb-Free strategy and soldering details, please
download the ON Semiconductor Soldering and Mounting Techniques
Reference Manual, SOLDERRM/D.
©ꢀ Semiconductor Components Industries, LLC, 2008
February, 2008 - Rev. 0
1
Publication Order Number:
NCP5393/D
NCP5393
48
1
VCCA
GND
VID1
VID0
NB_COMP
NB_FB
COMP
FB
DROOP
VS+
VS-
NB_DROOP
NB_VS+
NB_VS-
NB_OFFSET
NB_DIFFOUT
ROSC
OFFSET
DIFFOUT
VFIX
12VMON
PSI_L
VID5
VID4
Figure 1. Pinout
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2
NCP5393
NB_VS+
NB_VS-
-
+
+
-
NB_G
HI-Z
MID
Diff Amp
NB_DIFFOUT
PWM_NB
OVP
FAULT VDD PSI_L
1.3 V
+
-
NB_FB
+
-
Error Amp
ILIMIT_NB
NB_DRVON
NB_COMP
NB_DROOP
NB REGULATOR
Fault Logic
and
ILIMIT_NB =
ILIMIT_VDD/N
(N = VDD
NB_SRL
NB_DAC
NB_VS+
Monitor Circuits
Gain = 1
Droop Amplifier
phase count) NB_VS-
1.3 V
+
NB OFFSET
SCALING
X
NB_CS
NB_CSN
+
-
Gain
= 6
NORMAL OPERATION
NB_OFFSET
BOOT_VID & VFIX MODES
NB
NB_DAC OUT
Oscillator
PWRGOOD
PWROK
NB_SRL
OUT
+
NB
NB Slew
Rate Lim‐
it
VID0
f
= 1.27 x f
NB
VDD
PVI/SVI
HYBRID
VID1
VID2/SVD
VID3/SVC
VID4
INTERFACE
VDD Slew
Rate Limit
VID5
VDD_DAC OUT
+
VDD_SRL OUT
VS-
VS+
-
+
VDD
PSI_L
DIFFOUT
Diff Amp
NORMAL OPERATION
X
OFFSET
BOOT_VID & VFIX MODES
VDD OFFSET
SCALING
1.3 V
+
FB
FLAG
-
Error Amp
COMP
GND
DROOP
Gain = 1
1.3 V
VDD PSI_L
Droop Amplifier
+
+
CS1
CS1N
+
G1
+
-
PWM1
-
Gain = 6
HI-Z
HI-Z
HI-Z
MID
MID
+
CS2
CS2N
+
G2
G3
G4
+
-
PWM2
-
Gain = 6
+
CS3
CS3N
+
+
-
PMW3
-
Gain = 6
MID
MID
+
CS4
CS4N
+
-
+
-
PWM4
HI-Z
Gain = 6
VDD
SHED
FAULT
4OFF
Oscillator
OVP
ROSC
ILIM
+
-
ILIMIT_VDD
DRVON
V
REGULATOR
DD
ENABLE
VCCA
Fault Logic
3-Phase
+
-
Detection
and
5V UVLO
4.25V/4.05V
VDD_SRL
Monitor Circuits
VDD_DAC
VS+
VS-
12VMON
+
-
12V UVLO
NCP5393
8.5V/7.5V
Figure 2. NCP5393 Block Diagram
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NCP5393
Figure 3. NCP5393 Configured for 3 + 1 Phases, with Optional Droop
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NCP5393
NCP5393 PIN DESCRIPTIONS
Pin No.
Symbol
Description
1
VCCA
5 V supply pin for the NCP5393. The V bypassing capacitance must be connected between this
CC
pin and GND (preferably returned to the package flag).
2
3
4
5
GND
COMP
FB
Small-signal power supply return. This pin should be tied directly to the package flag (exposed pad).
Output of the voltage error amplifier for the V regulator.
DD
Voltage error amplifier inverting input for the V regulator.
DD
DROOP
Voltage output signal proportional to total current drawn from the V regulator. Used when load line
DD
operation (“droop”) is desired.
6
7
8
VS+
VS-
Non-inverting input to the differential remote sense amplifier for the V regulator.
DD
Inverting input to the differential remote sense amplifier for the V regulator.
DD
OFFSET
Input for offset voltage to be added to the V DAC's output voltage. Ground this pin for zero V
DD
DD
offset.
9
DIFFOUT
VFIX
Output of the differential remote sense amplifier for the V regulator.
DD
10
When pulled low, this pin causes the levels on the SVC (VID3) and SVD (VID2) pins to be decoded
as a two-bit DAC code, which controls the V and VDDNB outputs.
DD
11
12
12VMON
PSI_L
UVLO monitor input for the 12 V power rail.
Power Saving Control. Low = single phase operation, High = normal operation. This pin is not used in
SVI mode.
13
14
15
16
17
18
19
20
21
CS1
CS1N
CS2
Non-inverting input to current sense amplifier #1 for the V regulator. See Table: “Pin Connections
DD
vs. Phase Count”
Inverting input to current sense amplifier #1 for the V regulator. See Table: “Pin Connections vs.
DD
Phase Count”
Non-inverting input to current sense amplifier #2 for the V regulator. See Table: “Pin Connections
DD
vs. Phase Count”
CS2N
CS3
Inverting input to current sense amplifier #2 for the V regulator. See Table: “Pin Connections vs.
DD
Phase Count”
Non-inverting input to current sense amplifier #3 for the V regulator. See Table: “Pin Connections
DD
vs. Phase Count”
CS3N
CS4
Inverting input to current sense amplifier #3 for the V regulator. See Table: “Pin Connections vs.
DD
Phase Count”
Non-inverting input to current sense amplifier #4 for the V regulator. See Table: “Pin Connections
DD
vs. Phase Count”
CS4N
ILIM
Inverting input to current sense amplifier #4 for the V regulator. See Table: “Pin Connections vs.
DD
Phase Count”
Overcurrent shutdown threshold for V and VDDNB. A resistor divider from ROSC to GND is typic‐
DD
ally used to develop an appropriate voltage on ILIM.
22
23
24
25
26
27
VCCB
NB_CS
NB_CSN
VID4
5 V supply pin. Tie this pin to VCCA (Pin 1).
Non-inverting input to the current sense amplifier for the VDDNB regulator
Inverting input to the current sense amplifier for the VDDNB regulator
Parallel Voltage ID DAC Input 4. Not used in SVI mode.
Parallel Voltage ID DAC Input 5. Not used in SVI mode.
VID5
ROSC
A resistance from this pin to ground programs the V and VDDNB oscillator frequencies. This pin
DD
supplies a trimmed output voltage of 2 V.
28
29
NB_DIFFOUT
NB_OFFSET
Output of the differential remote sense amplifier for the VDDNB regulator.
Input for offset voltage to be added to the VDDNB DAC's output voltage. Ground this pin for zero
VDDNB offset.
30
31
NB_VS-
NB_VS+
Inverting input to the differential remote sense amplifier for the VDDNB regulator.
Non-inverting input to the differential remote sense amplifier for the VDDNB regulator.
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5
NCP5393
NCP5393 PIN DESCRIPTIONS
Pin No.
Symbol
Description
32
NB_DROOP
Voltage output signal proportional to total current drawn from the VDDNB regulator. Used when load
line operation (“droop”) is desired.
33
34
NB_FB
NB_COMP
VID0
Voltage error amplifier inverting input for the V
regulator.
DDNB
Output of the voltage error amplifier for the V
regulator.
DDNB
35
Parallel Voltage ID DAC Input 0. Not used in SVI mode.
Parallel Voltage ID DAC Input 1. Also used for PVI or SVI mode selection.
System power supplies status input. Used in SVI mode only.
High = Run, Low = Standby/Reset.
36
VID1
37
PWROK
ENABLE
VID3/SVC
VID2/SVD
PWRGOOD
NB_DRVON
DRVON
NB_G
38
39
Parallel Voltage ID DAC Input 1. Also used in SVI mode.
Parallel Voltage ID DAC Input 1. Also used in SVI mode.
Open drain output. High indicates that the active output(s) are within specification.
40
41
42
Bidirectional Gate Drive Enable to the gate driver for the V
regulator.
DDNB
43
Bidirectional Gate Drive Enable to gate drivers for the V regulator.
DD
44
PWM output to the V
gate driver.
DDNB
45
G4
PWM output #4. See Table: “Pin Connections vs. Phase Count”
PWM output #3. See Table: “Pin Connections vs. Phase Count”
PWM output #2. See Table: “Pin Connections vs. Phase Count”
PWM output #1. See Table: “Pin Connections vs. Phase Count”
46
G3
47
G2
48
G1
FLAG
PGND
High-current power supply return via metal pad (flag) underneath package. The package flag should
be tied directly to Pin 2.
PIN CONNECTIONS VS. PHASE COUNT
Number of
Phases
CS4 &
CS4N
CS3 &
CS3N
CS2 &
CS2N
CS1 &
CS1N
G4
G3
G2
G1
4
Phase 4
Out
Phase 3
Out
Phase 2
Out
Phase 1
Out
Phase 4 CS
Input
Phase 3 CS
Input
Phase 2 CS
Input
Phase 1 CS
Input
3
2
Tie to
GND
Phase 3
Out
Phase 2
Out
Phase 1
Out
Tie to GND
Phase 3 CS
Input
Phase 2 CS
Input
Phase 1 CS
Input
Tie to
GND
Phase 2
Out
Tie to
GND
Phase 1
Out
Tie to GND
Phase 2 CS
input
Tie to GND
Phase 1 CS
Input
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NCP5393
ABSOLUTE MAXIMUM RATINGS
ELECTRICAL INFORMATION
Pin Symbol
12VMON
V
V
I
I
SINK
MAX
MIN
SOURCE
13.2 V
7.0 V
5.5 V
5.5 V
5.5 V
5.5 V
5.5 V
3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
-0.3 V
N/A
50 mA
10 mA
10 mA
5 mA
20 mA
10 mA
20 mA
1 mA
1 mA
N/A
VCC
N/A
10 mA
5 mA
20 mA
5 mA
N/A
COMP, NB_COMP
DROOP, NB_DROOP
DIFFOUT, NB_DIFFOUT
DRVON, NB_DRVON
PWRGOOD
VS+, NB_VS+
VS-, NB_VS-
ROSC
1 mA
1 mA
1 mA
N/A
0.3 V
5.5 V
5.5 V
All Other Pins
N/A
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the
Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect
device reliability.
NOTE: All signals are referenced to GND unless noted otherwise.
THERMAL INFORMATION
Rating
Symbol
Value
30.5
Unit
°C/W
°C
Thermal Characteristic, QFN Package (Note 1)
Operating Junction Temperature Range (Note 2)
Operating Ambient Temperature Range
Maximum Storage Temperature Range
Moisture Sensitivity Level, QFN Package
R
q
JA
T
0 to 125
0 to 70
-55 to +150
1
J
T
A
°C
T
°C
STG
MSL
* The maximum package power dissipation must be observed.
1. JESD 51-5 (1S2P Direct-Attach Method) with 0 LFM.
2. JESD 51-7 (1S2P Direct-Attach Method) with 0 LFM.
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NCP5393
ELECTRICAL CHARACTERISTICS (Unless otherwise stated: 0°CvT v70°C; 4.75 VvV v5.25 V; All DAC Codes; C
= 0.1 mF)
A
CC
VCC
Parameter
Test Conditions
Min
Typ
Max
Unit
ERROR AMPLIFIERS (V & V
DD
)
DDNB
Input Bias Current
-200
-1.0
-
-
200
1.0
-
nA
mV
Input Offset Voltage (Note 3)
Open Loop DC Gain
V+ = V- = 1.3V
C = 60 pF to GND, R = 10 kW to GND
-
80
15
70
dB
L
L
Open Loop Unity Gain Bandwidth
Open Loop Phase Margin
Slew Rate
C = 60 pF to GND, R = 10 kW to GND
L L
-
-
MHz
deg
V/ms
C = 60 pF to GND, R = 10 kW to GND
L L
-
-
DV = 100 mV, AV = -10 V/V,
< 2.5 V,
IN
1.5 V < V
-
5
-
COMP
C = 60 pF, DC Loading = $125 mA
L
Maximum Output Voltage
Minimum Output Voltage
10 mV of Overdrive, I
10 mV of Overdrive, I
= 2.0 mA
3.5
-
-
-
2
2
-
1.0
-
V
V
SOURCE
= 2.0 mA
SINK
Output Source Current (Note 3)
Output Sink Current (Note 3)
10 mV of Overdrive, V
= 3.5 V
-
mA
mA
OUT
OUT
10 mV of Overdrive, V
= 1.0 V
-
-
DIFFERENTIAL SUMMING AMPLIFIERS (V & V
DD
)
DDNB
VS- Input Bias Current
VS+ Input Resistance
VS- Voltage at 0 V
DRVON = Low
DRVON = High
DRVON = Low
DRVON = High
33
1.0
7
mA
kW
VS+ Input Bias Voltage
0.37
0.05
-
V
VS+ Input Voltage Range (Note 3)
VS- Input Voltage Range (Note 3)
-3dB Bandwidth (Note 3)
-0.3
-0.3
3.0
0.3
V
V
-
C = 80 pF to GND, R = 10 kW to GND
L L
15
1.0
MHz
V/V
DC gain, VS+ to DIFFOUT
VS+ to VS- = 0.5 V to 2.35 V
0.982
1.022
DAC Accuracy (Measured at VS+)
Closed Loop Measurement, Error Amplifier Inside the
Loop.
1.0125 V v VDAC v 1.5500 V
0.8000 V v VDAC v 1.0000 V
12.5 mV v VDAC v 0.8000 V
-0.5
-5
-8
-
-
-
0.5
5
8
%
mV
mV
Slew Rate
DV = 100 mV, DV
IN
= 1.3 V-1.2 V
10
V/ms
V
OUT
Maximum Output Voltage
Minimum Output Voltage
Output source current (Note 3)
Output sink current (Note 3)
I
I
= 2 mA
= 2 mA
2.0
SOURCE
0.5
6.3
V
SINK
V
= 3 V
2.0
2.0
mA
mA
OUT
OUT
V
= 0.5 V
DROOP AMPLIFIERS (V & V
DD
)
DDNB
Gain from Current Sense Input to
Droop Amplifier Output
0 mV < (CSx - CSxN) < 60 mV
CSx = CSxN = 1.3 V
5.7
6.0
V/V
Droop Amplifier DC Output Voltage
Slew Rate
1.3
5.0
-
V
V/ms
V
C = 20 pF to GND, R = 1 kW to GND
L L
-
3.0
-
-
-
Maximum Output Voltage
Minimum Output Voltage
Output Source Current (Note 3)
Output Sink Current (Note 3)
I = 4.0 mA
SOURCE
I
= 1.0 mA
-
1.0
-
V
SINK
V
OUT
V
OUT
= 3.0 V
-
4.0
1.0
mA
mA
= 1.0 V
-
3. Guaranteed by design. Not production tested.
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NCP5393
ELECTRICAL CHARACTERISTICS (Unless otherwise stated: 0°CvT v70°C; 4.75 VvV v5.25 V; All DAC Codes; C
= 0.1 mF)
A
CC
VCC
Parameter
CURRENT SENSE AMPLIFIERS (V & V
Test Conditions
Min
Typ
Max
Unit
)
DDNB
DD
Input Bias Current
CSx = CSxN = 1.4 V
-50
-0.3
-120
-
-
-
50
2.6
120
nA
V
Common Mode Input Voltage Range
Differential Mode Input Voltage
Range (Note 3)
mV
Input Offset Voltage (Note 3)
CSx = CSxN = 1.00 V
-1.0
5.0
-
1.0
7.0
mV
V/V
Gain from Current Sense Input to
PWM Comparator
0 mV < (CSx - CSxN) < 60 mV
6.0
INTERNAL OFFSET VOLTAGE
Voltage at Error Amplifier Non-In‐
verting Inputs
-
1.3
-
V
DRVON & NB_DRVON
Output Voltage (High)
Output Voltage (Low)
Delay Time
Sourcing 500 mA
Sinking 500 mA
Propagation Delays
Sourcing 500 mA
Sinking 500 mA
3.0
-
-
-
0.7
-
V
V
-
-
10
ns
kW
W
Active Internal Pull-up Resistance
Active Internal Pull-down Resistance
Rise Time
-
2.0
150
130
15
-
-
-
C (PCB) = 20 pF, DV
L
= 10% to 90%
= 10% to 90%
-
-
ns
ns
OUT
Fall Time
C (PCB) = 20 pF, DV
L
-
-
OUT
V
DD
PWM OSCILLATOR
Switching Frequency Range
100
-
900
kHz
kHz
Switching Frequency Accuracy
2- or 4-phase
ROSC = 49.9 kW
ROSC = 24.9 kW
ROSC = 10 kW
196
380
803
-
-
-
226
420
981
Switching Frequency Accuracy
3-phase
ROSC = 49.9 kW
ROSC = 24.9 kW
ROSC = 10 kW
196
380
803
-
-
-
226
420
981
kHz
V
ROSC Output Voltage
10 mA ≤ IROSC ≤ 200 mA
1.94
2.0
2.06
V
DDNB
PWM OSCILLATOR
Switching Frequency
-
1.25
-
x f
VDD
PWM COMPARATORS (V & V
DD
)
DDNB
Minimum Pulse Width (Note 3)
Propagation Delay (Note 3)
Magnitude of the PWM Ramp
0% Duty Cycle
F
= 800 kHz
-
-
-
-
30
10
-
-
-
-
ns
ns
V
SW
$20 mV of Overdrive
1.0
0.2
COMP Voltage at which the PWM Outputs Remain
LOW
V
100% Duty Cycle
COMP Voltage at which the PWM Outputs Remain
HIGH
-
1.2
-
V
PWM Phase Angle Error
Between Adjacent Phases
-15
+15
°
PWRGOOD OUTPUT
PWRGOOD Output Voltage (Low)
PWRGOOD Rise Time
I
= 5 mA
-
-
-
0.4
-
V
PGD
External Pullup of 1 kW to 5 V C
= 10% to 90%
= 45 pF, DV
125
ns
TOTAL
OUT
PWRGOOD High-State Leakage
V
= 5.25 V
-
-
1
mA
PWRGOOD
3. Guaranteed by design. Not production tested.
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NCP5393
ELECTRICAL CHARACTERISTICS (Unless otherwise stated: 0°CvT v70°C; 4.75 VvV v5.25 V; All DAC Codes; C
= 0.1 mF)
A
CC
VCC
Parameter
PWRGOOD OUTPUT
Test Conditions
Min
Typ
Max
Unit
PWRGOOD Upper Threshold
PWRGOOD Lower Threshold
V
V
Increasing, DAC = 1.3 V (Wrt DAC)
Decreasing, DAC = 1.3 V
-
-
300
350
-
-
mV
mV
OUT
OUT
PWM OUTPUTS (V & V
DD
)
DDNB
Output Voltage (High)
Output Voltage (Mid)
Output Voltage (Low)
Rise and Fall Times
Tri-State Output Leakage
Sourcing 500 mA
3.0
1.3
-
-
1.5
-
V
V
V
CC
R = 4 kW to GND
L
1.7
0.15
-
Sinking 500 mA
V
C = 50 pF, 0.7 V to 3.0 V or 3.0 V to 0.7 V
L
-
15
-
ns
mA
W
Gx = 2.5 V (x = 1-4 or NB)
-1.5
-
1.5
-
Output Impedance - HIGH or LOW
State
Resistance to V or GND
CC
50
VDD REGULATOR 2/3/4 PHASE DETECTION
Gate Pin Source Current
-
-
-
80
250
20
-
-
-
mA
mV
ms
Gate Pin Threshold Voltage
Phase Detect Timer
SLEW RATE LIMITERS
Soft Start Ramp Time
Slew Rate Limit
DAC = 0 to DAC = BOOT_VID
In Any Mode after Soft-Start Completes
-
-
2
-
-
ms
3.25
mV/ms
VID INPUTS (Note: In SVI Mode, VID[2] = Bidirectional “SVD' Line and VID[3] = “SVC” Clock Input)
VID Input Voltage (High)
VID Input Voltage (Low)
VID Hysteresis
V
V
V
V
0.9
-
-
-
-
0.6
-
V
V
HIGH
LOW
HIGH
- V
or V
- V
HIGH
-
100
15
-
mV
mA
V
LOW
LOW
Input Pulldown Current
SVD Output Voltage (Low)
ENABLE INPUT
= 0.6 V - 1.9 V
-
-
IN
In SVI Mode, I
= 5 mA
0
0.25
SINK
ENABLE Input Voltage (High)
ENABLE Input Voltage (Low)
Enable Hysteresis
V
V
2.0
-
-
-
-
0.8
-
V
V
HIGH
LOW
Low - High or High - Low
Internal Pullup to V
-
200
15
mV
mA
Enable Input Pull-Up Current
VFIXEN INPUT (Active-Low Input)
VFIXEN Input Voltage (High)
VFIXEN Input Voltage (Low)
VFIXEN Hysteresis
-
-
CC
V
V
0.9
-
-
-
-
V
V
HIGH
0.6
LOW
Low - High or High - Low
Internal Pullup to V
100
15
mV
mA
VFIXEN Input Pull-Up Current
-
-
CC
3. Guaranteed by design. Not production tested.
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10
NCP5393
ELECTRICAL CHARACTERISTICS (Unless otherwise stated: 0°CvT v70°C; 4.75 VvV v5.25 V; All DAC Codes; C
= 0.1 mF)
A
CC
VCC
Parameter
Test Conditions
Min
Typ
Max
Unit
PSI_L (Power Saving Control, Active Low) (This pin is used in PVI mode only)
PSI_L Input Voltage (High)
PSI_L Input Voltage (Low)
PSI_L Hysteresis
V
HIGH
V
LOW
V
HIGH
0.9
-
-
-
-
V
V
0.6
- V
or V
- V
HIGH
100
mV
LOW
LOW
CURRENT LIMIT
Current Sense Amp to ILIM Gain
ILIM Pin Input Bias Current
20 mV < (CSx - CSxN) < 60 mV (CS inputs tied)
5.7
-
6.0
-
6.3
0.5
2.0
V/V
mA
V
ILIM Pin Working Voltage Range
(Noteꢀ3)
0.2
-
ILIM Offset Voltage
Offset extrapolated to CSx-CSxN = 0 V, and referred
to the ILIM pin
-
-
30
-
-
mV
Delay
600
1.0
ns
V
VDDNB Current Limit Coefficient
= N x V
/V
, where N = number of VDD
NBILIM ILIM
is the equivalent voltage
phases, and V
NBILIM
threshold for NB Current Limit resulting from V
.
ILIM
OFFSET INPUTS (V & V
DD
)
DDNB
Output Offset Voltage Above VDAC
OUTPUT OVERVOLTAGE PROTECTION (V & V
0
-
800
mV
mV
)
DDNB
DD
Over Voltage Threshold
In normal operation, with no VID changes
V
DAC
+ 250
VCCA UNDERVOLTAGE PROTECTION
VCCA UVLO Start Threshold
VCCA UVLO Stop Threshold
VCCA UVLO Hysteresis
INPUT SUPPLY CURRENT
VCC Operating Current
12VMON
4.0
3.8
4.25
4.05
200
4.5
4.3
V
V
mV
ENABLE held Low, No PWM operation
-
25
35
mA
12VMON (High Threshold)
12VMON (Low Threshold)
12VMON Hysteresis
8
7
8.5
7.5
1.0
9
8
V
V
V
Low - High or High - Low
3. Guaranteed by design. Not production tested.
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NCP5393
TYPICAL CHARACTERISTICS
2.03
2.01
1.99
1.5
1.4
Enable Increasing Voltage
1.3
1.2
1.97
1.95
Enable Decreasing Voltage
1.1
1.0
0
0
0
25
50
75
75
75
0
0
0
25
50
75
75
75
T , JUNCTION TEMPERATURE (°C)
T , JUNCTION TEMPERATURE (°C)
J
J
Figure 1. SS Time vs. Temperature
Figure 2. Enable Threshold Voltage vs.
Temperature
26.1
25.8
25.5
25.2
24.9
24.6
231.1
230.8
230.5
230.2
229.9
229.6
24.3
24.0
229.3
229.0
25
50
25
50
T , JUNCTION TEMPERATURE (°C)
T , JUNCTION TEMPERATURE (°C)
J
J
Figure 3. ICC Current vs. Temperature
Figure 4. 2/3/4 Phase Detection Threshold vs.
Temperature
4.5
4.0
2.009
2.008
2.007
2.006
2.005
V
Increasing Voltage
CCP
V
Decreasing Voltage
CCP
3.5
3.0
2.004
2.003
25
50
25
50
T , JUNCTION TEMPERATURE (°C)
J
T , JUNCTION TEMPERATURE (°C)
J
Figure 5. VCCP Undervoltage Lockout
Threshold Voltage vs. Temperature
Figure 6. ROSC Voltage vs. Temperature
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NCP5393
TYPICAL CHARACTERISTICS
10
370
PWRGOOD Upper Voltage
9.5
360
350
340
330
9.0
8.5
8.0
V
CC
Increasing Voltage
V
CC
Decreasing Voltage
7.5
7.0
320
310
PWRGOOD Lower Voltage
25
0
25
50
75
0
50
75
T , JUNCTION TEMPERATURE (°C)
J
T , JUNCTION TEMPERATURE (°C)
J
Figure 7. 12VMON Undervoltage Lockout
Threshold Voltage vs. Temperature
Figure 8. PWRGOOD Voltage vs. Temperature
Functional Description
General
NCP5393 is an universal CPU Power Supply Controller
compatible with both Parallel (PVI) and Serial (SVI)
protocols for AMD Processors. The device provides
and the Vcore ground reference point to VSN. This
configuration keeps ground potential differences between the
local controller ground and the Vcore ground reference point
from affecting regulation of Vcore between Vcore and Vcore
ground reference points. The RSA also subtracts the DAC
(minus VID offset) voltage, thereby producing an unamplified
output error voltage at the DIFFOUT pin. This output also has
a 1.3 V bias voltage as the floating ground to allow both
positive and negative error voltages.
complete control logic and protections for
a
high-performance step-down DC-DC voltage regulator,
optimized for advanced microprocessor power supply
supporting both PVI and SVI communication. It embeds two
independent controllers for CPU CORE and the integrated
NB, each one with its set of protections. The Controller
performs a single-phase control for the NB Section and a
programmable 2- to-4 phase control for the CORE Section
featuring Dual-Edge multiphase architecture.
Precision Programmable DAC
A precision programmable DAC is provided and system
trimmed. This DAC has 0.5% accuracy over the entire
operating temperature range of the part. The DAC can be
programmed to support both PVI and SVI VID code
specifications.
NCP5393 also supports V_FIX mode for board debug: in
this particular configuration the SVI bus is used as a static
bus configuring 4 operative voltages for both the sections
and ignoring any serial-VID command. It can be used for
the board debug before plugging-in the CPU.
High Performance Voltage Error Amplifier
The NCP5393 incorporates differential voltage sensing,
differential phase current sensing, optional load-line
voltage positioning, and programmable VDD and VDDNB
offsets to provide accurately regulated power parallel- and
serial-VID AMD processors. Dual-edge multiphase
modulation provides the fastest initial response to dynamic
load events.
NCP5393 is able to detect which kind of CPU is connected
in order to configure itself to work as a Single-Plane PVI
controller or Dual-Plane SVI controller. The NCP5393
manages On the Fly VID transitions and maintains the slew
rates as defined when the transitions take place. NCP5393
is available in TQFN48 Package.
The error amplifier is designed to provide high slew rate
and bandwidth. Although not required when operating as the
controller of a voltage regulator, a capacitor from COMP to
VFB is required for stable unity gain test configurations.
Gate Driver Outputs and 2/3/4 Phase Operation
The part can be configured to run in 2-, 3-, or 4-phase
mode. In 2-phase mode, phases 1 and 3 should be used to
drive the external gate drivers, G2 and G4 must be grounded.
In 3-phase mode, gate output G4 must be grounded. In
4-phase mode all 4 gate outputs are used as shown in the
4-phase Applications Schematic. The Current Sense inputs
of unused channels should be connected to GND. Please
refer to table “PIN CONNECTIONS vs. PHASE COUNTS”
for details.
Remote Output Sensing Amplifier (RSA)
A true differential amplifier allows the NCP5393 to measure
Vcore voltage feedback with respect to the Vcore ground
reference point by connecting the Vcore reference point to VSP,
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NCP5393
Differential Current Sense Amplifiers and Summing
Amplifier
oscillator generates up to 4 symmetrical triangle waveforms
with amplitude between 1.3_V and 2.3_V. The triangle
waves have a phase delay between them such that for 2-, 3-
and 4-phase operation the PWM outputs are separated by
180, 120, and 90 angular degrees, respectively.
Four differential amplifiers are provided to sense the
output current of each phase. The inputs of each current
sense amplifier must be connected across the current sensing
element of the phase controlled by the corresponding gate
output (G1, G2, G3, or G4). If a phase is unused, the
differential inputs to that phase's current sense amplifier
must be shorted together and connected to the GND.
The current signals sensed from inductor DCR are fed into
a summing amplifier to have a summed-up output. The
outputs of current sense amplifiers control three functions.
First, the summing current signal of all phases will go
through DROOP amplifier and join the voltage feedback
loop for output voltage positioning. Second, the output
signal from DROOP amplifier also goes to ILIM amplifier
to monitor the output current limit. Finally, the individual
phase current contributes to the current balance of all phases
by offsetting their ramp signals of PWM comparators.
When the NB phase is enabled, in order to ensure that the
VDDNB oscillator does not accidentally lock to the VDD
oscillator, the VDDNB oscillator will free-run at a
frequency which is nominally 1.25 ratio of f
.
VDD
CPU Support
NCP5393 is able to detect the CPU it is going to supply
and configure itself accordingly. At system Start-up, on the
rising-edge of the EN signal, the device monitors the status
of VID1 and switches in PVI mode (VID1 = 1) or SVI mode
(VID1 = 0). When in PVI mode, NCP5393 uses the
information available on the VID[0:5] bus to address the
CORE Section output voltage. NB Section is kept in HiZ
mode. When in SVI mode, NCP5393 discards the
information available on VID0, VID4 and VID5 and uses
VID2 and VID3 for SVC and SVD respectively.
Oscillator and Triangle Wave Generator
The controller embeds a programmable precision
dual-Oscillator: one section is used for the CORE and it is
a multiphase programmable oscillator managing equal
phase-shift among all phases and the other section is used
for the NB section. The oscillator's frequency is
programmed by the resistance connected from the ROSC
pin to ground. The user will usually form this resistance
from two resistors in order to create a voltage divider that
uses the ROSC output voltage as the reference for creating
the current limit setpoint voltage. The oscillator frequency
range is 100_kHz per phase to 1.0_MHz per phase. The
PVI - Parallel Interface
PVI is a 6-bit-wide parallel interface used to address the
CORE Section reference. According to the selected code,
the device sets the CORE Section reference and regulates its
output voltage. NB Section is kept in HiZ; no activity is
performed on this section. furthermore, PWROK
information is ignored as well since the signal is propietary
of the SVI protocol. Start-up sequences before soft start and
after soft start are given in Figure 9. Voltage identifications
for the 6Bit AMD mode is given in Table 1.
Figure 9. Power Up Sequences Before and After Soft Start in PVI Mode
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14
NCP5393
Table 1. SIX-BIT PARALLEL VID CODES in PVI Modes
SVID[5:0]
00_0000
00_0001
00_0010
00_0011
00_0100
00_0101
00_0110
10_0111
00_1000
00_1001
00_1010
00_1011
00_1100
00_1101
00_1110
00_1111
V
(V)
SVID[5:0]
01_0000
01_0001
01_0010
01_0011
01_0100
01_0101
01_0110
01_0111
01_1000
01_1001
01_1010
01_1011
01_1100
10_1101
01_1110
01_1111
V
(V)
SVID[5:0]
10_0000
10_0001
10_0010
10_0011
10_0100
10_0101
10_0110
10_0111
10_1000
10_1001
10_1010
10_1011
10_1100
10_1101
10_1110
10_1111
V
(V)
SVID[5:0]
11_0000
11_0001
11_0010
11_0011
11_0100
11_0101
11_0110
11_0111
11_1000
11_1001
11_1010
11_1011
11_1100
11_1101
11_1110
11_1111
V
(V)
OUT
OUT
OUT
OUT
1.5500
1.5250
1.5000
1.4750
1.4500
1.4250
1.4000
1.3750
1.3500
1.3250
1.3000
1.2750
1.2500
1.2250
1.2000
1.1750
1.1500
1.1250
1.1000
1.0750
1.0500
1.0250
1.0000
0.9750
0.9500
0.9250
0.9000
0.8750
0.8500
0.8250
0.8000
0.7750
0.7625
0.7500
0.7375
0.7250
0.7125
0.7000
0.6875
0.6750
0.6625
0.6500
0.6325
0.6250
0.6125
0.6000
0.5875
0.5750
0.5625
0.5500
0.5375
0.5250
0.5125
0.5000
0.4875
0.4750
0.4625
0.4500
0.4375
0.4250
0.4125
0.4000
0.3875
0.3750
SVI - Serial Interface
SVI is a two wire, Clock and Data, bus that connects a
single master (AMD processor) to one NCP5393. The
master initiates and terminates SVI transactions and drives
the clock, SVC, and the data SVD, during a transaction. The
slave receives the SVI transactions and acts accordingly.
SVI wire protocol is based on fast-mode I2C. The SVI
communications are given in Figure 10.
SVI interface also considers EN and PWROK signals for
start-up. The device returns a PWRGOOD signal if the
output voltages are in regulation. The VID codes for SVI are
given in Table 2.
Figure 10. SVI Communication - Send Byte
The start-up sequences before and after soft start are
given in Figure 11.
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NCP5393
Table 2. SEVEN-BIT SERIAL VID CODES for SVI Mode
SVID[6:0]
000_0000
000_0001
000_0010
000_0011
000_0100
000_0101
000_0110
000_0111
000_1000
000_1001
000_1010
000_1011
000_1100
000_1101
000_1110
000_1111
001_0000
001_0001
001_0010
001_0011
001_0100
001_0101
001_0110
001_0111
001_1000
001_1001
001_1010
001_1011
001_1100
001_1101
001_1110
001_1111
V
(V)
SVID[6:0]
010_0000
010_0001
010_0010
010_0011
010_0100
010_0101
010_0110
010_0111
010_1000
010_1001
010_1010
010_1011
010_1100
010_1101
010_1110
010_1111
011_0000
011_0001
011_0010
011_0011
011_0100
011_0101
011_0110
011_0111
011_1000
011_1001
011_1010
011_1011
011_1100
011_1101
011_1110
011_1111
V
(V)
SVID[6:0]
100_0000
100_0001
100_0010
100_0011
100_0100
100_0101
100_0110
100_0111
100_1000
100_1001
100_1010
100_1011
100_1100
100_1101
100_1110
100_1111
101_0000
101_0001
101_0010
101_0011
101_0100
101_0101
101_0110
101_0111
101_1000
101_1001
101_1010
101_1011
101_1100
110_1101
101_1110
101_1111
V
(V)
SVID[6:0]
110_0000
110_0001
110_0010
110_0011
110_0100
110_0101
110_0110
110_0111
110_1000
110_1001
110_1010
110_1011
110_1100
110_1101
110_1110
110_1111
111_0000
111_0001
111_0010
111_0011
111_0100
111_0101
111_0110
111_0111
111_1000
111_1001
111_1010
111_1011
111_1100
111_1101
111_1110
111_1111
V
(V)
OUT
OUT
OUT
OUT
1.5500
1.5375
1.5250
1.5125
1.5000
1.4875
1.4750
1.4625
1.4500
1.4375
1.4250
1.4125
1.4000
1.3875
1.3750
1.3625
1.3500
1.3375
1.3250
1.3125
1.3000
1.2875
1.2750
1.2625
1.2500
1.2375
1.2250
1.2125
1.2000
1.1875
1.1750
1.1625
1.1500
1.1375
1.1250
1.1125
1.1000
1.0875
1.0750
1.0625
1.0500
1.0375
1.0250
1.0125
1.0000
0.9875
0.9750
0.9625
0.9500
0.9375
0.9250
0.9125
0.9000
0.8875
0.8750
0.8625
0.8500
0.8375
0.8250
0.8125
0.8000
0.7875
0.7750
0.7625
0.7500
0.7375
0.7250
0.7125
0.7000
0.6875
0.6750
0.6625
0.6500
0.6325
0.6250
0.6125
0.6000
0.5875
0.5750
0.5625
0.5500
0.5375
0.5250
0.5125
0.5000
0.4875
0.4750
0.4625
0.4500
0.4375
0.4250
0.4125
0.4000
0.3875
0.3750
0.3625
0.3500
0.3375
0.3250
0.3125
0.3000
0.2875
0.2750
0.2625
0.2500
0.2375
0.2250
0.2125
0.2000
0.1875
0.1750
0.1625
0.1500
0.1375
0.1250
0.1125
0.1000
0.0875
0.0750
0.0625
0.0500
0.0375
0.0250
0.0125
OFF
OFF
OFF
OFF
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NCP5393
Figure 11. Power Up Sequences Before and After Soft Start in SVI Mode
Hardware Jumper Override - V_FIX
VFIX is an active low pin and when it is pulled low, the
controller enters V_FIX mode.The voltage regulator can be
powered when an external SVI bus master is not present.
When in VFIX mode, all of the voltage regulator's output
voltages will be governed by the information shown in
Tableꢁ3, regardless of the state of PWROK. VFIX mode is
for debug and bring-up only. If VFIX mode is necessary for
processor bring-up, VFIXEN, SVC, and SVD should be
connected with jumpers to either ground or VDDIO through
suitable pull-up resistors. SVC and SVD are considered as
static VID and the output voltage will change according to
their status.
• This capture is INDEPENDENT of any other signal.
SVI/PVI is determined by sampling VID[1] during
rising edge of ENABLE (SVI: VID[1]=0, PVI:
VID[1]=1). Once SVI/PVI is determined, the VID
controller is enabled and increments to the Boot VID at
the Soft Start rate. VFIXEN mode is entered once
VFIXEN is asserted.
• If VFIXEN is asserted prior to the VID controller
reaching the Boot VID, the VID controller will move to
the VFIXEN VID. Once the first VID value is reached
(either BOOT VID or VFIXEN VID), the VID will
now increment at the Normal rate. Once the VID
controller is enabled, the VID controller can receive
VFIXEN VIDs, independent of PWROK which is
ignored in VFIXEN mode.
Table 3. SVI VFIX VID CODES (TWO-BIT PARALLEL)
SVC
SVD
V
OUT
(V)
• If VFIXEN is de-asserted, the device PORs. This
0
0
1
1
0
1
0
1
1.4
occurs independent of ENABLE
1.2
1.0
0.8
PWROK De-assertion
Anytime PWROK de-asserts while EN is asserted, the
controller uses the previously stored BOOT VID and
regulates all planes to that level performing an on-the-Fly
transition to that level. PWRGOOD remains asserted in this
process.
Start-up sequences are presented below:
• Boot VID is captured from SVC and SVD pins on
rising edge of ENABLE.
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NCP5393
Protection Features:
voltage, the PWRGOOD goes low, the DRVON signal
remains high, the PWM outputs are set low. The outputs will
remain disabled until the VCC voltage is removed and
reapplied. Every time the OV is triggered it will increment
the OV counter. If the counter reaches a count of 16 then the
OV condition will latch into a permanent OV state. It will
require POR or disable/enable to restart. Prior to latching if
the OV condition goes away then normal operation will
resume. An OV decrement counter is also incorporated. It
consists of a free-running clock which runs at 8x the PWM
frequency. So essentially every 4096 PWM cycles the OV
counter will decrement. For example, for a max PWM
frequency of 1 MHz, the counter decrements roughly every
4ꢁms and for a PWM frequency of 400 kHz, it would be
about every 10 ms. During normal operation, if the output
voltage falls more than 350_mV below the DAC setting, the
PWRGOOD pin will be set low until the output voltage
rises.
Undervoltage Lockout
An undervoltage lockout (UVLO) senses the VCC and
VCCP input. During powerup, the input voltage to the
controller is monitored, and the PWM outputs and the
soft-start circuit are disabled until the input voltage exceeds
the threshold voltage of the UVLO comparator. The UVLO
comparator incorporates hysteresis to avoid chattering,
since VCC is likely to decrease as soon as the converter
initiates soft-start.
Overcurrent Shutdown
A programmable overcurrent function is incorporated
within the IC. A comparator and latch make up this function.
The inverting input of the comparator is connected to the
ILIM pin. The voltage at this pin sets the maximum output
current the converter can produce. The ROSC pin provides
a convenient and accurate reference voltage from which a
resistor divider can create the overcurrent setpoint voltage.
Although not actually disabled, tying the ILIM pin directly
to the ROSC pin sets the limit above useful levels -
effectively disabling overcurrent shutdown. The
comparator noninverting input is the summed current
information from the VDRP minus offset voltage. The
overcurrent latch is set when the current information
exceeds the voltage at the ILIM pin. The outputs are pulled
low, and the soft-start is pulled low. The outputs will remain
disabled until the VCCvoltage is removed and re-applied, or
the ENABLE input is brought low and then high.
Soft-Start
The NCP5393 simply ramps Vcore to boot voltage at a
fixed rate of 2 ms (0.8ꢁmV/uS), and then reads the VID pins
to determine the DAC setting. Then ramps Vcore to the final
DAC setting at the Dynamic VID slew rate of up to
3.25ꢁmV/mS. In SVI mode, SoftStart Time is intended as the
time required by the device to set the output voltages to the
Pre-PWROK Metal VID. In PVI mode, VID[0:5] or V_FIX
VID in V_FIX mode are the set output voltages. Typical soft
start sequence timing in SVI mode is given in Figure 12.
Output Overvoltage and Undervoltage Protection and
Power Good Monitor
An output voltage monitor is incorporated. Duringnormal
operation, if the output voltage is 250 mV over the DAC
Figure 12. Soft-Start Sequence to Vcore = 1.3 V
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NCP5393
Programming the Current Limit and the Oscillator Frequency
The demo board is set for an operating frequency of
approximately 330 kHz. The ROSC pin provides a 2.0 V
reference voltage which is divided down with a resistor
divider and fed into the current limit pin ILIM. Calculate the
total series resistance to set the frequency and then calculate
the individual RLIM1 and RLIM2 values for the divider.
The series resistors RLIM1 and RLIM2 sink current from
the ILIM pin to ground. This current is internally mirrored
into a capacitor to create an oscillator. The period is
proportional to the resistance and frequency is inversely
proportional to the total resistance. The total resistance may
be estimated by Equation 2. This equation is valid for the
individual phase frequency in both three and four phase
mode.
-1.1549
R
^ 24686 Fsw
TOTAL
(eq. 1)
-1.1549
30.5ꢀ·ꢀkW ^ 24686 330
Figure 13. ROSC vs. Frequency
The current limit function is based on the total sensed
current of all phases multiplied by a gain of 6. DCR sensed
inductor current is function of the winding temperature. The
best approach is to set the maximum current limit based on
the expected average maximum temperature of the inductor
windings.
DCR
+ DCR ꢀ·ꢀ
25C
Tmax
(eq. 2)
(1 ) 0.00393ꢀ(T
-25))
max
Calculate the current limit voltage:
DCR
Tmax
2ꢀ·ꢀVinꢀ·ꢀF
ꢀ·ꢀVout
Vin-Vout
L
Vout
L
(eq. 3)
ꢀ ·ꢀǒ
Ǔ
^ 6ꢀ·ꢀǒIMIN_OCP
Ǔ
V
ꢀ·ꢀDCR
Tmax
)
* (N-1)ꢀ·ꢀ
ILIMIT
sw
Solve for the individual resistors:
V
ꢀ·ꢀR
ILIMIT TOTAL
RLIM1 + R
-R
TOTAL LIM2
(eq. 4)
(eq. 5)
(eq. 6)
RLIM2 +
2ꢀ·ꢀV
Final Equation for the Current Limit Threshold
2ꢀ·ꢀVꢀ·ꢀRLIM2
RLIM1)RLIM2
ǒ
Ǔ
Vout
2ꢀ·ꢀVinꢀ·ꢀF
sw
Vin-Vout
L
Vout
L
ꢀ ·ꢀǒ
Ǔ
I
(T
LIMIT inductor
) ^
*
* (N-1)ꢀ·ꢀ
6ꢀ·ꢀ(DCR
ꢀ·ꢀ(1 ) 0.00393(T
25C
-25)))
Inductor
The inductors on the demo board have a DCR at 25°C of
limit of 152 A at 100°C. The total sensed current can be
observed as a scaled voltage at the VDRP pin added to a
positive, no-load offset of approximately 1.3 V.
0.75 mW. Selecting the closest available values of 16.9 kW
for RLIM1 and 13.7 kW for RLIM2 yield a nominal
operating frequency of 330 kHz and an approximate current
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19
NCP5393
OUTPUT OFFSET VOLTAGES
External offset voltages from 0 mv to 800 mV `above the DAC' can be added for the V and V independently.
Offset is set by a resistor divider from V to GND. Output offsets are ratiometric to V . As V changes, the on-chip scaling
DD
DD_NB
CC
CC
CC
factors change by the same amount:
Offset = 0.8 V x V
/V
OFFSET CC
For example: For 0 V offset: pin voltage = GND; For 800 mV offset: pin voltage = V
CC
Minimum Voffset_IN
(as Vin/Vcc)
Typical Voffset_IN
(as Vin/Vcc)
Maximum Voffset_IN
(as Vin/Vcc)
Resulting Output Offset
Units
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
mV
0
0
0.046875
0.078125
0.109375
0.140625
0.171875
0.203125
0.234375
0.265625
0.296875
0.328125
0.359375
0.390625
0.421875
0.453125
0.484375
0.515625
0.546875
0.578125
0.609375
0.640625
0.671875
0.703125
0.734375
0.765625
0.796875
0.828125
0.859375
0.890625
0.921875
0.953125
0.984375
Vcc+0.3V
0
0.046875
0.078125
0.109375
0.140625
0.171875
0.203125
0.234375
0.265625
0.296875
0.328125
0.359375
0.390625
0.421875
0.453125
0.484375
0.515625
0.546875
0.578125
0.609375
0.640625
0.671875
0.703125
0.734375
0.765625
0.796875
0.828125
0.859375
0.890625
0.921875
0.953125
0.984375
0.06250
0.09375
0.12500
0.15625
0.18750
0.21875
0.25000
0.28125
0.31250
0.34375
0.37500
0.40625
0.43750
0.46875
0.50000
0.53125
0.56250
0.59375
0.62500
0.65625
0.68750
0.71875
0.75000
0.78125
0.81250
0.84375
0.87500
0.90625
0.93750
0.96875
1.00000
25
50
75
100
125
150
175
200
225
250
275
300
325
350
375
400
425
450
475
500
525
550
575
600
625
650
675
700
725
750
800
The input to the OFFSET pin for the VDD output is encoded by an internal ADC.
The input to the NB_OFFSET pin for the VDDNB output is encoded by the same ADC.
The reference for this ADC is VCC. The ADC's output is ratiometric to VCC.
Voffset IN represents the voltage applied to the OFFSET or NB_OFFSET pin.
It is intended that these voltages be derived by a resistive divider from Vcc.
The recommended total driving impedance is <10 kilohms.
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20
NCP5393
PACKAGE DIMENSIONS
QFN48 7x7, 0.5P
CASE 485AJ-01
ISSUE O
NOTES:
1. DIMENSIONS AND TOLERANCING PER ASME
Y14.5M, 1994.
D
A B
2. CONTROLLING DIMENSION: MILLIMETERS.
3. DIMENSION b APPLIES TO THE PLATED
TERMINAL AND IS MEASURED ABETWEEN
0.15 AND 0.30 MM FROM TERMINAL TIP.
4. COPLANARITY APPLIES TO THE EXPOSED
PAD AS WELL AS THE TERMINALS.
PIN 1
LOCATION
MILLIMETERS
E
DIM MIN
0.80
A1 0.00
MAX
1.00
0.05
A
2X
L
A3
b
0.20 REF
0.15
C
0.20
0.30
D
D2 5.00
E 7.00 BSC
E2 5.00
7.00 BSC
DETAIL A
OPTIONAL CONSTRUCTION
2X SCALE
5.20
5.20
2X
0.15
C
C
TOP VIEW
e
K
L
0.50 BSC
0.20
0.30
---
0.50
(A3)
0.05
0.08
A
SOLDERING FOOTPRINT*
2X
C
A1
NOTE 4
SEATING
PLANE
5.20
C
SIDE VIEW
D2
DETAIL A
1
K
13
25
12
2X
7.30
48X
0.63
E2
48X
0.50 PITCH
0.30
1
36
DIMENSIONS: MILLIMETERS
48
37
48X
b
e
*For additional information on our Pb-Free strategy and soldering
details, please download the ON Semiconductor Soldering and
Mounting Techniques Reference Manual, SOLDERRM/D.
48X L
0.10 C A B
e/2
NOTE 3
C
0.05
BOTTOM VIEW
The products described herein (NCP5393), may be covered by one or more of the following U.S. patents, #US07057381. There may be other patents
pending.
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer's technical experts. SCILLC does not convey any license under its patent rights
nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should
Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,
and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
ꢁLiterature Distribution Center for ON Semiconductor
ꢁP.O. Box 5163, Denver, Colorado 80217 USA
N. American Technical Support: 800-282-9855 Toll Free
ꢁUSA/Canada
Europe, Middle East and Africa Technical Support:
ON Semiconductor Website: www.onsemi.com
Order Literature: http://www.onsemi.com/orderlit
ꢁPhone: 303-675-2175 or 800-344-3860 Toll Free USA/Canada ꢁPhone: 421 33 790 2910
ꢁFax: 303-675-2176 or 800-344-3867 Toll Free USA/Canada
ꢁEmail: orderlit@onsemi.com
For additional information, please contact your local
Sales Representative
Japan Customer Focus Center
ꢁPhone: 81-3-5773-3850
NCP5393/D
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