NCS7031D1G020R2G [ONSEMI]
80 V common-mode, Current Sense Amplifiers;
| 型号： | NCS7031D1G020R2G |
| 厂家： | 
ONSEMI |
| 描述： | 80 V common-mode, Current Sense Amplifiers |
| 文件： | 总16页 (文件大小：510K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
DATA SHEET
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Current Sense Amplifier,
80ꢀV Common-Mode
Voltage, Unidirectional
8
1
Micro8
CASE 846A−02
SOIC−8 NB
CASE 751−07
Product Preview
MARKING DIAGRAM
NCS7030, NCS7031,
NCV7030, NCV7031
8
1
8
XXXXX
ALYWX
XXXX
AYWG
G
G
The NCS7030 and NCS7031 are high voltage, current sense
amplifiers. They are available with gain options of 14 V/V and
20 V/V, with a maximum 0.3 % gain error over the entire
temperature range. Each part consists of a preamplifier and buffer with
access to output and input via A1 and A2 pins for an intermediate filter
network or modified gain. The current sense amplifiers offer excellent
input common−mode rejection from −6 V to 80 V. They can perform
unidirectional current measurements across a sense resistor in a
variety of applications. Automotive qualified options are available
under NCV prefix. All versions operate over the extended temperature
range from −40°C to 150°C.
1
XXXXX = Specific Device Code
A
L
Y
W
G
= Assembly Location
= Wafer Lot
= Year
= Work Week
= Pb−Free Package
(Note: Microdot may be in either location)
PIN CONNECTIONS
Features
• Bandwidth: 100 kHz
−IN
GND
A1
1
2
3
4
8
+IN
NC
VS
• Input Offset Voltage: 300 mV Max Over Temp
• Offset Drift over Temperature: 3 mV/°C max
• Gain Error: 0.3 % Max Over Temp
• Quiescent Current: 1.5 mA Typ
7
6
NCS7031
G = 20
A2
5
OUT
• Supply Voltage: 3 V to 5.5 V
• Common−Mode Input Voltage Range: −6 V to 80 V Operating,
−14 V to 85 V Survival
• CMRR: 85 dB Min
• PSRR: 75 dB Min
• Low−Pass Filter (1−pole or 2−pole)
• These are Pb−free Devices
−IN
GND
A1
1
2
3
4
8
+IN
VS
7
6
NCS7030
G = 14
NC
A2
5
OUT
ORDERING INFORMATION
Typical Applications
• Telecom Equipment
• Power Supply Designs
• Diesel Injection Control
• Automotive
See detailed ordering and shipping information on page 15 of
this data sheet.
• Motor Control
This document contains information on a product under development. onsemi reserves
the right to change or discontinue this product without notice.
© Semiconductor Components Industries, LLC, 2015
1
Publication Order Number:
June, 2023 − Rev. P7
NCS7030/D
NCS7030, NCS7031, NCV7030, NCV7031
A1 A2
V
S
NCS703x
EMI Filter
100 kW
1.4 MW
G = 2
−IN
−
+
OUT
+IN
+
−
G = 7 or 10
10 kW
1.4 MW
10 kW
GND
Figure 1. Simplified Block Diagram
5 V
NCS703x
high−side
switch
V
OUT
A1
S
5 V
+IN
NCS703x
sense
resistor
load
V
OUT
A1
S
A2
−IN
+IN
load
GND
sense
resistor
A2
−IN
low−side
switch
GND
Low−Side Current Sensing
High−Side Current Sensing
Figure 2. Application Schematic
PIN FUNCTION DESCRIPTION
NCS7031 (G = 20) Pinout
NCS7030 (G = 14) Pinout
Pin Name
−IN
Description
Inverting input – connect to sense resistor
Device ground
1
2
3
4
5
6
7
8
1
2
3
4
5
7
6
8
GND
A1
Pre−amp output connection
Buffer amp input connection
Device output
A2
OUT
V
S
Power supply connection
No connect
NC
+IN
Non−inverting input – connect to sense resistor
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2
NCS7030, NCS7031, NCV7030, NCV7031
ABSOLUTE MAXIMUM RATINGS
Rating
Symbol
Value
Unit
V
Supply Voltage Range (Note 1)
Input Common−Mode Range
Differential Input Voltage
V
S
−0.3 to 7
−14 to 85
V
CM
V
V
ID
V
S
V
Maximum Input Current
I
10
50
mA
mA
mW
°C
°C
V
I
Maximum Output Current
Continuous Total Power Dissipation
Maximum Junction Temperature
Storage Temperature Range
I
O
P
200
D
T
150
J(max)
T
−65 to 150
STG
ESD Capability (Note 2)
Human Body Model, Input pins
Human Body Model, All other pins
Charged Device Model
HBM
HBM
CDM
7000
4000
1000
Latch−Up Current (Note 3)
100
Level 1
260
mA
−
Moisture Sensitivity Level
MSL
Lead Temperature Soldering
T
SLD
°C
Reflow (SMD Styles Only), Pb−Free Versions (Note 4)
Stresses exceeding those listed in the Maximum Ratings table may damage the device. If any of these limits are exceeded, device functionality
should not be assumed, damage may occur and reliability may be affected.
1. Refer to ELECTRICAL CHARACTERISTICS and APPLICATION INFORMATION for Safe Operating Area.
2. This device series incorporates ESD protection and is tested by the following methods:
ESD Human Body Model tested per JS−001−2017 (AEC−Q100−002)
ESD Charged Device Model tested per JS−002−2014 (AEC−Q100−011)
3. Latch−up current maximum rating: 100 mA per JEDEC standard JESD78E (AEC−Q100−004).
4. For information, please refer to our Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
THERMAL CHARACTERISTICS (Note 5)
Symbol
Parameter
Thermal Resistance, Junction−to−Air
Package
Micro8
Value (Note 6)
163
Unit
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
q
JA
SOIC−8
Micro8
128
Y
JT
Thermal Characteristic, Junction−to−Case Top
Thermal Characteristic, Junction−to− Board
24.4
SOIC−8
Micro8
28.5
Y
JB
137.3
103.5
SOIC−8
5. Refer to ELECTRICAL CHARACTERISTICS and APPLICATION INFORMATION for Safe Operating Area.
2
2
6. Values based on copper area of 645 mm (or 1 in ) of 1 oz copper thickness and FR4 PCB substrate.
OPERATING RANGES (Note 7)
Rating
Symbol
Min
3
Max
5.5
Unit
Supply Voltage
V
S
V
V
Common−Mode Input Voltage Range
V
CM
−6
80
Ambient Temperature
T
A
−40
150 (Note 8)
°C
7. Refer to ELECTRICAL CHARACTERISTICS and APPLICATION INFORMATION for Safe Operating Area.
8. Operation up to T = 150°C is permitted, provided the total power dissipation is limited to prevent the junction temperature from exceeding
A
the 150°C absolute maximum limit.
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3
NCS7030, NCS7031, NCV7030, NCV7031
ELECTRICAL CHARACTERISTICS (At V = 5 V, T = +25°C, V = 12 V, R ≥ 10 kW, unless otherwise noted. Boldface limits
S
A
CM
L
apply over the specified temperature range, guaranteed by characterization and/or design.)
Symbol
GAIN
Parameter
Conditions
Temp (5C)
Min
Typ
Max
Unit
G
Total Gain, Preamplifier and
Buffer
G = 14 V//V
G = 20 V/V
25
−
−
14
20
−
−
V/V
%
G
Gain Error
−40 to 125
−40 to 150
−40 to 125
−
−
−
−
−
−
+0.3
+0.5
+20
e
DG/DT
Gain Drift
ppm / °C
mV
VOLTAGE OFFSET (Note 9)
Input Offset Voltage
V
OS
25
−
−
100
+300
+300
+400
+3
−40 to 125
−40 to 150
−40 to 125
−
DV /DT Input Offset Voltage Drift over
−
−
mV / °C
OS
Temperature
INPUT
V
CM
Common−Mode Input Voltage
Range
−40 to 150
−6
−
80
V
CMRR
Common−Mode Rejection
Ratio (Note 9)
V
= −6 to 80 V
−40 to 150
−40 to 150
85
105
−
dB
CM
f = 10 kHz
= 12 V, 1 V
G = 14
G = 20
65
70
75
80
−
−
V
CM
PP
PREAMPLIFIER
G
Gain
G = 14 V//V
G = 20 V/V
25
−
−
7
10
−
−
V/V
PRE
G
Gain Error
−40 to 125
−40 to 150
−40 to 150
25
−
−
+0.3
−
%
V
e
V
OH
Output Voltage Swing to V
V − 0.05 V − 0.002
S
S
S
V
OL
Output Voltage Swing to GND
Output Resistance
−
98
94
−
1.5
100
−
25
mV
kW
R
102
106
500
PRE
−40 to 150
−40 to 125
I
IB
Input Bias Current
200
mA
OUTPUT BUFFER
G
Gain
25
−
−
2
−
+0.3
−
V/V
%
OUT
G
Gain Error
−40 to 125
−40 to 150
−40 to 150
−40 to 125
−
e
V
Output Voltage Swing to V
V
S
− 0.05 V − 0.003
V
OH
S
S
V
Output Voltage Swing to GND
Input Bias Current
−
−
0.5
5
25
mV
nA
OL
I
+20
IB
DYNAMIC PERFORMANCE
BW
SR
Bandwidth
Slew Rate
25
25
−
−
100
1
−
−
kHz
V / ms
NOISE (Note 9)
V
Voltage Noise, Peak−to−Peak
f = 0.1 Hz to 10 Hz
f = 1 kHz
25
25
−
−
2
−
−
mV
p−p
n
e
N
Voltage Noise Density
120
nV / √Hz
POWER SUPPLY
V
Operating Voltage Range
Quiescent Current
−40 to 150
25
3
−
−
1.5
−
5.5
2.4
2.7
2.8
−
V
S
I
mA
DD
−40 to 125
−40 to 150
−40 to 150
−
−
−
PSRR
Power Supply Rejection Ratio
75
90
dB
Product parametric performance is indicated in the Electrical Characteristics for the listed test conditions, unless otherwise noted. Product
performance may not be indicated by the Electrical Characteristics if operated under different conditions.
9. Referred to input
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4
NCS7030, NCS7031, NCV7030, NCV7031
TYPICAL CHARACTERISTICS
At T = 25°C, V = 5 V, V
= 12 V, R = 10 kW, unless otherwise noted
A
S
CM
L
45
30
25
120 Units
120 Units
40
35
30
25
20
15
10
5
20
15
10
5
0
0
−75 −50 −25
0
25 50 75 100 125 150 175
−0.6 −0.4 −0.2
0
0.2 0.4 0.6 0.8
1
1.2
INPUT OFFSET VOLTAGE (mV)
INPUT OFFSET VOLTAGE DRIFT (mV/°C)
Figure 3. Input Offset Voltage Distribution
Figure 4. Input Offset Voltage Drift Distribution
150
100
50
1200
1000
800
600
5 Units
6 Units
400
200
0
0
−200
−400
−600
−50
−100
−50
−25
0
25
50
75
100
125
150
−10
0
10
20
30
40
50
60
70
80
TEMPERATURE (°C)
COMMON MODE VOLTAGE (V)
Figure 5. Input Offset Voltage vs. Temperature
Figure 6. Input Offset Voltage vs. Common
Mode Input Voltage
130
110
90
V
CM
= 1 Vpp
70
50
30
G = 14
G = 20
10
−10
−30
10
100
1k
10k
100k
1M
10M
FREQUENCY (Hz)
Figure 7. CMRR vs. Frequency
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NCS7030, NCS7031, NCV7030, NCV7031
TYPICAL CHARACTERISTICS
At T = 25°C, V = 5 V, V
= 12 V, R = 10 kW, unless otherwise noted
A
S
CM
L
100
90
80
70
60
50
40
30
20
2.80
2.72
2.64
2.56
100
90
80
70
60
50
40
30
20
4.2
4.0
3.8
3.6
3.4
3.2
3.0
2.8
2.6
4 typical units
output
4 typical units
output
2.48
2.40
input
2.4
2.2
10
0
10
0
input
TIME (20 ms/div)
TIME (500 ms/div)
Figure 8. Common Mode Step Response with
1 ms Rising Edge
Figure 9. Common Mode Step Response with
10 ms Rising Edge
100
90
80
70
60
50
40
30
20
2.80
100
90
80
70
60
50
40
30
20
2.6
2.4
2.2
4 typical units
2.72
2.64
2.56
input
input
2.0
1.8
1.6
1.4
1.2
1.0
output
output
2.48
2.40
10
0
0.8
0.6
10
0
4 typical units
TIME (500 ms/div)
TIME (10 ms/div)
Figure 10. Common Mode Step Response with
1 ms Falling Edge
Figure 11. Common Mode Step Response with
10 ms Falling Edge
300
I
IB
I
IB
−
+
250
200
150
100
50
0
−50
0
50
TEMPERATURE (°C)
100
150
Figure 12. Preamplifier Input Bias Current vs.
Temperature
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NCS7030, NCS7031, NCV7030, NCV7031
TYPICAL CHARACTERISTICS
At T = 25°C, V = 5 V, V
= 12 V, R = 10 kW, unless otherwise noted
A
S
CM
L
0.1
0.08
0.06
0.04
0.02
0
101.0
100.5
100.0
99.5
99.0
−0.02
−0.04
−0.06
98.5
98.0
−50
0
50
100
150
−50
0
50
100
150
TEMPERATURE (°C)
TEMPERATURE (°C)
Figure 13. Preamplifier Gain Error vs.
Temperature
Figure 14. Preamplifier Output Resistance vs.
Temperature
300
250
200
150
100
50
180
160
140
120
100
80
T
= −40°C
= 25°C
= 125°C
A
T
= −40°C
= 25°C
= 125°C
A
T
A
T
A
T
A
T
A
60
40
20
0
0
0
10
20
30
40
50
60
0
5
10
15
20
OUTPUT CURRENT (mA)
OUTPUT CURRENT (mA)
Figure 15. Buffer Output Voltage Swing to
GND vs. Output Current
Figure 16. Buffer Output Voltage Swing from
Supply Rail vs. Output Current
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NCS7030, NCS7031, NCV7030, NCV7031
TYPICAL CHARACTERISTICS
At T = 25°C, V = 5 V, V
= 12 V, R = 10 kW, unless otherwise noted
A
S
CM
L
1000
100
10
8
7
6
5
4
3
2
1
V
V
A2
= 1 V
= 2 V
A2
1
0.1
0.01
0
−50
0
50
TEMPERATURE (°C)
100
150
1
10
100
1k
10k
100k
1M
FREQUENCY (Hz)
Figure 17. Buffer, Input Bias Current vs.
Temperature
Figure 18. Buffer Output Impedance vs.
Frequency
0.02
0
50
40
30
20
10
−0.02
−0.04
−0.06
−0.08
−0.1
G = 14
G = 20
0
−0.12
−10
10
100
1k
10k
100k
1M
10M
−50
0
50
100
150
TEMPERATURE (°C)
FREQUENCY (Hz)
Figure 19. Total Gain Error vs. Temperature
Figure 20. Gain vs. Frequency
140
120
100
80
PSRR+
PSRR−
60
40
20
0
−20
−40
10
100
1k
10k
100k
1M
FREQUENCY (Hz)
Figure 21. PSRR vs. Frequency
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NCS7030, NCS7031, NCV7030, NCV7031
TYPICAL CHARACTERISTICS
At T = 25°C, V = 5 V, V
= 12 V, R = 10 kW, unless otherwise noted
A
S
CM
L
12.20
12.15
12.10
12.05
12.00
11.95
4.5
4.0
3.5
3.0
2.5
2.0
12.20
12.15
12.10
12.05
12.00
11.95
4.5
4.0
3.5
3.0
2.5
2.0
11.90
1.5
11.90
1.5
Input
Output
Input
Output
11.85
11.80
1.0
0.5
11.85
11.80
1.0
0.5
TIME (5 ms/div)
TIME (5 ms/div)
Figure 22. Transient Response
Figure 23. Transient Response
1k
1.50
1.25
1.00
0.75
0.50
0.25
100
10
0
−0.25
−0.50
−0.75
−1.00
−1.25
−1.50
100
1k
10k
100k
TIME (1 s/div)
FREQUENCY (Hz)
Figure 25. Noise, 0.1 Hz to 10 Hz, Referred to
Input
Figure 24. Voltage Noise Density
2.0
1.8
1.6
1.4
1.2
1.0
−50
0
50
TEMPERATURE (°C)
100
150
Figure 26. Quiescent Current
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NCS7030, NCS7031, NCV7030, NCV7031
APPLICATION INFORMATION
The NCS7030 and NCS7031 are current sense amplifiers
a simple op amp circuit. However, the NCS703x series of
devices provides the full differential input necessary to get
accurate shunt connections, while also providing a built−in
gain network with precision difficult to obtain with external
featuring a wide common mode voltage up to 80 V
independent of the supply voltage. The NCS703x
current−sense amplifiers can be configured for both
low−side and high−side current sensing.
resistors. The NCS703x is shown in
configuration in Figure 27 below.
a low−side
Current Sensing Techniques
Low−side sensing appears to have the advantage of being
straightforward, inexpensive, and can be implemented with
high−side
switch
5 V
NCS703x
load
V
OUT
A 1
S
+ IN
sense
resistor
A 2
− IN
GND
Figure 27. Low−side Current Sensing
While at times the application requires low−side sensing,
only high−side sensing can detect a short from the positive
supply line to ground. Furthermore, high−side sensing
avoids adding resistance to the ground path of the load being
measured. The sections below focus primarily on high−side
current sensing. Figure 28 shows the NCS703x configured
for high−side current sensing.
5 V
NCS703x
V
OUT
A 1
S
+ IN
sense
resistor
A 2
− IN
load
GND
low−side
switch
Figure 28. High−side Current Sensing
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NCS7030, NCS7031, NCV7030, NCV7031
Unidirectional Operation
A1 and A2 Pins
In unidirectional current sensing, the measured load
current always flows in the same direction. Common
applications for unidirectional operation include power
supplies and load current monitoring.
NCS703x is internally referenced to ground; therefore, it
can only measure current flowing in one direction. The +IN
pin of the NCS703x should be connected to the positive side
of the sense resistor, while the −IN pin should be connected
to the negative side of the sense resistor.
A1 is the preamplifier output and the A2 is the buffer
input. These pins can be used to make adjustments to the
gain or to create a low−pass filter. The output of the
preamplifier integrates a precision resistor of 100 kW 2%,
which can be utilized for either of these purposes.
The high impedances at the A1 and A2 pins make this
connection particularly sensitive, and a careful layout is
necessary if the high frequency response is required. Trace
lengths should be kept at a minimum and test points should
be avoided when possible at these pins. Even a small
capacitance of 20 pF from the PCB can lower the −3dB
signal bandwidth to 80 kHz. This filtering effect is useful for
decreasing noise, and is further discussed in the upcoming
”Filtering with A1 and A2” section.
When no current is flowing though the R , the
SHUNT
NCS703x output is expected to be within 50 mV of ground.
When current is flowing through R the output will
SHUNT,
swing positive, up to within 100 mV of the applied supply
voltage, V .
S
ǒ Ǔ
out + V)in * V*in G
V
Lowering the Gain with A1 and A2
The gain can be lowered by using the A1 and A2 pins.
Connecting A1 to A2 and adding a resistor from this net to
GND creates a resistor divider network in combination with
the internal 100 kW resistor, as shown by Figure 29. For
example, adding an external 100 kW resistor, reduces the
voltage going into A2 by half, reducing the overall gain by
half.
Power Supplies
The NCS703x can be connected to the same power supply
that it is monitoring current from, or it can be connected to
a separate power supply. If it is necessary to detect short
circuit current on the load power supply, which may cause
the load power supply to sag to near zero volts, a separate
power supply must be used on the NCS703x. When using
multiple supplies, there are no restrictions on power supply
sequencing.
Preamplifier
Gain = 7 or 10 V/V
Buffer
Gain = 2 V/V
+IN
+
+
OUT
−
−IN
−
10 kW
100 kW
10 kW
A1
A2
REXT
Figure 29. Lowering the Gain Using an External Resistor
The adjusted overall decreased gain, GADJ−, becomes a
factor of the total nominal gain, G, and the external resistor,
REXT.
This equation can be rearranged to calculate the external
resistor value for the desired gain value.
100 kW GADJ*
REXT
+
G * GADJ*
G REXT
GADJ*
+
R
EXT ) 100 kW
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NCS7030, NCS7031, NCV7030, NCV7031
Increasing the Gain with A1 and A2
The gain can be increased by adding an external resistor
in positive feedback as shown in Figure 30.
G REXT
EXT * 100 kW
GADJ)
+
R
Preamplifier
Gain = 7 or 10 V/V
Buffer
Gain = 2 V/V
+IN
+
+
OUT
−
−IN
−
10 kW
100 kW
10 kW
A1
A2
REXT
Figure 30. Increasing the Gain Using an External Resistor in Positive Feedback
Filtering with A1 and A2
the net to GND as shown in Figure 31. This creates a simple
RC filter with the internal 100 kW resistor. This single pole
filter has a 20 dB/decade attenuation.
In some applications, the current being measured may be
inherently noisy. A low−pass filter can be created by
connecting A1 and A2 together and adding a capacitor from
Preamplifier
Gain = 7 or 10 V/V
Buffer
Gain = 2 V/V
+IN
+
+
OUT
−
−IN
−
10 kW
100 kW
10 kW
A1
CFILT
Figure 31. Implementing a Single−pole, Low−pass RC Filter
1
fFILT
+
2p(100 kW)CFILT
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12
NCS7030, NCS7031, NCV7030, NCV7031
A two−pole filter with 40 dB/decade attenuation can be
created with a Sallen−Key topology as shown in Figure 32.
Preamplifier
Gain = 7 or 10 V/V
Buffer
Gain = 2 V/V
+IN
+
+
OUT
−
−IN
−
10 kW
100 kW
10 kW
A1
A2
REXT
C1
C2
Figure 32. Implementing a Two−pole, Low−pass Filter using the Sallen−Key Topology
Input Filtering
Some applications may require filtering at the input of the
current sense amplifier. Figure 33 shows the recommended
schematic for input filtering.
Vs
NCS703x
R
FILT
10 W
V
S
OUT
A1
+IN
R
SHUNT
C
FILT
200 mW
A2
−IN
0.25 mF
1 nH
GND
R
FILT
10 W
Figure 33. Input Filtering Compensates for Shunt Inductance on Shunts Less than 1 mW,
as Well as High Frequency Noise in any Application
Input filtering is complicated by the fact that the added
resistance of the filter resistors and the associated resistance
mismatch between them can adversely affect gain, CMRR,
and VOS. The effect on VOS is partly due to input bias currents
as well. As a result, the value of the input resistors should be
limited to 10 W or less.
As the shunt resistors decrease in value, shunt inductance
can significantly affect frequency response. At values below
1 mW, the shunt inductance causes a zero in the transfer
function that often results in corner frequencies in the low
100’s of kHz. This inductance increases the amplitude of
high frequency spike transient events on the current sensing
line that can overload the front end of any shunt current
sensing IC. This problem must be solved by filtering at the
input of the amplifier. Note that all current sensing IC’s are
vulnerable to this problem, regardless of manufacturer
claims. Filtering is required at the input of the device to
resolve this problem, even if the spike frequencies are above
the rated bandwidth of the device.
www.onsemi.com
13
NCS7030, NCS7031, NCV7030, NCV7031
Advantages When Used For Low−Side Current
Sensing
The NCS703x series offers many advantages for low−side
current sensing. The true differential input is ideal for
connection to either Kelvin Sensing shunts or conventional
shunts. Additionally, the true differential input rejects the
common−mode noise often present even in low−side current
sensing. Providing all of this in a tiny package makes it very
competitive when compared to discrete op amp solutions.
Ideally, select the capacitor to exactly match the time
constant of the shunt resistor and its inductance;
alternatively, select the capacitor to provide a pole below
that point. Make the input filter time constant equal to or
larger than the shunt and its inductance time constant:
LSHUNT
RSHUNT
v 2RFILTCFILT
To determine the value of CFILT based on using 10 W
resistors for each RFILT, the equation simplifies to:
Selecting the Shunt Resistor
LSHUNT
20RSHUNT
CFILT
w
The desired accuracy of the current measurement
determines the precision, shunt size, and the resistor value.
The larger the resistor value, the more accurate the
measurement possible, but a large resistor value also results
in greater power loss.
If the main purpose is to filter high frequency noise, the
capacitor should be increased to a value that provides the
desired filtering. As an example, a filtering frequency of
10 kHz would require an 0.8 mF capacitor.
For the most accurate measurements, use four terminal
current sense resistors. It provides two terminals for the
current path in the application circuit, and a second pair for
the voltage detection path of the sense amplifier. This
technique is also known as Kelvin Sensing. This insures that
the voltage measured by the sense amplifier is the actual
voltage across the resistor and does not include the small
resistance of a combined connection. When using
non−Kelvin shunts, closely follow manufacturers
recommendations on how to lay out the sensing traces.
1
fFILT
+
2p(2RFILT)CFILT
Common Mode Voltage Step Response
Large common mode voltage steps with fast slew rates can
invoke transient voltage spikes on the output. Certain
applications that operate with large common mode input
voltage steps, including solenoid applications, require a
thorough evaluation of the output response during such
events.
There are a few methods to address this. One way to
decrease the transient voltage spike is by decreasing the slew
rate of the common mode voltage step. The measurement
can also be filtered or averaged; this can be done by adding
a low−pass filter using the A1 and A2 pins as described in
the previous ”Filtering with A1 and A2” section. Finally,
there is the option of adding a time delay in the measurement
after a common mode voltage step occurs.
Shutting Down the NCS703x
While the NCS703x does not provide a shutdown pin, a
simple MOSFET, power switch, or logic gate can be used to
switch off the power to the NCS703x and eliminate the
quiescent current. Note that the shunt input pins will always
have a current flow via the input and feedback resistors. The
input pins support the rated common mode voltage even
when the NCS703x does not have power applied.
The ac response to disturbances in the CMRR voltage is
quantified to a certain degree in the CMRR vs. Frequency
graph.
www.onsemi.com
14
NCS7030, NCS7031, NCV7030, NCV7031
ORDERING INFORMATION
Gain
Device
Marking
Package
Shipping†
14
NCS7030D2G014RG
(In Development*)
7030
SOIC−8
2500 / Tape & Reel
NCS7030DM2G014R2G
(In Development*)
7030
7031
7031
Micro8
SOIC−8
Micro8
4000 / Tape & Reel
2500 / Tape & Reel
4000 / Tape & Reel
20
NCS7031D1G020R2G
(In Development*)
NCS7031DM1G020R2G
(In Development*)
AUTOMOTIVE QUALIFIED
Gain
Device
Marking
Package
Shipping†
14
NCV7030D2G014RG
(In Development*)
7030
SOIC−8
2500 / Tape & Reel
NCV7030DM2G014R2G
(In Development*)
7030
7031
7031
Micro8
SOIC−8
Micro8
4000 / Tape & Reel
2500 / Tape & Reel
4000 / Tape & Reel
20
NCV7031D1G020R2G
(In Development*)
NCV7031DM1G020R2G
(In Development*)
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specification Brochure, BRD8011/D.
*Contact local sales office for more information.
www.onsemi.com
15
NCS7030, NCS7031, NCV7030, NCV7031
PACKAGE DIMENSIONS
Micro8
CASE 846A−02
ISSUE K
onsemi,
, and other names, marks, and brands are registered and/or common law trademarks of Semiconductor Components Industries, LLC dba “onsemi” or its affiliates
and/or subsidiaries in the United States and/or other countries. onsemi owns the rights to a number of patents, trademarks, copyrights, trade secrets, and other intellectual property.
A listing of onsemi’s product/patent coverage may be accessed at www.onsemi.com/site/pdf/Patent−Marking.pdf. onsemi reserves the right to make changes at any time to any
products or information herein, without notice. The information herein is provided “as−is” and onsemi makes no warranty, representation or guarantee regarding the accuracy of the
information, product features, availability, functionality, or suitability of its products for any particular purpose, nor does onsemi assume any liability arising out of the application or use
of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. Buyer is responsible for its products
and applications using onsemi products, including compliance with all laws, regulations and safety requirements or standards, regardless of any support or applications information
provided by onsemi. “Typical” parameters which may be provided in onsemi data sheets and/or specifications can and do vary in different applications and actual performance may
vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. onsemi does not convey any license
under any of its intellectual property rights nor the rights of others. onsemi products are not designed, intended, or authorized for use as a critical component in life support systems
or any FDA Class 3 medical devices or medical devices with a same or similar classification in a foreign jurisdiction or any devices intended for implantation in the human body. Should
Buyer purchase or use onsemi products for any such unintended or unauthorized application, Buyer shall indemnify and hold onsemi and its officers, employees, subsidiaries, affiliates,
and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that onsemi was negligent regarding the design or manufacture of the part. onsemi is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
Email Requests to: orderlit@onsemi.com
TECHNICAL SUPPORT
North American Technical Support:
Voice Mail: 1 800−282−9855 Toll Free USA/Canada
Phone: 011 421 33 790 2910
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Phone: 00421 33 790 2910
For additional information, please contact your local Sales Representative
onsemi Website: www.onsemi.com
◊
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