LYT3326D-TL [POWERINT]
IC LED DVR DIM 12.6W 1-ST 16SOIC;型号: | LYT3326D-TL |
厂家: | Power Integrations |
描述: | IC LED DVR DIM 12.6W 1-ST 16SOIC 驱动 接口集成电路 |
文件: | 总18页 (文件大小:1833K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LYT3314-3328
LYTSwitch-3 Family
Single-Stage LED Driver IC with Combined PFC and
Constant Current Output for Outstanding TRIAC Dimming
in Isolated and Non-Isolated Topologies
Product Highlights
Combined Single-Stage PFC + Accurate CC Output
• Less than ±3% CC regulation over line and load
L
• Power Factor >0.9
• Ensures monotonic VA reduction with TRIAC phase angle
• Low THD, 15% typical for dimmable bulbs, as low as 7% in
T
LYTSwitch-3
BL
L
D
S
N
optimized designs
CONTROL
BS
DS
Advanced Integrated TRIAC Dimmer Detection
• Detects leading-edge and trailing-edge TRIAC dimmers
• High-efficiency mode when no dimmer is present
• Selectable dimming profile increases design flexibility
• Fast turn-on (<500 ms)
FB
BP
OC
T
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• Low pop-on and dead-travel
• Active bleeder drive for widest dimmer compatibility
Figure 1. Simplified Schematic (Buck).
Design Flexibility
• Supports buck, buck-boost, tapped buck-boost, boost, isolated and
non-isolated flyback
• Up to 20 W output
Output Power Table
Product2
Output Power1
Highest Reliability
• No electrolytic bulk capacitors or optoisolators for increased lifetime
• Comprehensive protection features
• Input and output overvoltage
• Output short-circuit and open-loop protection
• Advanced thermal control
• Thermal foldback ensures that light continues to be delivered at
elevated temperatures
• End-stop shutdown provides protection during fault conditions
85-132 VAC or 185-265 VAC
LYT33x4D3
LYT33x5D
LYT33x6D
LYT33x8D
5.7 W
8.8 W
12.6 W
20.4 W
Table 1. Output Power Table (Buck Topology).
Description
Notes:
1. Maximum practical continuous power in an open frame design with adequate
heat sinking, measured at 50˚C ambient (see Key Applications Considerations
for more information).
The LYTSwitch™-3 family is ideal for single-stage power factor
corrected constant current LED bulbs and downlighters.
2. Package: D: SO-16B.
Each device incorporates a high-voltage power MOSFET and discon-
tinuous mode, variable frequency variable on-time controller. The
controller also provides cycle-by-cycle current limit, output OVP, line
overvoltage, comprehensive protection features, plus advanced
thermal management circuitry.
3. ”x” digit describes VDSON(MAX) of the integrated switching MOSFET,
650 V = 1, 725 V = 2.
All LYTSwitch-3 ICs have a built-in TRIAC detector that discriminates
between leading-edge and trailing-edge dimmers. This capability
together with load monitoring circuitry regulates bleeder current during
each switching cycle. The controller disables the bleeder circuit
completely if no dimmer is detected, significantly increasing efficiency.
Figure 2. SO-16B (D Package).
The combination of a low-side switching topology, cooling via electroni-
cally quiet SOURCE pins and frequency jitter ensure extremely low EMI.
This reduces the size of the input filter components – greatly reducing
audible noise during dimming.
The part numbers shown in Table 1 describe 4 different power levels and
two MOSFET voltage options to cost-optimize designs while EcoSmartTM
switching technology insures maximum efficiency for each device size
and load condition.
www.power.com
April 2016
This Product is Covered by Patents and/or Pending Patent Applications.
LYT3314-3328
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Figure 3. Block Diagram.
2
Rev. D 04/16
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LYT3314-3328
FEEDBACK (FB) Pin
Pin Functional Description
In normal operation and full conduction the preset threshold on the
FEEDBACK pin is 300 mV. This threshold gets reduced linearly with
conduction angle until a minimum level is reached.
LINE-SENSE (L) Pin
LINE-SENSE pin implements input voltage waveform detection:
conduction angle is detected accurately since SOURCE pin is referenced
to bulk capacitor ground. Input OVP is activated when LINE-SENSE pin
current exceeds the predetermined threshold.
Cycle skipping is triggered when voltage on this pin exceeds 600 mV.
BYPASS (BP) Pin
5.25 V supply rail.
BLEEDER CURRENT SENSE (BS) Pin
BLEEDER CURRENT SENSE pin measures the total input current –
active bleeder current plus switch current. This current is sensed in
order to keep TRIAC current above its holding level. This is achieved by
modulating the bleeder dissipation.
OUTPUT COMPENSATION (OC) Pin
Output OVP for all topologies. Output voltage compensation for indirect
output current sense topologies.
DRAIN (D) Pin
High-voltage internal MOSFET (725 V or 650 V).
RBS (W)
Dim Curve
Load Shut Down (LSD)
SOURCE (S) Pin:
Power and signal ground.
6 k
Max. Dim Curve
Min. Dim Curve
Min. Dim Curve
No
No
12 k
24 k
Yes
Table 2. BS Pin Resistor Programming.
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DRIVER CURRENT SENSE (DS) Pin
DRIVER CURRENT SENSE pin senses the driver current. This current is
used to deduce output current: it is multiplied by the input voltage and
the result is then divided by the output voltage to obtain output current.
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Topology
6 k
Buck, Buck-Boost, Isolated Flyback
24 k
Non-Isolated Flyback
1
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3
4
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Table 3. Topology Selection Resistor.
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BLEEDER CONTROL (BL) Pin
BLEEDER CONTROL pin drives the external bleeder transistor in order to
maintain the driver input current above the holding current of the
dimmer TRIAC.
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Figure 4. Pin Configuration.
3
Rev. D 04/16
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LYT3314-3328
RDꢀ
D1
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Figure 5. Typical Schematic Buck (Low-Line).
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RDꢂ
Figure 6. Typical Schematic Buck-Boost (High-Line).
4
Rev. D 04/16
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LYT3314-3328
Applications Example
DER-524 8 W A19 LED Bulb Driver Dimmable, Tight
Regulation, High Power factor, Low ATHD Design
Example
RTN
L1
R7
1 mH
T1
1
150 Ω
2 W
R32
3 kΩ
2 W
R8
R20
2 MΩ
1%
C10
120 µF
80 V
1 kΩ
1 W
R19
82 kΩ
C4
C5
100 nF
400 V
47 nF
400 V
C3
47 nF
400 V
R18
2 MΩ
1%
2
+V
R9
2 kΩ
2 W
BR1
B10S-G
1000 V
D3
RF1
47 Ω
2 W
STTH1R06A
600 V
L
Q2
PN222A
RV1
275 VAC
LYTSwitch-3
U1
BL
L
D
LYT3325D
R11
24 kΩ
CONTROL
BS
DS
N
D2
R13
FB
BP
OC
S
BAV21W-7-F
6.04 kΩ
T1
8
1%
C2
8.2 nF
50 V
R4
20 Ω
R16
C6
178 kΩ
R15
39.2 kΩ
1%
C8
150 nF
25 V
C11
10 µF
1%
22 µF
10 V
50 V
R1
3.9 Ω
R14
6.2 kΩ
7
C7
22 µF
16 V
PI-7779-021016 HLBB
R12
4.3 Ω
1%
Figure 7. DER-524 8 W, 72 V, 115 mA Non-Isolated Dimmable A19 LED Bulb Driver using LYT3325D.
The circuit shown in Figure 7 is configured as a buck-boost power
supply utilizing the LYT3325D from the LYTSwitch-3 family of ICs.
This type of LED driver configuration is common for dimmable bulb
applications where high dimmer compatibility, accurate regulation,
high efficiency, high power factor and low ATHD are required along
with low component count for high reliability. The output can drive
an LED load from 68 V to 76 V with a constant output current of
115 mA ±3% across an input range of 195 VAC to 264 VAC and can
operate in maximum ambient temperature of 100 ºC with good margin
below the thermal foldback protection point. It has an efficiency of
greater than 86%, very low ATHD% (less than 20%) and high power
factor of greater than 0.9 measured across the input range.
conduction mode inherently eliminates reverse current from the
output diode when the power MOSFET is in the OFF-state reducing
high frequency noise and allowing the use of a simpler, smaller EMI
filter which also improves efficiency.
Input Filter
AC input power is rectified by bridge BR1. A 1000 V voltage rating is
recommended (the maximum clamp voltage for a typical 275 V
varistor is 720 V). The rectified DC is filtered by the input capacitors
C4 and C5. Too much capacitance degrades power factor and ATHD,
so the values of the input capacitors were adjusted to the minimum
values necessary to meet EMI with a suitable margin. Inductor L1,
C4 and C5 form a π (pi) filter, which attenuates conducted differential
and common mode EMI currents. Optional resistor R10 across L1
damps the Q of the filter inductor to improve filtering without
reducing low frequency attenuation. Fuse RF1 in Figure 7 provides
protection against catastrophic failures such as short-circuit at the
input. For cost reduction, this can be replaced by a fusible resistor
(typically a flame proof wire-wound type) which would need to be
rated to withstand the instantaneous dissipation induced when
charging the input capacitance when first connected to the input line.
Circuit Description
The LYTSwitch-3 device (U1 - LYT3325D) combines a high-voltage
power MOSFET, variable frequency and on-time control engine, fast
start-up, selectable dimming curves with load shutdown at deep
dimming and protection functions including line and output overvolt-
age into a single package, greatly reducing component count. The
integrated 725 V power MOSFET provides a large drain voltage
margin in high-line input AC applications thus increasing reliability.
A 625 V power MOSFET option is also offered to reduce cost in
applications where the voltage stress on the power MOSFET is lower.
Configured to operate as a discontinuous conduction mode buck-
boost converter, U1 provides high power factor and very low ATHD
via its internal control algorithm (the design also features low input
capacitance to further reduce THD and increase PF). Discontinuous
Selection of fuse RF1 in Figure 7 type and rating is dependent on input
surge requirements. Typical minimum requirement for bulb applica-
tion is 500 V differential surges. This design meets a 1 kV surge
specification, so a 47 W fusible resistor in Figure 7 was used. A fast-
blow fuse with high ampere energy (I2T) rating could also be used.
5
Rev. D 04/16
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LYT3314-3328
LYTSwitch-3 Output Regulation
capacitor should be greater than 7 V. The capacitor can be a ceramic
or electrolytic type, but tolerance should be less than 50%. The
capacitor must be physically located close to BYPASS and SOURCE
pins for effective noise decoupling.
In order to maintain very tight output current regulation – within
±3%, the FEEDBACK (FB) pin voltage (with an appropriately selected
low-pass filter comprising R15 and C8) is compared to a preset
average feedback voltage (VFB) of 300 mV. When the detected signal
is above or below the preset average VFB threshold voltage, the
onboard averaging-engine will adjust the frequency and/or on-time to
maintain regulation.
Output Rectification
During the switching OFF-state the output from the transformer main
winding is rectified by D3 and filtered by C10. An ultrafast 1 A, 600 V
with 35 ns reverse recovery time (tRR) diode was selected for efficiency.
The value of the output capacitor C10 was selected to give peak-to-
peak LED ripple current equal to 30% of the mean value. However,
the output ripple current will also depend on the type and impedance
characteristic of the LED load, so it is recommended to, use the
actual LED load for sizing the capacitor value for the output ripple
current. For designs where lower ripple is desirable the output
capacitance value can be increased unlike traditional power supplies,
low ESR capacitors are not required for the output stage of LED
designs.
The bias winding voltage is proportional to the output voltage
(controlled by the turns-ratio between the bias supply and output-
main winding). This allows the output voltage to be monitored
without the need for output-side feedback components. Resistor R16
in Figure 7 converts the bias voltage into a current which is fed into
the OUTPUT COMPENSATION (OC) pin of U1. The OUTPUT COMPEN-
SATION pin current is also used to detect output overvoltage which is
set to 30% above the nominal output voltage. Once the current
exceeds the IOOV threshold the IC will trigger a latch, which disables
switching which prevents the output from rising further. An AC
recycle is needed to reset this protection mode once triggered.
A small output pre-load resistor R19 discharges the output capacitor
when the driver is turned off, giving a relatively quick and smooth
decay of the LED light. Recommended pre-load power dissipation is
≤0.5% of the output power.
In order to provide line input voltage information to U1 the rectified
input AC voltage is fed into the LINE SENSE (L) pin of U1 as a current
via R20 and R18. This sensed current is also used by U1 to detect
the input zero crossing, type of dimmer (i.e. leading or trailing edge)
connected to the input and set the input line overvoltage protection
threshold. In a line overvoltage condition once this current exceeds
the ILOV+ threshold, the IC will instantaneously disable switching to
protect the power MOSFET from further voltage stress. The IC will
start switching as soon as the line voltage drops to safe levels
indicated by the LINE SENSE pin current dropping by 5 µA.
Phase-Cut Dimming
The biggest challenge in designing dimmable LED bulb is high
compatibility with a broad range of dimmer types and power rating.
As different type of dimmers have different minimum loading
requirements the dimmable LED bulb may manifest varying incompat-
ibility behavior depending on the dimming conditions from light
flickering or shimmering, ghosting, huge pop-on to low dim ratio.
There are two main types of phase-cut dimmers namely leading edge
(Figure 8) and trailing edge (Figure 9). Each type has its own
characteristic and nuances that particularly makes it challenging for
LED driver to achieve high compatibility and no one can ever know
what type of dimmer an LED bulb will be used with therefore it is
imperative that the designer must use a controller with bleeder with
the capability to satisfy the requirement depending the type of the
dimmer.
The primary switched current is sensed via R12 and filtered with C6.
The signal is fed into the DRIVER CURRENT SENSE (DS) pin. A low
ESR ceramic capacitor of at least 10 µF is recommended for capacitor
C6 for better regulation and reduced the AC RMS loss across R6. The
DRIVER CURRENT SENSE pin program resistor R13 is 6.04 kW 1% for
primary-side regulation for indirectly sensing of the output current.
The internal frequency/on-time engine inside the LYTSwitch-3 IC
combines the OUTPUT COMPENSATION pin current, the LINE SENSE
pin current and the DRIVER CURRENT SENSE pin current information
to deduce the FEEDBACK pin signal. This is compared to an internal
VFB threshold to maintain accurate constant output current.
The requirement to provide flicker-free output dimming with low-cost,
TRIAC-based, leading edge phase dimmers introduces a number of
trade-off in the design. Due to the much lower power consumed by
LED based lighting the current drawn by the overall lamp is below the
holding current of the TRIAC within the dimmer. This causes
undesirable behaviors such as limited dimming range and/or flickering.
The relatively large impedance the LED lamp presents to the line
allows significant ringing to occur due to the inrush current charging
the input capacitance when the TRIAC turns on. This too can cause
similar undesirable behavior as the ringing may cause the TRIAC
current to fall to zero and turn-off.
It is important to note that for accurate output current regulation the
use of 1% tolerance for LINE SENSE pin resistors (R20 and R18) is
recommended. This recommendation also applies to OUTPUT
COMPENSATION pin resistor R16, FEEDBACK pin resistor R15
(capacitor C8 at least X7R type), and DRIVER CURRENT SENSE pin
resistor R12 and R13.
Diode D2 and C11 provides a bias supply for U1 from an auxiliary
winding on the transformer. Bias supply recommended voltage level
is 20 V, when this voltage drops at low conduction angle during
dimming would be high enough to maintain supply for U1. Filter
capacitor C11 should be sized to ensure a low ripple voltage.
Capacitor C7 serves as local decoupling for the BYPASS pin of U1
which is the supply pin for the internal controller. Current via R14 is
typically limited to 2.5 mA. During start-up, C7 is charged to ~5.3 V
from an internal high-voltage current source internally fed from the
DRAIN pin. This allows U1 to start switching even at low conduction
angle when in dimming. After start-up the operating supply current is
provided from the bias supply via R14. The recommended value for
the BYPASS pin capacitor C7 is 22 µF. The voltage rating for the
Figure 9 shows the line voltage and current at the input of the power
supply with a trailing edge dimmer. In this example, the dimmer
conducts at 90 degrees. Many of these dimmers use back-to-back
connected power FETs rather than a TRIAC to control the load. This
eliminates the holding current issue of TRIACs and since the
conduction begins at the zero crossing, high current surges and line
ringing are minimized. Typically these types of dimmers do not
require damping circuits. However, would require a bleeder circuit to
provide a low impedance path for the internal supply to recharge and
reset its internal controller in order to operate normally and avoid
misfiring for the succeeding cycle of the incoming input.
6
Rev. D 04/16
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LYT3314-3328
ꢈ1
L
Rꢅ
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Figure 8. Typical Voltage and Current Waveform and Schematic of a TRIAC-Based Leading Edge Dimmer.
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D1
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Figure 9. Typical Voltage and Current Waveforms and Schematic of a MOSFET-Based Trailing Edge Dimmer.
LYTSwitch-3 Smart Active Bleeder
current falls below the holding current thus maintaining the current
set by the resistor R1. The holding current can be set using the
equation R1 = 120 mV / A. For this design (DER-524) it is 30 mA.
Bleeder resistors R9 and R32 recommended total value is 5 kW with
2 W power rating each resistor for high-line application (1.2 kW total
for low-line at 50 mA holding current).
To overcome the challenges of designing for dimmable LED driver
with high compatibility on any type of dimmer, LYTSwitch-3 family
features a built-in TRIAC detector that is able to discriminate between
leading-edge and trailing-edge dimmers. This capability together
with load monitoring circuitry enables the controller to adjust bleeder
operation during each switching cycle to ensure a TRIAC input
impedance, or to disable the bleeder circuitry completely if no
dimmer is detected (significantly increasing efficiency). The active
bleeder also helps in keeping the input current above the TRIAC
holding and latching current while the input current corresponding to
the effective driver resistance increases during each AC half-cycle.
Capacitor C2 and degenerative resistor R4 serve as stabilizing
network for the bleeder transistors for optimized dimming perfor-
mance. Resistor R4 typical range of value is 20 – 47 W while C2 is
between 4.7 – 22 nf.
Passive Bleeder and Damper
Both capacitor C3 and resistor R8 together with fusible resistor RF1
and damper R7 act as damper reducing the ringing current induced
by the spike of current charging the input bulk capacitors after the
TRIAC fired at the onset of input AC. The value of C3 is typically
from 47 nf to 220 nf, while R8 can be between 470 W to 1 kW.
The LYTSwitch-3 ICs provide excellent dimming performance with its
close loop smart bleeder function. Transistor Q1 together with Q2 in
emitter follower connection, function as a high gain active switch that
pulls current from the input via R9 and R32. This maintains the
holding current and latching current necessary to keep the TRIAC on
during the entire input cycle. The analog signal from the BLEEDER
CONTROL (BL) pin of U1 drives Q1 and Q2 linearly when the input
7
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LYT3314-3328
and enables the use of small and simple pi (π) filter. It also allows
simple magnetic construction where the main winding can be wound
continuously using the automated winding approach preferred for
low-cost manufacturing. The recommended location of the EMI filter
is after the bridge rectifier. This allows the use of regular film
capacitors as opposed to more expensive safety rated X-capacitors
that would be required if the filter is placed before the bridge.
Key Design Considerations
Device Selection
The data sheet power table (Table 4) represents the maximum
practical continuous output power that can be delivered in an open
frame design with adequate heat sinking.
Output Power Table
Surge Immunity Consideration
This design assumed a differential surge requirement of up to 1 kV
which can be met easily with LYTSwitch-3’s very accurate line
overvoltage protection and a MOV (RV1).
Output Power
Product
85-132 VAC or 185-265 VAC
LYT33x4D
LYT33x5D
LYT33x6D
LYT33x8D
5.7 W
8.8 W
Thermal and Lifetime Considerations
Lighting applications present thermal challenges to the driver. In
many cases the LED load dissipation determines the working ambient
temperature experienced by the drive. Thermal evaluation should be
performed with the driver inside the final enclosure. Temperature
has a direct impact on driver and LED lifetime. For every 10 °C rise in
temperature, component life is reduced by a factor of 2. Therefore it
is important to verify and optimize the operating temperatures of all
components.
12.6 W
20.4 W
Table 4.
Output Power Table.
DER-524 is an 8 W LED dimmable driver. Where LYT3325D was
chosen for its higher voltage power MOSFET rating of 725 V because
the topology chosen was a buck-boost and the specification called for
a maximum input voltage of 264 VAC. In other applications where
surge and line voltage conditions allow, it may be possible to use the
650 V power MOSFET option to reduce design cost without impacting
reliability.
Provide enough spacing between bleeder and damper components
for better natural heat convection cooling.
Quick Design Checklist
Maximum Drain Voltage – Verify that the peak Drain voltage stress
(VDS) does not exceed 725 V under all operating conditions, including
start-up and fault conditions.
Magnetics Design
A very common core type was selected, an EE10 with ferrite core
material and a wide winding window that allowed better convection
cooling for the winding.
Maximum Drain Current – Measure the peak Drain current under all
operation conditions (including start-up and fault conditions). Look for
transformer saturation (usually occurs at highest operating ambient
temperatures). Verify that the peak current is less than the stated
Absolute Maximum Rating in the data sheet.
To ensure that discontinuous conduction mode (DCM) operation of
LYTSwitch-3 is maintained over line input and inductance tolerance
variations that is needed for tight output current regulation, it is
recommended that the LYTSwitch-3 PIXls spreadsheet located at
PI Expert online (https://piexpertonline.power.com/site/login) should
be used for magnetics calculations.
Thermal Check – At maximum output power, for both minimum and
maximum line voltage and maximum ambient temperature; verify
that temperature specifications are not exceeded for the LYTSwitch-3,
transformer, output diodes, output capacitors and clamp components.
EMI Considerations
Total input capacitance affects PF and ATHD – increasing the value
will degrade performance. With LYTSwitch-3 the combination of a
low-side switching configuration and frequency jitter reduces EMI
8
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LYT3314-3328
As shown in Figure 10, minimize the loop areas of the following
switching circuit elements to lessen the creation of EMI.
PCB Layout Considerations
The EMI filter components should be located close together to improve
filter effectiveness. Place the EMI filter components C4 and L1 as far
away as possible from any switching nodes on the circuit board
especially U1 drain node, output diode (D3) and the transformer (T1).
• Loop area formed by the transformer output winding (T1), output
rectifier diode (D3) and output capacitor (C10).
• Loop area formed by transformer bias winding (T1), rectifier diode
(D2) and filter capacitor (C11).
Care should be taken in placing the components on the layout that
are used for processing input signals for the feedback loop – any high
frequency noise coupled to the signal pins of U1 may affect proper
system operation. The critical components in DER-524 are R18, R16,
C8, R15, R13 and R11. It is highly recommended that these compo-
nents be placed very close to the pins of U1 (to minimize long traces
which could serve as antenna) and far away as much as possible from
any high-voltage and high current nodes in the circuit board to avoid
noise coupling.
• Loop area formed by input capacitor (C5), sense resistor R12,
internal power MOSFET (U1) and transformer (T1) main winding.
Lastly, unlike discrete MOSFET designs where heat sinking is through
the drain tab and which generates significant EMI, LYTSwitch-3 ICs
employ low-side switching and the ground potential SOURCE pins are
used for heat sinking. This allows the designer to maximize the
copper area for good thermal management but without having the
risk of increased EMI.
Design Tools
The BYPASS pin supply capacitor C7 should be placed directly across
BYPASS pin and SOURCE pin of U1 for effective noise decoupling.
Up-to-date information on design tools can be found at the Power
Integrations web site: www.power.com
DRꢝꢍꢜR ꢛꢦRRꢜꢥꢧ
ꢜꢋꢝ ꢞπꢟ ꢈꢅꢑꢆeꢃ
ꢛ4ꢉ ꢠ1ꢉ ꢛꢡ
Rꢛ ꢐꢑeeꢒeꢃ
Rꢢꢉ ꢛꢓ
ꢌꢚꢆꢂꢚꢆ
ꢛꢀꢂꢀꢏꢅꢆꢇꢃ
ꢠꢝꢥꢜ ꢙꢜꢥꢙꢜ ꢣꢅꢘ
Reꢄꢅꢄꢆꢇꢃ R1ꢢ
ꢐꢠꢜꢜDꢜR ꢛꢦRRꢜꢥꢧ
ꢙꢜꢥꢙꢜ ꢣꢅꢘ Reꢄꢅꢄꢆꢇꢃ R11
ꢙꢜꢥꢙꢜ ꢣꢅꢘ
ꢌꢚꢆꢂꢚꢆ Dꢅꢇꢒe
Reꢏꢆꢅꢨꢅeꢃ Dꢓ ꢀꢘꢒ
ꢈꢅꢑꢆeꢃ ꢛꢀꢂꢀꢏꢅꢆꢇꢃ
ꢛ10
Dꢀꢁꢂeꢃ
Reꢄꢅꢄꢆꢇꢃꢄ
Rꢈ1ꢉ Rꢊ
Reꢄꢅꢄꢆꢇꢃ R1ꢓ
ꢋꢀꢩꢅꢁꢅꢪeꢒ
ꢛꢇꢂꢂeꢃ
ꢫeꢀꢆ ꢙꢅꢘꢬ
ꢨꢇꢃ ꢦ1
Tꢀꢁꢂꢃꢄꢅꢀꢆꢇꢀ
Tꢀꢁꢂꢃꢄꢅꢀꢆꢇꢀ
ꢐꢅꢀꢄ Dꢅꢇꢒe
Reꢏꢆꢅꢨꢅeꢃ Dꢔ
ꢀꢘꢒ ꢈꢅꢑꢆeꢃ ꢛ11
ꢋꢌꢍ
Rꢍ1
ꢈꢜꢜDꢐꢎꢛꢮ ꢣꢅꢘ
Reꢄꢅꢄꢆꢇꢃ R1ꢡ
ꢀꢘꢒ ꢛꢢ
ꢐꢗꢂꢀꢄꢄ ꢀꢘꢒ ꢐꢅꢀꢄ
ꢙꢚꢂꢂꢑꢗ ꢛꢀꢂꢀꢏꢅꢆꢇꢃꢄ
ꢛꢊꢉ ꢛ11
ꢎꢏꢆꢅve ꢐꢑeeꢒeꢃ
Rꢓꢔꢉ Rꢕꢉ ꢖ1ꢉ ꢖꢔ
Dꢃꢀꢅꢘ ꢛꢚꢃꢃeꢘꢆ
ꢌꢦꢧꢣꢦꢧ
ꢙeꢘꢄe R1ꢔ ꢀꢘꢒ ꢛ6 ꢛꢌꢋꢣꢜꢥꢙꢎꢧꢝꢌꢥ ꢣꢅꢘ
Reꢄꢅꢄꢆꢇꢃ R16
ꢐꢭꢣꢎꢙꢙ ꢣꢅꢘ
ꢛꢀꢂꢀꢏꢅꢆꢇꢃ ꢛꢊ
ꢣꢝꢤꢊꢢ6ꢕꢤ0ꢔ0416
Figure 10. Single-Side PCB Layout Example Showing the Arrangement and Location of Critical Components.
9
Rev. D 04/16
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LYT3314-3328
Absolute Maximum Ratings(1,3)
DRAIN Pin Voltage:
LYT331x............................-0.3 V to 650 V Notes:
LYT332x ...........................-0.3 V to 725 V
1. All voltages referenced to Source, TA = 25 °C.
2. 1/16 in. from case for 5 seconds.
DRAIN Pin Peak Current(4) LYT3314............................ 1.85 A (2.28 A)
LYT3324 ........................... 1.44 A (2.33 A)
3. The Absolute Maximum Ratings specified may be applied, one at a
time without causing permanent damage to the product. Exposure
to Absolute Maximum Ratings for extended periods of time may
affect product reliability.
4. The higher peak Drain current (in parentheses) is allowed while the
Drain voltage is simultaneously less than 400 V for 725 V integrated
MOSFET version, or less than 325 V for 650 V integrated MOSFET
version.
LYT3315 ........................... 2.39 A (2.95 A)
LYT3325 ............................1.95 A (3.16 A)
LYT3316 ........................... 3.25 A (4.00 A)
LYT3326 ........................... 2.64 A (4.35 A)
LYT3318 ........................... 5.06 A (6.30 A)
LYT3328 ............................4.16 A (6.86 A)
BP, BS, DS, BL, OC, L DS, FB Pin Voltage.....................-0.3 V to 6.5 V
Lead Temperature(2) .............................................................. 260 °C
Storage Temperature...................................................-65 to 150 °C
Operating Junction Temperature.................................. -40 to 150 °C
Thermal Resistance
Thermal Resistance: SO-16B Package:
Notes:
(qJA)..................................................78 °C/W(2) 1. Measured on the SOURCE pin close to plastic interface.
(qJA) .................................................68 °C/W(3) 2. Soldered to 0.36 sq. inch (232 mm2) 2 oz. (610 g/m2) copper clad,
(qJC)(1) ...............................................43 °C/W
with no external heat sink attached.
3. Soldered to 1 sq. in. (645 mm2), 2 oz, (610 g/m2) copper clad.
Conditions
SOURCE = 0 V
TJ = -40 °C to +125 °C
Parameter
Symbol
Min
Typ
Max
Units
(Note C) (Unless Otherwise Specified)
Control Functions
Average
TJ = 25 °C
115.3
124
8
132.7
kHz
%
Maximum
Output Frequency
fMAX
Peak-to-Peak Jitter
Average
TJ = 0 °C to 125 °C
40
8
kHz
%
Minimum
Output Frequency
fMIN
Peak-to-Peak Jitter
Frequency Jitter
Modulation Rate
fM
See Note A
1.76
kHz
Maximum On-Time
Minimum On-Time
FEEDBACK Pin Voltage
TON(MAX)
TON(MIN)
VFB
TJ = 25 °C
TJ = 25 °C
TJ = 25 °C
5.75
0.95
291
6.25
1.05
300
6.75
1.15
309
µs
µs
mV
FEEDBACK Pin Voltage
Triggering Cycle
Skipping
VFB(SK)
600
mV
mV
FEEDBACK Pin
Overvoltage Threshold
VFB(OV)
2000
FEEDBACK Pin
Undervoltage Threshold
VFB(UV)
IFB
22
mV
Feedback Pull-Up Current
-1.3
-1.0
-0.7
µA
10
Rev. D 04/16
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LYT3314-3328
Conditions
SOURCE = 0 V
TJ = -40 °C to +125 °C
Parameter
Symbol
Min
Typ
Max
Units
(Unless Otherwise Specified)
Control Functions (cont.)
VFB(ON) > VFB > VFB(SK)
(MOSFET not switching)
IS1
0.8
0.9
1.0
1.2
mA
LYT3314
LYT3324
LYT3315
1.0
1.0
1.3
1.3
DRAIN Supply Current
MOSFET Switching
LYT3325
LYT3316
LYT3326
LYT3318
LYT3328
LYT33x4
LYT33x5-8
LYT33x4
LYT33x5-8
1.1
1.4
IS2
at fMAX
mA
1.1
1.4
1.1
1.4
1.2
1.5
1.3
1.6
-8.5
-11.5
-6.5
-8.8
4.75
-7.5
-9.5
-5.2
-6.8
5.00
-6.0
-7.5
-4.0
-4.8
5.25
BYPASS Pin
Charge Current
ICH1
VBP = 0 V, TJ = 25 °C
VBP = 4 V, TJ = 25 °C
mA
BYPASS Pin
Charge Current
ICH2
mA
V
BYPASS Pin Voltage
VBP
BYPASS Pin
Shunt Voltage
VSHUNT
IBP = 5 mA
5.1
4.4
5.30
4.6
5.5
4.8
BYPASS Pin Power-Up
Reset Threshold Voltage
VBP(RESET)
V
Circuit Protection
Current Limit
di/dt = 662 mA/µs
TJ = 25 °C
LYT33x4
LYT33x5
LYT33x6
LYT33x8
843
1232
1767
2860
130
907
1325
1900
3075
970
1418
2033
3290
di/dt = 974 mA/µs
TJ = 25 °C
ILIMIT
mA
di/dt = 1403 mA/µs
TJ = 25 °C
di/dt = 2239 mA/µs
TJ = 25 °C
Leading Edge
Blanking Time
tLEB
TILD
TFB
TJ = 25 °C
165
160
142
ns
ns
°C
Current Limit Delay
TJ = 25 °C, See Note A
See Note A
Thermal Foldback
Temperature
138
155
146
165
Thermal Shutdown
Temperature
TSD
See Note A
160
°C
Thermal Shutdown
Hysteresis
TSD(H)
See Note A
TJ = 25 °C
75
°C
ns
SOA Switch ON-Time
TON(SOA)
610
690
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LYT3314-3328
Conditions
SOURCE = 0 V
TJ = -40 °C to +125 °C
Parameter
Symbol
Min
Typ
Max
Units
(Unless Otherwise Specified)
Circuit Protection (cont.)
Auto-Restart Current
Threshold for Output
Undervoltage
IOUV
TJ = 25 °C
40
52
58
µA
µA
Threshold
TJ = 25 °C
116
120
5
124
Current Threshold for
Input Overvoltage
ILOV+
Hysteresis
Latch-Off Current
Threshold for Output
Overvoltage
IOOV
TJ = 25 °C
127
134
144
µA
LINE-SENSE Pin Voltage
Output
VL
IL = 100 µA, TJ = 25 °C
2.05
2.25
2.45
V
OUTPUT COMPENSATION
Pin Voltage
IOC = 100 µA
TJ = 25 °C
VOC
2.05
2.25
2.45
V
TJ = 25 °C
5.40
8.40
3.80
5.70
2.75
4.25
1.75
2.70
6.20
9.70
4.35
6.55
3.15
4.90
2.00
3.10
LYT33x4
ID = 150 mA
TJ = 100 °Cdrdxd
TJ = 25 °C
LYT33x5
ID = 200 mA
TJ = 100 °C
ON-State
Resistance
RDS(ON)
W
TJ = 25 °C
LYT33x6
ID = 300 mA
TJ = 100 °C
TJ = 25 °C
LYT33x8
ID = 500 mA
TJ = 100 °C
VBP = 5.3 V, VFB > VFB(SK) , VDS = 580 V
TJ = 125 °C
OFF-State Leakage
Breakdown Voltage
IDSS
200
µA
VBP = 5.3 V, VFB
VFB(SK)
>
LYT331x
LYT332x
650
725
BVDSS
V
TJ = 25 °C
NOTES:
A. Guaranteed by design.
12
Rev. D 04/16
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LYT3314-3328
Typical Performance Curves
ꢀ00
1.ꢀ
1
ꢉꢊꢋꢌꢍꢎꢏ ꢐꢋꢊꢑꢒꢓꢔꢕ
ꢅꢆꢇꢃꢃꢀ4 1.0
ꢅꢆꢇꢃꢃꢀꢁ 1.4
ꢅꢆꢇꢃꢃꢀ6 ꢀ.0ꢁ
ꢅꢆꢇꢃꢃꢀꢈ ꢃ.ꢃꢁ
ꢄꢀꢃ ꢅ
6ꢃ0 ꢅ
1ꢂꢁ
1ꢁ0
0.ꢁ
0.6
1ꢀꢁ
100
ꢉꢊꢋꢌꢍꢎꢏ ꢐꢋꢊꢑꢒꢓꢔꢕ
ꢅꢆꢇꢃꢃ14 1.0
ꢅꢆꢇꢃꢃ1ꢁ 1.4
ꢅꢆꢇꢃꢃ16 ꢀ.0ꢁ
ꢅꢆꢇꢃꢃ1ꢈ ꢃ.ꢃꢁ
ꢂꢁ
ꢁ0
ꢀꢁ
0.4
0.ꢀ
0
ꢂꢀꢁ ꢄ
6ꢁ0 ꢄ
0
0
100 ꢀ00 ꢃ00 400 ꢁ00 600
0
100 ꢀ00 ꢂ00 400 ꢃ00 600 ꢄ00 ꢁ00
ꢀꢁꢂꢃꢄ ꢅꢆꢇꢈꢉꢊꢋ ꢌꢅꢍ
ꢀꢁꢂꢃꢄ ꢅꢆꢇꢈꢉꢊꢋ ꢌꢅꢍ
Figure 11. Power vs. Drain Voltage.
Figure 12. Maximum Allowable Drain Current vs. Drain Voltage.
1.ꢀ
1.6
1.4
1.ꢁ
1
ꢀ.ꢀ
ꢀ
1.ꢁ
1.6
1.4
1.ꢀ
1
0.ꢀ
0.ꢁ
0.6
ꢇꢈꢉꢊꢋꢌꢍ ꢎꢉꢈꢏꢐꢑꢒꢓ
0.6
0.4
0.ꢀ
0
ꢇꢈꢉꢊꢋꢌꢍ ꢎꢉꢈꢏꢐꢑꢒꢓ
ꢂꢃꢄꢅꢅ14 1.0
ꢂꢃꢄꢅꢅ1ꢆ 1.4
ꢂꢃꢄꢅꢅ16 ꢀ.0ꢆ
ꢂꢃꢄꢅꢅ1ꢁ ꢅ.ꢅꢆ
ꢔꢁꢆ ꢕ
ꢁꢆ ꢖꢗ
ꢔꢁꢆ ꢕ
1ꢁꢆ ꢖꢗ
6ꢆ0 ꢔ
ꢀꢆ ꢕꢖ
6ꢆ0 ꢔ
1ꢀꢆ ꢕꢖ
0.4
0.ꢁ
0
ꢂꢃꢄꢅꢅꢁ4 1.0
ꢂꢃꢄꢅꢅꢁꢆ 1.4
ꢂꢃꢄꢅꢅꢁ6 ꢁ.0ꢆ
ꢂꢃꢄꢅꢅꢁꢀ ꢅ.ꢅꢆ
0
ꢁ
4
6
ꢀ
10 1ꢁ 14 16 1ꢀ ꢁ0
0
ꢀ
4
6
ꢁ
10 1ꢀ 14 16 1ꢁ ꢀ0
ꢀꢁꢂꢃꢄ ꢅꢆꢇꢈꢉꢊꢋ ꢌꢅꢍ
ꢀꢁꢂꢃꢄ ꢅꢆꢇꢈꢉꢊꢋ ꢌꢅꢍ
Figure 13. Drain Current vs. Drain Voltage.
Figure 14. Drain Current vs. Drain Voltage.
10000
1000
100
1
ꢃꢀꢂ ꢄ
6ꢂ0 ꢄ
ꢉꢊꢋꢌꢍꢎꢏ ꢐꢋꢊꢑꢒꢓꢔꢕ
ꢅꢆꢇꢁꢁꢀ4 1.0
ꢅꢆꢇꢁꢁꢀꢂ 1.4
ꢅꢆꢇꢁꢁꢀ6 ꢀ.0ꢂ
ꢅꢆꢇꢁꢁꢀꢈ ꢁ.ꢁꢂ
ꢉꢊꢋꢌꢍꢎꢏ ꢐꢋꢊꢑꢒꢓꢔꢕ
ꢅꢆꢇꢁꢁ14 1.0
ꢅꢆꢇꢁꢁ1ꢂ 1.4
ꢅꢆꢇꢁꢁ16 ꢀ.0ꢂ
ꢅꢆꢇꢁꢁ1ꢈ ꢁ.ꢁꢂ
0
100 ꢀ00 ꢁ00 400 ꢂ00 600
ꢀꢁꢂꢃꢄ ꢅꢆꢇꢈꢉꢊꢋ ꢌꢅꢍ
Figure 15. Drain Capacitance vs. DRAIN Pin Voltage.
13
Rev. D 04/16
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LYT3314-3328
ꢀꢁ-1ꢂꢃ
3
4
ꢌꢍꢌ1ꢠ ꢎꢌꢍ48ꢏ
ꢌꢍꢌ13 ꢎꢌꢍ33ꢏ
ꢌꢍꢌꢒꢌ ꢎ1ꢍ2ꢡꢏ
14ꢢ
ꢌꢍꢌ1ꢌ ꢎꢌꢍ2ꢒꢏ ꢜ ꢣ ꢔ ꢃ
8 Lꢄꢅꢞ Tꢇꢤꢚ
ꢌꢍꢌ44 ꢎ1ꢍ1ꢌꢏ ꢐꢄꢑꢍ
ꢌꢍꢌ1ꢌ ꢎꢌꢍ2ꢒꢏ
1ꢂ
ꢠ
ꢌꢍꢌꢌꢒ ꢎꢌꢍ13ꢏ ꢣ
2ꢢ
ꢌꢍꢌꢌ4 ꢎꢌꢍ1ꢌꢏ ꢣ ꢃ
ꢥ
ꢌꢍ1ꢒ3 ꢎ3ꢍꢠꢌꢏ
ꢌꢍ23ꢠ ꢎꢂꢍꢌꢡꢏ
2
ꢕꢅꢖꢉꢄ ꢊꢋꢅꢈꢄ
ꢀꢄꢅꢆꢇꢈꢉ ꢊꢋꢅꢈꢄ
ꢦ
ꢦ
ꢌꢍꢌꢌꢒ ꢎꢌꢍ13ꢏ ꢣ
ꢂ Lꢄꢅꢞ Tꢇꢤꢚ
8
ꢌ
1
8
ꢃ
ꢣ
ꢊꢇꢈ ꢗ1 ꢘꢍꢓꢍ
ꢙLꢅꢚꢄꢛ ꢜꢅꢛꢝꢄꢞꢟ
ꢌꢍꢌ32 ꢎꢌꢍ81ꢏ
ꢌꢍꢌ22 ꢎꢌꢍꢒꢂꢏ
ꢌꢍ13ꢒ ꢎ3ꢍ43ꢏ
ꢐꢄꢑꢍ
2
ꢔ
ꢌꢍ3ꢠꢌ ꢎꢠꢍꢠ1ꢏ
ꢌꢍꢌꢌ4 ꢎꢌꢍ1ꢌꢏ ꢣ ꢔ 2ꢢ
DETAIL A
TOP VIEW
ꢊꢋꢌeꢍꢎ
1. Dꢏꢐeꢑꢍꢏꢋꢑꢏꢑꢒ ꢓꢑꢔ ꢌꢋꢕeꢖꢓꢑꢗꢏꢑꢒ ꢘeꢖ
ꢉꢇꢙꢚ ꢛ14.ꢅꢙꢂ1ꢜꢜ4.
ꢌꢍꢌꢂꢂ ꢎ1ꢍꢂꢠꢏ
ꢌꢍꢌꢒꢡ ꢎ1ꢍ4ꢂꢏ
ꢌꢍꢌꢒ4 ꢎ1ꢍ38ꢏ ꢐꢄꢑꢍ
ꢓꢄꢆꢅꢇꢋ ꢔ
ꢝ. Dꢏꢐeꢑꢍꢏꢋꢑꢍ ꢑꢋꢌeꢔ ꢓꢖe ꢔeꢌeꢖꢐꢏꢑeꢔ ꢓꢌ ꢌꢞe
ꢋꢟꢌeꢖꢐꢋꢍꢌ eꢠꢌꢖeꢐeꢍ ꢋꢡ ꢌꢞe ꢘꢕꢓꢍꢌꢏꢗ ꢢꢋꢔꢣ eꢠꢗꢕꢟꢍꢏve
ꢋꢡ ꢐꢋꢕꢔ ꢡꢕꢓꢍꢞꢤ ꢌꢏe ꢢꢓꢖ ꢢꢟꢖꢖꢍꢤ ꢒꢓꢌe ꢢꢟꢖꢖꢍꢤ ꢓꢑꢔ
ꢏꢑꢌeꢖꢂꢕeꢓꢔ ꢡꢕꢓꢍꢞꢤ ꢢꢟꢌ ꢏꢑꢗꢕꢟꢔꢏꢑꢒ ꢓꢑꢣ ꢐꢏꢍꢐꢓꢌꢗꢞ
ꢢeꢌꢥeeꢑ ꢌꢞe ꢌꢋꢘ ꢓꢑꢔ ꢢꢋꢌꢌꢋꢐ ꢋꢡ ꢌꢞe ꢘꢕꢓꢍꢌꢏꢗ ꢢꢋꢔꢣ.
ꢙꢓꢠꢏꢐꢟꢐ ꢐꢋꢕꢔ ꢘꢖꢋꢌꢖꢟꢍꢏꢋꢑ ꢏꢍ 0.ꢝꢅ ꢐꢐ ꢘeꢖ ꢍꢏꢔe.
ꢀꢄꢅꢆꢇꢈꢉ
ꢊꢋꢅꢈꢄ
ꢌꢍꢌ1ꢌ ꢎꢌꢍ2ꢒꢏ
ꢌꢍꢌꢌ4 ꢎꢌꢍ1ꢌꢏ
ꢄ. Dꢏꢐeꢑꢍꢏꢋꢑꢍ ꢑꢋꢌeꢔ ꢓꢖe ꢏꢑꢗꢕꢟꢍꢏve ꢋꢡ ꢘꢕꢓꢌꢏꢑꢒ
ꢌꢞꢏꢗꢦꢑeꢍꢍ.
ꢣ
ꢌꢍꢌ1ꢌ ꢎꢌꢍ2ꢒꢏ
ꢌꢍꢌꢌ4 ꢎꢌꢍ1ꢌꢏ
ꢌꢍꢌꢌ4 ꢎꢌꢍ1ꢌꢏ ꢣ
14 Lꢄꢅꢞꢚ
4. Dꢋeꢍ ꢑꢋꢌ ꢏꢑꢗꢕꢟꢔe ꢏꢑꢌeꢖꢂꢕeꢓꢔ ꢡꢕꢓꢍꢞ ꢋꢖ ꢘꢖꢋꢌꢖꢟꢍꢏꢋꢑꢍ.
ꢅ. Dꢏꢐeꢑꢍꢏꢋꢑꢍ ꢏꢑ ꢁꢑꢗꢞeꢍ ꢧꢐꢐꢨ.
END VIEW
6. Dꢓꢌꢟꢐꢍ ꢉ ꢓꢑꢔ ꢈ ꢌꢋ ꢢe ꢔeꢌeꢖꢐꢏꢑeꢔ ꢏꢑ Dꢓꢌꢟꢐ ꢩ.
ꢃ. ꢪꢚDꢚꢫ ꢖeꢡeꢖeꢑꢗeꢎ ꢙꢇ − 01ꢝ.
SIDE VIEW
ꢀꢁꢂꢃ4ꢃꢄꢂ061ꢅ1ꢅ
ꢀꢆDꢂꢇꢆꢂ16ꢈ Rev ꢉ
14
Rev. D 04/16
www.power.com
LYT3314-3328
ꢄꢅꢆꢇꢅꢈꢉ ꢊꢅꢋꢇꢌꢍꢈ
ꢀꢁ-1ꢂꢃ
ꢚ
ꢊ
1ꢀ4ꢀ
ꢁꢂꢃꢄꢄꢅꢆD
ꢇ4ꢈ16ꢉꢊ
ꢞ
D
ꢊ. ꢈꢎꢏeꢐ ꢋꢑꢒeꢓꢐꢔꢒꢕꢎꢑꢖ Reꢓꢕꢖꢒeꢐeꢗ ꢃꢐꢔꢗeꢘꢔꢐꢙ
ꢚ. ꢊꢖꢖeꢘꢛꢜꢝ Dꢔꢒe ꢞꢎꢗe ꢟꢜꢔꢖꢒ ꢒꢏꢎ ꢗꢕꢓꢕꢒꢖ ꢎꢠ ꢝeꢔꢐ ꢠꢎꢜꢜꢎꢏeꢗ ꢛꢝ ꢡꢌꢗꢕꢓꢕꢒ ꢏꢎꢐꢙ ꢏeeꢙꢢ
ꢞ. ꢈꢐꢎꢗꢣꢤꢒ ꢋꢗeꢑꢒꢕꢠꢕꢤꢔꢒꢕꢎꢑ ꢟꢈꢔꢐꢒ ꢥ/ꢈꢔꢤꢙꢔꢓe ꢃꢝꢦeꢢ
D. ꢁꢎꢒ ꢋꢗeꢑꢒꢕꢠꢕꢤꢔꢒꢕꢎꢑ ꢞꢎꢗe
ꢈꢋꢌꢉꢆ01ꢌ111ꢍ1ꢀ
15
Rev. D 04/16
www.power.com
LYT3314-3328
MSL Table
Part Number
MSL Rating
LYT33x4
LYT33x5
LYT33x6
LYT33x8
3
3
3
3
ESD and Latch-Up Table
Test
Conditions
JESD78D
Results
Latch-up at 125 °C
Human Body Model ESD
Machine Model ESD
> ±100 mA or > 2.5 kV (max) on all pins
> ±2000 V on all pins
JESD22-A114F
JESD22-A115CA
> ±200 V on all pins
Part Ordering Information
• LYTSwitch-3 Product Family
• Series Number
• Package Identifier
D
SO-16B
• Tape & Reel and Other Options
Blank
Tube of 50 pcs.
TL
Tape & Reel, 2500 pcs min/mult.
LYT 33x4 D - TL
16
Rev. D 04/16
www.power.com
LYT3314-3328
Notes
17
Rev. D 04/16
www.power.com
Revision Notes
Date
A
B
C
D
D
Code S Release.
09/15
11/09/15
02/16
Added Block diagram and Typical Performance Curves.
Code A Release.
Corrected IS2 parameter. Added VOC and VL parameters.
03/16
TON(MAX) parameter errors fixed.
04/01/16
For the latest updates, visit our website: www.power.com
Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power Integrations
does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES NO WARRANTY
HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED WARRANTIES OF MERCHANTABILITY,
FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS.
Patent Information
The products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered by one
or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power Integrations. A complete list of
Power Integrations patents may be found at www.power.com. Power Integrations grants its customers a license under certain patent rights as set
forth at http://www.power.com/ip.htm.
Life Support Policy
POWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS
WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein:
1. A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii) whose
failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in significant injury or
death to the user.
2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the
failure of the life support device or system, or to affect its safety or effectiveness.
The PI logo, TOPSwitch, TinySwitch, LinkSwitch, LYTSwitch, InnoSwitch, DPA-Switch, PeakSwitch, CAPZero, SENZero, LinkZero, HiperPFS,
HiperTFS, HiperLCS, Qspeed, EcoSmart, Clampless, E-Shield, Filterfuse, FluxLink, StakFET, PI Expert and PI FACTS are trademarks of Power
Integrations, Inc. Other trademarks are property of their respective companies. ©2016, Power Integrations, Inc.
Power Integrations Worldwide Sales Support Locations
World Headquarters
5245 Hellyer Avenue
San Jose, CA 95138, USA.
Main: +1-408-414-9200
Customer Service:
Phone: +1-408-414-9665
Fax: +1-408-414-9765
e-mail: usasales@power.com
Germany
Lindwurmstrasse 114
80337 Munich
Japan
Kosei Dai-3 Bldg.
2-12-11, Shin-Yokohama,
Kohoku-ku
Yokohama-shi, Kanagawa
222-0033 Japan
Phone: +81-45-471-1021
Fax: +81-45-471-3717
e-mail: japansales@power.com
Taiwan
5F, No. 318, Nei Hu Rd., Sec. 1
Nei Hu Dist.
Taipei 11493, Taiwan R.O.C.
Phone: +886-2-2659-4570
Fax: +886-2-2659-4550
e-mail: taiwansales@power.com
Germany
Phone: +49-895-527-39110
Fax: +49-895-527-39200
e-mail: eurosales@power.com
India
#1, 14th Main Road
Vasanthanagar
Bangalore-560052 India
Phone: +91-80-4113-8020
Fax: +91-80-4113-8023
e-mail: indiasales@power.com
UK
China (Shanghai)
Rm 2410, Charity Plaza, No. 88
North Caoxi Road
Shanghai, PRC 200030
Phone: +86-21-6354-6323
Fax: +86-21-6354-6325
e-mail: chinasales@power.com
Cambridge Semiconductor,
a Power Integrations company
Westbrook Centre, Block 5, 2nd Floor
Korea
RM 602, 6FL
Korea City Air Terminal B/D, 159-6 Milton Road
Samsung-Dong, Kangnam-Gu,
Seoul, 135-728, Korea
Phone: +82-2-2016-6610
Fax: +82-2-2016-6630
e-mail: koreasales@power.com
Cambridge CB4 1YG
Phone: +44 (0) 1223-446483
e-mail: eurosales@power.com
Italy
China (Shenzhen)
17/F, Hivac Building, No. 2, Keji Nan 20099 Sesto San Giovanni (MI)
Via Milanese 20, 3rd. Fl.
8th Road, Nanshan District,
Shenzhen, China, 518057
Phone: +86-755-8672-8689
Fax: +86-755-8672-8690
e-mail: chinasales@power.com
Italy
Singapore
51 Newton Road
Phone: +39-024-550-8701
Fax: +39-028-928-6009
e-mail: eurosales@power.com
#19-01/05 Goldhill Plaza
Singapore, 308900
Phone: +65-6358-2160
Fax: +65-6358-2015
e-mail: singaporesales@power.com
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