SC4614MSTRT [SEMTECH]
500kHz Voltage Mode PWM Controller; 500kHz的电压模式PWM控制器
| 型号： | SC4614MSTRT |
| 厂家： | 
SEMTECH CORPORATION |
| 描述： | 500kHz Voltage Mode PWM Controller |
| 文件： | 总14页 (文件大小：467K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
SC4614
500kHz Voltage Mode PWM Controller
POWER MANAGEMENT
Description
Features
The SC4614 is a high-speed, voltage mode PWM con-
troller that provides the control and protection features
necessary for a synchronous buck converter.
ꢀ 500kHz switching frequency
ꢀ 4V to 25V power rails
ꢀ 0.5V voltage reference for programmable output
voltages
ꢀ Internal LDO for optimum gate drive voltage
ꢀ 1.5A gate drive current
ꢀ Adaptive non-overlapping gate drives provide
shoot-through protection for MOSFETs
ꢀ Internal soft start
The SC4614 is designed to directly drive the top and
bottom MOSFETs of the buck converter. It allows the con-
verter to operate at 500kHz switching frequency with
4V to 25V power rail and as low as 0.5V output. It uses
an internal 8.2V supply as the gate drive voltage for mini-
mum driver power loss and MOSFET switching loss.
ꢀ Hiccup mode short circuit protection
ꢀ Power rail under voltage lockout
ꢀ MSOP-10 package, fully RoHS and WEEE compliant
The SC4614 features soft-start, supply power under volt-
age lockout, and hiccup mode over current protection.
The SC4614 monitors the output current by using the
Rdson of the bottom MOSFET in the buck converter that
eliminates the need for a current sensing resistor. The
SC4614 is offered in a MSOP-10 package.
Applications
ꢀ Embedded, low cost, high efficiency converters
ꢀ Point of load power supplies
ꢀ Set top box power supplies
ꢀ PDP/TFT TVs
ꢀ Consumer electronics
Typical Application Circuit
12V IN
+
1
2
3
4
5
10
9
BST
DH
PN
1.5V OUT
OCS
COMP
FB
1
2
8
DL
7
VCC
DRV
6
+
GND
SC4614
1
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January 16, 2007
SC4614
POWER MANAGEMENT
Absolute Maximum Ratings
Exceeding the specifications below may result in permanent damage to the device, or device malfunction. Operation outside of the parameters specified
in the Electrical Characteristics section is not implied.
Parameter
Symbol
Maximum
20
Units
V
Input Supply Voltage
VCC
BST to GND
VBST
VBST_PN
VPN
40
V
BST to PN
10
V
PN to GND
-1 to 30
-5
V
PN to GND Negative Pulse (tpulse < 20ns)
DL to GND
VPN_PULSE
VDL
V
-1 to +10
-3
V
DL to GND Negative Pulse (tpulse < 20ns)
DH to PN
VDL_PULSE
VDH_PN
VDH_PULSE
VDRV
V
-1 to +10
-3
V
DH to PN Negative Pulse (tpulse < 20ns)
DRV to GND
V
10
V
Operating Ambient Temperature Range
Operating Junction Temperature
Thermal Resistance Junction to Ambient
Thermal Resistance Junction to Case
Lead Temperature (Soldering) 10s
Storage Temperature
TA
-40 to 85
-40 to 125
136
°C
°C
°C/W
°C/W
°C
°C
TJ
θJA
45
θJC
TLEAD
TSTG
300
-65 to 150
Electrical Characteristics
Unless specified: VCC = 5V to 18V; VFB = VO; VBST - VPN = 5V to 8.2V; TA = -40 to 85°C
Parameter
Symbol
Conditions
Min
Typ
Max Units
General
VCC Supply Voltage
VCC Quiescent Current
VCC Under Voltage Lockout
BST to PN Supply Voltage
BST Quiescent Current
Internal LDO
V
CC
4
18
7
V
mA
V
IQVCC
UVVCC
VBST_PN
IQBST
5
V
V
CC = 12V, VBST -VPN = 8.2V
VHYST = 100mV
4
4
10
3
V
mA
CC = 12V, VBST -VPN = 8.2V
LDO Output
VDRV
8.6V < VCC < 18V
4V < VCC < 8.6V
8.2
0.4
V
V
Dropout Voltage
VDROP
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2
SC4614
POWER MANAGEMENT
Electrical Characteristics
Unless specified: VCC = 5V to 18V; VFB = VO; VBST - VPN = 5V to 8.2V; TA = -40 to 85°C
Parameter
Symbol
Conditions
Min
Typ
Max Units
Switching Regulator
Reference Voltage
Load Regulation
VREF
TA = 25°C, VCC = 12V
0.495 0.500 0.505
V
%
IO
= 0.2 to 4A
0.4
0.4
Line Regulation
V
CC = 10V to 14V
%
Operating Frequency
Ramp Amplitude (2)
Maximum Duty Cycle (2)
Minimum On-Time (2)
FS
400
500
0.8
97
600
kHz
V
Vm
DMAX
%
TON_MIN
tSRC_DH
tSINK_DH
tSRC_DL
tSINK_DL
125
41
ns
6V Swing at C
L
= 3.3nF
DH Rising/Falling Time
DL Rising/Falling Time
ns
ns
V
BST-VPN = 8.2V
27
29
6V Swing at C = 3.3nF
L
VDRV = 8.2V
42
DH, DL Nonoverlapping Time
Soft Start Time
30
ns
TA = 25°C, VCC = 12V
1.5
ms
Voltage Error Amplifier
Input Offset Voltage (2)
Input Offset Current (2)
Open Loop Gain (2)
Unity Gain Bandwidth (2)
Output Source Current
Output Sink Current
Slew Rate (2)
2
mV
nA
40
80
10
0.9
0.9
1.2
dB
MHz
mA
mA
V/us
For CL=500pF Load
Notes:
(1) This device is ESD sensitive. Use of standard ESD handling precautions is required.
(2) Guaranteed by design, not tested in production.
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3
SC4614
POWER MANAGEMENT
Pin Configuration
Ordering Information
Part Numbers
SC4614MSTRT(1)(2)
SC4614EVB
Package
TOP VIEW
MSOP-10
BST
OCS
COMP
FB
1
2
3
4
5
10
9
8
7
6
DH
PN
DL
VCC
DRV
Note:
(1) Only available in tape and reel packaging. A reel
contains 2500 devices.
GND
(2) Lead free product. This product is fully WEEE and
RoHS compliant.
Pin Descriptions
Pin #
Pin Name
Pin Function
1
BST
OCS
Boost input for top gate drive bias.
Current limit setting. Connect resistors from this pin to DRV pin and to ground to program
the trip point of load current. Refer to Applications Information Section for details.
2
3
4
5
COMP
FB
Error amplifier output for compensation.
Voltage feed back of sychronous buck converter.
Chip ground.
GND
Internal LDO output. Connect a 1uF ceramic capasitor from this pin to ground for
decoupling. This voltage is used for chip bias, including gate drivers.
6
DRV
Chip input power supply.
7
8
VCC
DL
Gate drive for bottom MOSFET.
9
PN
Phase node. Connect this pin to bottom N-MOSFET drain.
Gate drive for top MOSFET.
10
DH
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SC4614
POWER MANAGEMENT
Block Diagram
8.2V
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5
SC4614
POWER MANAGEMENT
Applications Information
THEORY OF OPERATION
To program a load trip point for short circuit protection, it
is recommended to connect a 3.3k resistor from the OCS
pin to the ground, and a resistor Rset from the OCS pin to
the DRV pin, as shown in Fig. 1.
The SC4614 is a high-speed, voltage mode PWM con-
troller that provides the control and protection features
necessary for a synchronous buck converter.
As shown in the block diagram of the SC4614, the volt-
age-mode PWM controller consists of an error amplifier,
a 500kHz ramp generator, a PWM comparator, a RS latch
circuit, and two MOSFET drivers. The buck converter out-
put voltage is fed back to the error amplifier negative
input and is regulated to a reference voltage level. The
error amplifier output is compared with the ramp to gen-
erate a PWM wave, which is amplified and used to drive
the MOSFETs in the buck converter. The PWM wave at
the phase node with the amplitude of Vin is filtered out
to get a DC output. The PWM controller works with soft-
start and fault monitoring circuitry to meet application
requirements.
12V
7
VCC
6
DRV
Rset
2
OCS
SC4614
3.3k
GND
5
UVLO, Start Up and Shut Down
Fig. 1. Programming load trip point
To initiate the SC4614, a supply voltage is applied to the
Vcc pin. The top gate (DH) and bottom gate (DL) are held
low until Vcc voltage exceeds UVLO (Under Voltage Lock
Out) threshold, typically 4.0V. Then the internal Soft-Start
(SS) capacitor begins to charge, the top gate remains
low, and the bottom gate is pulled high to turn on the
bottom MOSFET. When the SS voltage at the capacitor
reaches 0.4V, the top and bottom gates of PWM control-
ler begin to switch. The switching regulator output is slowly
ramping up for a soft turn-on.
350
325
300
275
250
225
200
175
150
If the supply voltages at the Vcc pin falls below UVLO
threshold during a normal operation, the SS capacitor
begins to discharge. When the SS voltage reaches 0.4V,
the PWM controller controls the switching regulator out-
put to ramp down slowly for a soft turn-off.
0
100
200
300
400
500
600
Rset (k-ohm)
Hiccup Mode Short Circuit Protection
Fig. 2. Pull up resistor (Rset) vs. trip voltage Vpn
The SC4614 uses low-side MOSFET Rdson sensing for
over current protection. In every switching cycle, after
the bottom MOSFET is on for 150ns, the SC4614 de-
tects the phase node voltage and compares it with an
internal setting voltage. If the phase node is lower than
the setting voltage, an overcurrent condition occurs. The
SC4614 will discharge the internal SS capacitor and shut-
down both outputs. After waiting for around 10 millisec-
onds, the SC4614 begins to charge the SS capacitor
again and initiates a fresh startup. The startup and shut-
down cycle will repeat until the short circuit is removed.
This is called a hiccup mode short circuit protection.
The resistor Rset can be found in Fig. 2 for a given phase
node voltage Vpn at the load trip point. This voltage is
the product of the inductor peak current at the load trip
point and the Rdson of the low-side MOSFET:
Vpn ꢀ I peak P Rds _on
The soft start time of the SC4614 is fixed at around
1.5ms. Therefore, the maximum soft start current is de-
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SC4614
POWER MANAGEMENT
Applications Information (Cont.)
duction losses of the top and bottom MOSFETs are given
by:
termined by the output inductance and output capaci-
tance. The values of output inductor and output bulk
capacitors have to be properly selected so that the soft
start peak current does not exceed the load trip point of
the short circuit protection.
P
ꢁ IO2 ꢀRdson ꢀD
C _TOP
P
ꢂ IO2 ꢁRdson ꢁ(1ꢀ D)
Internal LDO for Gate Drive
C _ BOT
An internal LDO is designed in the SC4614 to lower the
12V supply voltage for gate drive. A 1uF external ce-
ramic capacitor connected in between DRV pin to the
ground is needed to support the LDO. The LDO output is
connected to the low gate drive internally, and has to be
connected to the high gate drive through an external
bootstrap circuit. The LDO output voltage is set at 8.2V.
The manufacture data and bench tested results show
that, for low Rdson MOSFETs run at applied load current,
the optimum gate drive voltage is around 8.2V, where
the total power losses of power MOSFETs are minimized.
If the requirement of total power losses for each MOSFET
is given, the above equations can be used to calculate
the values of Rdson and gate charge, then the devices
can be determined accordingly. The solution should en-
sure the MOSFET is within its maximum junction tem-
perature at highest ambient temperature.
Output Capacitor
The output capacitors should be selected to meet both
output ripple and transient response criteria. The output
capacitor ESR causes output ripple VRIPPLE during the
inductor ripple current flowing in. To meet output ripple
criteria, the ESR value should be:
COMPONENT SELECTION
Lꢁ fOSC ꢁVRIPPLE
General design guideline of switching power supplies can
be applied to the component selection for the SC4614.
RESR
ꢂ
VO
VO ꢁ(1ꢀ
)
VIN
Inductor and MOSFETs
The selection of inductor and MOSFETs should meet ther-
mal requirements because they are power loss dominant
components. Pick an inductor with as high inductance
as possible without adding extra cost and size. The higher
inductance, the lower ripple current, the smaller core loss
and the higher efficiency will be. However, too high in-
ductance slows down output transient response. It is rec-
ommended to choose the inductance that creates an
inductor ripple current of approximate 20% of maximum
load current. So choose inductor value from:
The output capacitor ESR also causes output voltage tran-
sient VT during a transient load current IT flowing in. To
meet output transient criteria, the ESR value should be:
VT
IT
RESR
ꢀ
To meet both criteria, the smaller one of above two ESRs
is required.
The output capacitor value also contributes to load tran-
sient response. Based on a worst case where the induc-
tor energy 100% dumps to the output capacitor during
the load transient, the capacitance then can be calcu-
lated by:
5
VO
VIN
L ꢂ
ꢁVO ꢁ(1ꢀ
)
IO ꢁ fosc
The MOSFETs are selected by their Rdson, gate charge,
and package specifications. The SC4614 provides 1.5A
gate drive current and gives 50nC/1.5A=33ns switching
time for driving a 50nC gate charge MOSFET. The switch-
ing time ts contributes to the top MOSFET switching loss:
IT2
C ꢁ Lꢀ
VT2
P ꢁ IO ꢀVIN ꢀtS ꢀ fOSC
S
Input Capacitor
The input capacitor should be chosen to handle the RMS
ripple current of a synchronous buck converter. This value
There is no significant switching loss for the bottom
MOSFET because of its zero voltage switching. The con-
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SC4614
POWER MANAGEMENT
Applications Information (Cont.)
is given by:
SC4614AND MOSFETS
Vc
IRMS ꢃ (1ꢀ D)ꢁ II2N ꢂ Dꢁ(Io ꢀ IIN )2
REF
+
-
PWM
MODULATOR
EA
FB
L
Vo
where Io is the load current, IIN is the input average cur-
rent, and D is the duty cycle. Choosing low ESR input
capacitors will help maximize ripple rating for a given size.
OUT
COMP
Zf
Co
Bootstrap Circuit
Zs
Resr
The SC4614 uses an external bootstrap circuit to pro-
vide a voltage at the BST pin for the top MOSFET drive.
This voltage, referring to the Phase Node, is held up by a
bootstrap capacitor. Typically, it is recommended to use
a 1uF ceramic capacitor with 16V rating and a commonly
available diode IN4148 for the bootstrap circuit.
Fig. 3. Block diagram of the control loop
Filters for Supply Power
For each pin of DRV and Vcc, it is recommended to use a
1uF/16V ceramic capacitor for decoupling. In addition,
place a small resistor (10 ohm) in between the Vcc pin
and the supply power for noise reduction.
The model is a second order system with a finite DC gain,
a complex pole pair at Fo, and an ESR zero at Fz, as
shown in Fig. 4. The locations of the poles and zero are
determined by:
CONTROL LOOP DESIGN
1
LC
FO ꢀ
The goal of compensation is to shape the frequency re-
sponse charateristics of the buck converter to achieve a
better DC accuracy and a faster transient response for
the output voltage, while maintaining the loop stability.
1
FZ ꢀ
RESRC
The block diagram in Fig. 3 represents the control loop
of a buck converter designed with the SC4614. The con-
trol loop consists of a compensator, a PWM modulator,
and a LC filter.
The compensator in Fig. 3 includes an error amplifier and
impedance networks Zf and Zs. It is implemented by the
circuit in Fig. 5. The compensator provides an integrator,
double poles and double zeros. As shown in Fig. 4, the
The LC filter and PWM modulator represent the small integrator is used to boost the gain at low frequency.
signal model of the buck converter operating at fixed Two zeros are introduced to compensate excessive phase
switching frequency. The transfer function of the model lag at the loop gain crossover due to the integrator
is given by:
(-90deg) and complex pole pair (-180deg). Two high fre-
quency poles are designed to compensate the ESR zero
and attenuate high frequency noise.
VO VIN
1ꢀ sRESRC
ꢂ
ꢁ
VC Vm 1ꢀ sL/ R ꢀ s2LC
where VIN is the power rail voltage, Vm is the amplitude
of the 500kHz ramp, and R is the equivalent load.
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SC4614
POWER MANAGEMENT
Applications Information (Cont.)
(2). Select the open loop crossover frequency Fc located
at 10% to 20% of the switching frequency. At Fc, find the
required DC gain.
60
Fp1
Fz
Fp2
COMPENSATOR GAIN
(3). Use the first compensator pole Fp1 to cancel the
ESR zero Fz.
30
0
Fz1
Fz2
(4). Have the second compensator pole Fp2 at half the
switching frequency to attenuate the switching ripple and
high frequency noise.
Fo
Fc
-30
-60
(5). Place the first compensator zero Fz1 at or below
50% of the power stage resonant frequency Fo.
(6). Place the second compensator zero Fz2 at or below
the power stage resonant frequency Fo.
100
1K
10K
FREQUENCY (Hz)
100K
1M
A MathCAD program is available upon request for the
calculation of the compensation parameters.
Fig. 4. Bode plots for control loop design
LAYOUT GUIDELINES
C2
The switching regulator is a high di/dt power circuit. Its
Printed Circuit Board (PCB) layout is critical. A good lay-
out can achieve an optimum circuit performance while
minimizing the component stress, resulting in better sys-
tem reliability. During PCB layout, the SC4614 controller,
MOSFETs, inductor, and power decoupling capacitors have
to be considered as a unit.
C1
R2
C3
R3
Vo
Vc
-
+
2
1
3
Rtop
Rb ot
VREF
0.5V
The following guidelines are typically recommended for
using the SC4614 controller.
(1). Place a 4.7uF to 10uF ceramic capacitor close to
the drain of top MOSFET for the high frequency and high
current decoupling. The loop formed by the capacitor,
the top and bottom MOSFETs must be as small as pos-
sible. Keep the input bulk capacitors close to the drain
of the top MOSFETs.
Fig. 5. Compensation network
The top resistor Rtop of the voltage divider in Fig. 5 can
be chosen from 1k to 5k. Then the bottom resistor Rbot
is found from:
(2). Place the SC4614 over a quiet ground plane to avoid
pulsing current noise. Keep the ground return of the gate
drive short.
0.5V
VO ꢁ 0.5V
Rbot
ꢂ
ꢀ Rtop
(3). Connect bypass capacitors as close as possible to
the decoupling pins (DRV and Vcc) to the ground pin GND.
The trace length of the decoupling capacitor on DRV pin
should be no more than 0.2” (5mm).
where 0.5V is the internal reference voltage of the
SC4614.
(4). Locate the components of the bootstrap circuit close
to the SC4614.
The other components of the compensator can be cal-
culated using following design procedure:
(1). Plot the converter gain, including LC filter and PWM
modulator.
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SC4614
POWER MANAGEMENT
Applications Information (Cont.)
Typical Application Schematics with 12V Input
12V
Rcc
2R2
C4
+
C3
10uF
Q1
IPD05N03
1uF
1800uF
Rli mit
3.3k
R4
0
499k
C15
D1
U1
0
1.5V/15A
L1
1
2
3
4
5
10
9
1
2
BST
OC S
COMP
FB
DH
PN
D1N4148
1.2uH
R8
R12
301
+
C5
C7
8
R11
1R0
14. 7k
DL
Q3
IPD05N03
C9
1800uF
10uF
+
C6
7
2.2nF
VCC
DRV
6
1800uF
GN D
C18
1uF
C17
1uF
C13
0
2.2nF
R15
SC4614
0
C8
7.32k
10nF
C10
680pF
R13
0
11.5k
Bill of Materials (12V Input)
Item
1
2
3
4
5
6
7
8
Quantity Reference
Part
10uF/16V
10uF/6.3V
1800uF/16V
1800uF/6.3V
1uF
2.2nF
2.2nF
10nF
680pF
D1N4148
1.2uH
IPD05N03
2R2
3.3k
499k
301
1R0
Vendor
Vishay
Vishay
Rubycon, MBZ
Rubycon, MBZ
Vishay
Vishay
Vishay
Vishay
Vishay
1
1
1
2
3
1
1
1
1
1
1
2
1
1
1
1
1
1
1
1
1
C4
C7
C3
C5,C6
C15,C17,C18
C9
C13
C8
C10
D1
L1
Q3,Q1
Rcc
Rlimit
R4
9
10
11
12
13
14
15
16
17
18
19
20
21
Any
Cooper Electr. Tech
Infineon
Vishay
Vishay
Vishay
Vishay
Vishay
Vishay
Vishay
R8
R11
R12
R15
R13
U1
14.7k
7.32k
11.5k
SC4614
Vishay
SEMTECH
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10
SC4614
POWER MANAGEMENT
Applications Information (Cont.)
Performance Characteristics (12V Input)
Start up
Efficiency (%) vs Load Current
90
85
80
75
70
65
60
12V Input (5V/DIV)
1.5V Output (1V/DIV)
1
3
5
7
9
11
13
15
X=5ms/DIV
Load Current (A)
Transient Response
Load Characteristics (Output vs Load Current)
1.6
1.4
1.2
1.0
1.5V Output Response (100mV/DIV)
0.8
0.6
0.4
0.2
0.0
Step Load Current (10A/DIV)
0
5
10
15
20
X=20us/DIV
Load Current(A)
Gate Waveforms (Io=15A)
Short Circuit Protection
Output Short
DL (10V/DIV)
DH (10V/DIV)
1.5V OUT (1V/DIV)
PN (10V/DIV)
Output Current (10A/DIV)
X=5ms/DIV
X=50ns/DIV
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SC4614
POWER MANAGEMENT
Applications Information (Cont.)
Typical Application Schematics with 25V Input
Vin=25V
Rcc
C4
+
C3
732
10uF
Q1
IRLR7821
1uF
1800uF
Rli mit
3.3k
R4
0
499k
C15
D1
U1
5V/10A
0
L1
1
2
3
4
5
10
9
1
2
BST
OC S
COMP
FB
DH
PN
D1N4148
2.2uH
R8
R12
22k
301
C7
8
R11
1R 0
DL
Q3
IRLR7821
C9
10uF
7
2.2nF
+
C6
VCC
DR V
6
1800uF
GN D
C17
1uF
C13
0
2.2nF
R15
SC4614
0
C8
C18
1uF
2.43k
4.7nF
C10
1nF
R13
22k
D2
BZX84B16LT1
0
0
Note: Zener diode D2 is required when Vin is18V or higher.
Bill of Materials (25V Input)
Item
1
2
3
4
5
6
7
8
Quantity Reference
Part
Vendor
Murata
Vishay
Rubycon
Rubycon, MBZ
Vishay
Vishay
Vishay
Vishay
Vishay
1
1
1
1
3
1
1
1
1
1
1
1
2
1
1
1
1
1
1
1
1
1
C4
C7
C3
C6
10uF/35V
10uF/6.3V
1800uF/35V
1500uF/6.3V
1uF
2.2nF
2.2nF
4.7nF
1nF
D1N4148
BZX84B16LT1
2.2uH
IRLR7821
732
3.3k
499k
301
1R0
C15,C17,C18
C9
C13
C8
C10
D1
D2
9
10
11
12
13
14
15
16
17
18
19
20
21
22
Any
ON Semi
Cooper Electr. Tech
IR
Vishay
Vishay
Vishay
Vishay
Vishay
Vishay
L1
Q3,Q1
Rcc
Rlimit
R4
R8
R11
R12
R15
R13
U1
22k
2.43k
22k
SC4614
Vishay
Vishay
SEMTECH
www.semtech.com
2005 Semtech Corp.
12
SC4614
POWER MANAGEMENT
Applications Information (Cont.)
Performance Characteristics (25V Input)
Start up
Efficiency (%) vs Load Current
92
90
88
86
25V Input (10V/DIV)
5V Output (2V/DIV)
84
82
80
78
76
1
2
3
4
5
6
7
8
9
10
X=5ms/DIV
Load Current (A)
Gate Waveforms (Io=10A)
Transient Response
5V Output Response (200mV/DIV)
DL (10V/DIV)
DH (10V/DIV)
PN (10V/DIV)
Step Load Current (10A/DIV)
X=100ns/DIV
X=20us/DIV
www.semtech.com
2005 Semtech Corp.
13
SC4614
POWER MANAGEMENT
Outline Drawing - MSOP-10
DIMENSIONS
INCHES MILLIMETERS
e
DIM
A
A
MIN NOM MAX MIN NOM MAX
D
E
-
-
-
-
-
-
-
-
-
-
-
-
.043
1.10
0.15
0.95
0.27
0.23
N
A1 .000
A2 .030
.006 0.00
.037 0.75
.011 0.17
.009 0.08
b
c
D
.007
.003
2X E/2
.114 .118 .122 2.90 3.00 3.10
E1
E1 .114 .118 .122 2.90 3.00 3.10
PIN 1
E
e
.193 BSC
.020 BSC
4.90 BSC
0.50 BSC
INDICATOR
L
L1
N
.016 .024 .032 0.40 0.60 0.80
ccc
C
1 2
(.037)
10
-
(.95)
10
-
2X N/2 TIPS
B
01
aaa
0°
8°
0°
8°
.004
.003
.010
0.10
0.08
0.25
bbb
ccc
D
aaa
C
H
A2
A
SEATING
PLANE
c
GAGE
A1
bxN
bbb
C
PLANE
C
A-B D
0.25
L
01
(L1)
DETAIL A
SEE DETAIL A
SIDE VIEW
NOTES:
1. CONTROLLING DIMENSIONS ARE IN MILLIMETERS (ANGLES IN DEGREES).
2. DATUMS -A- AND -B- TO BE DETERMINED AT DATUM PLANE -H-
3. DIMENSIONS "E1" AND "D" DO NOT INCLUDE MOLD FLASH, PROTRUSIONS
OR GATE BURRS.
4. REFERENCE JEDEC STD MO-187, VARIATION BA.
Land Pattern - MSOP-10
X
DIMENSIONS
DIM
INCHES
(.161)
.098
MILLIMETERS
(4.10)
2.50
0.50
0.30
1.60
5.70
C
G
P
X
Y
Z
(C)
G
Y
Z
.020
.011
.063
.224
P
NOTES:
1. THIS LAND PATTERN IS FOR REFERENCE PURPOSES ONLY.
CONSULT YOUR MANUFACTURING GROUP TO ENSURE YOUR
COMPANY'S MANUFACTURING GUIDELINES ARE MET.
Contact Information
Semtech Corporation
Power Management Products Division
200 Flynn Road, Camarillo, CA 93012
Phone: (805)498-2111 FAX (805)498-3804
www.semtech.com
2005 Semtech Corp.
14
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