TDA7296AV [STMICROELECTRONICS]

70V - 60W DMOS AUDIO AMPLIFIER WITH MUTE/ST-BY; 70V - 60W DMOS音频放大器,具有静音/ ST- BY
TDA7296AV
型号: TDA7296AV
厂家: ST    ST
描述:

70V - 60W DMOS AUDIO AMPLIFIER WITH MUTE/ST-BY
70V - 60W DMOS音频放大器,具有静音/ ST- BY

音频放大器
文件: 总13页 (文件大小:243K)
中文:  中文翻译
下载:  下载PDF数据表文档文件
TDA7296A  
70V - 60W DMOS AUDIO AMPLIFIER WITH MUTE/ST-BY  
PRODUCT PREVIEW  
VERY HIGH OPERATING VOLTAGE RANGE  
(±35V)  
MULTIPOWER BCD TECHNOLOGY  
DMOS POWER STAGE  
HIGH OUTPUT POWER (UP TO 60W MUSIC  
POWER)  
MUTING/STAND-BY FUNCTIONS  
NO SWITCH ON/OFF NOISE  
NO BOUCHEROT CELLS  
VERYLOW DISTORTION  
VERYLOW NOISE  
Multiwatt 15  
ORDERING NUMBER: TDA7296AV  
SHORT CIRCUIT PROTECTION  
THERMAL SHUTDOWN  
CLIPPING DETECTION OUTPUT  
even in presence of poor supply regulation, with  
high Supply Voltage Rejection.  
DESCRIPTION  
The built in muting function with turn on delay  
simplifies the remote operation avoiding switching  
on-off noises.  
The device provides a circuit for the detection of  
clipping in the output stages. The output, on open  
collector, is able to drive system with automatic  
level control.  
The TDA7296A is a monolithic integrated circuit  
in Multiwatt15 package, intended for use as audio  
class AB amplifier in Hi-Fi field applications  
(Home Stereo, self powered loudspeakers, Top-  
class TV). Thanks to the wide voltage range and  
to the high out current capability it is able to sup-  
ply the highest power into both 4and 8loads  
Figure 1: Typical Application and Test Circuit  
C7 100nF  
+Vs C6 1000µF  
R3 22K  
+Vs  
7
+PWVs  
13  
C2  
22µF  
R2  
680Ω  
IN-  
2
3
-
14  
OUT  
C1 470nF  
IN+  
+
C5  
22µF  
R1 22K  
CD  
6
5
IN+MUTE  
4
BOOTSTRAP  
R5 10K MUTE  
STBY  
10  
9
+5V  
VM  
MUTE  
STBY  
1
THERMAL  
SHUTDOWN  
S/C  
PROTECTION  
15  
-PWVs  
VSTBY  
R4 22K  
8
STBY-GND  
-Vs  
C3 10µF  
C4 10µF  
C9 100nF  
C8 1000µF  
D96AU494  
-Vs  
June 1996  
1/13  
This is preliminary information on a new product now in development. Details are subject to change without notice.  
TDA7296A  
PIN CONNECTION (Topview)  
15  
14  
13  
12  
11  
10  
9
-VS (POWER)  
OUT  
+VS (POWER)  
N.C.  
N.C.  
MUTE  
STAND-BY  
-VS (SIGNAL)  
+VS (SIGNAL)  
BOOTSTRAP  
CD  
8
7
6
5
4
SVR  
3
NON INVERTING INPUT  
INVERTING INPUT  
STAND-BY GND  
2
1
D96AU495  
BLOCK DIAGRAM  
BOOTSTRAP  
+VS  
+
-
+
BOOTSTRAP  
IN+  
IN-  
OUTPUT  
CD  
CD  
+
-
+
-VS  
BIPOLAR  
TRANSCONDUCTANCE  
INPUT STAGE  
MOS GAIN &  
LEVEL SHIFTING  
STAGE  
MOS OUTPUT STAGE  
SHORT CIRCUIT  
PROTECTION  
D96AU496  
ABSOLUTE MAXIMUM RATINGS  
Symbol  
Parameter  
Value  
Unit  
V
VS  
IO  
Supply Voltage  
35  
5
±
Output Peak Current  
A
Ptot  
Power Dissipation Tcase = 70°C  
50  
W
Top  
Operating Ambient Temperature Range  
Storage and Junction Temperature  
0 to 70  
150  
C
C
°
°
Tstg, Tj  
2/13  
TDA7296A  
THERMAL DATA  
Symbol  
Description  
Thermal Resistance Junction-case  
Value  
1.5  
Unit  
C/W  
Rth j-case  
Max  
°
ELECTRICAL CHARACTERISTICS  
(Refer to the Test Circuit VS = ±24V, RL = 8, GV = 30dB;  
Rg = 50 ; Tamb = 25°C, f = 1 kHz; unless otherwise specified.  
Symbol  
VS  
Parameter  
Operating Supply Range  
Quiescent Current  
Test Condition  
Min.  
±10  
20  
Typ.  
Max.  
±35  
60  
Unit  
V
Iq  
30  
mA  
nA  
Ib  
Input Bias Current  
500  
+10  
+100  
VOS  
IOS  
Input Offset Voltage  
mV  
nA  
Input Offset Current  
PO  
RMS Continuous Output Power  
d = 0.5%:  
V = 24V, R = 8  
27  
27  
27  
30  
30  
30  
W
W
W
±
S
L
VS = ± 21V, RL = 6Ω  
ςS = ± 18V, RL = 4Ω  
Music Power (RMS) (*)  
d = 10%;  
t = 1s  
R = 8 ; V = 29V  
60  
60  
60  
W
W
W
±
L
S
RL = 6  
; VS = ±24V  
R = 4 ; V = 22V  
±
L
S
d
Total Harmonic Distortion (**)  
P
P
O = 5W; f = 1kHz  
O = 0.1to 20W; f = 20Hz to 20kHz  
0.005  
%
%
0.1  
0.1  
V = 18V, R = 4  
Ω:  
P
P
±
S
L
O = 5W; f = 1kHz  
O = 0.1to 20W; f = 20Hz to 20kHz  
0.01  
%
%
SR  
GV  
GV  
eN  
Slew Rate  
7
10  
80  
30  
V/µs  
dB  
Open Loop Voltage Gain  
Closed Loop Voltage Gain  
Total Input Noise  
24  
40  
5
dB  
A = curve  
f = 20Hz to 20kHz  
1
2
µV  
V
µ
fL, fH  
Ri  
Frequency Response (-3dB)  
Input Resistance  
PO = 1W  
20Hz to 20kHz  
100  
60  
kΩ  
SVR  
TS  
Supply Voltage Rejection  
Thermal Shutdown  
f = 100Hz; Vripple = 0.5Vrms  
75  
dB  
145  
C
°
STAND-BY FUNCTION (Ref: -VS or GND)  
VST on  
VST off  
Stand-by on Threshold  
Stand-by off Threshold  
1.5  
V
3.5  
70  
V
ATTst-by Stand-by Attenuation  
90  
dB  
mA  
Iq st-by  
Quiescent Current @ Stand-by  
1
3
MUTE FUNCTION (Ref: -VS or GND)  
VMon  
VMoff  
Mute on Threshold  
Mute off Threshold  
1.5  
V
V
3.5  
60  
ATTmute Mute AttenuatIon  
80  
dB  
%
DC Off  
Clipping detector OFF.  
CD output Duty Cycle  
THD = 1%  
TBD  
DC On  
Clipping detector On.  
CD output Duty Cycle  
THD = 10%  
TBD  
%
Note (*):  
MUSIC POWER is the maximal power which the amplifieris capableof producing across the rated load resistance (regardless of non linearity)  
1 sec after the application of a sinusoidal input signal of frequency 1KHz.  
Note (**): Tested with optimized Application Board (see fig. 2)  
3/13  
TDA7296A  
Figure 2:  
P.C.B. and components layout of the circuit of figure 1. (1:1 scale)  
TDA7296A  
Note:  
The Stand-by and Mute functions can be referred either to GND or -VS.  
On the P.C.B. is possible to set both the configuration through the jumper J1.  
4/13  
TDA7296A  
APPLICATION SUGGESTIONS (seeTest and Application Circuits of the Fig. 1)  
The recommended values of the external components are those shown on the application circuit of Fig-  
ure 1. Different values can be used; the following table can help the designer.  
LARGER THAN  
SUGGESTED  
SMALLER THAN  
SUGGESTED  
COMPONENTS  
SUGGESTED VALUE  
PURPOSE  
R1 (*)  
22k  
INPUT RESISTANCE  
INCREASE INPUT  
IMPRDANCE  
DECREASE INPUT  
IMPEDANCE  
R2  
R3 (*)  
R4  
680  
CLOSED LOOP GAIN DECREASE OF GAIN INCREASE OF GAIN  
SET TO 30dB (**)  
22k  
22k  
INCREASE OF GAIN DECREASE OF GAIN  
ST-BY TIME  
CONSTANT  
LARGER ST-BY  
ON/OFF TIME  
SMALLER ST-BY  
ON/OFF TIME;  
POP NOISE  
R5  
C1  
10k  
MUTE TIME  
CONSTANT  
LARGER MUTE  
ON/OFF TIME  
SMALLER MUTE  
ON/OFF TIME  
0.47 F  
INPUT DC  
DECOUPLING  
HIGHER LOW  
FREQUENCY  
CUTOFF  
µ
C2  
22µF  
FEEDBACK DC  
DECOUPLING  
HIGHER LOW  
FREQUENCY  
CUTOFF  
C3  
C4  
10 F  
MUTE TIME  
CONSTANT  
LARGER MUTE  
ON/OFF TIME  
SMALLER MUTE  
ON/OFF TIME  
µ
10µF  
ST-BY TIME  
CONSTANT  
LARGER ST-BY  
ON/OFF TIME  
SMALLER ST-BY  
ON/OFF TIME;  
POP NOISE  
C5  
22 F  
µ
BOOTSTRAPPING  
SIGNAL  
DEGRADATION AT  
LOW FREQUENCY  
C6, C8  
1000 F  
SUPPLY VOLTAGE  
BYPASS  
DANGER OF  
OSCILLATION  
µ
C7, C9  
0.1 F  
SUPPLY VOLTAGE  
BYPASS  
DANGER OF  
OSCILLATION  
µ
(*) R1 = R3 FOR POP OPTIMIZATION  
(**) CLOSED LOOP GAIN HAS TO BE 24dB  
5/13  
TDA7296A  
TYPICAL CHARACTERISTICS  
(Application Circuit of fig 1 unless otherwise specified)  
Figure 3:  
Figure 4:  
Distortion vs. Output Power  
Output Power vs. Supply Voltage.  
Figure 5: Output Power vs. Supply Voltage  
Figure 6: Distortion vs. Output Power  
Figure 8: Distortion vs. Frequency  
Figure 7: Distortion vs. Frequency  
6/13  
TDA7296A  
TYPICAL CHARACTERISTICS (continued)  
Figure 9:  
Figure10:  
SupplyVoltageRejectionvs.Frequency  
QuiescentCurrent vs. Supply Voltage  
Figure 11:  
MuteAttenuationvs. Vpin10  
Figure 12: St-byAttenuation vs. Vpin9  
Figure 14:  
PowerDissipation vs. Output Power  
Figure 13: Power Dissipation vs. OutputPower  
7/13  
TDA7296A  
monic distortion and good behaviour over fre-  
quency response; moreover, an accurate control  
of quiescent current is required.  
A local linearizing feedback, provided by differen-  
tial amplifier A, is used to fullfil the above require-  
ments, allowing a simple and effective quiescent  
current setting.  
Proper biasing of the power output transistors  
alone is however not enough to guarantee the ab-  
sence of crossover distortion.  
While a linearization of the DC transfer charac-  
teristic of the stage is obtained, the dynamic be-  
haviour of the system must be taken into account.  
INTRODUCTION  
In consumer electronics, an increasing demand  
has arisen for very high power monolithic audio  
amplifiers able to match, with a low cost the per-  
formance obtained from the best discrete de-  
signs.  
The task of realizing this linear integrated circuit  
in conventional bipolar technology is made ex-  
tremely difficult by the occurence of 2nd break-  
down phenomenon. It limits the safe operating  
area (SOA) of the power devices, and as a con-  
sequence, the maximum attainable output power,  
especially in presence of highly reactive loads.  
Moreover, full exploitation of the SOA translates  
into a substantial increase in circuit and layout  
complexity due to the need for sophisticated pro-  
tection circuits.  
To overcome these substantial drawbacks, the  
use of power MOS devices, which are immune  
from secondarybreakdown is highly desirable.  
A significant aid in keeping the distortion contrib-  
uted by the final stage as low as possible is pro-  
vided by the compensation scheme, which ex-  
ploits the direct connection of the Miller capacitor  
at the amplifier’s output to introduce a local AC  
feedback path enclosing the output stage itself.  
2) Protections  
The device described has therefore been devel-  
oped in a mixed bipolar-MOS high voltage tech-  
nology called BCD 80.  
In designing a power IC, particular attention must  
be reserved to the circuits devoted to protection  
of the device from short circuit or overload condi-  
tions.  
1) Output Stage  
Due to the absence of the 2nd breakdown phe-  
nomenon, the SOA of the power DMOS transis-  
tors is delimited only by a maximum dissipation  
curve dependent on the duration of the applied  
stimulus.  
In order to fully exploit the capabilities of the  
power transistors, the protection scheme imple-  
mented in this device combines a conventional  
SOA protection circuit with a novel local tempera-  
ture sensing technique which ” dynamically” con-  
trols the maximumdissipation.  
The main design task one is confrontedwith while  
developing an integrated circuit as a power op-  
erational amplifier, independently of the technol-  
ogy used, is that of realising the output stage.  
The solution shown as a principle schematic by  
Fig 15 represents the DMOS unity-gain output  
buffer of the TDA7296A.  
This large-signal, high-power buffer must be ca-  
pable of handling extremely high current and volt-  
age levels while maintaining acceptably low har-  
Figure 15: PrincipleSchematic of a DMOS unity-gain buffer.  
8/13  
TDA7296A  
Figure 16: Turn ON/OFF SuggestedSequence  
+Vs  
(V)  
+35  
-35  
-Vs  
V
(mV)  
IN  
V
ST-BY  
5V  
5V  
PIN #9  
(V)  
V
MUTE  
PIN #10  
(V)  
I
P
(mA)  
V
OUT  
(V)  
OFF  
ST-BY  
PLAY  
ST-BY  
OFF  
MUTE  
MUTE  
D93AU013  
Tj = 150 oC).  
Full protection against electrostatic discharges on  
every pin is included.  
In addition to the overload protection described  
above, the device features a thermal shutdown  
circuit which initially puts the device into a muting  
state (@ Tj = 145 oC) and then into stand-by (@  
3) Other Features  
Figure 17:  
SingleSignal ST-BY/MUTE Control  
Circuit  
The device is provided with both stand-by and  
mute functions, independently driven by two  
CMOS logic compatible input pins.  
The circuits dedicated to the switching on and off  
of the amplifier have been carefully optimized to  
avoid any kind of uncontrolledaudible transient at  
the output.  
The sequence that we recommend during the  
ON/OFF transients is shown by Figure 16.  
MUTE  
STBY  
20K  
30K  
MUTE/  
ST-BY  
10K  
The application of figure 17 shows the possibility  
of using only one command for both st-by and  
mute functions. On both the pins, the maximum  
applicable range corresponds to the operating  
supply voltage.  
10µF  
10µF  
1N4148  
D93AU014  
9/13  
TDA7296A  
4) Clipping Detector Output  
BRIDGE APPLICATION  
The TDA7296A is equipped with an internal cir-  
cuit able to detect the output stage saturation pro-  
viding a proper current sinking into on open col-  
lector output (pin 5) when a certain distortion level  
is reachedat output.  
This particular function allows gain compression  
facility whenever the amplifier is overdriven, thus  
obtaining high quality sound all listening levels.  
Another application suggestion is the BRIDGE  
configuration, where two TDA7296A are used, as  
shown by the schematic diagram of figure 19.  
In this application, the value of the load must not  
be lower than 8 Ohm for dissipation and current  
capability reasons.  
A suitable field of application includes HI-FI/TV  
subwoofersrealizations.  
The main advantagesoffered by this solution are:  
Figure 18:  
Clipping Detector Output Waveform  
- High power performanceswith limited supply  
voltage level.  
VO  
- Considerablyhigh output power even with high  
load values (i.e. 16 Ohm).  
OUTPUT  
SIGNAL  
The characteristics shown by figures 21 and 22,  
measured with loads respectively 8 Ohm and 16  
Ohm.  
With Rl= 8 Ohm, Vs = ±18V the maximum output  
power obtainable is 60W, while with Rl=16 Ohm,  
Vs = ±24V the maximumPout is 60W.  
ICLIP  
S96AU498  
t
Figure 19: Bridge Application Circuit  
+Vs  
0.22µF  
2200µF  
7
13  
6
3
22µF  
22K  
Vi  
+
-
14  
0.56µF  
22K  
1
4
2
680  
ST-BY/MUTE  
20K  
10  
9
15  
8
22K  
22µF  
-Vs  
0.22µF  
2200µF  
1N4148  
9
15  
8
10  
3
10K  
30K  
22µF  
6
22µF  
+
-
14  
0.56µF  
22K  
22K  
680  
1
4
2
7
13  
D96AU497  
10/13  
TDA7296A  
Figure 21: Distortion vs. Output Power  
Figure 20:  
FrequencyResponse of the Bridge  
Application  
Figure 22: Distortionvs. Output Power  
11/13  
TDA7296A  
MULTIWATT15 PACKAGE MECHANICAL DATA  
mm  
inch  
TYP.  
DIM.  
MIN.  
TYP.  
MAX.  
5
MIN.  
MAX.  
0.197  
0.104  
0.063  
A
B
2.65  
1.6  
C
D
1
0.039  
E
0.49  
0.66  
1.14  
17.57  
19.6  
0.55  
0.75  
1.4  
0.019  
0.026  
0.045  
0.692  
0.772  
0.022  
0.030  
0.055  
0.705  
F
G
1.27  
0.050  
0.700  
G1  
H1  
H2  
L
17.78  
17.91  
20.2  
22.6  
22.5  
18.1  
17.75  
10.9  
2.9  
0.795  
0.890  
0.886  
0.713  
0.699  
0.429  
0.114  
0.181  
0.209  
0.102  
0.102  
0.152  
22.1  
22  
0.870  
0.866  
0.695  
0.679  
0.406  
0.104  
0.165  
0.177  
0.075  
0.075  
0.144  
L1  
L2  
L3  
L4  
L7  
M
17.65  
17.25  
10.3  
2.65  
4.2  
17.5  
10.7  
0.689  
0.421  
4.3  
4.6  
0.169  
0.200  
M1  
S
4.5  
5.08  
5.3  
1.9  
2.6  
S1  
Dia1  
1.9  
2.6  
3.65  
3.85  
12/13  
TDA7296A  
Information furnished is believed to be accurate and reliable. However, SGS-THOMSON Microelectronics assumes no responsibility for the  
consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No  
license is granted by implication or otherwise under any patent or patent rights of SGS-THOMSON Microelectronics. Specification mentioned  
in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. SGS-  
THOMSON Microelectronics products are not authorized for use as critical components in life support devices or systems without express  
written approval of SGS-THOMSON Microelectronics.  
1996 SGS-THOMSON Microelectronics – Printed in Italy – All Rights Reserved  
SGS-THOMSON Microelectronics GROUP OF COMPANIES  
Australia - Brazil - Canada - China - France - Germany - Hong Kong - Italy - Japan - Korea - Malaysia - Malta - Morocco - The Netherlands -  
Singapore - Spain - Sweden - Switzerland - Taiwan - Thailand - United Kingdom - U.S.A.  
13/13  

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