TSM1051L [STMICROELECTRONICS]
CONSTANT VOLTAGE AND CONSTANT CURRENT CONTROLLER FOR BATTERY CHARGERS AND ADAPTORS; 恒定电压和恒定电流控制器电池充电器和适配器型号: | TSM1051L |
厂家: | ST |
描述: | CONSTANT VOLTAGE AND CONSTANT CURRENT CONTROLLER FOR BATTERY CHARGERS AND ADAPTORS |
文件: | 总9页 (文件大小:111K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
TSM1051
CONSTANT VOLTAGE AND CONSTANT CURRENT
CONTROLLER FOR BATTERY CHARGERS AND ADAPTORS
■ CONSTANT VOLTAGE AND CONSTANT
ORDER CODE
Part Number
CURRENT CONTROL
Package
Temperature
Range
■ LOW VOLTAGE OPERATION
Marking
■ PRECISION INTERNAL VOLTAGE
L
D
REFERENCE
TSM1051CLT
0 to 85°C
0 to 85°C
•
M801
■ LOW EXTERNAL COMPONENT COUNT
■ CURRENT SINK OUTPUT STAGE
■ EASY COMPENSATION
TSM1051CD
•
M1051C
L = Tiny Package (SOT23-6) - only available in Tape & Reel (LT)
D = Small Outline Package (SO) - also available in Tape & Reel (DT)
■ LOW AC MAINS VOLTAGE REJECTION
DESCRIPTION
TSM1051 is a highly integrated solution for SMPS
applications requiring CV (constant voltage) and
CC (constant current) mode.
TSM1051 integrates one voltage reference, two
operational amplifiers (with ORed outputs -
common collectors), and a current sensing circuit.
The voltage reference combined with one
operational amplifier makes it an ideal voltage
controller, and the other low voltage reference
combined with the other operational amplifier
makes it an ideal current limiter for output low side
current sensing.
L
D
SO8
SOT23-6
(Plastic Package)
(Plastic Micro package)
The current threshold is fixed, and precise.
The only external components are:
PIN CONNECTIONS (top view)
* a resistor bridge to be connected to the output of
the power supply (adapter, battery charger) to set
the voltage regulation by dividing the desired
output voltage to match the internal voltage
reference value.
SOT23-6
SO8
* a sense resistor having a value and allowable
dissipation power which need to be chosen
according to the internal voltage threshold.
1
2
3
Vctrl
Vcc
6
5
4
1
2
3
4
Vctrl
Vcc
Gnd
Out
Ictrl
Nc
8
7
6
5
Gnd Vsense
* optional compensation components (R and C).
TSM1051, housed in one of the smallest package
available, is ideal for space shrinked applications
such as adapters and battery chargers.
Out
Ictrl
Vsense
Nc
APPLICATIONS
■ ADAPTERS
■ BATTERY CHARGERS
January 2002
1/9
TSM1051
PIN DESCRIPTION
SOT23-6 Pinout
Name
Pin #
Type
Function
Vcc
Gnd
6
2
1
4
3
5
Power Supply
Power Supply
Analog Input
Analog Input
Positive Power Supply Line
Ground Line. 0V Reference For All Voltages
Input Pin of the Voltage Control Loop
Input Pin of the Current Control Loop
Vctrl
Ictrl
Out
Current Sink Output Output Pin. Sinking Current Only
Vsense
Analog Input
Input Pin of the Current Control Loop
SO8 Pinout
Name
Pin #
Type
Function
Vcc
Gnd
Vctrl
Ictrl
2
8
1
6
7
3
5
4
Power Supply
Power Supply
Analog Input
Analog Input
Positive Power Supply Line
Ground Line. 0V Reference For All Voltages
Input Pin of the Voltage Control Loop
Input Pin of the Current Control Loop
Out
Current Sink Output Output Pin. Sinking Current Only
Analog Input Input Pin of the Current Control Loop
Vsense
NC
NC
ABSOLUTE MAXIMUM RATINGS
Symbol
DC Supply Voltage
Value
Unit
Vcc
Vi
DC Supply Voltage
Input Voltage
14
-0.3 to Vcc
0 to 85
150
V
V
Top
Tj
Operating Free Air Temperature Range
°C
Maximum Junction Temperature
°C
Rthja
Rthja
Thermal Resistance Junction to Ambient SO8 package
Thermal Resistance Junction to Ambient SOT23-6 package
130
°C/W
°C/W
250
2/9
TSM1051
OPERATING CONDITIONS
Symbol
Parameter
Value
Unit
Vcc
DC Supply Conditions
2.5 to 12
V
ELECTRICAL CHARACTERISTICS
Tamb = 25°C and Vcc = +5V (unless otherwise specified)
Symbol
Total Current Consumption
Icc Total Supply Current - not taking the
Parameter
Test Condition
Min
Typ
Max
Unit
Tamb
1.1
1.2
2
mA
output sinking current into account
0 < Tamb < 85°C
Voltage Control Loop
Gmv
Transconduction Gain (Vctrl). Sink
Current Only
Tamb
1
3.5
2.5
mA/mV
V
1)
0 < Tamb < 85°C
2)
Vref
Iibv
Tamb
0 < Tamb < 85°C
1.198
1.186
1.21
1.222
1.234
Voltage Control Loop Reference
Input Bias Current (Vctrl)
Tamb
0 < Tamb < 85°C
50
100
nA
Current Control Loop
Gmi
Transconduction Gain (Ictrl). Sink
Current Only
Tamb
1.5
7
mA/mV
mV
3)
0 < Tamb < 85°C
4)
Vsense
Iibi
Iout = 2.5mA Tamb
0 < Tamb < 85°C
196
192
200
204
208
Current Control Loop Reference
Current out of pin ICTRL at -200mV
Tamb
0 < Tamb < 85°C
25
50
µA
mV
mA
Output Stage
Vol
Low output voltage at 10 mA sinking
current
Tamb
0 < Tamb < 85°C
200
Ios
Output Short Circuit Current. Output to Tamb
Vcc. Sink Current Only 0 < Tamb < 85°C
27
35
50
1. If the voltage on VCTRL (the negative input of the amplifier) is higher than the positive amplifier input (Vref=1.210V), and it is increased
by 1mV, the sinking current at the output OUT will be increased by 3.5mA.
2. The internal Voltage Reference is set at 1.210V (bandgap reference). The voltage control loop precision takes into account the cumulative
effects of the internal voltage reference deviation as well as the input offset voltage of the trans-conductance operational amplifier. The
internal Voltage Reference is fixed by bandgap, and trimmed to 0.5% accuracy at room temperature.
3. When the positive input at ICTRL is lower than -200mV, and the voltage is decreased by 1mV, the sinking current at the output OUT will
be increased by 7mA.
4. The internal current sense threshold is set to -200mV. The current control loop precision takes into account the cumulative effects of the
internal voltage reference deviation as well as the input offset voltage of the trans-conduction operational amplifier.
3/9
TSM1051
Figure 1 : Internal Schematic
Vcc
1.210V
Out
+
-
+
-
200mV
Ictrl
Gnd
Vsense
Figure 2 : Typical Adapter or Battery Charger Application Using TSM1051
D
OUT+
To primary
R2
TSM1051
Vcc
Rout
IL
1.210V
Out
Cvc1
Rvc1
470K
+
-
Cvc2
22pF
2.2nF
Cic1
2.2nF
+
-
+
200mV
Ictrl
Gnd
Ric1
22K
R1
+
Vsense
Ric2
500
Vsense
Rsense
OUT-
IL
In the above application schematic, the TSM1051 is used on the secondary side of a flyback adapter (or
battery charger) to provide an accurate control of voltage and current. The above feedback loop is made
with an optocoupler.
4/9
TSM1051
Figure 3 : Vref vs Ambient Temperature
Figure 6 : Vsense vs Ambient Temperature
1,230
1,225
203,5
203,0
202,5
202,0
201,5
201,0
200,5
Vcc=5V
2,5V Vcc 12V
≤
≤
1,220
1,215
1,210
1,205
1,200
Vcc=2,5V
Vcc=12V
0
20
40
60
80
100
120
0
20
40
60
80
100 120
Ta ambient temperature (°C)
Ta ambient temperature (°C)
Figure 4 : Vsense pin input bias current vs
Ambient Temperature
Figure 7 : Ictrl pin input bias current vs
Ambient Temperature
120
100
30
28
Vcc=2,5V
Vcc=12V
Vcc=5V
80
60
40
20
0
26
24
Vcc=12V
22
Vcc=2,5V
Vcc=5V
20
18
Victrl=200mV
0
20
40
60
80
100
120
0
20
40
60
80
100
120
Ta ambient temperature (°C)
Ta ambient temperature (°C)
Figure 5 : Output short circuit current vs
Ambient Temperature
Figure 8 : Supply current vs Ambient
Temperature
60
50
1,6
Vcc=12V
1,4
Vcc=5V
1,2
1,0
0,8
0,6
0,4
0,2
0,0
Vcc=12V
40
Vcc=5V
Vcc=2,5V
30
20
Vcc=2,5V
10
0
0
20
40
60
80
100
120
0
20
40
60
80
100
120
Ta ambient temperature (°C)
Ta ambient temperature (°C)
5/9
TSM1051
PRINCIPLE OF OPERATION AND APPLICATION HINTS
1. Voltage and Current Control
Vsense threshold is achieved internally by a re-
sistor bridge tied to the Vref voltage reference. Its
middle point is tied to the positive input of the cur-
rent control operational amplifier, and its foot is to
be connected to lower potential point of the sense
resistor as shown on the following figure. The re-
sistors of this bridge are matched to provide the
best precision possible.
The current sinking outputs of the two trans-con-
ductance operational amplifiers are common (to
the output of the IC). This makes an ORing func-
tion which ensures that whenever the current or
the voltage reaches too high values, the optocou-
pler is activated.
1.1. Voltage Control
The voltage loop is controlled via a first transcon-
ductance operational amplifier, the resistor bridge
R1, R2, and the optocoupler which is directly con-
nected to the output.
The relation between the values of R1 and R2
should be chosen as written in Equation 1.
R1 = R2 x Vref / (Vout - Vref)
Eq1
Where Vout is the desired output voltage.
To avoid the discharge of the load, the resistor
bridge R1, R2 should be highly resistive. For this
type of application, a total value of 100KΩ (or
more) would be appropriate for the resistors R1
and R2.
The relation between the controlled current and
the controlled output voltage can be described
with a square characteristic as shown in the fol-
lowing V/I output-power graph.
As an example, with R2 = 100KΩ, Vout = 4.10V,
Vref = 1.210V, then R1 = 41.9KΩ.
Note that if the low drop diode should be inserted
between the load and the voltage regulation resis-
tor bridge to avoid current flowing from the load
through the resistor bridge, this drop should be
taken into account in the above calculations by re-
placing Vout by (Vout + Vdrop).
Figure 9 : Output voltage versus output current
Vout
Voltage regulation
1.2. Current Control
The current loop is controlled via the second
trans-conductance operational amplifier, the
sense resistor Rsense, and the optocoupler.
The control equation verifies:
Rsense x Ilim = Vsense
Rsense = Vsense / Ilim
where Ilim is the desired limited current, and
Vsense is the threshold voltage for the current
control loop.
eq2
eq2’
TSM1051 Vcc : independent power supply
Iout
Secondary current regulation
0
TSM1051 Vcc : On power output
Primary current regulation
As an example, with Ilim = 1A, Vsense = -200mV,
then Rsense = 200mΩ.
Note that the Rsense resistor should be chosen
taking into account the maximum dissipation
(Plim) through it during full load operation.
2. Compensation
The voltage-control trans-conductance operation-
al amplifier can be fully compensated. Both of its
output and negative input are directly accessible
for external compensation components.
Plim = Vsense x Ilim.
eq3
As an example, with Ilim = 1A, and Vsense =
200mV, Plim = 200mW.
Therefore, for most adapter and battery charger
applications, a quarter-watt, or half-watt resistor to
make the current sensing function is sufficient.
An example of a suitable compensation network is
shown in Fig.2. It consists of a capacitor
Cvc1=2.2nF and a resistor Rcv1=470KΩ in series,
6/9
TSM1051
connected in parallel with another capacitor
Cvc2=22pF.
its power supply line in common with the power
supply line of the system.
Therefore, the current limitation can only be en-
sured by the primary PWM module, which should
be chosen accordingly.
The current-control trans-conductance operation-
al amplifier can be fully compensated. Both of its
output and negative input are directly accessible
for external compensation components.
An example of a suitable compensation network is
shown in Fig.2. It consists of a capacitor
Cic1=2.2nF and a resistor Ric1=22KΩ in series.
If the primary current limitation is considered not to
be precise enough for the application, then a suffi-
cient supply for the TSM1051 has to be ensured
under any condition. It would then be necessary
to add some circuitry to supply the chip with a sep-
arate power line. This can be achieved in numer-
ous ways, including an additional winding on the
transformer.
When the Vcc voltage reaches 12V it could be in-
teresting to limit the current coming through the
output in the aim to reduce the dissipation of the
device and increase the stability performances of
the whole application.
An example of a suitable Rout value could be
330Ω in series with the opto-coupler in case
Vcc=12V.
The following schematic shows how to realize a
low-cost power supply for the TSM1051 (with no
additional windings).
Please pay attention to the fact that in the particu-
lar case presented here, this low-cost power sup-
ply can reach voltages as high as twice the volt-
age of the regulated line. Since the Absolute Max-
imum Rating of the TSM1051 supply voltage is 14
V, this low-cost auxiliary power supply can only be
used in applications where the regulated line volt-
age does not exceed 7 V.
3. Start Up and Short Circuit Conditions
Under start-up or short-circuit conditions the
TSM1051 is not provided with a high enough sup-
ply voltage. This is due to the fact that the chip has
Figure 10 :
D
Vcc
OUT+
To primary
R2
TSM105
IL
Vcc
Rout
Rs
1.210V
Out
Cvc1
Rvc1
+
-
470K
Cvc2
2.2nF
22pF
DS
Cic1
2.2nF
+
-
+
200mV
Ictrl
Gnd
Ric1
22K
CS
+
+
R1
Vsense
Ric2
500
Vsense
OUT-
Rsense
IL
7/9
TSM1051
PACKAGE MECHANICAL DATA
6 PINS - PLASTIC PACKAGE SOT23-6
Millimeters
Dimensions
Inches
Typ.
Min.
Typ.
Max.
Min.
Max.
A
A1
A2
B
0.9
0
1.45
0.15
1.3
0.5
0.2
3
0.035
0
0.057
0.006
0.0512
0.02
0.9
0.35
0.09
2.8
1.5
0.035
0.0137
0.004
0.11
c
0.008
0.118
0.0689
D
E
1.75
0.059
e
0.95
0.0374
H
L
2.6
0.1
0
3
0.102
0.004
0
0.118
0.024
0.6
θ
10 deg.
10 deg.
8/9
TSM1051
PACKAGE MECHANICAL DATA
8 PINS - PLASTIC MICROPACKAGE (SO8)
Millimeters
Dim.
Inches
Typ.
Min.
Typ.
Max.
Min.
Max.
A
a1
a2
a3
b
1.75
0.25
1.65
0.85
0.48
0.25
0.5
0.069
0.010
0.065
0.033
0.019
0.010
0.020
0.1
0.004
0.65
0.35
0.19
0.25
0.026
0.014
0.007
0.010
b1
C
c1
D
45° (typ.)
4.8
5.8
5.0
6.2
0.189
0.228
0.197
0.244
E
e
1.27
3.81
0.050
0.150
e3
F
3.8
0.4
4.0
1.27
0.6
0.150
0.016
0.157
0.050
0.024
L
M
S
8° (max.)
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the
consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from
its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications
mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information
previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or
systems without express written approval of STMicroelectronics.
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© 2002 STMicroelectronics - Printed in Italy - All Rights Reserved
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9/9
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