T5744-TKS [TEMIC]
Telecom Circuit, 1-Func, PDSO20, SSO-20;型号: | T5744-TKS |
厂家: | TEMIC SEMICONDUCTORS |
描述: | Telecom Circuit, 1-Func, PDSO20, SSO-20 电信 光电二极管 电信集成电路 |
文件: | 总16页 (文件大小:157K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
T5744
UHF ASK Receiver
Description
The T5744 is a PLL receiver device for the receiving schemes including Manchester, Biphase and most PWM
range of f = 300 MHz to 450 MHz. It is developed for the protocols. Its main applications are in the areas of teleme-
0
demands of RF low-cost data communication systems tering, security technology and keyless-entry systems.
with low data rates and fits for most kind of modulation
FD eMatinuimrealsexternal circuitry requirements, no RF com-
D Various kinds of protocols like PWM, Manchester and
ponents on the PC board except matching to the
receiver antenna
Biphase supported
D Distinguishing the signal strength of several transmit-
ters via RSSI (Received Signal Strength Indicator)
D High sensitivity, especially at low data rates
D SSO20 and SO20 package
D ESD protection according to MIL-STD. 883
(4KV HBM)
D Fully integrated VCO
D High image frequency suppression due to 1 MHz IF
in conjunction with a SAW front-end filter. Up to
40 dB is thereby achievable with newer SAWs.
D Supply voltage 4.5 V to 5.5 V,
operating temperature range –40°C to 105°C
D Single-ended RF input for easy adaptation to l/4 an-
D Power management (polling) is possible by means of
a separate pin via the mC
tenna or printed antenna on PCB
D Low-cost solution due to high integration level
D Receiving bandwidth B = 600 kHz
IF
System Block Diagram
UHF ASK/FSK
Remote control transmitter
UHF ASK
Remote control receiver
1 Li cell
T5744
U2741B
Data
interface
1...3
Demod.
IF Amp
mC
Encoder
PLL
M44Cx9x
Keys
Antenna Antenna
XTO
VCO
PLL
XTO
Power
amp.
LNA
VCO
Figure 1. System block diagram
Ordering Information
Extended Type Number
T5744-TKS
Package
Remarks
SSO20
SSO20
SO20
Tube
T5744-TKQ
Taped and reeled
Tube
T5744-TGS
T5744-TGQ
SO20
Taped and reeled
Rev. A1, 01-Aug-01
1 (16)
Preliminary Information
T5744
Pin Description
Pin
1
Symbol
BR_0
Function
Baud rate select LSB
Baud rate select MSB
20
19
18
17
16
15
14
13
12
11
BR_0
BR_1
1
2
3
4
5
6
7
DATA
2
BR_1
ENABLE
TEST
3
CDEM
Lower cut-off frequency data fil-
ter
CDEM
4
5
6
7
8
AVCC
AGND
DGND
Analog power supply
Analog ground
RSSI
AVCC
AGND
Digital ground
MIXVCC Power supply mixer
MODE
DVCC
T5744
LNAGND High-frequency ground LNA and
mixer
DGND
9
LNA_IN RF input
XTO
MIXVCC
10
11
12
13
14
15
16
n.c.
LFVCC Power supply VCO
LF Loop filter
LFGND Ground VCO
Not connected
8
LFGND
LF
LNAGND
LNA_IN
9
XTO
Crystal oscillator
DVCC
Digital power supply
LFVCC
10
n.c.
MODE Selecting 433.92 MHz /315 MHz
Low: 315 MHz (USA)
High: 433.92 MHz (Europe)
Figure 2. Pinning SO20 and SSO20
17
18
RSSI
Output of the RSSI amplifier
TEST
Test pin, during operation at GND
19 ENABLE Selecting operation mode
Low: sleep mode
High: receiving mode
20
DATA
Data output
2 (16)
Rev. A1, 01-Aug-01
Preliminary Information
T5744
Block Diagram
BR_0 BR_1
ASK–
Demodulator
and data filter
Dem_out
DATA
TEST
CDEM
Data interface
RSSI
RSSI
AVCC
RSSI IF Amp
Test
AGND
DGND
MODE
DVCC
4. Order
ENABLE
LFGND
LPF
3 MHz
MIXVCC
Standby logic
LFVCC
XTO
LF
IF Amp
VCO
XTO
LPF
3 MHz
LNAGND
LNA_IN
f
LNA
64
Figure 3. Block diagram
RF Front End
The RF front end of the receiver is a heterodyne configu- figuration, V is controlled in a way that f /64 is equal
LF
LO
ration that converts the input signal into a 1-MHz IF to f
. If f is determined, f can be calculated using
XTO
LO
XTO
signal. According to figure 3, the front end consists of an the following formula:
LNA (low noise amplifier), LO (local oscillator), a mixer
and RF amplifier.
f
= f /64
XTO LO
The LO generates the carrier frequency for the mixer via The XTO is a one-pin oscillator that operates at the series
a PLL synthesizer. The XTO (crystal oscillator) generates resonance of the quartz crystal. According to figure 4, the
the reference frequency f . The VCO (voltage-con- crystal should be connected to GND via a capacitor CL.
XTO
trolled oscillator) generates the drive voltage frequency The value of that capacitor is recommended by the crystal
for the mixer. f is dependent on the voltage at Pin supplier. The value of CL should be optimized for the in-
f
LO
LO
LF. f is divided by factor 64. The divided frequency is dividual board layout to achieve the exact value of f
LO
XTO
compared to f
by the phase frequency detector. The and hereby of f . When designing the system in terms
XTO
LO
current output of the phase frequency detector is con- of receiving bandwidth, the accuracy of the crystal and
nected to a passive loop filter and thereby generates the the XTO must be considered.
control voltage V for the VCO. By means of that con-
LF
Rev. A1, 01-Aug-01
3 (16)
Preliminary Information
T5744
V
fLO
432.92
S
MODE + 1 (Europe) fIF +
DVCC
CL
The relation is designed to achieve the nominal IF fre-
quency of f = 1 MHz for most applications. For
XTO
LFGND
LF
IF
applications where f = 315 MHz, MODE must be set to
RF
‘0’. In the case of f = 433.92 MHz, MODE must be set
RF
R1 = 820 W
C9 = 4.7 nF
C10 = 1 nF
to ‘1’. For other RF frequencies, f is not equal to 1 MHz.
IF
f
is then dependent on the logical level at Pin MODE and
IF
on f . Table 1 summarizes the different conditions.
RF
The RF input either from an antenna or from a generator
must be transformed to the RF input Pin LNA_IN. The in-
put impedance of that pin is provided in the electrical
parameters. The parasitic board inductances and capaci-
tances also influence the input matching. The RF receiver
T5744 exhibits its highest sensitivity at the best signal-to-
noise ratio in the LNA. Hence, noise matching is the best
choice for designing the transformation network.
R1
C9
VS
C10
LFVCC
Figure 4. PLL peripherals
The passive loop filter connected to Pin LF is designed for
a loop bandwidth of BLoop = 100 kHz. This value for
BLoop exhibits the best possible noise performance of the
LO. Figure 4 shows the appropriate loop filter compo-
nents to achieve the desired loop bandwidth
A good practice when designing the network, is to start
with power matching. From that starting point, the values
of the components can be varied to some extent to achieve
the best sensitivity.
If a SAW is implemented into the input network a mirror
f
is determined by the RF input frequency f and the
RF
LO
frequency suppression of DP = 40 dB can be achieved.
Ref
IF frequency f using the following formula:
IF
There are SAWs available that exhibit a notch at
Df = 2 MHz. These SAWs work best for an intermediate
frequency of IF = 1 MHz. The selectivity of the receiver
is also improved by using a SAW. In typical automotive
applications, a SAW is used.
f
= f – f
LO
RF IF
To determine f , the construction of the IF filter must be
considered at this point. The nominal IF frequency is
f = 1 MHz. To achieve a good accuracy of the filter’s
corner frequencies, the filter is tuned by the crystal fre-
LO
IF
Figure 5 shows a typical input matching network for
quency f
. This means that there is a fixed relation
XTO
f
= 315 MHz and f = 433.92 MHz using a SAW. Fig-
RF
RF
between f and f , that depends on the logic level at pin
mode. This is described by the following formulas:
IF
LO
ure 6 illustrates an according input matching to 50 W
without a SAW. The input matching networks shown in
figure 6 are the reference networks for the parameters
given in the electrical characteristics.
fLO
MODE + 0 (USA) fIF +
314
Table 1 Calculation of LO and IF frequency
Conditions
Local Oscillator Frequency
Intermediate Frequency
f
f
= 315 MHz, MODE = 0
f
f
= 314 MHz
= 432.92 MHz
fRF
f
f
= 1 MHz
= 1 MHz
fRF
RF
RF
LO
LO
IF
IF
= 433.92 MHz, MODE = 1
fLO
+
fIF +
300 MHz < f < 365 MHz, MODE = 0
RF
1
314
1 ) 314
fRF
fRF
432.92
fLO
+
fIF +
365 MHz < f < 450 MHz, MODE = 1
RF
1
1 ) 432.92
4 (16)
Rev. A1, 01-Aug-01
Preliminary Information
T5744
8
9
8
9
LNAGND
LNAGND
T5744
T5744
L
L
C3
C3
LNA_IN
LNA_IN
25n
25n
22p
47p
C16
C16
C17
8.2p
C17
22p
100p
100p
L3
L3
TOKO LL2012
F27NJ
TOKO LL2012
F47NJ
f
= 433.92 MHz
f
= 315 MHz
RF
RF
27n
47n
L2
L2
TOKO LL2012
TOKO LL2012
RF
IN
RF
IN
F33NJ
F82NJ
1
2
5
1
2
5
B3555
B3551
IN
IN
OUT
OUT_GND
OUT
OUT_GND
33n
82n
6
6
IN_GND
IN_GND
C2
C2
CASE_GND
3,4 7,8
CASE_GND
3,4 7,8
8.2p
10p
Figure 5. Input matching network with SAW filter
f
= 433.92 MHz
f
= 315 MHz
RF
RF
8
9
8
LNAGND
LNAGND
T5744
T5744
9
LNA_IN
LNA_IN
25n
25n
C3
C3
15p
33p
RF
IN
RF
IN
3.3p
3.3p
100p
100p
22n
39n
TOKO LL2012
F22NJ
TOKO LL2012
F39NJ
Figure 6. Input matching network without SAW filter
Please note that for all coupling conditions (see figures 5 RF input frequencies, refer to table 1 to determine the
and 6), the bond wire inductivity of the LNA ground is center frequency.
compensated. C3 forms a series resonance circuit to-
The receiver T5744 employs an IF bandwidth of
gether with the bond wire. L = 25 nH is a feed inductor to
B
= 600 kHz and can be used together with the U2741B
IF
establish a DC path. Its value is not critical but must be
large enough not to detune the series resonance circuit.
For cost reduction, this inductor can be easily printed on
the PCB. This configuration improves the sensitivity of
the receiver by about 1 dB to 2 dB.
in ASK mode.
RSSI Amplifier
The subsequent RSSI amplifier enhances the output
signal of the IF amplifier before it is fed into the demod-
ulator. The dynamic range of this amplifier is
Analog Signal Processing
DR
= 60 dB. If the RSSI amplifier is operated within
RSSI
IF Amplifier
its linear range, the best S/N ratio is maintained. If the dy-
The signals coming from the RF front end are filtered by namic range is exceeded by the transmitter signal, the S/N
th
the fully integrated 4 -order IF filter. The IF center fre- ratio is defined by the ratio of the maximum RSSI output
quency is
f
IF
= 1 MHz for applications where voltage and the RSSI output voltage due to a disturber.
f
= 315 MHz or f = 433.92 MHz is used. For other The dynamic range of the RSSI amplifier is exceeded if
RF
RF
Rev. A1, 01-Aug-01
5 (16)
Preliminary Information
T5744
the RF input signal is about 60 dB higher compared to the The highpass filter cut-off frequency is defined by an ex-
RF input signal at full sensitivity.
ternal capacitor connected to Pin CDEM. The cut-off
frequency of the highpass filter is defined by the follow-
ing formula:
Pin RSSI
The output voltage of the RSSI amplifier (V
able at Pin RSSI. Using the RSSI output signal, the signal
strength of different transmitters can be distinguished.
) is avail-
RSSI
1
fcu_DF +
2 p RI CDEM
The usable input-power range P
–55 dBm.
is –100 dBm to
Ref
Recommended values for CDEM are given in the electri-
cal characteristics.
Since different RF input networks may exhibit slightly
different values for the LNA gain, the sensitivity values
given in the electrical characteristics refer to a specific in-
put matching. This matching is illustrated in figure 6 and
exhibits the best possible sensitivity.
The cut-off frequency of the lowpass filter is defined by
the selected baudrate range (BR_Range). BR_Range is
defined by the Pins BR_0 and BR_1. BR_Range must be
set in accordance to the used baudrate.
BR_1
BR_0
BR_Range
3.0
0
0
1
1
0
1
0
1
0
1
2
3
max
2.8
2.6
2.4
2.2
2.0
1.8
1.6
1.4
1.2
1.0
T
= –40_C
25_C
amb
105_C
Each BR_Range is defined by a minimum and a maxi-
mum edge-to-edge time (t ). These limits are defined
in the electrical characteristics. They should not be ex-
ceeded to maintain full sensitivity of the receiver.
min
ee_sig
–130–120–110–100–90 –80 –70 –60 –50 –40 –30
( dBm )
Receiving Characteristics
P
Ref
The RF receiver T5744 can be operated with and without
a SAW front end filter. In a typical automotive applica-
tion, a SAW filter is used to achieve better selectivity. The
selectivity with and without a SAW front end filter is il-
lustrated in figure 7. Note that the mirror frequency is
reduced by 40 dB. The plots are printed relatively to the
maximum sensitivity. If a SAW filter is used, an insertion
loss of about 4 dB must be considered.
Figure 7. RSSI characteristics
ASK Demodulator and Data Filter
The signal coming from the RSSI amplifier is converted
into the raw data signal by the ASK demodulator.
An automatic threshold control circuit (ATC) is employed
to set the detection reference voltage to a value where a
good signal-to-noise ratio is achieved. This circuit also
implies the effective suppression of any kind of inband
noise signals or competing transmitters. If the S/N ratio
exceeds 10 dB, the data signal can be detected properly.
When designing the system in terms of receiving band-
width, the LO deviation must be considered as it also
determines the IF center frequency. The total LO devi-
ation is calculated to be the sum of the deviation of the
crystal and the XTO deviation of the T5744. Low-cost
The output signal of the demodulator is filtered by the crystals are specified to be within 100 ppm. The XTO
data filter before it is fed into the digital signal processing deviation of the T5744 is an additional deviation due to
circuit. The data filter improves the S/N ratio as its pass- the XTO circuit. This deviation is specified to be
band can be adopted to the characteristics of the data
signal. The data filter consists of a 1st-order highpass and ation is 130 ppm in that case. Note that the receiving
a 1st-order lowpass filter. bandwidth and the IF-filter bandwidth are equivalent.
30 ppm. If a crystal of 100 ppm is used, the total devi-
6 (16)
Rev. A1, 01-Aug-01
Preliminary Information
T5744
Most applications are dominated by two transmission fre-
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
quencies: f
= 315 MHz is mainly used in USA, f
Send
Send
= 433.92 MHz in Europe. In order to ease the usage of all
-dependent parameters, the electrical characteristics
without SAW
T
Clk
display three conditions for each parameter.
D Application USA
(f
= 4.90625 MHz, MODE = L, T = 2.0383 µs)
Clk
XTO
D Application Europe
(f
= 6.76438 MHz, MODE = H, T = 2.0697 µs)
Clk
XTO
D Other applications
with SAW
(T is dependent on f
and on the logical state of
XTO
Clk
Pin MODE. The electrical characteristic is given as a
–6 –5 –4 –3 –2 –1
0
1
2
3
4
5
6
function of T ).
Clk
16564
df ( MHz )
The clock cycle of some function blocks depends on the
selected baud rate range (BR_Range) which is defined by
Figure 8. Receiving frequency response
the Pins BR_0 and BR_1. This clock cycle T
is de-
XClk
fined by the following formulas for further reference:
Basic Clock Cycle of the Digital Circuitry
BR_Range = BR_Range0: T
BR_Range1: T
= 8 × T
= 4 × T
= 2 × T
= 1 × T
XClk
XClk
XClk
XClk
Clk
Clk
Clk
Clk
The complete timing of the digital circuitry and the ana-
log filtering is derived from one clock. According to
BR_Range2: T
BR_Range3: T
figure 9, this clock cycle T is derived from the crystal
Clk
oscillator (XTO) in combination with a divider. The divi-
sion factor is controlled by the logical state at Pin MODE.
According to chapter ‘RF Front End’, the frequency of the
Pin ENABLE
Via the Pin ENABLE the operating mode of the receiver
can be selected (Figure 10, Figure 11).
crystal oscillator (f
) is defined by the RF input signal
XTO
(f
) which also defines the operating frequency of the
RFin
local oscillator (f ).
LO
If the Pin ENABLE is held to Low, the receiver remains
in sleep mode. All circuits for signal processing are dis-
abled and only the XTO is running in that case. The
T
Clk
current consumption is I = I
in that case. During the
S
Soff
MODE
16
sleep mode the receiver is not sensitive to a transmitter
signal.
L : USA(:10)
H: Europe(:14)
Divider
:14/:10
To activate the receiver, the Pin ENABLE must held to
f
DVCC
15
XTO
High. During the start-up period, T
, all signal proc-
Startup
essing circuits are enabled and settled. The duration of the
start-up period depends on the selected baud-rate range
(BR_Range).
XTO
14
XTO
After the start-up period all circuits are in a stable condi-
tion and the receiver is in the receiving mode.
In the receiving mode the internal data signal (Dem_out)
is switched to Pin DATA. To avoid a incorrect timing at
the begin of the data stream, the begin is synchronized to
a falling edge of the incoming data signal. The receiver
stays in the receiving mode until it is switched back to
sleep mode via Pin ENABLE.
Figure 9. Generation of the basic clock cycle
Pin MODE can now be set in accordance with the desired
clock cycle T . T controls the following application-
Clk Clk
relevant parameters:
D Timing of the analog and digital signal processing
During the start-up and the receiving mode the current
D IF filter center frequency (f
)
consumption is I = I
.
IF0
S
Son
Rev. A1, 01-Aug-01
7 (16)
Preliminary Information
T5744
Dem_out
ENABLE
DATA
tee_sig
Sleep mode
IS = I Soff
Start–up mode
Receiving mode
IS = I Son
IS = I Son
T
Start–up
Figure 10. Enable timing (1)
Dem_out
ENABLE
DATA
tee_sig
Sleep mode
IS = I Soff
Start–up mode
Receiving mode
IS = I Son
IS = I Son
T
Start–up
Figure 11. Enable timing (2)
of the DATA signal as a result is always an integral multi-
ple of T
Digital Signal Processing
XClk.
The data from the ASK demodulator (Dem_out) is digi-
tally processed in different ways and as a result converted
The minimum time period between two edges of the data
. This implies an
into the output signal DATA. This processing depends on signal is limited to tee_sig w T
DATA_min
the selected baud-rate range (BR_Range). Figure 12 illus- efficient suppression of spikes at the DATA output. At the
trates how Dem_out is synchronized by the extended same time it limits the maximum frequency of edges at
basic clock cycle T
. Data can change its state only af- DATA. This eases the interrupt handling of a connected
XClk
ter T
elapsed. The edge-to-edge time period tee_sig mC.
XClk
TXClk
Dem_out
Data_out (DATA)
tee_sig
Figure 12. Synchronization of the demodulator output
8 (16)
Rev. A1, 01-Aug-01
Preliminary Information
T5744
Dem_out
DATA
tDATA_min
tDATA_min
tDATA_min
tee
Figure 13. Debouncing of the demodulator output
tee
tee
Absolute Maximum Ratings
Parameter
Symbol
Min.
Max.
6
Unit
V
Supply voltage
V
S
Power dissipation
P
450
150
+125
+105
10
mW
°C
tot
Junction temperature
T
j
Storage temperature
T
stg
–55
–40
°C
Ambient temperature
T
amb
°C
Maximum input level, input matched to 50 W
P
dBm
in_max
Thermal Resistance
Parameter
Symbol
Value
100
Unit
K/W
K/W
Junction ambient SO20 package
Junction ambient SSO20 package
R
R
thJA
thJA
140
Electrical Characteristics
All parameters refer to GND, T
= –40°C to +105°C, V = 4.5 V to 5.5 V, f = 433.92 MHz and f = 315 MHz, un-
amb
S
0
0
less otherwise specified. (V = 5 V, T
= 25°C)
S
amb
Parameter
Test Condition
Symbol
6.76438 MHz Osc.
(MODE: 1)
4.90625 MHz Osc.
(MODE: 0)
Variable Oscillator
Typ.
Unit
Min.
Typ.
Max.
Min.
Typ.
Max.
Min.
Max.
Basic clock cycle of the digital circuitry
Basic clock
cycle
MODE = 0 (USA)
MODE = 1 (Europe)
T
2.0383
2.0383
1/(f /10)
xto
1/(f /10)
xto
µs
µs
Clk
2.0697
2.0697
1/(f /14)
1/(f /14)
xto
xto
Extended
basic clock
cycle
BR_Range0
BR_Range1
BR_Range2
BR_Range3
T
16.6
8.3
4.1
2.1
16.6
8.3
4.1
2.1
16.3
8.2
4.1
2.0
16.3
8.2
4.1
2.0
8 × T
8 × T
µs
µs
µs
µs
XClk
Clk
4 × T
Clk
4 × T
Clk
Clk
2 × T
2 × T
Clk
1 × T
Clk
1 × T
Clk
Clk
Start-up
time
see figures
BR_Range0
BR_Range1
BR_Range2
BR_Range3
T
1855
1061
1061
663
1855
1061
1061
663
1827
1045
1045
653
1827
1045
1045
653
896.5
512.5
512.5
320.5
896.5
512.5
512.5
320.5
µs
µs
µs
µs
µs
Startup
10 and 11
× T
Clk
× T
Clk
Receiving mode
Intermedi-
f
IF
ate fre-
quency
MODE=0 (USA)
MODE=1 (Europe)
1.0
f
× 64 / 314
MHz
MHz
XTO
× 64 / 432.92
1.0
f
XTO
Rev. A1, 01-Aug-01
9 (16)
Preliminary Information
T5744
Electrical Characteristics (continued)
All parameters refer to GND, T
= –40°C to +105°C, V = 4.5 V to 5.5 V, f = 433.92 MHz and f = 315 MHz, un-
amb
S
0
0
less otherwise specified. (V = 5 V, T
= 25°C)
S
amb
Parameter
Test Condition
Symbol
6.76438 MHz Osc.
(MODE: 1)
4.90625 MHz Osc.
(MODE: 0)
Variable Oscillator
Typ. Max.
Unit
Min.
Typ.
Max.
Min.
Typ.
Max.
Min.
Minimum
time period
between
edges at
Pin DATA
BR_Range0
BR_Range1
BR_Range2
BR_Range3
(figure 13)
T
DATA_min
165
83
41.4
20.7
165
83
41.4
20.7
163
81
40.7
20.4
163
81
40.7
20.4
10 × T
10 × T
µs
µs
µs
µs
XClk
XClk
10 × T
10 × T
XCl
XCl
10× T
10× T
XClk
10 × T
XClk
10 × T
XClk
XClk
Edge to
edge time
period of
the data sig- BR_Range3
nal for full
sensitivity
BR_Range0
BR_Range1
BR_Range2
t
400
200
100
50
8479
8479
8479
8479
400
200
100
50
8350
8350
8350
8350
µs
µs
µs
µs
ee_sig
BR_Range
4097
T
CLK
2 ms/T
CLK
(figure 10)
Parameters
Test Conditions / Pins
Symbol
Min.
Typ.
Max.
Unit
Current consumption
Sleep mode
(XTO active)
ISoff
190
276
µA
IC active
ISon
7.1
8.7
mA
(startup-, receiving mode)
Pin DATA = H
LNA mixer
Third-order intercept point
LNA/ mixer/ IF amplifier
input matched according to fig-
ure 6
IIP3
–28
–73
7
dBm
dBm
dB
LO spurious emission
@ RFIn
Input matched according to fig-
ure 6, required according to
I–ETS 300220
ISLORF
–57
Noise figure LNA and mixer Input matching according to fig-
NF
(DSB)
ure 6
LNA_IN input impedance
@ 433.92 MHz
@ 315 MHz
ZiLNA_IN
IP1db
1.0 || 1.56
1.3 || 1.0
kΩ || pF
kΩ || pF
1 dB compression point
(LNA, mixer, IF amplifier)
Input matched according to fig-
ure 6, referred to RFin
–40
dBm
Maximum input level
Input matched according to fig-
ure 6, BER ≤ 10–3
Pin_max
–20
dBm
Local oscillator
Operating frequency range
VCO
fVCO
299
449
MHz
Phase noise VCO / LO
fosc = 432.92 MHz
@ 1 MHz
L (fm)
–93
–113
–90
–110
dBC/Hz
dBC/Hz
@ 10 MHz
Spurious of the VCO
VCO gain
@
fXTO
–55
190
100
–47
dBC
MHz/V
kHz
KVCO
BLoop
Loop bandwidth of the PLL For best LO noise
(design parameter)
R1 = 820 W
C9 = 4.7 nF
C10 = 1 nF
10 (16)
Rev. A1, 01-Aug-01
Preliminary Information
T5744
Electrical Characteristics (continued)
All parameters refer to GND, T
= –40°C to +105°C, V = 4.5 V to 5.5 V, f = 433.92 MHz and f = 315 MHz, un-
amb
S
0
0
less otherwise specified. (V = 5 V, T
= 25°C)
S
amb
Parameters
Test Conditions / Pins
Symbol
Min.
Typ.
Max.
Unit
Capacitive load at Pin LF
XTO operating frequency
CLF_tot
fXTO
10
nF
XTO crystal frequency,
appropriate load capacitance
must be connected to XTAL
fXTAL = 6.764375 MHz (EU)
6.764375
–30 ppm
4.90625
–30 ppm
6.764375
4.90625
6.764375
+30 ppm
4.90625
+30 ppm
MHz
MHz
fXTAL = 4.90625 MHz (US)
Series resonance resistor of
the crystal
fXTO = 6.764 MHz
4.906 MHz
RS
Co
150
220
W
W
Static capacitance of the
crystal
6.5
pF
Analog signal processing
Input sensitivity
Input matched according to fig-
ure 6
PRef_ASK
ASK (level of carrier)
BER ≤ 10–3 (Manchester),
fin = 433.92 MHz/ 315 MHz
T = 25°C, VS = 5 V
IF = 1 MHz
f
BR_Range0 (1 kBd)
BR_Range1 (2 kBd)
BR_Range2 (4kBd)
–107
–105
–103
–101
–110
–108
–106
–104
–112
–110
–108
–106
dBm
dBm
dBm
dBm
BR_Range3 (8 kBd)
fin = 433.92 MHz/ 315 MHz
Sensitivity variation for the
full operating range
compared to Tamb = 25°C,
VS = 5 V
DPRef
f
IF = 1 MHz
PASK = PRef_ASK + DPRef
+2.5
–1.5
dB
fin = 433.92 MHz/ 315 MHz
DP
Ref
Sensitivity variation for full
operating range including IF
fIF = 0.79 MHz to 1.21 MHz
fIF = 0.73 MHz to 1.27 MHz
+5.5
+7.5
–1.5
–1.5
dB
dB
PASK = PRef_ASK + DPRef
filter
compared
to
Tamb = 25°C, VS = 5 V
S/N ratio to suppress inband
noise signals
SNR
10
60
12
dB
Dynamic range RSSI ampl.
RSSI output voltage range.
RSSI gain
DRRSSI
VRSSI
GRSSI
RI
dB
V
1.0
28
3.0
55
20
40
mV/dB
kOhm
1
RI of Pin CDEM for cut-off
frequency calculation
fcu_DF
+
2 p RI CDEM
Recommended CDEM for
best performance
BR_Range0
BR_Range1
BR_Range2
BR_Range3
CDEM
33
18
10
6.8
nF
nF
nF
nF
Rev. A1, 01-Aug-01
11 (16)
Preliminary Information
T5744
Electrical Characteristics (continued)
All parameters refer to GND, T
= –40°C to +105°C, V = 4.5 V to 5.5 V, f = 433.92 MHz and f = 315 MHz, un-
amb
S
0
0
less otherwise specified. (V = 5 V, T
= 25°C)
S
amb
Parameters
Test Conditions / Pins
Symbol
Min.
Typ.
Max.
Unit
Upper cut-off frequency data Upper cut-off frequency
fu
filter
BR_Range0
BR_Range1
BR_Range2
BR_Range3
1.75
3.5
7.0
2.2
4.4
8.8
2.65
5.3
10.6
21.2
kHz
kHz
kHz
kHz
14.0
17.6
Digital ports
Data output
– Saturation voltage LOW
– Internal pull-up resistor
Iol = 1 mA
VOI
RPup
0.08
50
0.3
65
V
kW
39
ENABLE input
– Low-level input voltage
– High-level input voltage
Sleep mode
Receiving mode
VIl
VIh
0.2 × VS
0.2 × VS
0.2 × VS
0.2 × VS
0.2 × VS
V
V
0.8 × VS
0.8 × VS
0.8 × VS
0.8 × VS
MODE input
– Low-level input voltage
– High-level input voltage
Division factor = 10
Division factor = 14
VIl
VIh
V
V
BR_0 input
– Low-level input voltage
– High-level input voltage
VIl
VIh
V
V
BR_1 input
– Low-level input voltage
– High-level input voltage
VIl
VIh
V
V
TEST input
– Low-level input voltage
Test input must always be set to
LOW
VIl
V
12 (16)
Rev. A1, 01-Aug-01
Preliminary Information
T5744
Application Circuits
VS
C7
2.2uF
10%
C6
10nF
10%
T5744
C14
1
2
3
20
19
18
17
16
BR_0
BR_1
CDEM
DATA
ENABLE
TEST
DATA
39nF 5%
ENABLE
GND
RSSI
RSSI
4
5
6
AVCC
AGND
DGND
MODE
C13
10nF 10%
15
14
DVCC
XTO
Q1
C11
7
MIXVCC
12pF
8
9
10
13
12
11
LNAGND
LNA_IN
NC
LFGND
LF
LFVCC
6.76438MHz
np0
2%
C3 15pF
5% np0
C12
10nF 10%
C15
150pF
10%
C8
150pF
10%
KOAX
C16
R1
820
5%
100pF
5% np0
C17
3.3pF
5% np0
L2 TOKO LL2012 F22NJ
22nH
5%
C9
4.7nF
5%
C10
1nF
5%
Figure 14. Application circuit: fRF = 433.92 MHz, without SAW filter
VS
C6
10nF
10%
C7
2.2uF
10%
T5744
C14
1
20
DATA
BR_0
BR_1
CDEM
DATA
39nF 5%
19
18
17
16
2
3
ENABLE
ENABLE
TEST
GND
RSSI
RSSI
4
5
6
AVCC
AGND
DGND
MODE
DVCC
XTO
C13
10nF 10%
15
14
Q1
C11
7
MIXVCC
13
12
11
15pF
8
9
10
4.90625MHz
LNAGND
LNA_IN
NC
LFGND
LF
LFVCC
np0
2%
C3 33pF
5% np0
C12
10nF 10%
C15
150pF
10%
C8
150pF
10%
C16
KOAX
R1
820
5%
C17
100pF
5% np0
L2 TOKO LL2012 F39NJ
39nH
5%
3.3pF
C9
4.7nF
5%
C10
1nF
5%
5% np0
Figure 15. Application circuit: fRF = 315 MHz, without SAW filter
Rev. A1, 01-Aug-01
13 (16)
Preliminary Information
T5744
VS
C7
2.2uF
10%
C6
10nF
10%
T5744
C14
39nF 5%
1
2
3
20
19
18
17
16
BR_0
BR_1
CDEM
DATA
ENABLE
TEST
DATA
ENABLE
GND
RSSI
RSSI
4
5
6
AVCC
AGND
DGND
MODE
C13
10nF 10%
15
14
DVCC
XTO
Q1
C11
7
MIXVCC
6.76438MHz 12pF
np0
8
13
12
11
LNAGND
LNA_IN
NC
LFGND
LF
LFVCC
2%
9
C3 22pF
5% np0
10
C15
150pF
10%
C8
150pF
10%
C12
10nF 10%
C16
C17
8,2pF
np0
L3 TOKO LL2012
F27 NJ
100pF
5%
5%
np0
R1
820
5%
27nH
5%
L2 TOKO LL2012
C9
4.7nF
5%
C10
1nF
5%
KOAX
F33NJ
1
5
IN
OUT
2
6
IN_GND
OUT_GND
33nH
5%
3
4
7
8
CASE_GND
CASE_GND
CASE_GND
CASE_GND
C2
8.2pF
5% np0
B3555
Figure 16. Application circuit: fRF = 433.92 MHz, with SAW filter
VS
C7
2.2uF
10%
C6
10nF
10%
T5744
C14
1
2
3
20
19
18
17
16
BR_0
BR_1
CDEM
DATA
ENABLE
TEST
DATA
39n F 5%
ENABLE
GND
RSSI
RSSI
4
5
6
AVCC
AGND
DGND
MODE
C13
10nF 10%
15
14
DVCC
XTO
Q1
C11
15pF
7
MIXVCC
8
9
10
13
12
11
LNAGND
LNA_IN
NC
LFGND
LF
LFVCC
4.90625MHz
2%
np0
C3 47pF
5% np0
C8
150pF
10%
C15
150pF
10%
C12
10nF 10%
C16
C17
22pF
100pF
5%
np0
5%
np0
L3 TOKO LL2012
F47NJ
R1
47nH
5%
820
5%
L2 TOKO LL2012
C9
C10
1nF
5%
KOAX
F82NJ
4.7nF
5%
1
5
IN
IN_GND
OUT
2
6
OUT_GND
82nH
5%
C2
10pF
3
4
7
8
CASE_GND
CASE_GND
CASE_GND
CASE_GND
5%
np0
B3551
Figure 17. Application circuit: fRF = 315 MHz, with SAW filter
14 (16)
Rev. A1, 01-Aug-01
Preliminary Information
T5744
Package Information
Package SO20
9.15
8.65
Dimensions in mm
12.95
12.70
7.5
7.3
2.35
0.25
0.25
0.10
0.4
10.50
10.20
1.27
11.43
20
11
technical drawings
according to DIN
specifications
13038
1
10
5.7
5.3
Package SSO20
Dimensions in mm
6.75
6.50
4.5
4.3
1.30
0.15
0.15
0.05
0.25
0.65
6.6
6.3
5.85
20
11
technical drawings
according to DIN
specifications
1
10
Rev. A1, 01-Aug-01
15 (16)
Preliminary Information
T5744
Ozone Depleting Substances Policy Statement
It is the policy of Atmel Germany GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances (ODSs).
The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and forbid
their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these
substances.
Atmel Germany GmbH has been able to use its policy of continuous improvements to eliminate the use of ODSs listed
in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency (EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.
Atmel Germany GmbH can certify that our semiconductors are not manufactured with ozone depleting substances
and do not contain such substances.
11.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use Atmel Wireless & Microcontrollers products for any unintended
or unauthorized application, the buyer shall indemnify Atmel Wireless & Microcontrollers against all claims,
costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death
associated with such unintended or unauthorized use.
Data sheets can also be retrieved from the Internet:
http://www.atmel–wm.com
Atmel Germany GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 (0)7131 67 2594, Fax number: 49 (0)7131 67 2423
16 (16)
Rev. A1, 01-Aug-01
Preliminary Information
相关型号:
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