U4065B [TEMIC]
FM Receiver; FM接收器型号: | U4065B |
厂家: | TEMIC SEMICONDUCTORS |
描述: | FM Receiver |
文件: | 总23页 (文件大小:288K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
U4065B
FM Receiver
Description
The IC U4065B is a bipolar integrated FM-frontend device is designed for high performance car radio and
circuit. It contains a mixer, an oscillator, two IF home receiver applications.
preamplifiers and an unique interference sensor. The
Features
All frontend functions of a high performance FM-
receiver, except the RF preamplifier, are integrated
Easy cascading of three IF filters (ceramic) by use of
two on-chip IF preamplifiers
Improved dynamic range by high current double
balanced mixer design and a new AGC conception
with 3 loops on chip
On-chip control functions are available for system
gain adjust (dB linear vs. dc current)
Low noise LO design
ESD protected
Improved blocking and intermod behavior by use of
an unique “interference” sensor controlling the AGC
Block Diagram
V
S
V
S
IF gain adjust
ANT
IF BPF
IF tank
IF BPF
IF outp
IF BPF
19
18
21
7
3
4
5
20
RF tank
16
14
15
2
PIN
ATT
Mixer
IF 1
IF 2
AGC
13
wide band
& IF
Inter-
ference
mixer
AGC adjust
(wide band)
RF
RF tank
D.N.C.
12
V
ref
= 4 V
I F &
detector
LO tank
23
24
17
Voltage
reg.
Local
oscill.
11
22
1
8
10
6
9
+
Interference
IF BPF
V
S
LO output
V
tune
V
S
94 8768
AGC level
Rev. A3, 15-Oct-98
1 (23)
U4065B
Pin Description
Pin
1
Symbol
Function
Pin
13
Symbol
Function
LOBUFF Buffered local oscillator output
AGCWB Threshold adjustment of the
wideband AGC
2
GND1
Ground of the second IF ampli-
fier
14
15
GND3
Mixer ground
3
4
IF2OUT
Output of the second IF ampli-
fier
MIXIN1
Input 1 of the double balanced
mixer
GAINIF1 Gain control of the first
IF amplifier
16
MIXIN2
Input 2 of the double balanced
mixer
5
6
7
8
9
IF2IN
VS
Input of the second IF amplifier
17
18
19
20
VREF
Reference voltage output
Supply voltage
MIXOUT1 Mixer output 1
MIXOUT2 Mixer output 2
IF1OUT
GND2
IMIFIN
Output of the first IF amplifier
Ground
GND4
Ground of the first
IF amplifier
Input of the amplifier for the
IM-sensor
21
22
23
24
IF1IN
GND5
LOE
Input of the first amplifier
Oscillator ground
10
AGCOUT Output of the automatic gain
control
Local oscillator (emitter)
Local oscillator (base)
11 IMMIXOUT Output of the intermodulation
mixer
LOB
12
D.N.C.
Do not connect
LOBUFF
GND1
+
94 8769
94 8770
23
50
1
ESD
1 V
8
ESD
2
Buffered local oscillator output:
It drives the FM-input of the PLL circuit (for example
Ground of the second IF amplifier:
U428xBM-family). The typical parallel output resistance There is no internal connection to the other ground pins.
at 100 MHz is 70 , the parallel output capacitance is
about 10 pF. When using an external load of 500
/
10 pF, the oscillator swing is about 100 mV. The second
harmonic of the oscillator frequency is less than
– 15 dBc.
2 (23)
Rev. A3, 15-Oct-98
U4065B
The parallel input resistance is 330 . The parallel input
capacitance is about 12 pF. No dc current is allowed. To
avoid overload of this stage an internal detector watches
the input level and causes current at the AGCOUT pin.
IF2OUT
3
ESD
V
S
IF1OUT
V
S
V
ref
ESD
94 8771
330
Output of the second IF amplifier:
The parallel output capacitance to ground is about 7 pF.
7
The external load resistance is to connect to V . The dc
S
current into the pin is typically 3 mA.
Note: Supply voltage V has to be protected against
S
IF-distortion
94 8774
GAINIF1
V
ref
17
Output of the first IF amplifier:
The parallel output resistance is 330 which allows the
use of a standard ceramic BPF. The parallel output capa-
citance is about 7 pF. The dc voltage at the pin is 0.5 V
2 k
less than V .
S
ESD
Gain control of the first IF amplifier:
4
94 8772
IMIFIN
The gain of the first IF amplifier can be adjusted by a re-
sistor to ground. This is useful for example to com-
pensate the insertion loss tolerances of the ceramic BPF’s.
Please ensure that the output current of the pin does not
exceed 150 A in any case. Linear increasing in the cur-
rent out of GAINIF1 effects dB linear increasing of the
gain (0.15 dB/ A).
94 8775
9
I4 = 0
G= Gmin = 2 dB
ESD
I4 = 140 A G = Gmax = 22 dB
IF2IN
94 8773
V
ref
Input of the IF amplifier for the IM-sensor:
5
The parallel input resistance is 330 . The amplifier is ex-
tremely sensitive to ac signals. A few hundred V of
IF-signal at this pin will cause current at the AGC output.
Therefore pay attention when connecting the standard ce-
ramic filter used between IMOUT and this pin. The
reference point of the filter has to be free of any ac signal.
Please avoid dc current at this pin.
ESD
Input of the second IF amplifier:
Rev. A3, 15-Oct-98
3 (23)
U4065B
AGCOUT
MIXIN1
V
ref
94 8776
10
2.5 k
15
ESD
1 k
ESD
1 V
94 8779
Input 1 of the double balanced mixer:
Output of the automatic gain control:
The parallel input resistance is 1.2 k . The parallel input
capacitance is about 9 pF. When using the mixer unbal-
anced this pin is to be grounded for RF-signals by an
external capacitance of a few nF. DC current is not allowed.
The AGC output is an open collector output. The current
of the pin diode is this current multiplied by the current
gain of the external PNP transistor. The dc voltage at the
pin may vary from 2 V to V , therefore you can easily use
S
this pin as an indicator of the AGC regulation state.
MIXIN2
IMMIXOUT
V
ref
V
S
2.5 k
16
ESD
300
11
ESD
94 8780
1 V
Input 2 of the double balanced mixer:
94 8777
The parallel input resistance is 1.6 k . The parallel input
capacitance is about 7 pF. The double sideband noise fig-
ure of the unbalanced mixer is about 7 dB. In the balanced
case the noise figure will be reduced by about 0.8 dB.
Output of the intermodulation mixer:
The parallel output resistance is 330 which allows the
use of a standard ceramic BPF without any further match-
ing network. Please ensure that the ground-pin of the filter
is free of ac signals.
VREF
94 8781
AGCWB
V
S
200
V
ref
25 k
4.6 V
17
ESD
32 k
13
ESD
94 8778
Reference voltage:
The internal temperature compensated reference voltage
is 3.9 V. It is used as bias voltage for most blocks, so the
Threshold adjustment of the wideband AGC:
The threshold of the wideband AGC can be adjusted by electrical characteristics of the U4065B are widely inde-
an external resistor to ground. The setting range is 10 dB. pendent of the supply voltage. The internal output
For minimum blocking this pin is connected to ground. In resistance of the reference voltage is less than 10 . To
order to set the threshold to smaller levels the resistance avoid internal coupling across this pin external capacitors
value should be up to a few hundred k .
are required. The maximum output current is I = 5 mA.
ref
4 (23)
Rev. A3, 15-Oct-98
U4065B
MIXOUT1, MIXOUT2
LOE
ESD
18
19
23
ESD
94 8785
94 8782
Mixer output 1, 2:
Emitter of the local oscillator:
The mixer output is an open collector of a bipolar transis- An external capacitor is connected between LOE and
tor. The minimum voltage at this pins is 5 V (V -voltage ground. The ground pin of this capacitor is to connect to
S
swing). The dc current into this pins is typically 9 mA. the pin GND5. GND5 is the chip internal ground of the
Good LO- and RF suppression at the mixer output can be local oscillator.
achieved by symmetrical load conditions at the pins MIX-
OUT1 and MIXOUT2.
LOB
IF1IN
24
ESD
21
V
ref
330
94 8786
ESD
Input of the first IF amplifier:
Base of the local oscillator:
94 8784
The tank of the local oscillator is connected at pin LOB.
The ground pin of this tank is to connect to the pin GND5.
The typical input resistance is 330 . The dc voltage is GND5 is the chip internal ground into pin 24 of the local
nearly the same one as the reference voltage. Please avoid oscillator. The resonant resistance of the tank should be
dc current at this pin.
about 250 . Minimum Q of the unloaded tank is 50.
Rev. A3, 15-Oct-98
5 (23)
U4065B
Functional Description
The U4065B FM-frontend IC is the dedicated solution for hand two or more strong out of channel signals may inter-
high end car radios. A new design philosophy enables to fere and generate an intermodulation signal on the desired
build up tuners with superior behavior. This philosophy frequency. By introducing input attenuation, the level of
is based on the fact that the sensitivity of state of the art the intermod signal decreases by a higher order, whereas
designs is at the physical border and cannot be enhanced the level of the desired signal shows only a linear depen-
any more. On the other hand, the spectral power density dency on the input attenuation. Therefore input
in the FM-band increases. An improvement of reception attenuation by pin diodes may keep up reception in the
can only be achieved by increasing the dynamic range of presence of strong signals.
the receiver. This description is to give the designer an
The standard solution to generate the pin diode current is
introduction to get familiar with this new product and its
to pick up the RF-signal in front of the mixer. Because the
philosophy.
bandwidth at that point is about 1.5 MHz, this is called
wideband AGC. The threshold of AGC start is a critical
1. The Signal Path
parameter. A low threshold does not allow any intermo-
The U4065B offers the complete signal path of an FM-
dulation but has the disadvantage of blocking if there is
frontend including a highly linear mixer and two IF
only one strong station on the band or if the intermod sig-
preamplifiers. The mixer is a double balanced high cur-
nals do not cover the desired channel. A higher AGC
rent Gilbert Cell. A high transit frequency of the internal
threshold may tolerate a certain ground floor of intermo-
transistors enables the use of the emitter grounded circuit
dulation. This avoids blocking, but it has the
with its favorable noise behavior. The full balanced out-
disadvantage, that no reception is possible, if the interfer-
put offers LO carrier reduction.
ing signals do generate an intermod signal inside the
desired channel. This contradiction could not be over-
come in the past.
The following IF preamplifier has a dB-linear gain adjust-
ment by dc means. Thus different ceramic filter losses can
be compensated and the overall tuner gain can be adapted
to the individual requirements. The low noise design sup-
presses post stage noise in the signal path. Input- and
output resistance is 330 to support standard ceramic fil-
ters. This was achieved without feedback, which would
cause different input impedances when varying the output
impedance.
With the new U4065B IC, a unique access to this problem
appears. This product has an interference sensor on chip.
Thus an input signal attenuation is only performed, if the
interfering signals do generate an intermod signal inside
the desired channel. If they do not, the still existing wide-
band AGC is yet active but at up to 20 dB higher levels.
The optimum AGC state is always generated.
The second IF preamplifier enables the use of three ce-
The figures 1 to 4 illustrate the situation. In figure 1 the
AGC threshold of a standard tuner is high to avoid block-
ing. But then the intermod signal suppresses the desired
signal. The interference sensor of the U4065B takes care
that in this case the AGC threshold is kept low as illus-
trated in figure 2.
ramic filters with real 330
input- and output
termination. Feedthrough of signals is kept low. The high
level of output compression is necessary to keep up a high
dynamic range.
Beneath the signal path the local oscillator part and the
AGC signal generation can be found on chip. The local
oscillator uses the collector grounded colpitts type. A low
phase noise is achieved with this access. A mutual cou-
pling in the oscillator coil is not necessary.
In figure 3 the situation is vice versa. The AGC threshold
of a standard tuner is kept low to avoid intermod prob-
lems. But then blocking makes the desired signal level
drop below the necessary stereo level. In this case, the
higher wideband AGC level of the U4065B enables per-
fect stereo reception.
2. The AGC Concept
Special care was taken to design a unique AGC concept.
It offers 3 AGC loops for different kinds of reception
conditions. The most important loop is the interference
sensor part.
By principle, this interference sensor is an element with
a third order characteristic. For input levels of zero, the
output level is zero, too. With increasing input level, the
output level is increased with the power of three, thus pre-
ferring intermod signals compared to linear signals. At
the same time, a down conversion to the IF level of
10.7 MHz is performed. If a corresponding 10.7 MHz IF
filter selects the intermod signals, an output is only gener-
ated, if an intermod signal inside the 10.7 MHz channel
is present.
In today’s high end car radios, the FM AGC is state of the
art. It is necessary to reduce the influence of 3rd and
higher order intermodulation to sustain reception in the
presence of strong signals in the band. On one hand, it
makes a sense to reduce the desired signal level by AGC
as few as possible to keep up stereo reception, on the other
6 (23)
Rev. A3, 15-Oct-98
U4065B
The circuit blocks interference sensor and IF & detector this unique feature.
build up a second IF chain. In an FM system, the max
deviation of a 3rd order intermod signal is the triple max A further narrow band AGC avoids overriding the second
deviation of the desired signal. Therefore the ceramic IF IF amplifier. The amplitude information of the channel is
BPF between Pin 11 and Pin 9 may be a large bandwidth not compressed in order to maintain multipath detection
type. This external part is the only additional amount for in the IF part of the receiver.
94 8821
Level
Level
94 8820
Interfering signals
Interfering signals
Intermod signal
Intermod signal
Desired
signal
Desired
signal
Stereo-level
Noise floor
Stereo-level
Noise floor
Intermod signal
Intermod signal
Desired
frequency
Desired
frequency
Frequency
Frequency
Figure 1 A high AGC threshold causes the intermod
signal to suppress the desired signal
Figure 2 The correct AGC threshold of the U4065B
provides optimum reception
94 8822
94 8823
Level
Level
Strong signal
Strong signal
Desired
signal
Stereo-level
Stereo-level
Desired
signal
Noise floor
Noise floor
Desired
frequency
Desired
frequency
Frequency
Frequency
Figure 3 A low AGC threshold causes the blocking
signal to suppress the desired signal
Figure 4 The correct AGC threshold of the U4065B
provides optimum reception
Rev. A3, 15-Oct-98
7 (23)
U4065B
Absolute Maximum Ratings
Reference point is ground (Pins 2, 8, 14, 20 and 22)
Parameters
Symbol
Value
10
Unit
V
Supply voltage
V
S
Power dissipation at T
Junction temperature
= 85°C
P
470
mW
°C
°C
°C
V
amb
tot
T
125
j
Ambient temperature range
Storage temperature range
T
amb
– 30 to + 85
– 50 to + 125
2000
T
stg
Electrostatic handling:
V
ESD
Human body model (HBM),
all I/O pins tested against the supply pins.
Thermal Resistance
Parameters
Symbol
Maximum
90
Unit
K/W
Thermal resistance
R
thJA
Electrical Characteristics
V = 8.0 V, f = 98 MHz, f
108.7 MHz, f = f
– f = 10.7 MHz
OSC RF
S
RF
OSC
IF
Reference point ground (Pins 2, 8, 14, 20 and 22),T
= 25 C, unless otherwise specified
amb
Parameters
Supply voltage
Test Conditions / Pins
Symbol
Min.
7
Typ.
8
Max.
10
Unit
Pins 3, 6, 10, 18 and 19
Pins 3+6+10+18+19
V
S
V
Supply current
I
37
47
mA
tot
Oscillator
(GND5 has to be connected to external oscillator components)
R
g24
= 220 , unloaded Q
of L
= 70, R = 520
L1
OSC
Pin 24
Pin 23
Pin 1
Pin 1
Pin 1
V
V
160
100
90
LOB
LOE
Oscillator voltage
mV
dBc
V
70
220
–15
LOBUFF
Harmonics
Output resistance
Voltage gain
Mixer
R
70
LO
Between pins 1 and 23
(GND3 has to be separated from GND1, GND2 and GND4)
0.9
Conversion power gain
3rd order input intercept
Conversion transconductance
Noise figure
Source impedance:
= 200
G
5
4
7
6
10
14
dB
dBm
mA/V
dB
k
C
R
G15,16
IP
3
Load impedance:
g
C
8
L18,19
NF
7
DSB
ignd15
ignd15
ignd16
ignd16
ii15,16
ii15,16
Input resistance to ground
Input capacitance to ground
Input resistance to ground
Input capacitance to ground
Input-input resistance
Pin 15
f = 100 MHz
R
C
R
C
R
C
1.2
9
pF
Pin 16
f = 100 MHz
1.6
7
k
pF
Between Pin 15 and Pin 16
Between Pin 15 and Pin 16
1.6
5
k
Input-input capacitance
pF
Output capacitance to GND Pin 18 and Pin 19
First IF preamplifier (IF 1)
C
9
pF
ignd18,19
Gain control deviation by I4 Pin 4
Gain control slope
17
20
24
dB
dG /dI
0.15
dB/ A
IF1
4
8 (23)
Rev. A3, 15-Oct-98
U4065B
Electrical Characteristics (continued)
V = 8.0 V, f = 98 MHz, f
108.7 MHz, f = f
– f = 10.7 MHz
OSC RF
S
RF
OSC
IF
Reference point ground (Pins 2, 8, 14, 20 and 22),T
= 25 C, unless otherwise specified
amb
Parameters
Test Conditions / Pins
Symbol
Min.
Typ.
Max.
Unit
A
External control current to
ground at G
at G
I
0
70
140
min
nom
max
4min
I
4nom
at G
I
4max
Power gain
at I
at I
at I
Between pins 21 and 7
Source impedance:
G
G
G
–2.5
11
19
2
12
22
2.5
16
28
4min
4nom
4max
min
nom
max
dB
R
= 200 ,
G21
Noise figure
at G
at G
at G
NF
NF
NF
7
9
15
max
nom
min
min
nom
max
Load impedance:
dB
R
L7
= 200
Temperature coefficient of
the gain at G
TKnom
+0.045
dB/K
nom
1 dB compression at G
–3 dB cutoff freq. at G
Input resistance
Pin 7
Pin 7
V
70
50
330
5
mV
nom
cnom
f
MHz
nom
cnom
Pin 21
f = 10 MHz
R
C
270
270
400
400
iIF1
iIF1
oIF1
oIF1
Input capacitance
Output resistance
pF
pF
dB
Pin 7
f = 10 MHz
R
C
330
7
Output capacitance
Second IF preamplifier (IF 2)
Power gain
etween pins 5 and 3
Source impedance:
G
15
18
19
IF2
R
G5
= 200
Load impedance:
=200
R
L3
Noise figure
NF
7
500
50
330
12
50
7
dB
mV
IF2
1 dB compression
Pin 3
Pin 3
V
comp
–3 dB cutoff frequency
Parallel input resistance
Parallel input capacitance
Parallel output resistance
Parallel output capacitance
Voltage regulator
f
MHz
c
Pin 5
f = 10 MHz
R
270
400
iIF2
iIF2
oIF2
oIF2
C
pF
k
Pin 3
f = 10 MHz
R
C
pF
Regulated voltage
Pin 17
Pin 17
Pin 17
V
3.7
5
3.9
7
4.9
50
V
ref
Maximum output current
I
mA
ref
Internal differential
resistance,
r
d17
dc /di when I = 0
17 17
17
Power supply suppression
f = 50 Hz, Pin 17
psrr
36
50
dB
AGC input voltage thresholds (AGC threshold current is 10 A at Pin 10)
IF2 input
Pin 5
V
85
42
86
43
92
48
dB V
dB V
thIF2
IF & detector
Pin 9
V
thIFD
Mixer input level of
wideband sensor
Between Pins 15 and 16
f
= 100 MHz
iRF
V at pin 13 = 0 V
I through pin 13 = 0 A
V
thWB1
V
thWB2
95
85
98
87
100
90
dB V
dB V
Rev. A3, 15-Oct-98
9 (23)
U4065B
Test Circuit
4.7n
vo IF
4.7n
vi IF
50
6
2
1
5
1
6
2
Gain IF 1
0 to 140 A
50
5
I4
4
RG5
RL7
vi IF
50
7
20
5
2
50
1
vo IF
I3
5
2
1
6
5
2
21
3
6
Vs
RG21
4.7n
RL3
IF 1
IF 2
I18,19
Vs
vo IF
V
I10
10
13
18
AGC
block
2
6
5
1
50
I13 R13
AGC adjust
RL18,19
19
14
(wide band)
Mixer
4.7n
15
16
2
6
6
5
Voltage
Vs
RG15,16
regulator
I6
50
1
4.7n
1
Vref = 4 V
RG9
Interference
mixer
vi RF
17
8 p
Rg24
24
23
4.7n
Local
Interference
amplifier
9
2
6
47p
33p
oscillator
fosc
Cosc
Losc
1
5
50
8
11
1
12
22
vi IF
RLOBUFF
470p
RG11
Z/Ohm
50 200
vo IF
1
2
1
2
4
RF Transformers MCL
Type TMO 4 – 1
IL = 0.7 dB
50
vLOBUFF
fLOBUFF
6
5
RL1
94 8829
4.7n
0
0
5
6
10 (23)
Rev. A3, 15-Oct-98
U4065B
Local Oscillator
R
g24
v
OSC24
24
23
Local
oscillator
47p
33p
f
OSC
Oscillator
output
v
, f
OSC1 OSC
1
buffer
520
T
amb
94 9410
Free running oscillator frequency f
110 MHz, v
= 160 mV, R =220 , Q = 70
OSC24 g24 L
OSC
180
160
140
120
100
80
60
40
20
0
–30
–10
10
30
50
( °C )
70
90
94 9411
T
amb
Oscillator swing versus temperature
Rev. A3, 15-Oct-98
11 (23)
U4065B
Mixer
f
= 110.7 MHz, v
160 mV, f = 10.7 MHz
OSC
OSC24
IF
voIF
IL2
50
18
19
14
IL1
2viRF1
fRF1
2viRF2
fRF2
1
5
2
1
5
2
6
Mixer
6
50
15
Rg24
24
23
Local
VS
oscillator
47p
22p
fOSC
Tamb
Conversion power gain GC = 20 log (voIF/viRF) + IL1 (dB) + IL2 (dB)
IL1, IL2 insertion loss of the RF transformers
120
Conversion
characteristic
100
3rd order
IM-characteristic
80
60
40
20
0
0
20
40
60
80
100
120
94 9413
vi , vi
( dB V )
RF2
RF1
Characteristic of the mixer
12 (23)
Rev. A3, 15-Oct-98
U4065B
8
7
6
5
4
3
2
1
0
11.0
10.7
10.4
10.1
9.8
9.5
9.2
8.9
8.6
8.3
8.0
–30
–10
10
30
50
( °C )
70
90
–30
–10
10
30
50
( °C )
70
90
94 9414
T
94 9415
T
amb
amb
Conversion power gain of the mixer stage
versus temperature
Current of the mixer stage versus temperature
1st IF Preamplifier
2 : 1
IL2
voIF
50
voIF7
1 : 2
IL1
viIF21 21
Rg21 = 200
7
IF
RL7 = 200
2
2
6
1
1
5
50
Tamb
V(PIN4)
I4
4
fIF
2viIF
6
5
94 9416
Power gain GIF = 20 log (voIF/viIF) + IL1 (dB) + IL2 (dB)
IL1, IL2 = insertion loss of the RF transformers
Rev. A3, 15-Oct-98
13 (23)
U4065B
25
20
15
10
5
25
20
15
10
5
G
max
T = 90°C
G
nom
T = -30°C
G
min
0
0
–5
–10
T = 30°C
–5
0
20
40
60
80 100 120 140
10 20 30 40 50 60 70 80 90 100
f ( MHz )
94 9417
I ( A )
94 9418
4
Power gain of the first IF amplifier versus I4
Power gain of the first IF amplifier versus frequency
3.8
3.6
3.4
T = 90°C
3.2
3.0
T = –30°C
2.8
T = 30°C
2.6
2.4
2.2
2
0
20
40
60
80 100 120 140
94 9419
I ( A )
4
V (Pin 4) versus I
4
14 (23)
Rev. A3, 15-Oct-98
U4065B
2nd IF Preamplifier
VS
330
2 : 1
IL2
3
voIF3
RL3 = 200
voIF
5
1 : 2
viIF5
Rg5 = 200
IF
IL1
1
5
2
2
6
1
5
50
50
fIF
Tamb
6
2viIF
Power gain GIF = 20 log (voIF/viIF) + IL1 (dB) + IL2 (dB)
IL1; IL2 = insertion loss of the RF transformers
94 9420
18.5
18.0
17.5
17.0
16.5
16.0
15.5
20
18
16
14
12
10
8
6
4
2
15
0
–30–20–10 0 10 20 30 40 50 60 70 80 90
10 20 30 40 50 60 70 80 90 100
f ( MHz )
94 9421
T
amb
( °C )
94 9422
Power gain of the second IF amplifier versus tempera-
ture
Power gain of the second IF amplifier versus frequency
Rev. A3, 15-Oct-98
15 (23)
U4065B
87.0
86.8
86.6
86.4
86.2
86.0
10000.00
1000.00
100.00
10.00
1.00
I10 (–30°C ) /
I10 (30°C ) /
I10 (90°C ) /
A
A
A
0.10
0.01
–30
–10
10
30
50
( °C )
70
90
80
85
90
95
100
105
94 9423
T
94 9424
vi ( dB A )
amb
IF
AGC threshold (I10 = 1 A) of the second IF amplifier
versus temperature
AGC characteristic of the second IF amplifier input
Interference Sensor (Mixer)
50
15
16
IL1
RL11 = 200
11
2viRF1
fiRF1
Interference
mixer
2
6
1
5
Rg15/16
=200
IL2
voIF
2viRF2
fiRF2
fIF
1
5
2
6
50
fLO
Local
oscillator
VS
IL1=IL2=0.7dB
94 9425
Test conditions for characteristic voIF versus viRF1
LO = 100 MHz, fRF1 = 89.3 MHz, viRF2 = 0, fIF = fLO – fRF1 = 10.7 MHz
Test conditions for 3rd order IM-characteristic voIF versus viRF1, viRF2
LO = 100 MHz. fRF1 =89.4 MHz, fRF2 = 89.5 MHz, fIF = fLO – (2 fRF1 –1 fRF2) = 10.7 MHz
IL1, IL2 = insertion loss of the RF transformer
:
f
:
f
16 (23)
Rev. A3, 15-Oct-98
U4065B
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
Conversion
characteristic
–30°C
30°C
90°C
3rd order
IM-characteristic
60 65 70 75 80 85 90 95 100
70 75 80 85 90 95 100 105 110 115
vi ( dB V )
94 9426
vi ( dB V )
RF
94 9428
RF
Characteristic of the interference sensor (mixer)
Conversion characteristic of the interference sensor
(mixer)
80
70
60
50
–30°C
40
30°C
90°C
30
20
70 75 80 85 90 95 100 105 110 115
94 9427
vi , vi
( dB V )
RF1
RF2
Third order interference characteristic of the interfer-
ence sensor (mixer)
Interference Sensor (Amplifier)
viIF9
10
9
1 : 2
IL1
VS
IF
I10
Rg9 = 200
2
6
1
5
50
Tamb
fIF
2viIF
94 9429
IL1=0.7dB
Rev. A3, 15-Oct-98
17 (23)
U4065B
AGC Thresholds
45.0
44.5
44.0
43.5
43.0
42.5
42.0
41.5
41.0
105
100
95
88 MHz
90
98 MHz
108 MHz
85
–30–20–10 0 10 20 30 40 50 60 70 80 90
( °C )
0
5
10 15 20 25 30 35 40 45 50 55
94 9430
T
amb
94 9433
I
13
( A )
AGC threshold of the interference IF amplifier versus
temperature
Wideband AGC threshold (I = 1 A) versus I
10
13
100
U13 = 0 V
98
96
94
I13 = 30
A
92
90
88
86
84
82
80
I13 = 0 A
–30–20–10 0 10 20 30 40 50 60 70 80 90
94 9432
T
amb
( °C )
Wideband AGC threshold (I = 1 A)
10
versus temperature
18 (23)
Rev. A3, 15-Oct-98
U4065B
AGC Characteristics
10000.00
1000.00
100.00
10.00
1.00
10000.00
1000.00
100.00
10.00
1.00
–30°C
30°C
90°C
–30°C
30°C
90°C
0.10
0.10
0.01
0.01
35
45
55
65
75
85
95
80 85 90 95 100 105 110 115 120
94 9431
vi ( dB V )
IF
94 9435
vi ( dB V )
RF
AGC characteristic of the interference IF & detector
block
Characteristic of the wideband AGC
(I13 = 0 V)
10000.00
1000.00
100.00
10.00
–30°C
1.00
30°C
0.10
90°C
0.01
90
95
100
105
110
115
120
94 9434
vi ( dB V )
RF
Characteristic of the wideband AGC (V13 = 0 V)
Rev. A3, 15-Oct-98
19 (23)
U4065B
DC Characteristics
18
16
14
12
10
8
3.88
3.87
3.86
3.85
3.84
3.83
3.82
3.81
I6
I18, I19
6
4
2
I3
0
6
6.5 7.0 7.5 8.0 8.5 9.0 9.5 10.0
( V )
–30–20–10 0 10 20 30 40 50 60 70 80 90
94 9436
V
94 9438
T
amb
( °C )
S
Supply currents versus supply voltage
Reference voltage versus temperature
40
4.00
35
30
25
20
15
10
5
I3 + I6 + I18 + I19
3.95
3.90
3.85
3.80
3.75
I6
I18, I19
I3
0
–30
–10
10
30
50
( °C )
70
90
–10
–8
–6
–4
–2
0
2
94 9437
T
94 9439
I
17
( mA )
amb
Supply currents versus temperature
Reference voltage versus I
17
20 (23)
Rev. A3, 15-Oct-98
(Tracking adj.)
R10
1.5k
94 9440
C21
1n
appr. 8mA
R7
56k
R19
10k
R16
15
R4
470
R13
C12
18p
1n
120k
C7
1
2
6
R6
R11
56k
IF
C18
R14
160k
47k
L5
L2
2.2uH
OSC
L6
R17
470
3
D4
4
C8
1n
C13
D5
100p
820
CF3
10p
R5
L4
C22
6.8p
C17
22
1p5
C10
C16
C14
C20 C23
22p 47p
C26
150n
1n 6.8p
4.7p
Q1
13
24
C1
BFR93A
D2
U4065B
3
1
2p7
S391D
4
6
R1
C2
1n
R3
56k
C11
10n
1
12
L3
D3
22
R2
100
C5
D1
10n
CF1
CF2
S392D
C3
R20
22k
R18
330
R15
22
10n
100k
R21
C4
1n
C24
Q2
BC858
C19
22n
CF4
R12
330k
1n
L1
Gain adj.
220nH
C15
100n
R9
220
C25
27p
470n C9
C6
1n
Vs=8.5V
VAGC
ANT
75 OHM
IF OUT
LO OUT
VTUN
1.7–6.5V
U4065B
Part List
Item
Q1
Description
BFR93AR (BFR93A)
BC858
Item
L4
Description
TOKO 7KL–type
# 291ENS 2341IB
Q2
L5
L6
TOKO 7KL–type
# M600BCS-1397N
D1
S392D
D2
S391D
TOKO 7KL–type
# 291ENS 2054IB
D3, 4, 5
L1
BB804
CF1
TOKO type SKM 2
(230 KHZ)
11 turns, 0.35 mm wire, 3 mm
diameter (approx. 220 nH)
CF2, 3, 4
TOKO type SKM 3
(180 KHZ)
L2
L3
2.2 H (high Q type)
TOKO 7KL–type
# 600ENF-7251x
Ordering and Package Information
Extended type number
Package
Remarks
U4065B-AFL
SO 24 plastic
SO 24 plastic
U4065B-AFLG3
Taping according ICE-286-3
Dimensions in mm
9.15
8.65
Package SO24
Dimensions in mm
15.55
15.30
7.5
7.3
2.35
0.25
0.10
0.25
0.4
10.50
10.20
1.27
13.97
24
13
technical drawings
according to DIN
specifications
13037
1
12
22 (23)
Rev. A3, 15-Oct-98
U4065B
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC Semiconductor GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances (ODSs).
The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and
forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban
on these substances.
TEMIC Semiconductor GmbH has been able to use its policy of continuous improvements to eliminate the use of
ODSs listed in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency (EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.
TEMIC Semiconductor GmbH can certify that our semiconductors are not manufactured with ozone depleting
substances and do not contain such substances.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized
application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of,
directly or indirectly, any claim of personal damage, injury or death associated with such unintended or
unauthorized use.
TEMIC Semiconductor GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 (0)7131 67 2594, Fax number: 49 (0)7131 67 2423
Rev. A3, 15-Oct-98
23 (23)
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