CC113LRGPT [TI]
超值系列低于 1GHz 无线接收器 | RGP | 20 | -40 to 85;
| 型号： | CC113LRGPT |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 超值系列低于 1GHz 无线接收器 | RGP | 20 | -40 to 85 电话 蜂窝 无线 电信 蜂窝电话电路 电信电路 |
| 文件： | 总77页 (文件大小：5139K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
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TI德仪州器无线链接品数产手据册
CC113L
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CC113L
www.ti.com.cn
ZHCS268A –MAY 2011–REVISED SEPTEMBER 2011
超值系列 (Value Line) 接收器
1
特性
应用
•
射频 (RF) 性能
•
工作于 315 / 433 / 868 / 915 MHz ISM / SRD 频段
的超低功耗无线应用
无线报警和安全系统
工业监测和控制
遥控
–
接收灵敏度低至 −116 dBm（在 0.6 kbps 数据
速率下）
•
•
•
•
•
–
–
可编程数据速率：范围是 0.6 至 600 kbps
频段：300 - 348 MHz、387 - 464 MHz 和 779
- 928 MHz
玩具
–
支持 2-FSK、4-FSK、GFSK、MSK 和 OOK
家庭和楼宇自动化
•
•
数字特性
常规
–
–
可灵活地支持面向分组的系统
•
极少的外部组件；完全集成于芯片之上的频率合成
对同步字插入、灵活和分组长度及自动 CRC 计
算提供了片上支持
器，无需外部滤波器或 RF 开关
低功耗特性
•
绿色环保型封装：符合 RoHS 标准，并且不含锑或
溴
–
–
200nA 睡眠模式电流消耗
快速启动时间；240 μs（从睡眠模式到接收
[RX] 模式）
•
•
小尺寸（采用 QLP 4x4 mm 封装，20 引脚）
适合那些旨在符合 EN 300 220（欧洲）和 FCC
CFR Part 15（美国）标准的系统
–
64 字节接收 (RX) FIFO
•
支持异步及同步串行发送模式，以返回兼容现有的
射频通信协议
说明
CC113L 是一款成本优化的 sub-1 GHz RF 接收器，适用于 300 - 348 MHz、387 - 464 MHz 和 779 - 928 MHz 频
段。 该电路基于受欢迎的 CC1101 RF 收发器，而且 RF 性能特征相同。 CC115L 发送器与 CC113L 接收器一起
实现了低成本的 RF 链路。
RF 接收器与一个具有高度可配置性的基带解调器实现了集成。 该调制解调器支持各种调制格式，并且具有高达
600 kbps 的可配置数据速率。
CC113L 提供了针对分组处理、数据缓冲和突发传输的丰富硬件支持。
CC113L 的主要工作参数及 64 字节接收 FIFO 可通过一个 SPI 接口进行控制。 在一般系统中，CC113L 将与微控
制器及少量的附加无源组件配合使用。
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CC113L
Abbreviations
Abbreviations used in this data sheet are described below.
2-FSK
4-FSK
ADC
Binary Frequency Shift Keying
Quaternary Frequency Shift Keying
Analog to Digital Converter
LSB
Least Significant Bit
Microcontroller Unit
Most Significant Bit
MCU
MSB
AFC
AGC
AMR
Automatic Frequency Compensation
Automatic Gain Control
Automatic Meter Reading
N/A
NRZ
OOK
Not Applicable
Non Return to Zero (Coding)
On-Off Keying
BER
BT
Bit Error Rate
PCB
PD
Printed Circuit Board
Power Down
Bandwidth-Time product
Code of Federal Regulations
Cyclic Redundancy Check
Carrier Sense
CFR
CRC
CS
PER
PLL
Packet Error Rate
Phase Locked Loop
Power-On Reset
POR
PTAT
QLP
QPSK
RC
DC
Direct Current
Proportional To Absolute Temperature
Quad Leadless Package
Quadrature Phase Shift Keying
Resistor-Capacitor
DVGA
ESR
FCC
FIFO
FS
Digital Variable Gain Amplifier
Equivalent Series Resistance
Federal Communications Commission
First-In-First-Out
RF
Radio Frequency
Frequency Synthesizer
Gaussian shaped Frequency Shift Keying
Intermediate Frequency
In-Phase/Quadrature
RSSI
RX
Received Signal Strength Indicator
Receive, Receive Mode
Surface Mount Device
Serial Peripheral Interface
Short Range Devices
GFSK
IF
SMD
SPI
I/Q
ISM
LC
Industrial, Scientific, Medical
Inductor-Capacitor
SRD
VCO
XOSC
XTAL
Voltage Controlled Oscillator
Crystal Oscillator
LNA
LO
Low Noise Amplifier
Local Oscillator
Crystal
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CC113L
Table Of Contents
APPLICATIONS..................................................................................................................................................1
KEY FEATURES .................................................................................................................................................1
RF PERFORMANCE ..........................................................................................................................................1
DIGITAL FEATURES.........................................................................................................................................1
LOW-POWER FEATURES................................................................................................................................1
GENERAL ............................................................................................................................................................1
PRODUCT DESCRIPTION................................................................................................................................1
ABBREVIATIONS...............................................................................................................................................2
TABLE OF CONTENTS .....................................................................................................................................3
1
2
3
ABSOLUTE MAXIMUM RATINGS.....................................................................................................5
OPERATING CONDITIONS .................................................................................................................5
GENERAL CHARACTERISTICS.........................................................................................................5
4
ELECTRICAL SPECIFICATIONS .......................................................................................................6
CURRENT CONSUMPTION ............................................................................................................................6
RF RECEIVE SECTION..................................................................................................................................8
CRYSTAL OSCILLATOR.............................................................................................................................. 12
FREQUENCY SYNTHESIZER CHARACTERISTICS.......................................................................................... 12
DC CHARACTERISTICS .............................................................................................................................. 13
POWER-ON RESET.....................................................................................................................................13
4.1
4.2
4.3
4.4
4.5
4.6
5
6
PIN CONFIGURATION........................................................................................................................ 13
CIRCUIT DESCRIPTION .................................................................................................................... 15
7
APPLICATION CIRCUIT .................................................................................................................... 15
BIAS RESISTOR ..........................................................................................................................................15
BALUN AND RF MATCHING....................................................................................................................... 15
CRYSTAL ................................................................................................................................................... 18
REFERENCE SIGNAL ..................................................................................................................................18
POWER SUPPLY DECOUPLING.................................................................................................................... 18
PCB LAYOUT RECOMMENDATIONS...........................................................................................................19
7.1
7.2
7.3
7.4
7.5
7.6
8
CONFIGURATION OVERVIEW........................................................................................................20
CONFIGURATION SOFTWARE........................................................................................................21
4-WIRE SERIAL CONFIGURATION AND DATA INTERFACE .................................................. 21
9
10
10.1 CHIP STATUS BYTE ...................................................................................................................................22
10.2 REGISTER ACCESS.....................................................................................................................................23
10.3 SPI READ .................................................................................................................................................. 23
10.4 COMMAND STROBES .................................................................................................................................23
10.5 RX FIFO ACCESS......................................................................................................................................24
11
MICROCONTROLLER INTERFACE AND PIN CONFIGURATION ..........................................25
11.1 CONFIGURATION INTERFACE..................................................................................................................... 25
11.2 GENERAL CONTROL AND STATUS PINS .....................................................................................................25
12
13
14
DATA RATE PROGRAMMING..........................................................................................................25
RECEIVER CHANNEL FILTER BANDWIDTH ..............................................................................25
DEMODULATOR, SYMBOL SYNCHRONIZER, AND DATA DECISION..................................26
14.1 FREQUENCY OFFSET COMPENSATION........................................................................................................26
14.2 BIT SYNCHRONIZATION............................................................................................................................. 27
14.3 BYTE SYNCHRONIZATION.......................................................................................................................... 27
15
PACKET HANDLING HARDWARE SUPPORT ..............................................................................27
15.1 PACKET FORMAT.......................................................................................................................................27
15.2 PACKET FILTERING....................................................................................................................................29
15.3 PACKET HANDLING ...................................................................................................................................30
15.4 PACKET HANDLING IN FIRMWARE.............................................................................................................30
16
MODULATION FORMATS.................................................................................................................30
16.1 FREQUENCY SHIFT KEYING....................................................................................................................... 30
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16.2 AMPLITUDE MODULATION ........................................................................................................................ 31
17
RECEIVED SIGNAL QUALIFIERS AND RSSI................................................................................31
17.1 SYNC WORD QUALIFIER............................................................................................................................ 31
17.2 RSSI.......................................................................................................................................................... 32
17.3 CARRIER SENSE (CS).................................................................................................................................33
18
RADIO CONTROL................................................................................................................................ 35
18.1 POWER-ON START-UP SEQUENCE.............................................................................................................36
18.2 CRYSTAL CONTROL...................................................................................................................................37
18.3 VOLTAGE REGULATOR CONTROL..............................................................................................................37
18.4 RECEIVE MODE (RX) ................................................................................................................................ 37
18.5 RX TERMINATION .....................................................................................................................................37
18.6 TIMING ...................................................................................................................................................... 38
19
20
21
RX FIFO.................................................................................................................................................. 38
FREQUENCY PROGRAMMING........................................................................................................40
VCO ......................................................................................................................................................... 40
21.1 VCO AND PLL SELF-CALIBRATION ..........................................................................................................40
22
23
24
VOLTAGE REGULATORS .................................................................................................................40
GENERAL PURPOSE / TEST OUTPUT CONTROL PINS............................................................. 41
ASYNCHRONOUS AND SYNCHRONOUS SERIAL OPERATION..............................................43
24.1 ASYNCHRONOUS SERIAL OPERATION........................................................................................................43
24.2 SYNCHRONOUS SERIAL OPERATION ..........................................................................................................43
25
SYSTEM CONSIDERATIONS AND GUIDELINES.........................................................................43
25.1 SRD REGULATIONS...................................................................................................................................43
25.2 CALIBRATION IN MULTI-CHANNEL SYSTEMS............................................................................................ 44
26
CONFIGURATION REGISTERS........................................................................................................45
26.1 CONFIGURATION REGISTER DETAILS - REGISTERS WITH PRESERVED VALUES IN SLEEP STATE ...............49
26.2 CONFIGURATION REGISTER DETAILS - REGISTERS THAT LOOSE PROGRAMMING IN SLEEP STATE ..........63
26.3 STATUS REGISTER DETAILS....................................................................................................................... 64
27
28
29
DEVELOPMENT KIT ORDERING INFORMATION .....................................................................66
REFERENCES .......................................................................................................................................67
GENERAL INFORMATION................................................................................................................68
29.1 DOCUMENT HISTORY ................................................................................................................................ 68
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1
Absolute Maximum Ratings
Under no circumstances must the absolute maximum ratings given in Table 1 be violated. Stress
exceeding one or more of the limiting values may cause permanent damage to the device.
Parameter
Min
Max
Units Condition
Supply voltage
–0.3
3.9
V
V
All supply pins must have the same voltage
Voltage on any digital pin
–0.3 VDD + 0.3,
max 3.9
Voltage on the pins RF_P, RF_N,
DCOUPL, RBIAS
–0.3
–50
2.0
V
Voltage ramp-up rate
Input RF level
120
+10
150
260
750
kV/µs
dBm
C
Storage temperature range
Solder reflow temperature
ESD
According to IPC/JEDEC J-STD-020
C
V
According to JEDEC STD 22, method A114, Human
Body Model (HBM)
ESD
400
V
According to JEDEC STD 22, C101C, Charged Device
Model (CDM)
Table 1: Absolute Maximum Ratings
Caution! ESD sensitive device. Precaution should be
used when handling the device in order to prevent
permanent damage.
2
Operating Conditions
The operating conditions for CC113L are listed in Table 2 below.
Parameter
Min
–40
1.8
Max
85
Unit
C
Condition
Operating temperature
Operating supply voltage
3.6
V
All supply pins must have the same voltage
Table 2: Operating Conditions
3
General Characteristics
Parameter
Min
300
387
Max
348
464
Unit
MHz
MHz
Condition/Note
Frequency range
If using a 27 MHz crystal, the lower frequency limit for this band
is 392 MHz
779
0.6
0.6
0.6
928
500
250
300
MHz
Data rate
kBaud
kBaud
kBaud
2-FSK
GFSK and OOK
4-FSK (the data rate in kbps will be twice the baud rate)
Optional Manchester encoding (the data rate in kbps will be half
the baud rate)
Table 3: General Characteristics
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CC113L
4
Electrical Specifications
4.1
Current Consumption
TA = 25 C, VDD = 3.0 V if nothing else stated. All measurement results are obtained using [1] and [2]. Reduced current settings
(MDMCFG2.DEM_DCFILT_OFF=1) gives a slightly lower current consumption at the cost of a reduction in sensitivity. See Table
5 for additional details on current consumption and sensitivity.
Parameter
Min
Typ Max Unit Condition
Current consumption
in power down modes
0.2
1
Voltage regulator to digital part off, register values retained (SLEEP
state). All GDO pins programmed to 0x2F (HW to 0)
A
100
Voltage regulator to digital part off, register values retained, XOSC
A
running (SLEEP state with MCSM0.OSC_FORCE_ONset)
165
1.7
Voltage regulator to digital part on, all other modules in power down
(XOFF state)
A
Current consumption
mA
Only voltage regulator to digital part and crystal oscillator running (IDLE
state)
8.4
mA
The current consumption for the intermediate states when going from
IDLE to RX, including the calibration state
Current consumption,
315 MHz
15.4
14.4
mA
mA
Receive mode, 1.2 kBaud, reduced current, input at sensitivity limit
Receive mode, 1.2 kBaud, register settings optimized for reduced
current, input well above sensitivity limit
15.2
14.3
16.5
15.1
16.0
15.0
15.7
15.0
17.1
15.7
mA
mA
mA
mA
mA
mA
mA
mA
mA
mA
Receive mode, 38.4 kBaud, register settings optimized for reduced
current, input at sensitivity limit
Receive mode, 38.4 kBaud, register settings optimized for reduced
current, input well above sensitivity limit
Receive mode, 250 kBaud, register settings optimized for reduced
current, input at sensitivity limit
Receive mode, 250 kBaud, register settings optimized for reduced
current, input well above sensitivity limit
Current consumption,
433 MHz
Receive mode, 1.2 kBaud, register settings optimized for reduced
current, input at sensitivity limit
Receive mode, 1.2 kBaud, register settings optimized for reduced
current, input well above sensitivity limit
Receive mode, 38.4 kBaud, register settings optimized for reduced
current, input at sensitivity limit
Receive mode, 38.4 kBaud, register settings optimized for reduced
current, input well above sensitivity limit
Receive mode, 250 kBaud, register settings optimized for reduced
current, input at sensitivity limit
Receive mode, 250 kBaud, register settings optimized for reduced
current, input well above sensitivity limit
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Parameter
Min
Typ Max Unit Condition
Current consumption,
868/915 MHz
15.7
14.7
15.6
14.6
16.9
15.6
mA
mA
mA
mA
mA
mA
Receive mode, 1.2 kBaud, register settings optimized for reduced
current, input at sensitivity limit. See Figure 1 for current consumption
with register settings optimized for sensitivity.
Receive mode, 1.2 kBaud, register settings optimized for reduced
current, input well above sensitivity limit. See Figure 1 for current
consumption with register settings optimized for sensitivity.
Receive mode, 38.4 kBaud, register settings optimized for reduced
current, input at sensitivity limit. See Figure 1 for current consumption
with register settings optimized for sensitivity.
Receive mode, 38.4 kBaud, register settings optimized for reduced
current, input well above sensitivity limit. See Figure 1 for current
consumption with register settings optimized for sensitivity.
Receive mode, 250 kBaud, register settings optimized for reduced
current, input at sensitivity limit. See Figure 1 for current consumption
with register settings optimized for sensitivity.
Receive mode, 250 kBaud, register settings optimized for reduced
current, input well above sensitivity limit. See Figure 1 for current
consumption with register settings optimized for sensitivity.
Table 4: Current Consumption
17,8
17,6
17,4
17,2
17
-40C
+25C
+85C
16,8
16,6
16,4
16,2
-110
-90
-70
-50
-30
-10
-20
-20
Input Power Level [dBm]
1.2 kBaud GFSK
17,8
17,6
17,4
17,2
17,0
16,8
16,6
16,4
16,2
-40C
+25C
+85C
-100
-80
-60
-40
Input Power Level [dBm]
38.4 kBaud GFSK
19,5
19
18,5
18
-40C
+25C
+85C
17,5
17
16,5
-100
-80
-60
-40
Input Power Level [dBm]
250 kBaud GFSK
Figure 1: Typical RX Current Consumption over Temperature and Input Power Level,
868/915 MHz, Sensitivity Optimized Setting
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4.2
RF Receive Section
TA = 25 C, VDD = 3.0 V if nothing else stated. All measurement results are obtained using [1] and [2].
Parameter
Min
Typ
Max
Unit Condition/Note
Digital channel
filter bandwidth
58
812
kHz User programmable. The bandwidth limits are proportional to crystal
frequency (given values assume a 26.0 MHz crystal)
dBm 25 MHz - 1 GHz
Spurious
emissions
–68
–66
–57
–47
(Maximum figure is the ETSI EN 300 220 V2.3.1 limit)
dBm Above 1 GHz
(Maximum figure is the ETSI EN 300 220 V2.3.1 limit)
Typical radiated spurious emission is –49 dBm measured at the VCO
frequency
RX latency
9
bit
Serial operation. Time from start of reception until data is available on the
receiver data output pin is equal to 9 bit
315 MHz
1.2 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(2-FSK, 1% packet error rate, 20 bytes packet length, 5.2 kHz deviation, 58 kHz digital channel filter bandwidth)
Receiver
sensitivity
–111
dBm Sensitivity can be traded for current consumption by setting
MDMCFG2.DEM_DCFILT_OFF=1. The typical current consumption is then
reduced from 17.2 mA to 15.4 mA at the sensitivity limit. The sensitivity is
typically reduced to -109 dBm
433 MHz
0.6 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(GFSK, 1% packet error rate, 20 bytes packet length, 14.3 kHz deviation, 58 kHz digital channel filter bandwidth)
Receiver
–116
dBm
sensitivity
1.2 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(GFSK, 1% packet error rate, 20 bytes packet length, 5.2 kHz deviation, 58 kHz digital channel filter bandwidth)
Receiver
sensitivity
–112
dBm Sensitivity can be traded for current consumption by setting
MDMCFG2.DEM_DCFILT_OFF=1. The typical current consumption is then
reduced from 18.0 mA to 16.0 mA at the sensitivity limit. The sensitivity is
typically reduced to –110 dBm
38.4 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(GFSK, 1% packet error rate, 20 bytes packet length, 20 kHz deviation, 100 kHz digital channel filter bandwidth)
Receiver
–104
dBm
sensitivity
250 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(GFSK, 1% packet error rate, 20 bytes packet length, 127 kHz deviation, 540 kHz digital channel filter bandwidth)
Receiver
–95
dBm
sensitivity
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Parameter
Min
Typ
Max
Unit Condition/Note
868/915 MHz
1.2 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(GFSK, 1% packet error rate, 20 bytes packet length, 5.2 kHz deviation, 58 kHz digital channel filter bandwidth)
Receiver sensitivity
–112
dBm Sensitivity can be traded for current consumption by setting
MDMCFG2.DEM_DCFILT_OFF=1. The typical current
consumption is then reduced from 17.7 mA to 15.7 mA at
sensitivity limit. The sensitivity is typically reduced to –109 dBm
Saturation
–14
dBm
FIFOTHR.CLOSE_IN_RX=0.See more in DN010 [5]
Adjacent channel rejection
±100 kHz offset
Desired channel 3 dB above the sensitivity limit.
100 kHz channel spacing
37
31
dB
dB
See Figure 2 for selectivity performance at other offset
frequencies
Image channel rejection
IF frequency 152 kHz
Desired channel 3 dB above the sensitivity limit
Blocking
Desired channel 3 dB above the sensitivity limit
±2 MHz offset
±10 MHz offset
–50
–40
dBm See Figure 2 for blocking performance at other offset
dBm frequencies
38.4 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(GFSK, 1% packet error rate, 20 bytes packet length, 20 kHz deviation, 100 kHz digital channel filter bandwidth)
Receiver sensitivity
–104
dBm Sensitivity can be traded for current consumption by setting
MDMCFG2.DEM_DCFILT_OFF=1. The typical current
consumption is then reduced from 17.7 mA to 15.6 mA at the
sensitivity limit. The sensitivity is typically reduced to -102 dBm
Saturation
–16
dBm
FIFOTHR.CLOSE_IN_RX=0.See more in DN010 [5]
Adjacent channel rejection
–200 kHz offset
+200 kHz offset
Desired channel 3 dB above the sensitivity limit.
200 kHz channel spacing
See Figure 3 for blocking performance at other offset
frequencies
12
25
dB
dB
Image channel rejection
23
dB
IF frequency 152 kHz
Desired channel 3 dB above the sensitivity limit
Blocking
Desired channel 3 dB above the sensitivity limit
±2 MHz offset
±10 MHz offset
–50
–40
dBm See Figure 3 for blocking performance at other offset
dBm frequencies
250 kBaud data rate, sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(GFSK, 1% packet error rate, 20 bytes packet length, 127 kHz deviation, 540 kHz digital channel filter bandwidth)
Receiver sensitivity
–95
dBm Sensitivity can be traded for current consumption by setting
MDMCFG2.DEM_DCFILT_OFF=1. The typical current
consumption is then reduced from 18.9 mA to 16.9 mA at the
sensitivity limit. The sensitivity is typically reduced to –91 dBm
Saturation
–17
dBm
dB
FIFOTHR.CLOSE_IN_RX=0. See more in DN010 [5]
Adjacent channel rejection
25
Desired channel 3 dB above the sensitivity limit.
750 kHz channel spacing
See Figure 4 for blocking performance at other offset
frequencies
Image channel rejection
14
dB
IF frequency 304 kHz
Desired channel 3 dB above the sensitivity limit
Blocking
Desired channel 3 dB above the sensitivity limit
±2 MHz offset
±10 MHz offset
–50
–40
dBm See Figure 4 for blocking performance at other offset
dBm frequencies
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Parameter
Min
Typ
Max
Unit
Condition/Note
4-FSK, 125 kBaud data rate (250 kbps), sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(1% packet error rate, 20 bytes packet length, 127 kHz deviation, 406 kHz digital channel filter bandwidth)
Receiver sensitivity
–96
dBm
4-FSK, 250 kBaud data rate (500 kbps), sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(1% packet error rate, 20 bytes packet length, 254 kHz deviation, 812 kHz digital channel filter bandwidth
Receiver sensitivity
–91
dBm
4-FSK, 300 kBaud data rate (600 kbps), sensitivity optimized, MDMCFG2.DEM_DCFILT_OFF=0
(1% packet error rate, 20 bytes packet length, 228 kHz deviation, 812 kHz digital channel filter bandwidth)
Receiver sensitivity
–89
dBm
Table 5: RF Receive Section
Supply Voltage
VDD = 1.8 V
Supply Voltage
VDD = 3.0 V
Supply Voltage
VDD = 3.6 V
Temperature [°C]
–40
–113
–105
–97
25
85
–40
–113
–105
–97
25
85
–40
25
85
Sensitivity [dBm] 1.2 kBaud
Sensitivity [dBm] 38.4 kBaud
Sensitivity [dBm] 250 kBaud
Sensitivity [dBm] 500 kBaud
–112
–104
–96
–110
–102
–92
–112
–104
–95
–110
–102
–92
–113
–105
–97
–112
–104
–94
–110
–102
–92
–91
–90
–86
–91
–90
–86
–91
–90
–86
Table 6: Typical Sensitivity over Temperature and Supply Voltage, 868 MHz,
Sensitivity Optimized Setting
Supply Voltage
VDD = 1.8 V
Supply Voltage
VDD = 3.0 V
Supply Voltage
VDD = 3.6 V
Temperature [°C]
–40
–113
–105
–97
25
85
–40
–113
–104
–97
25
85
–40
–113
–105
–97
25
85
Sensitivity [dBm] 1.2 kBaud
Sensitivity [dBm] 38.4 kBaud
Sensitivity [dBm] 250 kBaud
Sensitivity [dBm] 500 kBaud
–112
–104
–94
–110
–102
–92
–112
–104
–95
–110
–102
–92
–112
–104
–95
–110
–102
–92
–91
–89
–86
–91
–90
–86
–91
–89
–86
Table 7: Typical Sensitivity over Temperature and Supply Voltage, 915 MHz,
Sensitivity Optimized Setting
80
70
60
50
40
30
20
10
0
60
50
40
30
20
10
0
-40
-30
-20
-10
0
10
20
30
40
-10
-1 -0,9 -0,8 -0,7 -0,6 -0,5 -0,4 -0,3 -0,2 -0,1
0
0,1 0,2 0,3 0,4 0,5 0,6 0,7 0,8 0,9
1
-20
-10
Offset [MHz]
Offset [MHz]
Figure 2: Typical Selectivity at 1.2 kBaud Data Rate, 868.3 MHz, GFSK, 5.2 kHz Deviation.
IF Frequency is 152.3 kHz and the Digital Channel Filter Bandwidth is 58 kHz
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70
60
50
40
30
20
10
0
50
40
30
20
10
0
-1 -0,9 -0,8 -0,7 -0,6 -0,5 -0,4 -0,3 -0,2 -0,1
0
0,1 0,2 0,3 0,4 0,5 0,6 0,7 0,8 0,9
1
-40
-30
-20
-10
0
10
20
30
40
-10
-20
-10
-20
Offset [MHz]
Offset [MHz]
Figure 3: Typical Selectivity at 38.4 kBaud Data Rate, 868 MHz, GFSK, 20 kHz Deviation.
IF Frequency is 152.3 kHz and the Digital Channel Filter Bandwidth is 100 kHz
60
50
40
30
20
10
0
50
40
30
20
10
0
-2
-1,5
-1
-0,5
0
0,5
1
1,5
2
-40
-30
-20
-10
0
10
20
30
40
-10
-20
-10
-20
Offset [MHz]
Offset [MHz]
Figure 4: Typical Selectivity at 250 kBaud Data Rate, 868 MHz, GFSK,
IF Frequency is 304 kHz and the Digital Channel Filter Bandwidth is 540 kHz
60
50
40
30
20
10
0
40
30
20
10
0
-40
-30
-20
-10
0
10
20
30
40
-2
-1,5
-1
-0,5
0
0,5
1
1,5
2
-10
-20
-30
-10
-20
Offset [MHz]
Offset [MHz]
Figure 5: Typical Selectivity at 500 kBaud Data Rate, 868 MHz, GFSK,
IF Frequency is 355 kHz and the Digital Channel Filter Bandwidth is 812 kHz
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CC113L
4.3 Crystal Oscillator
TA = 25 C, VDD = 3.0 V if nothing else is stated. All measurement results obtained using [1] and [2].
Parameter
Min Typ Max Unit Condition/Note
Crystal
26
26
27
MHz For compliance with modulation bandwidth requirements under EN 300 220
frequency
V2.3.1 in the 863 to 870 MHz frequency range it is recommended to use a 26
MHz crystal for frequencies below 869 MHz and a 27 MHz crystal for frequencies
above 869 MHz
Tolerance
±40
13
ppm This is the total tolerance including a) initial tolerance, b) crystal loading, c)
aging, and d) temperature dependence. The acceptable crystal tolerance
depends on RF frequency and channel spacing / bandwidth.
Load
10
20
pF
Simulated over operating conditions
capacitance
ESR
100
Start-up time
150
µs
This parameter is to a large degree crystal dependent. Measured on [1] and [2]
using crystal AT-41CD2 from NDK
Table 8: Crystal Oscillator Parameters
4.4 Frequency Synthesizer Characteristics
TA = 25 C, VDD = 3.0 V if nothing else is stated. All measurement results are obtained using [1] and [2]. Min figures are given
using a 27 MHz crystal. Typ. and max figures are given using a 26 MHz crystal
Parameter
Min
Typ
Max
Unit
Condition/Note
Programmed frequency
resolution
397
FXOSC/216
412
Hz
26 - 27 MHz crystal. The resolution (in Hz) is equal for all
frequency bands
Synthesizer frequency
tolerance
±40
ppm
Given by crystal used. Required accuracy (including
temperature and aging) depends on frequency band and
channel bandwidth / spacing
RF carrier phase noise
RF carrier phase noise
RF carrier phase noise
RF carrier phase noise
RF carrier phase noise
RF carrier phase noise
RF carrier phase noise
RF carrier phase noise
–92
–92
dBc/Hz
dBc/Hz
dBc/Hz
dBc/Hz
dBc/Hz
dBc/Hz
dBc/Hz
dBc/Hz
s
@ 50 kHz offset from carrier
@ 100 kHz offset from carrier
@ 200 kHz offset from carrier
@ 500 kHz offset from carrier
@ 1 MHz offset from carrier
@ 2 MHz offset from carrier
@ 5 MHz offset from carrier
@ 10 MHz offset from carrier
–92
–98
–107
–113
–119
–129
75
PLL turn-on time
( See Table 26)
72
75
Time from leaving the IDLE state until arriving in the RX
state, when not performing calibration. Crystal oscillator
running.
PLL calibration time
(See Table 27)
685
712
724
Calibration can be initiated manually or automatically
before entering or after leaving RX
s
Table 9: Frequency Synthesizer Parameters
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4.5 DC Characteristics
TA = 25 C if nothing else stated.
Digital Inputs/Outputs
Min
Max
0.7
Unit
V
Condition
Logic "0" input voltage
0
Logic "1" input voltage
Logic "0" output voltage
Logic "1" output voltage
Logic "0" input current
Logic "1" input current
VDD – 0.7
0
VDD
0.5
V
V
For up to 4 mA output current
For up to 4 mA output current
Input equals 0 V
VDD – 0.3
N/A
VDD
–50
50
V
nA
nA
N/A
Input equals VDD
Table 10: DC Characteristics
4.6 Power-On Reset
For proper Power-On-Reset functionality the power supply should comply with the requirements in
Table 11 below. Otherwise, the chip should be assumed to have unknown state until transmitting an
SRESstrobe over the SPI interface. See Section 18.1 on page 36 for further details.
Parameter
Min
Typ
Max
Unit
Condition/Note
Power-up ramp-up time
Power off time
5
ms
ms
From 0V until reaching 1.8V
1
Minimum time between power-on and power-off
Table 11: Power-On Reset Requirements
5
Pin Configuration
The CC113L pin-out is shown in Figure 6 and Table 12. See Section 23 for details on the I/O
configuration.
20 19 18 17 16
SCLK 1
SO (GDO1) 2
GDO2 3
15 AVDD
14 AVDD
13 RF_N
12 RF_P
11 AVDD
DVDD 4
DCOUPL 5
GND
Exposed die
attach pad
6
7
8
9 10
Figure 6: Pinout Top View
Note: The exposed die attach pad must be connected to a solid ground plane as this is the main
ground connection for the chip
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Pin #
Pin Name
Pin type
Description
1
2
SCLK
Digital Input
Digital Output
Serial configuration interface, clock input
Serial configuration interface, data output
Optional general output pin when CSn is high
Digital output pin for general use:
Test signals
SO
(GDO1)
3
GDO2
Digital Output
FIFO status signals
Clock output, down-divided from XOSC
Serial output RX data
4
5
DVDD
Power (Digital)
Power (Digital)
1.8 - 3.6 V digital power supply for digital I/O‟s and for the digital core voltage
regulator
DCOUPL
1.6 - 2.0 V digital power supply output for decoupling
NOTE: This pin is intended for use with the CC113L only. It cannot be used to provide
supply voltage to other devices
6
GDO0
Digital I/O
Digital output pin for general use:
Test signals
FIFO status signals
Clock output, down-divided from XOSC
Serial output RX data
7
CSn
Digital Input
Serial configuration interface, chip select
Crystal oscillator pin 1, or external clock input
1.8 - 3.6 V analog power supply connection
Crystal oscillator pin 2
8
XOSC_Q1 Analog I/O
9
AVDD
Power (Analog)
10
11
12
13
14
15
16
17
18
19
20
XOSC_Q2 Analog I/O
AVDD
RF_P
RF_N
AVDD
AVDD
GND
Power (Analog)
1.8 - 3.6 V analog power supply connection
Positive RF input signal to LNA in receive mode
Negative RF input signal to LNA in receive mode
1.8 - 3.6 V analog power supply connection
1.8 - 3.6 V analog power supply connection
RF I/O
RF I/O
Power (Analog)
Power (Analog)
Ground (Analog) Analog ground connection
RBIAS
DGUARD
GND
Analog I/O
External bias resistor for reference current
Power (Digital)
Ground (Digital)
Digital Input
Power supply connection for digital noise isolation
Ground connection for digital noise isolation
Serial configuration interface, data input
SI
Table 12: Pinout Overview
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6
Circuit Description
RADIO CONTROL
SCLK
ADC
ADC
RF_P
SO (GDO1)
LNA
SI
RF_N
CSn
FREQ
SYNTH
0
GDO0
GDO2
90
BIAS
XOSC
XOSC_Q1 XOSC_Q2
RBIAS
Figure 7: CC113L Simplified Block Diagram
signals to the down-conversion mixers in
receive mode.
A simplified block diagram of CC113L is shown
in Figure 7.
A crystal is to be connected to XOSC_Q1 and
XOSC_Q2. The crystal oscillator generates the
reference frequency for the synthesizer, as
well as clocks for the ADC and the digital part.
CC113L features a low-IF receiver. The received
RF signal is amplified by the low-noise
amplifier (LNA) and down-converted in
quadrature (I and Q) to the intermediate
frequency (IF). At IF, the I/Q signals are
digitised by the ADCs. Automatic gain control
(AGC), fine channel filtering, demodulation,
and bit/packet synchronization are performed
digitally.
A 4-wire SPI serial interface is used for
configuration and data buffer access.
The digital baseband includes support for
channel configuration, packet handling, and
data buffering.
The frequency synthesizer includes
a
completely on-chip LC VCO and a 90 degree
phase shifter for generating the I and Q LO
7
Application Circuit
Figure 8 shows the low cost CC113LEM
application circuit ([10] and [11]) (see Table 13
for component values).
The designs in [1] and [2] were used for CC113L
characterization. The application circuits are
shown in Figure 9 and Figure 10 (see Table 14
for component values).
7.1 Bias Resistor
The 56 kΩ bias resistor R171 is used to set an
accurate bias current
7.2 Balun and RF Matching
The balun component values and their
placement are important to keep the
performance optimized. Gerber files and
schematics for the reference designs are
available for download from the TI website
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7.2.1 Balun and RF Matching (low cost
application circuit)
differential RF signal on CC113L. C124 is
needed for DC blocking.
The components between the RF_N/RF_P
pins and the point where the two signals are
joined together (C131, L132, C122, L122, see
Figure 8) form a balun that converts single-
The balun components also matches the
CC113L input impedance to a 50
source.
C126 provides DC blocking and is only
needed if there is a DC path in the antenna.
ended RF signal at the antenna to
a
1.8 V - 3.6 V
power supply
R171
SI
Antenna
(50 Ohm)
SCLK
1 SCLK
AVDD 15
C131
SO (GDO1)
2 SO
(GDO1)
AVDD 14
RF_N 13
RF_P 12
AVDD 11
L132
C126
GDO2 (optional)
CC113L
3 GDO2
DIE ATTACH PAD:
4 DVDD
C122
5 DCOUPL
L122
C124
C51
GDO0 (optional)
CSn
XTAL
C81
C101
Figure 8: Low Cost Application Circuit and Evaluation Circuit 315/433/868/915 MHz
(excluding supply decoupling capacitors) ([10] and [11])
Component Value at 315 MHz Value at 433 MHz Value at 868/915 MHz
C124
C122
C126
C131
L122
L132
220 pF
6.8 pF
220 pF
6.8 pF
33 nH
33 nH
220 pF
3.9 pF
220 pF
3.9 pF
27 nH
27 nH
100 pF
2.2 pF
100 pF
2.2 pF
12 nH
12 nH
Table 13: External Components (low cost application circuit)
C126 provides DC blocking and is only
needed if there is a DC path in the antenna.
7.2.2 Balun
and
RF
Matching
(characterization circuit)
Note that the 315/433 MHz design [1] use
Murata LQG15 multi-layer inductors while the
868/915 MHz design [2] use Murata LQW15
wire-wound inductors.
The components between the RF_N/RF_P
pins and the point where the two signals are
joined together (C131, C122, L122, and L132
in Figure 9 and L121, L131, C121, L122,
C131, C122, and L132 in Figure 10) form a
balun that converts single-ended RF signal at
the antenna to a differential RF signal on
CC113L. C124 is needed for DC blocking.
L123, L124, and C123 ( plus C125 in Figure 9)
form an LC low-pass filter. This filter is not
required for an RX-only design and can be
omitted.
The balun components also matches the
CC113L input impedance to a 50
source.
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CC113L
1.8 V - 3.6 V
power supply
R171
SI
Antenna
(50 Ohm)
SCLK
1 SCLK
AVDD 15
C131
L132
SO
2 SO
(GDO1)
AVDD 14
RF_N 13
RF_P 12
AVDD 11
(GDO1)
GDO2
(optional)
C126
C125
CC113L
3 GDO2
DIE ATTACH PAD:
4 DVDD
L123
L124
C123
C122
5 DCOUPL
L122
C124
C51
GDO0
(optional)
CSn
XTAL
C81
C101
Figure 9: Characterization Circuit 315/433 MHz (excluding supply decoupling capacitors) ([1])
1.8 V - 3.6 V
power supply
R171
SI
Antenna
(50 Ohm)
C131
L132
SCLK
1 SCLK
AVDD 15
SO
2 SO
(GDO1)
L131
L121
AVDD 14
RF_N 13
RF_P 12
AVDD 11
(GDO1)
GDO2
(optional)
C126
3 GDO2
L123
L124
CC113L
C121 C122
4 DVDD
DIE ATTACH PAD:
5 DCOUPL
C123
L122
C124
C51
GDO0
(optional)
CSn
XTAL
C81
C101
Figure 10: Characterization Circuit 868/915 MHz (excluding supply decoupling capacitors) ([2])
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Component Value at 315 MHz Value at 433 MHz Value at 868/915 MHz
C121
C122
C123
C124
C125
C126
C131
L121
L122
L123
L124
L131
L132
1 pF
6.8 pF
12 pF
3.9 pF
8.2 pF
220 pF
5.6 pF
220 pF
3.9 pF
1.5 pF
3.3 pF
100 pF
220 pF
6.8 pF
220 pF
6.8 pF
100 pF
1.5 pF
12 nH
18 nH
12 nH
12 nH
12 nH
18 nH
33 nH
18 nH
33 nH
27 nH
22 nH
27 nH
33 nH
27 nH
Table 14: External Components (characterization circuits)
7.3 Crystal
A crystal in the frequency range 26 - 27 MHz
must be connected between the XOSC_Q1and
XOSC_Q2 pins. The oscillator is designed for
parallel mode operation of the crystal. In
addition, loading capacitors (C81 and C101)
for the crystal are required. The loading
capacitor values depend on the total load
capacitance, CL, specified for the crystal. The
total load capacitance seen between the
crystal terminals should equal CL for the
crystal to oscillate at the specified frequency.
up the oscillations. When the amplitude builds
up, the current is reduced to what is necessary
to maintain approximately 0.4 Vpp signal
swing. This ensures a fast start-up, and keeps
the drive level to a minimum. The ESR of the
crystal should be within the specification in
order to ensure
a
reliable start-up
(see Section 4.3 on page 12).
The initial tolerance, temperature drift, aging
and load pulling should be carefully specified
in order to meet the required frequency
accuracy in a certain application.
1
CL
Cparasitic
1
1
Avoid routing digital signals with sharp edges
close to XOSC_Q1 PCB track or underneath
the crystal Q1 pad as this may shift the crystal
dc operating point and result in duty cycle
variation.
C81 C101
The parasitic capacitance is constituted by pin
input capacitance and PCB stray capacitance.
Total parasitic capacitance is typically 2.5 pF.
The crystal oscillator is amplitude regulated.
This means that a high current is used to start
7.4 Reference Signal
The chip can alternatively be operated with a
reference signal from 26 - 27 MHz instead of a
crystal. This input clock can either be a full-
swing digital signal (0 V to VDD) or a sine
wave of maximum 1 V peak-peak amplitude.
The reference signal must be connected to the
XOSC_Q1 input. The sine wave must be
connected to XOSC_Q1 using
a
serial
capacitor. When using a full-swing digital
signal, this capacitor can be omitted. The
XOSC_Q2 line must be left un-connected. C81
and C101 can be omitted when using a
reference signal.
7.5
Power Supply Decoupling
The power supply must be properly decoupled
close to the supply pins. Note that decoupling
capacitors are not shown in the application
circuit. The placement and the size of the
decoupling capacitors are very important to
achieve the optimum performance. The
CC113LEM reference designs ([10] and [11])
should be followed closely.
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7.6
PCB Layout Recommendations
The top layer should be used for signal
routing, and the open areas should be filled
with metallization connected to ground using
several vias.
Each decoupling capacitor ground pad should
be connected to the ground plane by separate
vias. Direct connections between neighboring
power pins will increase noise coupling and
should be avoided unless absolutely
necessary. Routing in the ground plane
underneath the chip or the balun/RF matching
circuit, or between the chip‟s ground vias and
the decoupling capacitor‟s ground vias should
be avoided. This improves the grounding and
ensures the shortest possible current return
path.
The area under the chip is used for grounding
and shall be connected to the bottom ground
plane with several vias for good thermal
performance and sufficiently low inductance to
ground.
In the CC113LEM reference designs ([10] and
[11]), 5 vias are placed inside the exposed die
attached pad. These vias should be “tented”
(covered with solder mask) on the component
side of the PCB to avoid migration of solder
through the vias during the solder reflow
process.
Avoid routing digital signals with sharp edges
close to XOSC_Q1 PCB track or underneath
the crystal Q1 pad as this may shift the crystal
dc operating point and result in duty cycle
variation.
The solder paste coverage should not be
100%. If it is, out gassing may occur during the
reflow process, which may cause defects
(splattering, solder balling). Using “tented” vias
reduces the solder paste coverage below
100%. See Figure 11 for top solder resist and
top paste masks.
The external components should ideally be as
small as possible (0402 is recommended) and
surface
mount
devices
are
highly
recommended. Please note that components
with different sizes than those specified may
have differing characteristics.
Precaution should be used when placing the
microcontroller in order to avoid noise
interfering with the RF circuitry.
Each decoupling capacitor should be placed
as close as possible to the supply pin it is
supposed to decouple. Each decoupling
capacitor should be connected to the power
line (or power plane) by separate vias. The
best routing is from the power line (or power
plane) to the decoupling capacitor and then to
the CC113L supply pin. Supply power filtering is
very important.
A CC11xL Development Kit with a fully
assembled CC113L Evaluation Module is
available. It is strongly advised that this
reference layout is followed very closely in
order to get the best performance. The
schematic, BOM and layout Gerber files are all
available from the TI website ([10] and [11]).
Figure 11: Left: Top Solder Resist Mask (Negative). Right: Top Paste Mask. Circles are Vias
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8
Configuration Overview
CC113L can be configured to achieve optimum
performance for many different applications.
Configuration is done using the SPI interface.
See Section 10 for more description of the SPI
interface. The following key parameters can be
programmed:
RX channel filter bandwidth
Data buffering with the 64-byte RX FIFO
Packet radio hardware support
Details of each configuration register can be
found in Section 26 starting on page 45.
Figure 12 shows a simplified state diagram
that explains the main CC113L states together
with typical usage and current consumption.
For detailed information on controlling the
CC113L state machine, and a complete state
diagram, see Section 18, starting on page 35.
Power-down / power up mode
Crystal oscillator power-up / power-down
Receive mode
Carrier Frequency / RF channel
Data rate
Modulation format
Lowest power mode. Most
Sleep
register values are retained.
Typ. current consumption:
SPWD
SIDLE
200 nA
Default state when the radio is not
receiving. Typ. current
CSn = 0
consumption: 1.7 mA.
IDLE
SXOFF
SCAL
Used for calibrating frequency
synthesizer upfront (entering
receive mode can then be
done quicker). Transitional
state. Typ. current
CSn = 0
All register values are
Crystal
Manual freq.
synth. calibration
retained. Typ. current
oscillator off
SRX
consumption: 165 µA.
consumption: 8.4 mA.
Frequency
synthesizer startup,
optional calibration,
settling
Frequency synthesizer is turned on, can optionally be
calibrated, and then settles to the correct frequency.
Transitional state. Typ. current consumption: 8.4 mA.
Typ. current
consumption:
from 14.7 mA (strong
input signal) to 15.7 mA
(weak input signal).
Receive mode
In Normal mode, this state is
entered if the RX FIFO
overflows. Typ. current
consumption: 1.7 mA.
RXOFF_MODE = 00
RX FIFO
overflow
Optional freq.
Optional transitional state. Typ.
synth. calibration
current consumption: 8.4 mA.
SFRX
IDLE
Figure 12: Simplified Radio Control State Diagram, with Typical Current Consumption at
1.2 kBaud Data Rate and MDMCFG2.DEM_DCFILT_OFF=1(current optimized).
Frequency Band = 868 MHz
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9
Configuration Software
After chip reset, all the registers have default
values as shown in the tables in Section 26.
The optimum register setting might differ from
the default value. After a reset all registers that
shall be different from the default value
therefore needs to be programmed through
the SPI interface.
CC113L can be configured using the SmartRF™
Studio software [4]. The SmartRF Studio
software is highly recommended for obtaining
optimum register settings, and for evaluating
performance and functionality.
10 4-wire Serial Configuration and Data Interface
cancelled. The timing for the address and data
transfer on the SPI interface is shown in Figure
13 with reference to Table 15.
CC113L is configured via a simple 4-wire SPI-
compatible interface (SI, SO, SCLK and CSn)
where CC113L is the slave. This interface is also
used to read buffered data. All transfers on the
SPI interface are done most significant bit first.
When CSn is pulled low, the MCU must wait
until CC113L SO pin goes low before starting to
transfer the header byte. This indicates that
the crystal is running. Unless the chip was in
the SLEEP or XOFF states, the SO pin will
always go low immediately after taking CSn
low.
All transactions on the SPI interface start with
a header byte containing a R/W¯ bit, a burst
access bit (B), and a 6-bit address (A5 - A0).
The CSn pin must be kept low during transfers
on the SPI bus. If CSn goes high during the
transfer of a header byte or during read/write
from/to
a
register, the transfer will be
tsp
tch
tcl
tsd
thd
tns
SCLK:
CSn:
Write to register:
X
0
B
B
DW
7
DW
6
DW
5
DW
4
DW
3
DW
2
DW
1
DW
0
A5
S5
A4
S4
A3
S3
A2
A1
S1
A0
S0
X
X
SI
Hi-Z S7
S2
S6
S2
Hi-Z
Hi-Z
S7
S5
S4
S3
S1
S0
SO
Read from register:
X
1
X
B
B
A5
S5
A4
S4
A3
S3
A2
S2
A1
S1
A0
S0
SI
Hi-Z
S7
DR7
DR6
DR5
DR4
DR3
DR2
DR1
DR0
SO
Figure 13: Configuration Registers Write and Read Operations
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Parameter Description
Min Max Units
fSCLK
SCLK frequency
-
10
MHz
100 ns delay inserted between address byte and data byte (single access), or between
address and data, and between each data byte (burst access).
SCLK frequency, single access. No delay between address and data byte
-
-
9
SCLK frequency, burst access. No delay between address and data byte, or between data
bytes
6.5
tsp,pd
tsp
CSn low to positive edge on SCLK, in power-down mode
150
20
50
50
-
-
-
s
ns
ns
ns
ns
ns
ns
CSn low to positive edge on SCLK, in active mode
tch
Clock high
-
tcl
Clock low
-
trise
tfall
tsd
Clock rise time
Clock fall time
40
40
-
-
Setup data (negative SCLK edge) to positive edge on SCLK
(tsd applies between address and data bytes, and between data bytes)
Single access
Burst access
55
76
20
20
-
thd
tns
Hold data after positive edge on SCLK
Negative edge on SCLK to CSn high.
-
ns
ns
-
Table 15: SPI Interface Timing Requirements
Note: The minimum tsp,pd figure in Table 15 can be used in cases where the user does not read
the CHIP_RDYnsignal. CSn low to positive edge on SCLK when the chip is woken from power-
down depends on the start-up time of the crystal being used. The 150 μs in Table 15 is the
crystal oscillator start-up time measured on [1] and [2] using crystal AT-41CD2 from NDK.
10.1 Chip Status Byte
When the header byte, data byte, or command
strobe is sent on the SPI interface, the chip
status byte is sent by the CC113L on the SO pin.
The status byte contains key status signals,
useful for the MCU. The first bit, s7, is the
CHIP_RDYnsignal and this signal must go low
before the first positive edge of SCLK. The
CHIP_RDYn signal indicates that the crystal is
running.
The last four bits (3:0) in the status byte
contains FIFO_BYTES_AVAILABLE. For
these bits to give any valid information, the
R/W¯ bit in the header byte must be set to 1.
The FIFO_BYTES_AVAILABLE field will then
contain the number of bytes that can be read
from
the
RX
FIFO.
When
FIFO_BYTES_AVAILABLE=15, 15 or more
bytes can be read. The RX FIFO should not be
emptied before the complete packet has been
received (see the CC113L Errata Notes [3] for
more details).
Bits 6, 5, and 4 comprise the STATE value.
This value reflects the state of the chip. The
XOSC and power to the digital core are on in
the IDLE state, but all other modules are in
power down. The frequency and channel
configuration should only be updated when the
chip is in this state.
Table 16 gives a status byte summary.
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Bits Name
Description
7
CHIP_RDYn
Stays high until power and crystal have stabilized. Should always be low when using
the SPI interface.
6:4
STATE[2:0]
Indicates the current main state machine mode
Value State
Description
000
IDLE
IDLE state (Also reported for some transitional
states instead of SETTLING or CALIBRATE)
001
010
011
100
101
110
RX
Receive mode
Reserved
Reserved
CALIBRATE
SETTLING
Frequency synthesizer calibration is running
PLL is settling
RXFIFO_OVERFLOW RX FIFO has overflowed. Read out any useful
data, then flush the FIFO with SFRX
111
Reserved
3:0
FIFO_BYTES_AVAILABLE[3:0] The number of bytes available in the RX FIFO
Table 16: Status Byte Summary
10.2 Register Access
Registers with consecutive addresses can be
accessed in an efficient way by setting the
burst bit (B) in the header byte. The address
bits (A5 - A0) set the start address in an
internal address counter. This counter is
incremented by one each new byte (every 8
clock pulses). The burst access is either a
read or a write access and must be terminated
by setting CSn high.
The configuration registers on the CC113L are
located on SPI addresses from 0x00 to 0x2E.
Table 31 on page 46 lists all configuration
registers. It is highly recommended to use
SmartRF Studio [4] to generate optimum
register settings. The detailed description of
each register is found in Section 26.1 and
Section 26.2, starting on page 49. All
configuration registers can be both written to
and read. The R/W¯ bit controls if the register
should be written to or read. When writing to
registers, the status byte is sent on the SO pin
each time a header byte or data byte is
transmitted on the SI pin. When reading from
registers, the status byte is sent on the SO pin
each time a header byte is transmitted on the
SI pin.
For register addresses in the range
0x30 - 0x3D, the burst bit is used to select
between status registers when burst bit is one,
and command strobes when burst bit is zero.
See more in Section 10.3 below. Because of
this, burst access is not available for status
registers and they must be accessed one at a
time. The status registers can only be read.
10.3 SPI Read
When reading register fields over the SPI
interface while the register fields are updated
by the radio hardware (e.g. MARCSTATE or
is being corrupt. As an example, the
probability of any single read from RXBYTES
being corrupt, assuming the maximum data
rate is used, is approximately 80 ppm. Refer to
the CC113L Errata Notes [3] for more details.
RXBYTES), there is
a
small, but finite,
probability that a single read from the register
10.4 Command Strobes
Command Strobes may be viewed as single
byte instructions to CC113L. By addressing a
command strobe register, internal sequences
will be started. These commands are used to
disable the crystal oscillator, enable receive
mode, enable calibration etc. The 8 command
strobes
on page 45.
are
listed
in
Table
30
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are written. The R/W¯ bit should be set to one if
the FIFO_BYTES_AVAILABLE field in the
status byte should be interpreted.
Note: An SIDLE strobe will clear all
pending command strobes until IDLE
state is reached. This means that if for
example an SIDLE strobe is issued
while the radio is in RX state, any other
command strobes issued before the
radio reaches IDLE state will be
ignored.
When writing command strobes, the status
byte is sent on the SO pin.
A command strobe may be followed by any
other SPI access without pulling CSn high.
However, if an SRES strobe is being issued,
one will have to wait for SO to go low again
before the next header byte can be issued as
shown in Figure 14. The command strobes are
executed immediately, with the exception of
the SPWD and the SXOFF strobes, which are
executed when CSn goes high.
The command strobe registers are accessed
by transferring a single header byte (no data is
being transferred). That is, only the R/W¯ bit,
the burst access bit (set to 0), and the six
address bits (in the range 0x30 through 0x3D)
CSn
SO
SI
HeaderSRES
HeaderAddr
Data
Figure 14: SRES Command Strobe
10.5 RX FIFO Access
The 64-byte RX FIFO is accessed through the
0x3F address. The RX FIFO is write-only and
the R/W¯ bit should therefore be one.
The following header bytes access the
RX FIFO:
0xBF: Single byte access to RX FIFO
0xFF: Burst access to RX FIFO
The burst bit is used to determine if the
RX FIFO access is a single byte access or a
burst access. The single byte access method
expects a header byte with the burst bit set to
zero and one data byte. After the data byte, a
new header byte is expected; hence, CSn can
remain low. The burst access method expects
one header byte and then consecutive data
bytes until terminating the access by setting
CSn high.
The RX FIFO may be flushed by issuing a
SFRX command strobe. A SFRX command
strobe can only be issued in the IDLE, or
RXFIFO_OVERFLOW states. The RX FIFO is
flushed when going to the SLEEP state.
Figure 15 gives a brief overview of different
register access types possible.
Csn
Command strobe(s)
HeaderStrobe
HeaderReg
HeaderStrobe
Data
HeaderStrobe
HeaderReg
Data n + 1
Read or write register(s)
Data
HeaderReg
Data
. . . . . . . . .
Read or write
consecutive register(s)
HeaderReg n
HeaderRX FIFO
HeaderReg
Datan
Datan + 2
DataByte 2
HeaderReg
. . . . . . . . .
Write n + 1 bytes to the
RX FIFO
DataByte 0
Data
DataByte 1
. . . . . . . . .
Data
DataByte n - 1
HeaderStrobe
DataByte n
. . . . . . . . .
DataByte 0
Combinations
HeaderStrobe
HeaderRX FIFO
DataByte 1
. . . .
Figure 15: Register Access Types
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11 Microcontroller Interface and Pin Configuration
In a typical system, CC113L will interface to a
microcontroller. This microcontroller must be
able to:
Read buffered data
Read back status information via the 4-wire
SPI-bus configuration interface (SI, SO,
SCLK and CSn)
Program CC113L into different modes
11.1 Configuration Interface
The microcontroller uses four I/O pins for the
SPI configuration interface (SI, SO, SCLK and
CSn). The SPI is described in Section 10 on
page 21.
11.2 General Control and Status Pins
GDO1 is shared with the SO pin in the SPI
interface. The default setting for GDO1/SO is
3-state output. By selecting any other of the
programming options, the GDO1/SO pin will
become a generic pin. When CSn is low, the
pin will always function as a normal SO pin.
The CC113L has two dedicated configurable
pins (GDO0 and GDO2) and one shared pin
(GDO1) that can output internal status
information useful for control software. These
pins can be used to generate interrupts on the
MCU. See Section 23 on page 41 for more
details on the signals that can be
programmed.
12 Data Rate Programming
The data rate expected in receive mode is
programmed by the MDMCFG3.DRATE_M and
The data rate can be set from 0.6 kBaud to
500 kBaud with the minimum step size
according to Table 17 below. See Table 3 for
the minimum and maximum data rates for the
different modulation formats.
the
MDMCFG4.DRATE_E
configuration
registers. The data rate is given by the formula
below. As the formula shows, the programmed
data rate depends on the crystal frequency.
Min Data
Rate
Typical
Data Rate
[kBaud]
Max Data
Rate
Data rate
Step Size
[kBaud]
[kBaud]
[kBaud]
(256 DRATE _ M ) 2DRATE _ E
0.6
1.0
0.79
1.58
3.17
6.33
12.7
25.3
50.7
101.4
202.8
405.5
500
0.0015
0.0031
0.0062
0.0124
0.0248
0.0496
0.0992
0.1984
0.3967
0.7935
1.5869
RDATA
fXOSC
228
0.79
1.59
3.17
6.35
12.7
25.4
50.8
101.6
203.1
406.3
1.2
2.4
4.8
The following approach can be used to find
suitable values for a given data rate:
9.6
RDATA 220
DRATE _ E og2
fXOSC
19.6
38.4
76.8
153.6
250
500
RDATA 228
fXOSC 2DRATE _ E
DRATE _ M
56
If DRATE_M is rounded to the nearest integer
and becomes 256, increment DRATE_E and
use DRATE_M = 0.
Table 17: Data Rate Step Size
(assuming a 26 MHz crystal)
13 Receiver Channel Filter Bandwidth
In order to meet different channel width
requirements, the receiver channel filter is
programmable. The MDMCFG4.CHANBW_E and
MDMCFG4.CHANBW_M configuration registers
control the receiver channel filter bandwidth,
which scales with the crystal oscillator
frequency.
The following formula gives the relation
between the register settings and the channel
filter bandwidth:
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bandwidth. The following example illustrates
this:
fXOSC
BWchannel
8 (4 CHANBW _ M )·2CHANBW _ E
With the channel filter bandwidth set to
500 kHz, the signal should stay within 80% of
500 kHz, which is 400 kHz. Assuming
915 MHz frequency and ±20 ppm frequency
uncertainty for both the transmitting device and
the receiving device, the total frequency
uncertainty is ±40 ppm of 915 MHz, which is
±37 kHz. If the whole transmitted signal
bandwidth is to be received within 400 kHz,
the transmitted signal bandwidth should be
maximum 400 kHz - 2·37 kHz, which is
326 kHz.
Table 18 lists the channel filter bandwidths
supported by the CC113L.
MDMCFG4.
MDMCFG4.CHANBW_E
00 01 10 11
812 406 203 102
CHANBW_M
00
01
10
11
650 325 162
541 270 135
464 232 116
81
68
58
Table 18: Channel Filter Bandwidths [kHz]
(assuming a 26 MHz crystal)
By compensating for
a frequency offset
between the transmitter and the receiver, the
filter bandwidth can be reduced and the
sensitivity can be improved, see more in
DN005 [9] and in Section 14.1.
For best performance, the channel filter
bandwidth should be selected so that the
signal bandwidth occupies at most 80% of the
channel filter bandwidth. The channel centre
tolerance due to crystal inaccuracy should also
be subtracted from the channel filter
14 Demodulator, Symbol Synchronizer, and Data Decision
(see Section 17.2 for more information), the
CC113L contains an advanced and highly
configurable demodulator. Channel filtering
and frequency offset compensation is
performed digitally. To generate the RSSI level
signal level in the channel is estimated. Data
filtering is also included for enhanced
performance.
14.1 Frequency Offset Compensation
since the algorithm may drift to the boundaries
when trying to track noise.
The CC113L has
a
very fine frequency
resolution (see Table 9). This feature can be
used to compensate for frequency offset and
drift.
The tracking loop has two gain factors, which
affects the settling time and noise sensitivity of
the algorithm. FOCCFG.FOC_PRE_K sets the
gain before the sync word is detected, and
FOCCFG.FOC_POST_K selects the gain after
the sync word has been found.
When using 2-FSK, GFSK, or 4-FSK
modulation, the demodulator will compensate
for the offset between the transmitter and
receiver frequency within certain limits, by
estimating the centre of the received data. The
frequency offset compensation configuration is
controlled from the FOCCFG register. By
compensating for a large frequency offset
between the transmitter and the receiver, the
sensitivity can be improved, see DN005 [9].
Note: Frequency offset compensation is
not supported for OOK modulation
The estimated frequency offset value is
available in the FREQEST status register. This
can be used for permanent frequency offset
compensation. By writing the value from
The tracking range of the algorithm is
selectable as fractions of the channel
bandwidth with the FOCCFG.FOC_LIMIT
configuration register.
FREQEST into
FSCTRL0.FREQOFF, the
frequency synthesizer will automatically be
adjusted according to the estimated frequency
offset. More details regarding this permanent
frequency compensation algorithm can be
found in DN015 [6].
If the FOCCFG.FOC_BS_CS_GATE bit is set,
the offset compensator will freeze until carrier
sense asserts. This may be useful when the
radio is in RX for long periods with no traffic,
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14.2 Bit Synchronization
The bit synchronization algorithm extracts the
clock from the incoming symbols. The
algorithm requires that the expected data rate
is programmed as described in Section 12 on
page 25. Re-synchronization is performed
continuously to adjust for error in the incoming
symbol rate.
14.3 Byte Synchronization
Byte synchronization is achieved by
a
sync word will be received if the sync word
detection is enabled in register MDMCFG2 (see
Section 17.1). The sync word detector
correlates against the user-configured 16 or 32
bit sync word. The correlation threshold can be
set to 15/16, 16/16, or 30/32 bits match. The
sync word can be further qualified using the
continuous sync word search. The sync word
is a 16 bit configurable field (can be repeated
to get a 32 bit) that must be inserted at the
start of the packet by the transmitter (for
example the CC115L, CC110L, or CC1101). The
MSB in the sync word must be transmitted
first. The demodulator uses this field to find the
byte boundaries in the stream of bits. The sync
word will also function as a system identifier,
since only packets with the correct predefined
preamble
quality
indicator
mechanism
described below and/or
a
carrier sense
condition. The sync word is configured through
the SYNC1 and SYNC0 registers.
15 Packet Handling Hardware Support
The CC113L has built-in hardware support for
packet oriented radio protocols and the packet
handler can be configured to implement the
following (if enabled):
Bit Field Name
Description
RSSI value
7:0 RSSI
Table 19: Received Packet Status Byte 1
(first byte appended after the data)
Preamble detection
Sync word detection
CRC computation and CRC check
One byte address check
Bit Field Name
CRC_OK
Description
7
1: CRC for received data OK (or
CRC disabled)
Packet length check (length byte checked
against a programmable maximum length)
0: CRC error in received data
6:0 Reserved
Optionally, two status bytes (see Table 19 and
Table 20) with RSSI value and CRC status can
be appended in the RX FIFO.
Table 20: Received Packet Status Byte 2
(second byte appended after the data)
Note: Register fields that control the
packet handling features should only be
altered when CC113L is in the IDLE state.
15.1 Packet Format
The CC113L can be configured to receive
packets of different format and the packet
should consists of the following items (see
Figure 16):
Synchronization word
Optional length byte
Optional address byte
Payload
Optional 2 byte CRC
Preamble
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Legend:
Processed and removed by the
radio
Optional CRC-16 calculation
Data field
OptIonal user-provided fields (processed by the
radio, but not removed)
Preamble bits
(1010...1010)
Unprocessed user data
8
8
8 x n bits
16/32 bits
8 x n bits
16 bits
bits bits
Figure 16: Packet Format
The preamble pattern is an alternating
sequence of ones and zeros that the receiver
uses for bit synchronisation.
Note: The minimum packet length
supported (excluding the optional length
byte and CRC) is one byte of payload
data.
The synchronization word is a two-byte value
set in the SYNC1 and SYNC0 registers. The
sync word provides byte synchronization of the
incoming packet. A one-byte sync word can be
emulated by setting the SYNC1 value to the
preamble pattern. It is also possible to emulate
15.1.1 Arbitrary Length Field Configuration
The packet length register, PKTLEN, can be
reprogrammed during RX. In combination with
a
32
bit
sync
word
by
setting
fixed
packet
length
mode
MDMCFG2.SYNC_MODE to 3 or 7. The sync
word searched for is the two-byte sync word
repeated twice.
(PKTCTRL0.LENGTH_CONFIG=0), this opens
the possibility to have a different length field
configuration than supported for variable
length packets (in variable packet length mode
the length byte is the first byte after the sync
word). At the start of reception, the packet
length is set to a large value. The MCU reads
out enough bytes to interpret the length field in
the packet. Then the PKTLEN value is set
according to this value. The end of packet will
occur when the byte counter in the packet
handler is equal to the PKTLEN register. Thus,
the MCU must be able to program the correct
length, before the internal counter reaches the
packet length.
CC113L supports both constant packet length
protocols and variable length protocols.
Variable or fixed packet length mode can be
used for packets up to 255 bytes. For longer
packets, infinite packet length mode must be
used.
Fixed packet length mode is selected by
setting PKTCTRL0.LENGTH_CONFIG=0. The
desired packet length is set by the PKTLEN
register. This value must be different from 0.
In
variable
packet
length
mode,
PKTCTRL0.LENGTH_CONFIG=1, the packet
length is configured by the first byte after the
sync word. The packet length is defined as the
payload data, excluding the length byte and
the optional CRC. The PKTLEN register is
used to set the maximum packet length
allowed. Any packet received with a length
byte with a value greater than PKTLEN will be
discarded. The PKTLEN value must be
different from 0.
15.1.2 Packet Length > 255
The packet automation control register,
PKTCTRL0, can be reprogrammed during
RX. This opens the possibility to receive
packets that are longer than 256 bytes and still
be able to use the packet handling hardware
support. At the start of the packet, the infinite
packet
length
mode
(PKTCTRL0.LENGTH_CONFIG=2) must be
active. When receiving, the MCU reads out
enough bytes to interpret the length field in the
packet and sets the PKTLEN register to
mod(length, 256). When less than 256 bytes
remains of the packet, the MCU disables
infinite packet length mode and activates fixed
With PKTCTRL0.LENGTH_CONFIG=2, the
packet length is set to infinite and reception
will continue until turned off manually. As
described in the next section, this can be used
to support packet formats with different length
configuration than natively supported by
CC113L.
packet
length
mode
(PKTCTRL0.LENGTH_CONFIG=0). When the
internal byte counter reaches the PKTLEN
value, the reception ends (the radio enters the
state determined by RXOFF_MODE). Automatic
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CRC appending/checking can also be used
Program the PKTLEN
register to
(by setting PKTCTRL0.CRC_EN=1).
mod(600, 256) = 88.
Receive at least 345 bytes (600 - 255)
When for example a 600-byte packet is to be
received, the MCU should do the following
(see also Figure 17)
Set PKTCTRL0.LENGTH_CONFIG=0.
The reception ends when the packet
counter reaches 88. A total of 600 bytes
have been received.
Set PKTCTRL0.LENGTH_CONFIG=2.
Receive enough bytes to interpret the
length field
Internal byte counter in packet handler counts from 0 to 255 and then starts at 0 again
0, 1............, 88, .............................................255, 0, ........, 88, .............................................255, 0, ........, 88, .............................................255, 0, ..
Infinite packet length mode enabled
600 bytes received
Fixed packet length mode anbled when
less than 256 bytes remains of packet
Length field received. PKTLEN set to
mod(600, 256) = 88
Figure 17: Packet Length > 255
15.2 Packet Filtering
used to set the maximum allowed packet
length. If the received length byte has a larger
value than this, the packet is discarded and
receive mode restarted (regardless of the
MCSM1.RXOFF_MODEsetting).
CC113L supports three different types of packet
filtering; address filtering, maximum length
filtering, and CRC filtering.
15.2.1 Address Filtering
Setting PKTCTRL1.ADR_CHK to any other
value than zero enables the packet address
filter. The packet handler engine will compare
the destination address byte in the packet with
the programmed node address in the ADDR
register and the 0x00 broadcast address when
PKTCTRL1.ADR_CHK=10 or both the 0x00
and 0xFF broadcast addresses when
PKTCTRL1.ADR_CHK=11. If the received
address matches a valid address, the packet
is received and written into the RX FIFO. If the
address match fails, the packet is discarded
and receive mode restarted (regardless of the
MCSM1.RXOFF_MODEsetting).
15.2.3 CRC Filtering
The filtering of a packet when CRC check fails
is
enabled
by
setting
PKTCTRL1.CRC_AUTOFLUSH=1. The CRC
auto flush function will flush the entire
RX FIFO if the CRC check fails. After auto
flushing the RX FIFO, the next state depends
on the MCSM1.RXOFF_MODEsetting.
When using the auto flush function, the
maximum packet length is 63 bytes in variable
packet length mode and 64 bytes in fixed
packet length mode. Note that when
PKTCTRL1.APPEND_STATUS is enabled, the
maximum allowed packet length is reduced by
two bytes in order to make room in the RX
FIFO for the two status bytes appended at the
end of the packet. Since the entire RX FIFO is
flushed when the CRC check fails, the
previously received packet must be read out of
the RX FIFO before receiving the current
packet. The MCU must not read from the
current packet until the CRC has been
checked as OK.
If the received address matches a valid
address when using infinite packet length
mode and address filtering is enabled, 0xFF
will be written into the RX FIFO followed by the
address byte and then the payload data.
15.2.2 Maximum Length Filtering
In
variable
packet
length
mode,
the
PKTCTRL0.LENGTH_CONFIG=1,
PKTLEN.PACKET_LENGTH register value is
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15.3 Packet Handling
In RX mode, the demodulator and packet
handler will search for a valid sync word.
When found, the demodulator has obtained
both bit and byte synchronization and will
receive the first payload byte.
Next, the packet handler optionally checks the
address and only continues the reception if the
address matches. If automatic CRC check is
enabled, the packet handler computes CRC
and matches it with the appended CRC
checksum.
When variable packet length mode is enabled,
the first byte is the length byte. The packet
handler stores this value as the packet length
and receives the number of bytes indicated by
the length byte. If fixed packet length mode is
used, the packet handler will accept the
programmed number of bytes.
At the end of the payload, the packet handler
will optionally write two extra packet status
bytes (see Table 19 and Table 20) that contain
CRC status, link quality indication, and RSSI
value.
15.4 Packet Handling in Firmware
When implementing a packet oriented radio
protocol in firmware, the MCU needs to know
b) SPI Polling
The PKTSTATUS register can be polled at a
given rate to get information about the current
GDO2 and GDO0 values respectively. The
RXBYTESregister can be polled at a given rate
to get information about the number of bytes in
the RX FIFO. Alternatively, the number of
bytes in the RX FIFO can be read from the
chip status byte returned on the MISO line
each time a header byte, data byte, or
command strobe is sent on the SPI bus.
when
a
packet has been received.
Additionally, for packets longer than 64 bytes,
the RX FIFO needs to be read while in RX
mode. This means that the MCU needs to
know the number of bytes that can be read
from the RX FIFO. There are two possible
solutions to get the necessary status
information:
a) Interrupt Driven Solution
The GDO pins can be used to give an interrupt
when a sync word has been received or when
a complete packet has been received by
setting IOCFGx.GDOx_CFG=0x06. In addition,
there are two configurations for the
IOCFGx.GDOx_CFG register that can be used
as an interrupt source to provide information
on how many bytes that are in the RX FIFO
It is recommended to employ an interrupt
driven solution since high rate SPI polling
reduces the RX sensitivity. Furthermore, as
explained in Section 10.3 and the CC113L
Errata Notes [3], when using SPI polling, there
is a small, but finite, probability that a single
read from registers PKTSTATUS, and
RXBYTES is being corrupt. The same is the
case when reading the chip status byte.
(IOCFGx.GDOx_CFG=0x00
and
IOCFGx.GDOx_CFG=0x01). See Table 29 for
more information.
16 Modulation Formats
decoded by the demodulator. This option is
CC113L supports amplitude, frequency, and
phase shift modulation formats. The desired
enabled
by
setting
MDMCFG2.MANCHESTER_EN=1.
modulation
format
is
set
in
the
MDMCFG2.MOD_FORMAT register.
Note: Manchester encoding is not
supported at the same time as using 4-
FSK modulation
Optionally, if the data has been Manchester
coded on the transmitter side it can be
16.1 Frequency Shift Keying
When 2-FSK/GFSK/4-FSK modulation is used,
the DEVIATN register specifies the expected
frequency deviation of incoming signals in RX
and should be the same as the deviation of the
CC113L supports 2-(G)FSK and 4-FSK
modulation. When selecting 4-FSK, the
preamble and sync word to be received needs
to be 2-FSK (see Figure 13).
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transmitted signal for demodulation to be
performed reliably and robustly.
Format
Symbol Coding
2-FSK/GFSK „0‟
– Deviation
The frequency deviation is programmed with
the DEVIATION_M and DEVIATION_E values
in the DEVIATN register. The value has an
exponent/mantissa form, and the resultant
deviation is given by:
„1‟
+ Deviation
4-FSK
„01‟
– Deviation
„00‟
„10‟
„11‟
– 1/3∙Deviation
+1/3∙Deviation
+ Deviation
fxosc
217
fdev
(8 DEVIATION _ M) 2DEVIATION _ E
Table 21: Symbol Encoding for 2-FSK/GFSK
and 4-FSK Modulation
The symbol encoding is shown in Table 21.
1/Baud Rate
1/Baud Rate
1/Baud Rate
+1
+1/3
-1/3
-1
1
0
1
0
1
0
1
0
1
1
0
1
0
0
1
1
00 01 01 11 10 00 11 01
Preamble
0xAA
Sync
0xD3
Data
0x17 0x8D
Figure 18: Data Sent Over the Air (MDMCFG2.MOD_FORMAT=100)
16.2 Amplitude Modulation
settings are not optimum. DN022 [8] gives
guidelines on how to find optimum OOK
settings from the preferred settings in
SmartRF Studio [4]. The DEVIATN register
setting has no effect when using OOK.
The amplitude modulation supported by CC113L
is On-Off Keying (OOK).
When using OOK, the AGC settings from the
SmartRF Studio [4] preferred FSK
17 Received Signal Qualifiers and RSSI
CC113L has several qualifiers that can be used
to increase the likelihood that a valid sync
word is detected:
Sync Word Qualifier
RSSI
Carrier Sense
17.1 Sync Word Qualifier
If sync word detection is enabled in the
MDMCFG2 register, the CC113L will not start
filling the RX FIFO and perform the packet
filtering described in Section 15.2 before a
valid sync word has been detected. The sync
MDMCFG2.
SYNC_MODE
Sync Word Qualifier Mode
000
001
010
011
100
No preamble/sync
15/16 sync word bits detected
16/16 sync word bits detected
30/32 sync word bits detected
word
qualifier
mode
is
set
by
MDMCFG2.SYNC_MODE and is summarized in
Table 22. Carrier sense in Table 22 is
described in Section 17.3.
No preamble/sync + carrier sense
above threshold
101
110
111
15/16 + carrier sense above threshold
16/16 + carrier sense above threshold
30/32 + carrier sense above threshold
Table 22: Sync Word Qualifier Mode
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17.2 RSSI
The RSSI value is an estimate of the signal
power level in the chosen channel. This value
is based on the current gain setting in the RX
chain and the measured signal level in the
channel.
2 BWchannel
8 2FILTER _ LENGTH
fRSSI
If PKTCTRL1.APPEND_STATUS is enabled,
the last RSSI value of the packet is
automatically added to the first byte appended
after the payload.
In RX mode, the RSSI value can be read
continuously from the RSSI status register
until the demodulator detects a sync word
(when sync word detection is enabled). At that
point the RSSI readout value is frozen until the
next time the chip enters the RX state.
The RSSI value read from the RSSI status
register is a 2‟s complement number. The
following procedure can be used to convert the
RSSI reading to an absolute power level
(RSSI_dBm)
Note: It takes some time from the radio
enters RX mode until a valid RSSI value is
present in the RSSI register. Please see
DN505 [7] for details on how the RSSI
response time can be estimated.
1) Read the RSSIstatus register
2) Convert the reading from a hexadecimal
number to a decimal number (RSSI_dec)
3) If RSSI_dec ≥ 128 then RSSI_dBm =
(RSSI_dec - 256)/2 – RSSI_offset
The RSSI value is given in dBm with a ½ dB
4) Else if RSSI_dec < 128 then RSSI_dBm =
resolution. The RSSI update rate, fRSSI
,
(RSSI_dec)/2 – RSSI_offset
depends on the receiver filter bandwidth
(BWchannel is defined in Section 13) and
AGCCTRL0.FILTER_LENGTH.
Table 23 gives typical values for the
RSSI_offset. Figure 19 and Figure 20 show
typical plots of RSSI readings as a function of
input power level for different data rates.
Data rate [kBaud] RSSI_offset [dB], 433 MHz RSSI_offset [dB], 868 MHz
1.2
74
74
74
74
74
74
74
74
38.4
250
500
Table 23: Typical RSSI_offset Values
0
-10
-20
-30
-40
-50
-60
-70
-80
-90
-100
-110
-120
-120
-110
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
0
Input Power [dBm]
1.2 kBaud
38.4 kBaud
250 kBaud
500 kBaud
Figure 19: Typical RSSI Value vs. Input Power Level for Different Data Rates at 433 MHz
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0
-10
-20
-30
-40
-50
-60
-70
-80
-90
-100
-110
-120
-120
-110
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
0
Input Power [dBm]
1.2 kBaud
500 kBaud
250 kBaud
38.4 kBaud
Figure 20: Typical RSSI Value vs. Input Power Level for Different Data Rates at 868 MHz
17.3 Carrier Sense (CS)
Carrier sense (CS) is used as a sync word
qualifier and can be asserted based on two
conditions which can be individually adjusted:
AGCCTRL2.MAX_LNA_GAIN
AGCCTRL2.MAX_DVGA_GAIN
AGCCTRL1.CARRIER_SENSE_ABS_THR
AGCCTRL2.MAGN_TARGET
CS is asserted when the RSSI is above a
programmable absolute threshold, and de-
asserted when RSSI is below the same
threshold (with hysteresis). See more in
Section 17.3.1.
For given AGCCTRL2.MAX_LNA_GAIN and
AGCCTRL2.MAX_DVGA_GAIN settings, the
absolute threshold can be adjusted ±7 dB in
steps
of
1
dB
using
CS is asserted when the RSSI has
increased with a programmable number of
dB from one RSSI sample to the next, and
de-asserted when RSSI has decreased
with the same number of dB. This setting
is not dependent on the absolute signal
level and is thus useful to detect signals in
environments with time varying noise floor.
See more in Section 17.3.2.
CARRIER_SENSE_ABS_THR.
The MAGN_TARGET setting is a compromise
between blocker tolerance/selectivity and
sensitivity. The value sets the desired signal
level in the channel into the demodulator.
Increasing this value reduces the headroom
for blockers, and therefore close-in selectivity.
It is strongly recommended to use SmartRF
Studio
[4]
to
generate
the
correct
Carrier sense can be used as a sync word
qualifier that requires the signal level to be
higher than the threshold for a sync word
search to be performed and is set by setting
MDMCFG2 . The carrier sense signal can be
observed on one of the GDO pins by setting
IOCFGx.GDOx_CFG=14 and in the status
register bit PKTSTATUS.CS.
MAGN_TARGET setting. Table 24 and Table 25
show the typical RSSI readout values at the
CS threshold at 2.4 kBaud and 250 kBaud
data rate respectively. The default reset value
for CARRIER_SENSE_ABS_THR= 0 (0 dB) has
been used. MAGN_TARGET = 3 (33 dB) and
7 (42 dB) have been used for 2.4 kBaud and
250 kBaud data rate respectively. For other
data rates, the user must generate similar
tables to find the CS absolute threshold.
17.3.1 CS Absolute Threshold
The absolute threshold related to the RSSI
value depends on the following register fields:
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If the threshold is set high, i.e. only strong
signals are wanted, the threshold should be
adjusted upwards by first reducing the
MAX_LNA_GAIN value and then the
MAX_DVGA_GAIN value. This will reduce
power consumption in the receiver front end,
since the highest gain settings are avoided.
MAX_DVGA_GAIN[1:0]
00 01 10
000 −97.5 −91.5 −85.5 −79.5
001 −94 −88 −82.5 −76
010 −90.5 −84.5 −78.5 −72.5
011 −88 −82.5 −76.5 −70.5
100 −85.5
11
17.3.2 CS Relative Threshold
−80
−78
−73.5
−72
−68
−66
−64
−61
The relative threshold detects sudden changes
in the measured signal level. This setting does
not depend on the absolute signal level and is
thus useful to detect signals in environments
with a time varying noise floor. The register
field AGCCTRL1.CARRIER_SENSE_REL_THR
is used to enable/disable relative CS, and to
select threshold of 6 dB, 10 dB, or 14 dB RSSI
change.
101
110
111
−84
−82
−79
−76
−70
−73.5
−67
Table 24: Typical RSSI Value in dBm at CS
Threshold with MAGN_TARGET= 3 (33 dB) at
2.4 kBaud, 868 MHz
MAX_DVGA_GAIN[1:0]
00
01
10
11
000 −90.5 −84.5 −78.5 −72.5
001
−88
−82
−76
−72
−70
−68
−66
−64
−62
−70
−66
−64
−62
−60
−58
−56
010 −84.5 −78.5
011 −82.5 −76.5
100 −80.5 −74.5
101
−78
−72
−70
−68
110 −76.5
111 −74.5
Table 25: Typical RSSI Value in dBm at CS
Threshold with MAGN_TARGET= 7 (42 dB) at
250 kBaud, 868 MHz
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18 Radio Control
SIDLE
SPWD
SLEEP
0
CAL_COMPLETE
MANCAL
3,4,5
IDLE
1
CSn = 0
SXOFF
SCAL
CSn = 0
XOFF
2
SRX
FS_WAKEUP
6,7
FS_AUTOCAL = 01
&
SRX
FS_AUTOCAL = 00 | 10 | 11
&
SRX
CALIBRATE
8
CAL_COMPLETE
SETTLING
9,10,11
SRX
RXOFF_MODE =
11
RX
13,14,15
RXFIFO_OVERFLOW
RXOFF_MODE = 00
&
FS_AUTOCAL = 10 | 11
RXOFF_MODE = 00
&
FS_AUTOCAL = 00 | 01
RX_OVERFLOW
17
CALIBRATE
12
SFRX
IDLE
1
Figure 21: Complete Radio Control State Diagram
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shown in Figure 12 on page 20. The complete
radio control state diagram is shown in Figure
21. The numbers refer to the state number
readable in the MARCSTATE status register.
This register is primarily for test purposes.
CC113L has a built-in state machine that is used
to switch between different operational states
(modes). The change of state is done either by
using command strobes or by internal events
such as RX FIFO overflow.
A simplified state diagram, together with
typical usage and current consumption, is
18.1 Power-On Start-Up Sequence
When the power supply is turned on, the
system must be reset. This is achieved by one
of the two sequences described below, i.e.
automatic power-on reset (POR) or manual
reset. After the automatic power-on reset or
manual reset, it is also recommended to
change the signal that is output on the GDO0
pin. The default setting is to output a clock
signal with a frequency of CLK_XOSC/192.
However, to optimize performance in RX, an
alternative GDO setting from the settings
found in Table 29 on page 42 should be
selected.
18.1.2 Manual Reset
The other global reset possibility on CC113L
uses the SRES command strobe. By issuing
this strobe, all internal registers and states are
set to the default, IDLE state. The manual
power-up sequence is as follows (see Figure
23):
Set SCLK = 1 and SI = 0.
Strobe CSn low / high.
Hold CSn low and then high for at least
40 µs relative to pulling CSn low
Pull CSn low and wait for SO to go low
(CHIP_RDYn).
18.1.1 Automatic POR
A power-on reset circuit is included in the
CC113L. The minimum requirements stated in
Table 11 must be followed for the power-on
reset to function properly. The internal power-
up sequence is completed when CHIP_RDYn
goes low. CHIP_RDYn is observed on the SO
pin after CSn is pulled low. See Section 10.1
for more details on CHIP_RDYn.
Issue the SRESstrobe on the SI line.
When SO goes low again, reset is
complete and the chip is in the IDLE state.
XOSC and voltage regulator switched on
40 us
CSn
When the CC113L reset is completed, the chip
will be in the IDLE state and the crystal
oscillator will be running. If the chip has had
sufficient time for the crystal oscillator to
stabilize after the power-on-reset, the SO pin
will go low immediately after taking CSn low. If
CSn is taken low before reset is completed,
the SO pin will first go high, indicating that the
crystal oscillator is not stabilized, before going
low as shown in Figure 22.
SO
XOSC Stable
SRES
SI
Figure 23: Power-On Reset with SRES
Note that the above reset procedure is
only required just after the power supply is
first turned on. If the user wants to reset
the CC113L after this, it is only necessary to
issue an SREScommand strobe.
CSn
SO
XOSC Stable
Figure 22: Power-On Reset
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18.2 Crystal Control
The crystal oscillator (XOSC) is either
automatically controlled or always on, if
MCSM0.XOSC_FORCE_ONis set.
state machine will then go to the IDLE state.
The SO pin on the SPI interface must be
pulled low before the SPI interface is ready to
be used as described in Section 10.1 on
page 22.
In the automatic mode, the XOSC will be
turned off if the SXOFF or SPWD command
strobes are issued; the state machine then
goes to XOFF or SLEEP respectively. This
can only be done from the IDLE state. The
XOSC will be turned off when CSn is released
(goes high). The XOSC will be automatically
turned on again when CSn goes low. The
If the XOSC is forced on, the crystal will
always stay on even in the SLEEP state.
Crystal oscillator start-up time depends on
crystal ESR and load capacitances. The
electrical specification for the crystal oscillator
can be found in Section 4.3 on page 12.
18.3 Voltage Regulator Control
The voltage regulator to the digital core is
controlled by the radio controller. When the
chip enters the SLEEP state which is the state
with the lowest current consumption, the
voltage regulator is disabled. This occurs after
CSn is released when a SPWD command
strobe has been sent on the SPI interface. The
chip is then in the SLEEP state. Setting CSn
low again will turn on the regulator and crystal
oscillator and make the chip enter the IDLE
state.
18.4 Receive Mode (RX)
Receive mode is activated directly by the MCU
IDLE
by using the SRXcommand strobe.
RX: Start search for a new packet
The frequency synthesizer must be calibrated
regularly. CC113L has one manual calibration
option (using the SCAL strobe), and three
automatic calibration options that are
controlled by the MCSM0.FS_AUTOCALsetting:
Note: When MCSM1.RXOFF_MODE=11
and a packet has been received, it will
take some time before a valid RSSI value
is present in the RSSIregister again even
if the radio has never exited RX mode.
This time is the same as the RSSI
response time discussed in DN505 [7].
Calibrate when going from IDLE to RX
Calibrate when going from RX to IDLE
automatically1
The SIDLE command strobe can always be
used to force the radio controller to go to the
IDLE state.
Calibrate every fourth time when going
from RX to IDLE automatically1
If the radio goes from RX to IDLE by issuing
an SIDLE strobe, calibration will not be
performed. The calibration takes a constant
number of XOSC cycles; see Table 26 for
timing details regarding calibration.
18.5 RX Termination
If the system expects the transmission to have
started when entering RX mode, the
MCSM2.RX_TIME_RSSIfunction can be used.
The radio controller will then terminate RX if
the first valid carrier sense sample indicates
no carrier (RSSI below threshold). See Section
17.3 on page 33 for details on Carrier Sense.
When RX is activated, the chip will remain in
receive mode until a packet is successfully
received or until RX mode terminated due to
lack of carrier sense (see Section 18.5). The
probability that a false sync word is detected
can be reduced by using CS together with
maximum sync word length as described in
Section 17. After a packet is successfully
received, the radio controller goes to the state
indicated by the MCSM1.RXOFF_MODE setting.
The possible destinations are:
For OOK modulation, lack of carrier sense is
only considered valid after eight symbol
periods. Thus, the MCSM2.RX_TIME_RSSI
function can be used in OOK mode when the
distance between two “1” symbols is eight or
less.
If RX terminates due to no carrier sense when
the MCSM2.RX_TIME_RSSI function is used,
the radio will always go back to IDLE,
1
Not forced in IDLE by issuing an SIDLE
strobe
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CC113L
setting.
regardless of the MCSM1.RXOFF_MODE
18.6 Timing
18.6.1 Overall State Transition Times
The crystal oscillator frequency, fxosc
The main radio controller needs to wait in
certain states in order to make sure that the
internal analog/digital parts have settled down
and are ready to operate in the new states. A
number of factors are important for the state
transition times:
The value of the TEST0, TEST1, and
FSCAL3registers
Table 26 shows timing in crystal clock cycles
for key state transitions.
Description
Transition Time
1953/fxosc
Transition Time [µs]
IDLE to RX, no calibration
75.1
IDLE to RX, with calibration 1953/fxosc + FS calibration Time 799
RX to IDLE, no calibration
RX to IDLE, with calibration 2/fxosc + FS calibration Time
Manual calibration 283/fxosc + FS calibration Time
2/fxosc
~0.1
724
735
Table 26: Overall State Transition Times (Example for 26 MHz crystal oscillator, 250 kBaud data
rate, and TEST0= 0x0B (maximum calibration time)).
18.6.2 Frequency Synthesizer Calibration
Time
SmartRF Studio software [4]. The possible
values for TEST0when operating with different
frequency bands are 0x09 and 0x0B. The
SmartRF Studio software [4] always sets
FSCAL3.CHP_CURR_CAL_ENto 10b.
Table
27
summarizes
the
frequency
synthesizer (FS) calibration times for possible
settings
of
TEST0
and
FSCAL3.CHP_CURR_CAL_EN.
Setting
The calibration time can be reduced from
712/724 µs to 145/157 µs. See Section 25.2
on page 44 for more details.
FSCAL3.CHP_CURR_CAL_EN to 00b disables
the charge pump calibration stage. TEST0 is
set to the values recommended by
TEST0 FSCAL3.CHP_CURR_CAL_EN
FS Calibration Time FS Calibration Time
fxosc = 26 MHz
fxosc = 27 MHz
0x09
0x09
0x0B
0x0B
00b
10b
00b
10b
3764/fxosc = 145 us
18506/fxosc = 712 us
4073/fxosc = 157 us
18815/fxosc = 724 us
3764/fxosc = 139 us
18506/fxosc = 685 us
4073/fxosc = 151 us
18815/fxosc = 697 us
Table 27. Frequency Synthesizer Calibration Times (26/27 MHz crystal)
19 RX FIFO
RX FIFO underflow will result in an error in the
data read out of the RX FIFO.
The CC113L contains a 64-byte RX FIFO for
received data and the SPI interface is used to
read the RX FIFO (see Section 10.5 for more
details). The FIFO controller will detect
overflow in the RX FIFO.
The chip status byte that is available on the
SO pin while transferring the SPI header
contains the fill grade of the RX FIFO
(R/W¯ = 1). Section 10.1 on page 22 contains
more details on this.
When reading the RX FIFO the MCU must
avoid reading it past its empty value since a
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FIFO_THR
The number of bytes in the RX FIFO can also
be read from the status register
Bytes in
RX FIFO
0 (0000)
1 (0001)
2 (0010)
3 (0011)
4 (0100)
5 (0101)
6 (0110)
7 (0111)
8 (1000)
9 (1001)
10 (1010)
11 (1011)
12 (1100)
13 (1101)
14 (1110)
15 (1111)
4
RXBYTES.NUM_RXBYTES. If a received data
byte is written to the RX FIFO at the exact
same time as the last byte in the RX FIFO is
read over the SPI interface, the RX FIFO
pointer is not properly updated and the last
read byte will be duplicated. To avoid this
problem, the RX FIFO should never be
emptied before the last byte of the packet is
received.
8
12
16
20
24
28
32
36
40
44
48
52
56
60
64
For packet lengths less than 64 bytes it is
recommended to wait until the complete
packet has been received before reading it out
of the RX FIFO.
If the packet length is larger than 64 bytes, the
MCU must determine how many bytes can be
read
from
the
RX
FIFO
(RXBYTES.NUM_RXBYTES-1). The following
Table 28: FIFO_THRSettings and the
software routine can be used:
Corresponding RX FIFO Thresholds
1. Read
RXBYTES.NUM_RXBYTES
A signal will assert when the number of bytes
in the RX FIFO is equal to or higher than the
programmed threshold. This signal can be
viewed on the GDO pins (see Table 29 on
page 42).
repeatedly at a rate specified to be at least
twice that of which RF bytes are received
until the same value is returned twice;
store value in n.
2. If n < # of bytes remaining in packet, read
n-1 bytes from the RX FIFO.
Figure 24 shows the number of bytes in the
RX FIFO when the threshold signal toggles in
the case of FIFO_THR=13. Figure 25 shows
the signal on the GDO pin as the RX FIFO is
filled above the threshold, and then drained
below in the case of FIFO_THR=13.
3. Repeat steps 1 and 2 until n = # of bytes
remaining in packet.
4. Read the remaining bytes from the RX
FIFO.
Overflow
margin
The 4-bit FIFOTHR.FIFO_THRsetting is used
to program threshold points in the FIFOs.
FIFO_THR=13
Table 28 lists the 16 FIFO_THR settings and
the corresponding thresholds for the RX FIFO.
56 bytes
RX FIFO
Figure 24: Example of RX FIFO at Threshold
NUM_RXBYTES
53 54 55 56 57 56 55 54 53
GDO
Figure 25: Number of Bytes in RX FIFO vs.
the GDO Signal
(GDOx_CFG=0x00and FIFO_THR=13)
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20 Frequency Programming
by the 24 bit frequency word located in the
FREQ2, FREQ1, and FREQ0 registers. This
word will typically be set to the centre of the
lowest channel frequency that is to be used.
The frequency programming in CC113L is
designed to minimize the programming
needed when changing frequency.
To set up a system with channel numbers, the
desired channel spacing is programmed with
The desired channel number is programmed
with the 8-bit channel number register,
CHANNR.CHAN, which is multiplied by the
channel offset. The resultant carrier frequency
is given by:
the
MDMCFG0.CHANSPC_M
and
MDMCFG1.CHANSPC_E registers. The channel
spacing registers are mantissa and exponent
respectively. The base or start frequency is set
fXOSC
216
fcarrier
(FREQ CHAN ((256 CHANSPC _ M) 2CHANSPC _ E ))
With a 26 MHz crystal the maximum channel
spacing is 405 kHz. To get e.g. 1 MHz channel
spacing, one solution is to use 333 kHz
channel spacing and select each third channel
in CHANNR.CHAN.
fXOSC
fIF
FREQ_ IF
210
If any frequency programming register is
altered when the frequency synthesizer is
running, the synthesizer may give an
undesired response. Hence, the frequency
should only be updated when the radio is in
the IDLE state
The preferred IF frequency is programmed
with the FSCTRL1.FREQ_IF register. The IF
frequency is given by:
21 VCO
The VCO is completely integrated on-chip.
21.1 VCO and PLL Self-Calibration
The VCO characteristics vary with temperature
and supply voltage changes as well as the
desired operating frequency. In order to
ensure reliable operation, CC113L includes
frequency synthesizer self-calibration circuitry.
This calibration should be done regularly, and
must be performed after turning on power and
before using a new frequency (or channel).
The number of XOSC cycles for completing
the PLL calibration is given in Table 26 on
page 38.
Note:
The
calibration
values
are
maintained in SLEEP mode, so the
calibration is still valid after waking up from
SLEEP mode unless supply voltage or
temperature has changed significantly.
To check that the PLL is in lock, the user can
program register IOCFGx.GDOx_CFG
to
0x0A, and use the lock detector output
available on the GDOx pin as an interrupt for
the MCU (x = 0,1, or 2). A positive transition
on the GDOx pin means that the PLL is in
lock. As an alternative the user can read
register FSCAL1. The PLL is in lock if the
register content is different from 0x3F. Refer
also to the CC113L Errata Notes [3].
The calibration can be initiated automatically
or manually. The synthesizer can be
automatically calibrated each time the
synthesizer is turned on, or each time the
synthesizer is turned off automatically. This is
configured with the MCSM0.FS_AUTOCAL
register setting. In manual mode, the
calibration is initiated when the SCAL
command strobe is activated in the IDLE
mode.
For more robust operation, the source code
could include a check so that the PLL is re-
calibrated until PLL lock is achieved if the PLL
does not lock the first time.
22 Voltage Regulators
can be viewed as integral parts of the various
modules. The user must however make sure
that the absolute maximum ratings and
CC113L contains several on-chip linear voltage
regulators that generate the supply voltages
needed by low-voltage modules. These
voltage regulators are invisible to the user, and
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required pin voltages in Table 1 and Table 12
are not exceeded.
If the chip is programmed to enter power-down
mode (SPWD strobe issued), the power will be
turned off after CSn goes high. The power and
crystal oscillator will be turned on again when
CSn goes low.
By setting the CSn pin low, the voltage
regulator to the digital core turns on and the
crystal oscillator starts. The SO pin on the SPI
interface must go low before the first positive
edge of SCLK (setup time is given in
Table 15).
The voltage regulator for the digital core
requires one external decoupling capacitor.
The voltage regulator output should only be
used for driving the C113L.
23 General Purpose / Test Output Control Pins
The three digital output pins GDO0, GDO1,
and GDO2 are general control pins configured
at power-on-reset, this can be used to clock
the MCU in systems with only one crystal.
When the MCU is up and running, it can
change the clock frequency by writing to
IOCFG0.GDO0_CFG.
with
IOCFG0.GDO0_CFG,
IOCFG1.GDO1_CFG, and IOCFG2.GDO2_CFG
respectively. Table 29 shows the different
signals that can be monitored on the GDO
pins. These signals can be used as inputs to
the MCU.
If the IOCFGx.GDOx_CFG setting is less than
0x20 and IOCFGx_GDOx_INV is 0 (1), the
GDO0 and GDO2 pins will be hardwired to 0
(1), and the GDO1 pin will be hardwired to 1
(0) in the SLEEP state. These signals will be
hardwired until the CHIP_RDYn signal goes
low.
GDO1 is the same pin as the SO pin on the
SPI interface, thus the output programmed on
this pin will only be valid when CSn is high.
The default value for GDO1 is 3-stated which
is useful when the SPI interface is shared with
other devices.
If the IOCFGx.GDOx_CFG setting is 0x20 or
higher, the GDO pins will work as programmed
also in SLEEP state. As an example, GDO1 is
The default value for
GDO0 is
a
135 - 141 kHz clock output (XOSC frequency
divided by 192). Since the XOSC is turned on
high
impedance
in
all
states
if
IOCFG1.GDO1_CFG=0x2E.
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GDOx_CFG[5:0]
Description
0 (0x00)
Associated to the RX FIFO: Asserts when RX FIFO is filled at or above the RX FIFO threshold. De-
asserts when RX FIFO is drained below the same threshold.
1 (0x01)
Associated to the RX FIFO: Asserts when RX FIFO is filled at or above the RX FIFO threshold or the
end of packet is reached. De-asserts when the RX FIFO is empty.
2 (0x02) - 3 (0x03)
Reserved - used for test.
4 (0x04)
5 (0x05)
6 (0x06)
Asserts when the RX FIFO has overflowed. De-asserts when the FIFO has been flushed.
Reserved - used for test.
Asserts when sync word has been received, and de-asserts at the end of the packet. The pin will
also de-assert when a packet is discarded due to address or maximum length filtering or when the
radio enters RXFIFO_OVERFLOW state.
7 (0x07)
Asserts when a packet has been received with CRC OK. De-asserts when the first byte is read from
the RX FIFO.
8 (0x08) - 9 (0x09)
10 (0x0A)
Reserved - used for test.
Lock detector output. The PLL is in lock if the lock detector output has a positive transition or is
constantly logic high. To check for PLL lock the lock detector output should be used as an interrupt
for the MCU.
11 (0x0B)
Serial Clock. Synchronous to the data in synchronous serial mode.
Data is set up on the falling edge by CC113L when GDOx_INV=0.
12 (0x0C)
Serial Synchronous Data Output. Used for synchronous serial mode.
Serial Data Output. Used for asynchronous serial mode.
13 (0x0D)
14 (0x0E)
Carrier sense. High if RSSI level is above threshold. Cleared when entering IDLE mode.
CRC_OK. The last CRC comparison matched. Cleared when entering/restarting RX mode.
Reserved - used for test.
15 (0x0F)
16 (0x10) - 27 (0x1B)
28 (0x1C)
LNA_PD. Note: LNA_PD will have the same signal level in SLEEP and RX states. To control an
external LNA in applications where the SLEEP state is used it is recommended to use
GDOx_CFGx=0x2Finstead.
Reserved - used for test.
29 (0x1D) – 38 (0x26)
39 (0x27)
CLK_32k.
40 (0x28)
Reserved - used for test.
41 (0x29)
CHIP_RDYn.
42 (0x2A)
43 (0x2B)
44 (0x2C) – 45 (0x2D)
46 (0x2E)
47 (0x2F)
Reserved - used for test.
XOSC_STABLE.
Reserved - used for test.
High impedance (3-state).
HW to 0 (HW1 achieved by setting GDOx_INV=1). Can be used to control an external LNA
48 (0x30)
CLK_XOSC/1
CLK_XOSC/1.5
CLK_XOSC/2
CLK_XOSC/3
CLK_XOSC/4
CLK_XOSC/6
CLK_XOSC/8
CLK_XOSC/12
CLK_XOSC/16
CLK_XOSC/24
CLK_XOSC/32
CLK_XOSC/48
CLK_XOSC/64
CLK_XOSC/96
CLK_XOSC/128
CLK_XOSC/192
Note: There are 3 GDO pins, but only one CLK_XOSC/n can be selected as an
output at any time. If CLK_XOSC/n is to be monitored on one of the GDO pins,
the other two GDO pins must be configured to values less than 0x30. The
GDO0 default value is CLK_XOSC/192.
49 (0x31)
50 (0x32)
51 (0x33)
To optimize RF performance, these signals should not be used while the radio is
in RX mode.
52 (0x34)
53 (0x35)
54 (0x36)
55 (0x37)
56 (0x38)
57 (0x39)
58 (0x3A)
59 (0x3B)
60 (0x3C)
61 (0x3D)
62 (0x3E)
63 (0x3F)
Table 29: GDOx Signal Selection (x = 0, 1, or 2)
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24 Asynchronous and Synchronous Serial Operation
Several features and modes of operation have
been included in the CC113L to provide
backward compatibility with previous Chipcon
products and other existing RF communication
systems. For new systems, it is recommended
to use the built-in packet handling features, as
they can give more robust communication,
significantly offload the microcontroller, and
simplify software development.
24.1 Asynchronous Serial Operation
Asynchronous transfer is included in the
CC113L for backward compatibility with systems
that are already using the asynchronous data
transfer.
does proper oversampling and that it can
handle the jitter on the data output line. The
MCU should tolerate a jitter of ±1/8 of a bit
period as the data stream is time-discrete
using 8 samples per bit.
When asynchronous transfer is enabled, all
packet handling support is disabled and it is
not possible to use Manchester encoding.
In asynchronous serial mode there will be
glitches of 37 - 38.5 ns duration (1/XOSC)
occurring infrequently and with random
periods. A simple RC filter can be added to the
data output line between CC113L and the MCU
to get rid of the 37 - 38.5 ns glitches if
considered a problem. The filter 3 dB cut-off
frequency needs to be high enough so that the
data is not filtered and at the same time low
enough to remove the glitch. As an example,
for 2.4 kBaud data rate a 1 kΩ resistor and
2.7 nF capacitor can be used. This gives a 3
dB cut-off frequency of 59 kHz.
Asynchronous serial mode is enabled by
setting PKTCTRL0.PKT_FORMAT to 3. Data
output can be on GDO0, GDO1, or GDO2.
This is set by the IOCFG0.GDO0_CFG,
IOCFG1.GDO1_CFG and IOCFG2.GDO2_CFG
fields.
In asynchronous serial mode no data decision
is done on-chip and the raw data is put on the
data output line. When using asynchronous
serial mode make sure the interfacing MCU
24.2 Synchronous Serial Operation
Setting
PKTCTRL0.PKT_FORMAT
to
1
CC113L provides a clock that is used to sample
data on the data output line. The data output
pin can be any of the GDO pins. This is set by
enables synchronous serial mode. When using
this mode, sync detection should be disabled
together
(MDMCFG2.SYNC_MODE=000
with
CRC
calculation
and
the
IOCFG0.GDO0_CFG,
IOCFG1.GDO1_CFG, and IOCFG2.GDO2_CFG
PKTCTRL0.CRC_EN=0).
Infinite
be
(PKTCTRL0.LENGTH_CONFIG=10b).
packet
used
fields. The RX latency is 9 bits.
length
mode
should
The MCU must handle preamble and sync
word detection in software, together with CRC
calculation.
In synchronous serial mode, data is
transferred on a two-wire serial interface. The
25 System Considerations and Guidelines
25.1 SRD Regulations
International regulations and national laws
regulate the use of radio receivers and
transmitters. Short Range Devices (SRDs) for
license free operation below 1 GHz are usually
operated in the 315 MHz, 433 MHz, 868 MHz
or 915 MHz frequency bands. The CC113L is
specifically designed for such use with its
300 - 348 MHz, 387 - 464 MHz, and
779 - 928 MHz operating ranges. The most
important regulations when using the CC113L in
the 315 MHz, 433 MHz, 868 MHz, or 915 MHz
frequency bands are EN 300 220 V2.3.1
(Europe) and FCC CFR47 part 15 (USA).
For compliance with modulation bandwidth
requirements under EN 300 220 V2.3.1 in the
863 to 870 MHz frequency range it is
recommended to use a 26 MHz crystal for
frequencies below 869 MHz and a 27 MHz
crystal for frequencies above 869 MHz.
Please note that compliance with regulations
is dependent on the complete system
performance. It is the customer‟s responsibility
to ensure that the system complies with
regulations.
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25.2 Calibration in Multi-Channel Systems
disable the charge pump calibration. After
writing to FSCAL3[5:4], strobe SRX with
CC115L is highly suited for multi-channel
systems due to its agile frequency synthesizer
and effective communication interface.
MCSM0.FS_AUTOCAL=1
for
each
new
frequency. That is, VCO current and VCO
capacitance calibration is done, but not charge
pump current calibration. When charge pump
current calibration is disabled the calibration
time is reduced from 712/724 µs to 145/157 µs
(26 MHz crystal and TEST0 = 0x09/0B, see
Table 27). The blanking interval between each
frequency hop is then 220/232 µs.
Charge pump current, VCO current, and VCO
capacitance array calibration data is required
for each frequency when implementing a multi-
channel system. There are 3 ways of obtaining
the calibration data from the chip:
1) Calibration for every frequency change. The
PLL calibration time is 712/724 µs (26 MHz
crystal and TEST0 = 0x09/0B, see Table 27).
The blanking interval between each frequency
is then 787/799 µs.
There is a trade-off between blanking time and
memory space needed for storing calibration
data in non-volatile memory. Solution 2) above
gives the shortest blanking interval, but
requires more memory space to store
calibration values. This solution also requires
that the supply voltage and temperature do not
vary much in order to have a robust solution.
Solution 3) gives 567 µs smaller blanking
interval than solution 1).
2) Perform all necessary calibration at startup
and store the resulting FSCAL3, FSCAL2, and
FSCAL1 register values in MCU memory. The
VCO capacitance calibration FSCAL1 register
value must be found for each RF frequency to
be used. The VCO current calibration value
and the charge pump current calibration value
available in FSCAL2 and FSCAL3 respectively
are not dependent on the RF frequency, so the
same value can therefore be used for all RF
frequencies for these two registers. Between
each frequency change, the calibration
process can then be replaced by writing the
FSCAL3, FSCAL2 and FSCAL1register values
that corresponds to the next RF frequency.
The PLL turn on time is approximately 75 µs
(Table 26). The blanking interval between
each frequency hop is then approximately
75 µs.
The
recommended
settings
change
for
with
TEST0.VCO_SEL_CAL_EN
frequency. This means that one should always
use SmartRF Studio [4] to get the correct
settings for a specific frequency before doing a
calibration, regardless of which calibration
method is being used.
Note: The content in the TEST0 register is
not retained in SLEEP state, thus it is
necessary to re-write this register when
returning from the SLEEP state.
3) Run calibration on a single frequency at
startup. Next write 0 to FSCAL3[5:4] to
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26 Configuration Registers
There are also 8 status registers that are listed
in Table 32. These registers, which are read-
only, contain information about the status of
CC113L.
The configuration of CC113L is done by
programming 8-bit registers. The optimum
configuration data based on selected system
parameters are most easily found by using the
SmartRF Studio software [4]. Complete
descriptions of the registers are given in the
following tables. After chip reset, all the
registers have default values as shown in the
tables. The optimum register setting might
differ from the default value. After a reset, all
registers that shall be different from the default
value therefore needs to be programmed
through the SPI interface.
The RX FIFO is accessed through one 8-bit
register. During the header byte transfer and
while writing data to a register, a status byte is
returned on the SO line. This status byte is
described in Table 16 on page 23.
Table 33 summarizes the SPI address space.
The address to use is given by adding the
base address to the left and the burst and
read/write bits on the top. Note that the burst
bit has different meaning for base addresses
above and below 0x2F.
There are 8 command strobe registers, listed
in Table 30. Accessing these registers will
initiate the change of an internal state or
mode. There are 43 normal 8-bit configuration
registers listed in Table 31, and SmartRF
Studio [4] will provide recommended settings
for these registers2.
“Reserved” must be configured according to
SmartRF Studio
2 Addresses marked as “Not Used” can be part
of a burst access and one can write a dummy
value to them. Addresses marked as
Address
0x30
Strobe Name
SRES
Description
Reset chip.
0x31
Reserved
SXOFF
0x32
Turn off crystal oscillator.
0x33
SCAL
Calibrate frequency synthesizer and turn it off. SCALcan be strobed from IDLE mode
without setting manual calibration mode (MCSM0.FS_AUTOCAL=0)
0x34
SRX
In IDLE state: Enable RX. Perform calibration first if MCSM0.FS_AUTOCAL=1.
0x35
Reserved
SIDLE
0x36
Enter IDLE state
0x37 - 0x38
0x39
Reserved
SPWD
SFRX
Enter power down mode when CSn goes high.
0x3A
Flush the RX FIFO buffer. Only issue SFRXin IDLE or RXFIFO_OVERFLOW states.
0x3B - 0x3C
0x3D
Reserved
SNOP
No operation. May be used to get access to the chip status byte.
Table 30: Command Strobes
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Address
Register
Description
Preserved in
SLEEP State
Details on
Page Number
0x00
IOCFG2
IOCFG1
IOCFG0
FIFOTHR
SYNC1
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
Yes
49
49
49
50
51
51
51
51
52
52
52
52
53
53
53
53
53
53
54
55
55
55
55
55
56
57
58
59
60
61
GDO2output pin configuration
GDO1output pin configuration
GDO0output pin configuration
RX FIFO threshold
0x01
0x02
0x03
0x04
Sync word, high byte
0x05
SYNC0
Sync word, low byte
0x06
PKTLEN
PKTCTRL1
PKTCTRL0
ADDR
Packet length
0x07
Packet automation control
Packet automation control
Device address
0x08
0x09
0x0A
0x0B
0x0C
0x0D
0x0E
0x0F
0x10
CHANNR
FSCTRL1
FSCTRL0
FREQ2
Channel number
Frequency synthesizer control
Frequency synthesizer control
Frequency control word, high byte
Frequency control word, middle byte
Frequency control word, low byte
Modem configuration
FREQ1
FREQ0
MDMCFG4
MDMCFG3
MDMCFG2
MDMCFG1
MDMCFG0
DEVIATN
MCSM2
0x11
Modem configuration
0x12
Modem configuration
0x13
Modem configuration
0x14
Modem configuration
0x15
Modem deviation setting
Main Radio Control State Machine configuration
Main Radio Control State Machine configuration
Main Radio Control State Machine configuration
Frequency Offset Compensation configuration
Bit Synchronization configuration
AGC control
0x16
0x17
MCSM1
0x18
MCSM0
0x19
FOCCFG
BSCFG
0x1A
0x1B
0x1C
0x1D
0x1E - 0x1F
0x20
AGCTRL2
AGCTRL1
AGCTRL0
Not Used
RESERVED
FREND1
Not Used
FSCAL3
FSCAL2
FSCAL1
FSCAL0
Not Used
RESERVED
TEST2
AGC control
AGC control
Yes
Yes
61
62
0x21
Front end RX configuration
0x22
0x23
Frequency synthesizer calibration
Frequency synthesizer calibration
Frequency synthesizer calibration
Frequency synthesizer calibration
Yes
Yes
Yes
Yes
62
62
62
62
0x24
0x25
0x26
0x27 - 0x28
0x29 - 0x2B
0x2C
0x2D
0x2E
No
No
No
No
63
63
63
63
Various test settings
Various test settings
Various test settings
TEST1
TEST0
Table 31: Configuration Registers Overview
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CC113L
Address
Register
PARTNUM
VERSION
FREQEST
CRC_REG
RSSI
Description
Details on page number
0x30 (0xF0)
0x31 (0xF1)
0x32 (0xF2)
0x33 (0xF3)
0x34 (0xF4)
0x35 (0xF5)
64
64
64
64
64
65
Part number for CC113L
Current version number
Frequency Offset Estimate
CRC OK
Received signal strength indication
MARCSTATE Control state machine state
Reserved
0x36 - 0x37
(0xF6 - 0xF7)
0x38 (0xF8)
PKTSTATUS
Reserved
Current GDOx status and packet status
66
0x39 - 0x3A
(0xF9 - 0xFA)
0x3B (0xFB)
RXBYTES
Reserved
Overflow and number of bytes in the RX FIFO 66
0x3C - 0x3D
(0xFC - 0xFD)
Table 32: Status Registers Overview
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CC113L
Write
Single Byte
+0x00
Read
Burst
+0x40
Single Byte
+0x80
Burst
+0xC0
0x00
0x01
0x02
0x03
0x04
0x05
0x06
0x07
0x08
0x09
0x0A
0x0B
0x0C
0x0D
0x0E
0x0F
0x10
0x11
0x12
0x13
0x14
0x15
0x16
0x17
0x18
0x19
0x1A
0x1B
0x1C
0x1D
0x1E
0x1F
0x20
0x21
0x22
0x23
0x24
0x25
0x26
0x27
0x28
0x29
0x2A
0x2B
0x2C
0x2D
0x2E
0x2F
0x30
0x31
0x32
0x33
0x34
0x35
0x36
0x37
0x38
0x39
0x3A
0x3B
0x3C
0x3D
0x3E
0x3F
IOCFG2
IOCFG1
IOCFG0
FIFOTHR
SYNC1
SYNC0
PKTLEN
PKTCTRL1
PKTCTRL0
ADDR
CHANNR
FSCTRL1
FSCTRL0
FREQ2
FREQ1
FREQ0
MDMCFG4
MDMCFG3
MDMCFG2
MDMCFG1
MDMCFG0
DEVIATN
MCSM2
MCSM1
MCSM0
FOCCFG
BSCFG
AGCCTRL2
AGCCTRL1
AGCCTRL0
Not Used
Not Used
RESERVED
FREND1
Not Used
FSCAL3
FSCAL2
FSCAL1
FSCAL0
Not Used
Not Used
RESERVED
RESERVED
RESERVED
TEST2
TEST1
TEST0
Not Used
SRES
Reserved
SXOFF
SCAL
SRX
Reserved
SIDLE
Reserved
Reserved
SPWD
SRES
PARTNUM
VERSION
FREQEST
CRC_REG
RSSI
MARCSTATE
Reserved
Reserved
PKTSTATUS
Reserved
Reserved
RXBYTES
Reserved
Reserved
Reserved
RX FIFO
Reserved
SXOFF
SCAL
SRX
Reserved
SIDLE
Reserved
Reserved
SPWD
SFRX
SFRX
Reserved
Reserved
SNOP
Reserved
Reserved
Reserved
Reserved
SNOP
Reserved
RX FIFO
Table 33: SPI Address Space
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CC113L
26.1 Configuration Register Details - Registers with preserved values in SLEEP state
0x00: IOCFG2 - GDO2 Output Pin Configuration
Bit
7
Field Name
Reset
R/W
R0
Description
Not used
6
0
R/W
Invert output, i.e. select active low (1) / high (0)
GDO2_INV
5:0
41 (101001)
R/W
Default is CHP_RDYn(See Table 29 on page 42).
GDO2_CFG[5:0]
0x01: IOCFG1 - GDO1 Output Pin Configuration
Bit
7
Field Name
GDO_DS
Reset
R/W
R/W
R/W
R/W
Description
0
Set high (1) or low (0) output drive strength on the GDO pins.
Invert output, i.e. select active low (1) / high (0)
Default is 3-state (See Table 29 on page 42).
6
0
GDO1_INV
5:0
46 (101110)
GDO1_CFG[5:0]
0x02: IOCFG0 - GDO0 Output Pin Configuration
Bit
7
Field Name
Reset
R/W
R/W
R/W
R/W
Description
0
Use setting from SmartRF Studio [4]
Invert output, i.e. select active low (1) / high (0)
Default is CLK_XOSC/192 (See Table 29 on page 42).
6
0
GDO0_INV
5:0
63 (0x3F)
GDO0_CFG[5:0]
It is recommended to disable the clock output in initialization, in
order to optimize RF performance.
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CC113L
0x03: FIFOTHR - RX FIFO Thresholds
Bit Field Name
Reset
R/W
R/W
R/W
Description
7
0
0
Use setting from SmartRF Studio [4]
6
ADC_RETENTION
0: TEST1 = 0x31 and TEST2= 0x88 when waking up from SLEEP
1: TEST1 = 0x35 and TEST2 = 0x81 when waking up from SLEEP
Note that the changes in the TEST registers due to the ADC_RETENTION bit
setting are only seen INTERNALLY in the analog part. The values read from
the TEST registers when waking up from SLEEP mode will always be the
reset value.
The ADC_RETENTION bit should be set to 1before going into SLEEP mode if
settings with an RX filter bandwidth below 325 kHz are wanted at time of
wake-up.
5:4 CLOSE_IN_RX[1:0] 0 (00)
R/W
For more details, please see DN010 [5]
Setting
0 (00)
1 (01)
2 (10)
3 (11)
RX Attenuation, Typical Values
0 dB
6 dB
12 dB
18 dB
3:0 FIFO_THR[3:0]
7 (0111)
R/W
Set the threshold for the RX FIFO. The threshold is exceeded when the
number of bytes in the RX FIFO is equal to or higher than the threshold value.
Setting
Bytes in RX FIFO
0 (0000)
1 (0001)
2 (0010)
3 (0011)
4 (0100)
5 (0101)
6 (0110)
7 (0111)
8 (1000)
9 (1001)
10 (1010)
11 (1011)
12 (1100)
13 (1101)
14 (1110)
15 (1111)
4
8
12
16
20
24
28
32
36
40
44
48
52
56
60
64
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0x04: SYNC1 - Sync Word, High Byte
Bit Field Name
Reset
211 (0xD3)
R/W Description
7:0 SYNC[15:8]
R/W 8 MSB of 16-bit sync word
0x05: SYNC0 - Sync Word, Low Byte
Bit Field Name
Reset
R/W
Description
7:0 SYNC[7:0]
145 (0x91)
R/W
8 LSB of 16-bit sync word
0x06: PKTLEN - Packet Length
Bit Field Name
Reset
R/W
Description
7:0 PACKET_LENGTH
255 (0xFF)
R/W
Indicates the packet length when fixed packet length mode is enabled.
If variable packet length mode is used, this value indicates the
maximum packet length allowed. This value must be different from 0.
0x07: PKTCTRL1 - Packet Automation Control
Bit Field Name
Reset
R/W
R/W
R0
Description
7:5
4
0 (000)
Use setting from SmartRF Studio [4]
Not Used.
0
0
3
CRC_AUTOFLUSH
APPEND_STATUS
R/W
Enable automatic flush of RX FIFO when CRC is not OK. This requires
that only one packet is in the RX FIFO and that packet length is limited
to the RX FIFO size.
2
1
R/W
R/W
When enabled, two status bytes will be appended to the payload of the
packet. The status bytes contain the RSSI value, as well as CRC OK.
1:0 ADR_CHK[1:0]
0 (00)
Controls address check configuration of received packages.
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Address check configuration
No address check
Address check, no broadcast
Address check and 0 (0x00) broadcast
Address check and 0 (0x00) and 255 (0xFF) broadcast
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0x08: PKTCTRL0 - Packet Automation Control
Bit Field Name
Reset
R/W
R0
Description
7
Not used
6
1
R/W
R/W
Use setting from SmartRF Studio [4]
Format of RX data
5:4 PKT_FORMAT[1:0]
0 (00)
Setting
0 (00)
1 (01)
Packet format
Normal mode, use RX FIFO
Synchronous serial mode, Data out on either of the
GDOx pins
2 (10)
3 (11)
Reserved
Asynchronous serial mode, Data out on either of the
GDOx pins
3
0
1
R0
Not used
2
CRC_EN
R/W
1: CRC calculation enabled
0: CRC calculation disabled
Configure the packet length
1:0 LENGTH_CONFIG[1:0]
1 (01)
R/W
Setting
0 (00)
Packet length configuration
Fixed packet length mode. Length configured in
PKTLENregister
1 (01)
Variable packet length mode. Packet length configured
by the first byte received after sync word
2 (10)
3 (11)
Infinite packet length mode
Reserved
0x09: ADDR - Device Address
Bit Field Name
Reset
R/W
Description
7:0 DEVICE_ADDR[7:0]
0 (0x00)
R/W
Address used for packet filtration. Optional broadcast addresses are
0 (0x00) and 255 (0xFF).
0x0A: CHANNR - Channel Number
Bit Field Name
Reset
R/W
Description
7:0 CHAN[7:0]
0 (0x00)
R/W
The 8-bit unsigned channel number, which is multiplied by the channel
spacing setting and added to the base frequency.
0x0B: FSCTRL1 - Frequency Synthesizer Control
Bit Field Name
Reset
R/W
R0
Description
7:6
Not used
5
0
R/W
Use setting from SmartRF Studio [4]
4:0 FREQ_IF[4:0]
15 (01111) R/W
The desired IF frequency to employ in RX. Subtracted from FS base
frequency in RX and controls the digital complex mixer in the
demodulator.
fXOSC
210
fIF
FREQ _ IF
The default value gives an IF frequency of 381kHz, assuming a 26.0
MHz crystal.
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0x0C: FSCTRL0 - Frequency Synthesizer Control
Bit Field Name
Reset
R/W
Description
7:0 FREQOFF[7:0]
0 (0x00)
R/W
Frequency offset added to the base frequency before being used by the
frequency synthesizer. (2s-complement).
Resolution is FXTAL/214 (1.59 kHz - 1.65kHz); range is ±202 kHz to ±210
kHz, dependent of XTAL frequency.
0x0D: FREQ2 - Frequency Control Word, High Byte
Bit
Field Name
Reset
R/W
Description
7:6
FREQ[23:22]
0 (00)
R
FREQ[23:22]is always 0 (the FREQ2register is less than 36 with
26 - 27 MHz crystal)
5:0
FREQ[21:16]
30
(011110)
R/W
FREQ[23:0]is the base frequency for the frequency synthesiser in
increments of fXOSC/216.
fXOSC
216
fcarrier
FREQ[23:0]
0x0E: FREQ1 - Frequency Control Word, Middle Byte
Bit
Field Name
Reset
R/W
Description
7:0
FREQ[15:8]
196 (0xC4)
R/W
Ref. FREQ2register
0x0F: FREQ0 - Frequency Control Word, Low Byte
Bit
Field Name
Reset
R/W
Description
7:0
FREQ[7:0]
236 (0xEC) R/W
Ref. FREQ2register
0x10: MDMCFG4 - Modem Configuration
Bit
7:6
5:4
Field Name
Reset
2 (10)
0 (00)
R/W
R/W
R/W
Description
CHANBW_E[1:0]
CHANBW_M[1:0]
Sets the decimation ratio for the delta-sigma ADC input stream and thus
the channel bandwidth.
fXOSC
BWchannel
8 (4 CHANBW _ M)·2CHANBW _ E
The default values give 203 kHz channel filter bandwidth, assuming a 26.0
MHz crystal.
3:0
DRATE_E[3:0]
12 (1100)
R/W
The exponent of the user specified symbol rate
0x11: MDMCFG3 - Modem Configuration
Bit
Field Name
Reset
R/W
Description
7:0
DRATE_M[7:0]
34 (0x22)
R/W
The mantissa of the user specified symbol rate. The symbol rate is
configured using an unsigned, floating-point number with 9-bit mantissa
and 4-bit exponent. The 9th bit is a hidden „1‟. The resulting data rate is:
(256 DRATE _ M ) 2DRATE _ E
RDATA
fXOSC
228
The default values give a data rate of 115.051 kBaud (closest setting to
115.2 kBaud), assuming a 26.0 MHz crystal.
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0x12: MDMCFG2 - Modem Configuration
Bit Field Name
Reset
R/W
Description
7
DEM_DCFILT_OFF
0
R/W
Disable digital DC blocking filter before demodulator.
0 = Enable (better sensitivity)
1 = Disable (current optimized). Only for data rates ≤ 250 kBaud
The recommended IF frequency changes when the DC blocking is disabled.
Please use SmartRF Studio [4] to calculate correct register setting.
6:4 MOD_FORMAT[2:0]
0 (000)
R/W
The modulation format of the radio signal
Setting
0 (000)
1 (001)
2 (010)
3 (011)
4 (100)
5 (101)
6 (110)
7 (111)
Modulation format
2-FSK
GFSK
Reserved
OOK
4-FSK
Reserved
Reserved
Reserved
4-FSK modulation cannot be used together with Manchester encoding
3
MANCHESTER_EN
0
R/W
R/W
Enables Manchester decoding.
0 = Disable
1 = Enable
Manchester encoding cannot be used when using asynchronous serial
mode or 4-FSK modulation
2:0 SYNC_MODE[2:0]
2 (010)
Combined sync-word qualifier mode.
The values 0 and 4 disables preamble and sync word detection
The values 1, 2, 5, and 6 enables 16-bit sync word detection. Only 15 of 16
bits need to match when using setting 1 or 5. The values 3 and 7 enables
32-bits sync word detection (only 30 of 32 bits need to match).
Setting
0 (000)
1 (001)
2 (010)
3 (011)
4 (100)
5 (101)
6 (110)
7 (111)
Sync-word qualifier mode
No preamble/sync
15/16 sync word bits detected
16/16 sync word bits detected
30/32 sync word bits detected
No preamble/sync, carrier-sense above threshold
15/16 + carrier-sense above threshold
16/16 + carrier-sense above threshold
30/32 + carrier-sense above threshold
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0x13: MDMCFG1 - Modem Configuration
Bit
7
Field Name
Reset
R/W
R/W
R0
Description
0
Use setting from SmartRF Studio [4]
Not used
6:2
1:0
CHANSPC_E[1:0]
2 (10)
R/W
2 bit exponent of channel spacing
0x14: MDMCFG0 - Modem Configuration
Bit
Field Name
Reset
R/W
Description
7:0
CHANSPC_M[7:0]
248 (0xF8) R/W
8-bit mantissa of channel spacing. The channel spacing is multiplied by
the channel number CHANand added to the base frequency. It is
unsigned and has the format:
fXOSC
218
CHANNEL
(256 CHANSPC _ M) 2CHANSPC _ E
The default values give 199.951 kHz channel spacing (the closest
setting to 200 kHz), assuming 26.0 MHz crystal frequency.
0x15: DEVIATN - Modem Deviation Setting
Bit
Field Name
Reset
R/W
R0
Description
Not used.
7
6:4
3
DEVIATION_E[2:0]
DEVIATION_M[2:0]
4 (100)
7 (111)
R/W
R0
Deviation exponent.
Not used.
2:0
R/W
2-FSK/
GFSK/
4-FSK
OOK
Specifies the expected frequency deviation of
incoming signal, must be approximately right for
demodulation to be performed reliably and robustly.
This setting has no effect.
0x16: MCSM2 - Main Radio Control State Machine Configuration
Bit
7:5
4
Field Name
Reset
R/W
R0
Description
Not used
RX_TIME_RSSI
0
R/W
Direct RX termination based on RSSI measurement (carrier sense).
For OOK modulation, RX times out if there is no carrier sense in the
first 8 symbol periods.
3:0
7 (0111)
R/W
Use setting from SmartRF Studio [4]
0x17: MCSM1 - Main Radio Control State Machine Configuration
Bit
7:6
5:4
3:2
Field Name
Reset
R/W
R0
Description
Not used
3 (11)
0 (00)
R/W
R/W
Use setting from SmartRF Studio [4]
Select what should happen when a packet has been received.
RXOFF_MODE[1:0]
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Next state after finishing packet reception
IDLE
Reserved
Reserved
Stay in RX
1:0
0 (00)
R/W
Use setting from SmartRF Studio [4]
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0x18: MCSM0 - Main Radio Control State Machine Configuration
Bit
7:6
5:4
Field Name
Reset
R/W
R0
Description
Not used
FS_AUTOCAL[1:0]
0 (00)
R/W
Automatically calibrate when going to to/from RX mode
Setting
0 (00)
1 (01)
2 (10)
3 (11)
When to perform automatic calibration
Never (manually calibrate using SCALstrobe)
When going from IDLE to RX
When going from RX back to IDLE automatically
Every 4th time when going from RX to IDLE automatically
3:2
PO_TIMEOUT
1 (01)
R/W
Programs the number of times the six-bit ripple counter must expire after
the XOSC has settled before CHP_RDYngoes low. 3
If XOSC is on (stable) during power-down, PO_TIMEOUTshall be set so
that the regulated digital supply voltage has time to stabilize before
CHP_RDYngoes low (PO_TIMEOUT=2recommended). Typical start-up
time for the voltage regulator is 50 μs.
For robust operation it is recommended to use PO_TIMEOUT = 2 or 3
when XOSC is off during power-down.
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Expire count
Timeout after XOSC start
Approx. 2.3 - 2.4 μs
Approx. 37 - 39 μs
1
16
64
256
Approx. 149 - 155 μs
Approx. 597 - 620 μs
Exact timeout depends on crystal frequency.
Use setting from SmartRF Studio [4]
1
0
0
0
R/W
R/W
XOSC_FORCE_ON
Force the XOSC to stay on in the SLEEP state.
3
Note that the XOSC_STABLE signal will be asserted at the same time as the CHIP_RDYn signal;
i.e. the PO_TIMEOUT delays both signals and does not insert a delay between the signals.
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0x19: FOCCFG - Frequency Offset Compensation Configuration
Bit Field Name
Reset R/W Description
7:6
R0
Not used
5
FOC_BS_CS_GATE
1
R/W If set, the demodulator freezes the frequency offset compensation and clock
recovery feedback loops until the CS signal goes high.
4:3 FOC_PRE_K[1:0]
2 (10) R/W The frequency compensation loop gain to be used before a sync word is
detected.
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Freq. compensation loop gain before sync word
K
2K
3K
4K
2
FOC_POST_K
1
R/W The frequency compensation loop gain to be used after a sync word is detected.
Setting
Freq. compensation loop gain after sync word
0
1
Same as FOC_PRE_K
K/2
1:0 FOC_LIMIT[1:0]
2 (10) R/W The saturation point for the frequency offset compensation algorithm:
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Saturation point (max compensated offset)
±0 (no frequency offset compensation)
±BWCHAN/8
±BWCHAN/4
±BWCHAN/2
Frequency offset compensation is not supported for OOK. Always use
FOC_LIMIT=0 with this modulation format.
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0x1A: BSCFG - Bit Synchronization Configuration
Bit Field Name
Reset R/W Description
7:6 BS_PRE_KI[1:0]
1 (01) R/W The clock recovery feedback loop integral gain to be used before a sync word is
detected (used to correct offsets in data rate):
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Clock recovery loop integral gain before sync word
KI
2KI
3KI
4KI
5:4 BS_PRE_KP[1:0] 2 (10) R/W The clock recovery feedback loop proportional gain to be used before a sync word
is detected.
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Clock recovery loop proportional gain before sync word
KP
2KP
3KP
4KP
3
2
BS_POST_KI
BS_POST_KP
1
1
R/W The clock recovery feedback loop integral gain to be used after a sync word is
detected.
Setting
Clock recovery loop integral gain after sync word
0
1
Same as BS_PRE_KI
KI /2
R/W The clock recovery feedback loop proportional gain to be used after a sync word is
detected.
Setting
Clock recovery loop proportional gain after sync word
0
1
Same as BS_PRE_KP
KP
1:0 BS_LIMIT[1:0]
0 (00) R/W The saturation point for the data rate offset compensation algorithm:
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Data rate offset saturation (max data rate difference)
±0 (No data rate offset compensation performed)
±3.125 % data rate offset
±6.25 % data rate offset
±12.5 % data rate offset
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0x1B: AGCCTRL2 - AGC Control
Bit Field Name
Reset
R/W
Description
7:6 MAX_DVGA_GAIN[1:0] 0 (00)
R/W
Reduces the maximum allowable DVGA gain.
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Allowable DVGA settings
All gain settings can be used
The highest gain setting cannot be used
The 2 highest gain settings cannot be used
The 3 highest gain settings cannot be used
5:3 MAX_LNA_GAIN[2:0]
0 (000)
R/W
Sets the maximum allowable LNA + LNA 2 gain relative to the maximum
possible gain.
Setting
0 (000)
1 (001)
2 (010)
3 (011)
4 (100)
5 (101)
6 (110)
7 (111)
Maximum allowable LNA + LNA 2 gain
Maximum possible LNA + LNA 2 gain
Approx. 2.6 dB below maximum possible gain
Approx. 6.1 dB below maximum possible gain
Approx. 7.4 dB below maximum possible gain
Approx. 9.2 dB below maximum possible gain
Approx. 11.5 dB below maximum possible gain
Approx. 14.6 dB below maximum possible gain
Approx. 17.1 dB below maximum possible gain
2:0 MAGN_TARGET[2:0]
3 (011)
R/W
These bits set the target value for the averaged amplitude from the digital
channel filter (1 LSB = 0 dB).
Setting
0 (000)
1 (001)
2 (010)
3 (011)
4 (100)
5 (101)
6 (110)
7 (111)
Target amplitude from channel filter
24 dB
27 dB
30 dB
33 dB
36 dB
38 dB
40 dB
42 dB
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0x1C: AGCCTRL1 - AGC Control
Bit Field Name
Reset
R/W
R0
Description
7
Not used
6
AGC_LNA_PRIORITY
1
R/W
Selects between two different strategies for LNA and LNA 2
gain adjustment. When 1, the LNA gain is decreased first.
When 0, the LNA 2 gain is decreased to minimum before
decreasing LNA gain.
5:4 CARRIER_SENSE_REL_THR[1:0] 0 (00)
R/W
Sets the relative change threshold for asserting carrier sense
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Carrier sense relative threshold
Relative carrier sense threshold disabled
6 dB increase in RSSI value
10 dB increase in RSSI value
14 dB increase in RSSI value
3:0 CARRIER_SENSE_ABS_THR[3:0] 0 (0000)
R/W
Sets the absolute RSSI threshold for asserting carrier sense.
The 2-complement signed threshold is programmed in steps
of 1 dB and is relative to the MAGN_TARGET setting.
Setting
Carrier sense absolute threshold
(Equal to channel filter amplitude when AGC
has not decreased gain)
-8 (1000)
-7 (1001)
…
Absolute carrier sense threshold disabled
7 dB below MAGN_TARGETsetting
…
-1 (1111)
0 (0000)
1 (0001)
…
1 dB below MAGN_TARGETsetting
At MAGN_TARGETsetting
1 dB above MAGN_TARGETsetting
…
7 (0111)
7 dB above MAGN_TARGETsetting
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0x1D: AGCCTRL0 - AGC Control
Bit
Field Name
Reset
R/W
Description
7:6
HYST_LEVEL[1:0]
2 (10)
R/W
Sets the level of hysteresis on the magnitude deviation (internal
AGC signal that determine gain changes).
Setting
0 (00)
1 (01)
Description
No hysteresis, small symmetric dead zone, high gain
Low hysteresis, small asymmetric dead zone, medium
gain
2 (10)
Medium hysteresis, medium asymmetric dead zone,
medium gain
3 (11)
Large hysteresis, large asymmetric dead zone, low gain
5:4
WAIT_TIME[1:0]
1 (01)
R/W
Sets the number of channel filter samples from a gain adjustment
has been made until the AGC algorithm starts accumulating new
samples.
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Channel filter samples
8
16
24
32
3:2
AGC_FREEZE[1:0]
0 (00)
R/W
Control when the AGC gain should be frozen.
Setting
0 (00)
1 (01)
Function
Normal operation. Always adjust gain when required.
The gain setting is frozen when a sync word has been
found.
2 (10)
3 (11)
Manually freeze the analogue gain setting and continue
to adjust the digital gain.
Manually freezes both the analogue and the digital gain
setting. Used for manually overriding the gain.
1:0
FILTER_LENGTH[1:0]
1 (01)
R/W
2-FSK and 4-FSK: Sets the averaging length for the amplitude from
the channel filter.
OOK: Sets the OOK decision boundary for OOK reception.
Setting
0 (00)
1 (01)
2 (10)
3 (11)
Channel filter samples
OOK decision boundary
8
4 dB
16
32
64
8 dB
12 dB
16 dB
0x20: RESERVED
Bit
7:3
2
Field Name
Reset
R/W
R/W
R0
Description
31 (11111)
Use setting from SmartRF Studio [4]
Not used
1:0
0 (00)
R/W
Use setting from SmartRF Studio [4]
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0x21: FREND1 - Front End RX Configuration
Bit Field Name
Reset
1 (01)
1 (01)
1 (01)
2 (10)
R/W
R/W
R/W
R/W
R/W
Description
7:6 LNA_CURRENT[1:0]
5:4 LNA2MIX_CURRENT[1:0]
3:2 LODIV_BUF_CURRENT_RX[1:0]
1:0 MIX_CURRENT[1:0]
Adjusts front-end LNA PTAT current output
Adjusts front-end PTAT outputs
Adjusts current in RX LO buffer (LO input to mixer)
Adjusts current in mixer
0x23: FSCAL3 - Frequency Synthesizer Calibration
Bit Field Name
Reset
R/W
Description
7:6 FSCAL3[7:6]
2 (10)
R/W
Frequency synthesizer calibration configuration. The value
to write in this field before calibration is given by the
SmartRF Studio software [4].
5:4 CHP_CURR_CAL_EN[1:0]
3:0 FSCAL3[3:0]
2 (10)
R/W
R/W
Disable charge pump calibration stage when 0.
9 (1001)
Frequency synthesizer calibration result register. Digital bit
vector defining the charge pump output current, on an
exponential scale: I_OUT = I0·2FSCAL3[3:0]/4
Please see Section 25.2 for more details.
0x24: FSCAL2 - Frequency Synthesizer Calibration
Bit Field Name
Reset
R/W
R0
Description
7:6
Not used
5
VCO_CORE_H_EN
0
R/W
R/W
Choose high (1) / low (0) VCO
4:0 FSCAL2[4:0]
10 (01010)
Frequency synthesizer calibration result register. VCO
current calibration result and override value.
Please see Section 25.2 for more details.
0x25: FSCAL1 - Frequency Synthesizer Calibration
Bit Field Name
7:6
Reset
R/W
R0
Description
Not used
5:0 FSCAL1[5:0]
32 (0x20)
R/W
Frequency synthesizer calibration result register. Capacitor
array setting for VCO coarse tuning.
Please see Section 25.2 for more details.
0x26: FSCAL0 - Frequency Synthesizer Calibration
Bit Field Name
7
Reset
R/W
R0
Description
Not used
6:0 FSCAL0[6:0]
13 (0x0D)
R/W
Frequency synthesizer calibration control. The value to use
in this register is given by the SmartRF Studio software [4].
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26.2 Configuration Register Details - Registers that Loose Programming in SLEEP State
0x29: RESERVED
Bit Field Name
Reset
R/W
Description
7:0
89 (0x59)
R/W
Use setting from SmartRF Studio [4]
0x2A: RESERVED
Bit Field Name
Reset
R/W
Description
7:0
127 (0x7F)
R/W
Use setting from SmartRF Studio [4]
0x2B: RESERVED
Bit Field Name
Reset
R/W
Description
7:0
63 (0x3F)
R/W
Use setting from SmartRF Studio [4]
0x2C: TEST2 - Various Test Settings
Bit Field Name
Reset
R/W
Description
7:0 TEST2[7:0]
136 (0x88)
R/W
Use setting from SmartRF Studio [4]
This register will be forced to 0x88 or 0x81 when it wakes up from SLEEP
mode, depending on the configuration of FIFOTHR.ADC_RETENTION.
Note that the value read from this register when waking up from SLEEP
always is the reset value (0x88) regardless of the ADC_RETENTION
setting. The inverting of some of the bits due to the ADC_RETENTION
setting is only seen INTERNALLY in the analog part.
0x2D: TEST1 - Various Test Settings
Bit Field Name
Reset
R/W
Description
7:0 TEST1[7:0]
49 (0x31)
R/W
Use setting from SmartRF Studio [4]
This register will be forced to 0x31 or 0x35 when it wakes up from SLEEP
mode, depending on the configuration of FIFOTHR.ADC_RETENTION.
Note that the value read from this register when waking up from SLEEP
always is the reset value (0x31) regardless of the ADC_RETENTION
setting. The inverting of some of the bits due to the ADC_RETENTION
setting is only seen INTERNALLY in the analog part.
0x2E: TEST0 - Various Test Settings
Bit Field Name
Reset
R/W
R/W
R/W
R/W
Description
7:2 TEST0[7:2]
2 (000010)
Use setting from SmartRF Studio [4]
Enable VCO selection calibration stage when 1
Use setting from SmartRF Studio [4]
1
0
VCO_SEL_CAL_EN
TEST0[0]
1
1
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26.3 Status Register Details
0x30 (0xF0): PARTNUM - Chip ID
Bit Field Name
Reset
R/W
Description
7:0 PARTNUM[7:0]
0 (0x00)
R
Chip part number
0x31 (0xF1): VERSION - Chip ID
Bit Field Name
Reset
R/W
Description
7:0 VERSION[7:0]
8 (0x08)
R
Chip version number.
0x32 (0xF2): FREQEST - Frequency Offset Estimate from Demodulator
Bit Field Name
Reset
R/W
Description
7:0 FREQOFF_EST
R
The estimated frequency offset (2‟s complement) of the carrier. Resolution is
FXTAL/214 (1.59 - 1.65 kHz); range is ±202 kHz to ±210 kHz, depending on XTAL
frequency.
Frequency offset compensation is only supported for 2-FSK, GFSK, and 4-FSK
modulation. This register will read 0 when using OOK modulation.
0x33 (0xF3): CRC_REG - CRC OK
Bit Field Name
Reset
R/W
Description
7
CRC OK
R
R
The last CRC comparison matched. Cleared when entering/restarting RX mode.
Reserved
6:0
0x34 (0xF4): RSSI - Received Signal Strength Indication
Bit Field Name
Reset
R/W
Description
7:0 RSSI
R
Received signal strength indicator
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0x35 (0xF5): MARCSTATE - Main Radio Control State Machine State
Bit
7:5
4:0
Field Name
Reset
R/W
R0
R
Description
Not used
MARC_STATE[4:0]
Main Radio Control FSM State
Value
State name
SLEEP
State (Figure 21, page 35)
0 (0x00)
1 (0x01)
2 (0x02)
3 (0x03)
4 (0x04)
5 (0x05)
6 (0x06)
7 (0x07)
8 (0x08)
9 (0x09)
10 (0x0A)
11 (0x0B)
12 (0x0C)
13 (0x0D)
14 (0x0E)
15 (0x0F)
16 (0x10)
17 (0x11)
SLEEP
IDLE
IDLE
XOFF
XOFF
VCOON_MC
REGON_MC
MANCAL
VCOON
MANCAL
MANCAL
MANCAL
FS_WAKEUP
FS_WAKEUP
CALIBRATE
SETTLING
SETTLING
SETTLING
CALIBRATE
RX
REGON
STARTCAL
BWBOOST
FS_LOCK
IFADCON
ENDCAL
RX
RX_END
RX_RST
RX
RX
Reserved
RXFIFO_OVERFLOW
Reserved
RXFIFO_OVERFLOW
18 (0x12)
-
22 (0x16)
Note: it is not possible to read back the SLEEP or XOFF state numbers
because setting CSn low will make the chip enter the IDLE mode from the
SLEEP or XOFF states.
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0x38 (0xF8): PKTSTATUS - Current GDOx Status and Packet Status
Bit Field Name
Reset
R/W
Description
7
CRC_OK
R
The last CRC comparison matched. Cleared when entering/restarting RX
mode.
6
5
4
3
CS
R
R
R
R
Carrier sense. Cleared when entering IDLE mode.
Reserved
Reserved
SFD
Start of Frame Delimiter. This bit is asserted when sync word has been
received and de-asserted at the end of the packet. It will also de-assert
when a packet is discarded due to address or maximum length filtering or
the radio enters RXFIFO_OVERFLOW state.
2
GDO2
R
Current GDO2 value. Note: the reading gives the non-inverted value
irrespective of what IOCFG2.GDO2_INVis programmed to.
It is not recommended to check for PLL lock by reading PKTSTATUS[2]
with GDO2_CFG=0x0A.
1
0
R0
R
Not used
GDO0
Current GDO0 value. Note: the reading gives the non-inverted value
irrespective of what IOCFG0.GDO0_INVis programmed to.
It is not recommended to check for PLL lock by reading PKTSTATUS[0]
with GDO0_CFG=0x0A.
0x3B (0xFB): RXBYTES - Overflow and Number of Bytes
Bit Field Name
Reset
R/W
R
Description
7
RXFIFO_OVERFLOW
6:0 NUM_RXBYTES
R
Number of bytes in RX FIFO
27 Development Kit Ordering Information
Orderable Evaluation Module
CC11xLDK-868-915
Description
Minimum Order Quantity
CC11xL Development Kit, 868/915 MHz
CC11xL Evaluation Module Kit, 433 MHz
1
1
CC11xLEMK-433
Figure 26: Development Kit Ordering Information
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28 References
[1]
Characterization Design 315 - 433 MHz
(Identical to the CC1101EM 315 - 433 MHz Reference Design (swrr046.zip))
Characterization Design 868 - 915 MHz
[2]
(Identical to the CC1101EM 868 - 915 MHz Reference Design (swrr045.zip))
CC113L Errata Notes (swrz038.pdf)
[3]
[4]
[5]
[6]
[7]
[8]
[9]
SmartRF Studio (swrc176.zip)
DN010 Close-in Reception with CC1101 (swra147.pdf)
DN015 Permanent Frequency Offset Compensation (swra159.pdf)
DN505 RSSI Interpretation and Timing (swra114.pdf)
DN022 CC11xx OOK/ASK register settings (swra215.pdf)
DN005 CC11xx Sensitivity versus Frequency Offset and Crystal Accuracy (swra122.pdf)
[10] CC113LEM 433 MHz Reference Design (swrr083.zip)
[11] CC113LEM 868 - 915 MHz Reference Design (swrr084.zip)
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CC113L
29 General Information
29.1 Document History
Revision
Date
Description/Changes
SWRS108
SWRS108A
05.24.2011
08.09.2011
Initial Release
Added three registers (CHANNR, MDMCFG1, and MDMCFG0). Changes made to
Section 20. Hyperlinks added to the CC113LEM 433 MHz Reference Design and the
CC113LEM 868 - 915 MHz Reference Design
Table 34: Document History
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PACKAGE OPTION ADDENDUM
www.ti.com
8-Sep-2011
PACKAGING INFORMATION
Status (1)
Eco Plan (2)
MSL Peak Temp (3)
Samples
Orderable Device
Package Type Package
Drawing
Pins
Package Qty
Lead/
Ball Finish
(Requires Login)
CC113LRTKR
CC113LRTKT
ACTIVE
ACTIVE
VQFN
VQFN
RTK
RTK
20
20
3000
250
Green (RoHS
& no Sb/Br)
CU NIPDAU Level-3-260C-168 HR
Green (RoHS
& no Sb/Br)
CU NIPDAU Level-3-260C-168 HR
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE MATERIALS INFORMATION
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
CC113LRTKR
CC113LRTKT
VQFN
VQFN
RTK
RTK
20
20
3000
250
330.0
330.0
12.4
12.4
4.3
4.3
4.3
4.3
1.5
1.5
8.0
8.0
12.0
12.0
Q2
Q2
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PACKAGE MATERIALS INFORMATION
www.ti.com
7-Sep-2011
*All dimensions are nominal
Device
Package Type Package Drawing Pins
SPQ
Length (mm) Width (mm) Height (mm)
CC113LRTKR
CC113LRTKT
VQFN
VQFN
RTK
RTK
20
20
3000
250
340.5
340.5
333.0
333.0
20.6
20.6
Pack Materials-Page 2
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技术和知识，并且认可和同意，尽管任何应用相关信息或支持仍可能由TI 提供，但他们将独力负责满足在关键安全应用中使用其产 品及TI
产品所需的所有法律、法规和安全相关要求。此外，购买者必须全额赔偿因在此类关键安全应用中使用TI 产品而对TI 及其 代表造成的损失。
TI 产品并非设计或专门用于军事/航空应用，以及环境方面的产品，除非TI 特别注明该产品属于“军用”或“增强型塑料”产品。只 有TI
指定的军用产品才满足军用规格。购买者认可并同意，对TI 未指定军用的产品进行军事方面的应用，风险由购买者单独承担，
并且独力负责在此类相关使用中满足所有法律和法规要求。
TI 产品并非设计或专门用于汽车应用以及环境方面的产品，除非TI 特别注明该产品符合ISO/TS 16949 要求。购买者认可并同意，
如果他们在汽车应用中使用任何未被指定的产品，TI 对未能满足应用所需要求不承担任何责任。
可访问以下URL 地址以获取有关其它TI 产品和应用解决方案的信息：
产品
www.ti.com.cn/audio
应用
www.ti.com.cn/telecom
数字音频
通信与电信
放大器和线性器件
http://www.ti.com.cn/amplifiers
计算机及周边
www.ti.com.cn/computer
http://www.ti.com.cn/dataconvert
ers
数据转换器
消费电子
www.ti.com/consumer-apps
DLP® 产品
www.dlp.com
能源
www.ti.com/energy
DSP - 数字信号处理器
http://www.ti.com.cn/dsp
工业应用
www.ti.com.cn/industrial
http://www.ti.com.cn/clockandtim
ers
时钟和计时器
医疗电子
www.ti.com.cn/medical
接口
http://www.ti.com.cn/interface
http://www.ti.com.cn/logic
http:///www.ti.com.cn/power
安防应用
汽车电子
视频和影像
www.ti.com.cn/security
www.ti.com.cn/automotive
www.ti.com.cn/video
逻辑
电源管理
http://www.ti.com.cn/microcontroll
ers
微控制器 (MCU)
无线通信
www.ti.com.cn/wireless
RFID 系统
http://www.ti.com.cn/rfidsys
www.ti.com.cn/radiofre
TI E2E 工程师社区
RF/IF 和 ZigBee® 解决方案
http://e2e.ti.com/cn/
IMPORTANT NOTICE
SHENZHEN RF-STAR TECHNOLOGY CO.,LTD
TEL:0755-86329829 FAX:0755-86329413
HTTP://WWW.SZRFSTAR.COM
相关型号：
CC1150RGVT
Highly integrated multichannel wireless transmitter designed for low-power wireless applications 16-VQFN -40 to 85
TI
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