INA310A5IDGKR [TI]
具有比较器的 -4V 至 110V、1.3MHz 超高精度电流检测放大器 | DGK | 8 | -40 to 125;
| 型号： | INA310A5IDGKR |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 具有比较器的 -4V 至 110V、1.3MHz 超高精度电流检测放大器 | DGK | 8 | -40 to 125 放大器 比较器 |
| 文件： | 总31页 (文件大小：2022K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
INA310A, INA310B
ZHCSNY8 –MARCH 2023
INA310x 具有开漏比较器和基准的-4V 至110V、1.3MHz 超精密电流检测放大器
1 特性
3 说明
• 宽共模电压：
INA310x 是一款超精密电流检测放大器，可不依赖于
具有集成式比较器的电源电压，在-4V 至110V 的宽共
模范围内测量分流电阻器上的压降。该器件在 20µV
（最大值）的低失调电压、0.15%（最大值）的小增益
误差和 160dB（典型值）的高直流 CMRR 等特性的综
合作用下，可实现高精度电流测量。INA310x 具有
1.3MHz 的高信号带宽，专为高压直流电流测量和快速
过流保护等高速应用而设计。
– 工作电压：-4 V 至+110 V
– 可承受电压：-20 V 至+120 V
• 高信号带宽：1.3 MHz
• 压摆率：2.5 V/µs
• 出色的共模抑制比(CMRR)：160 dB
• 精度
– 增益误差（最大值）
• 版本A：0.15%，10ppm/°C 漂移
• 版本B：0.5%，20ppm/°C 漂移
– 失调电压（最大值）
INA310x 包含一个开漏比较器和提供 0.6V 阈值的内部
基准。一个外部电阻分压器设定电流跳变点。比较器具
有锁存功能，可通过将 RESET 引脚接地（或悬空）进
入透明状态。
• 版本A：±20 µV，±0.25 µV/°C 漂移
• 版本B：±150 µV，±1 µV/°C 漂移
• 板载开漏比较器
• 内部比较器电压基准：0.6V
• 传播延迟时间：1 µs
• 比较器锁存功能
INA310x 由 2.7V 至 20V 的单电源供电，消耗 1.6mA
的电源电流。INA310x 有五个增益选项：20V/V、
50V/V、100V/V、200V/V 和 500V/V。这些增益选项
可以满足宽动态范围电流检测应用。
INA310x 的额定工作温度范围为-40°C 至+125°C，并
且采用节省空间的8 引脚VSSOP 封装。
• 可用增益：
– INA310A1、INA310B1：20 V/V
– INA310A2、INA310B2：50 V/V
– INA310A3、INA310B3：100 V/V
– INA310A4、INA310B4：200 V/V
– INA310A5、INA310B5：500V/V
• 封装选项：VSSOP-8
封装信息(1)
封装尺寸（标称值）
器件型号
INA310A
INA310B
封装
VSSOP (8)
3.00mm × 3.00mm
(1) 如需了解所有可用封装，请参阅数据表末尾的封装选项附录。
2 应用
2.7V to 20V
Supply
Battery
• 48V 直流/直流转换器
• 48V 电池管理系统(BMS)
• 测试和测量
• 宏远程无线电单元(RRU)
• 48V 机架式服务器
VS
INA310
IN+
+
OUT
IN-
-
CMPIN
Controller
ADC
+
ADC
CMPOUT
GPIO
• 48V 商用网络和服务器电源(PSU)
• 螺线管和传动器
-
0.6-V
Reference
RESET
GPIO
GND
典型应用
本文档旨在为方便起见，提供有关TI 产品中文版本的信息，以确认产品的概要。有关适用的官方英文版本的最新信息，请访问
www.ti.com，其内容始终优先。TI 不保证翻译的准确性和有效性。在实际设计之前，请务必参考最新版本的英文版本。
English Data Sheet: SBOSA86
INA310A, INA310B
ZHCSNY8 –MARCH 2023
www.ti.com.cn
Table of Contents
7.3 Feature Description...................................................14
7.4 Device Functional Modes..........................................17
8 Application and Implementation..................................21
8.1 Application Information............................................. 21
8.2 Typical Application.................................................... 22
8.3 Power Supply Recommendations.............................25
8.4 Layout....................................................................... 26
9 Device and Documentation Support............................27
9.1 Receiving Notification of Documentation Updates....27
9.2 支持资源....................................................................27
9.3 Trademarks...............................................................27
9.4 静电放电警告............................................................ 27
9.5 术语表....................................................................... 27
10 Mechanical, Packaging, and Orderable
1 特性................................................................................... 1
2 应用................................................................................... 1
3 说明................................................................................... 1
4 Revision History.............................................................. 2
5 Pin Configuration and Functions...................................3
6 Specifications.................................................................. 4
6.1 Absolute Maximum Ratings........................................ 4
6.2 ESD Ratings............................................................... 4
6.3 Recommended Operating Conditions.........................4
6.4 Thermal Information....................................................4
6.5 Electrical Characteristics.............................................5
6.6 Typical Characteristics................................................7
7 Detailed Description......................................................14
7.1 Overview...................................................................14
7.2 Functional Block Diagram.........................................14
Information.................................................................... 27
4 Revision History
DATE
REVISION
NOTES
March 2023
*
Initial release
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English Data Sheet: SBOSA86
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ZHCSNY8 –MARCH 2023
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5 Pin Configuration and Functions
VS
OUT
1
2
3
4
8
7
6
5
IN+
IN–
CMPIN
GND
CMPOUT
RESET
Not to scale
图5-1. INA310x: DGK Package 8-Pin VSSOP Top View
表5-1. Pin Functions
PIN
TYPE
DESCRIPTION
NAME
VS
NO
1
Power
Output
Input
Power supply, 2.7 V to 20 V
Output voltage
OUT
2
CMPIN
GND
3
Comparator input
Ground
4
Ground
Input
RESET
CMPOUT
5
Comparator reset pin, active low (Low: Transparent Mode, High: Latch Mode)
Comparator output (latch high when RESET = High)
6
Output
Shunt resistor negative sense input. For high-side applications, connect to load
side of sense resistor. For low-side applications, connect to ground side of sense
resistor.
7
8
Input
Input
IN–
Shunt resistor positive sense input. For high-side applications, connect to bus-
voltage side of sense resistor. For low-side applications, connect to load side of
sense resistor.
IN+
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English Data Sheet: SBOSA86
INA310A, INA310B
ZHCSNY8 –MARCH 2023
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6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1)
MIN
–0.3
MAX
UNIT
VS
Supply voltage
Analog inputs
22
V
(2)
12
Differential (VIN+) –(VIN–
)
–12
VIN+
VIN–
,
V
VIN+, VIN–, with respect to GND(2)
120
–20
VOUT
Analog output
(VS) + 0.3
V
V
GND –0.3
GND –0.3
GND –0.3
GND –0.3
Comparator reset pin
Comparator analog input
Comparator Output
Input current into any pin
Operating temperature
Junction temperature
Storage temperature
(VS) + 0.3
MIN of 5.5 or VS
V
22
5
V
mA
°C
°C
°C
TA
150
150
150
–55
–65
–65
TJ
Tstg
(1) Operation outside the Absolute Maximum Ratings may cause permanent device damage. Absolute Maximum Ratings do not imply
functional operation of the device at these or any other conditions beyond those listed under Recommended Operating Conditions. If
used outside the Recommended Operating Conditions but within the Absolute Maximum Ratings, the device may not be fully
functional, and this may affect device reliability, functionality, performance, and shorten the device lifetime.
(2) VIN+ and VIN– are the voltages at the IN+ and IN–pins, respectively.
6.2 ESD Ratings
VALUE
UNIT
Human body model (HBM), per ANSI/ESDA/ JEDEC JS-001, all pins(1)
±2000
V(ESD)
Electrostatic discharge
V
Charged device model (CDM), per ANSI/ESDA/JEDEC JS-002, all pins((2)) ±1000
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
–4
2.7
NOM
48
MAX
110
UNIT
V
VCM
VS
Common-mode input range
Operating supply voltage
5
20
V
VSENSE
TA
Differential sense input range
Operating free-air temperature
0
VS / G
125
V
°C
–40
6.4 Thermal Information
INA310x
DGK (VSSOP)
8 PINS
172.2
THERMAL METRIC(1)
UNIT
RθJA
RθJC(top)
RθJB
ΨJT
Junction-to-ambient thermal resistance
Junction-to-case (top) thermal resistance
Junction-to-board thermal resistance
°C/W
°C/W
°C/W
°C/W
°C/W
63.5
93.8
Junction-to-top characterization parameter
Junction-to-board characterization parameter
9.8
92.2
ΨJB
(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report.
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English Data Sheet: SBOSA86
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6.5 Electrical Characteristics
at TA = 25°C, VSENSE = VIN+ –VIN– = 0.5 V / Gain, VS = 5.0 V, VCM = VIN– = 48 V, and RPULLUP= 5.1 kΩconnected from
CMPout to Vs, (unless otherwise noted)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNIT
INPUT
Common-mode input
range
VCM
110
V
TA = –40°C to +125°C
–4
140
160
85
INA310Ax, VIN+ = –4 V to 110 V, TA = –40°C to +125°C
INA310Ax, f = 50 kHz
Common-mode
rejection ratio
CMRR
dB
120
140
65
INA310Bx, VIN+ = –4 V to 110 V, TA = –40°C to +125°C
INA310Bx, f = 50 kHz
INA310A1
±30
±100
±15
±55
±10
±30
±5
±150
±500
±80
INA310B1
INA310A2
INA310B2
±300
±50
INA310A3
VOS
Offset voltage, RTI(1)
µV
INA310B3
±250
±30
INA310A4
INA310B4
±30
±2
±200
±20
INA310A5
INA310B5
±15
±0.05
±0.025
±0.1
±1
±150
±0.5
TA = –40°C to +125°C, INA310A1, INA310A2, INA310A3
TA = –40°C to +125°C, INA310A4, INA310A5
TA = –40°C to +125°C, INA310Bx
INA310A1, 2.7 V ≤VS ≤20 V, TA = –40°C to +125°C
dVOS/dT
Offset drift, RTI
±0.25 µV/°C
±1
±8
INA310A2, INA310A3, 2.7 V ≤VS ≤20 V,
TA = –40°C to +125°C
±0.3
±0.1
±3
Power-supply rejection
ratio, RTI
PSRR
µV/V
±1
INA310A4, INA310A5, 2.7 V ≤VS ≤20 V,
TA = –40°C to +125°C
±1.5
20
±10
INA310Bx 2.7 V ≤VS ≤20 V, TA = –40°C to +125°C
IB
Input bias current
IB+, IB-, VSENSE = 0 mV
10
30
µA
OUTPUT
INA310A1, INA310B1
20
50
INA310A2, INA310B2
G
Gain
INA310A3, INA310B3
100
V/V
INA310A4, INA310B4
200
INA310A5, INA310B5
500
±0.02%
±0.07%
1
±0.15%
±0.5%
10
INA310Ax, GND + 50 mV ≤VOUT ≤VS –200 mV
INA310Bx, GND + 50 mV ≤VOUT ≤VS –200 mV
INA310Ax, TA = –40°C to +125°C
INA310Bx, TA = –40°C to +125°C
GND + 50 mV ≤VOUT ≤VS –200 mV
GERR
Gain error
ppm/°C
2
20
NLERR
Nonlinearity error
±0.01
%
Maximum capacitive
load
No sustained oscillation, no isolation resistor
500
pF
VOLTAGE OUTPUT
Swing to VS (Power-
supply rail)
VSP
VSN
mV
mV
RLOAD = 10 kΩ to GND, TA = –40°C to +125°C
(VS) –70
(VS) –150
RLOAD = 10 kΩ to GND, TA = –40°C to +125°C,
VSENSE = 0 mV
Swing to GND
(VGND) + 5 (VGND) + 20
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English Data Sheet: SBOSA86
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at TA = 25°C, VSENSE = VIN+ –VIN– = 0.5 V / Gain, VS = 5.0 V, VCM = VIN– = 48 V, and RPULLUP= 5.1 kΩconnected from
CMPout to Vs, (unless otherwise noted)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNIT
FREQUENCY RESPONSE
INA310A1, INA310B1, CLOAD = 5 pF, VSENSE = 200mV
INA310A2, INA310B2, CLOAD = 5 pF, VSENSE = 80mV
INA310A3, INA310B3, CLOAD = 5 pF, VSENSE = 40mV
INA310A4, INA310B4, CLOAD = 5 pF, VSENSE = 20mV
INA310A5, INA310B5, CLOAD = 5 pF, VSENSE = 8mV
Rising edge
1300
1300
1000
900
900
2.5
10
BW
Bandwidth
kHz
SR
tS
Slew rate
V/µs
µs
VOUT = 4 V ± 0.1 V step, Output settles to 0.5%
VOUT = 4 V ± 0.1 V step, Output settles to 1%
VOUT = 4 V ± 0.1 V step, Output settles to 5%
Settling time
5
µs
1
µs
NOISE
Ven
Voltage noise density
50
nV/√Hz
COMPARATOR
TA = 25°C
585
580
600
615
620
mV
mV
mV
Alert threshold
VTHRESHOLD
TA = –40°C to +125°C
TA = 25°C
Hysteresis
8
1
Small-signal
propagation delay
Comparator input overdrive = 20 mV
µs
µs
tP
Slew-rate-limited
propagation delay
VOUT step = 0.5 V to 4.5 V, VLIMIT ((3)) = 4 V
1.6
1
TA = 25°C, VCMPIN = 0.4 V to 1.2 V
-20
20
nA
nA
Input bias current,
CMPin PIN
IBCMPIN
250
TA = –40°C to +125°C, VCMPIN = 0.4 V to 1.2 V
High-level leakage
current
ILKG
VCMPout = VS
1
µA
IOL = 2.35 mA
300
350
mV
mV
Low-level output
voltage
VOL
TA = –40°C to +125°C, IOL = 2.35 mA
RESET High-level
1.2
VIH
input voltage threshold
V
V
TA = –40°C to +125°C
(2)
RESET Low-level
VIL
input voltage threshold
0.4
TA = –40°C to +125°C
TA = –40°C to +125°C
(2)
Minimum RESET
pulse width
100
250
200
ns
ns
RESET propagation
delay
POWER SUPPLY
VS
Supply voltage range
2.7
20
2
V
TA = –40°C to +125°C
TA = –40°C to +125°C
1.6
mA
mA
IQ
Quiescent current
2.25
(1) RTI = referred-to-input.
(2) The RESET input has an internal 2 MΩ (typical) pull-down. Leaving RESET open results in a LOW state, with transparent comparator
operation.
(3) VLIMIT is VOUT at the overcurrent threshold set by external resistors.
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English Data Sheet: SBOSA86
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6.6 Typical Characteristics
at TA = 25°C, VS = 5 V, VSENSE = VIN+ – VIN– = 0.5 V / Gain, VCM = VIN– = 48 V, and RPULLUP= 5.1 kΩ(unless
otherwise noted).
Input Offset Voltage (mV)
Input Offset Voltage (mV)
图6-2. INA310A2 Input Offset Production
图6-1. INA310A1 Input Offset Production
Distribution
Distribution
Input Offset Voltage (mV)
Input Offset Voltage (mV)
图6-3. INA310A3 Input Offset Production
图6-4. INA310A4 Input Offset Production
Distribution
Distribution
16
8
0
G = 20
G = 50
-8
G = 100
G = 200
G = 500
-16
-75 -50 -25
0
25
50
75 100 125 150 175
Temperature (èC)
Input Offset Voltage (mV)
图6-6. Input Offset Voltage vs Temperature
图6-5. INA310A5 Input Offset Production
Distribution
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20
10
0
180
160
140
120
100
80
G = 20
G = 50
60
-10
G = 100
G = 200
G = 500
40
20
-20
10
100
1k 10k
Frequency (Hz)
100k
1M
-75 -50 -25
0
25
50
75 100 125 150 175
Temperature (èC)
图6-8. Common-Mode Rejection Ratio vs
图6-7. Common-Mode Rejection Ratio vs
Frequency
Temperature
60
50
40
30
20
0.10
0.05
G = 20
G = 50
G = 100
G = 200
G = 500
0.00
G = 20
G = 50
G = 100
G = 200
G = 500
10
0
-0.05
-10
-0.10
10
100
1k
10k
Frequency (Hz)
100k
1M
10M
-75 -50 -25
0
25
50
75 100 125 150 175
Temperature (èC)
图6-9. Gain vs Frequency
图6-10. INA310A Gain Error vs Temperature
1.0
0.8
140
120
100
80
0.6
0.4
0.2
0.0
-0.2
-0.4
-0.6
-0.8
-1.0
60
G = 20
G = 50
G = 100
G = 200
G = 500
40
20
10
100
1k 10k
Frequency (Hz)
100k
1M
-75 -50 -25
0
25
50
75 100 125 150 175
Temperature (èC)
图6-12. Power-Supply Rejection Ratio vs
图6-11. Power-Supply Rejection Ratio vs
Frequency
Temperature
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25
20
15
10
5
25
20
15
10
5
VS = 2.7 to 20V, VCM = 48V
VS = 2.7 to 20V, VCM = 120V
VS = 2.7 to 20V, VCM = -4V
VS = 0V, VCM = 120V
VS = 5V
VS = 20V
VS = 2.7V
VS = 0V
VS = 0V, VCM = -4V
0
0
VS = 0V and 20V, VCM = -20V
-5
-5
-10
-20
-10
0
20
40
Common-Mode Voltage (V)
60
80
100
120
-75 -50 -25
0
25
50
75 100 125 150 175
Temperature (èC)
VSENSE = 0 V
.
图6-13. Input Bias Current vs Common-Mode
图6-14. Input Bias Current vs Temperature
Voltage
240
140
IB+
IB-
IB+
120
IB-
200
IB+, VS = 0V
160
IB-, VS = 0V
120
IB+, VS = 0V
IB-, VS = 0V
100
80
60
80
40
40
20
0
0
-40
-80
-120
-160
-20
-40
-60
-80
0
200
400
VSENSE (mV)
600
800
1000
0
100
200
VSENSE (mV)
300
400
图6-15. INA310x1 Input Bias Current vs VSENSE
图6-16. INA310x2, INA310x3 Input Bias Current vs
VSENSE
100
VS
IB+, G=200
IB+, G=500
IB-
25èC
125èC
-40èC
80
VS - 1
IB+, VS = 0V
IB-, VS = 0V
60
VS - 2
40
20
0
GND + 2
GND + 1
GND
-20
0
20
40
60
80
100
0
5
10
15
20
25
Output Current (mA)
30
35
40
VSENSE (mV)
.
VS = 2.7 V
图6-17. INA310x4, INA310x5 Input Bias Current vs
图6-18. Output Voltage vs Output Current
VSENSE
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VS
VS - 1
VS - 2
VS - 3
VS
VS - 1
VS - 2
VS - 3
25èC
125èC
-40èC
25èC
125èC
-40èC
GND + 3
GND + 2
GND + 1
GND
GND + 3
GND + 2
GND + 1
GND
0
5
10
15
Output Current (mA)
20
25
30
35
40
0
5
10
15
Output Current (mA)
20
25
30
35
40
VS = 5 V
VS = 20 V
图6-19. Output Voltage vs Output Current
图6-20. Output Voltage vs Output Current
1000
500
0.00
200
100
50
-0.10
-0.20
-0.30
20
10
5
2
1
0.5
0.2
0.1
0.05
-0.40
VS = 5V
VS = 20V
VS = 2.7V
0.02
0.01
-0.50
10
100
1k
10k
Frequency (Hz)
100k
1M
10M
-75 -50 -25
0
25
50
75 100 125 150 175
Temperature (èC)
图6-21. Output Impedance vs Frequency
图6-22. Swing to Supply vs Temperature
0.020
100
VS = 5V
VS = 20V
VS = 2.7V
G = 20
G = 500
80
70
60
50
0.015
0.010
0.005
0.000
40
30
20
10
10
100
1k 10k
Frequency (Hz)
100k
1M
-75 -50 -25
0
25
50
75 100 125 150 175
Temperature (èC)
图6-24. Input Referred Noise vs Frequency
图6-23. Swing to GND vs Temperature
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50
40
30
20
10
0
VS = 5V, Sourcing
VS = 5V, Sinking
VS = 20V, Sourcing
VS = 20V, Sinking
VS = 2.7V, Sourcing
VS = 2.7V, Sinking
-75 -50 -25
0
25
50
75 100 125 150 175
Time (1 s/div)
Temperature (èC)
图6-25. Input Referred Noise
图6-26. Short-Circuit Current vs Temperature
2.2
2
2
VS = 5V
VS = 20V
VS = 2.7V
1.8
1.6
1.4
1.2
1.8
1.6
1.4
1.2
1
25ꢀC
1
125ꢀC
-40ꢀC
0.8
-75 -50 -25
0
25
50
75 100 125 150 175
0
2
4
6
8
10
12
14
16
18
20
Temperature (ꢀC)
Supply Voltage (V)
图6-27. Quiescent Current vs Temperature
图6-28. Quiescent Current vs Supply Voltage
2
VCM
VOUT
VS = 5V
VS = 20V
1.8
1.6
1.4
1.2
1
VS = 2.7V
0V
0V
0.8
-20
Time (12.5ms/div)
0
20
40
60
80
100
120
Common-Mode Voltage (V)
.
图6-29. Quiescent Current vs Common-Mode
图6-30. Common-Mode Voltage Fast Transient
Voltage
Pulse
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Supply Voltage
Output Voltage
0V
0V
0V
Time (10 ms/div)
Time (5 ms/div)
图6-31. INA310x3 Step Response
图6-32. Start-Up Response
600
500
400
300
200
100
0
Supply Voltage
Output Voltage
0V
Time (50 ms/div)
0
1
2
3
4
5
6
Isink(mA)
.
图6-34. Comparator VOL vs ISINK
图6-33. Supply Transient Response
615
620
615
610
605
600
595
590
585
580
610
605
600
595
590
585
2
4
6
8
10
12
14
16
18
20
-75 -50 -25
0
25
50
75 100 125 150 175
Supply Voltage (V)
Temperature (ꢀC)
图6-35. Comparator Trip Point vs Supply Voltage
图6-36. Comparator Trip Point vs Temperature
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300
275
250
225
200
175
150
125
100
75
1.2
1.1
1
VIH
VIL
0.9
0.8
0.7
0.6
0.5
0.4
50
0
10
20
30
40
50
60
70
80
90 100
2
4
6
8
10
12
14
16
18
20
Overdrive Voltage (mV)
Supply Voltage (V)
图6-37. Comparator Propagation Delay vs
图6-38. Comparator Reset Voltage vs Supply
Overdrive Voltage
Voltage
130
115
100
85
VOD = 20 mV
Input
200 mV/div
Output
2 V/div
70
55
40
-75 -50 -25
0
25
50
75 100 125 150 175
2 ꢀs/div
Temperature (ꢀC)
图6-40. Comparator Propagation Delay
图6-39. Comparator Propagation Delay vs
Temperature
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7 Detailed Description
7.1 Overview
The INA310x is a high or low-side high-speed current-sense amplifier that offers a wide common-mode range,
precision zero-drift topology, excellent common-mode rejection ratio (CMRR) and fast slew rate. Different gain
versions are available to optimize the output dynamic range based on the application. The INA310x is designed
using an architecture that enables low input bias current of 20 µA with a specified common-mode voltage range
from −4 V to 110 V with signal bandwidths up to 1.3 MHz. The INA310x incorporates an open-drain comparator
and internal reference providing a 0.6-V threshold. An external resistor divider sets the current trip point. The
comparator includes a latching capability, that can be made transparent by grounding (or leaving open) the
RESET pin (see the RESET Function section).
7.2 Functional Block Diagram
INA310
VS
IN+
OUT
Gain
IN-
0.6-V
Reference
CMPIN
CMPOUT
Comparator
GND
RESET
7.3 Feature Description
7.3.1 Amplifier Input Common-Mode Signal
The INA310x supports large input common-mode voltages from –4 V to +110 V. The internal topology of the
INA310x enables the common-mode range to not be restricted by the power-supply voltage (VS). Due to this
feature, the INA310x can be used for both low-side and high-side current-sensing applications that extend
beyond the supply range of 2.7 V to 20 V.
7.3.2 Input-Signal Bandwidth
The INA310x is available with several gain options, including 20 V/V, 50 V/V, 100 V/V, 200 V/V, and 500 V/V. The
unique multistage design enables the amplifier to achieve high bandwidth at all gains. This high bandwidth
provides the throughput and fast response that is required for the rapid detection and processing of overcurrent
events.
7.3.3 Low Input Bias Current
The INA310x inputs draw a 20-µA input bias current per pin at a common-mode voltage as high as 110 V, which
enables precision current sensing on applications that require lower current leakage. Unlike many high voltage
current sense amplifiers whose input bias currents are proportional to the common-mode voltage, the input bias
current of the INA310x remains flat over the entire common-mode voltage range.
7.3.4 Low VSENSE Operation
The INA310x features high performance operation across the entire valid VSENSE range. The zero-drift input
architecture of the INA310x provides the low offset voltage and low offset drift needed to measure low VSENSE
levels accurately across the wide operating temperature of –40°C to +125°C. Low VSENSE operation is
particularly beneficial when using low ohmic shunts for high current measurements, as power losses across the
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shunt are significantly reduced. VSENSE low level is only limited by the output swing to GND (VSN). The minimum
VSENSE is limited to VSN divided by Gain.
7.3.5 Wide Fixed Gain Output
The INA310x maximum gain error is 0.15% at room temperature, with a maximum drift of 10 ppm/°C over the full
temperature range of –40°C to +125°C. The INA310x is available in multiple gain options of 20 V/V, 50 V/V, 100
V/V, 200 V/V, and 500 V/V, which the system designer should select based on their desired signal-to-noise ratio
and other system requirements, such as the dynamic current range and full-scale output voltage target.
The INA310x closed-loop gain is set by a precision, low-drift internal resistor network. The ratio of these resistors
are excellently matched, while the absolute values may vary significantly. TI does not recommend adding
additional resistance around the INA310x to change the effective grain because of this variation.
7.3.6 Wide Supply Range
The INA310x operates with a wide supply range from 2.7 V to 20 V. While the input voltage range of the
INA310x is independent of the supply voltage, the output voltage is bound by the supply voltage applied to the
device. The output voltage can range from as low as 20 mV to as high as 200 mV below the supply voltage.
7.3.7 Integrated Comparator
The INA310x incorporates an open-drain comparator with an internal reference providing a 0.6-V threshold. The
comparator input (CMPIN) can take voltage from 0 V up to 5.5 V or equal to power-supply voltage (if it is lower
than 5.5 V). The comparator has a built-in hysteresis of 8 mV (typical). 图 7-1 shows the hysteresis, which is the
difference between the rising-edge threshold and the falling-edge threshold. The hysteresis makes stable
switching at the comparator output by providing noise immunity at comparator input.
VTHRESHOLD
0.592 V
0.6 V
Comparator Input Voltage
Hysteresis = 8 mV
图7-1. The Comparator Threshold and Hysteresis
The open-drain output of the comparator can be tied to voltage range of 0 to 20 V (independent of power supply)
through a pullup resistor. When the voltage at the comparator input (CMPIN) exceeds 0.6 V, the output of the
comparator goes high. When the voltage at the comparator input falls below falling-threshold (0.6 V –
Hysteresis), the output of the comparator is pulled low by an internal open-drain transistor.
7.3.8 RESET Function
The RESET function allows the comparator to work in transparent mode or latching mode. 图 7-2 shows the two
modes of the RESET function. When the RESET pin is left open or connected to GND the comparator functions
in a transparent mode. In transparent mode comparator output (CMPOUT ) responds as a normal comparator.
When the RESET pin is connected to the supply voltage, the pin operates in latching mode. In the latching mode
when the comparator is triggered by the comparator input going higher than 0.6 V, the output of the comparator
stays high irrespective of comparator input after. To release the comparator from the latching mode, the RESET
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pin must be pulled to GND or released to open. The RESET pin can take a voltage range from 0 V to the power-
supply voltage.
0.6 V
CMPin
0 V
CMPout
RESET
图7-2. The Comparator RESET Function
7.3.9 Short Propagation Delay
The combination of a high-speed current sense amplifier and a fast comparator provides a short total
propagation delay of 1 µs. The sense voltage (across the shunt resistor) propagates through the output where
the output is divided down with the resistor divider to the comparator input and then to the comparator output. An
external resistor divider at VOUT sets overcurrent threshold. The total propagation delay is time taken from when
the sense voltage (across the shunt resistor) exceeds the overcurrent threshold to when the comparator output
drives high. The short propagation delay makes the INA310x well suited for overcurrent protection in systems
sensitive to overcurrent events.
7.3.10 Comparator Input Bias Current
The INA310x comparator input has a built-in circuit to protect the input devices in case of large input differential
voltage. This circuit results in the input bias current (IBCMPIN) curve against input voltage (VCMPIN) as shown in 图
7-3. The IBCMPIN reduces with VCMPIN from 0 V to 0.4 V, IBCMPIN is under 20 nA at 25°C for VCMPIN range from 0.4
V to 1.2 V, and IBCMPIN increases with VCMPIN from 1.8 V to 5.5 V. The nature of IBCMPIN does not contribute to
the inaccuracy of the comparator alert threshold voltage (VTHRESHOLD) significantly because the IBCMPIN goes
below 20 nA when the input voltage is close to the threshold voltage (0.6 V). Avoid using a high-value resistor for
the divider network for better VTHRESHOLD accuracy. The sum of the two resistors in the divider network as shown
in Overcurrent Threshold Connection is recommended to keep lower than 100 kΩ.
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70
60
50
40
30
20
10
0
-10
0
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
5.5
VCMPIN (V)
图7-3. Comparator IBCMPIN vs VCMPIN
7.4 Device Functional Modes
7.4.1 Basic Connections
图7-4 shows a basic circuit connection for INA310x. The INA310x is configurable to allow for unidirectional high-
side or low-side, current-sensing operation. The input pins (IN+ and IN–) must be connected as closely as
possible with Kelvin connections to the shunt resistor to minimize any resistance in series with the shunt
resistance. The Layout section provides the layout guidelines and a layout example.
Power-supply bypass capacitors are required for stability. Applications with noisy or high-impedance power
supplies may require additional decoupling capacitors to reject power-supply noise. Connect bypass capacitors
close to the device VS pin. The recommended value of a bypass capacitor is 0.01 μF
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RSHUNT
Load Supply
-4 V to 110 V
Load
5-V Supply
INA310x
1
2
VS
RPULL-UP
5.1 k
VIN+
VIN-
8
7
OUT
G
R1
0.6-V
Reference
CBYPASS 0.01 µF
3
CMPIN
GND
CMPOUT
RESET
6
5
Comparator
R2
4
Latch
Transparent / Reset
图7-4. INA310 Basic Connections
7.4.1.1 Overcurrent Threshold Connection
The INA310x comparator in 图 7-4 is configured to provide overcurrent alert signal when the current through
RSHUNT exceeds the overcurrent threshold. OUT voltage times R2 divided by R1 and R2 compared to the internal
reference voltage (0.6 V) sets the overcurrent threshold. 方程式1 shows the relation of the overcurrent threshold
with gain, RSHUNT, R1 and R2.
0.6 × R + R
1
2
I
=
(1)
Sense_Alert_Tℎresℎold
R
× G × R
2
sℎunt
R1 and R2 load OUT, therefore TI recommends to set the sum of these resistors higher than 10k. This helps
keep the high swing range at the OUT and lower total supply current. The high value of these resistors will
contribute to inaccuracy in comparator alert threshold voltage (VTHRESHOLD) as mentioned in Comparator Input
Bias Current. The Design Requirements section shows an example of resistors values to set the overcurrent
threshold.
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7.4.2 High-Side Switch Overcurrent Shutdown
The INA310x measures differential voltage developed by current flowing through a current-shunt resistor. 图 7-5
shows the circuit with INA310x used for turning off the high-side switch in case of overcurrent. When the current
exceeds overcurrent threshold, the comparator output (CMPOUT) signal goes high. This signal from the
comparator drives through the Q1 transistor to the gate of the high-side switch, causing the switch to shut down.
The Q1 transistor helps isolate CMPOUT from the high voltage of the Supply. There are three location options to
have shunt resistor to measure unidirectional current. Option 1 and Option 2 are high-side current sensing, and
Option 3 is low-side current sensing. Though both are high-side current sensing, Option 1 accounts for the
current flowing through the Q1 transistor, and Option 2 does not. The advantages of high-side current sensing
are that high-side sensing options do not contribute to ground disturbances and that high-side sensing can
detect load shorts. In high-side current sensing, input common-mode is close to the power supply so a current-
sensing amplifier with high CMRR and high common-mode is required for high-accuracy measurement. The low-
side current sensing does not require a high-voltage, current-sensing amplifier as common mode remains very
close to the ground. The disadvantages of low-side current sensing are that low-side sensing options contribute
to ground disturbances and that low-side current sensing cannot detect load shorts.
Shunt
Shunt
Option 1
Option 2
Supply
R3
To VIN+
To VIN-
To VIN+
To VIN-
R4
Load
5 V
Q1 2N3904
INA310x
1
2
VS
To VIN+
To VIN-
Shunt
Option 3
VIN+
VIN-
8
From
Shunt Option
1, 2, or 3
OUT
G
7
0.6-V
Reference
R1
3
CMPIN
GND
CMPOUT
RESET
6
5
Comparator
R2
4
RESET
图7-5. High-Side Switch for Overcurrent Shutdown
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7.4.3 Bidirectional Overcurrent Comparator
The INA310x can operate only in unidirectional mode, but 图 7-6 shows that two INA310xs can be configured to
provide a bidirectional overcurrent alert signal. The polarity of the differential voltage measured across the shunt
resistor is in reverse for one current sense amplifier. Two INA310x function to cover the opposite current
directions, and therefore provide bidirectional overcurrent monitor function.
RSHUNT
Supply
5.0 V
INA310x
1
VS
VIN+
VIN-
8
7
R5 5.1 k
OUT
2
3
G
0.6-V
Reference
R3
CMPIN
GND
CMPOUT
RESET
6
5
Comparator
R4
4
1
2
INA310x
R6 5.1 k
VS
VIN+
VIN-
8
7
OUT
G
0.6-V
Reference
R3
3
CMPIN
GND
CMPOUT
RESET
6
5
Comparator
CMPOUT
R7 200 k
R4
4
图7-6. Ground Referenced Output
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8 Application and Implementation
备注
以下应用部分中的信息不属于TI 器件规格的范围，TI 不担保其准确性和完整性。TI 的客 户应负责确定
器件是否适用于其应用。客户应验证并测试其设计，以确保系统功能。
8.1 Application Information
The INA310x amplifies the voltage developed across a current-sensing resistor as current flows through the
resistor to the load. The wide input common-mode voltage range and high common-mode rejection of the
INA310x make the device usable over a wide range of voltage rails while still maintaining accurate current
measurement.
8.1.1 RSENSE and Device Gain Selection
To maximize the accuracy of a current sense amplifier, TI recommends to choose the largest current sense
resistor value possible in an application. A larger value sense resistor maximizes the differential input signal for a
given amount of current flow and reduces the error contribution of the offset voltage. However, there are practical
limits as to how large the current-sense resistor value can be in a given application because of the physical
dimensions of the resistor, package construction and maximum power dissipation. 方程式 2 gives the maximum
value for the current-sense resistor for a given power dissipation budget:
PDMAX
RSENSE
<
2
IMAX
(2)
where:
• PDMAX is the maximum allowable power dissipation in RSENSE
• IMAX is the maximum current that will flow through RSENSE
.
.
An additional limitation on the size of the current sense resistor and device gain is due to the power-supply
voltage, VS, and device swing-to-rail limitations. To make sure that the current-sense signal is properly passed to
the output, both positive and negative output swing limitations must be examined. 方程式 3 provides the
maximum values of RSENSE and GAIN to keep the device from exceeding the positive swing limitation.
IMAX ª RSENSE ª GAIN < VSP
(3)
where:
• IMAX is the maximum current that will flow through RSENSE
• GAIN is the gain of the current-sense amplifier.
.
• VSP is the positive output swing as specified in the data sheet.
To avoid positive output swing limitations when selecting the value of RSENSE, there is always a trade-off
between the value of the sense resistor and the gain of the device under consideration. If the sense resistor
selected for the maximum power dissipation is too large, then it is possible to select a lower-gain device to avoid
positive swing limitations.
The negative swing limitation places a limit on how small the sense resistor value can be for a given application.
方程式4 provides the limit on the minimum value of the sense resistor.
IMIN ª RSENSE ª GAIN > VSN
(4)
where:
• IMIN is the minimum current that will flow through RSENSE
.
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• GAIN is the gain of the current-sense amplifier.
• VSN is the negative output swing of the device.
表 8-1 shows an example of the different results obtained from using five different gain versions of the INA310x.
From the table data, the highest gain device allows a smaller current-shunt resistor and decreased power
dissipation in the element.
表8-1. RSENSE Selection and Power Dissipation(1)
RESULTS AT VS = 5 V
PARAMETER
EQUATION
A1, B1
A2, B2
A3, B3
A4, B4
A5, B5
DEVICES
DEVICES
DEVICES
DEVICES
DEVICES
G
Gain
20 V/V
250 mV
25 mΩ
2.5 W
50 V/V
100 mV
10 mΩ
1 W
100 V/V
50 mV
5 mΩ
0.5 W
200 V/V
25 mV
500 V/V
10mV
1 mΩ
0.1 W
VDIFF
RSENSE
PSENSE
Ideal differential input voltage
VDIFF = VOUT / G
Current sense resistor value
RSENSE = VDIFF / IMAX
2.5 mΩ
0.25 W
Current-sense resistor power dissipation
RSENSE × IMAX2
(1) Design example with 10-A full-scale current with maximum output voltage set to 5 V.
8.2 Typical Application
The INA310x is a unidirectional, current-sense amplifier capable of measuring currents through a resistive shunt
with shunt common-mode voltages from –4 V to +110 V.
8.2.1 Current Sensing in a Solenoid Application
24 V
Solenoid
RSENSE
ISENSE
MCU
ADC
GND
5 V
INA310
VS
IN+
IN-
OUT
G
VS
0.6-V
Reference
R1
R2
RPull-up
CMPIN
CMPOUT
RESET
Comparator
GND
图8-1. Current Sensing in a Solenoid Application
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8.2.1.1 Design Requirements
In this example application, the common-mode voltage ranges from 0 V to 24 V. The maximum sense current is
1.5 A, an alert must be indicated if the current exceeds 1.9 A, and a 5 V supply is available for the INA310x.
Following the design guidelines from RSENSE and Device Gain Selection, a RSENSE of 50 mΩ and a gain of 50
V/V are selected to provide good output dynamic range. 表8-2 lists the design setup for this application.
表8-2. Design Parameters
DESIGN PARAMETERS
Power supply voltage
Common mode voltage range
Maximum sense current
RSENSE resistor
EXAMPLE VALUE
5 V
0 V to 24 V
1.5 A
50 mΩ
Gain option
50 V/V
Over-current Threshold
R1
1.9 A
69.15 kΩ
10 kΩ
R2
8.2.1.2 Detailed Design Procedure
The INA310x is designed to measure current in a typical solenoid application. The INA310x measures current
across the 50-mΩ shunt that is placed at the output of the half-bridge. The INA310x measures the differential
voltage across the shunt resistor, and the signal is internally amplified with a gain of 50 V/V. The output of the
INA310x is connected to the analog-to-digital converter (ADC) of an MCU to digitize the current measurements.
R2 is fixed as 10 kΩ to avoid loading of OUT as recommended in Overcurrent Threshold Connection. R1 is
calculated as 69.15 kΩusing 方程式1.
0.6 V × R + 10 kΩ
1
1.9 A =
10 kΩ × 50 × 50 mΩ
R1 (69.15 kΩ) and R2 (10 kΩ) divides down the output which is an input to the comparator. This sets the
overcurrent alert threshold of 1.9 A.
Solenoid loads are highly inductive and are often prone to failure. Solenoids are often used for position control,
precise fluid control, and fluid regulation. Measuring real-time current on the solenoid continuously can indicate
premature failure of the solenoid, which can lead to a faulty control loop in the system. Measuring high-side
current also indicates if there are any ground faults on the solenoid or the FETs that can be damaged in an
application. The INA310x, with high bandwidth and slew rate, can be used to detect fast overcurrent conditions
to prevent the solenoid damage from short-to-ground faults.
8.2.1.2.1 Overload Recovery With Negative VSENSE
The INA310x is a unidirectional current sense amplifier that is meant to operate with a positive differential input
voltage (VSENSE). If negative VSENSE is applied, the device is placed in an overload or saturated condition and
requires time to recover after VSENSE returns positive. The required overload recovery time increases with more
negative VSENSE
.
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8.2.1.3 Application Curve
图8-2 shows the output response of a solenoid.
6
4
2
0
VCM
VOUT
40
30
20
10
0
Time (50 ms/div)
图8-2. Solenoid Control Current Response
8.2.2 Low-Side Switch Overcurrent Shutdown
RSHUNT
Supply
To VIN+
To VIN-
Load
5.0 V
To VIN+
To VIN-
Shunt
Option 2
INA310x
R4 2.2 k
1
2
VS
VIN+
VIN-
8
From
Shunt Option
1, 2, or 3
OUT
R3 22 k
G
7
0.6-V
Reference
To VIN+
To VIN-
R1
Shunt
Option 3
3
CMPIN
GND
CMPOUT
RESET
6
5
Comparator
Q1 2N3904
R2
4
图8-3. Low-Side Switch Overcurrent Shutdown
8.2.2.1 Design Requirements
The INA310x measures current through a resistive shunt with current flowing in one direction that enables
detection of an overcurrent event only when the differential input voltage exceeds the threshold limit. When the
current reaches the set limit of the divider of R1 and R2, the output of comparator (CMPOUT) transitions high,
which turns on Q1, pulls the gate of the pass-FET low, and turns off the flow of the current. In this example
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application, the common-mode voltage is set at 5 V. The maximum sense current is 1 A, an alert must be
indicated if the current exceeds 1.2 A, and a 5 V supply is available for the INA310x. Following the design
guidelines from RSENSE and Device Gain Selection, a RSHUNT of 100 mΩ and a gain of 20 V/V are selected to
provide a good output dynamic range. 表8-3 lists the design setup for this application.
表8-3. Design Parameters
DESIGN PARAMETERS
Power supply voltage
Common mode voltage range
Maximum sense current
RSENSE resistor
EXAMPLE VALUE
5 V
5 V
1 A
100 mΩ
20 V/V
1.2 A
Gain option
Over-current Threshold
R1
10.2 kΩ
3.4 kΩ
R2
8.2.2.2 Detailed Design Procedure
图 8-3 shows the basic connections to the INA310x. The inputs terminals (IN+ and IN–) must be connected to
the current sense resistor as close as possible to minimize any resistance in series with the shunt resistor. The
INA310x measures current across the 100-mΩ shunt that is placed in series with load. The INA310x measures
the differential voltage across the shunt resistor, and the signal is internally amplified with a gain of 20 V/V.
R1 is fixed as 10.2 kΩ to avoid loading of OUT as recommended in Overcurrent Threshold Connection. R2 is
calculated as 3.4 kΩusing 方程式 1. R1 (10.2 kΩ) and R2 (3.4 kΩ) divides down the output which is an input to
the comparator. This sets the overcurrent alert threshold of 1.2 A.
8.2.2.3 Application Curve
图8-4 shows the output response the current sense amplifier and the comparator in event of overcurrent.
6
5.4
4.8
4.2
3.6
3
1
Comparator Input Voltage
VOUT
Comparator Output
0.8
0.6
0.4
0.2
0
2.4
1.8
1.2
0.6
0
-0.2
-0.4
-0.6
-0.8
-1
-0.6
-1.2
-8E-5
-7E-5
-6E-5
-5E-5
-4E-5
-3E-5
-2E-5
-1E-5
0
1E-5
2E-5
Time (s)
图8-4. Low-Side Switch Overcurrent Shutdown Response
8.3 Power Supply Recommendations
The INA310x makes accurate measurements beyond the connected power-supply voltage (VS) because the
inputs (IN+ and IN–) can operate anywhere between –4 V and 110 V independent of VS. For example, with the
VS power supply equal to 5 V, the common-mode voltage of the measured shunt can be as high as 110 V.
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8.3.1 Power Supply Decoupling
Place the power-supply bypass capacitor as close to the power-supply and ground pins as possible. TI
recommends a bypass capacitor value of 0.1 μF. Additional decoupling capacitance can be added to
compensate for noisy or high-impedance power supplies.
8.4 Layout
8.4.1 Layout Guidelines
Attention to good layout practices is always recommended.
• Connect the input pins to the sensing resistor using a Kelvin or 4-wire connection. This connection technique
makes sure that only the current-sensing resistor impedance is detected between the input pins. Poor routing
of the current-sensing resistor commonly results in additional resistance present between the input pins.
Given the very low ohmic value of the current resistor, any additional high-current carrying impedance can
cause significant measurement errors.
• Place the power-supply bypass capacitor as close to the device power-supply and ground pins as possible.
The recommended value of this bypass capacitor is 0.1 µF. Additional decoupling capacitance can be added
to compensate for noisy or high-impedance power supplies.
8.4.2 Layout Example
Via to Power or Ground Plane
Via to Internal Layer
Supply Voltage
VS
IN+
IN-
RSHUNT
OUT
CMPIN
GND
R1
R2
CBYPASS
CMPOUT
RESET
RPULL-UP
RESET
Output Signal
图8-5. INA310xx Recommended Layout
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9 Device and Documentation Support
9.1 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. In the upper
right corner, click on Alert me to register and receive a weekly digest of any product information that has
changed. For change details, review the revision history included in any revised document.
9.2 支持资源
TI E2E™ 支持论坛是工程师的重要参考资料，可直接从专家获得快速、经过验证的解答和设计帮助。搜索现有解
答或提出自己的问题可获得所需的快速设计帮助。
链接的内容由各个贡献者“按原样”提供。这些内容并不构成 TI 技术规范，并且不一定反映 TI 的观点；请参阅
TI 的《使用条款》。
9.3 Trademarks
TI E2E™ is a trademark of Texas Instruments.
所有商标均为其各自所有者的财产。
9.4 静电放电警告
静电放电(ESD) 会损坏这个集成电路。德州仪器(TI) 建议通过适当的预防措施处理所有集成电路。如果不遵守正确的处理
和安装程序，可能会损坏集成电路。
ESD 的损坏小至导致微小的性能降级，大至整个器件故障。精密的集成电路可能更容易受到损坏，这是因为非常细微的参
数更改都可能会导致器件与其发布的规格不相符。
9.5 术语表
TI 术语表
本术语表列出并解释了术语、首字母缩略词和定义。
10 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
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PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
INA310A1IDGKR
INA310A2IDGKR
INA310A3IDGKR
INA310A4IDGKR
INA310A5IDGKR
INA310B1IDGKR
INA310B2IDGKR
INA310B3IDGKR
INA310B4IDGKR
INA310B5IDGKR
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
VSSOP
VSSOP
VSSOP
VSSOP
VSSOP
VSSOP
VSSOP
VSSOP
VSSOP
VSSOP
DGK
DGK
DGK
DGK
DGK
DGK
DGK
DGK
DGK
DGK
8
8
8
8
8
8
8
8
8
8
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
2500 RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
-40 to 125
2OZB
2P1B
2P2B
2P3B
2P4B
2P5B
2P6B
2P7B
2P8B
2P9B
Samples
Samples
Samples
Samples
Samples
Samples
Samples
Samples
Samples
Samples
NIPDAU
NIPDAU
NIPDAU
NIPDAU
NIPDAU
NIPDAU
NIPDAU
NIPDAU
NIPDAU
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
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19-May-2023
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 2
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